CN103872920A - Leakage inductance current slope direct control method of isolation type two-way three-level converter - Google Patents
Leakage inductance current slope direct control method of isolation type two-way three-level converter Download PDFInfo
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Abstract
The invention relates to a leakage inductance current slope direct control method based on an isolation type two-way three-level converter and belongs to the field of power electronics. Leakage inductance current is directly sampled at a high speed in real time to realize direct control on the leakage inductance current; even a transformer turn ratio error and circuit parasitic parameters exist, better control on leakage inductance current slope can also be realized; thus the current stress and current-circulation loss of a circuit are reduced. The low voltage side of a main circuit is formed by a current type half-bridge topology structure with an active clamping circuit; a high voltage side adopts a three-level half-bridge topology structure; a control strategy is that output voltage, input current and the leakage inductance current are sampled, operation is performed by a digital operation controller (DSP (digital signal processor)), a duty ratio and a phase shift angle are generated by a digital PI regulator, switching tubes of primary and secondary sides are controlled, the circuit power transmission direction and the leakage inductance current slope are directly controlled, and thus the less current stress and current-circulation loss and seamless switching of two-way operation of the circuit are realized.
Description
Technical field
Patent of the present invention provides a kind of leakage inductance electric current of isolated two-way three-level converter direct slope control method, belongs to the high frequency switch power direction of field of power electronics.
Background technology
For the isolated two-way three-level converter that is applied in high pressure occasion, low-pressure side adopts the current mode half-bridge topology with active clamp circuit, and high-pressure side adopts three level topologys.The current mode half-bridge topology with active clamp circuit of low-pressure side can be good at reducing the ripple of input current, improves the useful life of storage battery.High-pressure side adopts three level topologys, make the voltage stress of high-pressure side power device be kept to the half of high side voltage, thereby can select withstand voltage lower, on state resistance is less, switching frequency is higher MOSFET, thereby obtain larger power density and transmission efficiency.For reversible transducer, the loop current loss of the current stress that low-side switch equipment is too high and converter is the challenge that we face always, has greatly limited the efficiency of converter.At present, in order to reduce circulation loss, conventional control method mainly contains now: 1. phase shifting control method; 2. phase shift adds pulse width modulation controlled method.Method one: IEEETransactiononPowerElectronic[power electronics periodical] delivered the traditional phase shifting control method of employing in " AnewZVSbidirectionaldc – dcconverterfor fuelcellandbatteryapplication " [being applied to the bidirectional, dc DC converter of fuel cell and storage battery] in 2004, sampling and outputting voltage is controlled former secondary-side switch pipe as feedback, the flow direction of the leading and hysteresis power ratio control by phase shifting angle, realizes two-way unified control method.But, in the time that former secondary voltage does not mate, will cause electric current slope larger on transformer leakage inductance, cause current stress and circulation loss that device is larger.Method two: IEEETransactiononpowerelectronics[power electronics periodical] delivered " AZVSBidirectionalDC-DCConverterWith Phase-ShiftPlusPWMControlScheme " [a kind of two-way DC converter that adopts phase shift to add the zero voltage switch of pulse width modulation controlled] literary composition in 2008, by sampling low-pressure side clamp capacitor voltage and high-pressure side output voltage, regulate the duty ratio of low-side switch pipe, thereby realize the coupling of transformer primary secondary voltage, thereby reduce the slope of transformer leakage inductance electric current in power transfer stages, current stress and circulation loss are reduced, thereby power density and the efficiency of converter are improved.But, when existing error or circuit, the transformer turn ratio exists in the situation of parasitic parameter, and the slope of leakage inductance electric current can not be controlled accurately, thereby can not make the current stress of switching tube and circulation loss remain on optimum state.
Summary of the invention
The object of the invention is the deficiency in order to overcome above-mentioned prior art, a kind of direct slope control method of leakage inductance electric current that is applicable to isolated two-way three-level converter has been proposed, by to leakage inductance electric current high speed Direct Sampling in real time, realize the direct control of leakage inductance electric current.Even if there is transformer turn ratio error and circuit parasitic parameter, also can realize leakage inductance electric current slope and control preferably.Thereby current stress and the circulation loss of circuit are reduced.
The object of the invention is to be achieved through the following technical solutions.
A kind of direct slope control method of leakage inductance electric current of isolated two-way three-level converter, control method is based on isolated two-way three-level converter topology, main circuit low-pressure side is made up of the current mode half-bridge topology with active clamp circuit, and high-pressure side adopts tri-level half-bridge topology.
The direct slope control method of leakage inductance electric current of isolated two-way three-level converter comprises two control loops, pulse-width modulation (PWM) control ring and phase shifting control ring.Concrete control step is as follows:
Step 1: phase shifting control ring is by the voltage sensor high side voltage V that samples
2value as the Voltage Feedback of phase shifting control ring, calculating voltage set-point V
refwith V
2difference, this difference is as the input of Voltage loop pi regulator, the output of Voltage loop pi regulator is given as electric current loop.
Step 2: by the current sensor low-pressure side electric current I of sampling
invalue as the current feedback of phase shifting control ring, calculate electric current loop set-point and I
indifference as the input of electric current loop pi regulator, the output of electric current loop pi regulator is as the phase shifting angle Φ of secondary-side switch pipe carrier wave and reference carrier.
Step 3: generate reference carrier V by digital operation controller (DSP)
tr1, according to its databook, configuration switch frequency is 50kHz, initial phase is 0.Result from reference carrier phase simultaneously and differ from 180 °, the staggered carrier wave V that switching frequency is identical
tr2.
Step 4: it is Φ that the phase shifting angle Φ stack of the phase place of reference carrier and the output of phase shifting control ring obtains phase place, the carrier wave V of switching frequency identical with reference carrier (50kHz)
tr3.Set carrier wave V
tr3comparison value be V
tr3the half of peak value, i.e. V
tr3(peak)/ 2, thus the driving signal of secondary-side switch obtained, its duty ratio 0.5, the phase shifting angle of itself and former limit switching tube is Φ.
Step 5: in CPLD (CPLD), by driving signal S
1, S
2, Q
2athe same S of logical AND
3, S
4, Q
1athe result of logical AND is carried out exclusive disjunction, thereby obtains a logic control signal, input digital operation controller (DSP) start in each switch periods as DSP the to sample triggering signal of leakage inductance electric current.
When step 6: DSP receives control signal and becomes high level, start to carry out the sampling for the first time in a switch periods to leakage inductance electric current by current sensor and inner digital to analog converter (AD), be designated as i
lr1.
Step 7: complete for the first time after sampling, DSP carry out twentieth switch periods delay timing (under the switching frequency of 50kHz, be 1 μ s), afterwards leakage inductance electric current is sampled for the second time, be designated as i
lr2.
Step 8: pass through i
lr1deduct i
lr2as the pi regulator of leakage inductance electric current slope input PWM control ring, output is as carrier wave V
tr1and V
tr2comparison value, wherein with V
tr1the control signal relatively producing is as switching tube Q
1pWM drive signal, oppositely after as switching tube Q
1apWM drive signal; With V
tr2the control signal relatively producing is as switching tube Q
2pWM drive signal, oppositely after as switching tube Q
2apWM drive signal.
Step 9: after converter powers on, digitial controller produces the pwm signal of former secondary-side switch pipe according to the control method of setting, converter is started working: PWM control ring is by the current sensor transformer leakage inductance electric current of sampling, within the switch periods level time, calculate leakage inductance electric current slope, regulate the duty ratio of former limit switching tube according to step 5 to step 8, control transformer original edge voltage, realize former secondary voltage coupling, thereby making leakage inductance electric current slope is zero in power transfer stages, current stress and the circulation loss of circuit are effectively reduced, transformer efficiency density and efficiency are improved.
Step 10: when secondary voltage is lower than giving timing, former limit switching tube signal phase is ahead of secondary-side switch pipe, and converter is operated in (boost) pattern of boosting, and realizes the stable of secondary voltage.When secondary voltage is higher than giving timing, the outer shroud regulator saturation of phase shifting control, now former limit switching tube phase lag signal is in secondary-side switch pipe, and now transformer is operated in step-down (buck) pattern, realizes the constant-current source output of former limit.
The annexation of bidirectional three-level converter topology is as described below:
Low-pressure side input storage battery (V
1), its positive voltage side connects respectively inductance L
1and L
2one end; L
1the other end (being defined as a point) meet a switch mosfet pipe (Q
2a) source electrode and a switch mosfet pipe (Q
2) drain electrode; Switching tube Q
2adrain electrode meet 30 μ f clamp capacitor (C
d1) one end, the electric capacity other end and switching tube Q
2source electrode connect the negative voltage side of storage battery; Equally, L
2switch mosfet pipe (Q of another termination
1a) source electrode and a switch mosfet pipe (Q
1) drain electrode; Switching tube Q
1adrain electrode meet 30 μ f clamp capacitor (C
d2) one end, the electric capacity other end and switching tube Q
1source electrode connect the negative voltage side of storage battery; L
1the one end (a point) not joining with accumulator positive voltage side is connected leakage inductance (L
r) one end, L
ranother termination transformer primary side side one end (is defined as a
1point).L
2the one end (b point) not joining with accumulator positive voltage side connects the transformer primary avris other end and (is defined as b
1point).
Secondary high-pressure side, switching tube S
1, S
2, S
3, S
4series connection, i.e. S
1drain electrode connect the positive terminal of high-pressure side output, S
1source electrode and S
2drain electrode join, S
2source electrode and S
3drain electrode join (being defined as c point), S
3source electrode and S
4drain electrode join, S
4source electrode connect the negative voltage side of output.C point meets transformer secondary and a
1for one end of Same Name of Ends.The transformer secondary other end (being defined as d point) meets diode D
1anode and diode D
2negative electrode, D
1negative electrode meet clamp capacitor C
cone end and S
1source electrode, D
2anode meet clamp capacitor C
cthe other end and S
3source electrode.The C that just joins of high-pressure side output
3one end, another termination C
4one end and the d point of transformer, C
4the negative side of another termination output.
Described switching tube is the switching tube that has the parasitic capacitance of antiparallel body diode and the drain-source utmost point.
Beneficial effect
1, the direct slope control method of the leakage inductance electric current of isolated two-way three-level converter of the present invention, while there is error in the transformer turn ratio, because the present invention directly samples to leakage inductance electric current in the power transfer stages of a switch periods continuously by current sensor, calculate leakage inductance electric current slope, and regulate thus the duty ratio of former limit switching tube, thereby realize the coupling of former secondary voltage, can not be subject to the impact of transformer turn ratio error.
2, the direct slope control method of the leakage inductance electric current of isolated two-way three-level converter of the present invention, in circuit, there is on state resistance, while causing transformer primary side voltage magnitude to be less than clamp capacitor voltage, can carry out computing by Direct Sampling leakage inductance electric current slope equally and regulate former limit switching tube duty ratio compensation on state voltage to fall.
3, the direct slope control method of the leakage inductance electric current of isolated two-way three-level converter of the present invention, based on 1 and 2, by the direct control in power transfer stages to leakage inductance electric current slope, this invention is mated former secondary voltage under the not enough ideal situations of circuit, the current stress and the circulation loss that have effectively reduced circuit, improved transformer efficiency density and efficiency.
Brief description of the drawings
Fig. 1 is isolated two-way three-level converter;
Fig. 2 is the direct slope control method of leakage inductance electric current of the present invention schematic diagram;
Fig. 3 is the main oscillogram of the present invention.
Embodiment
Below in conjunction with drawings and Examples, the present invention is elaborated.
The present invention is the direct slope control method of a kind of leakage inductance electric current based on isolated two-way three-level converter.
For isolated two-way three-level converter, the topology of isolated two-way three-level converter, as shown in Figure 1, i
infor low-pressure side electric current, i
l1, i
l2be respectively input inductance L
1, L
2electric current, i
lrfor leakage inductance electric current, converter high-pressure side output voltage is V
2, transformer primary polygonal voltage is the voltage V between 2 of a, b
ab, transformer secondary voltage is the voltage V between 2 of c, d
cd.S
1, S
2, S
3, S
4, Q
1, Q
1a, Q
2, Q
2arepresent respectively the gate signal of corresponding switching tube.The direct slope control method of the leakage inductance electric current schematic diagram of isolated two-way three-level converter as shown in Figure 2.This control method is divided into pulse-width modulation (PWM) control ring and phase shifting control ring.
Institute's extracting method of the present invention and the circuit topology course of work thereof are as follows:
After converter powers on and starts working, for phase shifting control ring, when secondary voltage is lower, converter is operated in (boost) pattern of boosting.Digitial controller (DSP) TMS320F28335 is by sensor sample low-pressure side current i
inwith high side voltage V
2as feedback.V
reffor high side voltage given, by V
ref-V
2value through digital pi regulator and amplitude limiter, output valve is given as electric current loop, then by it low-pressure side current i with sampling
insubtract each other, the error amount digital pi regulator of process and amplitude limiter, as output regulated value, obtain phase shift phase place Φ through phase shift carrier controller.By by DSP according to the reference carrier V of converter switches frequency setting
tr1after superposition phase Φ, obtain carrier wave V
tr3.V
tr3(
peak) be carrier wave V
tr3peak value, steady state value V
tr3(peak)/ 2 with carrier wave V
tr3compare the pwm control signal of rear generation secondary-side switch pipe.Hence one can see that, and the duty ratio perseverance of secondary-side switch pipe is 0.5.
As high side voltage V
2be greater than set-point V
reftime, converter will be operated in step-down (buck) pattern.Now, V
ref-V
2be a negative value, by the integral action of digital pi regulator and the amplitude limit of amplitude limiter, its output valve becomes the minimum value of amplitude limiter, and given value of current is negative, thereby makes converter be operated in step-down (buck) pattern.Now, the output valve of electric current loop adjuster becomes negative equally.Obtaining phase shift phase place Φ through phase shift carrier controller is now negative value, i.e. its carrier wave V obtaining
tr3phase place is ahead of reference carrier V
tr1angle Φ.Thus, the pwm control signal of the secondary-side switch pipe of converter is ahead of former limit, makes power flow to low-pressure side by high-pressure side, thereby realizes the two-way switching of converter.
For PWM control ring, first to determine the sampling interval of leakage inductance electric current.The present invention, in CPLD (CPLD), passes through S
1, S
2, Q
2athe same S of logical AND
3, S
4, Q
1athe result of logical AND is carried out exclusive disjunction, thereby obtain a logical signal, the input signal that sets it as digital operation controller (DSP) checks, rising edge when it becomes high level is as the triggering signal of the leakage inductance electric current that starts to sample in a switch periods.As shown in Figure 3, in the time that digital operation controller (DSP) detects that triggering signal is high level, be now moment θ
7(or θ
15), digital operation controller (DSP) the leakage inductance current analog signal that current current sensor collection comes of sampling is converted to digital signal by inner AD, is denoted as i
lr1; Digital operation controller (DSP) inside arranges a constant time lag Δ θ simultaneously, and the concrete time is set as 1/20th of switch periods, when time delay finishes, i.e. and moment θ
7+ Δ θ (or θ
15+ Δ θ), digital operation controller (DSP) again gathers the leakage inductance electric current that current current sensor collection comes and is converted to digital signal, is denoted as i
lr2.
Then try to achieve i by digital operation controller (DSP)
lr1-i
lr2value, through design digital pi regulator and amplitude limiter digital operation controller (DSP) in, then by its output valve respectively with carrier wave V
tr1and V
tr2compare and draw low-side switch Q
1and Q
2pwm control signal.Wherein, carrier wave V
tr1and V
tr2180 ° of phase phasic differences, thus realize Q
1and Q
2staggered open-minded, reduced the pulsation of former limit input current, improved the life of storage battery.Q simultaneously
1aand Q
2arespectively with Q
1and Q
2complementary conducting, so, to Q
1and Q
2fetch logic is anti-, obtains low-side switch Q
1aand Q
2apwm control signal.
The concrete control signal change procedure of PWM control ring is as follows: work as i
lr2-i
lr1when >0, leakage inductance electric current slope be on the occasion of, voltage in leakage inductance reduce to one on the occasion of, now transformer primary polygonal voltage is higher than transformer secondary voltage, cause voltage not mate, now because being greater than, leakage inductance slope wishes to obtain and given 0, for transformer primary polygonal voltage and transformer secondary voltage are matched, adjuster output valve limit is little, the duty ratio of low-side switch reduces, transformer primary polygonal voltage is reduced, thereby transformer primary polygonal voltage and transformer secondary voltage are matched, leakage inductance electric current slope is reduced to 0 gradually.In like manner, work as i
lr2-i
lr1when <0, leakage inductance electric current slope is a negative value, now transformer primary polygonal voltage is lower than transformer secondary voltage, cause voltage not mate, at this moment adjuster will increase the duty ratio of low-side switch, transformer primary polygonal voltage is increased, thereby realize transformer primary polygonal voltage and transformer secondary voltage matches.By this control mode, even if the converter turn ratio exists error, by the direct control to leakage inductance electric current slope, can make i
lrslope by regulate duty ratio controlled well.
To sum up, this control method proposing by the present invention, can well realize the control of leakage inductance electric current slope, thereby has fundamentally reduced the circulation loss of low-side switch tube current stress and converter, improves efficiency and the power density of converter.Meanwhile, this control method can realize the seamless switching of bidirectional, dc DC converter, has good dynamic and steady-state behaviour.
Claims (2)
1. the direct slope control method of the leakage inductance electric current of an isolated two-way three-level converter, it is characterized in that: control method is based on isolated two-way three-level converter topology, main circuit low-pressure side is made up of the current mode half-bridge topology with active clamped circuit, and high-pressure side adopts tri-level half-bridge topology;
The direct slope control method of leakage inductance electric current of isolated two-way three-level converter comprises two control loops, pulse-width modulation (PWM) control ring and phase shifting control ring; Concrete control step is as follows:
Step 1: phase shifting control ring is by the voltage sensor high side voltage V that samples
2value as the Voltage Feedback of phase shifting control ring, calculating voltage set-point V
refwith V
2difference, this difference is as the input of Voltage loop pi regulator, the output of Voltage loop pi regulator is given as electric current loop;
Step 2: by the current sensor low-pressure side electric current I of sampling
invalue as the current feedback of phase shifting control ring, calculate electric current loop set-point and I
indifference as the input of electric current loop pi regulator, the output of electric current loop pi regulator is as the phase shifting angle Φ of secondary-side switch pipe carrier wave and reference carrier;
Step 3: generate reference carrier V by digital operation controller (DSP)
tr1, according to its databook, configuration switch frequency is 50kHz, initial phase is 0; Produce with reference carrier phase and differ from 180 °, the staggered carrier wave V that switching frequency is identical simultaneously
tr2;
Step 4: it is Φ that the phase shifting angle Φ stack of the phase place of reference carrier and the output of phase shifting control ring obtains phase place, the carrier wave V of switching frequency identical with reference carrier (50kHz)
tr3; Set carrier wave V
tr3comparison value be V
tr3the half of peak value, i.e. V
tr3(peak)/ 2, thus the driving signal of secondary-side switch obtained, its duty ratio 0.5, the phase shifting angle of itself and former limit switching tube is Φ;
Step 5: in CPLD (CPLD), by driving signal S
1, S
2, Q
2athe same S of logical AND
3, S
4, Q
1athe result of logical AND is carried out exclusive disjunction, thereby obtains a logic control signal, input digital operation controller (DSP) start in each switch periods as DSP the to sample triggering signal of leakage inductance electric current;
When step 6: DSP receives control signal and becomes high level, start to carry out the sampling for the first time in a switch periods to leakage inductance electric current by current sensor and inner digital to analog converter (AD), be designated as
iLr1;
Step 7: complete after sampling for the first time, DSP carries out the delay timing (being 1us under the switching frequency of 50khz) of twentieth switch periods, afterwards leakage inductance electric current is sampled for the second time, is designated as
iLr2;
Step 8: pass through i
lr1deduct i
lr2as the pi regulator of leakage inductance electric current slope input PWM control ring, output is as carrier wave V
tr1and V
tr2comparison value, wherein with V
tr1the control signal relatively producing is as switching tube Q
1pWM drive signal, oppositely after as switching tube Q
1apWM drive signal; With V
tr2the control signal relatively producing is as switching tube Q
2pWM drive signal, oppositely after as switching tube Q
2apWM drive signal;
Step 9: after converter powers on, digitial controller produces the pwm signal of former secondary-side switch pipe according to the control method of setting, converter is started working: PWM control ring is by the current sensor transformer leakage inductance electric current of sampling, within the switch periods level time, calculate leakage inductance electric current slope, regulate the duty ratio of former limit switching tube according to step 5 to step 8, control transformer original edge voltage, realize former secondary voltage coupling, thereby making leakage inductance electric current slope is zero in power transfer stages, current stress and the circulation loss of circuit are effectively reduced, transformer efficiency density and efficiency are improved,
Step 10: when secondary voltage is lower than giving timing, former limit switching tube signal phase is ahead of secondary-side switch pipe, and converter is operated in (boost) pattern of boosting, and realizes the stable of secondary voltage; When secondary voltage is higher than giving timing, the outer shroud regulator saturation of phase shifting control, now former limit switching tube phase lag signal is in secondary-side switch pipe, and now transformer is operated in step-down (buck) pattern, realizes the constant-current source output of former limit.
2. the direct slope control method of the leakage inductance electric current of a kind of isolated two-way three-level converter as claimed in claim 1, is characterized in that: the annexation of described bidirectional three-level converter topology is as follows:
Low-pressure side input storage battery (V
1), its positive voltage side connects respectively inductance L
1and L
2one end; L
1the other end (being defined as a point) meet a switch mosfet pipe (Q
2a) source electrode and a switch mosfet pipe (Q
2) drain electrode; Switching tube Q
2adrain electrode meet 30uf clamp capacitor (C
d1) one end, the electric capacity other end and switching tube Q
2source electrode connect the negative voltage side of storage battery; Equally, L
2switch mosfet pipe (Q of another termination
1a) source electrode and a switch mosfet pipe (Q
1) drain electrode; Switching tube Q
1adrain electrode meet 30uf clamp capacitor (C
d2) one end, the electric capacity other end and switching tube Q
1source electrode connect the negative voltage side of storage battery; L
1the one end (a point) not joining with accumulator positive voltage side is connected leakage inductance (L
r) one end, L
ranother termination transformer primary side side one end (is defined as a
1point); L
2the one end (b point) not joining with accumulator positive voltage side connects the transformer primary avris other end and (is defined as b
1point);
Secondary high-pressure side, switching tube S
1, S
2, S
3, S
4series connection, i.e. S
1drain electrode connect the positive terminal of high-pressure side output, S
1source electrode and S
2drain electrode join, S
2source electrode and S
3drain electrode join (being defined as c point), S
3source electrode and S
4drain electrode join, S
4source electrode connect the negative voltage side of output; C point meets transformer secondary and a
1for one end of Same Name of Ends; The transformer secondary other end (being defined as d point) meets diode D
1anode and diode D
2negative electrode, D
1negative electrode meet clamp capacitor C
cone end and S
1source electrode, D
2anode meet clamp capacitor C
cthe other end and S
3source electrode; The C that just joins of high-pressure side output
3one end, another termination C
4one end and the d point of transformer, C
4the negative side of another termination output.
Described switching tube is the switching tube that has the parasitic capacitance of antiparallel body diode and the drain-source utmost point.
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