CN103687186A - Circuit and method for driving LEDs - Google Patents

Circuit and method for driving LEDs Download PDF

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Publication number
CN103687186A
CN103687186A CN201310403618.8A CN201310403618A CN103687186A CN 103687186 A CN103687186 A CN 103687186A CN 201310403618 A CN201310403618 A CN 201310403618A CN 103687186 A CN103687186 A CN 103687186A
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signal
circuit
load current
led
level
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CN103687186B (en
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贝恩德·普夫老姆
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Infineon Technologies Austria AG
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/375—Switched mode power supply [SMPS] using buck topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/39—Circuits containing inverter bridges

Abstract

The invention discloses a circuit and a method for driving LEDs. The circuit for driving light emitting diodes includes a first semiconductor switch that is responsive to a driver signal and a freewheeling device coupled between a first supply terminal that provides a supply voltage and a second supply terminal that provides a reference potential. An LED and an inductor are coupled in series between a common circuit node of the first semiconductor switch and the freewheeling device and either the first supply terminal or the second supply terminal. A current measurement circuit is coupled to the LED and provides a load current signal that represents a load current passing through the at least one LED. A first feedback circuit includes an on-off controller that receives load current signal and a reference signal, compares the load current signal with the reference signal and generates the driver signal dependent on the comparison. A modulator provides duty cycle with expectation and modulating signals of amplitude, the duty cycle being used as reference signals.

Description

Circuit and method for driving LED
Technical field
The present invention relates to for driving circuit and the method for light-emitting diode (LED).Particularly, relate to for driving value that load current is adjusted to expect to keep circuit and the method for LED of the perceived brightness of gained.
Background technology
In recent years, there is the light-emitting diode as variable light source.The light-emitting diode that is also referred to as solid-state lighting device or abbreviation LED is efficient, durable and long persistent lighting device.Since nineteen sixty, first LED came into the market, this technology has obtained huge development.LED is the industrial standard in various specific illumination market at present, and welcome lamp enters rapidly general lighting market.For example, LED lamp is than incandescent lamp, halogen bulb with fluorescent lamp efficiency is higher and persistence is longer.Normally four times to five times of incandescent lamp and there is the useful life that surpasses several ten thousand hours of the efficiencies that the development of technology makes LED.
LED is the device of current drives, and the brightness of LED and its mean forward current (also referred to as its average load current) are proportional.For this reason, conventionally with providing the current source of constant current to carry out driving LED.Constant current source has been eliminated the load current that the variation by the forward voltage of LED causes and has been changed, and therefore guarantees constant LED brightness.In known LED driver (being conventionally implemented as the dc-dc converter such as step-down controller, boost converter or type of voltage step-up/down converter), integrated a plurality of parts are assessed voltage and these voltages are compared with reference voltage.Power semiconductor switch is (for example,, MOSFET) conventionally according to this result conducting and disconnection relatively, so that inductor is charged or electric discharge.
The application notices AN874 " Buck Configuration High-Power LED Driver " Microchip Technology, and 2006 have described the switching power circuit of controlling the load current that is supplied to LED.Yet, need to carry out the measurement of LED electric current and activator switch (for example, due to propagation delay) with the time delay that inductor is charged or discharge between, surpassed the maximum of the expectation of LED electric current.This just causes the average load current of expectation and is supplied to the mismatch between the actual average load current of LED, thereby causes the less desirable enhancing of brightness of LED.
Although can consider this mismatch in circuit design, yet, be supplied to the average load current of LED and therefore LED brightness itself by the difference of the forward voltage because of LED (it becomes with temperature) and because of the difference of the LED number that is connected in series and be applied to LED and the difference of the supply voltage of LED driver difference.; even common LED driver-when being designed to current source-for example, because the above-mentioned delay cycle of mentioning can not keep average load current constant (, when supply voltage or LED forward voltage change or because the different inductance value of inductor) conventionally.Therefore, for various situation, need to reconfigure LED driver.
Need a kind of economic single effectively solution to guarantee for different supply voltages or different LED forward voltages the brightness that (almost) is constant, and without reconfiguring circuit.
Summary of the invention
Described for driving the circuit of light-emitting diode (LED).According to an example of the present invention, this circuit comprises the first semiconductor switch and current following device, is coupled in series in and the first power end of supply voltage is provided and provides between the second source end of reference potential, and wherein, the first semiconductor switch is in response to driving signal.At least one LED and inductor are in series coupled between the common circuit node and the first power end or second source end of the first semiconductor switch and current following device.Current measurement circuit is coupled to LED and provides expression to flow through the load current signal of the load current of at least one LED.The first feedback circuit comprises on-off controller, and described on-off controller receives load current signal and reference signal, load current signal compared with reference signal and relatively produce driving signal according to this.Modulator is provided as the modulation signal with expectation duty ratio and peak value of reference signal.In addition, the second feedback circuit receives load current signal, determines average load current signal and according to average load current signal and reference value adjustment, is supplied to the peak value of the modulation reference signals of the first feedback circuit.
According to another example of the present invention, this circuit comprises the first semiconductor switch and the current following device being in series coupled between the second source end that the first power end of supply voltage is provided and reference potential is provided, and wherein, the first semiconductor switch is in response to driving signal.At least one LED and inductor are in series coupled between the common circuit node and the first power end or second source end of the first semiconductor switch and current following device.Current measurement circuit is coupled to LED and the load current signal that represents to flow through at least one LED is provided.The first feedback circuit comprises on-off controller, and described on-off controller receives load current signal and reference signal, load current signal compared with reference signal and relatively produce driving signal according to this.Modulator is provided as the modulation signal with expectation duty ratio and peak value of reference signal.In addition, be provided with the second feedback circuit.The second feedback circuit comprises filter and adjuster.Filter receives load current signal and the filtering signal that represents average load current is provided.Adjuster receives this filtering signal and as the reference value that point value is set, the difference according to predetermined control law based between reference value and filtering signal is determined control signal, and according to the amplitude of the reference signal of control signal adjustment modulation.
In addition described for driving the LED driver of at least one LED.LED driver is at driver output end and provide respectively between supply voltage and reference potential the first power end or second source end coupled in series to inductor.According to an example of the present invention, LED drives and comprises the first semiconductor switch and the current following device being in series coupled between the second source end that the first power end of supply voltage is provided and reference potential is provided.The first semiconductor switch is in response to driving signal.In addition, the common circuit node of the first semiconductor switch and current following device is connected to output.LED drives and further comprises that current measurement circuit, described current measurement circuit are coupled to LED and provide expression to flow through the load current signal of the load current of at least one LED.Modulator is provided as the modulation signal with expectation duty ratio and amplitude of reference signal.
The first feedback circuit comprises on-off controller, and described on-off controller receives load current signal and reference signal, load current signal is compared with reference signal and relatively produce driving signal according to this.In addition, be provided with the second feedback circuit.The second feedback circuit comprises filter and adjuster.Filter receives load current signal and the filtering signal that represents average load current is provided.Accept filter signal and as the reference value of point value is set of adjuster, the difference according to predetermined control law based between reference value and filtering signal is determined control signal, and according to control signal, adjusts the amplitude of modulation reference signals.
Still further described for driving the method for at least one LED.This at least one LED is at output and provide respectively between the first power end of supply voltage and reference potential or second source end coupled in series to inductor.According to an example of the present invention, the method comprises: measure the load current that flows through at least one LED, produce thus the load current signal that represents load current; According to driving signal alternately supply voltage or reference potential to be applied to output, load current signal is compared with reference signal and relatively produce driving signal according to this; From load current signal, determine average load current signal; Generation has the on/off modulating input signal that disconnects level, conduction level and duty ratio; The signal of adjusting the conduction level of input signal and adjustment being provided according to average load current signal and reference value is as with reference to signal.
Accompanying drawing explanation
With reference to the following drawings and description, can understand better the present invention.Parts in accompanying drawing need not be drawn in proportion, but are to emphasize illustrating basic principle of the present invention.In addition, in the accompanying drawings, identical reference number represents corresponding parts.In the accompanying drawings:
Fig. 1 shows the LED drive circuit in buck topology;
Fig. 2 shows the current characteristics in the circuit of Fig. 1;
Fig. 3 shows the LED current control circuit in buck configuration;
Fig. 4 shows LED current characteristics in the circuit of Fig. 3 and the on off state of switch;
Fig. 5 a, Fig. 5 b and Fig. 5 c show three different examples of LED drive circuit.
Fig. 6 shows another exemplary L ED drive circuit with improved upper electrical properties;
Fig. 7 shows another exemplary L ED drive circuit of the example that is similar to Fig. 6;
Fig. 8 illustrates in greater detail the LED drive circuit of Fig. 5 c;
Fig. 9 shows an example of the controller being used in LED drive circuit described herein;
Figure 10 shows the function of the example of Fig. 8 by the sequential chart of coherent signal; And
Figure 11 shows an illustrative embodiments of the modulator of the example for describing in this article.
Embodiment
In following specific descriptions, with reference to the accompanying drawing that forms the part of this explanation, wherein by illustrating, how to implement instantiation of the present invention and illustrate.Given this, with reference to the orientation of described accompanying drawing, use the directional terminology such as " top ", " bottom ", " front ", " back side ", 'fornt', 'back' etc.Because the assembly of illustrative embodiments can be positioned in a plurality of different directions, therefore directional terminology is for the object illustrating and unrestricted.Should be understood that, within not departing from scope of the present invention, can adopt other example and make change in structure or in logic.Therefore, following detailed description does not have restrictive, sense, and is defined by the following claims scope of the present invention.Should be understood that, unless clearly represented really not soly, otherwise the characteristic of the various illustrative embodiments of describing in this article can combine mutually.
Fig. 1 shows the LED driver that comprises step-down controller (buck converter).In this drive circuit, switch S 1be coupled in voltage V is provided iNthe first power end and inductor L 1first end between.Diode D 1be coupled in switch S 1with inductor L 1common circuit node and provide between the second source end of reference potential GND.Diode D 1thereby positive pole be connected to second source end.Output capacitor C 1be coupled in inductor L 1the second end and provide between reference potential GND second source end.Load as the series circuit (also referred to as " LED chain ") of LED or several LED is coupled to capacitor C in parallel 1.
Step-down controller is by high power supply voltage V iNconvert the voltage regulator of low output voltage to.This can be by inductor/capacitor (LC) network between Switching power voltage rapidly and ground connection, thereby makes alternately by supply voltage V iNor reference potential (ground connection) GND is applied to LC network and realizes.Work as switch S 1when closed, inductor L 1be connected to input voltage V iN, lc circuit is in its " charged state ", and the inductive current I increasing lfrom the first power end, (applied input voltage V iN) by inductor L 1transfer to by output capacitor C 1parallel circuits with LED formation.
As charging current I lthrough inductor L 1while flowing to LED, charging current I lportion of energy as magnetic field, be stored in inductor L 1in.Work as switch S 1while being disconnected by (again), circuit enters its " discharge condition " and inductor L 1field decay, although electric current continues to flow to LED.As inductive current I lwhile dropping to zero, switch S 1closure and charge/discharge cycle restart again.The result of this switching circulation is inductive current I lin the process medium dip of whole circulation, rise and decline, as shown in Figure 2.
Capacitor C in LC network 1be used for inductive current I llevel and smooth for flowing to the DC electric current of LED.As inductive current I lbe greater than load current I lEDtime, by inductive current I lload current I is provided lEDand any residual current I call flow into capacitor C 1thereby to its charging.In Fig. 2, this is illustrating the condenser current I changing along with the time csequential chart in as stage B, illustrate.As inductive current I lwhile dropping to required following of load current, by capacitor C 1electric current I coppositely and condenser current I caugment inductive current I lto make up inductive current I lwith required load current I lEDbetween difference.In Fig. 2, this is illustrating capacitance current I csequential chart in as stage A, illustrate.
Feedback circuit is implemented to regulate output current (that is, the load current i that is offered load by dc-dc converter conventionally lED).Such feedback circuit is to load current I lEDmonitor and it is compared with stable benchmark.Based on this result relatively, the duty ratio of the regulation of electrical circuit handover operation is to compensate any deviation.Any variation of the load voltage that feedback circuit compensation is produced by assembly or sequential tolerance, and it adjusts duty ratio with compensation input voltage V iNvariation, thereby by load current I lEDremain on its expectation level.
A kind of Switching power design concept is at continuous and discontinuous inductive current I lbetween the design distinguished.Be commonly called " discontinuous current pattern " (be called for short: in operator scheme DCM), as mentioned above, inductive current I lwhen each discharge cycle finishes, drop to zero and within the limited time period, remain zero.Yet, be commonly called " continuous current mode " (be called for short: in another operator scheme CCM), inductive current I ldo not drop to zero.But, inductor L 1in whole switch periods, remain DC current component.
The inductive current I of gained lthe existing AC component of its waveform has again DC component.DC component equals to switch the average current L of cycle period aVGand by reference voltage V dRIVEdetermine.AC component is for being superimposed upon DC component I aVGon triangular waveform and by the switching of drive circuit (that is, dc-dc converter), caused.The advantage of CCM operation is inductive current I lflow to continuously output, thereby reduce capacitor C 1the requirement of charging storage.
Drive circuit shown in Fig. 3 has utilized with the inductive current I in the dc-dc converter of CCM operation ldC component I aVG.Switching transistor T 1, inductor L 2, LED(its also can be regarded as representing LED chain) and current measurement resistance device R 2(shunt resistor) is in series coupled in provides power supply potential V bATTthe first power end with for example provide reference potential GND(, ground connection) second source end between.Transistor T 1load current path (for example, the in the situation that of MOSFET, drain-source current path) be coupled in power supply potential V bATTthe first power end and inductor L 2between.Inductor L 2be coupled in transistor T 1load current path and LED between.The positive pole of LED is coupled to inductance L 2.Current measurement resistance device R 2be coupled between the negative pole of LED and the second source end of reference potential GND.
Can be the diode D of Schottky diode 2be coupled in transistor T 1with inductor L 2common circuit node and second source (GND) between.It should be noted diode D 2be operating as fly-wheel diode and can use transistor seconds (for example, MOSFET) to replace.In this case, two transistors can form transistor half-bridge.Resistor R 1be coupled in LED and current measurement resistance device R 2common circuit node and first (non-return) input of comparator 1 between.Another capacitor C 2be coupled in comparator 1 and resistor R 1common circuit node and second source end (GND) between.The output of comparator 1 is coupled to transistor T 1control end (that is, the gate terminal in MOSFET situation).At its second (anti-phase) input terminal place, comparator 1 receives reference voltage V dRIVE.
When the circuit of analysis chart 3, can find out capacitor C 2with resistor R 1formed RC low pass filter.This filter receives and inductive current i in its input lproportional voltage signal i lr 2(that is, current measurement resistance device R 2and be provided as the voltage V of output signal the pressure drop at two ends), aVG, this voltage V aVGrepresent average inductor current i aVG.Therefore comparator 1 is in fact that the signal that represents average inductor current is compared with corresponding reference signal.Comparator 1 has hysteresis.That is, comparator 1 triggers transistor T when average inductor current rises to higher than the first threshold values 1disconnect, and average inductor current drop to lower than be less than the first threshold values the second threshold values time trigger transistor T 1conducting.In this, comparator 1 is as bang bang controller (bang-bang controller) (on-off controller).
Except feedback circuit (comprises resistor R 1, capacitor C 2, comparator 1) and current measurement resistance device R 2outside, the circuit of Fig. 3 is with the example shown in Fig. 1 is basic identical before.Yet, in the example of Fig. 3, do not need output capacitor C 1(see figure 1).Therefore step-down controller circuit shown in Fig. 3 has similar charge/discharge cycle to the step-down controller of Fig. 1.By turn-on transistor T 1start the charged state of switching circulation (switching cycle).This just causes from power end (V bATT) flow through transistor T 1, inductor L 2, LED and shunt resistor R 2electric current increase.As capacitor C 2the voltage at two ends (it represents average inductor current) surpasses the reference voltage V that is supplied to comparator 1 dRIVEtime, comparator 1 disconnects transistor T 1, so the discharge condition of start-up circuit.
Under discharge condition, electric current flows through sustained diode 2, inductor L 2with resistor R 2.Inductive current I ltilt to decline until capacitor C 2voltage on two ends (expression average inductor current) drops to reference voltage V dRIVEbelow.Thereby, transistor T 1the next circulation of conducting and beginning again.Flow through the electric current I of the gained of LED and inductor lEDthe DC level I of little triangle AC " pulsation " the electric current stack of synchronizeing with charge/discharge cycle aVG.Fig. 4 shows this situation.At its mean value I aVGnear electric current I lEDaC component for all known switch regulators (switching regulator), share.For the circuit that comprises the dimmed ability of LED, reference voltage V dRIVEit can be on/off modulation DC voltage.For example, can use the duty ratio of the reference voltage of pulse-width modulation and modulation to represent darkness level value.For example, 50% duty ratio reduces half brightness of high-high brightness, and high-high brightness is corresponding to 100% duty ratio.
Fig. 4 shows the load current I that flows through LED lEDthe transistor T of (it equals inductive current) and gained 1switching state.Although be provided with, regulate average load current I aVGfeedback circuit, for different supply voltage V bATTwith different inductor L 2inductance and different LED forward voltages, this load current I lEDstill different.This is mainly the result postponing, and this delay is at comparator output signal and transistor T 1the transformation of actual handover operation between the passage of (for example,, from low level to high level, vice versa) time.Between this time delay, there is the instantaneous of inductive current and overflow.That is its when, the peak level of the AC component of inductive current is zero higher than delay is worth originally.The voltage that is applied to inductor is higher, and overflowing of given delay time is just higher.Similarly, induction coefficient is lower, and overflowing of given time delay is just higher.Because for activating and disable transistor T 1delay time unequal, higher for the peak value of inductive current, overflow higher, result, the mean value of inductive current is for different inductor value and different supply voltage V bATTdifferent.The average inductor current changing can be perceived as the variation brightness of LED.That is, the brightness of LED is depended on supply voltage in less desirable mode.The feedback circuit of the LED drive circuit of Fig. 3 can not compensate this effect, and therefore, supply voltage V bATTvariation bear corresponding brightness and change.When LED light modulation is activated, (by applying the reference voltage of modulation, see Fig. 3) equally, in the conduction period of reference voltage, occurred identical problem.
Fig. 5 shows some exemplary circuit that can compensate above-mentioned less desirable effect.Fig. 5 a shows and keeps LED electric current I lEDmean value I aVGconstant or reduce at least significantly by supply voltage V bATTthe first exemplary circuit of changing of the brightness that produces of variation.In the context of this example, " mean value " is regarded as appearing at (modulation) reference signal S rEFthe short term average of conduction period.That is, LED electric current I lEDshort-term averaging I aVGbe in the conduction period of reference signal, to flow through the average current of LED, and according to the duty ratio of reference signal, can reduce significantly the long-term average of LED electric current.
The circuit of Fig. 5 a is similar to the circuit of Fig. 3.Yet semiconductor switch 6 is low-end switch (low-side switch), and in the example of Fig. 3 transistor T 1high-end switch (high-side switch).In this example, low-end switch 6 is connected in series to inductor L 2represent single led or comprise the LED chain of the LED of any right quantity with LED().Switch 6, LED and inductor L 2series circuit be coupled in supply voltage V be provided bATTfirst power end of (for example, the cell voltage of Vehicular battery) with in reference potential GND(for example, ground connection) second source end between.Inductor L 2interchangeable with the order of LED.Current measurement circuit 3 can be coupled to series circuit (by switch 6, LED and inductor L 2form), thus current measurement circuit can be measured be supplied to the load current i of LED lED.In this configuration, load current i lEDwith inductive current i lequate.Current measurement circuit 3 produces and represents load current i lload current signal S iL.In the art, many suitable current measurement circuits are known and with reference to Fig. 5 c, an exemplary current measurement circuit are described subsequently.By by suitable driving signal S oUTbe applied to the corresponding control signal of switch 6 with conducting and disconnection semiconductor switch 6.If MOSFET is used as semiconductor switch, drive signal S oUTcan be grid current or the grid voltage that is enough to activate (conducting) or forbidding (disconnection) switch 6.
By comparator 2, produce and drive signal (being similar to the example of Fig. 3), wherein, load current signal S iLwith reference signal S rEFbe provided for comparator 2, reference signal S rEFaccording to the darkness level S of expectation dIMthe on/off modulation signal being produced by modulator 9.Comparator 2 has hysteresis, and works as S rEF-S iLdifference produce the output signal S of high level while surpassing first threshold oUT(for activator switch 6).Similarly, work as S rEF-S iLdifference drop to Second Threshold when following, this comparator 2 produces low-level output signal S oUT(for disabled switch 6).Two threshold values conventionally equate in size, but have contrary symbol.(there is no above-mentioned any propagation delay) in ideal conditions, actual loading electric current I lEDat average On current I aVGnear variation, this average On current I aVGcorresponding to the reference signal S when reference signal non-zero the conduction period of reference signal (that is) rEF.The peak-to-peak amplitude that the AC component of stack (also referred to as " pulsating current ") has triangular waveform substantially and depends on the hysteresis of comparator 2.As mentioned above, drive signal S oUTthe corresponding handover operation of conversion and switch 6 between delay can cause system mistake, thereby produce actual average load current I aVG=I rEFthe overgauge Δ I of+Δ I, wherein, I rEFcorresponding to reference signal S rEF" ideal " average load current, and deviation delta I depends on supply voltage V bATT.Conventionally, comparator 2 is first feedback circuit CL 1a part, wherein, comparator 2 has been implemented in fact on-off controller (also referred to as bang bang controller) with regulating load current i l.Reference signal is the first feedback circuit CL 1the reference input (set-point value) of on-off controller.
Modulator 9 is according to the darkness level S of expectation dIMproduce on/off modulation reference signals S rEF.For example, can use pulse-width modulation (PWM).Yet pulse frequency modulated (PFM) and pulse density modulated (PDM also claims that ∑-Δ is for modulation), random on/off modulation and other modulation schemes are also applicable.According to the darkness level S of expectation dIM(it can be such as digital number or analog signal), modulator 9 is set the duty ratio (conventionally representing with percentage) of modulation.In context, for example, 40% duty ratio refers to that the time of reference signal average 60% for example, in (disconnecting level, the in the situation that of voltage signal, be 0V) and time of average 40% in conduction level (peak level, for example, 5V), wherein, conduction period and off period replace.Switch 6 is at reference signal S rEFeach off period disconnect, and switch 6 (drives signal S in whole conduction period of reference signal according to comparator output signal oUT) alternately conducting and disconnection.Therefore, average On current I aVGcorresponding to reference signal S rEFconduction level.It should be noted in the discussion above that reference signal S rEFturn-on cycle and break period conventionally in 0.1 to several milliseconds (for example, the PWM with 10000kHz or larger carrier frequency) in scope, and in conduction period, the handover operation of switch 6 has for example, cycle period in the scope (, the switching frequency to as high as the scope of several MHz from 100kHz) in several microseconds.
For compensating the negative effect of above-mentioned time delay, be provided with the second feedback circuit CL 2(control loop).This second feedback circuit receives the load current signal S as input signal iLand adjust for the first feedback circuit CL 1(modulated) reference signal S rEFamplitude (that is, peak level).According to by the second feedback circuit CL 2the control law of implementing, reference signal S rEFrepresent average load current value I aVGand the difference between preset steady state value.An illustrative embodiments of the second feedback circuit is discussed with reference to Fig. 5 c subsequently.
The second feedback circuit CL 2operation and effect thereof can be summarized as follows: at reference signal S rEFconduction period, as load current i lEDthe average I of reality (short-term) aVGin response to supply voltage V bATTvariation and while changing (due to the negative effect of above-mentioned time delay), the second feedback loop CL 2the modulation reference signals S that is used for the first feedback circuit by adjustment rEFthe conduction level (peak level) of (that is, point value being set) is offset average load current I aVGthis variation.When average load current is in response to cumulative supply voltage V bATTand while starting to increase, the second feedback circuit CL 2reduce and be supplied to the first feedback circuit CL 1reference signal S rEFthe turn-on level of (that is, point value being set), thereby the supply voltage V that compensation raises bATTimpact.For the same reason, for different inductor L 2inductance value and different LED forward voltages, the brightness of LED is not constant.
The circuit of describing in the example of Fig. 5 b and Fig. 5 a is almost identical.Unique difference is that power semiconductor switch 6 is high-side switch rather than low side switch (as shown in Figure 5 a).In this case, can complete current measurement at downside.Sustained diode 3be coupled in inductor L 2be not coupled to as the power supply potential V in Fig. 5 a with common circuit node and the reference potential GND(of switch 6 bATT) between.The operation of the LED drive circuit of Fig. 5 b is identical with the operation of the LED drive circuit of Fig. 5 a.
Fig. 5 c shows substantially in the identical LED drive circuit shown in Fig. 5 a.Yet, illustrate in greater detail the second feedback circuit CL 2with current measurement circuit 3.Example before being similar to, low side switch 6 is connected to inductor L 2and LED, this LED can be replaced by LED chain.Switch 6, LED and inductor L 2series circuit be coupled in the first power end (supply voltage V bATT) and second source end (for example, ground connection GND) between.Inductor L 2interchangeable with the order of LED.Current measurement circuit 3 comprises the shunt resistor R that is in series coupled to LED 3thereby, make load current i lEDsame through shunt resistor and shunt resistor R 3on pressure drop R 3i lEDwith load current I lED(or inductive current I l=I lED) be proportional.Shunt resistor R 3on pressure drop R 3i lEDcan be supplied to amplifier AMP, this amplifier AMP amplifies described pressure drop and produces expression load current i lcorresponding load current signal S iL.Amplifier AMP can be such as simple differential amplifier, operational amplifier, trsanscondutance amplifier or any other suitable amplifying circuit.Current signal S iLcan be voltage signal, alternatively, be the current signal that depends on actual enforcement.By by suitable driving signal S oUTthe corresponding control signal (for example, the signal when using MOSFET as power semiconductor switch) that is applied to switch 6 goes up and conducting and disconnection semiconductor switch 6.
The first feedback circuit receives the load current signal S as input signal iLand modulation reference signals S rEF, the conduction level of modulation reference signals (that is, peak level or amplitude) can be regarded as the point value that arranges for the on-off controller by above-mentioned comparator 2 enforcements.Comparator 2 receives reference signal S rEFwith load current signal S iLand produce the output signal S for driving power semiconductor switch 6 oUT, as illustrated with reference to Fig. 5 a.The first feedback circuit CL 1the example of operation and Fig. 5 a in identical, therefore here no longer repeat.Load current i lEDwaveform and the handover operation of switch 6 corresponding to reference signal S rEFsequential chart shown in (, whole conduction period) Fig. 4 during conducting.
For at supply voltage V bATTwhen (or forward voltage that depends on temperature of LED) changes by load current I lEDactual (short-term) average I aVGmaintain constant level, the second feedback circuit CL 2regulate reference signal S rEFthereby conduction level regulate for the first feedback circuit CL 1point value is set.As mentioned above, by the second feedback circuit CL 2the control law of implementing has been guaranteed according to average load current value I aVGfor example, with preset steady state value (, burning voltage V sTAB) between difference adjust reference signal S rEFconduction level.For this reason, the second feedback circuit CL 2comprise filter 4 circuit, these filter 4 circuit receive the load current signal S as input signal iLand what be provided as output signal can be regarded as expression (for example, mobile) average load current I aVGthe filtering signal V of signal aVG.For example, filter can be the passive RC filter consisting of resistor and capacitor.Alternatively, can carry out digitlization load current signal S with any suitable analog-digital converter iL.In this case, filter 4 may be implemented as the digital filter that uses digital processing unit and suitable software.Use suitable programmable signal processor, not only can implement filter 4 in digitlization ground, can also implement whole the second feedback circuit CL in digitlization ground 2(the first feedback circuit CL even 1part).In this case, the entity that is called as circuit herein can be regarded as the functional unit of implement software.
By filter output signal V aVG(represent average load current I aVG) and stable reference value (for example, the register value of stable reference voltage or digital execution mode) be supplied to adjuster 5.In simple example, adjuster 5 can be P controller.Yet adjuster 5 can also be PI controller, PID controller or PT1 controller etc.Conventionally, controller 5 can be configured to minimize or at least reduce average load current (by signal V aVGrepresent) and reference value V sTABbetween any side-play amount V sTAB-V aVG.Having the stable state that can realize offset of zero such as the adjuster of the I parts of PI controller controls.
Adjuster 5 can comprise operational amplifier 51.According to the type (P, PI, PIC, PTI etc.) of the adjuster 5 using, need different assemblies that adjuster 5 is set.For example, the in the situation that of PT1 controller, operational amplifier 51 receives reference value V at its inverting input sTAB.The first resistor R 11with the second resistor R 12and the parallel circuits of capacitor C4 is coupled in series between the inverting input and output of operational amplifier 51.Fig. 9 shows the example of such adjuster 5.In some illustrative embodiments, it is favourable using PT1 controller.Yet, in other examples, can use the controller 5 of other types.In this case, need to implement corresponding controller type at other assemblies of difference configuration.
Can and change side-play amount V in the interior amplification of adjuster 5 sTAB-V aVG, and regulator output signal can directly offer modulator circuit 9.Modulator circuit 9 can comprise level adjusting circuit 7, the on/off modulation signal of described level adjusting circuit 7 receiver regulator output signals and predetermined amplitude and described modulation signal is carried out to level adjustment according to regulator output signal.The modulation signal that level is adjusted is as with reference to signal S rEFoffer the first feedback circuit CL 1.Circuit 7 can be configured to change reference signal S rEFamplitude (conduction level), it is for the first feedback circuit CL 1(that is, at reference signal S rEFthe on-off controller 2 of conduction period) point value is set.Circuit 7 can be carried out a kind of level shift simply.After the example of circuit 7 will be discussed.
Fig. 6 shows for being independent of supply voltage V bATTby average load current I aVGremain on expectation level another exemplary circuit.This circuit is generally corresponding to the circuit shown in Fig. 5 a and Fig. 5 c.Yet, show in more detail filter 4(average circuit).Filter 4 for example can comprise by resistor R 5with capacitor C 3the passive single order RC low pass filter forming, other filter types (for example, higher order filter, digital filter) are equally also applicable.
For avoiding the less desirable transient effect in moving (after circuit is powered on) process, can use initializing circuit 8 by the filter output of filter 4 be set as in or close to by stable reference value V sTABthe initial value of given desired value.In simple (thereby very worthwhile and be applicable to low-cost application program) execution mode of implementing in the example of Fig. 6, the capacitor C that initializing circuit 8 is exported being connected to filter rapidly immediately LED drive circuit powers on after 3carry out precharge.This can pass through via semiconductor switch T 2temporarily by stable reference voltage V sTABbeing connected to capacitor realizes.Switch T 2for example, predetermined (, fixing) closed in the time period.Use the closure of timer circuit 81 controllable switch and reopen, for example, timer circuit 81 can be in response to the timer circuit (for example, monostable flipflop) that power on signal produces the pulse of predetermined length.
In the example of describing at Fig. 6, semiconductor switch T 2the first end of (for example, MOSFET or BJT) is via another resistor R 6(optionally) is connected to resistor R 3with capacitor C 3between common circuit node.Semiconductor switch T 2the second end be coupled to stable voltage V be provided sTABvoltage source.Yet, can also use any other magnitude of voltage as initial value, for example, V sTAB90%.Switch T 2control inputs (in the situation that of MOSFET, be grid; The in the situation that of BJT, be base terminal) be connected to above-mentioned timer circuit 81.If timer units is implemented as monostable flipflop, it remains on capacitor C by the voltage with predetermined 3place's regular hour, thus filter is exported to the initial value that is initialized to expectation.For example, time delay unit 81 is triggered by power-on reset signal.Once system powers on, this power-on reset signal is exactly available.
The example of Fig. 6 before example shown in Fig. 7 is very similar to.Difference is only, the enforcement of timer circuit 81.In this example, timer circuit 81 is also in response to driving signal S oUTthis drives signal S oUTtriggering power semiconductor switch 6 activates and forbidding.In this example, timer circuit reinitializes (for example,, by activator switch T in response to the conducting triggering of power semiconductor switch 6 2regular time section), but only have, disconnect predetermined time when switch 6.That is, in the conduction period of reference signal SREF switch " normally " handover operation process of 6, can not trigger and reinitialize, and only switch 6 by its disconnection opening time, section finished time trigger and reinitialize.That is, for example,, when the handover operation of power semiconductor switch 6 interrupts (, for light modulation object) predetermined shortest time temporarily, when the normal handover operation of switch 6 recovers, triggered and reinitialized.
The LED drive circuit of describing in Fig. 6 and Fig. 7 is configured the capacitor C of filter 4 3on voltage, thereby filter output signal V aVGvalue clamp down on as corresponding to stable reference value V sTABvalue.Conventionally, for drives LED such function not necessarily, yet, in circuit start and light modulation operating process, be useful, in the meantime for example, according to predetermined modulation scheme (, pulse-width modulation, the modulation of ∑-Δ etc.) by repeatedly conducting of load current and disconnection.
The example of Fig. 8 shows the LED driver circuit of the circuit that is similar to Fig. 5 c.Yet this example comprises in addition to using the more detailed description of the exemplary level adjusting circuit in modulator 9.
As in example before, filter 4 can be to comprise resistor R 5with capacitor C 3passive RC filter.Adjuster 5 for example can comprise operational amplifier 51(, sees Fig. 5 c).
In this example, the class of operation of level adjusting circuit 7 is similar to level shifter.It comprises transistor T 3.Transistor T 3be coupled to the output of adjuster 5.Transistor T 3load current path be connected to reference potential GND and resistor R 9between.Another resistor R 10be coupled in resistor R 9with positive potential V sterminal between.Be supplied to the reference signal S of the first feedback circuit rEFat two resistor R 9and R 10between common circuit Nodes by tap.Just as already mentioned, level adjusting circuit 7 is according to predetermined characteristic curve, by the reference signal S being produced by adjuster 5 rEF' (that is, control signal) carry out level shift, in this example, predetermined characteristic curve depends on transistor T 3with resistor R 10characteristic with resistor R9.Level adjusting circuit 7 shown in this example can be regarded as controlled voltage divider, and this can control voltage divider by input voltage V s(it is provided by the on/off modulator 91 in this example) is divided into part voltage V s(R 9+ R oN)/(R 9+ R 10+ R oN), wherein, R oNit is transistor T 3conducting resistance, and therefore reference voltage S rEF' function by adjuster 5, provide and be provided for transistorized control end (that is, the in the situation that of MOSFET, being, gate terminal).The centre tap of voltage divider provides " level adjustment " reference signal S rEFthe output circuit node of level adjusting circuit 7, this is the control signal S being provided by adjuster 5 rEF' bijective function of (that is, one to one corresponding).This function depends on characteristic curve and resistor R 9with R 10resistance value.
Conventionally, the control signal S that the function being provided by circuit 7 is provided by adjuster 7 according to characteristic curve adjustment rEF' level.Controlled voltage divider shown in Figure 10 is regarded as a simple example.Those skilled in the art use difference channel (for example, amplifier circuit etc.) will realize without difficulty identical or similar function.In digital execution mode, characteristic curve can be by being stored in parameter in memory or being limited by the interpolation method of question blank.Yet for application cheaply, digital solutions can be too complicated and expensive.
According to the duty ratio (conventionally representing with percentage) of expectation, by on/off, modulate the input voltage V that is supplied to level adjusting circuit 7 scan easily implement dimming capability.For example, 30% duty ratio needs reference signal S rEFaverage disconnection (for example, at earthing potential place, 0V) 70% time.For this reason, provide and be used for generating input signal V into level adjusting circuit smodulator 8.The modulation of any class is all applicable, such as pulse-width modulation, pulse frequency modulated, ∑-Δ modulation (also referred to as pulse density modulated), various Stochastic Modulation schemes etc.It should be noted, the mode that can be different from the example shown in Fig. 7 realizes reference signal S rEFmodulation.Those skilled in the art use different circuit to realize without difficulty identical or similar functions.For example, can use according to input signal V sconstant modulation signal (for example, being provided by modulator 8) is activated and will receives reference signal S with the switch of forbidding rEFcomparator input be connected to earthing potential.
It should be noted in the discussion above that the filter initialization shown in the example of Fig. 7 can be effectively applied to this example.For example, compare with the switching frequency (, in hundreds of kilohertz range) of power semiconductor switch 6, the modulating frequency of modulator 9 is less (for example,, lower than 10 kilo hertzs) conventionally.That is, when light modulation is activated, opening time, section can be long, thereby, the average load current signal V being provided by filter 4 aVGdecline.Yet the value of paying close attention to being provided by filter is the average load current during the conducting phase of load current.For fear of transient effect, such as what see in the power turn-on phase process at circuit, at switch 6, " long " time period () is initially the average load current signal level V close to expectation while being switched to conducting afterwards being disconnected at every turn for filter output aVGvalue, each switch 6 after disconnecting " longer " period connection (that is, as reference signal S rEFwhile not having modulated device 9 to eliminate (blank), be longer than the opening time during " normally " handover operation).For this reason, initialization unit 81(is shown in Fig. 7) ignore to appear at and drive signal S oUTin rising edge, unless its low one period of given minimum opening time.Can be selected as being applicable to the time constant of filter 4 this shortest opening time.
Figure 10 shows the waveform of the modulator output signal of 50% exemplary duty ratio (on/off modulator 91), corresponding load current signal S iL, average load current signal V aVGand offer the first feedback circuit CL 1the reference signal V of gained rEF.As mentioned above, switch modulator 91 produces on/off modulation signals, and described on/off modulation signal is in this example for 0V or 2.5V and have and depend on and offer modulator as the darkness level S of input signal dIMduty ratio.At the top of Figure 10, there is shown corresponding waveform.Second illustrates by current measurement circuit 3 and provides and be supplied to average circuit 4(filter 4, also can be referring to Fig. 7) corresponding load current signal S iL.Can see at modulator output signal V sconducting phase during, the high frequency handover operation of power switch 6 (being about in this example 400KHz switching frequency).The 3rd timing diagram shows the average load current signal V of gained aVG, described average load current signal V aVGcan observe in the filter output that comprises the filter circuit 4 of above-mentioned initialization ability.At modulator output V sdisconnected phase during, filter output signal is clamped down on into the value of mean value close to expectation.This clamps down on the stabilization time (time of staying, settle time) of greatly having reduced filter circuit 4.The bottom diagram of Figure 10 shows the reference signal V of gained rEF.As mentioned above, reference signal V rEFconduction level by the second feedback circuit CL 2regulate.
Figure 11 shows pwm generator, and it can be in conjunction with above-mentioned example as on/off modulator 9 or 91.In known LED driver, can change the reference voltage that is supplied to comparator 2 and (for example, see Fig. 5 a) so that LED electric current I lEDweaken.Yet, the common inaccuracy of this method and depend on temperature.
PWM modulator circuit shown in Figure 11 comprises saw-toothed wave generator S twith comparator C OMP 2.This saw-toothed wave generator S tcomprise the first current mirror CM 1, the second current mirror CM 2and comparator C OMP 1.Capacitor C 5be coupled in comparator C OMP 1non-inverting input and output between.In addition capacitor C, 5be coupled to the first current mirror CM 1thereby, make with constant current i 1to capacitor charging, this constant current i 1with the constant input current i of current mirror 0proportional (i in this example, 1=i 0/ 10).Transistor T 4be coupled in comparator C OMP 1the input of noninverting comparator and the terminal of reference potential GND between.Transistor T 4control end (for example, grid) be coupled to comparator C OMP 1output.Therefore, capacitor C 5comparator output switching during to high level via transistor T 4electric discharge.
Resistor R 13be coupled in the second current mirror CM 2and between the terminal of reference potential GND.Comparator C OMP 1inverting input be connected to current mirror CM 2with resistor R 13common circuit node.Another resistor R 14with another transistor T 5series circuit and resistor R 13coupled in parallel.Transistor T 5according to comparator C OMP 1comparator output signal and conducting and disconnection.At transistor T 5while being disconnected, by the second current mirror CM 2the constant current i providing 2(i in this example, 2=i 03) flow through resistor R 13thereby, at resistor R 13upper generation pressure drop V 2=i 2r 13.Therefore, (linear rising) voltage V on capacitor 1reach threshold voltage V 2time, comparator C OMP 1from low level, switch to high level.Comparator C OMP 1non-inverting input provide corresponding to capacitor C 5on voltage V 1the output signal (sawtooth signal) of saw-toothed wave generator.
The analog voltage that outside provides is by this second comparator C OMP 2be transformed into corresponding PWM-signal V s.Constant current i 0by the first current mirror CM 1be transformed into current i 1.For example, it can be high-end pMOS current mirror.For example, reference current i 0can be 10 μ A.If use the current mirror of 1:10, i 1current value be about 1 μ A.The second current mirror CM 2produce the second current i 2.For example, the second current mirror CM 2generation is than constant current i 0senior Three current i doubly 2(i 2=30 μ A).Then, this current i 2flow through resistor R 13thereby on resistor, produce voltage V 2.
As comparator C OMP 1comparator export when low, transistor T 4, T 5both all not conductings (disconnection).Capacitor C 5interior by current i during this 1charging.Work as capacitor C 5the voltage V at two ends 1surpass voltage V 2time, comparator C OMP 1become and activate and by two transistor Ts 4, T 5switch to conducting.Because transistor T 5contact resistance R 14and and resistance R 13parallel connection, transistor T 4by capacitor C 5be discharged to V suddenly 2(V 2=i 2r 13r 14(R 13+ R 14)) value.Because capacitor C 5have to via transistor T 4electric discharge, therefore voltage V 2than voltage V 1what decline is faster.Opening time can be by transistor T 4length-width ratio limit.
As condenser voltage V 1drop to voltage V 2when following, comparator C OMP 1output signal be back to low level and transistor T 4, T 5again become non-conductive.As a result, at comparator C OMP 1inverting input voltage V is provided again 2=i 2r 13, and capacitor C 5again start charging.
In this circuit, by resistor R 13can capping threshold values and by resistor R 14(coupled in parallel is to resistor R 13) setting lower limit threshold values.
Another comparator C OMP 2at the output voltage of first input end reception saw-toothed wave generator ST and by itself and the reference voltage V that is supplied to the second input dIMcompare.When saw-tooth voltage reaches reference voltage V dIMtime, comparator output switching.The duty ratio of pwm signal and reference voltage V dIMproportional.
Although described illustrative embodiments and advantage thereof in detail, yet, should be understood that, within not departing from the spirit of the present invention and scope being defined by the following claims, can make various changes, replacement and distortion.The scope of noting above-mentioned distortion and application, should be understood that, the present invention is also neither subject to foregoing description restriction not limited by accompanying drawing.But the present invention is only subject to the restriction of following claim and legal equivalents thereof.
For convenience of description to illustrate that an elements relative is in the location of the second element, used such as " in ... below ", " ... under ", " bottom ", " ... on ", the space relative terms such as " top ".These terms are intended to comprise the different location of the device these location of describing in being different from accompanying drawing.In addition, term such as " first ", " second " etc. are not intended to restriction yet for describing various elements, region, part etc.Identical term refers to identical element in whole description.
As used in this article, term " has ", " containing (containing) ", " comprising (including) " and " comprising (comprising) " etc. mean the open term of the existence of described element or characteristic, but do not get rid of other element or characteristic.Singulative " one (a) ", " one (an) " and " described (the) " are intended to also comprise plural form, unless that context clearly represents is really not so.

Claims (14)

1. for driving a circuit for light-emitting diode, described circuit comprises:
The first semiconductor switch and current following device in response to driving signal, be coupled in and the first power end of supply voltage be provided and provide between the second source end of reference potential;
LED and inductor, be coupled in series between the common circuit node and described the first power end or described second source end of described the first semiconductor switch and described current following device;
Current measurement circuit, is coupled to described LED and is configured to provide expression to flow through the load current signal of the load current of described LED;
The first feedback circuit, comprises on-off controller, and described on-off controller is configured to receive described load current signal and reference signal, so that described load current signal is compared with described reference signal, thereby relatively produces described driving signal according to described;
Modulator, is configured to be provided as the duty ratio with expectation of reference signal and the modulation signal of amplitude; And
The second feedback circuit, is configured to receive described load current signal to determine average load current signal, and according to the amplitude of the reference signal of the difference adjustment modulation between described average load current signal and reference value.
2. circuit according to claim 1, wherein, described the second feedback circuit comprises:
Filter, is coupled to and receives described load current signal and the filtering signal that represents described average load current is provided; And
Adjuster, be configured to receive described filtering signal and as the described reference value that point value is set, with according to predetermined control law the difference based between described reference value and described filtering signal determine control signal, and the described amplitude of the reference signal of modulating according to described control signal adjustment.
3. circuit according to claim 2, wherein, described modulator comprises level adjusting circuit, described level adjusting circuit is configured to receive described control signal from described adjuster, according to described control signal, on/off modulating input signal is carried out to level adjustment, thereby provide described reference signal.
4. circuit according to claim 3, wherein, described level adjusting circuit comprises amplifier.
5. circuit according to claim 3, wherein, described level adjusting circuit comprises the voltage divider with controlled voltage ratio, described voltage divider is configured to receive on/off modulation input voltage and using a part for described input voltage as offer described the first feedback circuit with reference to signal, described controlled voltage ratio is in response to the described control signal being provided by described adjuster.
6. circuit according to claim 3, wherein, described input signal is modulated between zero level and the peak level corresponding to described signal amplitude, wherein, described in be modulated to a kind of in following: pulse-width modulation, pulse frequency modulated, the modulation of ∑-Δ or random on/off modulation.
7. circuit according to claim 3, wherein, described modulator is coupled to the modulation signal that provides darkness level and be provided as the input signal of described level adjusting circuit, and described modulation signal has zero level or according to the predetermined peak level of the duty ratio corresponding to described darkness level.
8. circuit according to claim 2, wherein, described the second feedback circuit further comprises initializing circuit, described initializing circuit be configured in response in following event at least one by the output of described filter be initialized as in or close to the initial value of described reference value: the powering on of described circuit; After the disabled predetermined minimum time of described the first semiconductor switch, activate described the first semiconductor switch; Or be converted to conduction period from the off period of modulated reference signal.
9. circuit according to claim 8,
Wherein, described initializing circuit comprises timing circuit and another switch that is coupled to described filter; And
Wherein, described switch by timing unit, activated predetermined time the output of described filter is connected to during section have in or close to the initial voltage of the voltage level of described reference value, thereby described filtering signal is initialized as to described voltage level.
10. the LED driver for driving LED, described LED between driver output end and the first power end or second source end with inductor coupled in series, described the first power end carrying supply voltage and described second source end carrying reference potential, described LED driver comprises:
The first semiconductor switch and current following device, be coupled between described the first power end and described second source end, described the first semiconductor switch is in response to driving signal, and the common circuit node between described the first semiconductor switch and described current following device is connected to described output;
Current measurement circuit, is coupled to described LED, and described current measurement circuit is configured to provide expression to flow through the load current signal of the load current of described LED;
Modulator, is configured to be provided as the duty ratio with expectation of reference signal and the modulation signal of amplitude;
The first feedback circuit, comprises on-off controller, and described on-off controller is configured to receive load current signal and described reference signal, so that described load current signal is compared with described reference signal, thereby relatively produces described driving signal according to described;
The second feedback circuit, comprises filter and adjuster,
Wherein, described filter is coupled to and receives described load current signal and the filtering signal that represents average load current is provided; And
Wherein, described adjuster is configured to receive described filtering signal and as the reference value that point value is set, with according to predetermined control law the difference based between described reference value and described filtering signal determine control signal, and according to described control signal, adjust the described amplitude of described reference signal.
11. 1 kinds of methods for driving LED, coupled in series is to inductor between output and the first power end or second source end for described LED, and described the first power end carrying supply voltage and described second source end carry reference potential, and described method comprises:
The load current of described LED is flow through in measurement;
Produce the load current signal that represents described load current;
According to driving signal alternately described supply voltage or described reference potential to be applied to described output;
Described load current signal is compared with reference signal;
According to described, relatively produce described driving signal;
From described load current signal, determine average load current signal;
Generation has the on/off modulating input signal that disconnects level, conduction level and duty ratio; And
According to the described conduction level of input signal described in described average load current signal and reference value adjustments and provide regulated signal as with reference to signal.
12. methods according to claim 11, wherein, determine that described average load current signal comprises:
To described load current signal filtering; And
Be provided as the filtering signal of average load current signal.
13. methods according to claim 12, wherein, determine described average load current signal further comprise in response in following event at least one by described filtering signal be initialized as in or close to the signal value of described reference value: the detection of power on signal or described reference potential be applied to described output be longer than predetermined minimum time after described supply voltage be applied to the detection of described output.
14. methods according to claim 12, wherein, produce described reference signal and comprise:
Determine the difference between described filtering signal and described reference value;
According to predetermined control law, based on described difference, produce control signal; And
Adjust the level of described input signal so that described reference signal to be provided.
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