CN103532392A - Controller for a power converter and method of operating the same - Google Patents
Controller for a power converter and method of operating the same Download PDFInfo
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- CN103532392A CN103532392A CN201310278566.6A CN201310278566A CN103532392A CN 103532392 A CN103532392 A CN 103532392A CN 201310278566 A CN201310278566 A CN 201310278566A CN 103532392 A CN103532392 A CN 103532392A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0025—Arrangements for modifying reference values, feedback values or error values in the control loop of a converter
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0032—Control circuits allowing low power mode operation, e.g. in standby mode
- H02M1/0035—Control circuits allowing low power mode operation, e.g. in standby mode using burst mode control
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
- H02M1/007—Plural converter units in cascade
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33571—Half-bridge at primary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Each embodiment of the invention generally relates to a controller for a power converter and a method for operating the same. Concretely, a controller for a power converter and method of operating the same are provided. In one embodiment, the controller includes an inductor-inductor-capacitor ('LLC') controller configured to receive an error signal from an error amplifier to control a switching frequency of an LLC stage of the power converter to regulate an output voltage thereof. The controller also includes a power factor correction ('PFC') controller configured to control a bus voltage produced by a PFC stage of the power converter and provided to the LLC stage so that an average switching frequency thereof is substantially maintained at a desired switching frequency.
Description
Technical field
Present invention relates in general to power electronic device, and relate in particular to a kind of for the controller of power converter and the method operating on it.
Background technology
Switched mode power converter (being also known as " power converter " or " adjuster ") is that input voltage waveform is converted to power supply or the Power Processing circuit of specifying output voltage or current waveform.Power factor correction (PFC)/resonant inductor-Inductor-Capacitor (LLC) power converter comprises the power train of the PFC level with heel LLC level.This power converter is coupled to electric power source (exchanging (ac) power supply) and direct current (dc) output voltage is provided.PFC level (from ac power supply) receives the rectified version of ac input voltage and dc busbar voltage is provided.LLC level adopts busbar voltage to provide dc output voltage to load.The power converter that comprises PFC level and LLC level can be used to build " ac adapter " so that dc output voltage to be provided from ac power supply to notebook etc.
The controller being associated with power converter manages the operation of power converter by controlling the turn-on cycle of the power switch that wherein adopted.Conventionally, controller is coupling between the input and output of power converter with feedback loop structure (being also known as " control loop " or " closed control loop ").Often two kinds of control procedures of employing are controlled the output voltage of the power converter of the PFC level formation that utilizes heel LLC level.A kind of busbar voltage of process control PFC level is so that output voltage is controlled, and another kind of process is controlled the switching frequency of LLC level output voltage is controlled.As will be more apparent, adopt two kinds of self-contained process to carry out control and can cause impairing the operation of this power converter and some design problems of efficiency thering is the output voltage of the power converter of PFC level and LLC level.
Detection and the operation about another domain of interest of power converter, normally under underloading condition, it carried out.Under such condition, for power converter, it can be favourable entering burst operation pattern.With regard to burst operation pattern, the power loss of power converter depends on the gate drive signal of power switch and conventionally substantially not with other continuation power loss of load variations.These power losses are generally by being used burst operation pattern to be solved at low-down power level, wherein within a period of time (for example, one second) make controller invalid, the high power operation (for example, 10 milliseconds (ms)) that is subsequently the short time has low-loss harmonic(-)mean power output to provide.Controller can adopt output (or load) power of the time interval estimating power transducer of burst operation pattern as described herein.
Therefore, this area needs a kind of controller, and it is attached to mixed method for adopt the control procedure of power converter of different capacity level to avoid defect of the prior art in its power train.In addition, this area needs a kind of controller, and it can detect and manage the power converter in underloading situation, comprises that power converter enters the operation of burst operation pattern, to avoid defect of the prior art.
Summary of the invention
Technical advantage is achieved by useful embodiment of the present invention generally, and it comprises a kind of for the controller of power converter and the method operating on it.In one embodiment, this controller comprises inductor-Inductor-Capacitor (LLC) controller, and it is configured to receive error signal from error amplifier and with the switching frequency of the LLC level of power ratio control transducer, the output voltage of power converter is adjusted.This controller also comprises power factor correction (PFC) controller, and it is configured to PFC level by power converter to produce and provide to the busbar voltage of LLC level control so that the average frequency of switching of LLC level is maintained at the switching frequency of expectation substantially.
On the other hand, a kind of burst mode controller for power converter comprises that burst mode initiates circuit, and it is configured to initiate burst operation pattern when the signal of output voltage that represents power converter is crossing with the first burst threshold level.This burst mode controller also comprises voltage lifting circuit, its be configured at time window in the situation that represent the signal of output voltage of power converter and the second burst threshold level intersect before the expired voltage that provides promote signal with boosted output voltages.
Below quite broadly feature of the present invention and technical advantage are summarized, so that can be better, detailed description of the present invention be subsequently understood.Below will be described supplementary features of the present invention and advantage, they have formed the theme of the claims in the present invention.Those skilled in the art should be realized, disclosed concept and specific embodiment can easily be used as revising or designing other structure or process to implement the basis of identical object of the present invention.Those skilled in the art should also realize that, such equivalent constructions does not deviate from as the spirit and scope of the present invention given in claims.
Accompanying drawing explanation
In order to understand more all sidedly the present invention, with reference now to the description of carrying out below in conjunction with accompanying drawing, wherein:
Fig. 1 illustrates the block diagram of the embodiment of the power converter that comprises controller that principle according to the present invention constructs;
Fig. 2 illustrates the schematic diagram of a part for the power converter that comprises the exemplary power system that adopts Boost topology that principle according to the present invention constructs;
Fig. 3 illustrates the circuit diagram of the embodiment of the power converter that PFC level that utilization that principle according to the present invention constructs is coupled to LLC level forms;
Fig. 4-Fig. 6 illustrates according to the diagrammatic representation of the exemplary operation characteristic of the power converter of principle of the present invention;
Fig. 7 and Fig. 8 illustrate the diagram of the embodiment of the power converter that PFC level that utilization that principle according to the present invention constructs is coupled to LLC level forms;
Fig. 9 illustrates the schematic diagram according to the embodiment that is configured to burst mode controller that the burst operation pattern of power converter is managed of principle of the present invention;
Figure 10 illustrates the diagrammatic representation in the example waveform according to producing in the power converter of principle of the present invention;
Figure 11 illustrates the diagram of embodiment of the resitstance voltage divider of the output voltage that is coupled to power converter that principle according to the present invention constructs; And
Figure 12 illustrates in the voltage lifting circuit that principle according to the present invention constructs the diagram for generation of the embodiment of the part of slope signal, the slope of the output voltage of the power converter that this slope signal indication can adopt in burst mode controller.
Unless otherwise noted, in different diagrams, corresponding numbers and symbols is often referred to corresponding part of generation, and may after the first example, no longer be described for simple and clear object.Accompanying drawing is drawn to be illustrated for the related fields to exemplary embodiment.
Embodiment
Below the manufacture of this exemplary embodiment and use are discussed in detail.Yet, should be realized, the invention provides the many applicable inventive concept that can be embodied in various specific environments.The specific embodiment of discussing is only the explanation of manufacturing and use concrete mode of the present invention, and scope of the present invention is not limited.
Present invention is described to put up with the exemplary embodiment of the concrete context controller of power converter (that is, for).Although the environment of the controller for power factor correction (PFC)/resonant inductor-Inductor-Capacitor (LLC) power converter is described principle of the present invention, any application that can benefit from the controller such as power amplifier or electric machine controller is equally within broad range of the present invention.
First with reference to figure 1, it illustrates the block diagram of the embodiment of the power converter that comprises controller 110 that principle according to the present invention constructs.Power converter is coupled to by the represented ac main line of the ac power supply that input voltage vin is provided.This power converter comprises the power train (power train) 105 of being controlled by controller 110.Controller 110 is measured the operating characteristic such as its output voltage V out of power converter conventionally, and the duty ratio D that controls power switch wherein in response to measured operating characteristic is to adjust this characteristic.Power train 105 can comprise that a plurality of power stages are to provide output voltage V out or other output characteristic through adjusting to load.The power train 105 of power converter comprises and is coupled to magnetic apparatus so that a plurality of power switchs of power transfer function to be provided.
Turn to now Fig. 2, it illustrates the schematic diagram of a part for the power converter that comprises the exemplary power system (for example, PFC level 201) that adopts Boost topology (for example, PFC voltage-boosting stage) that principle according to the present invention constructs.The PFC level 210 of power converter is for example inputted reception, from the input voltage vin (, unadjusted ac input voltage) of the electric power source such as ac main line and DC busbar voltage (being also the known as busbar voltage) Vbus through adjusting is provided at it.Conform to the principle of Boost topology, this busbar voltage Vbus usually above input voltage vin so that its switching manipulation can adjust busbar voltage Vbus.Make main line power switch S
1(for example, n NMOS N-channel MOS N (NMOS) " active " switch) can and be coupled to boost inductor L by input voltage vin by bridge rectifier 203 by the main interval of gate drive signal GD conducting
boost.During the main interval D of switch periods, inductor current i
inincrease and pass through boost inductor L
boostflow to local circuit earth terminal.Boost inductor L
boostconventionally the efficiency of utilizing single layer winding to form to reduce closing effect and improving power converter.
The duty ratio of PFC level 201 depends on that according to following equation input voltage knows the ratio of busbar voltage (being respectively Vin, Vbus) under stable state:
During complementary interval 1-D, master power switch S
1be converted to nonconducting state and auxiliary power switch (for example, diode D1) conducting.In interchangeable circuit arrangement, auxiliary power switch can comprise the second active switch, and it is controlled by complementary gate drive signal conducting.Auxiliary power switch D1 provides a kind of maintenance to flow through boost inductor L
boostinductor current i
insuccessional approach.During complementary interval 1-D, flow through boost inductor L
boostinductor current i
inreduce, and can vanishing, and remaining zero in a period of time, this causes " discontinuous conduction mode " of operation.
During complementary interval 1-D, flow through boost inductor L
boostinductor current i
inby diode D1 (that is, auxiliary power switch), flow into filtering capacitor C.Conventionally, master power switch S
1duty ratio (and complementary duty cycle of auxiliary power switch D1) can be conditioned to keep the adjustment of the busbar voltage Vbus of PFC level 201.Understood by one of ordinary skill in the art, by using " damper (snubber) " circuit element (not shown) or passing through control circuit sequential, master power switch S
1can separate to avoid cross-conduction electric current therebetween by the little time interval with the turn-on cycle of auxiliary power switch D1, and advantageously reduce the switching losses being associated with power converter.Be used for avoiding master power switch S
1and the circuit of the cross-conduction electric current between auxiliary power switch D1 and control technology are being known in the art and for concise and to the point and will it be described further.Boost inductor L
boostconventionally utilize single layer winding to form to reduce the power loss being associated with closing effect.
Turn to now Fig. 3, the utilization that illustrates constructed according to principles of the present invention is coupled to the circuit diagram of the embodiment of the power converter that the PFC level (such as the PFC level 201 of Fig. 2) of LLC level 320 (for example, semibridge system LLC isolation resonance buck stages) forms.PFC level 201 and LLC level 320 for example can be used to structure " ac adapter ", so that dc output voltage V out (, 19.5 volts) to be provided from ac main supply (being represented by input voltage vin) to notebook.
As the above mentioned, often adopt two kinds of control procedures to control to utilize the output voltage V out of the PFC level 201 formed power converters of heel LLC level 320.A kind of busbar voltage Vbus of process control PFC level 201 and output voltage V out is controlled, another kind of process is controlled the switching frequency (being also named as switching frequency fs) of LLC level 320 and output voltage V out is controlled.The busbar voltage Vbus being produced by PFC level 201 in the responsive feedback loop compared with slow in response to be coupled to LLC level 320 output load and be controlled.LLC level 320 operates with fixed switching frequency fs, and this switching frequency fs is selected to increase its power conversion efficiency.LLC level 320 is utilized the continued operation by the busbar voltage Vbus of PFC level 201 generations in desirable transformer state, and this PFC level 320 is controlled to the IR in LLC level 320 (electric current is multiplied by resistance) to decline and compensate.Conventionally, the magnitude that is changed to tens of volts of the busbar voltage Vbus being produced by PFC level 201.
Use switching frequency to control LLC level 320, PFC level 201 produces constant dc busbar voltage Vbus, but 320 of LLC levels utilize switching frequency to operate, this switching frequency in response to be coupled to power converter output load variation and utilize fast-response control loop (that is the control loop, with high crossover frequency) to control.The switching frequency that changes LLC level 320 makes LLC level 320 operate with the switching frequency of poor efficiency conventionally.
A kind of mixing control method is provided, and the busbar voltage Vbus wherein being produced by PFC level 201 utilizes and controls to process average load power compared with slow-response control loop (that is the control loop, with low crossover frequency).Utilize quick responsive feedback loop to control to process to the switching frequency of LLC level 320 event that load transient and ac main signal exit (dropout).Control PFC level 201 so that output voltage V out is controlled and caused some design problems.First, busbar voltage Vbus is conventionally because low PFC control loop crossover frequency shows very poor transient response.Secondly, on to the busbar voltage Vbus of LLC level 320 power supplies, there is the ripple voltage (for example, the ripple voltage of 100-120 hertz) appearing in a large number on its output.
As described here, the switching frequency of LLC level 320 utilizes fast-response control loop to control to decay conventionally to appear at the impact of the ripple voltage being produced by PFC level 201 in the output of LLC level 320.In addition, in the frequency field of the transformer/stage gain of LLC level 320 between 1/ (2 π sqrt ((Lm+Lk) Cr)) and 1/ (2 π sqrt (LkCr)), by fast-response control loop, adopted to adapt to the event that the signal of large load step change and ac main line input voltage vin exits.The busbar voltage Vbus of PFC level 201 in response to the slow variation of load, be controlled to make LLC level 320 can be ideally with its resonance frequency or near operation unceasingly, its power conversion efficiency is generally best at this point.By make LLC level 320 most of times its resonance frequency or near operate, but allow switching frequency to change in response to transition, the load stride response that can be improved, the ripple of the output voltage V out reducing and higher power conversion efficiency.
The primary inductance of transformer T1 is that leakage inductance Lk adds magnetizing inductance Lm, and it is reference that two inductance all be take the armature winding of transformer T1.Resonant capacitor is Cr.Resonant capacitor Cr can be divided into two capacitors that are coupling in serial circuit, and one end of this serial circuit is coupled to the earth terminal other end and is coupled to busbar voltage Vbus.Serial circuit is arranged and can be used to reduce the inrush current while starting.The perfect switch frequency of fs is fo=1/ (2 π sqrt (Lkcr)), and this is efficient operation point (for example, 50 kilo hertzs (kHz)) under normal circumstances.The low switching frequency that starts poor efficiency capacitance switch at it is fmin=1/ (2 π sqrt (LpCr)).Conventionally expectation operates to be greater than the switching frequency of minimal switching frequency fmin, and even avoids approaching the switching frequency of minimal switching frequency fmin.
As shown in Figure 3, input voltage vin is coupled to Electromagnetic interference filter (EMI) 310, and its output is coupled to bridge rectifier 203 to produce commutating voltage Vrect.PFC level 201 produces busbar voltage Vbus, and its input that is coupled to LLC level 320 is to produce output voltage V out, and this output voltage V out carries out filtering by the output filter capacitor Cout of power converter.In alternative embodiment, can utilize full-bridge type topology to form LLC level 320.Utilize error amplifier 340 sensing output voltage V out, this error amplifier 340 is coupled to the resitstance voltage divider that utilizes the first resistor Rsensel and the second resistor Rsense2 to form.Output signal from error amplifier 340 is coupled to optical coupler 350, and it produces output voltage error signal (being also known as " error signal ") δ V.Output voltage error signal δ V and busbar voltage Vbus are coupled to pfc controller 330 and/or the LLC controller 333 (following just Fig. 7 is below being described in more detail) of controller 325.325 couples of busbar voltage Vbus that produced by PFC level 201 of controller and the switching frequency fs of LLC level 320 jointly control that output voltage V out is adjusted, and switching frequency fs (most of time) are remained on to the efficient operation point of LLC level 320 simultaneously.
In operation, the zero load that is coupled to the load of output voltage V out for example can make busbar voltage Vbus from 370 volts, drop to 290 volts due to the low crossover frequency inherently of controller 325 to the step change of fully loaded (zero-to-full).By utilizing fast-response control loop that the switching frequency fs of LLC level 320 is down to 25kHz from 50kHz, can for 1.3 to 1 or the voltage gain that increases of higher LLC level 320 can be used to the decline of busbar voltage Vbus to carry out substance compensation.Along with busbar voltage Vbus returns to about 390 volts, with the IR in LLC level 320, decline and compensate, its switching frequency fs is back to 50kHz.
Same principle can be applied to keeping (holdup) event when ac rail voltage (input voltage vin) signal exits.At busbar voltage Vbus, drop in 280 volts from 390 volts, the dump energy being stored in the filtering capacitor C of PFC level 201 can be used to keep the adjustment to output voltage V out.Equally, the voltage gain that depends on frequency of LLC level 320 is used to the output voltage V out of power converter to adjust in response to fast-response control loop.The response of LLC level 320 therefore can be used to reduce PFC level 201 filtering capacitor C size or increase running (ride-through) time that power converter declines for ac input voltage (input voltage vin).As described further below, adopt nonlinear feedback to carry out control loop compensation.
As described in more detail below, by controller 325, draw burst mode control signal.When burst mode control signal is high level, controller 325 is enabled and operates.On the contrary, when burst mode control signal is low level, controller 325 is disabled.Burst mode control signal can be used to the burst operation pattern of enable power transducer.Pfc controller 330 the master power switch S1 for PFC level 201 during the main duty ratio D of switch periods and complementary duty cycle 1-D provide gate drive signal, and LLC controller 333 is master power switch M1 and the auxiliary power switch M of LLC level 320 during the master space D of switch periods and complementary interval 1-D
2gate drive signal is provided.Pfc controller 330 also adopts voltage Vrect to control the low-frequency current waveform from bridge rectifier 203.Called after GDM
2gate drive signal represent in the circuit shown in Figure 12 by during the complementary interval 1-D of the LLC level 320 adopting to auxiliary power switch M
2gate drive signal.
Turn to now Fig. 4-6, illustrate according to the diagrammatic representation of the exemplary operation characteristic of the power converter of principle of the present invention.Fig. 4 illustrates the voltage-transfer characteristic of the LLC level of power converter.The output voltage V out of the LLC level (and power converter) of locating at the specific busbar voltage Vbus from PFC level (such as 400 volts) depends on the switching frequency fs of LLC level in nonlinear mode.Along with busbar voltage, Vbus reduces, output voltage V out proportional reducing approx in the situation that switching frequency fs is constant.Consequently switching frequency fs can change that output voltage V out is controlled when busbar voltage Vbus changes.Yet change switching frequency fs is nonlinear for the impact of output voltage V out.Resonance frequency fres represents the resonance frequency of LLC level.
Turn to now Fig. 5, illustrate the diagrammatic representation as the contrafunctional correction factor G of the curve that depends on frequency shown in Fig. 4.The curve that depends on frequency as shown in Figure 4 multiplying each other with this correction factor G produces the straight line of the characteristic that depends on frequency of the voltage-transfer characteristic of LLC level.The result multiplying each other with correction factor G illustrates in Fig. 6, such as the straight line 610 that equals the busbar voltage Vbus of 400 volts.In one embodiment, correction factor G is similar to by the broken line correction factor shown in Fig. 5 (such as five sections of broken line correction factors) G '.
Turn to now Fig. 7, illustrate the diagram of the embodiment of the power converter that PFC level (such as the PFC level 201 of Fig. 2) that utilization that principle according to the present invention constructs is coupled to LLC level (such as the LLC level 320 of Fig. 3) forms.This power converter reception input voltage also (via bridge rectifier) provides commutating voltage Vrect, and this commutating voltage Vrect is converted to output voltage V out by PFC level 201 and LLC level 320.The resitstance voltage divider that utilization is formed by the first resistor Rsensel and the second resistor Rsense2 carrys out sensing output voltage V out, and the output voltage of institute's sensing is coupled to the anti-phase input of the operational amplifier 345 of error amplifier 340.Error amplifier 340 comprises that at its feedback path resistor-capacitor network 360 is to produce output voltage error signal (being also known as " error signal ") δ V.
By adopting switching frequency fs that nonlinear function subsystem 335 controls LLC level 320 to compensate and obtained larger feedback loop stability it is depended on to the response of frequency in feedback loop.According to non-linear subsystem 335, correction factor G for example, is similar to the form of broken line correction factor (, five sections of broken line correction factor G '), and it is applied to output voltage error signal δ V to produce calibrated error signal δ V_cor.Should be understood that, optical coupler (all optical couplers 350 as shown in Figure 3) can cooperate to produce output voltage error signal δ V with error amplifier 340.In one embodiment, in nonlinear function subsystem 335, adopt five sections of broken line correction factor G ' to reduce the nonlinear feedback effect being produced by LLC level 320.These five sections of broken line correction factor G ' can more generally be known as broken line correction factor.Calibrated error signal δ V_cor is coupled to the input of the voltage controlled oscillator (VCO) 336 that the switching frequency fs of LLC level 320 is controlled.Nonlinear function subsystem 335 and voltage controlled oscillator 336 form at least a portion (equally referring to Fig. 3) of LLC controller 333.
Switching frequency fs is also coupled to pfc controller 330, and it produces the master power switch S for PFC level 201
1gate drive signal GD (seeing Fig. 3).The busbar voltage Vbus of pfc controller 330 sensing PFC levels 201.Pfc controller 330 controls the mean value of switching frequency fs to be remained near perfect switch frequency f o=1/ (2 π sqrt (LkCr)) to keep the power conversion efficiency that LLC level 320 is high to busbar voltage Vbus in compared with slow-response control loop.
Aspect another, pfc controller 330 (for example promotes busbar voltage Vbus simply frequently, in 20 milliseconds, promoted 6 volts or 7 volts) with generated error in error signal δ V, or generated error in calibrated error signal δ V_cor correspondingly, thereby make it possible to enter burst operation pattern to detect underloading operation.As described in more detail below, the operating basis burst mode controller 370 of the burst mode in underloading situation and the obvious improvement that produces power conversion efficiency.Pfc controller 330 can promote busbar voltage Vbus by promoting simply the reference voltage that is wherein used for that in conjunction with error amplifier busbar voltage Vbus is adjusted.As described below with reference to Fig. 8, the busbar voltage that is coupled to the input of error amplifier 332 is promoted simply so that can detect underloading and is operated with reference to Vbus_ref.When intersecting, error signal δ V or calibrated error signal δ V_cor and threshold level enter burst mode.
In operation in underloading situation, busbar voltage Vbus is because the reduction loss of LLC level 320 is reduced to low value.When busbar voltage Vbus is raised within the short time period, in error signal δ V, caused variation (for example, reducing) is used to determine whether enter burst mode.Higher busbar voltage Vbus reduces the switching frequency of LLC level 320.The busbar voltage Vbus and the underloading that increase fully decline error signal δ V, and this is detected and enters burst mode.When drifting to threshold level as indicated in the lifting by error signal δ V downwards, exits output voltage V out burst mode.In burst operation pattern, the switch motion of PFC level 201 and LLC level 320 is all closed (the alternation characteristic of duty ratio D that for example, stops being used for controlling the gate drive signal of corresponding power switch).
Turn to now Fig. 8, illustrate the diagram that utilization that principle according to the present invention constructs is coupled to the PFC level (such as the PFC level 201 of Fig. 2) of LLC level (such as the LLC level 320 of Fig. 3) and the embodiment of the power converter that controller (each several part that comprises the controller 325 of Fig. 7) forms.Pfc controller 330 comprises error amplifier (E/A) 331, and it has an input that is coupled to the switching frequency fs being produced by voltage controlled oscillator (VCO) 336, is preferably anti-phase input.Another input (being preferably noninverting input) of error amplifier 331 is coupled to frequency reference fs_ref, and this is the switching frequency of the expectation of LLC level 320.In one embodiment, the switching frequency of expectation (being similar to perfect switch frequency) is fo=1/ (2 π sqrt (LkCr)).Error amplifier 331 produces busbar voltage with reference to Vbus_ref, and it is used for the busbar voltage Vbus being produced by PFC level 201 to adjust by error amplifier (E/A) 332 in compared with slow-response control loop.Busbar voltage represents to provide to power converter the expectation voltage level of the busbar voltage Vbus of high power conversion efficiency with reference to Vbus_ref.By this way, 325 couples of busbar voltage Vbus that produced by PFC level 201 of controller adjust to produce the average frequency of switching fs of LLC level 320, and it causes the high power conversion efficiency of LLC level 320.Error amplifier 340 is held to utilize fast-response control loop the output voltage V out of power converter to be adjusted so that power converter can utilize the ripple voltage level of reduction to carry out compactness adjustment to output voltage V out, and this ripple voltage will otherwise be produced by the ripple voltage on the busbar voltage Vbus of PFC level 201.
Therefore, at this, controller for power converter is introduced.In one embodiment, this controller comprises LLC controller, its be configured to receive from the error signal of error amplifier with control this power converter LLC level (for example, LLC resonance buck stages) switching frequency and its output voltage is adjusted.This controller also comprises pfc controller, it is configured to busbar voltage to control, this busbar voltage by the PFC level of this power converter (for example, PFC voltage-boosting stage) for example produce and be provided to LLC level, so that its average frequency of switching is maintained at the switching frequency (, being substantially equal to the resonance frequency of LLC level) of expectation substantially.The control loop being associated with LLC level can have than the control loop being associated with PFC level and responds faster.LLC controller can comprise nonlinear function subsystem, and it is for example configured to, to error signal application correction factor (, being similar to by broken line correction factor) to produce calibrated error signal.LLC controller can comprise voltage controlled oscillator, and it is configured to receive calibrated error signal so that the switching frequency of LLC level is controlled.
Pfc controller is configured to promote busbar voltage and with generated error in error signal, carrys out the underloading operation of detection power transducer.Error amplifier is coupled to resitstance voltage divider, and this resitstance voltage divider is configured to sensing output voltage and the output voltage of institute's sensing is provided to the operational amplifier of error amplifier to produce error signal.PFC level can comprise at least one error amplifier, and it is configured to the busbar voltage of the function of the switching frequency of the switching frequency as LLC level and expectation to control.This controller can also comprise burst mode controller, and it is configured such that this power converter in underloading situation and/or when error signal and burst threshold level intersect, enters burst operation pattern.This controller can also be coupled to the resitstance voltage divider that is configured to sensing output voltage, and the first sense switch and the second sense switch that are coupled to this resitstance voltage divider, it is configured to reduce power loss when this power converter enters burst operation pattern.
Turn to now Fig. 9, illustrate the schematic diagram according to the embodiment that is configured to burst mode controller (such as the burst mode controller 370 of Fig. 7 and Fig. 8) that the burst operation pattern of power converter is managed of principle of the present invention.The time span (or the time interval or window) that operating in therebetween of controller 325 is disabled (gate drive signal that for example, controller is not exported PFC level or LLC level) can be used as for determining the indicating device quite accurately of power output.This time interval can be used to determine that the outlet of burst mode is to prepare possible subsequently transition load step.The turn-off time of using the voltage that produces across ramp voltage time capacitor Cramp to carry out Mersure Controler 325.
Utilize the first comparator 920 and the second comparator 930 to form burst mode controller 370, this first comparator 920 has and is coupled to the noninverting input of error signal δ V and the anti-phase input of the horizontal Vburst_high of paramount burst threshold that is coupled (the second burst threshold level), and this second comparator 930 has the anti-phase input that is coupled to error signal δ V and the noninverting input that is coupled to the horizontal Vburst_low of low burst threshold (the first burst threshold level).The output of comparator 920,930 is coupled to " set " input and " reset " of the first set-reset flip-flop 940 and the second set-reset flip-flop 970 and one of inputs." Q " output of the first set-reset flip-flop 940 arranges burst mode control signal Fon.Comparator 920,930 and the first set-reset flip-flop 940 form the burst mode of burst mode controller 370 and initiate at least a portion of circuit.
Voltage promotes signal Fves and is set to high level in the situation that be greater than condenser voltage threshold value V_cap_thresh across the condenser voltage Vcap of ramp voltage time capacitor Cramp.Across the high voltage of ramp voltage time capacitor Cramp, be considered to be coupled to the indication of low power load of the output of power converter, make it possible to thus enter burst operation pattern.Voltage promotes signal Fves and also in response to carrying out the signal of self-timer 980, is set to high level, and this provides a kind of mechanism for testing being coupled to the load of the output of power converter.
Turn to now Figure 10, illustrate the diagrammatic representation in the example waveform according to producing in the power converter of principle of the present invention.Continue with reference to previous accompanying drawing, as indicated in the periodic switch of the duty ratio D of the gate drive signal of the switch of the power train by for this power converter, suppose that at first power converter provides substantive power to the load that is coupled to its output.The periodic switch of the switch of this power converter is enabled by burst mode control signal Fon.Error signal δ V be assumed to be numerical value between the horizontal Vburst_high of high burst threshold and the horizontal Vburst_low of low burst threshold with indication output voltage V out in acceptable voltage adjusting range.Condenser voltage Vcap is because burst mode control signal Fon is that high level remains zero volt, and this conducting slope switch Qramp, makes ramp voltage time capacitor Cramp short circuit.
In time T 0, the output of timer 980 second set-reset flip-flops 970 is set to high level, and this voltage promotes the reference voltage Vref that signal Fves is set to the operational amplifier 345 of high level and rising error amplifier 340 (seeing Fig. 7, Fig. 8 and Figure 11).Voltage promotes signal Fves and initiates being coupled to the test of underloading of the output of power converter.As its response, the output voltage V out of rising power converter, it is finally reduced to the horizontal Vburst_low of low burst threshold in time T 1 by error signal δ V.This is reset as low level (to enter burst operation pattern) burst mode control signal Fon, and voltage lifting signal Fves is also set to low level.As indicated by the disappearance of duty ratio D, stop the switch motion of power converter.And if the load rising on power converter on condenser voltage Vcap slope is fully low, it intersects with condenser voltage threshold value V_cap_thresh in time T 2, and this makes voltage promote signal Fves and burst mode control signal Fon is set to high level.Therefore, the time window of burst operation pattern is between time T 1 and time T 2.Therefore, voltage promote signal Fves due to time window before error signal δ V and the horizontal Vburst_high of high burst threshold are crossing the expired high level that is set to the output voltage V out of rising power converter.Alternatively, timer 980 can make voltage promote signal Fves and be set to high level, and correspondingly the reference voltage Vref that will promote is set.Therefore, use error signal δ V carries out indirect sensing to the output voltage V out of power converter and adopts by carry out the power output of estimating power transducer for controlling the slope of measured output signal Vout of time interval of burst operation pattern.
The time interval (time window) of the indicating device of the slope of output voltage V out 960 sensings of the 3rd comparator is as shown in Figure 9 determined.If condenser voltage Vcap between time T 1 and time T 2 (for example, when burst mode control signal Fon is that low level is while indicating output voltage V out within acceptable voltage adjusting range) do not intersect with condenser voltage threshold value v_cap_thresh, the slope of output voltage V out is fully little and signaling enters burst operation pattern.Therefore, the load on power converter is estimated as and is less than predetermined low threshold level.For example, if the specified load that provides 60 watts of power converter, predetermined low threshold level can determine that by operation described above power output is less than 5 watts for 5 watts and burst mode controller 370.In other words, burst mode controller 370 is estimated power output in conjunction with the slope of output voltage V out.
On the contrary, if condenser voltage Vcap before time T 2 (for example, when burst mode control signal Fon is that low level is while indicating output voltage V out lower than acceptable voltage adjusting range) intersect with condenser voltage threshold value V_cap_thresh, the abundant height of the slope of output voltage V out and signaling exits (that is, the switch motion of enable power transducer) from burst operation pattern.Therefore, the load on power converter is estimated to be greater than predetermined low threshold level.For example, if the specified load that provides 60 watts of power converter, predetermined low threshold level can determine that by operation described above power output is greater than 5 watts for 5 watts and burst mode controller 370.In other words, burst mode controller 370 is estimated power output in conjunction with the slope of output voltage V out.
Result is that fully high output voltage V out burst mode control signal Fon is set to low level, and low output voltage Vout burst mode control signal Fon is set to high level.Timer 980 periodically voltage promotes signal Fves and is set to high level, and the abundant high condenser voltage Vcap producing across ramp voltage time capacitor Cramp also voltage promote signal Fves and be set to high level.Therefore, the time interval of the burst operation pattern of power converter is used to determine that the slope of output voltage V out estimates with the power output to this power converter.The low power load that is coupled to the output of power converter is detected and makes this power converter can enter burst operation pattern.Be used as the indicating device of low slope of the output voltage V out of power converter with the crossing condenser voltage Vcap of condenser voltage threshold value V_cap_thresh, and correspondingly as the indicating device of low power load.
Turn to now Figure 11, illustrate the utilization that principle according to the present invention constructs and be coupled to the first resistor Rsensel of output voltage V out of power converter (for example, seeing the power converter of Fig. 3, Fig. 7 and Fig. 8) and the diagram of the embodiment of the resitstance voltage divider that the second resistor Rsense2 forms.This resitstance voltage divider for example, is coupled to the noninverting input of operational amplifier 345 by the first sense switch (, n channel mosfet) Qsense2 now, and for example, is coupled to earth terminal by the second sense switch (, n channel mosfet) Qsensel.Burst mode control signal Fon power converter as burst mode control signal Fon be low level indicated in burst operation pattern time open the first sense switch Qsensel and the second sense switch Qsense2 to reduce power loss.
The reference voltage Vref that is used for the output voltage V out of power converter to adjust is coupled to voltage source V 1 by resistor R1, and is coupled to voltage lifting signal Fves by another resistor R2.By this way, voltage promotes signal Fves and when voltage lifting signal Fves is set to high level, promotes reference voltage Vref.
Turn to now Figure 12, illustrate the diagram of embodiment of a part for the voltage lifting circuit that can adopt that principle according to the present invention constructs in burst mode controller 370, it for example, for generation of the slope signal Vslope of the slope of the output voltage V out of indicated horsepower transducer (, seeing the power converter of Fig. 3, Fig. 7 and Fig. 8).This part of the voltage lifting circuit of Figure 12 is the replacement form of current source 950, the 3rd comparator 960, slope switch Qramp and the ramp voltage time capacitor Cramp of the burst mode controller 370 shown in Fig. 9.Error signal δ v shown in this part alternate figures 9 of the voltage lifting circuit of Figure 12 carrys out sensing output voltage V out.Resistor Rrip is coupled to output voltage V out with the derivative of sensing output voltage V out by capacitor Crip.Utilize low pass filter to carry out filtering to produce the slope signal Vslope through filtering to this derivative, utilize the filter resistor Rfilter that is coupled to filtering capacitor Cfilter to form this low pass filter.In one embodiment, utilizing the time constant of the circuit of the resistor Rrip formation that is coupled to capacitor Crip is the multiple (for example, 10 of switch periods times) of the switch periods of power converter.In one embodiment, utilizing the time constant of the low pass filter of the filter resistor Rfilter formation that is coupled to filtering capacitor Cfilter is the approximate number (for example, 0.01 of switch periods times) of the switch periods of power converter.
During complementary interval 1-D, slope signal Vslope can be used to output or the bearing power that estimation is coupled to the output of power converter.This slope signal Vslope is coupled to the noninverting input of comparator 1220, and the anti-phase input of comparator 1220 is coupled to slope reference voltage Vref l.The output signal 1230 of comparator 1220 is coupled to the input with (AND) door 1240, and is coupled to gate drive signal GDM with another input of (AND) door 1240
2, it is illustrated in during the complementary interval 1-D of LLC level 320 (seeing Fig. 3) to auxiliary power switch M
2gate drive signal.Corresponding to output signal 990, its second set-reset flip-flop 970 that is used to illustrate and describe with reference to figure 9 arranges voltage and promotes signal Fves with the output of (AND) door 1240.
The voltage slope dVout/dt of output voltage V out is relevant to bearing power by following equation:
Wherein Cout is the output filter capacitor of power converter as shown in Figure 3.
As mentioned with regard to burst operation pattern above, the power loss of power converter depends on for the gate drive signal of power switch and conventionally substantially not with other continuous power loss of load variations.These power losses are generally by being used burst operation pattern to be solved at low-down power level place, wherein within a period of time (for example, one second) make controller (such as the controller 325 in accompanying drawing before) invalid subsequently for example, for the high power operation of short time (, 10 milliseconds (ms)) has low-loss harmonic(-)mean power output to provide.Controller can adopt output (or load) power of the time interval estimating power transducer of burst operation pattern as described herein.
Therefore, here to introducing for the burst mode controller using with power converter.In one embodiment, this burst mode controller comprises that burst mode initiates circuit, and it is configured to initiate burst operation pattern when the signal of output voltage that represents power converter is crossing with the first burst threshold level.This burst mode controller also comprises voltage lifting circuit, its be configured at time window in the situation that represent the signal of output voltage of power converter and the second burst threshold level intersect before the expired voltage that provides promote signal with boosted output voltages.This burst mode is initiated circuit and be also configured to stop burst operation pattern when the signal of output voltage that represents power converter is crossing with the second burst threshold level.
This burst mode is initiated circuit can comprise comparator, and it is configured to the signal and the first burst threshold level that represent the output voltage of power converter to compare.This burst mode is initiated circuit can also comprise trigger, and it is configured to arrange burst mode control signal when the signal that represents the output voltage of power converter intersects with the first burst threshold level with initiation burst operation pattern.This voltage lifting circuit can comprise current source, ramp voltage time capacitor and be configured to the whether expired comparator of window detection time.This voltage lifting circuit can also comprise trigger, and it is configured to arrange voltage and promotes signal with boosted output voltages.This voltage promotes signal be configured to raise reference voltage of error amplifier, and this error amplifier is configured to the output voltage of power converter to control.This burst mode is initiated circuit and be configured to make voltage lifting invalidating signal when the signal that represents the output voltage of power converter is intersected with the first burst threshold level.This burst mode controller can also comprise timer, and it is configured to initiate (and/or periodically initiating) voltage and promotes signal with boosted output voltages.
This controller and correlation technique may be implemented as hardware (being included in one or more chips of the integrated circuit comprising such as application-specific integrated circuit (ASIC)), or may be implemented as software or firmware for for example, being carried out according to memory by processor (, digital signal processor).Especially, the in the situation that of firmware or software, exemplary embodiment may be provided in the computer program that comprises computer-readable medium, and this computer-readable medium comprises computer program code (that is, software or firmware) thereon to be carried out for processor.
The program or the code segment that form each embodiment can be stored in computer-readable medium.For example, comprise that the computer program that is stored in for example, program code in computer-readable medium (, non-instantaneous computer-readable medium) can form each embodiment." computer-readable medium " can comprise and can store or the arbitrary medium of transmission information.The example of computer-readable medium comprises electronic circuit, semiconductor memory devices, read-only memory (ROM), flash memory, erasable ROM (EROM), floppy disk, CD (CD)-ROM etc.
Before one skilled in the art will appreciate that described comprise the power converter of the magnetic texure that comprises the U-shaped core body being positioned in straight line core body and form the embodiment of correlation technique of this power converter only submitted for illustrative object.Although magnetic texure is described in the environment of power converter, this magnetic texure can also be applied to other system, such as, but not limited to power amplifier or electric machine controller.
In order to understand better power converter, " Modern DC-to-DC Power Switch-mode Power Converter Circuits " (New York, New York Van Nostrand Reinhold company referring to Rudolph P.Severns and Gordon Bloom, 1985), and J.G.Kassakian, M.F.Schlecht and G.C.Verghese " Principles of Power Electronics " (Addison-Wesley, 1991).Above-mentioned list of references is incorporated into this by reference of text.
And, although the present invention and advantage thereof be have been described in detail, should be understood that, can carry out various changes, replacement and variation therein and not deviate from the spirit and scope of the present invention as being defined by the following claims.For example, many processes discussed above can be implemented and be substituted by other process or its combination with distinct methods.
In addition, the application's scope is not intended to be limited to the specific embodiment of process, machine, manufacture, combinations of substances, means, method and step described in specification.As those skilled in the art, will easily recognize from disclosure of the present invention, can be according to the present invention process, machine, manufacture, combinations of substances, means, method or the step carrying out substantially the same function with corresponding embodiment described herein or obtain substantially the same result existing or that will develop be used later.Therefore, within claims are intended to that such process, machine, manufacture, combinations of substances, means, method or step are included in to its scope.
Claims (20)
1. for the controller with power converter use, described controller comprises:
Inductor-Inductor-Capacitor (LLC) controller, is configured to receive and with the output voltage to described power converter, adjusts to control the switching frequency of the LLC level of described power converter from the error signal of error amplifier; And
Power factor correction (PFC) controller, the busbar voltage that is configured to the PFC level by described power converter to produce and be provided to described LLC level is controlled so that the average frequency of switching of described LLC level is maintained at the switching frequency of expectation substantially.
2. controller according to claim 1, wherein said PFC level is that PFC voltage-boosting stage and described LLC level are LLC resonance buck stages.
3. controller according to claim 1, the control loop being wherein associated with described LLC level has than the control loop being associated with described PFC level and responds faster.
4. controller according to claim 1, wherein said LLC controller comprises nonlinear function subsystem, described nonlinear function subsystem is configured to described error signal application correction factor to produce calibrated error signal.
5. controller according to claim 4, wherein said correction factor is similar to by broken line correction factor.
6. controller according to claim 4, wherein said LLC controller comprises voltage controlled oscillator, described voltage controlled oscillator is configured to receive described calibrated error signal and controls with the described switching frequency to described LLC level.
7. controller according to claim 1, wherein said pfc controller is configured to promote described busbar voltage and with generated error in described error signal, detects the underloading operation of described power converter.
8. controller according to claim 1, wherein said error amplifier is coupled to resitstance voltage divider, and described resitstance voltage divider is configured to output voltage described in sensing and provides operational amplifier to described error amplifier to produce described error signal the output voltage of sensing.
9. controller according to claim 1, wherein said PFC level comprises at least one error amplifier, and described error amplifier is configured to the described busbar voltage of the function of the switching frequency of the described switching frequency as described LLC level and described expectation to control.
10. controller according to claim 1, further comprises burst mode controller, and described burst mode controller is configured such that described power converter enters burst operation pattern in the situation that of underloading.
11. controllers according to claim 1, further comprise burst mode controller, and described burst mode controller is configured such that described power converter enters burst operation pattern when described error signal and burst threshold level intersect.
12. controllers according to claim 1, wherein resitstance voltage divider is configured to output voltage described in sensing, and the first sense switch and the second sense switch that are coupled to described resitstance voltage divider are configured to reduce power loss when described power converter enters burst operation pattern.
13. controllers according to claim 1, the switching frequency of wherein said expectation is substantially equal to the resonance frequency of described LLC level.
14. 1 kinds of methods that power converter is operated, comprising:
Reception is adjusted the output voltage of described power converter to control the switching frequency of inductor-Inductor-Capacitor (LLC) level of described power converter from the error signal of error amplifier; And
The busbar voltage that power factor correction by described power converter (PFC) level is produced and is provided to described LLC level is controlled so that the average frequency of switching of described LLC level is maintained at the switching frequency of expectation substantially.
15. methods according to claim 14, the control loop being wherein associated with described LLC level has than the control loop being associated with described PFC level and responds faster.
16. methods according to claim 14, further comprise to described error signal application correction factor and using and produce calibrated error signal and the described switching frequency of the described LLC level of the function as described calibrated error signal is controlled.
17. methods according to claim 14, further comprise that promoting described busbar voltage detects the underloading operation of described power converter with generated error in described error signal.
18. methods according to claim 14, further comprise and make described power converter in the situation that of underloading, enter burst operation pattern.
19. methods according to claim 14, further comprise and make described power converter when described error signal and burst threshold level intersect, enter burst operation pattern.
20. methods according to claim 14, further comprise output voltage described in sensing, and when described power converter enters burst operation pattern, reduce power loss.
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| US13/543,503 US9190898B2 (en) | 2012-07-06 | 2012-07-06 | Controller for a power converter and method of operating the same |
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| TWM561825U (en) | 2018-02-12 | 2018-06-11 | Chicony Power Tech Co Ltd | Power conversion control circuit |
| US10797606B2 (en) * | 2018-12-13 | 2020-10-06 | Power Integrations, Inc. | Controller with limit control to change switching period or switching frequency of power converter and methods thereof |
| US10763756B2 (en) | 2018-12-13 | 2020-09-01 | Power Integrations, Inc. | Apparatus and methods for sensing resonant circuit signals to enhance control in a resonant converter |
| CN112003455B (en) * | 2019-05-27 | 2022-04-29 | 台达电子工业股份有限公司 | Power supply and control method thereof |
| US10985664B1 (en) | 2019-10-18 | 2021-04-20 | Raytheon Company | Controlling operation of a voltage converter based on transistor drain voltages |
| US10938309B1 (en) | 2019-10-18 | 2021-03-02 | Raytheon Company | Controlling operation of a voltage converter based on inductor current |
| US11424684B2 (en) * | 2020-06-10 | 2022-08-23 | Apple Inc. | High performance two stage power converter with enhanced light load management |
| US11552563B2 (en) * | 2020-11-18 | 2023-01-10 | Apple Inc. | Voltage regulator with dv/dt detection |
| TWI771882B (en) * | 2021-01-27 | 2022-07-21 | 群光電能科技股份有限公司 | Power converter device and driving method |
| US11742808B1 (en) | 2022-09-15 | 2023-08-29 | University Of Houston System | Compact pulsed power supplies |
| TWI837944B (en) * | 2022-11-15 | 2024-04-01 | 宏碁股份有限公司 | Power supply device with high output stability |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20050099827A1 (en) * | 2003-11-11 | 2005-05-12 | Hitachi Ltd. | Resonant converter and control method thereof |
| JP2005348560A (en) * | 2004-06-04 | 2005-12-15 | Sanken Electric Co Ltd | Switching power supply apparatus and power factor improving circuit |
| CN101123395A (en) * | 2006-08-04 | 2008-02-13 | 凌特公司 | Circuits and methods for adjustable peak inductor current and hysteresis for burst mode in switching regulators |
| US20090072626A1 (en) * | 2005-05-26 | 2009-03-19 | Rohm Co., Ltd. | Power supply apparatus having switchable switching regulator and linear regulator |
| US20100020578A1 (en) * | 2008-07-25 | 2010-01-28 | Samsung Electro-Mechanics Co., Ltd. | Adapter power supply |
Family Cites Families (411)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US1376978A (en) | 1917-11-24 | 1921-05-03 | Cutler Hammer Mfg Co | Regulator for alternating currents |
| US2387943A (en) | 1943-03-25 | 1945-10-30 | Westinghouse Electric Corp | Magnetic core structure |
| US2473662A (en) | 1944-08-02 | 1949-06-21 | Lorain Prod Corp | Rectifying arrangement |
| US3007060A (en) | 1959-03-23 | 1961-10-31 | Gen Dynamics Corp | Circuitry for independently delaying the leading and trailing edges of an input pulse |
| US3346798A (en) | 1963-08-08 | 1967-10-10 | Gen Electric | Regulator for inverter |
| US3358210A (en) | 1964-06-25 | 1967-12-12 | Gen Electric | Voltage regulator |
| US3433998A (en) | 1965-04-24 | 1969-03-18 | Philips Corp | Circuit arrangement for frame correction |
| US3484562A (en) | 1966-09-21 | 1969-12-16 | Nortronics Co | Magnetic transducer with clamped body sections to hold core pieces |
| FR96147E (en) | 1967-09-14 | 1972-05-19 | Ibm | Converter improves direct current to direct current with constant power to the load. |
| US3622868A (en) | 1970-02-06 | 1971-11-23 | Joachim H Todt | Regulating power transformer with magnetic shunt |
| US3681679A (en) | 1971-05-07 | 1972-08-01 | Kheemoy Chung | Constant voltage transformer three-phase ferro resonant |
| US3708742A (en) | 1971-06-30 | 1973-01-02 | Ibm | High dc to low dc voltage converter |
| US3708744A (en) | 1971-08-18 | 1973-01-02 | Westinghouse Electric Corp | Regulating and filtering transformer |
| US4019122A (en) | 1974-08-14 | 1977-04-19 | Telcon-Magnetic Cores Limited | Stabilized power supplies |
| US4011498A (en) | 1975-06-26 | 1977-03-08 | General Electric Company | Controlling circuit |
| US4075547A (en) | 1975-07-23 | 1978-02-21 | Frequency Technology, Inc. | Voltage regulating transformer |
| US4327348A (en) | 1977-05-20 | 1982-04-27 | Tdk Electronics Co., Ltd. | Variable leakage transformer |
| US4202031A (en) | 1978-11-01 | 1980-05-06 | General Electric Company | Static inverter employing an assymetrically energized inductor |
| US4257087A (en) | 1979-04-02 | 1981-03-17 | California Institute Of Technology | DC-to-DC switching converter with zero input and output current ripple and integrated magnetics circuits |
| US4274071A (en) | 1979-11-16 | 1981-06-16 | Bell Telephone Laboratories, Incorporated | Three-phase ferroresonant transformer structure embodied in one unitary transformer construction |
| JPS5797361U (en) | 1980-12-05 | 1982-06-15 | ||
| US4570174A (en) | 1981-08-21 | 1986-02-11 | The United States Of America As Represented By The Secretary Of The Army | Vertical MESFET with air spaced gate electrode |
| US4471423A (en) | 1982-02-17 | 1984-09-11 | Hase A M | Multi-voltage DC output with single reactor voltage control |
| JPH0718087B2 (en) | 1982-12-07 | 1995-03-01 | コモンウエルス・サイエンテイフィック・アンド・インダストリアル・リサーチ・オーガニゼーション | Method of protecting wool, dyed wool, silk, nylon or a blend thereof from light deterioration and wool protected from light degradation, dyed wool, silk, nylon or a blend thereof |
| US4577268A (en) | 1982-12-20 | 1986-03-18 | Rca Corporation | Switching dc-to-dc converters |
| US4499481A (en) | 1983-09-14 | 1985-02-12 | The United States Of America As Represented By The Secretary Of The Navy | Heterojunction Schottky gate MESFET with lower channel ridge barrier |
| US4613841A (en) | 1983-11-30 | 1986-09-23 | General Electric Company | Integrated transformer and inductor |
| US4581691A (en) | 1984-04-23 | 1986-04-08 | At&T Bell Laboratories | Balanced constant current sensing circuit inherently immune to longitudinal currents |
| US4636823A (en) | 1984-06-05 | 1987-01-13 | California Institute Of Technology | Vertical Schottky barrier gate field-effect transistor in GaAs/GaAlAs |
| JPS61107813A (en) | 1984-10-30 | 1986-05-26 | Mitsubishi Electric Corp | Semiconductor device |
| DE3575055D1 (en) | 1985-01-24 | 1990-02-01 | Bull Hn Information Syst | SIMPLY CONTROLLED POWER SUPPLY WITH LOAD COMPENSATION FROM Auxiliary Voltage Output. |
| FR2586146A1 (en) | 1985-08-09 | 1987-02-13 | Pham Dang Tam | HIGH POWER ELECTRONIC VOLTAGE CONVERTER |
| US4803609A (en) | 1985-10-31 | 1989-02-07 | International Business Machines Corporation | D. C. to D. C. converter |
| US4785387A (en) | 1986-04-28 | 1988-11-15 | Virginia Tech Intellectual Properties, Inc. | Resonant converters with secondary-side resonance |
| DE3632746C2 (en) | 1986-09-26 | 1995-04-13 | Kommunikations Elektronik | Circuit arrangement for generating an AC voltage |
| US4780653A (en) | 1987-03-05 | 1988-10-25 | Pulse Electronics, Inc. | Anti-stall motor drive |
| US4823249A (en) | 1987-04-27 | 1989-04-18 | American Telephone And Telegraph Company At&T Bell Laboratories | High-frequency resonant power converter |
| DK382687A (en) | 1987-07-22 | 1989-04-14 | Scanpower | POWER SUPPLY CIRCUIT |
| JPH01108917U (en) | 1988-01-18 | 1989-07-24 | ||
| US4770668A (en) | 1988-01-19 | 1988-09-13 | National Starch And Chemical Corporation | Ethylene urea compositions useful as permanent press promoting chemicals |
| US5106778A (en) | 1988-02-02 | 1992-04-21 | Massachusetts Institute Of Technology | Vertical transistor device fabricated with semiconductor regrowth |
| US4903089A (en) | 1988-02-02 | 1990-02-20 | Massachusetts Institute Of Technology | Vertical transistor device fabricated with semiconductor regrowth |
| US4876638A (en) | 1988-02-10 | 1989-10-24 | Electronic Research Group, Inc. | Low-noise switching power supply having variable reluctance transformer |
| US4837496A (en) | 1988-03-28 | 1989-06-06 | Linear Technology Corporation | Low voltage current source/start-up circuit |
| US4866367A (en) | 1988-04-11 | 1989-09-12 | Virginia Tech Intellectual Properties, Inc. | Multi-loop control for quasi-resonant converters |
| JPH0779063B2 (en) | 1988-08-15 | 1995-08-23 | 三菱電機株式会社 | Phase adjustment transformer |
| US5223449A (en) | 1989-02-16 | 1993-06-29 | Morris Francis J | Method of making an integrated circuit composed of group III-V compound field effect and bipolar semiconductors |
| US5068756A (en) | 1989-02-16 | 1991-11-26 | Texas Instruments Incorporated | Integrated circuit composed of group III-V compound field effect and bipolar semiconductors |
| US4962354A (en) | 1989-07-25 | 1990-10-09 | Superconductivity, Inc. | Superconductive voltage stabilizer |
| US4922400A (en) | 1989-08-03 | 1990-05-01 | Sundstrand Corporation | Neutral forming circuit |
| IT1231052B (en) | 1989-09-27 | 1991-11-12 | Bull Hn Information Syst | SWITCHING POWER SUPPLY WITH MULTIPLE OUTPUTS, ADJUSTING AN OUTPUT VOLTAGE AND LOAD COMPENSATION. |
| US5027264A (en) | 1989-09-29 | 1991-06-25 | Wisconsin Alumni Research Foundation | Power conversion apparatus for DC/DC conversion using dual active bridges |
| US4964028A (en) | 1989-10-26 | 1990-10-16 | Plessey Electronic Systems Corp. | Current limited quasi-resonant voltage converting power supply |
| US5182535A (en) | 1989-12-19 | 1993-01-26 | Dhyanchand P John | Summing transformer core for star-delta inverter having a separate secondary winding for each primary winding |
| US5177460A (en) | 1990-01-04 | 1993-01-05 | Dhyanchand P John | Summing transformer for star-delta inverter having a single secondary winding for each group of primary windings |
| US5014178A (en) | 1990-05-14 | 1991-05-07 | Power Integrations, Inc. | Self powering technique for integrated switched mode power supply |
| US5206621A (en) | 1990-07-02 | 1993-04-27 | General Electric Company | Barrel-wound conductive film transformer |
| US5055991A (en) | 1990-10-12 | 1991-10-08 | Compaq Computer Corporation | Lossless snubber |
| DK173534B1 (en) | 1990-11-14 | 2001-02-05 | Scanpower | Power supply circuit with integrated magnetic components |
| US5126714A (en) | 1990-12-20 | 1992-06-30 | The United States Of America As Represented By The Secretary Of The Navy | Integrated circuit transformer |
| US5132888A (en) | 1991-01-07 | 1992-07-21 | Unisys Corporation | Interleaved bridge converter |
| GB2252208B (en) | 1991-01-24 | 1995-05-03 | Burr Brown Corp | Hybrid integrated circuit planar transformer |
| US5291382A (en) | 1991-04-10 | 1994-03-01 | Lambda Electronics Inc. | Pulse width modulated DC/DC converter with reduced ripple current coponent stress and zero voltage switching capability |
| US5134771A (en) | 1991-07-05 | 1992-08-04 | General Electric Company | Method for manufacturing and amorphous metal core for a transformer that includes steps for reducing core loss |
| US5172309A (en) | 1991-08-07 | 1992-12-15 | General Electric Company | Auxiliary quasi-resonant dc link converter |
| ATE135856T1 (en) | 1991-08-30 | 1996-04-15 | Alcatel Bell Sdt Sa | AC CURRENT METER AND POWER SUPPLY CIRCUIT |
| JP3311391B2 (en) | 1991-09-13 | 2002-08-05 | ヴィエルティー コーポレーション | Leakage inductance reducing transformer, high frequency circuit and power converter using the same, and method of reducing leakage inductance in transformer |
| US5651667A (en) | 1991-10-11 | 1997-07-29 | Helix Technology Corporation | Cryopump synchronous motor load monitor |
| US5208739A (en) | 1992-01-07 | 1993-05-04 | Powercube Corporation | Integrated magnetic power converter |
| US5225971A (en) | 1992-01-08 | 1993-07-06 | International Business Machines Corporation | Three coil bridge transformer |
| EP0624249B1 (en) | 1992-01-31 | 1999-03-31 | Northrop Grumman Corporation | Arrayed eddy current probe system |
| US5204809A (en) | 1992-04-03 | 1993-04-20 | International Business Machines Corporation | H-driver DC-to-DC converter utilizing mutual inductance |
| US5305191A (en) | 1992-04-20 | 1994-04-19 | At&T Bell Laboratories | Drive circuit for zero-voltage switching power converter with controlled power switch turn-on |
| US5468661A (en) | 1993-06-17 | 1995-11-21 | Texas Instruments Incorporated | Method of making power VFET device |
| US5231037A (en) | 1992-04-30 | 1993-07-27 | Texas Instruments Incorporated | Method of making a power VFET device using a p+ carbon doped gate layer |
| US5342795A (en) | 1992-04-30 | 1994-08-30 | Texas Instruments Incorporated | Method of fabricating power VFET gate-refill |
| US5262930A (en) | 1992-06-12 | 1993-11-16 | The Center For Innovative Technology | Zero-voltage transition PWM converters |
| US5244829A (en) | 1992-07-09 | 1993-09-14 | Texas Instruments Incorporated | Organometallic vapor-phase epitaxy process using (CH3)3 As and CCl4 for improving stability of carbon-doped GaAs |
| US5336985A (en) | 1992-11-09 | 1994-08-09 | Compaq Computer Corp. | Tapped inductor slave regulating circuit |
| US5343140A (en) | 1992-12-02 | 1994-08-30 | Motorola, Inc. | Zero-voltage-switching quasi-resonant converters with multi-resonant bipolar switch |
| US5369042A (en) | 1993-03-05 | 1994-11-29 | Texas Instruments Incorporated | Enhanced performance bipolar transistor process |
| US5303138A (en) | 1993-04-29 | 1994-04-12 | At&T Bell Laboratories | Low loss synchronous rectifier for application to clamped-mode power converters |
| US5554561A (en) | 1993-04-30 | 1996-09-10 | Texas Instruments Incorporated | Epitaxial overgrowth method |
| US6229197B1 (en) | 1993-04-30 | 2001-05-08 | Texas Instruments Incorporated | Epitaxial overgrowth method and devices |
| US6097046A (en) | 1993-04-30 | 2000-08-01 | Texas Instruments Incorporated | Vertical field effect transistor and diode |
| US5712189A (en) | 1993-04-30 | 1998-01-27 | Texas Instruments Incorporated | Epitaxial overgrowth method |
| US5889298A (en) | 1993-04-30 | 1999-03-30 | Texas Instruments Incorporated | Vertical JFET field effect transistor |
| US5636116A (en) | 1993-07-14 | 1997-06-03 | Melcher Ag | Synchronous rectifier impervious to reverse feed |
| US5555494A (en) | 1993-09-13 | 1996-09-10 | Morris; George Q. | Magnetically integrated full wave DC to DC converter |
| US5477175A (en) | 1993-10-25 | 1995-12-19 | Motorola | Off-line bootstrap startup circuit |
| US5374887A (en) | 1993-11-12 | 1994-12-20 | Northern Telecom Limited | Inrush current limiting circuit |
| US5539630A (en) | 1993-11-15 | 1996-07-23 | California Institute Of Technology | Soft-switching converter DC-to-DC isolated with voltage bidirectional switches on the secondary side of an isolation transformer |
| US5610085A (en) | 1993-11-29 | 1997-03-11 | Texas Instruments Incorporated | Method of making a vertical FET using epitaxial overgrowth |
| US5459652A (en) | 1994-01-28 | 1995-10-17 | Compaq Computer Corp. | Boot strap circuit for power up control of power supplies |
| EP0665634B1 (en) | 1994-01-31 | 1997-05-14 | Siemens Aktiengesellschaft | Circuit arrangement with a field effect transistor |
| US5523673A (en) | 1994-03-04 | 1996-06-04 | Marelco Power Systems, Inc. | Electrically controllable inductor |
| JP3317045B2 (en) | 1994-10-14 | 2002-08-19 | 株式会社村田製作所 | Common mode choke coil |
| US6208535B1 (en) | 1994-10-31 | 2001-03-27 | Texas Instruments Incorporated | Resonant gate driver |
| JP3097485B2 (en) | 1995-02-03 | 2000-10-10 | 株式会社村田製作所 | choke coil |
| JP3450929B2 (en) | 1995-03-23 | 2003-09-29 | 株式会社リコー | Switching power supply |
| US5508903A (en) | 1995-04-21 | 1996-04-16 | Alexndrov; Felix | Interleaved DC to DC flyback converters with reduced current and voltage stresses |
| EP0741447A3 (en) | 1995-05-04 | 1997-04-16 | At & T Corp | Circuit and method for controlling a synchronous recifier converter |
| US5804943A (en) | 1995-05-12 | 1998-09-08 | Texas Instruments Incorporated | Resonant bilateral charging and discharging circuit |
| US5756375A (en) | 1995-06-14 | 1998-05-26 | Texas Instruments Incorporated | Semiconductor growth method with thickness control |
| US5783984A (en) | 1995-06-16 | 1998-07-21 | Hughes Electronics | Method and means for combining a transformer and inductor on a single core structure |
| US5742491A (en) | 1995-08-09 | 1998-04-21 | Lucent Technologies Inc. | Power converter adaptively driven |
| US5671131A (en) | 1995-08-25 | 1997-09-23 | Dell U.S.A. L.P. | Method and apparatus for detecting an isolated power switch |
| US5760671A (en) | 1995-09-15 | 1998-06-02 | Celestica Inc. | Transformer with dual flux path |
| US5663876A (en) | 1995-09-25 | 1997-09-02 | Lucent Technologies Inc. | Circuit and method for achieving zero ripple current in the output of a converter |
| US5910665A (en) | 1995-12-29 | 1999-06-08 | Texas Instruments Incorporated | Low capacitance power VFET method and device |
| US5784266A (en) | 1996-06-14 | 1998-07-21 | Virginia Power Technologies, Inc | Single magnetic low loss high frequency converter |
| US5736842A (en) | 1996-07-11 | 1998-04-07 | Delta Electronics, Inc. | Technique for reducing rectifier reverse-recovery-related losses in high-voltage high power converters |
| US5734564A (en) | 1996-07-26 | 1998-03-31 | Lucent Technologies Inc. | High-efficiency switching power converter |
| US5700703A (en) | 1996-08-06 | 1997-12-23 | Motorola | Method of fabricating buried control elements in semiconductor devices |
| TW340280B (en) | 1996-09-06 | 1998-09-11 | Toko Inc | Interface module |
| US5801522A (en) | 1996-09-26 | 1998-09-01 | Compaq Computer Corporation | Power limit circuit for computer system |
| JP3215911B2 (en) | 1996-11-01 | 2001-10-09 | 株式会社呉竹精昇堂 | Multi-color ink for Japanese paper written with a brush |
| JP3162639B2 (en) | 1996-11-22 | 2001-05-08 | 株式会社三社電機製作所 | Power supply |
| US6008519A (en) | 1996-12-16 | 1999-12-28 | Texas Instruments Incorporated | Vertical transistor and method |
| US5909110A (en) | 1996-12-17 | 1999-06-01 | Texas Insturments Incorporated | Integrated voltage regulator circuit with vertical transistor |
| US5889660A (en) | 1997-03-06 | 1999-03-30 | Eaton Corporation | Isolated power supply for indicator light |
| CA2232199C (en) | 1997-04-22 | 2000-02-22 | Kabushiki Kaisha Toshiba | Power converter with voltage drive switching element |
| US5956578A (en) | 1997-04-23 | 1999-09-21 | Motorola, Inc. | Method of fabricating vertical FET with Schottky diode |
| US6069799A (en) | 1997-05-14 | 2000-05-30 | Lucent Technologies Inc. | Self-synchronized drive circuit for a synchronous rectifier in a clamped-mode power converter |
| US5870299A (en) | 1997-05-28 | 1999-02-09 | Lucent Technologies Inc. | Method and apparatus for damping ringing in self-driven synchronous rectifiers |
| US6118351A (en) | 1997-06-10 | 2000-09-12 | Lucent Technologies Inc. | Micromagnetic device for power processing applications and method of manufacture therefor |
| US5815386A (en) | 1997-06-19 | 1998-09-29 | Factor One, Inc. | Snubber for zero current switched networks |
| US6011703A (en) | 1997-07-30 | 2000-01-04 | Lucent Technologies Inc. | Self-synchronized gate drive for power converter employing self-driven synchronous rectifier and method of operation thereof |
| DE69822284T2 (en) | 1997-08-04 | 2005-02-24 | Koninklijke Philips Electronics N.V. | POWER SUPPLY WITH SYNCRONIC EQUATION |
| FR2767612B1 (en) | 1997-08-21 | 2002-06-14 | Gec Alsthom Transport Sa | DIRECT CURRENT ENERGY CONVERSION DEVICE |
| US5886508A (en) | 1997-08-29 | 1999-03-23 | Computer Products, Inc. | Multiple output voltages from a cascaded buck converter topology |
| US5933338A (en) | 1997-10-14 | 1999-08-03 | Peco Ii, Inc. | Dual coupled current doubler rectification circuit |
| US5870296A (en) | 1997-10-14 | 1999-02-09 | Maxim Integrated Products, Inc. | Dual interleaved DC to DC switching circuits realized in an integrated circuit |
| US5907481A (en) | 1997-10-31 | 1999-05-25 | Telefonaktiebolaget Lm Ericsson | Double ended isolated D.C.--D.C. converter |
| KR100297340B1 (en) | 1997-11-18 | 2001-10-26 | 이형도 | Asymmetry flyback converter |
| US5999429A (en) | 1997-12-19 | 1999-12-07 | Dell Usa, L.P. | Bulk filter capacitor discharge in a switching power supply |
| US5982640A (en) | 1998-02-03 | 1999-11-09 | Philips Electronics North America Corporation | Arrangement for reducing the effects of capacitive coupling in a control circuit for a switched-mode power supply |
| US6046664A (en) | 1998-03-05 | 2000-04-04 | Century Manufacturing Company | Welding power supply transformer apparatus and method |
| US6181231B1 (en) | 1998-04-06 | 2001-01-30 | Silicon Graphics, Inc. | Diamond-based transformers and power convertors |
| US6060943A (en) | 1998-04-14 | 2000-05-09 | Nmb (Usa) Inc. | Circuit simulating a diode |
| US6469564B1 (en) | 1998-04-14 | 2002-10-22 | Minebea Co., Ltd. | Circuit simulating a diode |
| US6317021B1 (en) | 1998-05-18 | 2001-11-13 | Nmb (Usa) Inc. | Variable inductor |
| US5940287A (en) | 1998-07-14 | 1999-08-17 | Lucent Technologies Inc. | Controller for a synchronous rectifier and power converter employing the same |
| US6156611A (en) | 1998-07-20 | 2000-12-05 | Motorola, Inc. | Method of fabricating vertical FET with sidewall gate electrode |
| US6084792A (en) | 1998-08-21 | 2000-07-04 | Vpt, Inc. | Power converter with circuits for providing gate driving |
| JP2000068132A (en) | 1998-08-26 | 2000-03-03 | Toko Inc | Inverter transformer |
| US6309918B1 (en) | 1998-09-21 | 2001-10-30 | Motorola, Inc. | Manufacturable GaAs VFET process |
| EP0989662B1 (en) | 1998-09-23 | 2003-05-02 | STMicroelectronics S.r.l. | Completely integrated switch-on control-loop of a high voltage power transistor of a quasi resonant flyback converter |
| US6091616A (en) | 1998-10-21 | 2000-07-18 | Lucent Technologies Inc. | Drive compensation circuit for synchronous rectifier and method of operating the same |
| KR100293979B1 (en) | 1998-11-10 | 2001-09-17 | 김덕중 | Switching Mode Power Supply |
| JP2000152617A (en) | 1998-11-10 | 2000-05-30 | Sony Corp | Switching power supply |
| US6144187A (en) | 1998-11-12 | 2000-11-07 | Fairchild Semiconductor Corporation | Power measurement for adaptive battery charger |
| US6963178B1 (en) | 1998-12-07 | 2005-11-08 | Systel Development And Industries Ltd. | Apparatus for controlling operation of gas discharge devices |
| US6069798A (en) | 1999-01-14 | 2000-05-30 | Lucent Technologies Inc. | Asymmetrical power converter and method of operation thereof |
| JP2000260639A (en) | 1999-03-11 | 2000-09-22 | Murata Mfg Co Ltd | Coil device and switching power supply device |
| US6295217B1 (en) | 1999-03-26 | 2001-09-25 | Sarnoff Corporation | Low power dissipation power supply and controller |
| US6498367B1 (en) | 1999-04-01 | 2002-12-24 | Apd Semiconductor, Inc. | Discrete integrated circuit rectifier device |
| US6147886A (en) | 1999-05-15 | 2000-11-14 | Technical Witts, Inc. | Dual opposed interleaved coupled inductor soft switching converters |
| US6212084B1 (en) | 1999-05-17 | 2001-04-03 | Page Aerospace Limited | Active rectifier |
| JP3829534B2 (en) | 1999-05-26 | 2006-10-04 | 松下電工株式会社 | Discharge lamp lighting device |
| US6323090B1 (en) | 1999-06-09 | 2001-11-27 | Ixys Corporation | Semiconductor device with trenched substrate and method |
| US6094038A (en) | 1999-06-28 | 2000-07-25 | Semtech Corporation | Buck converter with inductive turn ratio optimization |
| US6160374A (en) | 1999-08-02 | 2000-12-12 | General Motors Corporation | Power-factor-corrected single-stage inductive charger |
| US7021971B2 (en) | 2003-09-11 | 2006-04-04 | Super Talent Electronics, Inc. | Dual-personality extended-USB plug and receptacle with PCI-Express or Serial-At-Attachment extensions |
| US7393247B1 (en) | 2005-03-08 | 2008-07-01 | Super Talent Electronics, Inc. | Architectures for external SATA-based flash memory devices |
| US6320490B1 (en) | 1999-08-13 | 2001-11-20 | Space Systems/Loral, Inc. | Integrated planar transformer and inductor assembly |
| US6163466A (en) | 1999-09-16 | 2000-12-19 | Lucent Technologies, Inc. | Asymmetrical DC/DC converter having output current doubler |
| US6325035B1 (en) | 1999-09-30 | 2001-12-04 | Caterpillar Inc. | Method and apparatus for starting an engine using capacitor supplied voltage |
| US6215290B1 (en) | 1999-11-15 | 2001-04-10 | Semtech Corporation | Multi-phase and multi-module power supplies with balanced current between phases and modules |
| US6445598B1 (en) | 1999-12-09 | 2002-09-03 | Sanken Electric Co., Ltd. | Dc-dc converter |
| US6539299B2 (en) | 2000-02-18 | 2003-03-25 | Optimum Power Technology | Apparatus and method for calibrating an engine management system |
| US6351396B1 (en) | 2000-03-04 | 2002-02-26 | Mark Elliott Jacobs | Method and apparatus for dynamically altering operation of a converter device to improve conversion efficiency |
| TW465168B (en) | 2000-03-10 | 2001-11-21 | Ericsson Telefon Ab L M | Synchronous rectification in a flyback converter |
| SE517685C2 (en) | 2000-03-24 | 2002-07-02 | Ericsson Telefon Ab L M | Method and apparatus for controlling a synchronous rectifier in a DC converter |
| US6400579B2 (en) | 2000-03-24 | 2002-06-04 | Slobodan Cuk | Lossless switching DC to DC converter with DC transformer |
| DE60035100T2 (en) | 2000-04-10 | 2008-01-31 | Stmicroelectronics S.R.L., Agrate Brianza | Method and device for digitally controlling the turn-off time of synchronous rectifiers for switching power supplies with isolated topologies |
| WO2001082460A1 (en) | 2000-04-21 | 2001-11-01 | Fujitsu Limited | Switching dc-dc converter |
| US6188586B1 (en) | 2000-04-21 | 2001-02-13 | Lucent Technologies Inc. | Asymmetrical half-bridge power converter having reduced input ripple and method of manufacturing the same |
| US6348848B1 (en) | 2000-05-04 | 2002-02-19 | Edward Herbert | Transformer having fractional turn windings |
| US6304460B1 (en) | 2000-05-05 | 2001-10-16 | Slobodan Cuk | Switching DC-to-DC converter utilizing a soft switching technique |
| WO2001086794A1 (en) | 2000-05-10 | 2001-11-15 | Sony Corporation | Resonant switching power supply circuit with voltage doubler output |
| US20020057080A1 (en) | 2000-06-02 | 2002-05-16 | Iwatt | Optimized digital regulation of switching power supply |
| US6344986B1 (en) | 2000-06-15 | 2002-02-05 | Astec International Limited | Topology and control method for power factor correction |
| US6668296B1 (en) | 2000-06-30 | 2003-12-23 | Hewlett-Packard Development Company, L.P. | Powering a notebook across a USB interface |
| US6218891B1 (en) | 2000-07-28 | 2001-04-17 | Lucent Technologies Inc. | Integrated circuit including a driver for a metal-semiconductor field-effect transistor |
| US6392902B1 (en) | 2000-08-31 | 2002-05-21 | Delta Electronics, Inc. | Soft-switched full-bridge converter |
| JP4395881B2 (en) | 2000-09-06 | 2010-01-13 | Ｔｄｋラムダ株式会社 | Synchronous rectifier circuit for switching power supply |
| US6373734B1 (en) | 2000-09-15 | 2002-04-16 | Artesyn Technologies, Inc. | Power factor correction control circuit and power supply including same |
| US6559689B1 (en) | 2000-10-02 | 2003-05-06 | Allegro Microsystems, Inc. | Circuit providing a control voltage to a switch and including a capacitor |
| ATE325462T1 (en) | 2000-11-01 | 2006-06-15 | Koninkl Philips Electronics Nv | SWITCHING POWER SUPPLY |
| US6262564B1 (en) | 2000-11-10 | 2001-07-17 | Lucent Technologies Inc. | Driver for a controllable switch in a power converter |
| US6570268B1 (en) | 2000-11-20 | 2003-05-27 | Artesyn Technologies, Inc. | Synchronous rectifier drive circuit and power supply including same |
| US6831847B2 (en) | 2000-11-20 | 2004-12-14 | Artesyn Technologies, Inc. | Synchronous rectifier drive circuit and power supply including same |
| US6414578B1 (en) | 2000-12-18 | 2002-07-02 | Ascom Energy Systems Ag | Method and apparatus for transmitting a signal through a power magnetic structure |
| US6396718B1 (en) | 2000-12-19 | 2002-05-28 | Semiconductor Components Industries Llc | Switch mode power supply using transformer flux sensing for duty cycle control |
| JP2002199718A (en) | 2000-12-22 | 2002-07-12 | Sony Corp | Resonance-type switching power supply device |
| US6525603B1 (en) | 2001-01-05 | 2003-02-25 | Remec, Inc. | Feedforward amplifier linearization adapting off modulation |
| US6388898B1 (en) | 2001-01-22 | 2002-05-14 | Delta Electronics, Inc. | Dc/dc power processor with distributed rectifier stage |
| US6580627B2 (en) | 2001-01-29 | 2003-06-17 | International Rectifier Corporation | Voltage sensing with high and low side signals for deadtime compensation and shutdown for short circuit protection |
| WO2002061926A2 (en) | 2001-02-01 | 2002-08-08 | Di/Dt, Inc. | Isolated drive circuitry used in switch-mode power converters |
| US6504321B2 (en) | 2001-02-06 | 2003-01-07 | Koninklijke Philips Electronics N.V. | Universal hardware/software feedback control for high-frequency signals |
| US6466461B2 (en) | 2001-02-09 | 2002-10-15 | Netpower Technologies, Inc. | Method and circuit for reducing voltage level variation in a bias voltage in a power converter |
| US6674658B2 (en) | 2001-02-09 | 2004-01-06 | Netpower Technologies, Inc. | Power converter including circuits for improved operational control of synchronous rectifiers therein |
| JP2002244069A (en) | 2001-02-19 | 2002-08-28 | Nec Corp | Laser scanning optical device and laser scanning method using this optical device |
| US6784644B2 (en) | 2001-02-22 | 2004-08-31 | Virginia Tech Intellectual Properties, Inc. | Multiphase clamp coupled-buck converter and magnetic integration |
| JP3872331B2 (en) | 2001-03-07 | 2007-01-24 | 富士通株式会社 | DC-DC converter and power supply circuit |
| DE10112820A1 (en) | 2001-03-16 | 2002-10-02 | Bosch Gmbh Robert | Measuring currents in multi-phase converters involves performing a current or voltage measurements on pairs of half bridges combined to form current measurement units |
| US6362986B1 (en) | 2001-03-22 | 2002-03-26 | Volterra, Inc. | Voltage converter with coupled inductive windings, and associated methods |
| US6545453B2 (en) | 2001-04-03 | 2003-04-08 | Abb Inc. | Systems and methods for providing voltage regulation externally to a power transformer |
| JP4122721B2 (en) | 2001-04-09 | 2008-07-23 | サンケン電気株式会社 | Switching power supply |
| DE10119106A1 (en) | 2001-04-19 | 2002-10-24 | Philips Corp Intellectual Pty | Transformer for switch-mode power supply, has three cores formed as separate components and with air gaps between |
| US6512352B2 (en) | 2001-06-07 | 2003-01-28 | Koninklijke Philips Electronics N.V. | Active clamp step-down converter with power switch voltage clamping function |
| US6696910B2 (en) | 2001-07-12 | 2004-02-24 | Custom One Design, Inc. | Planar inductors and method of manufacturing thereof |
| FI118026B (en) | 2001-08-07 | 2007-05-31 | Salcomp Oy | Use of the rectified voltage on the primary-side switching power source control switch |
| JP3661666B2 (en) | 2001-08-10 | 2005-06-15 | 株式会社村田製作所 | Isolated switching power supply |
| JP3571012B2 (en) | 2001-08-17 | 2004-09-29 | Ｔｄｋ株式会社 | Switching power supply |
| US6501193B1 (en) | 2001-09-07 | 2002-12-31 | Power-One, Inc. | Power converter having regulated dual outputs |
| US6563725B2 (en) | 2001-10-03 | 2003-05-13 | Bruce W. Carsten | Apparatus and method for control and driving BJT used as synchronous rectifier |
| US6597592B2 (en) | 2001-10-03 | 2003-07-22 | Bruce W. Carsten | Apparatus and method for turning off BJT used as controlled rectifier |
| WO2003032477A2 (en) | 2001-10-12 | 2003-04-17 | Northeastern University | Integrated magnetics for a dc-dc converter with flexible output inductor |
| US6548992B1 (en) | 2001-10-18 | 2003-04-15 | Innoveta Technologies, Inc. | Integrated power supply protection circuit |
| US6552917B1 (en) | 2001-11-05 | 2003-04-22 | Koninklijke Philips Electronics N.V. | System and method for regulating multiple outputs in a DC-DC converter |
| US20040148047A1 (en) | 2001-12-18 | 2004-07-29 | Dismukes John P | Hierarchical methodology for productivity measurement and improvement of productions systems |
| US6731486B2 (en) | 2001-12-19 | 2004-05-04 | Fairchild Semiconductor Corporation | Output-powered over-voltage protection circuit |
| US6636025B1 (en) * | 2002-01-09 | 2003-10-21 | Asic Advantage, Inc. | Controller for switch mode power supply |
| JP3789364B2 (en) | 2002-01-24 | 2006-06-21 | Ｔｄｋ株式会社 | Two-stage DC-DC converter |
| US6975098B2 (en) * | 2002-01-31 | 2005-12-13 | Vlt, Inc. | Factorized power architecture with point of load sine amplitude converters |
| US6483724B1 (en) | 2002-02-15 | 2002-11-19 | Valere Power, Inc. | DC/DC ZVS full bridge converter power supply method and apparatus |
| US6549436B1 (en) | 2002-02-21 | 2003-04-15 | Innovative Technology Licensing Llc | Integrated magnetic converter circuit and method with improved filtering |
| US20040034555A1 (en) | 2002-03-18 | 2004-02-19 | Dismukes John P. | Hierarchical methodology for productivity measurement and improvement of complex production systems |
| EP1490958B1 (en) | 2002-03-29 | 2011-11-02 | DET International Holding Limited | Method and apparatus for controlling a synchronous rectifier |
| TW595077B (en) | 2002-04-03 | 2004-06-21 | Int Rectifier Corp | Synchronous buck converter improvements |
| US7295094B2 (en) | 2002-04-12 | 2007-11-13 | Det International Holding Limited | Low profile magnetic element |
| US7046523B2 (en) | 2002-04-18 | 2006-05-16 | Coldwatt, Inc. | Core structure and interleaved DC—DC converter topology |
| US7280026B2 (en) | 2002-04-18 | 2007-10-09 | Coldwatt, Inc. | Extended E matrix integrated magnetics (MIM) core |
| US6873237B2 (en) | 2002-04-18 | 2005-03-29 | Innovative Technology Licensing, Llc | Core structure |
| CN1452308A (en) | 2002-04-18 | 2003-10-29 | 姜涛 | Environment protection switch power supply |
| SE0201432D0 (en) | 2002-04-29 | 2002-05-13 | Emerson Energy Systems Ab | A Power supply system and apparatus |
| US6614206B1 (en) | 2002-05-23 | 2003-09-02 | Palm, Inc. | Universal USB charging accessory |
| US6751106B2 (en) | 2002-07-25 | 2004-06-15 | General Electric Company | Cross current control for power converter systems and integrated magnetic choke assembly |
| US6661276B1 (en) | 2002-07-29 | 2003-12-09 | Lovoltech Inc. | MOSFET driver matching circuit for an enhancement mode JFET |
| US6765810B2 (en) | 2002-08-02 | 2004-07-20 | Artesyn Technologies, Inc. | Full-wave coupled inductor power converter having synchronous rectifiers and two input switches that are simultaneously off for a time period of each switching cycle |
| US6813170B2 (en) | 2002-08-19 | 2004-11-02 | Semtech Corporation | Multiple output power supply having soft start protection for load over-current or short circuit conditions |
| DE10238824A1 (en) | 2002-08-23 | 2004-03-11 | Forschungszentrum Jülich GmbH | Method and device for the rapid tomographic measurement of the electrical conductivity distribution in a sample |
| US6944033B1 (en) | 2002-11-08 | 2005-09-13 | Va Tech Intellectual Properties | Multi-phase interleaving isolated DC/DC converter |
| KR100525393B1 (en) | 2002-11-26 | 2005-11-02 | 엘지전자 주식회사 | A Power Supply |
| US6867678B2 (en) | 2003-01-28 | 2005-03-15 | Entrust Power Co., Ltd. | Transformer structure |
| US6741099B1 (en) | 2003-01-31 | 2004-05-25 | Power-One Limited | Transistor driver circuit |
| EP1443335B1 (en) | 2003-01-31 | 2006-09-06 | Agilent Technologies, Inc. - a Delaware corporation - | Sensor apparatus, measuring system and method of calibration |
| JP3705495B2 (en) | 2003-02-03 | 2005-10-12 | Ｓｍｋ株式会社 | Constant current output control method and constant current output control device for switching power supply circuit |
| US6882548B1 (en) | 2003-02-24 | 2005-04-19 | Tyco Electronics Power Systems, Inc. | Auxiliary active clamp circuit, a method of clamping a voltage of a rectifier switch and a power converter employing the circuit or method |
| JP4289904B2 (en) | 2003-02-27 | 2009-07-01 | キヤノン株式会社 | AC-DC converter |
| DE10310361B4 (en) | 2003-03-10 | 2005-04-28 | Friwo Mobile Power Gmbh | Control circuit for switching power supply |
| TW200421103A (en) | 2003-04-10 | 2004-10-16 | Benq Corp | Connecting wire for universal serial bus interface |
| US7583555B2 (en) | 2003-04-11 | 2009-09-01 | Qualcomm Incorporated | Robust and Efficient dynamic voltage scaling for portable devices |
| US20040217794A1 (en) | 2003-04-30 | 2004-11-04 | Mark Strysko | Propagation delay adjustment circuit |
| US6862194B2 (en) | 2003-06-18 | 2005-03-01 | System General Corp. | Flyback power converter having a constant voltage and a constant current output under primary-side PWM control |
| US6856149B2 (en) | 2003-06-19 | 2005-02-15 | Niko Semiconductor Co., Ltd. | Current detecting circuit AC/DC flyback switching power supply |
| US6839247B1 (en) | 2003-07-10 | 2005-01-04 | System General Corp. | PFC-PWM controller having a power saving means |
| US7095638B2 (en) | 2003-09-03 | 2006-08-22 | Tyco Electronics Power Systems, Inc. | Controller for complementary switches of a power converter and method of operation thereof |
| US6906934B2 (en) | 2003-09-04 | 2005-06-14 | System General Corp. | Integrated start-up circuit with reduced power consumption |
| US6992524B2 (en) | 2003-09-08 | 2006-01-31 | Skyworks Solutions, Inc. | Quiescent current control circuit for high-power amplifiers |
| US7009486B1 (en) | 2003-09-18 | 2006-03-07 | Keithley Instruments, Inc. | Low noise power transformer |
| AT501424B1 (en) | 2003-10-31 | 2008-08-15 | Fronius Int Gmbh | METHOD FOR AN INVERTER AND INVERTER, ESPECIALLY SOLAR CHANGEARK |
| DE10352509A1 (en) | 2003-11-11 | 2005-06-02 | Robert Bosch Gmbh | Method for operating a pulse width modulation controlled electric motor |
| US7489225B2 (en) | 2003-11-17 | 2009-02-10 | Pulse Engineering, Inc. | Precision inductive devices and methods |
| US7148669B2 (en) | 2004-02-02 | 2006-12-12 | The Regents Of The University Of Colorado, A Body Corporate | Predictive digital current controllers for switching power converters |
| US7034586B2 (en) | 2004-03-05 | 2006-04-25 | Intersil Americas Inc. | Startup circuit for converter with pre-biased load |
| US6982887B2 (en) | 2004-04-26 | 2006-01-03 | Astec International Limited | DC-DC converter with coupled-inductors current-doubler |
| US7431862B2 (en) | 2004-04-30 | 2008-10-07 | Coldwatt, Inc. | Synthesis of magnetic, dielectric or phosphorescent NANO composites |
| TWI278875B (en) | 2004-04-30 | 2007-04-11 | Hon Hai Prec Ind Co Ltd | DC transformer with output inductor integrated on the magnetic core thereof and a DC/DC converter employing the same |
| US7446512B2 (en) | 2004-05-07 | 2008-11-04 | Matsushita Electric Industrial Co., Ltd. | Resonant switching power supply device |
| FR2870403B1 (en) | 2004-05-11 | 2007-09-14 | Thales Sa | AC / DC CONVERTER WITH LOW ANHARMONIC CURRENTS |
| US20050281058A1 (en) | 2004-06-21 | 2005-12-22 | Issa Batarseh | Dynamic optimization of efficiency using dead time and FET drive control |
| US7136293B2 (en) | 2004-06-24 | 2006-11-14 | Petkov Roumen D | Full wave series resonant type DC to DC power converter with integrated magnetics |
| US7098640B2 (en) | 2004-07-06 | 2006-08-29 | International Rectifier Corporation | Method and apparatus for intelligently setting dead time |
| CA2484957A1 (en) | 2004-07-07 | 2006-01-07 | Veris Industries, Llc | Split core sensing transformer |
| JP4064377B2 (en) | 2004-07-20 | 2008-03-19 | 松下電器産業株式会社 | Switching power supply device and semiconductor device for switching power supply |
| US6977824B1 (en) | 2004-08-09 | 2005-12-20 | System General Corp. | Control circuit for controlling output current at the primary side of a power converter |
| US7170268B2 (en) | 2004-08-09 | 2007-01-30 | Lite-On Technology Corporation | DC to DC converter with high frequency zigzag transformer |
| US7016204B2 (en) | 2004-08-12 | 2006-03-21 | System General Corp. | Close-loop PWM controller for primary-side controlled power converters |
| US7012414B1 (en) | 2004-08-19 | 2006-03-14 | Coldwatt, Inc. | Vertically packaged switched-mode power converter |
| US7427910B2 (en) | 2004-08-19 | 2008-09-23 | Coldwatt, Inc. | Winding structure for efficient switch-mode power converters |
| US6980077B1 (en) | 2004-08-19 | 2005-12-27 | Coldwatt, Inc. | Composite magnetic core for switch-mode power converters |
| US7321283B2 (en) | 2004-08-19 | 2008-01-22 | Coldwatt, Inc. | Vertical winding structures for planar magnetic switched-mode power converters |
| US7362593B2 (en) | 2004-09-16 | 2008-04-22 | System General Corp. | Switching control circuit having off-time modulation to improve efficiency of primary-side controlled power supply |
| US7362592B2 (en) | 2004-09-16 | 2008-04-22 | System General Corp. | Switching control circuit for primary-side controlled power converters |
| US7348612B2 (en) | 2004-10-29 | 2008-03-25 | Cree, Inc. | Metal-semiconductor field effect transistors (MESFETs) having drains coupled to the substrate and methods of fabricating the same |
| US7075799B2 (en) | 2004-11-23 | 2006-07-11 | Power-One, Inc. | Self-driven synchronous rectifier circuit |
| GB0500183D0 (en) | 2005-01-07 | 2005-02-16 | Koninkl Philips Electronics Nv | Switched mode power supply |
| JP2006211744A (en) | 2005-01-25 | 2006-08-10 | Sony Corp | Switching power supply circuit |
| US7417875B2 (en) | 2005-02-08 | 2008-08-26 | Coldwatt, Inc. | Power converter employing integrated magnetics with a current multiplier rectifier and method of operating the same |
| US7176662B2 (en) | 2005-02-23 | 2007-02-13 | Coldwatt, Inc. | Power converter employing a tapped inductor and integrated magnetics and method of operating the same |
| US7385375B2 (en) | 2005-02-23 | 2008-06-10 | Coldwatt, Inc. | Control circuit for a depletion mode switch and method of operating the same |
| US7876191B2 (en) | 2005-02-23 | 2011-01-25 | Flextronics International Usa, Inc. | Power converter employing a tapped inductor and integrated magnetics and method of operating the same |
| US7076360B1 (en) | 2005-03-15 | 2006-07-11 | Thomas Tsoi Hei Ma | Auto-ignition timing control and calibration method |
| US20070241721A1 (en) | 2005-03-21 | 2007-10-18 | Eveready Battery Company, Inc. | Direct current power supply |
| US7439557B2 (en) | 2005-03-29 | 2008-10-21 | Coldwatt, Inc. | Semiconductor device having a lateral channel and contacts on opposing surfaces thereof |
| US7439556B2 (en) | 2005-03-29 | 2008-10-21 | Coldwatt, Inc. | Substrate driven field-effect transistor |
| JP4219909B2 (en) | 2005-03-31 | 2009-02-04 | Ｔｄｋ株式会社 | Filter circuit and power supply device |
| US7715217B2 (en) | 2005-03-31 | 2010-05-11 | Toyota Jidosha Kabushiki Kaisha | Voltage conversion device and vehicle |
| US7339801B2 (en) | 2005-04-08 | 2008-03-04 | Sony Corporation | Switching power supply circuit |
| US20060237968A1 (en) | 2005-04-20 | 2006-10-26 | Rockwell Scientific Licensing, Llc | High efficiency power converter for energy harvesting devices |
| US7339208B2 (en) | 2005-05-13 | 2008-03-04 | Coldwatt, Inc. | Semiconductor device having multiple lateral channels and method of forming the same |
| US7386404B2 (en) | 2005-05-27 | 2008-06-10 | Savi Technology, Inc. | Method and apparatus for monitoring battery discharge state |
| FR2888396B1 (en) | 2005-07-05 | 2007-09-21 | Centre Nat Rech Scient | METHOD AND DEVICE FOR SUPPLYING A MAGNETIC COUPLER |
| EP1900087A2 (en) | 2005-07-06 | 2008-03-19 | Cambridge Semiconductor Limited | Switch mode power supply control systems |
| US20070007942A1 (en) | 2005-07-08 | 2007-01-11 | Microchip Technology Incorporated | Automatic non-linear phase response calibration and compensation for a power measurement device |
| TWM280051U (en) | 2005-07-08 | 2005-11-01 | Pchome Online Inc | Internet protocol phone having female stereo connector |
| US7453709B2 (en) | 2005-07-08 | 2008-11-18 | Power Integrations, Inc. | Method and apparatus for increasing the power capability of a power supply |
| JP4573197B2 (en) | 2005-07-21 | 2010-11-04 | Ｓｍｃ株式会社 | Solenoid valve drive control device |
| US7285807B2 (en) | 2005-08-25 | 2007-10-23 | Coldwatt, Inc. | Semiconductor device having substrate-driven field-effect transistor and Schottky diode and method of forming the same |
| US7061358B1 (en) | 2005-09-12 | 2006-06-13 | Sen-Tai Yang | Structure of inductance core and wire frame |
| US7269038B2 (en) | 2005-09-12 | 2007-09-11 | Fairchild Semiconductor Corporation | Vrms and rectified current sense full-bridge synchronous-rectification integrated with PFC |
| JP4849972B2 (en) | 2005-09-15 | 2012-01-11 | パナソニック株式会社 | Communication device, communication system, image acquisition device, moving image acquisition device, and setting method thereof |
| US7462891B2 (en) | 2005-09-27 | 2008-12-09 | Coldwatt, Inc. | Semiconductor device having an interconnect with sloped walls and method of forming the same |
| US7558539B2 (en) | 2005-09-30 | 2009-07-07 | Freescale Semiconductor, Inc. | Power control feedback loop for adjusting a magnitude of an output signal |
| US7375994B2 (en) * | 2005-10-11 | 2008-05-20 | Texas Instruments Incorporated | Highly efficient isolated AC/DC power conversion technique |
| US7099163B1 (en) | 2005-11-14 | 2006-08-29 | Bcd Semiconductor Manufacturing Limited | PWM controller with constant output power limit for a power supply |
| CN100525044C (en) | 2005-11-28 | 2009-08-05 | 伊博电源（杭州）有限公司 | Self driving circuit for three winding reverse exciting converter synchronous rectifier |
| JP4986863B2 (en) | 2005-12-14 | 2012-07-25 | シャープ株式会社 | Discharge lamp lighting device |
| US20070139984A1 (en) * | 2005-12-20 | 2007-06-21 | Yu-Kang Lo | Resonant conversion control method and device with a very low standby power consumption |
| KR101017017B1 (en) | 2006-01-10 | 2011-02-23 | 삼성전자주식회사 | DC to DC Converter |
| CN2904469Y (en) | 2006-01-13 | 2007-05-23 | 北京动力源科技股份有限公司 | Driving circuit for synchronous rectifying |
| TW200740089A (en) | 2006-03-07 | 2007-10-16 | Rohm Co Ltd | Capacitor charging apparatus |
| US20070222463A1 (en) | 2006-03-23 | 2007-09-27 | Qahouq Jaber A | Power conversion efficiency management |
| JP2007281224A (en) | 2006-04-07 | 2007-10-25 | Sony Corp | Transformer |
| WO2007135453A2 (en) | 2006-05-23 | 2007-11-29 | Cambridge Semiconductor Limited | Switch mode power supply controllers |
| GB2438465B (en) | 2006-05-23 | 2008-05-21 | Cambridge Semiconductor Ltd | Switch mode power supply controllers |
| GB2438464A (en) | 2006-05-23 | 2007-11-28 | Cambridge Semiconductor Ltd | Regulating the output of a switch mode power supply |
| US7663183B2 (en) | 2006-06-21 | 2010-02-16 | Flextronics International Usa, Inc. | Vertical field-effect transistor and method of forming the same |
| US7541640B2 (en) | 2006-06-21 | 2009-06-02 | Flextronics International Usa, Inc. | Vertical field-effect transistor and method of forming the same |
| US8415737B2 (en) | 2006-06-21 | 2013-04-09 | Flextronics International Usa, Inc. | Semiconductor device with a pillar region and method of forming the same |
| US7746041B2 (en) | 2006-06-27 | 2010-06-29 | Virginia Tech Intellectual Properties, Inc. | Non-isolated bus converters with voltage divider topology |
| CN101106850A (en) | 2006-07-12 | 2008-01-16 | 鸿富锦精密工业（深圳）有限公司 | LED drive circuit |
| US20080012423A1 (en) | 2006-07-13 | 2008-01-17 | Emile Mimran | USB connector devices for charging |
| US7471523B2 (en) | 2006-08-15 | 2008-12-30 | System General Corp. | Method and apparatus for detecting demagnetizing time of magnetic device |
| US8125205B2 (en) | 2006-08-31 | 2012-02-28 | Flextronics International Usa, Inc. | Power converter employing regulators with a coupled inductor |
| JP2008092635A (en) | 2006-09-29 | 2008-04-17 | Ricoh Co Ltd | Synchronous rectifying type switching regulator, control circuit of synchronous rectifying type switching regulator, and operation control method of synchronous rectifying type switching regulator |
| JP4934403B2 (en) | 2006-10-31 | 2012-05-16 | ローム株式会社 | Power control circuit |
| US7675759B2 (en) | 2006-12-01 | 2010-03-09 | Flextronics International Usa, Inc. | Power system with power converters having an adaptive controller |
| US7889517B2 (en) | 2006-12-01 | 2011-02-15 | Flextronics International Usa, Inc. | Power system with power converters having an adaptive controller |
| US7675758B2 (en) | 2006-12-01 | 2010-03-09 | Flextronics International Usa, Inc. | Power converter with an adaptive controller and method of operating the same |
| US7667986B2 (en) | 2006-12-01 | 2010-02-23 | Flextronics International Usa, Inc. | Power system with power converters having an adaptive controller |
| US20080137381A1 (en) | 2006-12-12 | 2008-06-12 | Matthew Beasley | Generation of auxiliary voltages in a ballast |
| US7940035B2 (en) | 2007-01-19 | 2011-05-10 | System General Corp. | Control circuit having an impedance modulation controlling power converter for saving power |
| US7848117B2 (en) * | 2007-01-22 | 2010-12-07 | Power Integrations, Inc. | Control arrangement for a resonant mode power converter |
| US7778051B2 (en) | 2007-03-14 | 2010-08-17 | System General Corp. | Output current control circuit for power converter with a changeable switching frequency |
| US7468649B2 (en) | 2007-03-14 | 2008-12-23 | Flextronics International Usa, Inc. | Isolated power converter |
| JP4608519B2 (en) * | 2007-05-11 | 2011-01-12 | 株式会社ナナオ | Switching power supply |
| US8278889B2 (en) | 2007-05-30 | 2012-10-02 | Texas Instruments Incorporated | Adaptive rectifier architecture and method for switching regulators |
| US20080316779A1 (en) | 2007-06-19 | 2008-12-25 | Chandrasekaran Jayaraman | System and method for estimating input power for a power processing circuit |
| JP5138287B2 (en) | 2007-06-27 | 2013-02-06 | 三菱電機株式会社 | Gate drive device |
| US7787264B2 (en) | 2007-07-25 | 2010-08-31 | System General Corp. | Apparatus to provide synchronous rectifying circuit for flyback power converters |
| US7788531B2 (en) | 2007-07-31 | 2010-08-31 | Cove Distribution, Inc. | Generation of backing electric current on the basis of a combination of components |
| TWI358187B (en) | 2007-08-16 | 2012-02-11 | Delta Electronics Inc | Magnetic integrated circuit for multiphase interle |
| US7626370B1 (en) | 2007-09-21 | 2009-12-01 | National Semiconductor Corporation | Apparatus and method for hysteretic boost DC-DC converter |
| WO2009039684A1 (en) | 2007-09-28 | 2009-04-02 | Iwatt Inc. | Dynamic drive of switching transistor of switching power converter |
| JP4954290B2 (en) | 2007-10-02 | 2012-06-13 | 三菱電機株式会社 | Gate drive circuit |
| CN100511949C (en) | 2007-10-17 | 2009-07-08 | 上海优昌电源科技有限公司 | Capacitance decompression AC-DC switch power source |
| TWI380565B (en) | 2007-10-26 | 2012-12-21 | Niko Semiconductor Co Ltd | Three terminal integrated synchronous rectifier and flyback synchronous rectifying circuit |
| JP5230181B2 (en) | 2007-12-07 | 2013-07-10 | パナソニック株式会社 | Energy transfer device and semiconductor device for energy transfer control |
| CN101489335B (en) | 2008-01-18 | 2012-12-19 | 尼克森微电子股份有限公司 | LED driving circuit and secondary side controller thereof |
| US20090257250A1 (en) | 2008-04-15 | 2009-10-15 | Green Mark Technology Inc. | Synchronous rectifier dc/dc converters using a controlled-coupling sense winding |
| US8749209B2 (en) | 2008-05-05 | 2014-06-10 | Infineon Technologies Austria Ag | System and method for providing adaptive dead times |
| TWI390378B (en) | 2008-05-14 | 2013-03-21 | Richtek Technology Corp | Control circuit and method of Chi - back power converter |
| US8693213B2 (en) | 2008-05-21 | 2014-04-08 | Flextronics Ap, Llc | Resonant power factor correction converter |
| US7965528B2 (en) | 2008-06-13 | 2011-06-21 | System General Corporation | Method and apparatus for measuring the switching current of power converter operated at continuous current mode |
| US20090315530A1 (en) | 2008-06-18 | 2009-12-24 | Shailendra Kumar Baranwal | Pulse controlled soft start scheme for buck converter |
| CN201252294Y (en) | 2008-07-29 | 2009-06-03 | 黄金富 | SUPER-USB connecting device provided with load power supply terminal |
| US8184456B1 (en) * | 2008-08-26 | 2012-05-22 | International Rectifier Corporation | Adaptive power converter and related circuitry |
| US7817447B2 (en) * | 2008-08-30 | 2010-10-19 | Active-Semi, Inc. | Accurate voltage regulation of a primary-side regulation power supply in continuous conduction mode operation |
| CN102217181B (en) | 2008-11-14 | 2014-09-03 | 伟创力国际美国公司 | Driver for a synchronous rectifier and power converter employing the same |
| US8330389B2 (en) * | 2008-12-31 | 2012-12-11 | Stmicroelectronics S.R.L. | Switching power supply system for optical sources or a load requiring a controlled supply current |
| US8179699B2 (en) | 2008-12-31 | 2012-05-15 | Stmicroelectronics S.R.L. | Method for controlling a switching regulator and related switching regulator |
| US8644041B2 (en) | 2009-01-14 | 2014-02-04 | Nxp B.V. | PFC with high efficiency at low load |
| CN102342008B (en) | 2009-01-19 | 2016-08-03 | 伟创力国际美国公司 | Controller for power converter |
| WO2010083511A1 (en) | 2009-01-19 | 2010-07-22 | Flextronics International Usa, Inc. | Controller for a power converter |
| CN101826796B (en) | 2009-03-02 | 2015-10-21 | 昂宝电子（上海）有限公司 | Utilize quasi resonator system and the method for Multi-model control |
| US9019061B2 (en) | 2009-03-31 | 2015-04-28 | Power Systems Technologies, Ltd. | Magnetic device formed with U-shaped core pieces and power converter employing the same |
| US8643222B2 (en) | 2009-06-17 | 2014-02-04 | Power Systems Technologies Ltd | Power adapter employing a power reducer |
| US9077248B2 (en) | 2009-06-17 | 2015-07-07 | Power Systems Technologies Ltd | Start-up circuit for a power adapter |
| US8514593B2 (en) | 2009-06-17 | 2013-08-20 | Power Systems Technologies, Ltd. | Power converter employing a variable switching frequency and a magnetic device with a non-uniform gap |
| TWI393337B (en) * | 2009-07-31 | 2013-04-11 | Delta Electronics Inc | Two stage switching power conversion circuit |
| US8638578B2 (en) | 2009-08-14 | 2014-01-28 | Power System Technologies, Ltd. | Power converter including a charge pump employable in a power adapter |
| US8373400B2 (en) | 2009-09-15 | 2013-02-12 | Intersil Americas Inc. | System and method for smoothing mode transitions in a voltage supply |
| CN101668369A (en) * | 2009-10-01 | 2010-03-10 | 英飞特电子（杭州）有限公司 | High-efficiency constant-current LED driver |
| TWI411212B (en) | 2009-10-20 | 2013-10-01 | Alpha & Omega Semiconductor | High efficiency energy control method in single inductor converter |
| KR101031217B1 (en) * | 2009-10-21 | 2011-04-27 | 주식회사 오리엔트전자 | Two-stage bidirectional isolated dc/dc power converter using fixed duty llc resonant converter |
| US8976549B2 (en) | 2009-12-03 | 2015-03-10 | Power Systems Technologies, Ltd. | Startup circuit including first and second Schmitt triggers and power converter employing the same |
| US8520420B2 (en) | 2009-12-18 | 2013-08-27 | Power Systems Technologies, Ltd. | Controller for modifying dead time between switches in a power converter |
| US8059429B2 (en) | 2009-12-31 | 2011-11-15 | Active-Semi, Inc. | Using output drop detection pulses to achieve fast transient response from a low-power mode |
| US8787043B2 (en) | 2010-01-22 | 2014-07-22 | Power Systems Technologies, Ltd. | Controller for a power converter and method of operating the same |
| WO2011116225A1 (en) | 2010-03-17 | 2011-09-22 | Power Systems Technologies, Ltd. | Control system for a power converter and method of operating the same |
| DE112011101073T5 (en) | 2010-03-26 | 2013-01-10 | Power Systems Technologies,Ltd. | Power supply with a hub for a universal serial bus |
| JP2011211836A (en) | 2010-03-30 | 2011-10-20 | Panasonic Corp | Switching device driving unit and semiconductor apparatus |
| US8502461B2 (en) | 2010-05-25 | 2013-08-06 | Green Solution Technology Co., Ltd. | Driving circuit and control circuit |
| TWI445440B (en) | 2011-03-22 | 2014-07-11 | Green Solution Tech Co Ltd | Driving circuit |
| CN101834541B (en) | 2010-06-02 | 2013-03-13 | 英飞特电子（杭州）股份有限公司 | Constant current circuit with high power factor |
| CN102340251B (en) | 2010-07-20 | 2014-06-04 | 台达电子工业股份有限公司 | Alternating-current to direct-current converter and control circuit thereof |
| US8792257B2 (en) | 2011-03-25 | 2014-07-29 | Power Systems Technologies, Ltd. | Power converter with reduced power dissipation |
| US9735673B2 (en) | 2011-03-30 | 2017-08-15 | Infineon Technologies Ag | Burst-mode operation of a switching converter |
| US8681513B2 (en) * | 2011-06-28 | 2014-03-25 | General Electric Company | Optimization of a power converter employing an LLC converter |
| US20140254215A1 (en) | 2011-08-29 | 2014-09-11 | Power Systems Technologies Ltd. | Controller for a power converter and method of operating the same |
| CN102412727B (en) | 2011-11-25 | 2014-02-19 | 成都芯源系统有限公司 | Switching power supply, control circuit thereof and dimming method |
| US9143043B2 (en) | 2012-03-01 | 2015-09-22 | Infineon Technologies Ag | Multi-mode operation and control of a resonant converter |
| US9602018B2 (en) | 2012-03-20 | 2017-03-21 | Infineon Technologies Austria Ag | Power converter with reduced power consumption in standby mode |
| US20140091718A1 (en) | 2012-09-28 | 2014-04-03 | Power Systems Technologies, Ltd. | Power Converter with an Inductor-Inductor-Capacitor Stage and Method of Operating the Same |
| US20140091720A1 (en) * | 2012-09-28 | 2014-04-03 | Power Systems Technologies, Ltd. | Controller for Use with a Power Converter and Method of Operating the Same |
| US20150098254A1 (en) | 2013-10-09 | 2015-04-09 | Power Systems Technologies Ltd. | Controller for use with a power converter and method of operating the same |
| US9300206B2 (en) | 2013-11-15 | 2016-03-29 | Power Systems Technologies Ltd. | Method for estimating power of a power converter |
-
2012
- 2012-07-06 US US13/543,503 patent/US9190898B2/en active Active
-
2013
- 2013-05-28 DE DE102013105485.4A patent/DE102013105485A1/en not_active Ceased
- 2013-06-28 CN CN201310278566.6A patent/CN103532392B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20050099827A1 (en) * | 2003-11-11 | 2005-05-12 | Hitachi Ltd. | Resonant converter and control method thereof |
| JP2005348560A (en) * | 2004-06-04 | 2005-12-15 | Sanken Electric Co Ltd | Switching power supply apparatus and power factor improving circuit |
| US20090072626A1 (en) * | 2005-05-26 | 2009-03-19 | Rohm Co., Ltd. | Power supply apparatus having switchable switching regulator and linear regulator |
| CN101123395A (en) * | 2006-08-04 | 2008-02-13 | 凌特公司 | Circuits and methods for adjustable peak inductor current and hysteresis for burst mode in switching regulators |
| US20100020578A1 (en) * | 2008-07-25 | 2010-01-28 | Samsung Electro-Mechanics Co., Ltd. | Adapter power supply |
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Also Published As
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|---|---|
| DE102013105485A1 (en) | 2014-01-09 |
| CN103532392B (en) | 2016-10-26 |
| US20140009978A1 (en) | 2014-01-09 |
| US9190898B2 (en) | 2015-11-17 |
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