CN102342028A - High frequency module - Google Patents
High frequency module Download PDFInfo
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- CN102342028A CN102342028A CN201080010829XA CN201080010829A CN102342028A CN 102342028 A CN102342028 A CN 102342028A CN 201080010829X A CN201080010829X A CN 201080010829XA CN 201080010829 A CN201080010829 A CN 201080010829A CN 102342028 A CN102342028 A CN 102342028A
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- 238000002955 isolation Methods 0.000 abstract description 23
- 239000000758 substrate Substances 0.000 description 41
- 230000005611 electricity Effects 0.000 description 35
- 230000005540 biological transmission Effects 0.000 description 22
- 230000000052 comparative effect Effects 0.000 description 14
- 101100381996 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) BRO1 gene Proteins 0.000 description 8
- 101000702394 Homo sapiens Signal peptide peptidase-like 2A Proteins 0.000 description 7
- 101100058964 Arabidopsis thaliana CALS5 gene Proteins 0.000 description 6
- 101100388543 Caenorhabditis elegans glt-1 gene Proteins 0.000 description 6
- 238000010586 diagram Methods 0.000 description 6
- 239000000178 monomer Substances 0.000 description 5
- 230000001939 inductive effect Effects 0.000 description 4
- 230000005012 migration Effects 0.000 description 3
- 238000013508 migration Methods 0.000 description 3
- 101100058970 Arabidopsis thaliana CALS11 gene Proteins 0.000 description 2
- 101000702393 Homo sapiens Signal peptide peptidase-like 2B Proteins 0.000 description 2
- 101100341076 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) IPK1 gene Proteins 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 230000005764 inhibitory process Effects 0.000 description 2
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- 102100025961 Glutaminase liver isoform, mitochondrial Human genes 0.000 description 1
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
- H04B1/0053—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band
- H04B1/006—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band using switches for selecting the desired band
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
- H03J5/00—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner
- H03J5/24—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection
- H03J5/242—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection used exclusively for band selection
- H03J5/244—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection used exclusively for band selection using electronic means
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- Signal Processing (AREA)
- Transceivers (AREA)
- Filters And Equalizers (AREA)
- Waveguide Switches, Polarizers, And Phase Shifters (AREA)
Abstract
The present invention aims to provide a high frequency module which is able to secure isolation between desired signals without the addition of a new switch circuit and filter. The high frequency module (1) is provided with a low pass filter (LPF1) and a filter adjusting capacitor (CCC). The signal line that connects an antenna port (ANT) to a signal port (1800/1900-Tx) is connected to a switch circuit (SW1) which controls the propagation of signals to the signal port, is connected to a low pass filter (LPF1) at the signal port side of the switch circuit (SW1), and is connected to a first end of a filter adjusting capacitor (CCC) at the signal port side of the low pass filter (LPF1). The signal line that connects the antenna port (ANT) to a signal port (1900-Rx) is connected to switch circuits (SW2, SW4) which control the propagation of signals to the signal port. The second end of the filter adjusting capacitor (CCC) is connected to an anode of a diode (DD2) of the switch circuit (SW2).
Description
Technical field
The high-frequency model that leading section that the present invention relates to portable phone etc. is adopted.
Background technology
For portable phone can be used, adopt the corresponding high-frequency model of multifrequency (for example with reference to patent documentation 1 Fig. 2) sometimes at the leading section of portable phone etc. in the different a plurality of communication systems of frequency band.
The high-frequency model that above-mentioned patent documentation disclosed is a module of utilizing the corresponding type of three frequencies of PCS, DCS, these three communication systems of EGSM.This high-frequency model comprises the many signal line that connect independent signal input/output port and common antenna port.The common antenna port is connected with shared device.Shared device separates the signal of PCS and DCS with the signal of EGSM.In addition, the branched portion that is positioned at level behind the shared device on the holding wire comprises the 1st and the 2nd diode.A holding wire of the 1st diode and fork is connected in series.Another root holding wire of the 2nd diode and fork is connected in parallel.In addition, has low pass filter in the holding wire of transmission transmission signal.Low pass filter is removed the high order harmonic component of sending signal.
The the 1st and the 2nd diode of each branched portion carries out conduction and cut-off synchronously and switches.When making the 1st diode and the 2nd diode current flow, the inductive component of the 2nd diode and capacitor constitute series resonant circuit.Setting is observed the impedance of the holding wire be provided with the 2nd diode from branched portion, and making becomes infinity when the frequency of the signal through a square signal line produces series resonance.Thus, can suppress to the signal wire transmits unwanted signal that is provided with the 2nd diode.In addition, when the 1st and the 2nd diode ended, the 1st diode broke off.Thus, can suppress to the signal wire transmits unwanted signal that is provided with the 1st diode.
This high-frequency model, be positioned at shared device after the signal line side that is used to transmit PCS and DCS signal of level, separate with the transmission signal at the branched portion of the first order reception signal PCS and DCS.Then, in the holding wire of the reception signal that transmits PCS and DCS, partial branched portion is set.Thus, be made as appropriate timing through switch with each branched portion, thus a part of overlapping PCS that can guarantee frequency band send signal (1850～1910MHz) with the DCS reception signal (isolation between 1805～1880MHz).
The prior art document
Patent documentation
Patent documentation 1: Japanese Patent Laid is opened the 2004-128799 communique
Summary of the invention
The portable telephone communication system shifts to the EDGE mode from the GPRS mode.Therefore, PCS that frequency band overlaps sends signal and DCS receives the isolation between the signal except needs improve, also need improve the PCS that frequency band do not overlap the transmission signal (1850～1910MHz) with reception signal (1930～1990) between isolation.
Yet, in existing circuit structure,, also improve the transmission signal of PCS and the isolation between the reception signal than the height of GPRS mode on one side Yi Bian be difficult to guarantee that PCS sends signal and DCS receives the isolation between the signal.
Suppose if append switching circuit or filter, then can improve the transmission signal of PCS and receive the isolation between the signal to existing circuit structure.Yet, in this case, append switching circuit or filter and may cause the through characteristic of each holding wire to reduce and cause the maximization of module size.The problems referred to above are not only for the transmission signal that improves PCS with receive the isolation between the signal and can take place when appending switching circuit or filter, also can append improving the isolation between arbitrary signal under the situation of switching circuit or filter to take place.
Therefore, the object of the present invention is to provide a kind of high-frequency model, this high-frequency model does not append new switching circuit or the filter that is used to improve the isolation between desirable signal in circuit structure, just can guarantee the isolation between desirable signal.
High-frequency model of the present invention comprises a plurality of independent signal input/output ports, common antenna port, switching circuit, first holding wire, and secondary signal line, comprises that also the adjustment of filter and filter use capacitor.Switching circuit switches being connected between common antenna port and a plurality of independent signal input/output ports.First and second holding wire connects independent signal input/output port and common antenna port.Switching circuit comprises the switch element that connects first and second holding wire respectively.Filter is connected in series in the link position of ratio switching circuit of first holding wire more near the position of independent signal input/output terminal oral-lateral.Filter adjustment is connected the link position of ratio filter of first holding wire more near the position of independent signal input/output terminal oral-lateral with first end of capacitor.In addition, its second end is connected on the switch element that is connected with the secondary signal line.
In this structure, when the filter adjustment was connected with the secondary signal line with capacitor, the inductor and the filter adjustment that constitute filter produced resonance with the parallel circuits that capacitor constituted.Therefore, utilize these two resonance of resonance of this resonance and filter monomer, can make the frequency characteristic of high-frequency model produce desirable variation.Particularly, through setting filter adjustment electricity consumption capacity of condenser, thus the attenuation of the frequency band of the frequency band of the signal that can guarantee to be transmitted along first holding wire, the signal that transmitted along the secondary signal line.Thus, can improve the signal that transmitted along first holding wire and the signal that transmitted along the secondary signal line between isolation.
Filter of the present invention also can comprise parallel resonance capacitor and the parallel resonant inductor device that is connected in parallel, and the resonance frequency of the parallel resonance that parallel resonant inductor device and parallel resonance capacitor are produced is set at the frequency of the high order harmonic component of the signal that is transmitted along first holding wire.Utilize this structure, can remove the high order harmonic component in first holding wire.In addition, also can the resonance frequency of the resonant circuit that is made up of with capacitor and parallel resonant inductor device filter adjustment be set at the first-harmonic of the signal that edge first holding wire transmitted or the frequency of high order harmonic component.Thus, can improve the signal that transmitted along first holding wire and the signal that transmitted along the secondary signal line between isolation.
Also can be that the switch element that is connected with first holding wire of the present invention is the 1st diode, the switch element that is connected with the secondary signal line be the 2nd diode.The anode of the 1st diode is connected with the common antenna port side of first holding wire, and negative electrode is connected with independent signal input/output terminal oral-lateral.The negative electrode of the 2nd diode is connected with the secondary signal line, and negative electrode is connected with control terminal.The anode of the 2nd diode is through series resonance capacitor ground connection.In addition, the filter adjustment is connected the link position of the 2nd diode and series resonance capacitor with second end of capacitor.
According to this structure, through applying bias voltage, make the diode current flow that is connected with the secondary signal line, thereby can make the also conducting of diode that is connected with first holding wire from control terminal.At this moment, with switching circuit that the secondary signal line is connected in produce series resonance, utilize this series resonance, can suppress the signal that will flow into the secondary signal line is transmitted.In addition; Through making the diode that is connected with the secondary signal line end; Thereby make the diode that is connected with first holding wire also end, adjust under the situation about being connected with capacitor with filter, can make the secondary signal line transmit signal at cut-out secondary signal line.Thereby,, the secondary signal line cuts off the connection of filter adjustment when transmitting signal with capacitor, can remove the filter adjustment with the influence of capacitor to the through characteristic of secondary signal line.
In high-frequency model of the present invention; The pattern electrode of at least a portion of preferably feasible formation parallel resonance capacitor, relative on the interarea normal direction of multilager base plate with the pattern electrode of at least a portion that constitutes series resonance capacitor constitutes filter adjustment and uses capacitor.In addition, preferred cloth line electrode that is connected with the parallel resonance capacitor and the cloth line electrode that is connected with series resonance capacitor of making is relative on the interarea normal direction of multilager base plate, constitutes the filter adjustment and uses capacitor.
Thus, constitute the filter adjustment and use capacitor, thereby can both suppress the increase of module size, the filter adjustment is set again uses capacitor.In addition, can adjust the parasitic capacitance that connecting wiring produced by rejects trap, can make the series resonance of series resonance capacitor and diode stable, suppress the change of the through characteristic of secondary signal line with capacitor.
According to the present invention, through being set, the filter adjustment adjusts capacitance with capacitor, and can make the frequency characteristic of high-frequency model produce desirable variation.Particularly, first holding wire that can guarantee to be connected with capacitor and the isolation between the secondary signal line with filter adjustment.
Description of drawings
Fig. 1 is the schematic circuit diagram of the related high-frequency model of execution mode of the present invention 1.
Fig. 2 is the performance plot of high-frequency model shown in Figure 1.
Fig. 3 is the range upon range of figure of high-frequency model shown in Figure 1.
Fig. 4 is the range upon range of figure of high-frequency model shown in Figure 1.
Fig. 5 is the schematic circuit diagram of the related high-frequency model of execution mode of the present invention 2.
Fig. 6 is the performance plot of high-frequency model shown in Figure 5.
Fig. 7 is the schematic circuit diagram of the related high-frequency model of execution mode of the present invention 3.
Fig. 8 is the performance plot of high-frequency model shown in Figure 7.
Reference numeral
1 high-frequency model
The shared device of DPX
The HPF high pass filter
LPF, LPF1, LPF2 low pass filter
11A～11C branched portion
SW1～SW6 switching circuit
DD1, DD2, GD1, GD2, PD1, PD2 diode
Capacitor is used in the adjustment of CCC filter
Embodiment
Below, the structure example of the high-frequency model that execution mode of the present invention 1 is related is described.
The high-frequency model of this execution mode is applied to the leading section of the portable phone of EDGE mode, is corresponding to the corresponding pattern piece of three frequencies that utilizes PCS, DCS, these three communication systems of EGSM.
Fig. 1 is the schematic circuit diagram of the related high-frequency model of this execution mode.
High-frequency model 1 comprises shared device DPX, branched portion 11A～11C, low pass filter LPF1, LPF2, reaches filter adjustment electricity consumption container C CC.In addition, as external connection port, comprising: the antenna port ANT that is equivalent to common antenna port of the present invention; The signal port 1800/1900-Tx, 1900-Rx, 1800-Rx, 850/900-Tx, the 850/900-Rx that are equivalent to independent signal input/output port of the present invention; And be equivalent to the control port Vc1～Vc3 of control terminal of the present invention.
Shared device DPX comprises low pass filter LPF and high pass filter HPF, and the tie point of low pass filter LPF and high pass filter HPF is connected with antenna port ANT with capacitor through stopping direct current.The low pass filter LPF of duplexer DPX passes through the signal of EGSM, makes the signal attenuation of PCS and DCS.In addition, high pass filter HPF passes through the signal of PCS and DCS, makes the signal attenuation of EGSM.
Low pass filter LPF is connected between antenna port ANT and the branched portion 11C.This low pass filter LPF comprises capacitor Ct1, inductor Lt1, reaches capacitor Cu1, constitutes the low pass filter that the signal band of EGSM is made as passband.First end of inductor Lt1 is connected with antenna port ANT, and second end is connected with branched portion 11C.Capacitor Ct1 and inductor Lt1 are connected in parallel.Second end of inductor Lt1 is through capacitor Cu1 ground connection.
High pass filter HPF is connected between antenna port ANT and the branched portion 11A.This high pass filter HPF comprises capacitor Cc1, Cc2, inductor Lt2, reaches capacitor Ct2, constitutes the high pass filter that the signal band of PCS and DCS is made as passband.First end of capacitor Cc1 is connected with antenna port ANT, and second end is connected with capacitor Cc2.First end of capacitor Cc2 is connected with capacitor Cc1, and second end is connected with branched portion 11A.First end of inductor Lt2 is connected with first end of second end of capacitor Cc1 and capacitor Cc2.Second end of inductor Lt2 is through capacitor Ct2 ground connection.
Branched portion 11C comprises switching circuit SW5, SW6, and the tie point of switching circuit SW5 and switching circuit SW6 is connected with low pass filter LPF.Branched portion 11C switches EGSM transmit status and EGSM accepting state based on the voltage that is input to control port Vc1 from the outside.
Switching circuit SW5 is connected between low pass filter LPF and the low pass filter LPF2.This switching circuit SW5 comprises diode GD1 and inductor GSL1.The anode of diode GD1 is connected with low pass filter LPF, and negative electrode is connected with low pass filter LPF2.The negative electrode of diode GD1 is through inductor GSL1 ground connection.
Switching circuit SW6 is connected between low pass filter LPF and the signal port 850/900-Rx.This switching circuit SW6 comprises inductor GSL2, capacitor GCu3, diode GD2, capacitor GC5, reaches resistor R g.First end of inductor GSL2 is connected with low pass filter LPF, and second end is connected with signal port 850/900-Rx with capacitor through stopping direct current.Second end of inductor GSL2 passes through capacitor GCu3 ground connection, and is connected with the negative electrode of diode GD2.The anode of diode GD2 is connected with control port Vc1 through resistor R g, and through capacitor GC5 ground connection.
Branched portion 11C is when the EGSM transmit status, and switching circuit SW6 suppresses the transmission signal of EGSM is transmitted, and switching circuit SW5 transmits the transmission signal of EGSM.At this moment, through applying voltage, thereby will the voltage higher be applied to the anode of diode GD2 than switching voltage from control port Vc1.Therefore, diode GD2 conducting, second end of inductor GSL2 is through capacitor GC5 ground connection, and the inductive component of diode GD2 and capacitor GC5 carry out series resonance.The line length of inductor GLS2 is set at about 1/4 the length of wavelength of the transmission signal band of EGSM; When switching circuit SW5 one side is observed inductor GSL2 one side, to become impedance be infinitely-great open-circuit condition because diode GD2 one side of inductor GSL2 because of series resonance ground connection, therefore is set at.Thereby, can suppress switching circuit SW6 the transmission signal of EGSM is transmitted.On the other hand, in switching circuit SW5, apply the voltage higher than switching voltage to the anode of diode GD1.Therefore, diode GD1 conducting, switching circuit SW5 transmits the transmission signal of EGSM.
Branched portion 11C is when the EGSM accepting state, and switching circuit SW6 transmits the reception signal of EGSM, and switching circuit SW5 suppresses the reception signal of EGSM is transmitted.At this moment, through applying voltage, thereby will the voltage lower be applied to the anode of diode GD2 than switching voltage from control port Vc1.Therefore, diode GD2 ends.Thereby switching circuit SW6 transmits the reception signal of EGSM.On the other hand, in switching circuit SW5, apply the voltage lower than switching voltage to the anode of diode GD1.Therefore, diode GD1 ends, and inhibition switching circuit SW5 transmits the reception signal of EGSM.
Low pass filter LPF2 is connected between switching circuit SW5 and the signal port 850/900-Tx.This low pass filter LPF2 comprises inductor GLt1, capacitor GCc1, reaches capacitor GCu1, GCu2, constitutes the second harmonic of the transmission signal of removing EGSM and the low pass filter of third-harmonic component.First end of inductor GLt1 is connected with switching circuit SW5, and second end is connected with signal port 850/900-Tx with capacitor through stopping direct current.Capacitor GCc1 and inductor GLt1 are connected in parallel.First end of inductor GLt1 is through capacitor GCu1 ground connection.Second end of inductor GLt1 is through capacitor GCu2 ground connection.
Branched portion 11A comprises switching circuit SW1, SW2, and the tie point of switching circuit SW1 and switching circuit SW2 is connected with high pass filter HPF.Branched portion 11A switches transmit status and accepting state based on the voltage that is input to control port Vc2 from the outside.
Switching circuit SW1 is connected between high pass filter HPF and the low pass filter LPF1.This switching circuit SW1 comprises diode DD1, inductor DPSLt, capacitor DPCt1, reaches inductor DPSL1.The anode of diode DD1 is connected with high pass filter HPF, and negative electrode is connected with low pass filter LPF1.First end of inductor DPSLt is connected with the anode of diode DD1, and second end is connected with first end of capacitor DPCt1.First end of capacitor DPCt1 is connected with first end of inductor DSLt, and second end is connected with the negative electrode of diode DD1.The negative electrode of diode DD1 is through inductor DPSL1 ground connection.
Switching circuit SW2 is connected between high pass filter HPF and the branched portion 11B.This switching circuit SW2 comprises inductor DSL2, capacitor CDPr, capacitor DCu4, diode DD2, capacitor DC5, reaches resistor R d.First end of capacitor DSL2 is connected with high pass filter HPF, and second end is connected with first end of capacitor CDPr and the negative electrode of diode DD2.Second end of capacitor CDPr passes through capacitor DCu4 ground connection, and is connected with branched portion 11B.The anode of diode DD2 is connected with control port Vc2 through resistor R d, and through being equivalent to the capacitor DC5 ground connection of series resonance capacitor of the present invention, second end of adjusting electricity consumption container C CC with the filter that hereinafter is described in detail is connected.
Branched portion 11A is when transmit status, and switching circuit SW2 suppresses the transmission signal of PCS and DCS is transmitted, and switching circuit SW1 transmits the transmission signal of PCS and DCS.At this moment, through applying voltage, thereby will the voltage higher be applied to the anode of diode DD2 than switching voltage from control port Vc2.Therefore, diode DD2 conducting, second end of inductor DSL2 is through capacitor DC5 ground connection, and the inductive component of diode DD2 and capacitor DC5 carry out series resonance.The line length of inductor DSL2 is set at about 1/4 the length of wavelength of the transmission signal band of PCS and DCS; When switching circuit SW1 one side is observed inductor DSL2 one side, to become impedance be infinitely-great open-circuit condition because diode DD2 one side of inductor DSL2 because of series resonance ground connection, therefore is set at.Thereby, can suppress switching circuit SW2 the transmission signal of PCS and DCS is transmitted.On the other hand, in switching circuit SW1, apply the voltage higher than switching voltage to the anode of diode DD1.Therefore, diode DD1 conducting, switching circuit SW1 transmits the transmission signal of PCS and DCS.
Branched portion 11A is when accepting state, and switching circuit SW2 transmits the reception signal of PCS and DCS, and switching circuit SW1 suppresses the reception signal of PCS and DCS is transmitted.At this moment, through applying voltage, thereby will the voltage lower be applied to the anode of diode DD2 than switching voltage from control port Vc2.Therefore, diode DD2 ends.Thus, switching circuit SW2 transmits the reception signal of PCS and DCS.On the other hand, in switching circuit SW1, apply the voltage lower than switching voltage to the anode of diode DD1.Therefore, diode DD1 ends, and switching circuit SW1 suppresses the reception signal of PCS and DCS is transmitted.
Low pass filter LPF1 is connected between switching circuit SW1 and the signal port 1800/1900-Tx.This low pass filter LPF1 comprises inductor DLt1, DLt2, capacitor DCc1, reaches capacitor DCu1, DCu2, constitutes the second harmonic of the transmission signal of removing PCS and DCS and the low pass filter of third-harmonic component.Inductor DLt1 is equivalent to parallel resonant inductor device of the present invention, and first end is connected with switching circuit SW1, and second end is connected with first end of inductor DLt2.First end of inductor DLt2 is connected with first end of inductor DLt1, and second end of inductor DLt2 is connected with signal port 1800/1900-Tx with capacitor through stopping direct current.Capacitor DCc1 is equivalent to parallel resonance capacitor of the present invention, and DLt1 is connected in parallel with inductor.First end of inductor DLt1 is through capacitor DCu1 ground connection.Second end of inductor DLt1 is through capacitor DCu2 ground connection, and with after first end of the filter adjustment electricity consumption container C CC that states be connected.
Branched portion 11B comprises switching circuit SW3, SW4, and the tie point of switching circuit SW3 and switching circuit SW4 is connected with switching circuit SW2.Branched portion 11B switches PCS accepting state and DCS accepting state based on the voltage that is input to control port Vc3 from the outside.
Switching circuit SW3 is connected between switching circuit SW2 and the signal port 1900-Rx.This switching circuit SW3 comprises diode PD1, inductor PSL1, reaches capacitor PCu3.The anode of diode PD1 is connected with switching circuit SW2, and negative electrode is connected with signal port 1900-Rx with capacitor through stopping direct current.The negative electrode of diode PD1 is through inductor PSL1 ground connection, through capacitor PCu3 ground connection.
Switching circuit SW4 is connected between switching circuit SW2 and the signal port 1800-Rx.This switching circuit SW4 comprises inductor PSL2, capacitor DCu3, diode PD2, capacitor PC5, reaches resistor R p.First end of inductor PSL2 is connected with switching circuit SW2, and second end is connected with signal port 1800-Rx with capacitor through stopping direct current.Second end of inductor PSL2 passes through capacitor DCu3 ground connection, and is connected with the negative electrode of diode PD2.The anode of diode PD2 is connected with control port Vc3 through resistor R p, and through capacitor PC5 ground connection.
As filter adjustment electricity consumption container C CC, adopt the capacitance that is approximately 0.2pF here.First end of filter adjustment electricity consumption container C CC is compared LC antiresonant circuit low pass filter LPF1, that be made up of inductor DLt1 and capacitor DCc1 and is connected more near signal port 1800/1900-Tx one side.In addition, its second end is connected with the anode of the diode DD2 that is arranged at switching circuit SW2.Thus; Among the branched portion 11A; Between diode DD2 conducting, filter adjustment electricity consumption container C CC and transmit status that second end of inductor DSL2 is connected, the parallel circuits generation resonance of the inductor DLt1 of low pass filter LPF1 and filter adjustment electricity consumption container C CC formation.Therefore, utilize this resonance, can make the frequency characteristic of high-frequency model produce desirable variation.
In addition, if the capacitance value of filter adjustment electricity consumption container C CC is excessive, then may worsen by the isolation between the holding wire of filter adjustment electricity consumption container C CC connection, the through characteristic between each holding wire.Therefore; The capacitance of preferably filter being adjusted electricity consumption container C CC is set very for a short time; Be preferably for example 0.1pF～0.6pF, thus, through reducing the capacitance of filter adjustment electricity consumption container C CC; Come suitably circuit constant etc. to proofread and correct, thereby can make the frequency characteristic of high-frequency model produce desirable variation low pass filter LPF1.
In said structure, low pass filter LPF1 is equivalent to the switching circuit SW1 that compares of the present invention and is connected in series in more the filter of the present invention near signal port 1800/1900-Tx side.And the holding wire that connects antenna port ANT and signal port 1800/1900-Tx is equivalent to first holding wire of the present invention.In addition, the holding wire of connection antenna port ANT and signal port 1900-Rx is equivalent to secondary signal line of the present invention respectively with the holding wire that is connected antenna port ANT and signal port 1800-Rx.
Fig. 2 is the performance plot that the frequency characteristic of the related high-frequency model of this execution mode is shown for example.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example that is not provided with filter adjustment electricity consumption container C CC.
Fig. 2 (A) is the performance plot that the through characteristic between antenna port ANT and the signal port 1800/1900-Tx is shown for example.In the through characteristic between these ports, in this structure example, the attenuation pole of the high frequency side of passband is positioned at about 3.37GHz.On the other hand, in the comparative structure example, the attenuation pole of the high frequency side of passband is positioned at about 3.57GHz.The attenuation pole of the high frequency side of these passbands is frequencies that the high order harmonic component of PCS signal and DCS signal is ended because of the main effect of low pass filter LPF1.In this structure example; The frequency of the attenuation pole of the high frequency side of passband is compared the comparative structure example obvious migration is not taken place; But, even can confirm to be provided with the high order harmonic component that filter adjustment electricity consumption container C CC also can end the signal that is transmitted by signal port 1800/1900-Tx fully.
Hence one can see that, and the through characteristic that is provided with the holding wire of low pass filter LPF1 receives the resonance of low pass filter LPF1 monomer, reaches the influence of filter adjustment electricity consumption container C CC.Yet the influence that receives filter adjustment electricity consumption container C CC is less than the influence of the resonance that receives low pass filter LPF1 monomer, even therefore filter adjustment electricity consumption container C CC is set, also can not cause too big infringement to the through characteristic of this holding wire.Therefore, according to the present invention, we can say can be in the through characteristic of not damaging first holding wire, improve the signal that transmitted along first holding wire and the signal that transmitted along the secondary signal line between isolation.
Fig. 2 (B) and Fig. 2 (C) are the performance plots that the isolation characteristic between signal port 1800/1900-Tx and the signal port 1900-Rx is shown for example.In the frequency characteristic between these ports, in the comparative structure example, the roughly the same frequency of attenuation pole that the caused attenuation pole of low pass filter LPF1 monomer is positioned at the frequency characteristic shown in the dotted line with Fig. 2 (A) is about 3.57GHz.On the other hand, in this structure example, the caused attenuation pole of low pass filter LPF1 monomer is positioned at about 3.00GHz (with reference to the solid line of Fig. 2 (B)) that will hang down about 370MHz than the attenuation pole of the frequency characteristic shown in the solid line of Fig. 2 (A).In this structure example; Through filter adjustment electricity consumption container C CC is set; Thereby can constitute another antiresonant circuit with the inductor DLt1 that constitutes low pass filter LPF; Thereby can be in the frequency characteristic between signal port 1800/1900-Tx and the signal port 1900-Rx, the frequency of the attenuation pole of the high frequency side of passband is reduced to frequently little than structure example.And, can confirm: although near almost not decay about 1.71GHz in the comparative structure example in this structure example, can significantly decay near it.Thus, although in the comparative structure example, at the frequency band that spreads all over about 1.71GHz～about 1.91GHz; The attenuation that can guarantee is about 23.9dB; But in this structure example,, can guarantee the attenuation of about 31.1dB at the frequency band that spreads all over about 1.71GHz～about 1.91GHz.That is, can guarantee that (1850～1910MHz) attenuation is about 31.1dB, can improve the isolation between signal port 1800/1900-Tx and the signal port 1900-Rx for frequency band at the transmission signal of PCS.
Fig. 3, the 4th, the range upon range of figure of the high-frequency model that this execution mode is related.Fig. 3 (A) to (O), Fig. 4 (P) to (Y) are the upward views of looking up substrate (A) to (Y) with the order from the orlop to the superiors.In addition, Fig. 4 (Z) is the vertical view that the substrate (Y) of the superiors of multilager base plate is overlooked.In addition, the through hole electrode of substrate (A)～(Y) is used circular icon representation in the drawings.
Substrate (A) is laminated in the orlop of multilager base plate, and its lower surface is the installed surface of high-frequency model, is formed with a plurality of installing electrodes.Arrow shown in the figure illustrates the port name of installing electrodes.
Substrate (B) is layered in from the second layer of the orlop of multilager base plate, is provided with the internal layer grounding electrode at the lower surface of substrate, in the substrate set inside through hole electrode is arranged.
Substrate (C) is layered in from the 3rd layer of the orlop of multilager base plate, is provided with pattern electrode that constitutes capacitor GCu3 and the pattern electrode that constitutes capacitor GC5 at base lower surface, in the substrate set inside through hole electrode is arranged.
Substrate (D) is layered in from the 4th layer of the orlop of multilager base plate, is provided with the internal layer grounding electrode at the lower surface of substrate, in the substrate set inside through hole electrode is arranged.At the grounding electrode of the grounding electrode of substrate (D) and substrate (B) be clipped between the pattern electrode of the substrate (C) between two grounding electrodes and constitute capacitor GCu3, GC5.
Substrate (E) is layered in from the layer 5 of the orlop of multilager base plate; Be provided with the pattern electrode of the pattern electrode that constitutes capacitor PC5, the pattern electrode that constitutes capacitor GC5, formation capacitor DC5 and the pattern electrode of formation capacitor GCu2 at base lower surface, through hole electrode arranged in the substrate set inside.
Substrate (F) is layered in from the layer 6 of the orlop of multilager base plate, is provided with pattern electrode and the internal layer grounding electrode that constitutes capacitor DCu2 at base lower surface, in the substrate set inside through hole electrode is arranged.At the grounding electrode of the grounding electrode of substrate (F) and substrate (D) be clipped between the pattern electrode of the substrate (E) between two grounding electrodes and constitute capacitor PC5, GC5, DC5, GCu2.
Here, the pattern electrode of the pattern electrode of the formation capacitor DC5 of substrate (E) and the formation capacitor DCu2 of substrate (F) is relative across substrate (E), through the overlapping function that plays as filter adjustment electricity consumption container C CC of these pattern electrodes.
Substrate (G) is layered in from the layer 7 of the orlop of multilager base plate; Be provided with the pattern electrode of the pattern electrode that constitutes capacitor Ct2, the pattern electrode that constitutes capacitor Cu1, formation capacitor DCu2 and the pattern electrode of formation capacitor GCu1 at base lower surface, through hole electrode arranged in the substrate set inside.
Substrate (H) is layered in from the 8th layer of the orlop of multilager base plate, is provided with the internal layer grounding electrode at the lower surface of substrate, in the substrate set inside through hole electrode is arranged.This grounding electrode and be formed at and constitute capacitor Ct2, Cu1, DCu2, GCu1 between the pattern electrode of substrate (G).
Substrate (I) is layered in from the 9th layer of the orlop of multilager base plate; Be provided with pattern electrode that constitutes capacitor DCu4 and the pattern electrode that constitutes capacitor DCu1 at base lower surface, and be formed between the grounding electrode of substrate (H) and constitute capacitor DCu4, DCu1.At substrate set inside through hole electrode.
Substrate (J) is layered in from the tenth layer of the orlop of multilager base plate, in the substrate set inside through hole electrode is arranged.
Substrate (K)～(Y) is layered in from the 11～25 layer of the orlop of multilager base plate, is provided with a plurality of pattern electrodes that constitute a plurality of inductors at base lower surface, in the substrate set inside through hole electrode is arranged.Be provided with a plurality of surface electrodes of the circuit element that connects discrete component at the upper surface of substrate (Y).
As this execution mode; Make the pattern electrode of formation capacitor DCu2 of pattern electrode and substrate (F) of formation capacitor DC5 of substrate (E) play function as filter adjustment electricity consumption container C CC; Thereby can not need to be provided in addition constituting the pattern electrode of filter adjustment electricity consumption container C CC, can suppress the module volume and increase.In addition; Owing to need not to be used to connect the line electrode of filter adjustment electricity consumption container C CC and other circuit elements, therefore, can suppress to produce unnecessary parasitic capacitance; Can make the series resonance of capacitor DC5 and diode DD2 stable, can suppress the change of the through characteristic of secondary signal line.
In addition, can also adjust electricity consumption container C CC thereby constitute filter through making the cloth line electrode that is connected with capacitor DC5 relative with the cloth line electrode that is connected with capacitor DCu2.In addition, as this execution mode,, produce stray inductance thereby can be suppressed at grounding electrode portion through grounding electrode being configured in the orlop of multilager base plate or near the layer it.Therefore, through electrode for capacitors is configured in grounding electrode near, thereby can reduce the stray inductance that produces in the capacitor of ground connection at one end, can improve the Q value of above-mentioned series resonance, can improve the isolation between first holding wire and the secondary signal line.
Next, the structure example of the high-frequency model that execution mode of the present invention 2 is related is described.In following explanation, to the structure additional phase identical with the related high-frequency model of execution mode 1 with label, and omit explanation.
Fig. 5 is the schematic circuit diagram of the related high-frequency model of this execution mode.In this execution mode, first end of filter being adjusted electricity consumption container C CC is connected with second end of the inductor DLt2 of low pass filter LPF1.Even employing foregoing circuit, also embodiment of the present invention well.
Fig. 6 is the performance plot that the frequency characteristic of the related high-frequency model of this execution mode is shown for example.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example that is not provided with filter adjustment electricity consumption container C CC.
Fig. 6 (A) is the performance plot that the through characteristic between antenna port ANT and the signal port 1800/1900-Tx is shown for example.In the through characteristic between these ports, this structure example all is positioned at about 3.03GHz with the attenuation pole of the high frequency side of the passband of comparative structure example.Can confirm in this structure example; The frequency of the attenuation pole of the high frequency side of passband is compared with the comparative structure example; Obviously migration takes place, even filter adjustment electricity consumption container C CC, the high order harmonic component that also can end the signal that is transmitted by signal port 1800/1900-Tx fully are set.
Fig. 6 (B) illustrates the performance plot of the isolation characteristic between signal port 1800/1900-Tx and the signal port 1900-Rx for example.In the isolation characteristic of these ports; In the comparative structure example; At the frequency band that spreads all over about 1.71GHz～about 1.91GHz, the attenuation that can guarantee is about 22.5dB, but in this structure example; In the frequency band that spreads all over the 1.91GHz of about 1.71GHz～approximately of the frequency band of the transmission signal that comprises PCS, can guarantee the attenuation of about 31.1dB.
Next, the structure example of the high-frequency model that execution mode of the present invention 3 is related is described.In following explanation, to the structure additional phase identical with the related high-frequency model of execution mode 1 with label, and omit explanation.
Fig. 7 is the schematic circuit diagram of the related high-frequency model of this execution mode.In this execution mode, first end of filter being adjusted electricity consumption container C CC is connected with second end of the inductor GLt1 of low pass filter LPF2.Then, second end of filter being adjusted electricity consumption container C CC is connected with the anode of the diode GD2 of switching circuit SW6.Can suitably implement filter adjustment electricity consumption container C CC here.
Fig. 8 is the performance plot that the frequency characteristic of the related high-frequency model of this execution mode is shown for example.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example that is not provided with filter adjustment electricity consumption container C CC.
Fig. 8 (A) is the performance plot that the through characteristic between antenna port ANT and the signal port 850/900-Tx is shown for example.In the through characteristic between these ports, this structure example all is positioned at about 1.83GHz with the attenuation pole of the high frequency side of the passband of comparative structure example.The attenuation pole of the high frequency side of these passbands is frequencies that the high order harmonic component of EGSM signal is ended because of the main effect of low pass filter LPF2.Can confirm in this structure example; The frequency of the attenuation pole of the high frequency side of passband is compared with the comparative structure example; Obviously migration takes place, even filter adjustment electricity consumption container C CC, the high order harmonic component that also can end the signal that is transmitted by signal port 850/900-Tx fully are set.
Fig. 8 (B) illustrates the performance plot of the isolation characteristic between signal port 850/900-Tx and the signal port 900-Rx for example.In the isolation characteristic of these ports; In the comparative structure example; At the frequency band that spreads all over about 820MHz～about 920MHz, the attenuation that can guarantee is about 26.4dB, but in this structure example; In the frequency band that spreads all over the 920MHz of about 820MHz～approximately of the frequency band of the transmission signal that comprises EGSM, can guarantee the attenuation of about 29.6dB.
Except above-mentioned each execution mode is shown,, also can suitably implement even the present invention changes the link position of filter adjustment electricity consumption container C CC in the foregoing circuit structure.For example, also can adopt following structure: promptly, first end that filter is adjusted electricity consumption container C CC is connected the back level of low pass filter LPF1, second end is connected the anode of diode PD2 etc.
In addition, the present invention can also be applied to other circuit structures.For example; Can also adopt following structure: promptly; Append Filter Structures to signal port 1900-Rx of above-mentioned circuit structure etc.; Signal end oral-lateral at this filter is connected with first end of filter adjustment electricity consumption container C CC, and second end of filter being adjusted electricity consumption container C CC is connected with the anode of diode PD2.
Claims (7)
1. high-frequency model comprises:
A plurality of independent signal input/output ports; The common antenna port; To the switching circuit that switches said common antenna port and being connected of said a plurality of independent signal input/output ports; And first and second holding wire that connects said common antenna port and said independent signal input/output port, it is characterized in that,
Said switching circuit comprises the switch element that connects said first and second holding wire respectively, and said high-frequency model also comprises:
Filter, this filter are connected in series in the link position of the said switching circuit of ratio of said first holding wire more near the position of said independent signal input/output terminal oral-lateral; And
Capacitor is used in the filter adjustment; The adjustment of this filter is connected the link position of the said filter of ratio of said first holding wire more near the position of said independent signal input/output terminal oral-lateral with first end of capacitor; Its second end is connected on the said switch element, and said switch element is connected with said secondary signal line.
2. high-frequency model as claimed in claim 1 is characterized in that,
Said filter comprises parallel resonance capacitor and the parallel resonant inductor device that is connected in parallel, and the resonance frequency of the parallel resonance that said parallel resonant inductor device and said parallel resonance capacitor are produced is set at the frequency of the high order harmonic component of the signal that is transmitted along said first holding wire.
3. high-frequency model as claimed in claim 2 is characterized in that,
The resonance frequency of the resonant circuit that will be made up of with capacitor and said parallel resonant inductor device the adjustment of said filter is set at the first-harmonic of the signal that said first holding wire in edge transmitted or the frequency of high order harmonic component.
4. like each described high-frequency model of claim 1 to 3, it is characterized in that,
The said switch element that is connected with said first holding wire is the 1st diode, and its anode is connected with the said common antenna port side of said first holding wire, and negative electrode is connected with said independent signal input/output terminal oral-lateral,
The said switch element that is connected with said secondary signal line is the 2nd diode, and its negative electrode is connected with said secondary signal line, and anode is connected with control terminal, and said anode passes through series resonance capacitor ground connection,
Said filter adjustment is connected the link position of said the 2nd diode and said series resonance capacitor with said second end of capacitor.
5. high-frequency model as claimed in claim 4 is characterized in that,
The pattern electrode of at least a portion of the said parallel resonance capacitor of feasible formation, relative on the interarea normal direction of multilager base plate with the pattern electrode of at least a portion that constitutes said series resonance capacitor constitutes the adjustment of said filter and uses capacitor.
6. high-frequency model as claimed in claim 4 is characterized in that,
Make cloth line electrode that is connected with said parallel resonance capacitor and the cloth line electrode that is connected with said series resonance capacitor relative on the interarea normal direction of multilager base plate, constitute said filter adjustment and use capacitor.
7. like each described high-frequency model of claim 1 to 6, it is characterized in that,
The electric capacity that said filter is adjusted with capacitor is made as about 0.1pF～about 0.6pF.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2009-049657 | 2009-03-03 | ||
| JP2009049657 | 2009-03-03 | ||
| PCT/JP2010/053284 WO2010101130A1 (en) | 2009-03-03 | 2010-03-02 | High frequency module |
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| Publication Number | Publication Date |
|---|---|
| CN102342028A true CN102342028A (en) | 2012-02-01 |
| CN102342028B CN102342028B (en) | 2015-02-18 |
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| Application Number | Title | Priority Date | Filing Date |
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| CN201080010829.XA Expired - Fee Related CN102342028B (en) | 2009-03-03 | 2010-03-02 | High frequency module |
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|---|---|
| JP (1) | JP5201260B2 (en) |
| CN (1) | CN102342028B (en) |
| WO (1) | WO2010101130A1 (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105379129A (en) * | 2013-07-16 | 2016-03-02 | 株式会社村田制作所 | Front end circuit |
| CN107453763A (en) * | 2016-05-17 | 2017-12-08 | 株式会社村田制作所 | Switch module and high-frequency model |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1336731A (en) * | 2000-07-27 | 2002-02-20 | 株式会社村田制作所 | High frequency module, and mobile communicaltion device using same |
| CN1398048A (en) * | 2001-07-13 | 2003-02-19 | 株式会社村田制作所 | Compound high frequency switch and high frequency module and communicator |
| CN1555607A (en) * | 2001-09-18 | 2004-12-15 | �ʼҷ����ֵ��ӹɷ�����˾ | Rf signal switch for a wireless communication device |
| CN1875550A (en) * | 2003-11-11 | 2006-12-06 | 株式会社村田制作所 | High frequency module |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2002064400A (en) * | 2000-06-09 | 2002-02-28 | Hitachi Metals Ltd | High frequency switch module |
| WO2008004557A1 (en) * | 2006-07-03 | 2008-01-10 | Hitachi Metals, Ltd. | Branch circuit, high frequency circuit and high frequency module |
-
2010
- 2010-03-02 CN CN201080010829.XA patent/CN102342028B/en not_active Expired - Fee Related
- 2010-03-02 JP JP2011502753A patent/JP5201260B2/en not_active Expired - Fee Related
- 2010-03-02 WO PCT/JP2010/053284 patent/WO2010101130A1/en active Application Filing
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1336731A (en) * | 2000-07-27 | 2002-02-20 | 株式会社村田制作所 | High frequency module, and mobile communicaltion device using same |
| CN1398048A (en) * | 2001-07-13 | 2003-02-19 | 株式会社村田制作所 | Compound high frequency switch and high frequency module and communicator |
| CN1555607A (en) * | 2001-09-18 | 2004-12-15 | �ʼҷ����ֵ��ӹɷ�����˾ | Rf signal switch for a wireless communication device |
| CN1875550A (en) * | 2003-11-11 | 2006-12-06 | 株式会社村田制作所 | High frequency module |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105379129A (en) * | 2013-07-16 | 2016-03-02 | 株式会社村田制作所 | Front end circuit |
| CN107453763A (en) * | 2016-05-17 | 2017-12-08 | 株式会社村田制作所 | Switch module and high-frequency model |
Also Published As
| Publication number | Publication date |
|---|---|
| JPWO2010101130A1 (en) | 2012-09-10 |
| CN102342028B (en) | 2015-02-18 |
| JP5201260B2 (en) | 2013-06-05 |
| WO2010101130A1 (en) | 2010-09-10 |
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