CN102342028B - High frequency module - Google Patents
High frequency module Download PDFInfo
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- CN102342028B CN102342028B CN201080010829.XA CN201080010829A CN102342028B CN 102342028 B CN102342028 B CN 102342028B CN 201080010829 A CN201080010829 A CN 201080010829A CN 102342028 B CN102342028 B CN 102342028B
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- diode
- electricity container
- switching circuit
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- 239000003990 capacitor Substances 0.000 claims abstract description 101
- 230000005611 electricity Effects 0.000 claims description 66
- 239000004744 fabric Substances 0.000 claims description 6
- 238000002955 isolation Methods 0.000 abstract description 23
- 239000000758 substrate Substances 0.000 description 41
- 230000005540 biological transmission Effects 0.000 description 29
- 230000000052 comparative effect Effects 0.000 description 14
- 101100381996 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) BRO1 gene Proteins 0.000 description 8
- 101000702394 Homo sapiens Signal peptide peptidase-like 2A Proteins 0.000 description 7
- 101100058964 Arabidopsis thaliana CALS5 gene Proteins 0.000 description 6
- 101100388543 Caenorhabditis elegans glt-1 gene Proteins 0.000 description 6
- 238000010586 diagram Methods 0.000 description 6
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- 230000015572 biosynthetic process Effects 0.000 description 4
- 230000001939 inductive effect Effects 0.000 description 4
- 230000005012 migration Effects 0.000 description 3
- 238000013508 migration Methods 0.000 description 3
- 230000001629 suppression Effects 0.000 description 3
- 101100058970 Arabidopsis thaliana CALS11 gene Proteins 0.000 description 2
- 101000702393 Homo sapiens Signal peptide peptidase-like 2B Proteins 0.000 description 2
- 101100341076 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) IPK1 gene Proteins 0.000 description 2
- 230000003071 parasitic effect Effects 0.000 description 2
- 102100025961 Glutaminase liver isoform, mitochondrial Human genes 0.000 description 1
- 101000856993 Homo sapiens Glutaminase liver isoform, mitochondrial Proteins 0.000 description 1
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Classifications
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
- H04B1/0053—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band
- H04B1/006—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with common antenna for more than one band using switches for selecting the desired band
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
- H03J5/00—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner
- H03J5/24—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection
- H03J5/242—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection used exclusively for band selection
- H03J5/244—Discontinuous tuning; Selecting predetermined frequencies; Selecting frequency bands with or without continuous tuning in one or more of the bands, e.g. push-button tuning, turret tuner with a number of separate pretuned tuning circuits or separate tuning elements selectively brought into circuit, e.g. for waveband selection or for television channel selection used exclusively for band selection using electronic means
Abstract
The present invention aims to provide a high frequency module which is able to secure isolation between desired signals without the addition of a new switch circuit and filter. The high frequency module (1) is provided with a low pass filter (LPF1) and a filter adjusting capacitor (CCC). The signal line that connects an antenna port (ANT) to a signal port (1800/1900-Tx) is connected to a switch circuit (SW1) which controls the propagation of signals to the signal port, is connected to a low pass filter (LPF1) at the signal port side of the switch circuit (SW1), and is connected to a first end of a filter adjusting capacitor (CCC) at the signal port side of the low pass filter (LPF1). The signal line that connects the antenna port (ANT) to a signal port (1900-Rx) is connected to switch circuits (SW2, SW4) which control the propagation of signals to the signal port. The second end of the filter adjusting capacitor (CCC) is connected to an anode of a diode (DD2) of the switch circuit (SW2).
Description
Technical field
The high-frequency model that the leading section etc. that the present invention relates to portable phone adopts.
Background technology
In order to enable portable phone use in multiple communication systems that frequency band is different, at the high-frequency model (such as with reference to Fig. 2 of patent documentation 1) that the leading section etc. of portable phone adopts multifrequency corresponding sometimes.
The high-frequency model that above-mentioned patent documentation discloses is the module of the corresponding type of three frequencies utilizing these three communication systems of PCS, DCS, EGSM.This high-frequency model comprises the many signal line connecting independent signal input/output port and common antenna port.Common antenna port is connected with duplexer.The signal of PCS and DCS is separated with the signal of EGSM by duplexer.In addition, branched portion holding wire being positioned at duplexer rear class comprises the 1st and the 2nd diode.A holding wire of the 1st diode and fork is connected in series.Another root holding wire of 2nd diode and fork is connected in parallel.In addition, transmit in the holding wire of transmission signal and there is low pass filter.The high order harmonic component sending signal removed by low pass filter.
1st and the 2nd diode of each branched portion synchronously carries out conduction and cut-off switching.When making the 1st diode and the 2nd diode current flow, inductive component and the capacitor of the 2nd diode form series resonant circuit.Set and observe from branched portion the impedance being provided with the holding wire of the 2nd diode, make to become infinitely great when the frequency of the signal by a square signal line produces series resonance.Thereby, it is possible to suppress the holding wire transmission unwanted signal to being provided with the 2nd diode.In addition, when the 1st and the 2nd diode cut-off, the 1st diode disconnects.Thereby, it is possible to suppress the holding wire transmission unwanted signal to being provided with the 1st diode.
This high-frequency model, the signal line side for transmitting PCS and DCS signal that is positioned at duplexer rear class, at the branched portion of the first order, the Received signal strength of PCS and DCS is separated with transmission signal.Then, the branched portion of the second level is set in the holding wire of Received signal strength transmitting PCS and DCS.Thus, by the switch of each branched portion is set to suitable timing, thus can guarantee that the PCS of the part overlap of frequency band sends the isolation between signal (1850 ~ 1910MHz) and DCS Received signal strength (1805 ~ 1880MHz).
Prior art document
Patent documentation
Patent documentation 1: Japanese Patent Laid-Open 2004-128799 publication
Summary of the invention
Portable telephone communication system shifts from GPRS mode to EDGE mode.Therefore, except needing to improve the isolation between the PCS transmission signal of frequency band coincidence and DCS Received signal strength, also need to improve the isolation between the transmission signal (1850 ~ 1910MHz) of the PCS that frequency band does not overlap and Received signal strength (1930 ~ 1990).
But, in existing circuit structure, be difficult to guarantee that PCS sends the isolation between signal and DCS Received signal strength, while also improved by the isolation between the transmission signal of PCS and Received signal strength than the height of GPRS mode.
Add switching circuit or filter if suppose to existing circuit structure, then can improve the isolation between the transmission signal of PCS and Received signal strength.But in this case, additional switching circuit or filter may cause being reduced by characteristic and causing the maximization of module size of each holding wire.The problems referred to above can occur when not only adding switching circuit or filter at the isolation in order to improve between the transmission signal of PCS and Received signal strength, occur when also can add switching circuit or filter at the isolation improved between arbitrary signal.
Therefore, the object of the present invention is to provide a kind of high-frequency model, this high-frequency model does not add new switching circuit for improving the isolation between desired signal or filter in circuit structure, just can guarantee the isolation between desired signal.
High-frequency model of the present invention comprises multiple independent signal input/output port, common antenna port, switching circuit, the first holding wire and secondary signal line, also comprises Filter and Filltering device adjustment electricity container.Switching circuit switches the connection between common antenna port and multiple independent signal input/output port.First and second holding wire connects independent signal input/output port and common antenna port.Switching circuit comprises the switch element connecting first and second holding wire respectively.Filters in series is connected to the position of link position closer to independent signal input/output port side of the ratio switching circuit of the first holding wire.The first end of filter adjustment electricity container is connected to the position of link position closer to independent signal input/output port side of the ratio filter of the first holding wire.In addition, its second end is connected on the switch element that is connected with secondary signal line.
In the structure shown here, when filter being adjusted electricity container and being connected with secondary signal line, form the inductor of filter and filter and adjust the parallel circuits that electricity container forms and produce resonance.Therefore, utilize these two resonance of resonance of this resonance and filter monomer, the change desired by frequency characteristic generation of high-frequency model can be made.Specifically, by the capacitance of setting filter adjustment electricity container, thus the frequency band that the signal transmitted along the first holding wire can be guaranteed, the attenuation of the frequency band of signal that transmits along secondary signal line.Thereby, it is possible to improve the signal that transmits along the first holding wire and isolation between the signal transmitted along secondary signal line.
Filter of the present invention also can comprise the parallel resonant capacitor and parallel resonant inductor device that are connected in parallel, and the resonance frequency of parallel resonance parallel resonant inductor device and parallel resonant capacitor produced is set as the frequency of the high order harmonic component of the signal transmitted along the first holding wire.Utilize this structure, the high order harmonic component in the first holding wire can be removed.In addition, also the resonance frequency of the resonant circuit be made up of filter adjustment electricity container and parallel resonant inductor device can be set as the first-harmonic of the signal transmitted along the first holding wire or the frequency of high order harmonic component.Thereby, it is possible to improve the signal that transmits along the first holding wire and isolation between the signal transmitted along secondary signal line.
Also can be the switch element be connected with the first holding wire of the present invention be the 1st diode, the switch element be connected with secondary signal line be the 2nd diode.The anode of the 1st diode is connected with the common antenna port side of the first holding wire, and negative electrode is connected with independent signal input/output port side.The negative electrode of the 2nd diode is connected with secondary signal line, and negative electrode is connected with control terminal.The anode of the 2nd diode is by series resonance capacitor ground connection.In addition, the second end of filter adjustment electricity container is connected to the link position of the 2nd diode and series resonance capacitor.
According to this structure, by applying bias voltage from control terminal, make the diode current flow be connected with secondary signal line, thus the diode also conducting that is connected with the first holding wire can be made.Now, in the switching circuit be connected with secondary signal line, produce series resonance, utilize this series resonance, the signal to secondary signal line will be flowed into can be suppressed to transmit.In addition, end by making the diode be connected with secondary signal line, thus the diode be connected with the first holding wire is also ended, when cutting off the connection of secondary signal line and filter adjustment electricity container, secondary signal line transmission signal can be made.Thus, cut off the connection of filter adjustment electricity container when secondary signal line transmission signal, filter adjustment electricity container can be removed on the impact by characteristic of secondary signal line.
In high-frequency model of the present invention, preferably make to form the pattern electrode at least partially of parallel resonant capacitor, the pattern electrode at least partially of series resonance capacitor is relative in the interarea normal direction of multilager base plate with forming, form filter and adjust electricity container.In addition, preferably make the cloth line electrode that is connected with parallel resonant capacitor relative in the interarea normal direction of multilager base plate with the cloth line electrode that is connected with series resonance capacitor, form filter adjustment electricity container.
Thus, form filter adjustment electricity container, thus can the increase of both suppression module sizes, filter adjustment electricity container is set again.In addition, can the parasitic capacitance that produces of connecting wiring of rejects trap adjustment electricity container, the series resonance of series resonance capacitor and diode can be made to stablize, the variation by characteristic of suppression secondary signal line.
According to the present invention, adjusting capacitance by arranging filter adjustment electricity container, the change desired by frequency characteristic generation of high-frequency model can be made.Specifically, the isolation between the first holding wire and secondary signal line that electricity container is connected can be guaranteed to adjust with filter.
Accompanying drawing explanation
Fig. 1 is the schematic circuit diagram of the high-frequency model involved by embodiments of the present invention 1.
Fig. 2 is the performance plot of the high-frequency model shown in Fig. 1.
Fig. 3 is the stacked figure of the high-frequency model shown in Fig. 1.
Fig. 4 is the stacked figure of the high-frequency model shown in Fig. 1.
Fig. 5 is the schematic circuit diagram of the high-frequency model involved by embodiments of the present invention 2.
Fig. 6 is the performance plot of the high-frequency model shown in Fig. 5.
Fig. 7 is the schematic circuit diagram of the high-frequency model involved by embodiments of the present invention 3.
Fig. 8 is the performance plot of the high-frequency model shown in Fig. 7.
Reference numeral
1 high-frequency model
DPX duplexer
HPF high pass filter
LPF, LPF1, LPF2 low pass filter
11A ~ 11C branched portion
SW1 ~ SW6 switching circuit
DD1, DD2, GD1, GD2, PD1, PD2 diode
CCC filter adjustment electricity container
Embodiment
Below, the structure example of the high-frequency model involved by embodiments of the present invention 1 is described.
The high-frequency model of present embodiment is applied to the leading section of the portable phone of EDGE mode, is corresponding to utilizing the corresponding pattern block of three of these three communication systems of PCS, DCS, EGSM frequencies.
Fig. 1 is the schematic circuit diagram of the high-frequency model involved by present embodiment.
High-frequency model 1 comprises duplexer DPX, branched portion 11A ~ 11C, low pass filter LPF1, LPF2 and filter adjustment electricity container CCC.In addition, as external connection port, comprising: the antenna port ANT being equivalent to common antenna port of the present invention; Be equivalent to signal port 1800/1900-Tx, 1900-Rx, 1800-Rx, 850/900-Tx, 850/900-Rx of independent signal input/output port of the present invention; And be equivalent to the control port Vc1 ~ Vc3 of control terminal of the present invention.
Duplexer DPX comprises low pass filter LPF and high pass filter HPF, and low pass filter LPF is connected with antenna port ANT by stopping direct current electricity container with the tie point of high pass filter HPF.The low pass filter LPF of duplexer DPX makes the signal of EGSM pass through, and makes the signal attenuation of PCS and DCS.In addition, high pass filter HPF makes the signal of PCS and DCS pass through, and makes the signal attenuation of EGSM.
Low pass filter LPF is connected between antenna port ANT and branched portion 11C.This low pass filter LPF comprises capacitor Ct1, inductor Lt1 and capacitor Cu1, forms the low pass filter signal band of EGSM being set to passband.The first end of inductor Lt1 is connected with antenna port ANT, and the second end is connected with branched portion 11C.Capacitor Ct1 and inductor Lt1 is connected in parallel.Second end of inductor Lt1 is by capacitor Cu1 ground connection.
High pass filter HPF is connected between antenna port ANT and branched portion 11A.This high pass filter HPF comprises capacitor Cc1, Cc2, inductor Lt2 and capacitor Ct2, forms the high pass filter signal band of PCS and DCS being set to passband.The first end of capacitor Cc1 is connected with antenna port ANT, and the second end is connected with capacitor Cc2.The first end of capacitor Cc2 is connected with capacitor Cc1, and the second end is connected with branched portion 11A.The first end of inductor Lt2 is connected with the first end of capacitor Cc2 with second end of capacitor Cc1.Second end of inductor Lt2 is by capacitor Ct2 ground connection.
Branched portion 11C comprises switching circuit SW5, SW6, and switching circuit SW5 is connected with low pass filter LPF with the tie point of switching circuit SW6.Branched portion 11C switches EGSM based on the voltage being input to control port Vc1 from outside and sends state and EGSM accepting state.
Switching circuit SW5 is connected between low pass filter LPF and low pass filter LPF2.This switching circuit SW5 comprises diode GD1 and inductor GSL1.The anode of diode GD1 is connected with low pass filter LPF, and negative electrode is connected with low pass filter LPF2.The negative electrode of diode GD1 is by inductor GSL1 ground connection.
Switching circuit SW6 is connected between low pass filter LPF and signal port 850/900-Rx.This switching circuit SW6 comprises inductor GSL2, capacitor GCu3, diode GD2, capacitor GC5 and resistor Rg.The first end of inductor GSL2 is connected with low pass filter LPF, and the second end is connected with signal port 850/900-Rx by stopping direct current electricity container.Second end of inductor GSL2 by capacitor GCu3 ground connection, and is connected with the negative electrode of diode GD2.The anode of diode GD2 is connected with control port Vc1 by resistor Rg, and by capacitor GC5 ground connection.
Branched portion 11C is when EGSM sends state, and switching circuit SW6 suppresses to transmit the transmission signal of EGSM, and switching circuit SW5 transmits the transmission signal of EGSM.Now, by applying voltage from control port Vc1, thus the voltage higher than switching voltage is applied to the anode of diode GD2.Therefore, diode GD2 conducting, second end of inductor GSL2 is by capacitor GC5 ground connection, and inductive component and the capacitor GC5 of diode GD2 carry out series resonance.The line length of inductor GLS2 is set as the length of about 1/4 of the wavelength of the transmission signal band of EGSM, due to the diode GD2 side of inductor GSL2 because of series resonance ground connection, becoming impedance when being therefore set as from switching circuit SW5 side to observe inductor GSL2 side is infinitely-great open-circuit condition.Thus, the transmission signal of switching circuit SW6 to EGSM can be suppressed to transmit.On the other hand, in switching circuit SW5, the anode to diode GD1 applies the voltage higher than switching voltage.Therefore, diode GD1 conducting, switching circuit SW5 transmits the transmission signal of EGSM.
Branched portion 11C is when EGSM accepting state, and switching circuit SW6 transmits the Received signal strength of EGSM, and switching circuit SW5 suppresses to transmit the Received signal strength of EGSM.Now, by applying voltage from control port Vc1, thus the voltage lower than switching voltage is applied to the anode of diode GD2.Therefore, diode GD2 ends.Thus, switching circuit SW6 transmits the Received signal strength of EGSM.On the other hand, in switching circuit SW5, the anode to diode GD1 applies the voltage lower than switching voltage.Therefore, diode GD1 ends, and suppresses the Received signal strength of switching circuit SW5 to EGSM to transmit.
Low pass filter LPF2 is connected between switching circuit SW5 and signal port 850/900-Tx.This low pass filter LPF2 comprises inductor GLt1, capacitor GCc1 and capacitor GCu1, GCu2, forms the second harmonic of transmission signal and the low pass filter of third-harmonic component of removing EGSM.The first end of inductor GLt1 is connected with switching circuit SW5, and the second end is connected with signal port 850/900-Tx by stopping direct current electricity container.Capacitor GCc1 and inductor GLt1 is connected in parallel.The first end of inductor GLt1 is by capacitor GCu1 ground connection.Second end of inductor GLt1 is by capacitor GCu2 ground connection.
Branched portion 11A comprises switching circuit SW1, SW2, and switching circuit SW1 is connected with high pass filter HPF with the tie point of switching circuit SW2.Branched portion 11A switches transmission state and accepting state based on the voltage being input to control port Vc2 from outside.
Switching circuit SW1 is connected between high pass filter HPF and low pass filter LPF1.This switching circuit SW1 comprises diode DD1, inductor DPSLt, capacitor DPCt1 and inductor DPSL1.The anode of diode DD1 is connected with high pass filter HPF, and negative electrode is connected with low pass filter LPF1.The first end of inductor DPSLt is connected with the anode of diode DD1, and the second end is connected with the first end of capacitor DPCt1.The first end of capacitor DPCt1 is connected with the first end of inductor DSLt, and the second end is connected with the negative electrode of diode DD1.The negative electrode of diode DD1 is by inductor DPSL1 ground connection.
Switching circuit SW2 is connected between high pass filter HPF and branched portion 11B.This switching circuit SW2 comprises inductor DSL2, capacitor CDPr, capacitor DCu4, diode DD2, capacitor DC5 and resistor Rd.The first end of capacitor DSL2 is connected with high pass filter HPF, and the second end is connected with the negative electrode of diode DD2 with the first end of capacitor CDPr.Second end of capacitor CDPr by capacitor DCu4 ground connection, and is connected with branched portion 11B.The anode of diode DD2 is connected with control port Vc2 by resistor Rd, and by being equivalent to the capacitor DC5 ground connection of series resonance capacitor of the present invention, the second end adjusting electricity container CCC with the filter hereafter described in detail is connected.
Branched portion 11A is when the state of transmission, and switching circuit SW2 suppresses to transmit the transmission signal of PCS and DCS, and switching circuit SW1 transmits the transmission signal of PCS and DCS.Now, by applying voltage from control port Vc2, thus the voltage higher than switching voltage is applied to the anode of diode DD2.Therefore, diode DD2 conducting, second end of inductor DSL2 is by capacitor DC5 ground connection, and inductive component and the capacitor DC5 of diode DD2 carry out series resonance.The line length of inductor DSL2 is set as the length of about 1/4 of the wavelength of the transmission signal band of PCS and DCS, due to the diode DD2 side of inductor DSL2 because of series resonance ground connection, becoming impedance when being therefore set as from switching circuit SW1 side to observe inductor DSL2 side is infinitely-great open-circuit condition.Thus, the transmission signal of switching circuit SW2 to PCS and DCS can be suppressed to transmit.On the other hand, in switching circuit SW1, the anode to diode DD1 applies the voltage higher than switching voltage.Therefore, diode DD1 conducting, switching circuit SW1 transmits the transmission signal of PCS and DCS.
Branched portion 11A is when accepting state, and switching circuit SW2 transmits the Received signal strength of PCS and DCS, and switching circuit SW1 suppresses to transmit the Received signal strength of PCS and DCS.Now, by applying voltage from control port Vc2, thus the voltage lower than switching voltage is applied to the anode of diode DD2.Therefore, diode DD2 ends.Thus, switching circuit SW2 transmits the Received signal strength of PCS and DCS.On the other hand, in switching circuit SW1, the anode to diode DD1 applies the voltage lower than switching voltage.Therefore, diode DD1 ends, and switching circuit SW1 suppresses to transmit the Received signal strength of PCS and DCS.
Low pass filter LPF1 is connected between switching circuit SW1 and signal port 1800/1900-Tx.This low pass filter LPF1 comprises inductor DLt1, DLt2, capacitor DCc1 and capacitor DCu1, DCu2, forms the second harmonic of transmission signal and the low pass filter of third-harmonic component of removing PCS and DCS.Inductor DLt1 is equivalent to parallel resonant inductor device of the present invention, and first end is connected with switching circuit SW1, and the second end is connected with the first end of inductor DLt2.The first end of inductor DLt2 is connected with the first end of inductor DLt1, and second end of inductor DLt2 is connected with signal port 1800/1900-Tx by stopping direct current electricity container.Capacitor DCc1 is equivalent to parallel resonant capacitor of the present invention, is connected in parallel with inductor DLt1.The first end of inductor DLt1 is by capacitor DCu1 ground connection.Second end of inductor DLt1 by capacitor DCu2 ground connection, and is connected with the first end that filter described later adjusts electricity container CCC.
Branched portion 11B comprises switching circuit SW3, SW4, and switching circuit SW3 is connected with switching circuit SW2 with the tie point of switching circuit SW4.Branched portion 11B switches PCS accepting state and DCS accepting state based on the voltage being input to control port Vc3 from outside.
Switching circuit SW3 is connected between switching circuit SW2 and signal port 1900-Rx.This switching circuit SW3 comprises diode PD1, inductor PSL1 and capacitor PCu3.The anode of diode PD1 is connected with switching circuit SW2, and negative electrode is connected with signal port 1900-Rx by stopping direct current electricity container.The negative electrode of diode PD1 passes through inductor PSL1 ground connection, by capacitor PCu3 ground connection.
Switching circuit SW4 is connected between switching circuit SW2 and signal port 1800-Rx.This switching circuit SW4 comprises inductor PSL2, capacitor DCu3, diode PD2, capacitor PC5 and resistor Rp.The first end of inductor PSL2 is connected with switching circuit SW2, and the second end is connected with signal port 1800-Rx by stopping direct current electricity container.Second end of inductor PSL2 by capacitor DCu3 ground connection, and is connected with the negative electrode of diode PD2.The anode of diode PD2 is connected with control port Vc3 by resistor Rp, and by capacitor PC5 ground connection.
Branched portion 11B is when PCS accepting state, and switching circuit SW4 suppresses to transmit the Received signal strength of PCS, and switching circuit SW3 transmits the Received signal strength of PCS.Now, by applying voltage from control port Vc3, thus the voltage higher than switching voltage is applied to the anode of diode PD2.Therefore, diode PD2 conducting, second end of inductor PSL2 is by capacitor PC5 ground connection, and inductive component and the capacitor PC5 of diode PD2 carry out series resonance.The line length of inductor PSL2 is set as the length of about 1/4 of the wavelength of the Received signal strength frequency band of PCS, due to the diode PD2 side of inductor PSL2 because of series resonance ground connection, therefore, becoming impedance when being set as from switching circuit SW3 side to observe inductor PSL2 side is infinitely-great open-circuit condition.Thus, the Received signal strength of switching circuit SW4 to PCS can be suppressed to transmit.On the other hand, in switching circuit SW3, the anode to diode PD1 applies the voltage higher than switching voltage.Therefore, diode PD1 conducting, switching circuit SW3 transmits the Received signal strength of PCS.
Branched portion 11B is when DCS accepting state, and the Received signal strength of switching circuit SW4 to DCS transmits, and switching circuit SW3 suppresses to transmit the Received signal strength of DCS.Now, by applying voltage from control port Vc3, thus the voltage lower than switching voltage is applied to the anode of diode PD2.Therefore, diode PD2 ends.Thus, switching circuit SW4 transmits the Received signal strength of DCS.On the other hand, in switching circuit SW3, the anode to diode PD1 applies the voltage lower than switching voltage.Therefore, diode PD1 ends, and suppresses the Received signal strength of switching circuit SW3 to DCS to transmit.
Herein, as filter adjustment electricity container CCC, the capacitance being approximately 0.2pF is adopted.The first end of filter adjustment electricity container CCC compares low pass filter LPF1, the LC antiresonant circuit that is made up of inductor DLt1 and capacitor DCc1 is connected to closer to signal port 1800/1900-Tx side.In addition, its second end is connected with the anode of the diode DD2 being arranged at switching circuit SW2.Thus, in branched portion 11A, between diode DD2 conducting, the transmission state that is connected with second end of inductor DSL2 of filter adjustment electricity container CCC, the inductor DLt1 of low pass filter LPF1 and filter adjust the parallel circuits that electricity container CCC forms and produce resonance.Therefore, utilize this resonance, the change desired by frequency characteristic generation of high-frequency model can be made.
In addition, if the capacitance value of filter adjustment electricity container CCC is excessive, then may be worsened by characteristic between the isolation between the holding wire connected by filter adjustment electricity container CCC, each holding wire.Therefore, the capacitance preferably filter being adjusted electricity container CCC sets very little, be preferably such as 0.1pF ~ 0.6pF, thus, by reducing the capacitance of filter adjustment electricity container CCC, come suitably to correct the circuit constant etc. of low pass filter LPF1, thus the change desired by frequency characteristic generation of high-frequency model can be made.
In said structure, low pass filter LPF1 is equivalent to the switching circuit SW1 that compares of the present invention and is connected in series in filter of the present invention closer to signal port 1800/1900-Tx side.And the holding wire connecting antenna port ANT and signal port 1800/1900-Tx is equivalent to the first holding wire of the present invention.In addition, connect antenna port ANT and be equivalent to secondary signal line of the present invention with the holding wire of signal port 1900-Rx respectively with the holding wire being connected antenna port ANT and signal port 1800-Rx.
Fig. 2 is the performance plot that citing illustrates the frequency characteristic of the high-frequency model involved by present embodiment.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example not being provided with filter adjustment electricity container CCC.
Fig. 2 (A) is the performance plot by characteristic that citing illustrates between antenna port ANT and signal port 1800/1900-Tx.Passing through in characteristic between these ports, in this structure example, the attenuation pole of the high frequency side of passband is positioned at about 3.37GHz.On the other hand, in comparative structure example, the attenuation pole of the high frequency side of passband is positioned at about 3.57GHz.The attenuation pole of the high frequency side of these passbands is frequencies that the high order harmonic component of PCS signal and DCS signal is cut off because of the Main Function of low pass filter LPF1.In this structure example, the frequency of the attenuation pole of the high frequency side of passband is compared comparative structure example and obvious migration is not occurred, even if but it is possible to confirm that arranging filter adjustment electricity container CCC also can end the high order harmonic component of the signal transmitted by signal port 1800/1900-Tx fully.
It can thus be appreciated that what be provided with the holding wire of low pass filter LPF1 is subject to the resonance of low pass filter LPF1 monomer and the impact of filter adjustment electricity container CCC by characteristic.But the impact being subject to filter adjustment electricity container CCC is less than the impact of the resonance being subject to low pass filter LPF1 monomer, even if therefore arrange filter adjustment electricity container CCC, also too large infringement can not be caused to this holding wire by characteristic.Therefore, according to the present invention, can not damage the first holding wire by characteristic while, improve the signal that transmits along the first holding wire and isolation between the signal transmitted along secondary signal line.
Fig. 2 (B) and Fig. 2 (C) is the performance plot that citing illustrates the isolation characteristic between signal port 1800/1900-Tx and signal port 1900-Rx.In frequency characteristic between these ports, in comparative structure example, the attenuation pole caused by low pass filter LPF1 monomer is positioned at the frequency roughly the same with the attenuation pole of the frequency characteristic shown in the dotted line of Fig. 2 (A) and about 3.57GHz.On the other hand, in this structure example, the attenuation pole caused by low pass filter LPF1 monomer be positioned at than the frequency characteristic shown in the solid line of Fig. 2 (A) attenuation pole will low about 370MHz about 3.00GHz (with reference to Fig. 2 (B) solid line).In this structure example, by arranging filter adjustment electricity container CCC, thus another antiresonant circuit can be formed together with forming the inductor DLt1 of low pass filter LPF, thus can in the frequency characteristic between signal port 1800/1900-Tx and signal port 1900-Rx, what the frequency of the attenuation pole of the high frequency side of passband be reduced to frequently compared with structure example is little.And, can confirm: although almost do not decay near about 1.71GHz in comparative structure example, in this structure example, can significantly decay in its vicinity.Thus, although in comparative structure example, at the frequency band throughout about 1.71GHz ~ about 1.91GHz, the attenuation that can guarantee is about 23.9dB, but in this structure example, at the frequency band throughout about 1.71GHz ~ about 1.91GHz, the attenuation of about 31.1dB can be guaranteed.That is, the attenuation of the frequency band (1850 ~ 1910MHz) can guaranteed at the transmission signal of PCS is about 31.1dB, can improve the isolation between signal port 1800/1900-Tx and signal port 1900-Rx.
Fig. 3,4 is stacked figure of the high-frequency model involved by present embodiment.Fig. 3 (A) to (O), Fig. 4 (P) to (Y) are to look up the upward view of substrate (A) to (Y) with the order from orlop to the superiors.In addition, Fig. 4 (Z) is the vertical view that the substrate (Y) of the superiors to multilager base plate is overlooked.In addition, the through hole electrode of substrate (A) ~ (Y) uses circular icon representation in the drawings.
Substrate (A) is laminated in the orlop of multilager base plate, and its lower surface is the installed surface of high-frequency model, is formed with multiple installing electrodes.Arrow shown in figure illustrates the port name of installing electrodes.
Substrate (B) is layered in the second layer from the orlop of multilager base plate, and the lower surface of substrate is provided with internal layer grounding electrode, and substrate inside is provided with through hole electrode.
Substrate (C) is layered in the third layer from the orlop of multilager base plate, base lower surface is provided with the pattern electrode forming capacitor GCu3 and the pattern electrode forming capacitor GC5, substrate inside is provided with through hole electrode.
Substrate (D) is layered in the 4th layer from the orlop of multilager base plate, the lower surface of substrate is provided with internal layer grounding electrode, substrate inside is provided with through hole electrode.Capacitor GCu3, GC5 is formed at the grounding electrode of substrate (D) and between the grounding electrode of substrate (B) and the pattern electrode being clipped in the substrate (C) between two grounding electrodes.
Substrate (E) is layered in the layer 5 from the orlop of multilager base plate, base lower surface is provided with the pattern electrode forming capacitor PC5, the pattern electrode forming capacitor GC5, forms the pattern electrode of capacitor DC5 and form the pattern electrode of capacitor GCu2, substrate inside is provided with through hole electrode.
Substrate (F) is layered in the layer 6 from the orlop of multilager base plate, is provided with the pattern electrode and internal layer grounding electrode that form capacitor DCu2, substrate inside is provided with through hole electrode at base lower surface.Capacitor PC5, GC5, DC5, GCu2 is formed at the grounding electrode of substrate (F) and between the grounding electrode of substrate (D) and the pattern electrode being clipped in the substrate (E) between two grounding electrodes.
Herein, the pattern electrode of the formation capacitor DC5 of substrate (E) is relative across substrate (E) with the pattern electrode of the formation capacitor DCu2 of substrate (F), plays the function as filter adjustment electricity container CCC by the overlap of these pattern electrodes.
Substrate (G) is layered in the layer 7 from the orlop of multilager base plate, base lower surface is provided with the pattern electrode forming capacitor Ct2, the pattern electrode forming capacitor Cu1, forms the pattern electrode of capacitor DCu2 and form the pattern electrode of capacitor GCu1, substrate inside is provided with through hole electrode.
Substrate (H) is layered in the 8th layer from the orlop of multilager base plate, the lower surface of substrate is provided with internal layer grounding electrode, substrate inside is provided with through hole electrode.Capacitor Ct2, Cu1, DCu2, GCu1 is formed between this grounding electrode and the pattern electrode being formed at substrate (G).
Substrate (I) is layered in the 9th layer from the orlop of multilager base plate, base lower surface is provided with the pattern electrode forming capacitor DCu4 and the pattern electrode forming capacitor DCu1, and forms capacitor DCu4, DCu1 between the grounding electrode being formed at substrate (H).In substrate inside, through hole electrode is set.
Substrate (J) is layered in the tenth layer from the orlop of multilager base plate, and substrate inside is provided with through hole electrode.
Substrate (K) ~ (Y) is layered in the 11 ~ 25 layer from the orlop of multilager base plate, is provided with the multiple pattern electrodes forming multiple inductor, substrate inside is provided with through hole electrode at base lower surface.Multiple surface electrodes of the circuit element connecting discrete component are provided with at the upper surface of substrate (Y).
As in the present embodiment, the pattern electrode of the pattern electrode of the formation capacitor DC5 of substrate (E) and the formation capacitor DCu2 of substrate (F) is made to play the function adjusting electricity container CCC as filter, thus can not need to arrange the pattern electrode adjusting electricity container CCC for forming filter in addition, can increase by suppression module volume.In addition, due to without the need to the line electrode for connecting filter adjustment electricity container CCC and other circuit elements, therefore, it is possible to suppress to produce unnecessary parasitic capacitance, the series resonance of capacitor DC5 and diode DD2 can be made to stablize, the variation by characteristic of secondary signal line can be suppressed.
In addition, by making and the cloth line electrode that capacitor DC5 is connected and relative with the cloth line electrode that capacitor DCu2 is connected, thus filter adjustment electricity container CCC can also be formed.In addition, as in the present embodiment, by grounding electrode being configured in the orlop of multilager base plate or the layer near it, thus can suppress to produce stray inductance in grounding electrode portion.Therefore, by being configured near grounding electrode by electrode for capacitors, thus the stray inductance that produces in the capacitor of at one end ground connection can be reduced, the Q value of above-mentioned series resonance can be improved, the isolation between the first holding wire and secondary signal line can be improved.
Next, the structure example of the high-frequency model involved by embodiments of the present invention 2 is described.In the following description, identical label is added to the structure identical with the high-frequency model involved by execution mode 1, and omits the description.
Fig. 5 is the schematic circuit diagram of the high-frequency model involved by present embodiment.In the present embodiment, filter is adjusted the first end of electricity container CCC to be connected with second end of the inductor DLt2 of low pass filter LPF1.Even if employing foregoing circuit, also the present invention can be implemented well.
Fig. 6 is the performance plot that citing illustrates the frequency characteristic of the high-frequency model involved by present embodiment.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example not being provided with filter adjustment electricity container CCC.
Fig. 6 (A) is the performance plot by characteristic that citing illustrates between antenna port ANT and signal port 1800/1900-Tx.Passing through in characteristic between these ports, the attenuation pole of the high frequency side of the passband of this structure example and comparative structure example is all positioned at about 3.03GHz.Can confirm in this structure example, the frequency of the attenuation pole of the high frequency side of passband is compared with comparative structure example, there is not obvious migration, even if arrange filter adjustment electricity container CCC, can end the high order harmonic component of the signal transmitted by signal port 1800/1900-Tx fully yet.
Fig. 6 (B) citing illustrates the performance plot of the isolation characteristic between signal port 1800/1900-Tx and signal port 1900-Rx.In the isolation characteristic of these ports, in comparative structure example, at the frequency band throughout about 1.71GHz ~ about 1.91GHz, the attenuation that can guarantee is about 22.5dB, but in this structure example, comprise PCS transmission signal frequency band in the frequency band of the 1.91GHz of about 1.71GHz ~ approximately, the attenuation of about 31.1dB can be guaranteed.
Next, the structure example of the high-frequency model involved by embodiments of the present invention 3 is described.In the following description, identical label is added to the structure identical with the high-frequency model involved by execution mode 1, and omits the description.
Fig. 7 is the schematic circuit diagram of the high-frequency model involved by present embodiment.In the present embodiment, filter is adjusted the first end of electricity container CCC to be connected with second end of the inductor GLt1 of low pass filter LPF2.Then, filter is adjusted second end of electricity container CCC to be connected with the anode of the diode GD2 of switching circuit SW6.Herein, filter adjustment electricity container CCC can suitably be implemented.
Fig. 8 is the performance plot that citing illustrates the frequency characteristic of the high-frequency model involved by present embodiment.In addition, represent the data of this structure example in the drawings with solid line, be represented by dotted lines the data of the comparative structure example not being provided with filter adjustment electricity container CCC.
Fig. 8 (A) is the performance plot by characteristic that citing illustrates between antenna port ANT and signal port 850/900-Tx.Passing through in characteristic between these ports, the attenuation pole of the high frequency side of the passband of this structure example and comparative structure example is all positioned at about 1.83GHz.The attenuation pole of the high frequency side of these passbands is frequencies that the high order harmonic component of EGSM signal is cut off because of the Main Function of low pass filter LPF2.Can confirm in this structure example, the frequency of the attenuation pole of the high frequency side of passband is compared with comparative structure example, there is not obvious migration, even if arrange filter adjustment electricity container CCC, can end the high order harmonic component of the signal transmitted by signal port 850/900-Tx fully yet.
Fig. 8 (B) citing illustrates the performance plot of the isolation characteristic between signal port 850/900-Tx and signal port 900-Rx.In the isolation characteristic of these ports, in comparative structure example, at the frequency band throughout about 820MHz ~ about 920MHz, the attenuation that can guarantee is about 26.4dB, but in this structure example, comprise EGSM transmission signal frequency band in the frequency band of the 920MHz of about 820MHz ~ approximately, the attenuation of about 29.6dB can be guaranteed.
Except shown by the respective embodiments described above, even if the present invention changes the link position of filter adjustment electricity container CCC in foregoing circuit structure, also can suitably implement.Such as, also can adopt following structure: namely, first end filter being adjusted electricity container CCC is connected to the rear class of low pass filter LPF1, the second end is connected to the anode etc. of diode PD2.
In addition, the present invention can also be applied to other circuit structures.Such as, following structure can also be adopted: namely, to the structure of the additional filter such as signal port 1900-Rx of above-mentioned circuit structure, the first end adjusting electricity container CCC with filter in the signal port side of this filter is connected, and the second end filter being adjusted electricity container CCC is connected with the anode of diode PD2.
Claims (5)
1. a high-frequency model, comprising:
Multiple independent signal input/output port; Common antenna port; To the switching circuit that the connection of described common antenna port and described multiple independent signal input/output port switches; And connect first and second holding wire of described common antenna port and described independent signal input/output port, it is characterized in that,
Described switching circuit comprises the switch element connecting first and second holding wire described respectively, and described high-frequency model also comprises:
Filter, the link position of switching circuit described in the ratio that this filters in series is connected to described first holding wire is closer to the position of described independent signal input/output port side; And
Filter adjustment electricity container, the link position of filter described in the ratio that the first end of this filter adjustment electricity container is connected to described first holding wire is closer to the position of described independent signal input/output port side, its second end is connected on described switch element, described switch element is connected with described secondary signal line
Described filter comprises the parallel resonant capacitor and parallel resonant inductor device that are connected in parallel, the resonance frequency of the parallel resonance described parallel resonant inductor device and described parallel resonant capacitor produced is set as the frequency of the high order harmonic component of the signal transmitted along described first holding wire
The described first end of described filter adjustment electricity container is connected to the tie point of described parallel resonant capacitor and described parallel resonant inductor device, the resonance frequency of the resonant circuit be made up of described filter adjustment electricity container and described parallel resonant inductor device is set as the first-harmonic of signal that transmits along described first holding wire or the frequency of high order harmonic component.
2. high-frequency model as claimed in claim 1, is characterized in that,
The described switch element be connected with described first holding wire is the 1st diode, and its anode is connected with the described common antenna port side of described first holding wire, and negative electrode is connected with described independent signal input/output port side,
The described switch element be connected with described secondary signal line is the 2nd diode, and its negative electrode is connected with described secondary signal line, and anode is connected with control terminal, and described anode passes through series resonance capacitor ground connection,
Described second end of described filter adjustment electricity container is connected to the link position of described 2nd diode and described series resonance capacitor.
3. high-frequency model as claimed in claim 2, is characterized in that,
Make to form the pattern electrode at least partially of described parallel resonant capacitor, relative in the interarea normal direction of multilager base plate with the pattern electrode at least partially forming described series resonance capacitor, form described filter and adjust electricity container.
4. high-frequency model as claimed in claim 2, is characterized in that,
Make and the cloth line electrode that described parallel resonant capacitor is connected and relative in the interarea normal direction of multilager base plate with the cloth line electrode that described series resonance capacitor is connected, form described filter adjustment electricity container.
5. the high-frequency model as described in any one of Claims 1-4, is characterized in that,
The electric capacity of described filter adjustment electricity container is set to 0.1pF ~ 0.6pF.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2009-049657 | 2009-03-03 | ||
| JP2009049657 | 2009-03-03 | ||
| PCT/JP2010/053284 WO2010101130A1 (en) | 2009-03-03 | 2010-03-02 | High frequency module |
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| Publication Number | Publication Date |
|---|---|
| CN102342028A CN102342028A (en) | 2012-02-01 |
| CN102342028B true CN102342028B (en) | 2015-02-18 |
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| CN201080010829.XA Expired - Fee Related CN102342028B (en) | 2009-03-03 | 2010-03-02 | High frequency module |
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| JP (1) | JP5201260B2 (en) |
| CN (1) | CN102342028B (en) |
| WO (1) | WO2010101130A1 (en) |
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| WO2015008558A1 (en) * | 2013-07-16 | 2015-01-22 | 株式会社村田製作所 | Front end circuit |
| JP2017208656A (en) * | 2016-05-17 | 2017-11-24 | 株式会社村田製作所 | Switch module and high frequency module |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1336731A (en) * | 2000-07-27 | 2002-02-20 | 株式会社村田制作所 | High frequency module, and mobile communicaltion device using same |
| CN1398048A (en) * | 2001-07-13 | 2003-02-19 | 株式会社村田制作所 | Compound high frequency switch and high frequency module and communicator |
| CN1555607A (en) * | 2001-09-18 | 2004-12-15 | �ʼҷ����ֵ��ӹɷ�����˾ | Rf signal switch for a wireless communication device |
| CN1875550A (en) * | 2003-11-11 | 2006-12-06 | 株式会社村田制作所 | High frequency module |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
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| JP2002064400A (en) * | 2000-06-09 | 2002-02-28 | Hitachi Metals Ltd | High frequency switch module |
| WO2008004557A1 (en) * | 2006-07-03 | 2008-01-10 | Hitachi Metals, Ltd. | Branch circuit, high frequency circuit and high frequency module |
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2010
- 2010-03-02 CN CN201080010829.XA patent/CN102342028B/en not_active Expired - Fee Related
- 2010-03-02 JP JP2011502753A patent/JP5201260B2/en not_active Expired - Fee Related
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN1336731A (en) * | 2000-07-27 | 2002-02-20 | 株式会社村田制作所 | High frequency module, and mobile communicaltion device using same |
| CN1398048A (en) * | 2001-07-13 | 2003-02-19 | 株式会社村田制作所 | Compound high frequency switch and high frequency module and communicator |
| CN1555607A (en) * | 2001-09-18 | 2004-12-15 | �ʼҷ����ֵ��ӹɷ�����˾ | Rf signal switch for a wireless communication device |
| CN1875550A (en) * | 2003-11-11 | 2006-12-06 | 株式会社村田制作所 | High frequency module |
Also Published As
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| WO2010101130A1 (en) | 2010-09-10 |
| JPWO2010101130A1 (en) | 2012-09-10 |
| CN102342028A (en) | 2012-02-01 |
| JP5201260B2 (en) | 2013-06-05 |
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