CN101764522B - Flyback power supply with forced primary regulation - Google Patents
Flyback power supply with forced primary regulation Download PDFInfo
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- CN101764522B CN101764522B CN200910261084.3A CN200910261084A CN101764522B CN 101764522 B CN101764522 B CN 101764522B CN 200910261084 A CN200910261084 A CN 200910261084A CN 101764522 B CN101764522 B CN 101764522B
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
A flyback converter with forced primary regulation is disclosed. An example flyback converter includes a coupled inductor including a first winding, a second winding, and a third winding. The first winding is coupled to an input voltage and the second winding is coupled to an output of the power converter. A switched element is coupled to the second winding. A secondary control circuit is coupled to the switched element and the second winding. The secondary control circuit is coupled to switch the switched element in response to a difference between a desired output value and an actual output value to force a current in the third winding that is representative of the difference between the desired output value and the actual output value. A primary switch is coupled to the first winding. A primary control circuit is coupled to the primary switch and the third winding. The primary control circuit is coupled to switch the primary switch to regulate the output of the power converter in response to the forced current.
Description
Technical field
The present invention relates generally to power supply (power supply), and more specifically, the present invention relates to utilize AC-to DC (ac-to-dc) and/or DC-to-DC (dc-to-dc) power supply of flyback converter (flyback converter) Technology of Power Conversion.
Background technology
Usually, flyback converter is the conventional topology that meets mobile phone and use the low cost power supply of the requirement of other portable electric appts of rechargeable battery.In typical application, ac-dc power supply is received in the input between 100 and 240 volts of effective values (rms) from common AC Power supply socket (electrical outlet).Switch on and off the switch in power supply by control circuit, may be suitable for operating electronic equipment or subtend electronic equipment the output through regulating of the battery charging of electric energy is provided to provide.Output is generally the dc voltage that is less than 10 volts of dc.In addition, in the time that power supply charges to battery, conventionally to regulating from the electric current of output.
Release mechanism requires power supply to provide electric current isolation (galvanicisolation) conventionally between input and output.Electric current isolation prevents that dc electric current from flowing between the input of power supply and output.In other words the high dc voltage, being applied between input terminal and the lead-out terminal of power supply can not produce dc electric current between the input terminal of power supply and lead-out terminal.A difficult problem that increases power supply cost to the requirement of electric current isolation.
The power supply with electric current isolation must maintain and will input with output from the electric isolation barrier separating (isolation barrier).Must cross over isolation barrier transmit energy, so that electric energy is offered to output, and must cross over isolate barrier transmit signal form information with regulation output.Electric current isolation normally utilizes electromagnetic equipment and electro-optic device to realize.Electromagnetic equipment such as transformer and coupling inductor (coupled inductor) is usually used to transmit energy between input and output, so that output electric energy to be provided, and electro-optic device is usually used between output and input, transmitting the transmission of signal with the energy between control inputs and output.
The effort that reduces power supply cost focuses in the elimination of electro-optic device and associated circuit thereof.Alternative solution uses the single energy conveying element such as transformer or coupling inductor that energy is offered to output conventionally, and obtains the required information of output of controlling.The configuration of least cost is placed in the input side of isolating barrier by control circuit and high-voltage switch conventionally.Controller obtains the information about output indirectly according to the observation of the voltage at the winding place to energy conveying element.Provide the winding of information also on the input side of isolation barrier.
Sometimes the input side of isolation barrier is called to primary side (primary side), and sometimes the outlet side of isolation barrier is called to primary side (secondary side).Be not also primary side winding with the winding of the energy conveying element of primary side electric current isolation, it is also sometimes referred to as elementary with reference to winding.Sometimes being coupled to input voltage the winding the primary side of input voltage received energy referred to as armature winding.Can there is title of describing its major function, for example setover winding or sensing winding with reference to winding to other of the circuit delivery of energy in primary side is elementary.The winding of isolating with primary side winding current is primary side winding, is sometimes referred to as output winding.
Summary of the invention
A kind of flyback converter, comprising: coupling inductor, comprise the first winding, the second winding and the tertiary winding, and wherein, described the first winding is coupled to input voltage and described the second winding and is coupled to the output of power converter; Switch element, is coupled to described the second winding; Secondary control circuit, be coupled to described switch element and described the second winding, described secondary control circuit is coupled in response to the difference between desired output and real output value and switches described switch element, so that the electric current that represents the difference between described desired output and described real output value is forced in the described tertiary winding; Primary switch, is coupled to described the first winding; And primary control circuit, being coupled to described primary switch and the described tertiary winding, described primary control circuit is coupled in response to forced electric current and switches described primary switch to regulate the output of described power converter.
A method that regulates the output of flyback converter, comprising: in response to the difference between real output value and desired output, switch the switch element of the second winding that is coupled to the coupling inductor being coupled with the output of power converter; In response to the switching to described switch element, force electric current to pass through the tertiary winding of described coupling inductor; And switch the primary switch of the first winding that is coupled to described coupling inductor in response to forced electric current, to regulate the output of described flyback converter.
Brief description of the drawings
The embodiment of non-limiting and nonexcludability of the present invention will be described with reference to the drawings, wherein, unless otherwise specify, otherwise in each view similarly label refer to similar part.
Fig. 1 is the schematic diagram that instruction according to the present invention shows the example flyback power supply of the principal character of power supply.
Fig. 2 A and 2B show according to the function equivalent example of the switch element of instruction of the present invention and represent.
Fig. 3 is according to a part for the flyback power supply of Fig. 1 of the more details that show example primary control circuit of instruction of the present invention.
Fig. 4 is the part that instruction according to the present invention shows the flyback power supply of Fig. 1 of the more details of example secondary control circuit.
Fig. 5 shows instruction according to the present invention in the time operating in DCM, from the sequential chart of the example waveform of the power supply of Fig. 1.
Fig. 6 illustrates that instruction according to the present invention in the time operating in continuous conduction mode, from the sequential chart of the example waveform of the power supply of Fig. 1.
Fig. 7 illustrates that instruction according to the present invention is for the example switch element of the flyback power supply of Fig. 1 and the schematic diagram of example secondary control circuit.
Fig. 8 illustrates the schematic diagram of instruction according to the present invention for the example of another switch element with another secondary control circuit of the flyback power supply of Fig. 1.
Fig. 9 shows instruction utilization according to the present invention and regulates with the switch element of secondary control circuit the example of a part for the output voltage of flyback power supply and the flyback power supply of output current.
Embodiment
Disclose according to the relevant example of the power supply with thering is the elementary adjusting (forced primaryregulation) of forcing of the present invention.In the following description, multiple details have been set forth to provide thorough understanding of the present invention.But those skilled in the art, by clear, realize the present invention and might not adopt these details.In other example, do not describe known material or method in detail, to avoid fuzzy the present invention.
In this manual, mention that " embodiment ", " embodiment ", " example " or " example " refer to that special characteristic, structure or the characteristic described are included at least one embodiment of the present invention or example in conjunction with the embodiments.Therefore, needn't all refer to identical embodiment in each local phrase " in one embodiment ", " in an embodiment ", " in one example " or " in example " occurring of this specification.In one or more embodiment or example, for example, can be any suitable combination and/or sub-portfolio by special characteristic, structure or property combination.In addition, special characteristic, structure or characteristic can be included in to integrated circuit, electronic circuit, combinational logic circuit or provide in other suitable assembly of described function.In addition, will be understood that, the accompanying drawing providing is here object for those of ordinary skill in the art are described, and accompanying drawing needn't be drawn in proportion.
In power supply, be used for obtaining about a kind of common methods of the collateral information of power supply output and depend on the predictable relationship between the voltage at armature winding place and the state of the output of power supply.The where the shoe pinches of the method is can accurately not learn the relation between the voltage at armature winding place and the voltage of the output of power supply.Although the voltage on armature winding is proportional with the output voltage of power supply approx, but many non-ideal effects cause output voltage to be independent of voltage on armature winding and change.
As will be discussed, disclose a kind of instruction according to the present invention provide the output to power supply fine adjustment through improving one's methods and installing.In one example, the flyback power supply according to instruction of the present invention has been discussed, it enables using single energy conveying element that the fine adjustment of the output of the flyback power supply of electric current isolation is provided between the input of power supply and output.
In order to illustrate, Fig. 1 shows the schematic diagram of an example of dc-dc power supply 100 in general manner, and dc-dc power supply 100 receives input voltage V
iN102 to produce output voltage V at load 154 places
o156 and output current I
o152.In the example of ac-dc power supply, dc input voltage V
iN102 can be through rectification and through the ac of filtering input voltage.Input voltage V
iN102 is positive with respect to input circuit (input return) 108.Output voltage V
obe positive with respect to output loop (outputreturn) 150.
The example power supply 100 of Fig. 1 is the flyback converters through regulating.As illustrated in the example shown, the flyback converter of power supply 100 comprises energy conveying element L1132, and it is the coupling inductor with three windings.Energy conveying element L1132 is sometimes referred to as transformer, because the voltage on its winding is relevant with the number of turn on each winding.Energy conveying element L1132 comprises having N
pthe input winding 128 of circle, there is N
sthe output winding 130 of circle and there is N
bthe biasing winding 126 of circle.
In the example shown, between the circuit in circuit and the power supply output of energy conveying element L1132 in the input of power supply, provide electric current isolation.The dc voltage, being applied between input circuit 108 and output loop 150 can not be created in dc electric current mobile between input circuit 108 and output loop 150.It is the electric insulation between winding that the isolation barrier of electric current isolation is provided.Input winding 128 and biasing winding 126 are in the primary side of isolation barrier.Output winding 130 is on the outlet side of isolation barrier.
As shown shown in example, the switch S 1106 in the primary side of isolation barrier is to disconnecting in the driving signal 114 from primary control circuit 116 and closed.In one example, switch S 1106 can be mos field effect transistor (MOSFET).In another example, switch S 1 106 can be bipolar junction transistor (BJT).In another example, switch S 1106 can be insulated gate bipolar transistor (IGBT) or other suitable switch.
In one example, primary control circuit 116 generates and drives signal 114 in response to the signal at control terminal 160 places, carrys out the switching of control switch S1 106.Primary control circuit 116 can also be to the electric current I in indicator cock S 1106
dthe current sensing signal 112 of 104 value responds.Any method in some methods of the electric current in the sense switch of implementing in the art can provide current sensing signal 112.
In one example, 116 disconnections of primary control circuit and Closing Switch S1 106 are to be adjusted to desirable value by the output of power supply 100.Output can be the combination of voltage, electric current or voltage and electric current.The example power supply 100 of Fig. 1 has provided the output voltage V through regulating at load 154 places
o156.Load 154 receives output current I
o152.
The switch disconnecting can not conduction current.Closed switch can conduction current.In the time that switch S 1 106 is closed, primary current I
p158 enter the armature winding 128 of coupling inductor L1132, store the energy in the magnetic field of coupling inductor L1132.In the time that switch S 1 106 is closed, in output winding 130 and biasing winding 126, there is not electric current.In the time that switch S 1 106 is closed, the switch element 138 that is coupled to the diode 118 of biasing winding 126 and is coupled to output winding 130 stops the electric current in corresponding windings.
In the time that switch S 1106 disconnects, electric current I
s134 can flow in output winding 130, and electric current I
b120 can flow in biasing winding 126.After switch S 1106 disconnects, all or part energy being stored in coupling inductor L1132 can be released by winding 126 and 130.When, switch S 1106 is closed by primary current I
p158 energy that are stored in winding 128 are sent to received current I from winding 126 and winding 130 respectively in the time that S1106 disconnects
b120 and electric current I
s134 circuit.Electric current I
s134 and I
b120 respectively to capacitor C1148 and C2122 charging, to produce corresponding voltage V
o156 and V
c124.In the example of Fig. 1, capacitor C1 148 and C2122 have enough electric capacity to make voltage V
o156 and V
c124 are essentially dc voltage.In the example of Fig. 1, electric current I
b120 forward bias rectifiers 118 are to charge to capacitor C2122.In the example of Fig. 1, as rectifier 118 conduction current I
b, there is forward voltage V at 120 o'clock
f164.
In the example shown, voltage V
b162 with voltage V
srelation between 136 is recently determined by the number of turn on each winding 126 and 130.,
With voltage V
b162 and voltage V
sfixed relationship between 136 forms contrast, the electric current I in each winding 126 and 130
b120 and I
s134 is irrelevant with the number of turn of winding.But, electric current I
b120 and I
s134 are determined by the character of the circuit at each winding place respectively.That is, in the time that switch S 1106 disconnects, electric current I
b120 and I
s134 can be any ratio.Arbitrary winding can have zero current in any time in the time that switch S 1106 disconnects.In the time that switch S 1106 disconnects, electric current I
b120 and I
s134 are subject to the quantitative limitation of remaining energy in coupling inductor, but each electric current can be got any value that is no more than this restriction.Therefore,, according to instruction of the present invention, can come as required institute's stored energy to be directed to arbitrary winding by utilizing control circuit to locate to force electric current at one of winding.
As illustrated in the example depicted in fig. 1, power supply 100 comprises the secondary control circuit 146 according to instruction of the present invention, and its console switch element 138 is to distribute (portion) from coupling inductor 132 to output winding 130 and the transmission of the energy of biasing winding 126.In example, secondary control circuit 146 receives the voltage V at winding 130 places
s136 as signal 140 and reception output voltage V
o156 as signal 144.In example, the insignificant electric current of signal 140 and 144 conduction.According to instruction of the present invention, secondary control circuit 146 produces the driving signal 142 of diverter switch element 138, to make to represent output voltage V
o156 actual value and output voltage V
othe energy of the difference between 156 desired value shifts (divert) to biasing winding 126 from output winding 130.Output voltage V
o156 desired value is specified for particular power source.The designer of power supply arranges the output voltage of expectation conventionally according to the reference voltage of setting up in secondary control circuit 146, as will be discussed in this is open after a while.Represent output voltage V
o156 actual value and output voltage V
othe energy of the difference between 156 desired value can be considered to error signal.
The energy that is transferred to biasing winding 126 receives the signal as control switch S 1106 by primary control circuit 116, to make output voltage V
o156 are adjusted to desired value., secondary control circuit 146 will represent output voltage V
othe energy of the error between 156 actual value and desired value is transferred to biasing winding 126.The electric current I of primary control circuit 116 to the information that comprises error signal
b120 respond.Primary control circuit 116 diverter switch S 1106 are with by output voltage V
o156 are adjusted to desired value, reduce thus the value of error signal.
That illustrate as in the example of Figure 1 and in the disclosure after a while by describe in detail, the voltage V on capacitor C2122
c124 are regulated by primary control circuit 116.Voltage and turn ratio are selected by designer, to make only just to have electric current in biasing winding 126 in the time that biasing winding 126 is transferred to energy in switch element 138 operations.,
By primary current I
p158 sub-fractions that are stored in the energy in armature winding 128 can not be sent to other winding, and this is because the magnetic coupling between armature winding 128 and other winding of coupling inductor imperfect.In the example power supply 100 of Fig. 1, the energy that can not be sent to other winding is received by clamper (clamp) circuit 110, and the voltage that clamp circuit 110 limits armature winding 128 two ends is not damaged by excessive voltage with protection switch S1106.
Fig. 2 A and Fig. 2 B usually show the function equivalent example that can be used in the switch element 138 in the example power supply 100 of Fig. 1 according to instruction of the present invention.As will be discussed, switch element 138 is coupled to be switched to has the effective impedance that equals the first impedance or the second impedance between terminal 240 and 244, wherein, and the first and second impedance differences.In one example, the first impedance between terminal 240 and 244 and the second impedance are all non-vanishing.In one example, impedance can be nonlinear.
In order to describe, Fig. 2 A shows by driving signal 142 to control with in position 1 or the single-pole double-throw switch (SPDT) S of position 2
a205.Work as switch S
a205 in the time of position 1, and the electric current transmitting between the terminal 240 of switch element 138 and terminal 244 must pass through impedance Z 1210.Work as switch S
ain the time of position 2, the electric current transmitting between terminal 240 and terminal 244 must pass through impedance Z 2220.Usually, impedance Z 1210 and Z2220 can be any values including zero-sum infinity, as long as impedance Z 1210 is different with Z2220.In the example shown, the impedance between terminal 240 and the terminal 244 of switch element 138 must be different for the high value and the low value that drive signal 142.
Fig. 2 B illustrates and comprises by driving signal 142 to control with the single-pole single-throw switch (SPST) S in disconnection or closure state
b230 example switch element 138.Fig. 2 B also comprises impedance Z 3250 and Z4255.Main difference between the configuration of Fig. 2 A and Fig. 2 B is that the impedance Z 3250 between terminal 240 and terminal 244 is not switched in the configuration of Fig. 2 B., work as switch S
b230 disconnect and work as switch S
bwhen closed, impedance Z 3250 is all between terminal 240 and terminal 244.Work as switch S
b230 when disconnect, and all electric currents that transmit between the terminal 240 of switch element 138 and terminal 244 all must be through impedance Z 3250.Work as switch S
bwhen closed, a part for the electric current that can transmit through impedance Z 3250 and between terminal 240 and 244 in a part for the electric current transmitting between terminal 240 and terminal 244 can be passed through impedance Z 4255.Usually, except Z3250 can not be zero and Z4255 can not be for infinity, impedance Z 3250 and Z4255 can be any value, and they needn't be different value.
In one example, any impedance Z 1210, Z2220, Z3250 and the Z4255 in Fig. 2 A and Fig. 2 B can be nonlinear., the voltage at impedance two ends may not be directly proportional to the electric current of the impedance of flowing through.For example, pn junction diode can be considered to have nonlinear impedance.Schottky (Schottky) diode also can be considered to have nonlinear impedance.
Usually, switch element 138 can be two-way or unidirectional.Bilateral switching element allows conduction current in either direction.Unidirectional switch elements only allows conduction current in one direction.In the time that impedance Z 1210, Z2220, Z3250 and Z4255 comprise diode, the switch element of Fig. 2 A and Fig. 2 B can be unidirectional.
Fig. 3 illustrates in greater detail the example primary control circuit 116 in the example power supply 100 that can be used in Fig. 1.As shown in the figure, example primary control circuit 116 comprises the oscillator 310 that is coupled to logic and driver circuitry 305, and logic and driver circuitry 305 is coupled to shunt regulator (shuntregulator) 315.In the example shown, primary control circuit 116 receives the energy of automatic biasing winding 126 at control terminal 160 places.The energy that carrys out automatic biasing winding 126 provides electric energy to carry out operation control circuit 116.The energy that carrys out automatic biasing winding 126 also provides and output voltage V
othe relevant information of difference between 156 actual value and desired value.That is, according to instruction of the present invention, the electric current I in biasing winding 126
b120 comprise supply current and the error signal for control circuit 116.
As shown in example, there is value I
dDcurrent source 355 represent the supply current that operation of primary control circuit 116 is required, and can comprise the electric current that console switch S1106 is required.In one example, primary control circuit 116 can be included in monolithic integrated circuit.In another example, integrated circuit can comprise primary control circuit 116, switch S 1114 and current sensing signal 112.The example integrated circuit being included in power supply 100 can be California, one of the TOPSwitch of the Power Integrations company of San Jose or DPA-Switch series of products.
Continue the example shown in Fig. 3, primary control circuit 116 comprises shunt regulator 315, and it is coupled the control voltage V on capacitor C2122
c124 are adjusted to desired value.In the operation of power supply 100, the energy that guides to biasing winding 126 is greater than to primary control circuit 126 provides electric energy required amount.Exceed the energy of amount needing to primary control circuit 116 power supply stations by shunt regulator 315 with branch current I
sH320 form dissipates.
When controlling voltage V
c124 when be conditioned, branch current I
sHthe 320th, carry out the electric current I of automatic biasing winding 126
b120 mean value with from the electric current I of current source 355
dDbetween poor.By this way, branch current I
sH320 represent to exceed the energy of transferring to biasing winding 126 that the required amount of electric energy is provided to primary control circuit 116.Due to the error that is directed to the energy of overage of biasing winding 126 and represents between actual value and the desired value of output, therefore, branch current I
sHerror between 320 actual value and the desired values that represent to export.Therefore, branch current I
sHthe 320th, error current, and electric current I in winding 126
b120 mean value is error current I
sH320 with supply current I
dD355 sums.
As shown in the example shunt regulator 315 at Fig. 3, there is optional feedback circuit H
f1340 amplifier 330 receives desired control voltage V at reversed input terminal 350 places of amplifier 330
c124 ratio is K
1part.Amplifier 330 receives reference voltage V at in-phase input terminal 345 places
rEFC.The output of amplifier 330 drives p channel mosfet 325 with conduction branch current I
sH320, to make the voltage K at reversed input terminal 350 places
1v
creference voltage V with in-phase input terminal 345 places
rEFCsubstantially the same.Therefore, control voltage V
c124 value of being adjusted to V
rEFCdivided by ratio K
1.
In example shunt regulator 315, branch current I
sH320 are converted to error voltage by resistor 335.Logic and driver circuitry 305 receives from the error voltage of resistor 335, from timing signal and the current sensing signal 112 of oscillator 310, to produce the driving signal 114 of the switching that is coupled control switch S1106.
Fig. 4 illustrates in greater detail example secondary control circuit 146.Secondary control circuit 146 comprises the secondary error amplifier 425 that secondary error signal 415 is provided.In one example, logic, timing and drive circuit 410 receive secondary error signal 415 and voltage V
s136, to produce the driving signal 142 for switch element 138.
As shown in the example of Fig. 4, secondary error amplifier 425 comprises having optional feedback network H
f2420 operational amplifier 430.Reversed input terminal 440 is coupled to receive output voltage V
o156 ratio is K
2part.Amplifier 430 receives reference voltage V at in-phase input terminal 435 places
rEFO.In this example, desired output voltage is reference voltage V
rEFOdivided by K
2.The output of amplifier 430 is received by logic, timing and drive circuit 410, and logic, timing and drive circuit 410 are coupled console switch element 138 at the biasing winding 126 generation current I of place
b120, to make the voltage K at reversed input terminal 440 places
2v
oreference voltage V with in-phase input terminal 435 places
rEFOsubstantially the same.Therefore, output voltage V
o156 value of being adjusted to V
rEFOdivided by ratio K
2.
Fig. 5 illustrates to illustrate in the time of operation in DCM (DCM), the sequential chart 500 of the waveform of the operation of the example power supply 100 in Fig. 1.In the time that the power supply 100 in Fig. 1 operates in DCM, at switch S 1106 off periods, all energy in coupling inductor L1132 are removed from inductor L1132.,, in the time that switch S 1106 is closed at first, do not exist dump energy to be stored in coupling inductor L1132.In the time that the power supply 100 in Fig. 1 operates in DCM, the electric current I in switch S 1106
d104 just have null value after closure in switch S 1106.
Waveform in the sequential chart 500 of Fig. 5 shows in the time that switch element 138 has the characteristic of Fig. 2 A and Fig. 2 B and impedance Z 1210 and Z3250 infinity and impedance Z 2220 and Z4255 and is zero, the operation of the power supply 100 of Fig. 1.That is, when driving signal 142 while being high, switch element 138 conduction current I
s134, and when driving signal 142 while being low, switch element 138 non-conducting electric currents.
Fig. 5 shows complete switch periods T
s530.From the driving signal 114 of primary control circuit 116 at T
oNduring 505, be high, this makes the switch S 1106 can conduction current I
d104.Drive signal 114 at T
oFFduring 515, be low, to prevent switch S 1106 conductings.From the driving signal 142 of secondary control circuit 146 at T
oN505 finish T afterwards
1during 510, be high, this makes switch element 138 can conduct the electric current I in secondary winding 130
s134.From the driving signal 142 of secondary control circuit 146 at T
1step-down when 510 end, to prevent switch element 138 conduction currents.
In the example of Fig. 5, when switch element 138 conducts the electric current I from secondary winding 130
s134 o'clock, bias current was zero, and this is because diode 118 is reverse biased.That is, in the time of switch element 138 conducting, the voltage V on biasing winding 126
b162 are less than control voltage V
c124 add forward voltage V
f164 sums.
When driving signal 142 at T
1when 510 end, step-down is to reduce the electric current I in secondary winding 130
s134 o'clock, the energy of storing in coupling inductor L1132 was by electric current I
b120 force in biasing winding 126, to make secondary voltage V
s136 are greater than output voltage V
o156.Drive signal 142 to remain low until T
oN505 finish to have passed through afterwards T
2till 520.Drive signal in time T
2when 520 end, uprise, to allow switch element 138 again to conduct the electric current I from secondary winding 130
s134, thereby by secondary voltage V
s136 are reduced to output voltage V
o156, and prevent the electric current I in conduction biasing winding 126
b120.When removed all energy from coupling inductor L1132 after, switch element 138 is at time t
x525 places stop conducting.Therefore, according to instruction of the present invention, from the driving signal 142 of secondary control circuit 146 at turn-off time T
oFFin at least a portion of 515, be low, this makes switch element 138 reduce the electric current I from secondary winding 130
s134, with by electric current I
b120 force in biasing winding 126.In one example, according to instruction of the present invention, secondary control circuit 146 is coupled in response to the difference between desired output and the real output value of power converter and makes switch element 138 reduce the electric current I from secondary winding 130
s134.
In the example of Fig. 5, in the time that all stored energys remove from coupling inductor L1132, from the driving signal 142 of secondary control circuit 146 at time t
x525 place's step-downs.If switch element 138 is unidirectional switch elements, in the time no longer including the energy of storage in coupling inductor L1132, needn't vanishing from the driving signal 142 of secondary control circuit 146.
Fig. 6 illustrates the sequential chart 600 that illustrates the waveform of the operation of the power supply 100 in Fig. 1 in the time of operation in continuous conduction mode (CCM).In the time that the power supply 100 in Fig. 1 operates in CCM,, there is energy in coupling inductor L1132 in the whole time durations disconnecting in switch S 1106.,, in the time of switch S 1106 initial closure, in coupling inductor L1132, there is energy.In the time that the power supply 100 in Fig. 1 operates in CCM, the electric current in switch S 1106 just has the value that is greater than zero after closure in switch S 1106.
With class of operation in the DCM shown in Fig. 5 seemingly, Fig. 6 shows in CCM, drives the time T of signal 142 after switch S 1106 disconnects
1during 610, be high, this makes the switch element 138 can conduction current I
s134.At T
1when 610 end, switch element 138 disconnects reducing electric current I
s134, with by electric current I
b120 force in biasing winding 126.The time T of switch element 138 when switch S 1106 disconnects
2closed to allow I after 620
s134 conduction.Therefore, according to instruction of the present invention, from the driving signal 142 of secondary control circuit 146 at turn-off time T
oFFin at least a portion of 515, be low, this makes switch element 138 reduce the electric current I from secondary winding 130
s134, with by electric current I
b120 force in biasing winding 126.In one example, according to instruction of the present invention, secondary control circuit 146 is coupled in response to the difference between desired output and the real output value of power converter and makes switch element 138 reduce the electric current I from secondary winding 130
s134.
Other example power supply of being benefited from instruction of the present invention can utilize the sequential chart after the diagram 600 of diagram 500 to Fig. 5 and Fig. 6 is modified to operate.For the operation in DCM or CCM, switch element 138 can reduce or stop electric current I in any time of switch S 1106 off periods
s134 conduction.The time that, switch element 138 disconnects after switch S 1106 disconnects may more approach T
oFF515 beginning or more approach T
oFF515 ending.Switch element 138 can repeatedly reduce or stop electric current I at switch S 1106 off periods
s134 conduction.Secondary controller 146 can be at T
oFFnumber of times as required disconnects and Closing Switch element 138 during this time, with by enough electric current I
bforce in biasing winding 126 and carry out regulation output.
Fig. 7 shows the details for example secondary control circuit 146 and the example switch element 138 of the power supply 100 of Fig. 1.In Fig. 7 example shown, switch element 138 is the unidirectional switch elements that comprise diode 705 and n channel mosfet 710.Secondary error amplifier 425 comprises it can being the three end shunt regulators 750 of TL431 adjuster etc. in one example.TL431 adjuster is the common three end integrated circuits that comprise internal reference voltage.In the time being applied to the external voltage of reference terminal and exceeding reference voltage, TL431 is at its two other terminal place conduction current.Resistor 745 and 760 is coupled to form voltage divider with by output voltage V
o156 ratio is K
2part offer the reference terminal 765 of shunt regulator 750.In this example, desired output voltage is that the reference voltage of TL431 is divided by K
2.Secondary error signal 415 is the voltage being produced on resistor 755 by the electric current from pnp transistor 740.
Shown in example, logic, timing and drive circuit 410 comprise the capacitor 715 that is coupled to charging diode 730 and discharge diode 720 as shown, and discharge diode 720 is coupled to resistor 725, and resistor 725 is coupled to npn transistor 735.Capacitor 715, charging diode 730 and discharge diode 720 have formed to the grid of n channel mosfet 710 charge pump that drives signal 142 are provided, and this charge pump is a part for unidirectional switch elements 138.
In the time of operation, as secondary voltage V
s136 at time interval T
oNwhile being negative during 505, capacitor 715 charges.As secondary voltage V
s136 is timing, and capacitor 715 discharges by diode 720, resistor 725 and npn transistor 735.As secondary voltage V
s136 become timing from bearing, and drive on signal 142 and exist enough voltage to make 710 conductings of n channel mosfet.Switch element 138 conducts secondary current I
s134, thus until making capacitor 715 discharge fully to reduce the voltage driving on signal 142, npn transistor 735 make n channel mosfet 710 stop conducting.In the example of Fig. 7, only conducting is once in switch periods for switch element 138.In the example of Fig. 7, secondary error signal 415 is larger, will make npn transistor 735 that capacitor 715 is discharged faster, and this makes the switch periods T of switch element 138 after switch S 1106 disconnects
sin 530, stop earlier conducting.
Fig. 8 illustrates the example of another switch element and another secondary control circuit, and wherein, switch element 138 is the synchronous rectifiers that comprise n channel mosfet 820 and parallel diode 810.Synchronous rectifier is used for the diode in the output winding of alternative switch power supply sometimes, and this is that the voltage at MOSFET two ends can be much smaller than the voltage at diode two ends because in the time of conduction current.The low voltage of synchronous rectifier has improved efficiency by the energy fewer than diode that dissipate.In one example, parallel diode 810 represents the intrinsic body diodes of n channel mosfet 820.In one example, parallel diode 810 is the discrete diode that can be Schottky diode.
In the example of Fig. 8, secondary control circuit 146 is synchronous rectifier controllers.Secondary control circuit 146 provides and drives signal 830 to n channel mosfet 820.And can stop conduction secondary current I by insert very high impedance between secondary winding 130 and output 146 in the example of Fig. 7
s134 switch element 138 is compared, and the switch element 138 in the example of Fig. 8 reduces secondary current I by the impedance that changes switch element 138 between two low values
s134.When driving signal 830 while being low, switch element 138 has the impedance of diode 810.When driving signal 830 while being high, switch element 138 have MOSFET 820 compared with Low ESR.The insertion of the diode 810 of higher resistance has reduced secondary current I
s134, increased the electric current I in biasing winding 126 simultaneously
b120.
Fig. 9 shows the example of a part for flyback power supply, and wherein, secondary control circuit 940 is controlled output current I
o152 and output voltage V
o156, and drive signal 930 to be coupled control switch element 138.In this example, secondary control circuit 940 is sentenced the form sensing output voltage V of signal 144 in current-sense resistor 910
o156 and with the form sensing output current I of signal 920
o152.In the example of Fig. 9, the voltage at current-sense resistor 910 two ends is poor between signal 920 and signal 144.Therefore, Fig. 9 shows according to instruction of the present invention, and how example of the present invention instruction can be suitable for controlling as the output of voltage or as the output of electric current, or as the output of the combination of voltage and current.
The description above to example shown in the present describing in summary does not wish it is exclusiveness, or is limited to disclosed precise forms.Although described for illustrative purposes specific embodiments of the invention and example here, but in the situation that not departing from broad spirit of the present invention and scope, the various amendments that are equal to are fine.In fact, will be understood that, concrete voltage, electric current, frequency, power range values, time etc. are the objects that is provided for explanation, and according to instruction of the present invention, can also in other embodiment and example, apply other value.
In view of detailed description above, can make these amendments to example of the present invention.The term using in appended claims should not be interpreted as limiting the invention to disclosed specific embodiment in specification and claims.But scope determined on the whole by appended claims, the principle that appended claims is explained according to the claim of having established makes an explanation.Therefore, this specification and accompanying drawing are considered to illustrative and nonrestrictive.
Claims (17)
1. a flyback converter, comprising:
Coupling inductor, comprises the first winding, the second winding and the tertiary winding, and wherein, described the first winding is coupled to input voltage and described the second winding and is coupled to the output of flyback converter;
Switch element, is coupled to described the second winding;
Secondary control circuit, be coupled to described switch element and described the second winding, described secondary control circuit is coupled in response to the difference between desired output and real output value and switches described switch element, so that the electric current that represents the difference between described desired output and described real output value is forced in the described tertiary winding;
Primary switch, is coupled to described the first winding; And
Primary control circuit, is coupled to described primary switch and the described tertiary winding, and described primary control circuit is coupled in response to forced electric current and switches described primary switch to regulate the output of described flyback converter,
Wherein, the electric current of forcing comprise for the supply current of described primary control circuit and represent described desired output and described real output value between the error signal of difference;
Wherein, described primary control circuit comprises from the shunt regulator of error signal described in forced current draw, and wherein, described primary control circuit is coupled in response to described error signal and switches described primary switch.
2. flyback converter as claimed in claim 1, wherein, described second winding of described coupling inductor and described the first winding and the described tertiary winding are electric current isolation.
3. flyback converter as claimed in claim 1, wherein, described switch element is coupled to switch to has the first impedance or the second impedance, and wherein, described the first impedance and described the second impedance are unequal.
4. flyback converter as claimed in claim 3, wherein, described the first impedance be zero and described the second impedance for infinitely great.
5. flyback converter as claimed in claim 1, wherein, described switch element is unidirectional.
6. flyback converter as claimed in claim 1, wherein, described switch element is two-way.
7. flyback converter as claimed in claim 1, wherein, described secondary control circuit comprises secondary error amplifier, and described secondary error amplifier is coupled to a voltage divider and a reference voltage to determine the difference between described desired output and described real output value.
8. flyback converter as claimed in claim 1, wherein, described secondary control circuit comprises the shunt regulator that is coupled to a voltage divider, described shunt regulator has internal reference voltage, and described shunt regulator is coupled the difference of determining between described desired output and described real output value.
9. flyback converter as claimed in claim 1, wherein, described switch element comprises synchronous rectifier.
10. flyback converter as claimed in claim 1, wherein, described secondary control circuit is coupled to utilize the driving signal that is coupled to described switch element to control output current and the output voltage of described flyback converter.
11. flyback converters as claimed in claim 1, wherein, described secondary control circuit makes described switch element reduce the electric current from described the second winding, so that electric current is forced in the described tertiary winding during being coupled the portion of time in the opening time of described primary switch.
12. 1 kinds regulate the method for the output of flyback converter, comprising:
In response to the difference between real output value and desired output, switch the switch element of the second winding that is coupled to the coupling inductor being coupled with the output of flyback converter;
In response to the switching to described switch element, force electric current to pass through the tertiary winding of described coupling inductor; And
Switch the primary switch of the first winding that is coupled to described coupling inductor in response to forced electric current, to regulate the output of described flyback converter,
Wherein, the electric current of forcing comprise for the supply current of primary control circuit and represent described desired output and described real output value between the error signal of difference;
Wherein, the primary switch that switches the first winding that is coupled to described coupling inductor in response to forced electric current comprises with the output that regulates described flyback converter: from the current draw error signal of being forced, wherein, the switching of described primary switch is in response to described error signal.
13. methods as claimed in claim 12, wherein, comprise the switching of described switch element: switch described switch element to make it having the first impedance or the second impedance, wherein, described the first impedance and described the second impedance are unequal.
14. methods as claimed in claim 12, wherein, to having reduced the electric current from described the second winding during the portion of time in the opening time that switches in described primary switch of described switch element, to force electric current to pass through the described tertiary winding.
15. methods as claimed in claim 12, wherein, switch and be coupled to and the switch element of the second winding of the coupling inductor that the output of flyback converter is coupled comprises: the difference between the real output value of more described flyback converter and a reference voltage in response to the difference between real output value and desired output.
16. methods as claimed in claim 12, wherein, switch and be coupled to and the switch element of the second winding of the coupling inductor that the output of flyback converter is coupled comprises: the difference between the real output value of more described flyback converter and the internal reference voltage of a shunt regulator in response to the difference between real output value and desired output.
17. methods as claimed in claim 12, wherein, the second winding of described coupling inductor and described the first winding and the described tertiary winding are electric current isolation.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US12/341,353 | 2008-12-22 | ||
| US12/341,353 US7876583B2 (en) | 2008-12-22 | 2008-12-22 | Flyback power supply with forced primary regulation |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101764522A CN101764522A (en) | 2010-06-30 |
| CN101764522B true CN101764522B (en) | 2014-09-03 |
Family
ID=42102032
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200910261084.3A Expired - Fee Related CN101764522B (en) | 2008-12-22 | 2009-12-22 | Flyback power supply with forced primary regulation |
Country Status (4)
| Country | Link |
|---|---|
| US (4) | US7876583B2 (en) |
| EP (1) | EP2209195A3 (en) |
| JP (1) | JP5618532B2 (en) |
| CN (1) | CN101764522B (en) |
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Also Published As
| Publication number | Publication date |
|---|---|
| EP2209195A2 (en) | 2010-07-21 |
| US7876583B2 (en) | 2011-01-25 |
| EP2209195A3 (en) | 2014-03-12 |
| US8243477B2 (en) | 2012-08-14 |
| US20110085357A1 (en) | 2011-04-14 |
| JP5618532B2 (en) | 2014-11-05 |
| US20110267849A1 (en) | 2011-11-03 |
| CN101764522A (en) | 2010-06-30 |
| JP2010148352A (en) | 2010-07-01 |
| US8000115B2 (en) | 2011-08-16 |
| US20100157630A1 (en) | 2010-06-24 |
| US20120281439A1 (en) | 2012-11-08 |
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