CN101103538A - Communication device, multi-band reception device, and reception device - Google Patents
Communication device, multi-band reception device, and reception device Download PDFInfo
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- CN101103538A CN101103538A CNA2006800023863A CN200680002386A CN101103538A CN 101103538 A CN101103538 A CN 101103538A CN A2006800023863 A CNA2006800023863 A CN A2006800023863A CN 200680002386 A CN200680002386 A CN 200680002386A CN 101103538 A CN101103538 A CN 101103538A
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/06—Receivers
- H04B1/16—Circuits
- H04B1/30—Circuits for homodyne or synchrodyne receivers
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
- H04B1/0067—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges with one or more circuit blocks in common for different bands
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L25/00—Baseband systems
- H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
- H04L25/06—Dc level restoring means; Bias distortion correction ; Decision circuits providing symbol by symbol detection
- H04L25/061—Dc level restoring means; Bias distortion correction ; Decision circuits providing symbol by symbol detection providing hard decisions only; arrangements for tracking or suppressing unwanted low frequency components, e.g. removal of dc offset
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Abstract
In an orthogonal demodulator of direct conversion method used in a multi-band reception device, it is possible to reduce the affect of DC offset drift generated during band switching to reception characteristic. The multi-band reception device includes: a plurality of orthogonal demodulators (5, 6) orthogonally demodulating a plurality of band inputs; a selector switch for selecting one of the plurality of orthogonal demodulators by a band switching control signal (15): and a broadband pass filter (8) for receiving the output of the selector switch (7) as an input. In the multi-band reception device, upon band switching, control is performed to increase the cut-off frequency of the broadband pass filter (8) so as to reduce the convergence time of the DC offset drift contained in the output signal.
Description
Technical field
The present invention relates to communication equipment, multiband receiver, and receiver.
Background technology
For DC (direct current) skew of AGC (automatic gain control) circuit that makes the outfit in CDMA (Code Division Multiple Access) receiver reduces, for example Japanese Patent Application Publication No.2003-224488 (patent references 1) it was suggested a time period (wherein the DC in the internal circuit that is equipped with in Direct Transform type receiver skew may surpass threshold value because of the AGC operation) has been detected, and the cut-off frequency of the high pass filter that is equipped with in the gain amplifying circuit that base band is variable is made as the normal frequency that is higher than in the detected time period, thereby promptly makes the transient response convergence of the signal that passes through high pass filter.
Recently develop subscriber equipment (UE), for example covering the mobile phone of mutually different a plurality of frequency band (for example, 2GHz frequency band and 800MHz frequency band).
During handover (handover), subscriber equipment (UE) is necessary to set up frequency is switched to another frequency after synchronous between will carrying out frequently between different carrier frequencies.For this reason, subscriber equipment (UE) is designed to carrying out during the time period (being called " transmission gap ") of a part of frame that stops to transmit active link and subscriber equipment scheduled measurement that the carrier frequency that has is relevant after the execution handover, and during the activity time section, be included in the data (being the data in the transmission gap) of deleting in the time period, thereby improve through-put power with high rate data transmission.Thereby can keep transmission rate and channel quality.Aforesaid this control is called as " compact model " (3GPP compact model) (for example, seeing non-patent references 1,2 and 3).
When being necessary to carry out handover, base station (BTS) indication subscriber equipment (UE) carries out work with compact model.Compact model is by reducing dispersion rate and carrying out by deleted bit from data (promptly carry out brachymemma (puncture), but only at down link).
Condensed frame is periodically defined or should be required and defined.Condensed frame has variable speed and type, and described variable speed and type all depend on environment and measurement requirement.
As with the similar structure of mentioning after a while of a part according to a second embodiment of the present invention, Japanese Patent Application Publication No.04-297182 (patent references 2) it was suggested a kind of cis, wherein two picture signals sending from CCD (charge coupled device) are exaggerated the AC amplifier, and described AC amplifier is electrically connected mutually by capacitor C1 and C2 in the AC mode.The end of capacitor C3 and C4 is electrically connected to the output port of AC amplifier, and its other end is electrically connected to the DC buffer.The other end of capacitor C3 and C4 is electrically connected mutually according to the clamper signal.
Patent references 1: Japanese Patent Application Publication No.2003-224488
Patent references 2: Japanese Patent Application Publication No.04-297182
Non-patent references 1:3GPP TS 25.215 V3.10.0 Technical SpecificationGroup Radio Access Network; Physical layer-Measurement (FDD) (Release1999)
Non-patent references 2:3GPP TS 25.212 V3.11.0 Technical SpecificationGroup Radio Access Network; Multiplexing and Channel Coding (FDD) (Release 1999)
Non-patent references 3:3GPP TS 25.101 V3.17.0 Technical SpecificationGroup Radio Access Network; User Equipment (UE) radio transmission andreception (FDD) (Release 1999)
Summary of the invention
Problem to be solved by this invention
The multiband receiver that can cover a plurality of frequency bands is designed to the quadrature demodulator that comprises that a plurality of and a plurality of frequency bands are associated.When a frequency band is switched to another frequency band, signal is input to the base band variable-gain amplification circuit (for example, by the high pass filter (HPF) in the downstream that is arranged in quadrature demodulator and switch, AGC amplifier by switch, high pass filter, and the AGC amplifier is formed) in.
If the DC skew does not match mutually between a plurality of quadrature demodulators, then when being switched to another frequency band, a frequency band will cause following problem.
In other words, if when a frequency band is switched to another frequency band, cause DC offset drifts (being defined as the drift that the DC skew causes when not matching mutually between a plurality of quadrature demodulators), although it depends on the cut-off frequency of high pass filter, but will cause AGC level error in a certain period after being switched to another frequency band being right after frequency band, perhaps will cause the shortage of pilot data, thereby cause signal to accept the deterioration of performance.
For example, suppose that the gain in the base band variable-gain amplification circuit is about 40dB, then being right after a frequency band is switched to the DC offset drifts that causes after another frequency band and (for example will be exaggerated 100 times on voltage, the DC offset drifts of 10mV is enlarged into 1V), thereby (for example cause AGC level error and/or data error, bit error rate (BER)) increase (for example, suppose that the gain in the base band variable-gain amplification circuit is 60dB, then the DC offset drifts of 1mV is enlarged into 1V).
In addition, be delayed, then during transmission gap, will can correctly do not carry out measurement, thereby cause the accident error during carrying out handover with compact model if be right after the convergence that a frequency band is switched to the DC offset drifts after another frequency band.
Consider the problems referred to above in traditional receiver, an object of the present invention is to provide receiver and comprise the communication equipment of this receiver, described receiver and communication equipment can both reduce the influence that signal receiving performance caused by the DC offset drifts that generates in the Direct Transform type quadrature demodulator that is equipped with when a frequency band is switched to another frequency band in multiband receiver.
The solution of problem
In order to address the above problem, a kind of communication equipment is provided, it comprises a plurality of quadrature demodulators that cover each frequency band in a plurality of frequency bands separately, wherein the part of the frame in the frequency band in a plurality of frequency bands is stopped in the transmission gap of transmission and carries out scheduled measurement at another frequency band in these a plurality of frequency bands, and the data in the described transmission gap are sent out, this communication equipment is characterised in that convergence time shortens device, when it is used for a frequency band at described a plurality of frequency bands and is switched to another frequency band in described a plurality of frequency band, shorten by the convergence time that a quadrature demodulator in a plurality of quadrature demodulators is switched to the DC offset drifts that another quadrature demodulator causes.
In communication equipment according to the present invention, shorten described convergence time by the cut-off frequency that improves following high pass filter when convergence time shortens device and can be designed as a frequency band in a plurality of frequency bands and be switched to another frequency band in a plurality of frequency bands, described high pass filter receives the output of sending from the quadrature demodulator that is associated with another frequency band a plurality of frequency bands.
Communication equipment according to the present invention is made up of the communication equipment of operating with so-called compact model.
In communication equipment according to the present invention, convergence time shortens device preferably changes high pass filter in transformable scope cut-off frequency.
Communication equipment according to the present invention can be designed as and also comprises the DC short-circuiting means, when it is used for a frequency band at a plurality of frequency bands and is switched to another frequency band in a plurality of frequency bands, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from the quadrature demodulator that is associated with a frequency band a plurality of frequency bands and send from the quadrature demodulator that is associated with another frequency band a plurality of frequency bands.
A kind of communication equipment also is provided, it comprises a plurality of quadrature demodulators that cover each frequency band in a plurality of frequency bands separately, wherein the part of the frame in the frequency band in a plurality of frequency bands is stopped in the transmission gap of transmission and carries out scheduled measurement at another frequency band in a plurality of frequency bands, and the data in the described transmission gap are sent out, this communication equipment is characterised in that the DC short-circuiting means, when it is used for a frequency band at a plurality of frequency bands and is switched to another frequency band in a plurality of frequency bands, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from the quadrature demodulator that is associated with a frequency band a plurality of frequency bands and send from the quadrature demodulator that is associated with another frequency band a plurality of frequency bands.
In communication equipment according to the present invention, the frequency band that another frequency band in a plurality of frequency bands is preferably selected after handover is performed when carrying out handover between different carrier frequencies.
Can form by mobile communication equipment according to communication equipment of the present invention.
A kind of multiband receiver also is provided, and it comprises: a plurality of quadrature demodulators, and quadrature demodulation is carried out in each the frequency band input in its a plurality of frequency band inputs of respectively doing for oneself; Switch, it is electrically connected to the output of a plurality of quadrature demodulators, and selects one of output of sending from a plurality of quadrature demodulators according to the frequency band switch-over control signal; High pass filter, it receives the output of sending from switch; And variable-gain amplification circuit, it is disposed in the downstream of high pass filter, this multiband receiver is characterised in that convergence time shortens device, it is used for when a frequency band is switched to another frequency band, shortens by the convergence time that a quadrature demodulator in a plurality of quadrature demodulators is switched to the DC offset drifts that another quadrature demodulator causes.
In multiband receiver according to the present invention, convergence time shortening device can be designed as when a frequency band is switched to another frequency band and shortens convergence time by the cut-off frequency that improves high pass filter.
In multiband receiver according to the present invention, the data relevant with frequency that convergence time shortens device preferably to be provided according to the outside produce described frequency band switch-over control signal, and produce the cut-off frequency control signal of the cut-off frequency be used to control high pass filter simultaneously, thereby the cut-off frequency of control high pass filter.
In multiband receiver according to the present invention, convergence time shortens device and can be designed as the cut-off frequency that changes high pass filter in transformable scope.
Multiband receiver according to the present invention can be designed as and also comprises the DC short circuit current, it is used for making the output of sending from last quadrature demodulator and sends from the quadrature demodulator of new selection when a frequency band is switched to another frequency band one period scheduled time of the mutual DC short circuit of output.
A kind of multiband receiver also is provided, and it comprises: a plurality of quadrature demodulators, and quadrature demodulation is carried out in each the frequency band input in its a plurality of frequency band inputs of respectively doing for oneself; Switch, it is electrically connected to the output of a plurality of quadrature demodulators, and selects one of output of sending from a plurality of quadrature demodulators according to the frequency band switch-over control signal; High pass filter, it receives the output of sending from switch; And variable-gain amplification circuit, it is disposed in the downstream of high pass filter, this multiband receiver is characterised in that the DC short circuit current, it is used for making the output of sending from last quadrature demodulator and sends from the quadrature demodulator of new selection when a frequency band is switched to another frequency band one period scheduled time of the mutual DC short circuit of output.
A kind of receiver also is provided, and it comprises: a plurality of quadrature demodulators; Switch, it is electrically connected to the output of a plurality of quadrature demodulators, and selects one of output of sending from a plurality of quadrature demodulators according to the frequency band switch-over control signal; High pass filter, it receives the output of sending from switch; And variable-gain amplification circuit, it is disposed in the downstream of high pass filter, this multiband receiver is characterised in that convergence time shortens device, it is used for when a frequency band is switched to another frequency band, shortens by the convergence time that a quadrature demodulator in a plurality of quadrature demodulators is switched to the DC offset drifts that another quadrature demodulator causes.
In receiver according to the present invention, convergence time shortening device can be designed as when a frequency band is switched to another frequency band and shortens convergence time by the cut-off frequency that improves high pass filter.
Receiver according to the present invention can be designed as and also comprises the DC short circuit current, it is used for making the output of sending from last quadrature demodulator and sends from the quadrature demodulator of new selection when a frequency band is switched to another frequency band one period scheduled time of the mutual DC short circuit of output.
A kind of receiver also is provided, and it comprises: a plurality of quadrature demodulators; Switch, it is electrically connected to the output of a plurality of quadrature demodulators, and selects one of output of sending from a plurality of quadrature demodulators according to the frequency band switch-over control signal; High pass filter, it receives the output of sending from switch; And variable-gain amplification circuit, it is disposed in the downstream of high pass filter, this multiband receiver is characterised in that the DC short circuit current, it is used for making the output of sending from last quadrature demodulator and sends from the quadrature demodulator of new selection when a frequency band is switched to another frequency band one period scheduled time of the mutual DC short circuit of output.
Advantage provided by the present invention
According to the present invention, can reduce the influence that the DC offset drifts causes signal receiving performance by shortening by the convergence time that when a frequency band is switched to another frequency band, a quadrature demodulator is switched to the DC offset drifts that another quadrature demodulator causes.
In addition, by shortening, during transmission gap, can have the enough time to be used to carry out scheduled measurement, thereby guarantee the correctness of measuring by the convergence time that a quadrature demodulator is switched to the DC offset drifts that another quadrature demodulator causes.
In addition, according to the present invention, when a frequency band was switched to another frequency band, the output of sending from the quadrature demodulator that is associated with a frequency band and the output of sending from the quadrature demodulator that is associated with another frequency band were by one period scheduled time of DC short circuit.Thereby can prevent by the generation that a quadrature demodulator is switched to the DC offset drifts that another quadrature demodulator causes, thereby guarantee that signal receiving performance will be subjected to the still less adverse effect of DC offset drifts.
Embodiment
Be used to implement most preferred embodiment of the present invention
[first embodiment]
In multiband receiver, after input signal is transformed to baseband signal, the cut-off frequency of high pass filter (HPF) is controlled, thereby improved signal receiving performance according to the first embodiment of the present invention.Not only can be applied to the multiband receiver of 2 frequency bands according to the first embodiment of the present invention, and can be applied to 3 or the multiband receiver of multiband more.
Fig. 1 is the block diagram according to the multiband receiver of first embodiment of the invention.
As shown in Figure 1, the multiband receiver according to first embodiment comprises frequency band 1 quadrature demodulator 5, frequency band 1 local signal oscillator 3, frequency band 2 quadrature demodulators 6, frequency band 2 local signal oscillators 4, switch 7, first high pass filter (HPF) 8, an AGC amplifier 9, second high pass filter 10, the 2nd AGC amplifier 11 and the 3rd high pass filter 12.
Switch 7 frequency acceptance band switch-over control signals 15.First high pass filter 8 receives HPF cut-off frequency control signal B17.In second high pass filter 10 and the 3rd high pass filter 12 each receives HPF cut-off frequency control signal A16.The example of the signal transmitter that is used to send frequency band switch-over control signal 15, HPF cut-off frequency control signal B17 and HPF cut-off frequency control signal A16 is described with reference to Fig. 8 after a while.
In Fig. 1, just illustrate double-frequency-band receiver in order to simplify description.Yet, should be noted in the discussion above that first embodiment not only can be applied to 2 frequency bands (double frequency-band) receiver, and can be applied to N frequency band receiver that wherein the N indication is equal to, or greater than three integer.
In addition, in order to simplify, I (homophase) signal and Q (quadrature) signal that send from quadrature demodulator illustrate with the individual signals line.
In the multiband receiver according to first embodiment shown in Figure 1, shorten the convergence time of DC offset drifts by the cut-off frequency that improves first high pass filter 8 according to HPF cut-off frequency control signal B17, thereby guarantee to reduce the adverse effect to the signal receiving performance of multiband receiver, described DC offset drifts does not match and causes by be switched to DC level between another frequency band time-frequency band 1 quadrature demodulator 5 and frequency band 2 quadrature demodulators 6 at frequency band.
Frequency band 1 quadrature demodulator 5 carries out quadrature demodulation according to the local signal that receives from frequency band 1 local signal oscillator 3 to the signal that receives by frequency band 1 input, thus with this signal transformation be baseband signal (I, Q).
When the frequency band that will use in multiband receiver is determined, indicate the signal of determined frequency band to be sent to the control signal generation circuit (not shown among Fig. 1) that is equipped with the multiband receiver by outside from multiband receiver.When receiving this signal, control signal generation circuit produces frequency band switch-over control signal 15 according to frequency band indicated in the signal.Frequency band switch-over control signal 15 is sent to switch 7.
According to the frequency band switch-over control signal 15 that receives, switch 7 is selected the output of sending from frequency band 1 quadrature demodulator 5 and one of the output of sending from frequency band 2 quadrature demodulators 6, and allow selected output by switch 7, described selected output indication is with the frequency band that is used.
Be imported into first high pass filter 8 by the output of sending from frequency band 1 quadrature demodulator 5 of switch 7 and the output of sending from frequency band 2 quadrature demodulators 6.First high pass filter 8 only allows HFS to pass through.
Fig. 2 is the circuit diagram of the circuit of indication and 8 equivalences of first high pass filter.
As shown in Figure 2, first high pass filter 8 is equivalent to the circuit of being made up of capacitor and resistor, and described capacitor has capacitor C 1, and an end of described resistor is electrically connected to described capacitor and other end ground connection, and described resistor has resistance R 1.
Consider equivalent electric circuit shown in Figure 2 (CR circuit), the cut-off frequency Fc and the timeconstant of first high pass filter 8 are expressed as followsin:
Fc＝1/(2πC1×R1) (1)
τ＝C1×R1
The signal that sends from first high pass filter 8 is exaggerated an AGC amplifier 9, is imported into then in second high pass filter 10.Second high pass filter 10 only allows HFS to pass through.
The signal that sends from second high pass filter 10 is exaggerated the 2nd AGC amplifier 11, is imported into then in the 3rd high pass filter 12.The 3rd high pass filter 12 only allows HFS to pass through.
Thereby, the output of sending from frequency band 1 quadrature demodulator 5 or the output of sending from frequency band 2 quadrature demodulators 6 by from 12 outputs of the 3rd high pass filter as baseband signal, i.e. I and Q signal 13.
When an AGC amplifier 9 and 11 pairs of signals of the 2nd AGC amplifier amplify, change each Amplifier Gain in an AGC amplifier 9 and the 2nd AGC amplifier 11 according to AGC control signal 14, make I and Q signal can have required output level.
In second high pass filter 10 and the 3rd high pass filter 12 each improves cut-off frequency according to HPF cut-off frequency control signal A16 promptly makes the convergence of interferences (glitch) noise, the adverse effect that the interference noise of generation causes the signal receiving performance of multiband receiver when reducing to be changed rapidly by the gain at an AGC amplifier 9 and the 2nd AGC amplifier 11.
In the multiband receiver shown in Fig. 1 according to first embodiment, for example when switch 7 switches output according to band switch control signal 15,, the DC of frequency band 1 quadrature demodulator 5 and frequency band 2 quadrature demodulators 6 generates following DC offset drifts Δ V because being offset not match mutually.
ΔV＝V1-V2 (3)
In equation (3), the dc voltage of V1 indication frequency band 1 quadrature demodulator 5, and the dc voltage of V2 indication frequency band 2 quadrature demodulators 6.
The DC offset drifts Δ V that generates when frequency band is switched to another frequency band determines according to the time constant of first high pass filter 8.
According to equation (2) and (3), the convergence time of DC offset drifts Δ V can be represented with following equation (4).
V
0＝ΔV×e
(-t/τ)
∴t＝-τ×ln(V
0/ΔΔ) (4)
In equation (4), " V
0" indicate the DC offset drifts that sends from first high pass filter 8, the convergence time of " t " indication DC offset drifts, and " e " indicates the truth of a matter of natural logrithm.
In order to simplify, ignore the influence that second high pass filter 10 and the 3rd high pass filter 12 are caused, the DC offset drifts that generates when frequency band is switched to another frequency band is enlarged into the degree that equates with the gain of an AGC amplifier 9 and the 2nd AGC amplifier 11, is output as IQ output 13 then.In other words, included DC offset drifts changes on amplitude according to the gain of an AGC amplifier 9 and the 2nd AGC amplifier 11 in the IQ output 13.
Viq＝G×V
0＝(G9+G11)×ΔV×e
(-t/τ) (9)
tiq＝-τ×ln(V
0/ΔΔV(G9+G11)) (10)
In equation (9) and (10), the DC offset drifts that is generated in " Viq " indication IQ output 13, the convergence time of the DC offset drifts that is generated in " tiq " indication IQ output 13, the magnification ratio of " G9 " indication the one AGC amplifier 9, and the magnification ratio of " G11 " indication the 2nd AGC amplifier 11.
As an example, illustrate " t " and " V among Fig. 3
0" between relation, wherein Δ V is 10mV, τ is 106 microseconds (cut-off frequency Fc=1.5kHz), and G is 12dB (=* 4), illustrates " tiq " and the relation between " Viq " under the same terms among Fig. 4.
Generated the DC offset drifts owing to frequency band being switched to another frequency band.In multiband receiver according to first embodiment, when frequency band switch-over control signal 15 is sent to switch 7, HPF cut-off frequency control signal B17 is sent to first high pass filter 8, in addition, made the cut-off frequency Fc of first high pass filter 8 improve a certain period before restraining at the DC offset drifts.
Thereby reduced timeconstant, and therefore can shorten convergence time tiq according to the DC offset drifts Viq of equation (6) definition.
As " t " shown in Figure 3 and " V
0" between relation and " tiq " and a reference example of the relation between " Viq " shown in Figure 4, illustrate observed when cut-off frequency Fc is enhanced 3kHz " t " and " V among Fig. 5
0" between relation, and illustrate " tiq " and the relation between " Viq " under the same terms among Fig. 6.
More conspicuous as between the comparison between Fig. 3 and Fig. 5 and Fig. 4 and Fig. 6, the shortening of the convergence time tiq of DC offset drifts Viq and the raising of cut-off frequency Fc be inversely proportional to (the cut-off frequency Fc among Fig. 5 and Fig. 6 has improved twice than the cut-off frequency Fc among Fig. 3 and Fig. 4).
As shown in Figure 6, the convergence time tiq of the DC offset drifts Viq that generates when frequency band is switched to another frequency band is equal to or less than 250 microseconds.
Therefore, when handover will be performed, can there be enough a period of times in frequency band, to measure (for example, the measurement of electric field strength), thereby have guaranteed correct measurement.This helps to be avoided mistake during carrying out handover.
For example, if transmission gap is 5 time slots (for example, suppose that a time slot equals 667 microseconds, then 5 time slots equal 3335 microseconds), then can have in first time slot half or more than half time.
By contrast, in Fig. 4, the convergence time tiq of the DC offset drifts that generates when frequency band is switched to another frequency band is about 500 microseconds, thereby causes can't measuring in nearly all time in first time slot in transmission gap.
Fig. 3 and example shown in Figure 4 show the situation that does not improve the cut-off frequency Fc of first high pass filter 8 when frequency band is switched to another frequency band according to HPF cut-off frequency control signal B17.
As mentioned above, the multiband receiver according to first embodiment provides following advantage:
(1) by improves the cut-off frequency of first high pass filter 8 according to HPF cut-off frequency control signal B17, can shorten the convergence time tiq of DC offset drifts Viq included in the IQ output 13, thereby guarantee to reduce the adverse effect that DC offset drifts Viq applies the signal receiving performance of multiband receiver.
(2) by shortening the convergence time tiq of DC offset drifts Viq, can there be enough a period of times in transmission gap, to carry out essential measurement, thereby guarantee the correctness of measurement.
(3) frequency band switch-over control signal 15 produces by selecting a certain frequency.The cut-off frequency that can be synchronized with 15 pairs first high pass filters 8 of frequency band switch-over control signal is controlled.
(4) can at random define the convergence time tiq of DC offset drifts Viq according to the excursion of the cut-off frequency of first high pass filter 8.
(5), also can only shorten the convergence time tiq of DC offset drifts Viq by the cut-off frequency that improves first high pass filter 8 even after input signal has been transformed to baseband signal in the receiver of two or more frequency bands.
(6) not only when being switched to another frequency band, frequency band can obtain above-mentioned advantage (1), and as the same when frequency is switched to another frequency.For example, 2110MHz and the frequency between the 2170MHz that first embodiment can be applied in the 2G frequency band are switched, perhaps 875MHz in the 800M frequency band and the frequency between the 885MHz are switched, and wherein, frequency band switch-over control signal 15 shown in Figure 1 is used from the effect of the control signal of switching frequency.
[second embodiment]
Fig. 7 is the block diagram according to the multiband receiver of second embodiment of the invention.
Only be to comprise DC short switch (in claims, being defined as DC short-circuiting means or DC short circuit current) and do not use HPF cut-off frequency control signal B17 that described DC short switch is arranged in parallel between the output of sending from frequency band 1 quadrature demodulator 5 and the output of sending from frequency band 2 quadrature demodulators 6 according to the multiband receiver of second embodiment according to the multiband receiver of second embodiment and architectural difference according to the multiband receiver of first embodiment.Correspondingly, with according to the parts of the multiband receiver of first embodiment or the corresponding parts of element or element be provided identical label.
DC short switch 20 is switched on when receiving frequency band switch-over control signal 15 and is turned off after over and done with certain period, and wherein said frequency band switch-over control signal 15 will be transfused to when frequency band is switched to another frequency band.
In the multiband receiver according to second embodiment, the DC offset drifts that generates when being switched to another with switch of frequency band in one of quadrature demodulator 5 and 6 is not to be generated by the DC short circuit output of sending towards each other from quadrature demodulator 5 and 6.
As above illustrated, in multiband receiver according to second embodiment, DC short switch 20 when frequency band is switched to another frequency band, make the output of sending from frequency band 1 quadrature demodulator 5 with from the mutual DC short circuit period of output that frequency band 2 quadrature demodulators 6 send, thereby guarantee to prevent to generate the DC offset drifts.
In according to the multiband receiver of second embodiment, also can use HPF cut-off frequency control signal B17.
Example
As example, the example of having used 3 frequency band receivers of the present invention has been described hereinafter according to multiband receiver of the present invention.
Fig. 8 is the block diagram according to the multiband receiver of an example of the present invention.
Multiband receiver according to this example is by antenna 101, a plurality of duplexers (antenna filter 103), switch (RFSW) 102, a plurality of low noise amplifiers (LNA) 104, transmitter 100, a plurality of band pass filters (BPF) 105, first to the 3rd quadrature demodulator 106, switch 107, first high pass filter 108, the one AGC amplifier 109, second high pass filter 110, the 2nd AGC amplifier 111, the 3rd high pass filter 112, AD converter 113, digital signal processor (DSP) 114, CCPU 121, combinator serial line interface 120, voltage controlled oscillator (VCO) 118, phase-locked loop (PLL) 119 and serial line interface 122 are formed, wherein one of antenna 101 and duplexer 103 are electrically connected mutually by switch 102, a plurality of low noise amplifiers 104 are electrically connected to each in the duplexer 103 separately, transmitter 100 is electrically connected to duplexer 103, a plurality of band pass filters 105 are electrically connected to each in the low noise amplifier 104 separately, first to the 3rd quadrature demodulator 106 is electrically connected to each in the band pass filter (BPF) 105 separately, switch 107 is selected one of first to the 3rd quadrature demodulator 106, the output of sending from the quadrature demodulator of being selected by switch 107 is imported into first high pass filter 108, the one AGC amplifier 109 amplifies the output that sends from first high pass filter 108, second high pass filter 110 receives the output of sending from an AGC amplifier 109,111 pairs of outputs of sending from second high pass filter 110 of the 2nd AGC amplifier are amplified, AD converter 113 will be numeral output from the simulation output transform that the 3rd high pass filter 112 sends, 114 pairs of digital signals of sending from AD converter 113 of digital signal processor are carried out Base-Band Processing, the operation of the above-mentioned parts of CCPU 121 controls, combinator serial line interface 120 is used from the effect of the device that shortens convergence time, and voltage controlled oscillator 118 sends the frequency band local signal.
First to the 3rd quadrature demodulator 106 covers frequency band A, B and C respectively.
The signal that receives by antenna 101 is sent to duplexer 103 by switch 102.The signal that each duplexer 103 allows to have receive frequency passes through, thereby removes unnecessary frequency part.
After this, the signal that receives is sent to first to the 3rd quadrature demodulator 106 by low noise amplifier (LNA) 104 and band pass filter 105.
The signal that receives in first to the 3rd quadrature demodulator 106 of respectively covering frequence frequency band A, B and C by demodulation.The IQ signal that sends from the quadrature demodulator 106 that covers switch 107 selected frequency band is imported into first high pass filter 108.
Under difference modes, send each (I and IB, Q and QB) in I signal and the Q signal in the mode of balance.
The output signal of sending from first high pass filter 108 (analog signal) is input to AD converter 113 by an AGC amplifier 109, second high pass filter 110, the 2nd AGC amplifier 111 and the 3rd high pass filter 112, and is transformed to digital signal in AD converter 113.
Digital signal is sent to the digital signal processor (DSP) of carrying out Base-Band Processing.Digital signal processor 114 sends to demodulation part (not shown) with output signal.
When AD converter 113 receives I and Q signal, digital signal processor 114 sends to serial line interface 122 according to the I and the Q signal that receive with control signal.Serial line interface 122 produces AGC control signal 123 according to the control signal that receives, then AGC control signal 123 is sent to an AGC amplifier 109 and the 2nd AGC amplifier 111, thereby control the gain of an AGC amplifier 109 and the 2nd AGC amplifier 111 changeably.
Voltage controlled oscillator (VCO) 118 plays frequency band local signal oscillator.Particularly, voltage controlled oscillator 118 sends to relevant quadrature demodulator in first to the 3rd quadrature demodulator 106 with clock signal as local signal (signal of local oscillations).
The basic frequency of the clock signal that combinator serial line interface 120 will receive from voltage controlled oscillator 118 is selected as the frequency at selected frequency band.
In order to simplify, in Fig. 8, only illustrate a voltage controlled oscillator 118 that serves as frequency band local signal oscillator.Yet as shown in Figure 1, multiband receiver can be designed as and comprises a plurality of voltage controlled oscillators, and these a plurality of voltage controlled oscillators cover each in a plurality of frequency bands separately.Multiband receiver shown in Figure 8 is designed to comprise three voltage controlled oscillators 118 that are associated with three frequency band A, B and C.
Voltage controlled oscillator 118 and phase-locked loop (PLL) 119 cooperated each other and defined frequency synthesizer.
Frequency band switch-over control signal 115 and the HPF cut-off frequency control signal 117 sent from combinator serial line interface 120 (being used to shorten the device of convergence time) correspond respectively to frequency band switch-over control signal 15 shown in Figure 1 and HPF cut-off frequency control signal B17.Under the control of CCPU 121, combinator serial line interface 120 sends to the switch 107 and first high pass filter 108 respectively with frequency band switch-over control signal 115 and HPF cut-off frequency control signal 117.
In example, frequency band switch-over control signal 115 and HPF cut-off frequency control signal 117 are produced independently of one another.Yet, should be noted that frequency band switch-over control signal 115 and HPF cut-off frequency control signal 117 can be generated as single control signal.
Under the control of CCPU 121, combinator serial line interface 120 sends to second high pass filter 110 and the 3rd high pass filter 112 with HPF cut-off frequency control signal 116.HPF cut-off frequency control signal 116 is corresponding to HPF cut-off frequency control signal A16 shown in Figure 1.
The adverse effect that the signal receiving performance of multiband receiver is applied for the interference noise that reduces when the gain of an AGC amplifier 109 and the 2nd AGC amplifier 111 changes rapidly to generate, second high pass filter 110 and the 3rd high pass filter 112 improve cut-off frequency according to the HPF cut-off frequency control signal 116 that receives from combinator serial line interface 120, thereby interference noise is promptly restrained.
In Fig. 8, voltage controlled oscillator 118 and phase-locked loop (PLL) 119 (for example being made up of phase frequency comparator, charge pump, loop filter etc.) is illustrated as separated components.Yet, should be noted in the discussion above that voltage controlled oscillator 118 can be provided in the phase-locked loop 119.
Fig. 9 is the block diagram of quadrature demodulator 106 shown in Figure 8.
Figure 10 is the circuit diagram of an example of high pass filter 108.
As shown in figure 10, first high pass filter 108 is equivalent to the CR circuit of being made up of capacitor C, a pair of resistor R and switch SW 1.Capacitor C has capacitor C 1.One end of each resistor R is electrically connected to capacitor C, and other end ground connection.Each resistor R has resistance R 1.In addition, this is electrically connected resistor R is in parallel mutually.Switch SW 1 is disposed between one of resistor R and the capacitor C.
Switch SW 1 receives HPF cut-off frequency control signal 117.Switch SW 1 is turned off when HPF cut-off frequency control signal 117 inertias, and switch SW 1 is switched on when 117 activities of HPF cut-off frequency control signal.
Switch SW 1 is turned off when HPF cut-off frequency control signal 117 inertias, and in this case, first high pass filter of being made up of CR circuit shown in Figure 10 108 has the resistance that equates with resistance R.
On the other hand, switch SW 1 is switched on when 117 activities of HPF cut-off frequency control signal, in this case, the timeconstant that the resistance of first high pass filter 108 equals R1/2, first high pass filter 108 is reduced to half, and the cut-off frequency Fc of first high pass filter 108 is doubled.
The structure of first high pass filter 108 is not limited to all such structures of CR circuit as shown in figure 10, and this structure is controlled the resistance of definition time constant τ changeably according to HPF cut-off frequency control signal 117.For example, first high pass filter 108 can be designed as the structure with the capacitor C 1 that is used for controlling changeably definition time constant τ.
Second high pass filter 110 that the cut-off frequency that is had is controlled by HPF cut-off frequency control signal 116 changeably is structurally identical with first high pass filter 108 with the 3rd high pass filter 112.
Description of drawings
[Fig. 1] Fig. 1 is the block diagram according to the multiband receiver of first embodiment of the invention.
[Fig. 2] Fig. 2 is the circuit diagram with the circuit of first high pass filter, 8 equivalences shown in Figure 1.
[Fig. 3] Fig. 3 shows convergence time " t " and the DC offset drifts V that exports from first high pass filter 8 (Fc=1.5KHz)
oBetween relation.
The convergence time " tiq " that [Fig. 4] Fig. 4 shows DC offset drifts included in the IQ output and IQ export the relation between the DC offset drifts " Viq " included in (Fc=1.5KHz).
[Fig. 5] Fig. 5 shows convergence time " t " and the DC offset drifts V that exports from first high pass filter 8 (Fc=3KHz)
oBetween relation.
The convergence time " tiq " that [Fig. 6] Fig. 6 shows DC offset drifts included in the IQ output and IQ export the relation between the DC offset drifts " Viq " included in (Fc=3KHz).
[Fig. 7] Fig. 7 is the block diagram according to the multiband receiver of second embodiment of the invention.
[Fig. 8] Fig. 8 is the block diagram according to 3 frequency band receivers of example of the present invention.
[Fig. 9] Fig. 9 is the block diagram of an example of quadrature demodulator.
[Figure 10] Figure 10 is the circuit diagram of an example of first high pass filter 108 shown in Figure 8.
Label declaration
1 input of 1 frequency band
2 inputs of 2 frequency bands
3 frequency bands, 1 local signal oscillator
4 frequency bands, 2 local signal oscillators
5 frequency bands, 1 quadrature demodulator
6 frequency bands, 2 quadrature demodulators
7 switches
8 first high pass filters (HPF)
10 second high pass filters (HPF)
12 the 3rd high pass filters (HPF)
9 the one AGC amplifiers
11 the 2nd AGC amplifiers
13I and Q output
The 14AGC control signal
15 frequency band switch-over control signals
16HPF cut-off frequency control signal A
17HPF cut-off frequency control signal B
The 20DC short switch
100 transmitters
101 antennas
The 102RF switch
103 duplexers
104 low noise amplifiers (LNA)
105BPF
106 quadrature demodulators
107 switches
108 first high pass filters
109 the one AGC amplifiers
110 second high pass filters
111 the 2nd AGC amplifiers
112 the 3rd high pass filters
The 113AD converter
114 digital signal processors (DSP)
115 frequency band switch-over control signals
116HPF cut-off frequency control signal
117HPF cut-off frequency control signal
118 voltage controlled oscillators (VCO)
119 phase-locked loops (PLL)
120 combinator serial line interfaces (being used to shorten the device of convergence time)
121CCPU
122 serial line interfaces
The 123AGC control signal
Claims (17)
1. communication equipment, it comprises a plurality of quadrature demodulators, in described a plurality of quadrature demodulator each covers each in a plurality of frequency bands separately, wherein the part of the frame in the frequency band in described a plurality of frequency bands is stopped in the transmission gap of transmission and carries out scheduled measurement at another frequency band in described a plurality of frequency bands, and the data in the described transmission gap are sent out
Described communication equipment is characterised in that:
Convergence time shortens device, when it is used for a described frequency band at described a plurality of frequency bands and is switched to described another frequency band in described a plurality of frequency band, shorten the convergence time of the DC offset drifts that causes by a quadrature demodulator in described a plurality of quadrature demodulators is switched to another quadrature demodulator.
2. communication equipment as claimed in claim 1, wherein, when the described frequency band in described a plurality of frequency bands is switched to described another frequency band in described a plurality of frequency band, described convergence time shortens device and shortens described convergence time by the cut-off frequency that improves following high pass filter, and described high pass filter receives the output of sending from the quadrature demodulator that is associated with described another frequency band described a plurality of frequency bands.
3. communication equipment as claimed in claim 2, wherein, described convergence time shortens device changes described high pass filter in transformable scope described cut-off frequency.
4. as any one described communication equipment in the claim 1 to 3, also comprise the DC short-circuiting means, when it is used for a described frequency band at described a plurality of frequency bands and is switched to described another frequency band in described a plurality of frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from the quadrature demodulator that is associated with a described frequency band described a plurality of frequency bands and send from the quadrature demodulator that is associated with described another frequency band described a plurality of frequency bands.
5. communication equipment, it comprises a plurality of quadrature demodulators, in described a plurality of quadrature demodulator each covers each in a plurality of frequency bands separately, wherein the part of the frame in the frequency band in described a plurality of frequency bands is stopped in the transmission gap of transmission and carries out scheduled measurement at another frequency band in described a plurality of frequency bands, and the data in the described transmission gap are sent out
Described communication equipment is characterised in that:
The DC short-circuiting means, when it is used for a described frequency band at described a plurality of frequency bands and is switched to described another frequency band in described a plurality of frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from the quadrature demodulator that is associated with a described frequency band described a plurality of frequency bands and send from the quadrature demodulator that is associated with described another frequency band described a plurality of frequency bands.
6. as any one the described communication equipment in the claim 1 to 5, wherein, in the time will carrying out handover between different carrier frequencies, described another frequency band in described a plurality of frequency bands is the frequency band of selecting after described handover is performed.
7. as any one the described communication equipment in the claim 1 to 6, wherein, described communication equipment is made up of mobile communication equipment.
8. multiband receiver, it comprises:
A plurality of quadrature demodulators, wherein each quadrature demodulator is carried out quadrature demodulation at each the frequency band input in a plurality of frequency band inputs separately;
Switch, it is electrically connected to the output of described quadrature demodulator, and selects one of output of sending from described quadrature demodulator according to the frequency band switch-over control signal;
High pass filter, it receives the output of sending from described switch; And
Variable-gain amplification circuit, it is disposed in the downstream of described high pass filter,
Described multiband receiver is characterised in that:
Convergence time shortens device, and it is used for when a frequency band is switched to another frequency band, shortens the convergence time of the DC offset drifts that causes by a quadrature demodulator in described a plurality of quadrature demodulators is switched to another quadrature demodulator.
9. multiband receiver as claimed in claim 8, wherein, described convergence time shortens device when a frequency band is switched to another frequency band, shortens described convergence time by the cut-off frequency that improves described high pass filter.
10. multiband receiver as claimed in claim 9, wherein, the data relevant with frequency that described convergence time shortens device to be provided according to the outside produce described frequency band switch-over control signal, and produce the cut-off frequency control signal of controlling the cut-off frequency of described high pass filter according to it simultaneously, thereby control the cut-off frequency of described high pass filter.
11. as claim 9 or 10 described multiband receivers, wherein, described convergence time shortens device changes described high pass filter in transformable scope described cut-off frequency.
12. as the described multiband receiver of claim 8 to 11, also comprise the DC short circuit current, it is used for when a frequency band is switched to another frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from last quadrature demodulator and send from the quadrature demodulator of new selection.
13. a multiband receiver, it comprises:
A plurality of quadrature demodulators, wherein quadrature demodulation is carried out in each frequency band input of respectively doing for oneself in the input of a plurality of frequency bands of each quadrature demodulator;
Switch, it is electrically connected to the output of described quadrature demodulator, and selects one of output of sending from described quadrature demodulator according to the frequency band switch-over control signal;
High pass filter, it receives the output of sending from described switch; And
Variable-gain amplification circuit, it is disposed in the downstream of described high pass filter,
Described multiband receiver is characterised in that:
The DC short circuit current, it is used for when a frequency band is switched to another frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from last quadrature demodulator and send from the quadrature demodulator of new selection.
14. a receiver, it comprises:
A plurality of quadrature demodulators;
Switch, it is electrically connected to the output of described quadrature demodulator, and selects one of output of sending from described quadrature demodulator according to the frequency band switch-over control signal;
High pass filter, it receives the output of sending from described switch; And
Variable-gain amplification circuit, it is disposed in the downstream of described high pass filter,
Described receiver is characterised in that:
Convergence time shortens device, and it is used for when a frequency band is switched to another frequency band, shortens by the convergence time that one of described a plurality of quadrature demodulators is switched to the DC offset drifts that another quadrature demodulator causes.
15. receiver as claimed in claim 14, wherein, described convergence time shortens device when a frequency band is switched to another frequency band, shortens described convergence time by the cut-off frequency that improves described high pass filter.
16. as claim 14 or 15 described receivers, also comprise the DC short circuit current, it is used for when a frequency band is switched to another frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from last quadrature demodulator and send from the quadrature demodulator of new selection.
17. a receiver, it comprises:
A plurality of quadrature demodulators;
Switch, it is electrically connected to the output of described quadrature demodulator, and selects one of output of sending from described quadrature demodulator according to the frequency band switch-over control signal;
High pass filter, it receives the output of sending from described switch; And
Variable-gain amplification circuit, it is disposed in the downstream of described high pass filter,
Described receiver is characterised in that:
The DC short circuit current, it is used for when a frequency band is switched to another frequency band, the one period scheduled time of the mutual DC short circuit of output that makes the output of sending from last quadrature demodulator and send from the quadrature demodulator of new selection.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2005008309 | 2005-01-14 | ||
| JP008309/2005 | 2005-01-14 | ||
| PCT/JP2006/300230 WO2006075631A1 (en) | 2005-01-14 | 2006-01-11 | Communication device, multi-band reception device, and reception device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN101103538A true CN101103538A (en) | 2008-01-09 |
| CN101103538B CN101103538B (en) | 2014-06-04 |
Family
ID=36677656
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN200680002386.3A Expired - Fee Related CN101103538B (en) | 2005-01-14 | 2006-01-11 | Communication device, multi-band reception device, and reception device |
Country Status (5)
| Country | Link |
|---|---|
| US (1) | US8238858B2 (en) |
| EP (1) | EP1845626A1 (en) |
| JP (2) | JP4241832B2 (en) |
| CN (1) | CN101103538B (en) |
| WO (1) | WO2006075631A1 (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105308478A (en) * | 2013-06-18 | 2016-02-03 | 松下知识产权经营株式会社 | Mobile-body detection device |
| CN105721124A (en) * | 2014-12-22 | 2016-06-29 | 松下电器产业株式会社 | Wireless Communications System And Wireless Communication Device |
| CN109450472A (en) * | 2018-12-14 | 2019-03-08 | 安徽德诺科技股份公司 | A kind of switch actuator and signal receiving circuit |
| WO2021093417A1 (en) * | 2019-11-12 | 2021-05-20 | 华为技术有限公司 | Receiver, optical line terminal and passive optical network system |
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| EP2039015A2 (en) * | 2006-06-22 | 2009-03-25 | Nxp B.V. | Dual band receiver with control means for preventing signal overloading |
| JP2008258741A (en) * | 2007-04-02 | 2008-10-23 | Nec Electronics Corp | Receiving apparatus and signal processing method |
| US20090088106A1 (en) * | 2007-09-27 | 2009-04-02 | Nanoamp Solutions Inc. (Cayman) | Radio frequency filtering |
| US8086205B2 (en) | 2008-05-02 | 2011-12-27 | Infineon Technologies Ag | Multimode receiver with active blocker suppression |
| US9319018B2 (en) * | 2009-12-04 | 2016-04-19 | Telefonaktiebolaget L M Ericsson (Publ) | Detection of radio signals in a receiver |
| US20110194623A1 (en) * | 2010-02-09 | 2011-08-11 | Broadcom Corporation | Reconfigurable Filter for Cable Frequency Tilt Compensation and MoCA Transmitter Leakage Cancellation |
| US9077393B2 (en) | 2010-08-30 | 2015-07-07 | Samsung Electronics Co., Ltd. | Apparatus and method for a multi-band radio operating in a wireless network |
| JPWO2013187037A1 (en) * | 2012-06-14 | 2016-02-04 | パナソニックＩｐマネジメント株式会社 | Mixer, mixer device, and radio receiver including the same |
| DE102013222293A1 (en) | 2013-11-04 | 2015-05-07 | Robert Bosch Gmbh | battery module |
| US9490764B2 (en) | 2014-04-17 | 2016-11-08 | Interdigital Patent Holdings, Inc. | Fast automatic gain control (AGC) for packet based systems |
| EP3244584B1 (en) * | 2016-05-11 | 2019-07-03 | Stichting IMEC Nederland | Receiver for frequency offset correction |
| KR102573878B1 (en) * | 2017-01-17 | 2023-09-01 | 삼성전자주식회사 | An apparatus for processing signal in a wireless communication system and a method thereof |
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| CN105721124A (en) * | 2014-12-22 | 2016-06-29 | 松下电器产业株式会社 | Wireless Communications System And Wireless Communication Device |
| CN109450472A (en) * | 2018-12-14 | 2019-03-08 | 安徽德诺科技股份公司 | A kind of switch actuator and signal receiving circuit |
| CN109450472B (en) * | 2018-12-14 | 2024-04-02 | 安徽德诺科技股份公司 | Switch actuator and signal receiving circuit |
| WO2021093417A1 (en) * | 2019-11-12 | 2021-05-20 | 华为技术有限公司 | Receiver, optical line terminal and passive optical network system |
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Also Published As
| Publication number | Publication date |
|---|---|
| CN101103538B (en) | 2014-06-04 |
| JP2009077420A (en) | 2009-04-09 |
| US20090022246A1 (en) | 2009-01-22 |
| JP4650558B2 (en) | 2011-03-16 |
| JPWO2006075631A1 (en) | 2008-06-12 |
| US8238858B2 (en) | 2012-08-07 |
| WO2006075631A1 (en) | 2006-07-20 |
| JP4241832B2 (en) | 2009-03-18 |
| EP1845626A1 (en) | 2007-10-17 |
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