WO2024088990A1 - Circuit et procédé pour faire fonctionner un circuit - Google Patents

Circuit et procédé pour faire fonctionner un circuit Download PDF

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Publication number
WO2024088990A1
WO2024088990A1 PCT/EP2023/079537 EP2023079537W WO2024088990A1 WO 2024088990 A1 WO2024088990 A1 WO 2024088990A1 EP 2023079537 W EP2023079537 W EP 2023079537W WO 2024088990 A1 WO2024088990 A1 WO 2024088990A1
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Prior art keywords
voltage
circuit
common mode
mode voltage
phase
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PCT/EP2023/079537
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German (de)
English (en)
Inventor
Fabian Schnabel
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Fraunhofer-Gesellschaft zur Förderung der angewandten Forschung e.V.
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Publication of WO2024088990A1 publication Critical patent/WO2024088990A1/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H02M1/123—Suppression of common mode voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration

Definitions

  • Embodiments of the present invention relate to an (electrical) circuit with a power converter circuit and to a corresponding operating method. According to different aspects of the invention, there are circuits designed for different applications (for example TN-CS system, TN-S system or TT system). Further embodiments relate to a computer-implemented method. Preferred embodiments relate to a method for reducing leakage currents for non-isolating rectifiers. When operating non-isolating rectifiers (AC-DC conversion, unidirectional or bidirectional), the common mode voltage of the rectifier creates leakage currents in the Y capacitors of the rectifier and the connected DC source or sink. Fig.
  • FIG. 1 shows a simplified common mode equivalent circuit diagram of a typical rectifier 100 and its EMC filter 102.
  • High-frequency components of the common mode voltage can be reduced by the common mode inductances L CM of the filter 102.
  • L CM common mode inductances
  • the publication [1] describes that it is not possible to reduce the leakage currents below the limit value with the B6 topology and the EMC filter used.
  • a later publication [2] describes that the problem of leakage currents for the three-phase topology can be reduced by an intermediate circuit symmetry controller for the capacitors.
  • the active filter 114 (ripple port RP) balances out the power consumption from the mains, which pulsates at 100 Hz, by keeping the total power constant through anti-phase control. This means that the total voltage ⁇ ⁇ 1 + ⁇ ⁇ 2 can be kept constant. Since the voltage at ⁇ ⁇ 2 is thus kept constant in theory, the low-frequency leakage current can be greatly reduced by C CM .
  • a major challenge is the precise control of the power of the active filter 114 (RP area). This can only be done with limited dynamics. Furthermore, displacement voltages and potential differences between the operating and system earths cannot be compensated.
  • the converter circuit has a DC voltage connection with two potential taps and one or more phase connections.
  • the controller is designed to control switchable elements of the converter circuit, such as transistors of an H4 or B6 bridge or generally transistors of the converter circuit, namely in such a way that a voltage is applied to FH221002PDE-2022297546 one of the two potential taps and/or at one or more phase connections based on a common mode voltage.
  • the common mode voltage ⁇ ⁇ ⁇ ⁇ is influenced by the following factors, among others: - fluctuation in the total intermediate circuit voltage - voltage drop across the filter and mains impedance - displacement voltage - potential difference between the operating and system earths - fluctuations in the intermediate circuit voltage ⁇ ⁇ ⁇ , particularly important in single-phase operation - asymmetrical currents in three-phase operation, e.g. harmonics or unbalanced loads
  • Embodiments of the invention show four methods for determining the common mode voltage V CM for modulating the converter circuit, which take the (above) factors influencing the common mode voltage ⁇ ⁇ ⁇ ⁇ partially or fully into account.
  • the calculated common mode voltage ⁇ ⁇ ⁇ ⁇ ⁇ can be compensated by modulating the voltage at one of the two potential taps and/or at one or more phase connections taking into account the calculated common mode voltage ⁇ ⁇ ⁇ ⁇ .
  • the methods for calculating the common mode voltage ⁇ ⁇ ⁇ ⁇ and thus also for compensating it can be used separately or in combination. Individual calculation methods and preferred combinations are explained below.
  • a fluctuating total intermediate circuit voltage ⁇ ⁇ ⁇ leads to a fluctuating common mode voltage ⁇ ⁇ ⁇ ⁇ during operation. This influence can be compensated according to a first method based on the formula can be calculated.
  • ⁇ ⁇ ⁇ is the measured value of the voltage between two potential taps of the DC voltage connection.
  • the voltage is the mean value of the measured voltage or, for example, the setpoint of a regulated intermediate circuit voltage.
  • FH221002PDE-2022297546 According to a second method, the common mode voltage calculated based on the following formula.
  • the common mode voltage ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ is calculated based on the following formula:
  • the common mode voltage ⁇ ⁇ ⁇ can be calculated based on the formula can be calculated. The methods partially enable the composition of different influencing factors, as will be explained in detail below.
  • Preferred, exemplary combinations are methods 1+2 and 1+4, since (firstly) all significant influencing variables (including filter influences) can be compensated and (secondly) good dynamics are achieved.
  • Embodiments of the present invention are based on the knowledge that the leakage currents of a capacitor C CM connected on the DC voltage side or generally of a capacitance present or formed on the DC voltage side can be reduced by a clever control method (for the converter circuit, such as a non-isolated rectifier or AC-DC converter). By choosing half the average fluctuation as the modulation variable, the common mode voltage is modulated with respect to ground potential so that this voltage ⁇ ⁇ ⁇ ⁇ at the capacitance C CM is kept constant and leakage currents via the capacitor C CM are avoided.
  • the table for the calculation methods for the common mode voltage also assigns the different quantities to be compensated to the individual calculation methods.
  • the calculation methods can also be used in combination. Combination 1+4 is explained below as an example.
  • phase current measurement ⁇ ( ⁇ ) of the mains current or the inductances L D1 is carried out as input.
  • the circuit according to embodiments has a measuring unit which is designed to determine or measure the corresponding voltage (see table or phase) and to pass it on to the calculation unit as an input variable.
  • the concept described above is designed for different network types, such as TN-CS or TN-S.
  • the concept of common mode voltage suppression can also be used in different modes.
  • the currents in the one or more phases are symmetrical. An example of this is the three-phase operation of the converter circuit.
  • the currents in the one or more phases can also be asymmetrical.
  • An example of this would be the single-phase operation of the converter circuit.
  • the calculation method of ⁇ ⁇ ⁇ can vary.
  • the symmetrical for example three-phase case, one of the calculations explained above for ⁇ ⁇ ⁇ is used, e.g. according to method 1.
  • FH221002PDE-2022297546 In an asymmetrical case, such as an unbalanced load, the common mode voltage of the filter elements L D1 , L D2 and the network impedance must be compensated in addition to the fluctuation of the intermediate circuit voltage.
  • the converter circuit is designed for single-phase operation or only for single-phase operation.
  • L defines the inductance
  • R the resistance
  • i the associated current
  • v the associated voltage
  • the index marks the position in the circuit, with 1 representing the inductances or resistances between the center tap of the converter circuit and an optional filter, 2 the inductances or resistances between the optional filter and the phase connection, and G the inductances or resistances on the mains side.
  • the indices for 1 and 2 together create an LCL filter/sine filter.
  • a capacitance (one capacitance per phase connection) or generally a capacitance arrangement can be provided at the phase connections.
  • an intermediate circuit or a split intermediate circuit can be provided on the DC voltage side.
  • the intermediate circuit or the split intermediate circuit is arranged, for example, between two potential taps of the DC voltage connection.
  • a center point of the intermediate circuit or the symmetrical intermediate circuit can be connected to one phase via a capacitor or to several phases via a capacitor arrangement.
  • the circuit can be used as part of a rectifier or a non-isolated rectifier or a battery charger.
  • the rectifier such as a non-isolated rectifier or a rectifier of a battery charger, is connected to a TN-C, TN-CS or TN-S network for operation.
  • the method can be computer-implemented. All embodiments explained above are optimized for common mode compensation in TN-C, TN-S or TN-CS systems. Common mode voltage suppression in TT systems can be achieved according to further embodiments by the variant with the formula ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ 2 , since this is suitable for all network types.
  • the circuit comprises a converter circuit which has a first voltage connection with two potential taps and one or more phase connections.
  • the controller is designed to FH221002PDE-2022297546 switchable elements of the converter circuit such that a voltage at one of the two potential taps and/or at one of the phase connections is modulated based on a common mode voltage.
  • the circuit further comprises a measuring unit which is designed to determine a voltage between one of the potential taps and the local earth potential PE (e.g. protective conductor connection of the device). This measurement can detect an occurring displacement voltage or potential difference between the mains and system earth.
  • the common mode voltage is determined using the voltage measured by the measuring unit.
  • a further embodiment creates a rectifier, non-isolated rectifier or a battery charger with an explained circuit.
  • the rectifier is preferably designed for operation on a TT system, but can also be operated on another mains system, such as a TN-C or TN-CS or TN-S system, according to further embodiments.
  • a further embodiment provides a method for operating a corresponding circuit with the step of modulating a voltage at one of the two potential taps and/or at one of the phase connections based on a common mode voltage, wherein the common mode voltage is determined using a voltage measured by a measuring unit.
  • the method can also have the step of measuring a voltage between one of the two potential taps and a protective conductor/PE (with the special feature that this protective conductor in the TT system is connected to the system earthing instead of to the earthing of the network/transformer).
  • the method can be computer-implemented. In this respect, a computer program is created for carrying out the method.
  • a voltage measurement can also be carried out in order to determine the common mode voltage.
  • at least one voltage on the DC voltage side is determined in relation to PE.
  • An example of this would be the voltage from a center point of an intermediate circuit that is arranged between the potential taps in relation to PE. This can be determined, for example, by measuring the center point of the intermediate circuit in relation to one of the potential taps. An additional voltage measurement between a phase on the AC side and the center point can also be taken into account.
  • FIG. 1 FH221002PDE-2022297546
  • FIG. 1 A circuit with a converter circuit that has a DC voltage connection with two potential taps and one or more phase connections; and a controller, wherein the controller is designed to control switchable elements of the converter circuit such that a voltage at one of the two potential taps and/or at one of the phase connections is modulated based on a common mode voltage; measuring unit designed to determine a voltage on the DC voltage side with respect to ground; wherein the common mode voltage is determined using the voltage measured by the measuring unit.
  • the voltage between a center point of an intermediate circuit arranged between the two potential taps and one of the potential taps can be measured.
  • the voltage between a center point of an intermediate circuit arranged between the two potential taps and one of the potential taps can be measured, wherein an additional voltage on the AC voltage side is measured between one of the phases and the center point of the intermediate circuit or wherein the additional voltage is measured between one of the phases and ground.
  • a rectifier such as a non-isolated rectifier or specifically to a battery charger with a circuit according to one of the preceding claims with a measuring device.
  • this rectifier can be operated in a TT system.
  • Another embodiment provides a method for operating this circuit.
  • the method comprises the step of modulating a voltage at one of the two potential taps and/or at one of the phase connections based on a common mode voltage, wherein the common mode voltage is determined using the voltage measured by the measuring unit on the DC side with respect to earth.
  • this method can also be computer-implemented.
  • Fig.1 a simplified common mode equivalent circuit including the structure of an EMC filter (according to [1]);
  • Fig.2 a simplified block diagram of a V2 PFC with additional activated intermediate circuit balancing (BC) (according to [3]);
  • Fig.3 a schematic table to illustrate different calculation methods of the common mode voltage for use in embodiments; list of measured variables, dynamics and disadvantages Fig.4a/b/c different network types;
  • Fig.5a/b shows schematic representations for the single-phase and three-phase case, the common mode voltage compensation according to embodiments;
  • Fig.5c a schematic block diagram of an electrical circuit with common mode voltage reduction for single-phase operation according to an extended embodiment;
  • Fig.6 a schematic block diagram of a circuit with common mode voltage reduction for three-phase operation according to an extended embodiment;
  • Fig.7a/b/c schematic block diagrams of an electrical circuit with common mode voltage reduction by means of voltage measurement according to another embodiment;
  • the TN-CS system on the system side comprises the three phases L 1 , L 2 and L 3 as well as the neutral conductor and PE conductor.
  • PE and N are combined to form a PEN.
  • the star point of the three phases and PEN is connected to the operational earth electrode 153.
  • An earth electrode 154 is also provided on the system side.
  • the TN-S system shown in Fig. 4b is extended in that the PE conductor is led directly to the power grid 152'.
  • the star point consisting of L 1 , L 2 , L 3 , N and PE is connected to the operational earth 153. No system earth is provided on the consumer 150 side.
  • a potential difference can arise between the earth (depending on whether it is the system earth or operational earth) and one of the potential taps of a converter circuit. If one assumes that a capacitance/parasitic capacitance of any kind arises between the potential tap on the one side and earth on the other side, a current flow can result due to the potential difference or, in particular, fluctuating potential difference. These currents are called leakage currents.
  • the capacitor is referred to as C CM in the examples below and can be present on both the negative intermediate circuit potential side DC- and the positive intermediate circuit potential side DC+. An example of this would be a non-isolated charger for electric cars, where the capacitance C CM is represented by Y capacitors in the battery or in the vehicle.
  • the connection between the operational and system earthing is made via the ground. Furthermore, potential differences can arise between the operational earthing and system earthing due to the spreading resistance between the earthing electrodes. In all network types, displacement voltage can also occur as a result of earth faults or unbalanced loads in the network. This leads to a fluctuating FH221002PDE-2022297546 Potential difference between the DC-side potential tap and PE and thus to leakage currents. Leakage currents or unbalanced loads of other devices in the same network section can increase the potential fluctuation. A concept is explained below as to how the leakage current can be optimally reduced. Fig.
  • FIG. 5c shows an electrical circuit 10 comprising a converter circuit 12 with, for example, two half-bridges 12a and 12b.
  • the two half-bridges 12a and 12b are provided between the potential taps 20a and 20b.
  • Each half-bridge comprises, for example, two switchable elements, which are provided with the reference number 14.
  • the two switchable elements 14 are connected in series, with a respective center node 16 being connected to the phases 18a and 18b by a phase connection 18.
  • a capacitance C CM with the voltage ⁇ ⁇ ⁇ ⁇ ⁇ is also illustrated as an example to illustrate the common mode fluctuation on the common mode side 20a + 20b as well as an example controller 25 for controlling the switchable elements.
  • the power converter circuit 12 can, for example, be a rectifier which, based on a voltage applied to the voltage connection 18, here an AC voltage connection, provides a DC voltage ⁇ ⁇ ⁇ between the DC voltage connections 20a and 20b or generally the potential taps 20a and 20b.
  • the switchable elements 14 are controlled accordingly, namely by the controller 25.
  • the controlled variable is ⁇ ⁇ ⁇ , i.e. the controller 25 controls the specific sequence and control times of the switchable elements 14 such that a corresponding value ⁇ ⁇ ⁇ is achieved. According to the embodiments, this value ⁇ ⁇ ⁇ can of course also be measured.
  • the intermediate circuit or, in general, the voltage potential of 20a and 20b can be shifted relative to the earth potential by appropriate modulation of the elements 14 (change in voltage ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ). This voltage shift is dropped across C CM . As a result of the fluctuation, a corresponding current flows through C CM (leakage current).
  • the voltage ⁇ ⁇ ⁇ ⁇ ⁇ or ⁇ ⁇ ⁇ ⁇ can be kept constant, or as constant as possible, in order to avoid leakage currents via the capacitor C CM .
  • a control process is used according to which the voltage ⁇ ⁇ 4 of the switchable elements of the converter circuit (voltage ⁇ ⁇ 4 is to be described as a voltage averaged over a switching period, applied to the semiconductors or resulting from the modulation of the PWM (cf. Fig. 5a)) is modulated with the common mode voltage ⁇ ⁇ ⁇ .
  • ⁇ ⁇ ⁇ is shown as the voltage between the potential tap 20a and the potential tap 20b.
  • the fluctuation in the voltage ⁇ ⁇ ⁇ ⁇ can be greatly reduced with the common mode modulation of the converter circuit 12, here an H4 bridge in single-phase operation or with other converter circuits, such as a B6 bridge in three-phase operation, and the leakage currents through C CM can be reduced by compensating for the fluctuation resulting from the fluctuation in the intermediate circuit voltage ⁇ ⁇ ⁇ .
  • ⁇ ⁇ ⁇ ⁇ is advantageously kept constant. It should be noted at this point that differences in the formulas with e.g.
  • ⁇ ⁇ ⁇ ⁇ typically represent a difference to the mean value of the respective voltage. Since this value is usually a controlled variable (e.g. the (measurable/measured) intermediate circuit voltage ⁇ ⁇ ⁇ ), the setpoint from the control can also be used instead of averaging from the measured value .
  • FH221002PDE-2022297546 Embodiments ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ the control value, such as the setpoint on the DC side or the mean value on the DC side.
  • Fig. 5a shows an equivalent circuit diagram for the single-phase case.
  • the single-phase voltage connection is provided with the reference number 18.
  • Fig.5b the same situation is shown starting from a three-phase voltage source 18'.
  • asymmetrical currents i or mains voltages 18' in the individual phases L1, L2 and L3 can lead to asymmetrical voltage drops V ZL on e.g. the filter components, so that on the DC side ⁇ ⁇ ⁇ a common mode voltage ⁇ ⁇ ⁇ ⁇ drops compared to PE.
  • a displacement voltage or leakage currents can lead to a voltage drop V ZPE at the impedance between the local earth and the operational earth, which is added to the common mode voltage ⁇ ⁇ ⁇ ⁇ .
  • Fig. 6 shows a converter circuit 12' with three half-bridges 12a', 12b' and 12c', each of which is arranged between two potential taps 20a and 20b. Each of these three half-bridges 12a', 12b' and 12c' is connected to one of the phases via a respective center node 16. The phases are provided with the reference symbols 18a', 18b' and 18c'.
  • the converter circuit can also have an additional intermediate circuit 22, here a symmetrical intermediate circuit with two intermediate circuit capacitances 22C1 and 22C2.
  • phase connections Via a middle node between the two capacities 22C1 and 22C2, which is provided with the reference symbol 22m, FH221002PDE-2022297546 according to embodiments, one or all of the phases 18a', 18b' and 18c' are capacitively coupled.
  • a capacitance arrangement 24 with three capacitances is provided between the phases 18a', 18b' and 18c'.
  • Each of the phase connections has one or more inductances and resistors L D1 , R D1 , L D2 , R D2 , L G and R G drawn in here.
  • R D1 , R D2 are not shown in the figures, with R D1 , R D2 being the resistors or the ohmic component of the respective inductances L D1 and L D2 .
  • L G and R G it should be noted that the inductance L G or the resistor R G is not shown in the attached drawings and is only mentioned for the sake of completeness. This is the system impedance (system inductance and system resistance) on the side of the voltage source V G .
  • the elements L D1 , L D2 , R D1 and R D2 are arranged on the side of the converter circuit, i.e.
  • the inductance L G and the resistor R G are each on the mains side.
  • the inductance L D1 and the resistor R D1 represent the inductances connected in series and their ohmic resistances between the capacitor arrangement 24 and the respective center point 16, while the inductance L D2 and the resistor R 2 are arranged between the capacitor arrangement 24 and the mains connection.
  • the elements L D1 , R D1 , L D2 , R D2 , L G and R G are arranged in series, i.e. connected in series, for each phase connection 18a', 18b' and 18c'.
  • the inductances and resistors do not necessarily have to be explicitly provided electrical components, but can also be formed by the cable itself. Now that the structure has been explained in detail, the functionality will be discussed. By connecting the capacitors C X to the intermediate circuit center point 22m, the high-frequency components of the common mode interference voltage ⁇ ⁇ ⁇ are already greatly reduced via L D1 and C X , but this is not absolutely necessary for the control method to function.
  • the inductances L D1 , L D2 , L G and the resistors R D1 , R D2 , R G were for the FH221002PDE-2022297546 Representation assumed to be the same in each case.
  • the method also works with different values for these elements.
  • the output voltage of the B6 bridge 12' can be modulated with a common mode voltage ⁇ ⁇ ⁇ , ⁇ 6 .
  • the intermediate circuit or the potential taps 20a' and 20b' can thus be shifted with respect to the earth potential PE (change in voltage ⁇ ⁇ ⁇ ⁇ ⁇ ).
  • the aim of the control method is to keep the voltage ⁇ ⁇ ⁇ ⁇ constant in order to avoid leakage currents via the capacitor C CM .
  • the common mode voltages ⁇ ⁇ ⁇ 1 ⁇ ⁇ and ⁇ ⁇ ⁇ 2 ⁇ ⁇ across the chokes and resistors of the rectifier and ⁇ ⁇ ⁇ ⁇ across the impedance of the mains connection can be determined using formulas (4), (5) and (6).
  • an LCL filter structure was assumed (L D1 -C X -L D2 ).
  • Other components in the current path of the rectifier must be taken into account accordingly.
  • phase L1 is connected to the first half-bridge and neutral N is connected to the second half-bridge.
  • the first half-bridge L1 is controlled with the mains voltage v L1 (in practice with the output voltage setpoint of the current regulator) and the common mode voltage ⁇ ⁇ ⁇ , ⁇ 4 (8).
  • the second half-bridge N is controlled with the common mode voltage ⁇ ⁇ ⁇ , ⁇ 4 (9).
  • ⁇ ⁇ 4, ⁇ 1 ⁇ ⁇ 1 + ⁇ ⁇ ⁇ , ⁇ 4 (8)
  • ⁇ ⁇ 4, ⁇ ⁇ ⁇ ⁇ , ⁇ 4 (9)
  • the common mode voltages are calculated according to formulas (10) to (12).
  • the common mode modulation voltage for the H4 bridge is summarized in formula (13).
  • ⁇ ⁇ , ⁇ 4 ⁇ 2 + ⁇ ⁇ ⁇ 1 ⁇ ⁇ + ⁇ ⁇ ⁇ 2 ⁇ ⁇ + ⁇ ⁇ ⁇ ⁇ ⁇
  • the capacitance C CM can also be connected to the positive intermediate circuit connection.
  • An additional DCDC converter can also be connected to the intermediate circuit (e.g. for a battery).
  • the capacitance FH221002PDE-2022297546 C CM of the battery is switched from DC- or from DC+ to earth potential.
  • the half-bridges are controlled in such a way that the voltage is modulated based on the common mode voltage.
  • the common mode voltage is calculated based on a formula with the term ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ 2.
  • This calculation method advantageously makes it possible to compensate for the common mode voltage resulting from the fluctuation in the intermediate circuit voltage. According to other embodiments, this compensation for the fluctuation in the common mode voltage is also possible using other calculation methods.
  • An overview of four different calculation methods is shown in Fig.3.
  • the third calculation method is based, for example, on a voltage measurement of ⁇ ⁇ ⁇ and ⁇ ⁇ 2 .
  • a measurement of the phase currents or the currents in the respective relevant inductances is used. It should be noted here that the permissible working currents are determined depending on the device class. FH221002PDE-2022297546
  • the control method described here shows in simulations a strong reduction in leakage currents compared to conventional control.
  • Fig.7a-c another embodiment is now explained that is particularly suitable for the TT system.
  • Fig.7a shows another electrical circuit, here an electrical charger that is connected to a TN-CS system.
  • Fig.7b the same charger is connected to a TN-S system.
  • a separate conductor is used for PE and not the common PEN conductor.
  • Fig.7c the connection of the same charger to a TT system is used. Both on the system side and on the network side there is a separate earthing electrode, which, in contrast to the TN-S and TN-CS systems, does not have a common potential through a separate connection. In this respect, displacement voltages or potential differences between the operating and system earthing electrodes can occur here.
  • the charger eg from Fig. 7a, 7b or 7c, comprises an EMC filter 1000 on the input side, which connects the respective power system (cf. voltage source V G ) with the actual rectifier 1100.
  • the rectifier here a PVC rectifier with LCL sine filter (differential mode filter) connects the AC voltage side of the network with the DC voltage side 1200.1200 here refers to the DC voltage intermediate circuit, which is arranged between the two potential taps 20a and 20b.
  • the intermediate circuit 12 here comprises two series-connected capacitors with a center point M, over which the filters arranged on the input side (EMC filter and LCL sine filter) are arranged.
  • An optional (non-isolated) DC voltage converter 1300 and an optional EMC filter 1400 can then follow on the DC voltage side.
  • the reference number 1500 indicates a DC source and/or DC sink, such as a battery.
  • Y capacitors can optionally be used as common mode filter capacitors in the EMC filter 1400 in the charger (C Y1 and C Y2 ). These capacitances are connected to the ground potential on the DC voltage side. Y capacitors in the HV on-board network of a vehicle can have a higher capacitance depending on the design and are optional.
  • different voltages can be determined by measurement, preferably voltages on the DC side, in order to regulate the common mode voltage.
  • ⁇ ⁇ 2 i.e. between the center point M of the intermediate circuit 12 and one of the potential taps 20a and 20b, is measured on the DC voltage side.
  • This is an alternative for calculating the voltage drop across the inductance L D1 , where no derivative of the current with respect to time is necessary.
  • This approach is less dynamic because the measured value must have a filter or a regulator (TF in Fig.8 (b)). Displacement voltages and potential differences between the operational and system earth electrodes and other filter components e.g. L D2 cannot be compensated with this method.
  • measurements are preferably only taken on the DC voltage side, so that compensation is carried out by directly measuring the voltage to PE.
  • a direct voltage measurement of ⁇ ⁇ ⁇ ⁇ ⁇ can also be carried out.
  • a measurement from DC+ to PE or from battery+ to PE can also be carried out. Based on this, it is also possible to regulate the common mode voltage or common mode voltage fluctuation.
  • all elements are compensated for with the measurement on the DC voltage side, in particular the filter components, the intermediate circuit voltage, the network impedance, the displacement voltage, and potential differences between the operational and system earth electrodes.
  • the voltage to PE e.g. from DC+, M, DC- to PE.
  • a combination would also be conceivable, or a combination with the measurement of the intermediate circuit voltage ⁇ ⁇ 1 and ⁇ ⁇ 2 .
  • the common mode voltage is then calculated or the fluctuation in the common mode voltage is calculated so that it can then be compensated for by adjusting the control of the converter circuit.
  • the adjustment is made in such a way that the common mode voltage or common mode voltage fluctuation calculated on the basis of measured values can be compensated for by, for example, adjusting the corresponding target value on the DC side accordingly (reducing or increasing by the fluctuation).
  • the calculation method is explained below with reference to Fig.8a and 8b using an example block diagram. The pulse width modulation to be used to regulate the common mode voltage is discussed explicitly here.
  • Fig.8a shows a control system with the three elements 16, 17 and 18.
  • the half-bridges in single-phase operation set the voltage 0 V or duty cycle 0.5 for the neutral conductor and the half-bridges for the phase set the full voltage.
  • Block 1800 illustrates the application of the common mode voltage for the control process.
  • the voltage ⁇ ⁇ ⁇ is added to all voltages (neutral conductor and phases).
  • the value compensated for by the common mode voltage ⁇ ⁇ ⁇ is then transferred to the pulse width modulation, taking into account the intermediate circuit voltage ⁇ ⁇ ⁇ .
  • Fig. 8b is also based on blocks 1600, 1700, but is expanded to include block 1900, in which the common mode voltage is regulated in accordance with the above embodiments.
  • ⁇ ⁇ ⁇ ⁇ ⁇ ⁇ serves as the input signal for the transfer function TF, which outputs the common mode voltage ⁇ ⁇ ⁇ .
  • the transfer function TF can, for example, be implemented in the form of a filter or a controller.
  • Figure 8a for example, enables the combination of methods 1 and 4, for example.
  • the following mathematical relationship shows the calculation of the modulation voltage in general. ⁇ ⁇ ⁇ ⁇ ⁇ .
  • ⁇ ⁇ 6 ⁇ ⁇ ⁇ + ⁇ ⁇ ⁇ FH221002PDE-2022297546
  • this path can be used to take into account both method 1 and method 4 as well as the combination of methods 1 and 4 as a simple sum of the formulas associated with methods 1 and 4.
  • the sum of the common mode voltage according to methods 1 and 4 is then added to the voltage ⁇ ⁇ ⁇ via the summation point of block 16. This is possible in a similar way in Fig. 8b, which is also made clear here by the arrow 1800, which leads to the summation point of block 1600.
  • Fig. 8b which is also made clear here by the arrow 1800, which leads to the summation point of block 1600.
  • the transfer function TF in block 1900 is used for this.
  • the common mode voltage according to methods 1 and/or 4 can be taken into account by adding the common mode voltage to ⁇ ⁇ ⁇ , while alternatively or additively the common mode voltage according to methods 2 and 3 can also be added to the signal ⁇ ⁇ ⁇ according to a transfer function TF.
  • the objectives of the previous embodiments and in particular the efficiency will be discussed below.
  • the objective of these embodiments is again to provide the voltage ⁇ ⁇ ⁇ ⁇ with as little fluctuation as possible. This means that a reduction in the operating current by ⁇ ⁇ ⁇ is desired.
  • Fig.9a illustrates the behavior when compensating for the influence of the fluctuation in the intermediate circuit voltage ⁇ ⁇ ⁇ .
  • the voltage of the upper intermediate circuit half ⁇ ⁇ 1 was kept constant and a fluctuation was assumed for the lower intermediate circuit half ⁇ ⁇ 2 .
  • the fluctuation in the voltage ⁇ ⁇ 2 leads to a fluctuation in the voltage ⁇ ⁇ ⁇ ⁇ across capacitance ⁇ ⁇ ⁇ and thus to the leakage current ⁇ ⁇ ⁇ ⁇ .
  • Fig.9c illustrates compensation via voltage measurement ⁇ ⁇ ⁇ in the neutral conductor path and ⁇ ⁇ 2 according to method 3 using a controller.
  • the voltage drop across L D1 in the neutral conductor ⁇ ⁇ ⁇ (see Fig. 5 a) and a fluctuation in the intermediate circuit voltage are compensated. Compensation according to method 3 can greatly reduce the leakage current.
  • the level of the remaining leakage current depends on the filtering or the controller used (TF Fig.8 b).
  • Fig. 9d shows compensation for the voltage drop ⁇ ⁇ ⁇ across the filter components (e.g. L D1 ). Compensation according to method 4 can greatly reduce the leakage current.
  • the level of the remaining leakage current depends on the filtering or the controller used (TF Fig.8 b). All elements in the path can be taken into account by calculating the sum of the voltage drops. Factors that have an influence include the inductances L D1 and L D2 , their ohmic components, the voltage drop of the semiconductor switches, the network impedance (this value is usually unknown) and connecting cables.
  • LD1, LD2 and the network impedance in the neutral conductor are taken into account by the last three terms in formula 13.
  • the elements of the three phases are taken into account by the last three terms in formula 7.
  • a fuel cell or electrolysis a fuel cell or electrolysis.
  • the focus was on certain systems, such as the TN-CS system here.
  • the influences on the common mode voltage are different.
  • displacement voltages and potential differences occur between the operating and system earthing, e.g. in the TT system (see Fig. 7c).
  • these displacement voltage potential differences are regulated as best as possible using the approaches described above and in particular using the approach from Fig. 3, e.g. method 2.
  • aspects described in the context of a device it is to be understood that these aspects also represent a description of the corresponding method, so that a block or component of a device can also be understood as a corresponding method step or as a feature of a method step.
  • aspects described in the context of or as a method step also represent a description of a corresponding block or detail or feature of a corresponding device.
  • Some or all of the method steps can be implemented by a hardware apparatus (or using a hardware apparatus), such as a microprocessor, a programmable computer, or an electronic circuit. In some embodiments, some or more of the key method steps can be performed by such an apparatus. Depending on particular implementation requirements, embodiments of the invention can be implemented in hardware or in software.
  • the implementation may be carried out using a digital storage medium, such as a floppy disk, a DVD, a Blu-ray Disc, a CD, a ROM, a PROM, an EPROM, an EEPROM or a FLASH memory, a hard disk or other magnetic or optical storage, on which electronically readable control signals are stored that can be communicated with a programmable computer system of such a type FH221002PDE-2022297546 can interact or interact so that the respective method is carried out. Therefore, the digital storage medium can be computer-readable.
  • Some embodiments according to the invention thus comprise a data carrier which has electronically readable control signals which are able to interact with a programmable computer system such that one of the methods described herein is carried out.
  • embodiments of the present invention can be implemented as a computer program product with a program code, wherein the program code is effective to carry out one of the methods when the computer program product runs on a computer.
  • the program code can also be stored on a machine-readable medium, for example.
  • Other embodiments comprise the computer program for carrying out one of the methods described herein, wherein the computer program is stored on a machine-readable medium.
  • an embodiment of the method according to the invention is thus a computer program which has a program code for carrying out one of the methods described herein when the computer program runs on a computer.
  • a further embodiment of the method according to the invention is thus a data carrier (or a digital storage medium or a computer-readable medium) on which the computer program for carrying out one of the methods described herein is recorded.
  • a further embodiment of the method according to the invention is thus a data stream or a sequence of signals which represents the computer program for carrying out one of the methods described herein.
  • the data stream or the sequence of signals can be configured, for example, to be transferred via a data communication connection, for example via the Internet.
  • FH221002PDE-2022297546 Another embodiment comprises a processing device, for example a computer or a programmable logic device, which is configured or adapted to carry out one of the methods described herein.
  • Another embodiment comprises a computer on which the computer program for carrying out one of the methods described herein is installed.
  • Another embodiment according to the invention comprises a device or a system which is designed to transmit a computer program for carrying out at least one of the methods described herein to a recipient.
  • the transmission can be electronic or optical, for example.
  • the recipient can be, for example, a computer, a mobile device, a storage device or a similar device.
  • the device or system can, for example, comprise a file server for transmitting the computer program to the recipient.
  • a programmable logic device for example, a field-programmable gate array, an FPGA
  • FPGA field-programmable gate array
  • a field-programmable gate array can cooperate with a microprocessor to carry out one of the methods described herein.
  • the methods in some embodiments are performed by any hardware device.
  • This may be general-purpose hardware such as a computer processor (CPU) or hardware specific to the method such as an ASIC.
  • CPU computer processor
  • ASIC application specific integrated circuit

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

L'invention concerne un circuit (10) présentant les caractéristiques suivantes : un circuit convertisseur (12), qui comporte une borne de tension continue présentant deux prises de potentiel (20a, 20b) et une ou plusieurs bornes de phase (18a, 18b, 18a', 18b', 18c') ; et une commande (25), cette commande (25) étant conçue pour commander des éléments (14) commutables du circuit convertisseur (12) de sorte qu'une tension sur l'une des deux prises de potentiel (20a, 20b) et/ou sur la ou les bornes de phase (18a, 18b, 18a', 18b', 18c') soit modulée sur la base d'une tension en mode commun ; cette tension en mode commun étant calculée.
PCT/EP2023/079537 2022-10-28 2023-10-24 Circuit et procédé pour faire fonctionner un circuit WO2024088990A1 (fr)

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FR3063191A1 (fr) * 2017-02-23 2018-08-24 Renault S.A.S Dispositif et procede de charge d'une batterie reduisant les courants de mode commun dudit dispositif
DE102017216468A1 (de) 2017-09-18 2019-03-21 Conti Temic Microelectronic Gmbh Aufladen eines elektrischen Energiespeichers eines Kraftfahrzeugs
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