WO2024031223A1 - 三相csr整流电路节能和并联叠加的接线方法 - Google Patents

三相csr整流电路节能和并联叠加的接线方法 Download PDF

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Publication number
WO2024031223A1
WO2024031223A1 PCT/CN2022/110803 CN2022110803W WO2024031223A1 WO 2024031223 A1 WO2024031223 A1 WO 2024031223A1 CN 2022110803 W CN2022110803 W CN 2022110803W WO 2024031223 A1 WO2024031223 A1 WO 2024031223A1
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csr
bridge
phase
windings
full
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PCT/CN2022/110803
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English (en)
French (fr)
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薛洛良
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薛洛良
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Priority to PCT/CN2022/110803 priority Critical patent/WO2024031223A1/zh
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
    • H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
    • H02M5/10—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using transformers
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/145—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
    • H02M7/155—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
    • H02M7/162—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only in a bridge configuration

Definitions

  • the present invention relates to the technical field of CSR rectifier circuits, and in particular to a three-phase CSR rectifier circuit energy-saving and parallel superposition wiring method.
  • the CSR rectifier circuit is a high-frequency PWM (pulse width adjustment) current source step-down rectifier power supply circuit. High-power rectifier circuits all use three-phase input power.
  • Figure 1 shows the three-phase six-switch CSR rectifier circuit used in the existing technology. Topology.
  • the existing CSR rectifier circuit has the characteristics of high PFC function power factor and high output power control accuracy; the current CSR rectifier circuit uses high-power switching tubes to achieve high-frequency operation, and the harmonics generated by the high loop operating frequency are small.
  • the on-off control of the switching tube in the existing CSR rectifier circuit is completed by a control loop.
  • the control loop is completed by adjusting the conduction pulse width, that is, PWM, according to the needs of the load size.
  • the pulse width is determined by modulating the triangular wave carrier with a sine wave. Because the power supply is a sine wave, in order to improve the power factor, a sine wave is used as the modulation wave to make the current and voltage change synchronously. It is also called SPWM high-frequency rectified power supply. S represents sine wave, which is represented by PWM below.
  • CSR rectifier circuits need to work under high voltage and high current conditions.
  • the current manufacturing technology of transistors does not allow high voltage and high current switching tubes to operate so fast.
  • the harmonics generated by the circuit are small.
  • the operating frequency of the circuit must be greater than 20 kilohertz, which must be completed by using multiple sets of CSR rectifier circuits in parallel and superimposed.
  • the present invention provides an energy-saving and parallel superposition wiring method for a three-phase CSR rectifier circuit that reduces switching tubes, reduces power consumption, has high withstand voltage, large power factor, small harmonics, and increased power.
  • a three-phase CSR rectifier circuit energy-saving and parallel superposition wiring method The low-voltage side of the power distribution transformer outputs two windings.
  • the two windings respectively supply power to two sets of CSR half-bridge rectifier circuits.
  • the voltages of the two windings are equal, corresponding to The phases are the same.
  • Each of the windings has a set of CSR non-full-bridge circuits.
  • the two sets of CSR non-full-bridge circuits work at their own working hours.
  • the corresponding angle interval of the working hours is 60°, forming an alternating working mode and complementary time, completing the full Bridge CSR high frequency rectification function.
  • the two groups of CSR non-full-bridge circuits can be superimposed in parallel to form multiple groups of CSR non-full-bridge circuits.
  • the present invention reduces the number of working switching tubes in the CSR rectifier circuit to reduce loop losses;
  • the specific method is to provide two windings on the low-voltage side of the power distribution transformer, the voltages of the two windings are equal, and they are not electrically connected , and each has a CSR non-full bridge loop.
  • the two sets of circuits work at their own working hours, and the corresponding angle of the working time is 60°, forming an alternating mode and the working time is complementary.
  • the current sine wave does not deform, completing a perfect "full bridge" CSR high frequency Rectification function; in addition, the low-voltage side of the distribution transformer of the present invention has two windings, each with a set of CSR half-bridge circuits, and the upper and lower half-bridges each have an energy storage inductor.
  • the loop operation is symmetrical, and parallel superposition can be completed well to increase the output power.
  • Figure 1 is a topology diagram of a three-phase CSR rectifier circuit in the prior art according to the energy-saving and parallel superposition wiring method of the three-phase CSR rectifier circuit according to the embodiment of the present invention
  • Figure 2 is a waveform diagram of the three-phase CSR rectifier circuit using the energy-saving and parallel superposition wiring method of the three-phase CSR rectifier circuit according to the embodiment of the present invention
  • Figure 3 is a three-phase CSR rectifier circuit diagram of the energy-saving and parallel superposition wiring method of the three-phase CSR rectifier circuit according to the embodiment of the present invention.
  • the present invention proposes an energy-saving and parallel superposition wiring method for a three-phase CSR rectifier circuit.
  • FIG. 1 is the topology diagram of the CSR rectifier circuit, in which V1, V2, and V3 are A and B. , C three-phase upper-side arm switch tube, D1, D2, D3, are A, B, C three-phase upper-side arm diodes; V4, V5, V6 are A, B, C three-phase lower side arm switch tube, D4, D5 and D6 are the three-phase lower arm diodes of A, B and C, L4 is the energy storage inductor, and D7 is the freewheeling diode.
  • the power supply for the existing three-phase CSR rectifier circuit is provided by one winding of the distribution transformer.
  • only one of the three switching tubes of the upper arm and the three lower arm of the lower arm is turned on to form a closed circuit of inter-phase rectification.
  • the switch tube V1 of the upper arm is turned on and the lower arm is turned on, one of the switch tubes V5 or V6 is turned on to form a current path.
  • the actions of other switching tubes can be deduced in the same way.
  • FIG 2 is a three-phase sine wave waveform diagram of a three-phase CSR rectifier circuit.
  • Ua, Ub, and Uc represent the three-phase voltage variation curves of A, B, and C with time (or angle).
  • Figure 2 Select any point D on the time axis. At this time, the voltage values corresponding to the three phases A, B, and C are points F, G, and E respectively.
  • the working voltage at this point should be Uab (line segment FG represents the size of Uab) or Ubc (line segment EG represents the size of Ubc).
  • the corresponding switching tubes V1 and V5 in Figure 1 are turned on, and the current i flows from phase A as shown by the dotted line in Figure 1, passes through V1, D1, L4, load RL, V5, D5 and then flows back to B Mutually.
  • the main loss-producing devices in the CSR circuit are V1, D1, V5, D5, two switching tubes and two diodes.
  • each conduction process will produce losses of two switching tubes and two diodes.
  • the loss of the switching tube is much larger than that of the diode. Reducing the number of switch tubes is the main task of the present invention.
  • the present invention reduces the number of working switching tubes in the existing CSR rectifier circuit to reduce loop losses.
  • the specific method is to install two windings on the low-voltage side of the power distribution transformer.
  • the two windings have the same voltage, are not electrically connected, and each has a CSR non-full-bridge circuit.
  • the two sets of circuits work at their own working hours, and the corresponding angle of the working time is 60°, forming an alternating mode and the working time is complementary. From the input of the primary side of the transformer, the current sine wave does not deform, completing a perfect "full bridge" CSR high frequency Rectification function.
  • the primary side of the distribution transformer 1 is connected to the high voltage of the power grid, and the secondary side outputs two windings, namely the first winding and the second winding.
  • the voltages of these two windings are equal, and the corresponding phases of each phase are the same.
  • the two windings each have their own CSR half-bridge circuit.
  • the combination of the first CSR half-bridge circuit 2 with the first winding, the distribution transformer 1 and the first CSR half-bridge circuit 2 is called the upper half; the second CSR half-bridge circuit with the second winding 3.
  • the combination of distribution transformer 1 and second CSR half-bridge circuit 3 is called the lower half.
  • the CSR half-bridge circuit of the present invention is different from the traditional CSR full-bridge circuit.
  • the existing CSR full-bridge circuit is shown in Figure 1.
  • the upper and lower bridge arms each have three symmetrical switching tubes and diodes.
  • the CSR half-bridge circuit of the present invention is shown in Figure 3.
  • the dotted box 2 in Figure 3 shows the first CSR half-bridge circuit 2 in the upper half.
  • the first CSR half-bridge circuit 2 eliminates the three switching tubes of the lower arm of the existing circuit.
  • the first CSR half-bridge circuit 2 in the upper half is specifically composed of the upper half bridge consisting of switching tubes V11, V12, V13, diode D11, It is composed of D12 and D13, and the lower half bridge is composed of diodes D14, D15 and D16.
  • the second CSR half-bridge circuit 3 in the lower half eliminates the three switching tubes of the upper bridge arm of the existing circuit.
  • the specific structure of the second CSR half-bridge circuit 3 is that the upper half bridge is composed of diodes D21 and D22. , D23, the lower half bridge is composed of switch tubes V24, V25, V26 and diodes D24, D25, D26.
  • the angles corresponding to the working periods in the upper and lower half zones are strictly defined.
  • the working intervals in the upper half zone are between 0° ⁇ 60°, 120° ⁇ 180°, 240° ⁇ 300o...; the working intervals in the lower half zone are between 60° ⁇ 120°, 180° ⁇ 240°, 300° ⁇ 360o....
  • the working process is that V11 is turned on, and the current flows from phase A through D11, V11, L14, load RL and D15 and returns to phase B.
  • Figure 3 the current i flows in the CSR half-bridge circuit 2 in the upper half area.
  • the corresponding voltage values of the three phases A, B, and C at point D are points F, G, and E respectively.
  • the voltage of phase B is the lowest in the range of 0° to 60°.
  • the lower bridge arm has three three-phase diodes D14, D15 and D16, but the current can only flow back from phase B with the lowest potential, so the A-phase current can only flow back from phase B D15, not from phase C. Therefore, the main loss-producing devices in the CSR circuit during Uab operation are D11, V11, D15, a switch tube and two diodes. This process reduces the loss of one switching tube compared with traditional CSR work.
  • the devices that cause losses in the CSR circuit during Ubc operation include D13, V13, D15, a switch tube and two diodes. This process also reduces the loss of one switching tube compared to traditional CSR work.
  • the voltage runs in the range of 60° to 120°.
  • the second winding of the distribution transformer 1 and the second CSR half-bridge circuit 3 in the lower half are working.
  • the switching tubes in the CSR half-bridge circuit 2 in the upper half of the first winding of the distribution transformer 1 are all cut off, that is, V11, V12, and V13 (including V121, V122, and V123) are all cut off, and the upper half is not working during this period.
  • the points corresponding to the three-phase voltage values of A, B, and C are K, J, and I respectively.
  • phase A has the highest potential in the range of 60° to 120°, so the current can only flow out from phase A diode D21, but not from phase B and C diodes D22. , D23 flows out.
  • CSR circuit characteristics At this moment, the working voltage can only be Uab or Uac. Taking the Uab voltage operation as an example, V25 is turned on, and the current flows back from phase B through V25.
  • the devices that cause loss in the CSR half-bridge circuit include D21, V25, D25, a switch tube and two diodes, which reduces the loss of one switch tube compared with the traditional CSR rectifier circuit. The same goes for analyzing the operating loss of voltage Uac.
  • the characteristics of the CSR circuit at this moment can only operate with voltages Uac and Ubc, and the A and B phase currents can only flow back from the C phase.
  • the devices that cause losses in the CSR half-bridge circuit during operation are also a switch tube and two diodes.
  • the upper and lower half-bridge circuits switch every 60°, and the control method is arranged according to the above principles to successfully complete the CSR symmetric rectification work.
  • the CSR half-bridge rectification circuit of the present invention saves the loss of one switching tube.
  • the switching tube loss consists of two parts, one is the switching process loss, and the other is the saturated conduction voltage drop loss.
  • the saturated conduction voltage drop is about 3 volts. If the loop has a current of 50 A, the saturated conduction loss of the switch tube is At 150 watts, the switching process loss is more than three times the saturated conduction loss.
  • the diode voltage drop is less than 1 volt, and the diode loss is less than 50 watts when the loop current is 50 amps. Therefore, the CSR half-bridge rectifier circuit of the present invention saves the work of one switching tube, which is equivalent to reducing the circuit loss by more than 30%.
  • the operating frequency of high-voltage and high-power switching tubes cannot be too high.
  • multiple sets of CSR rectifier circuits are required to work in parallel and superimposed.
  • the existing CSR full-bridge rectifier circuit bridge-end output loop can only have one energy storage inductor, such as L4 in Figure 1, which makes the output circuit asymmetrical.
  • L4 energy storage inductor
  • the voltage can be superimposed in parallel in the first half of the sine wave, but not in the second half.
  • Parallel connection causes the CSR rectifier circuit to be unable to superimpose multiple groups in parallel.
  • each winding has a set of CSR half-bridge circuits to form the upper and lower half areas, and the half bridges in the upper and lower half areas.
  • Each has an energy storage inductor, so that the upper and lower half cycles of the voltage sine wave are balanced, and the combination of the two half areas completes the fully symmetrical CSR rectification work.
  • the two half-bridges in the upper half have inductors L14 and L124 respectively; the two half-bridges in the lower half have inductors L24 and L224 respectively.
  • the loop work is symmetrical and parallel superposition can be completed well.
  • the first CSR half-bridge circuit 2 in the upper half includes a first parallel superposition circuit 4, which is the second group of CSR half-bridge circuits in the upper half.
  • the specific components are switching tubes V121, V122, V123 and diodes D121, D122, D123.
  • the inductor L124 is the energy storage element of the first parallel superimposed circuit 4 half-bridge. The current of each switch tube in the first parallel superposition circuit 4 performs work through the load and then flows through the diodes D14, D15 and D16 in the first CSR half-bridge circuit 2 and returns to the power terminal.
  • the second CSR half-bridge circuit 3 includes a second parallel superposition loop 5, and the second parallel superposition loop 5 is the second group of CSR half-bridge loops in the lower half.
  • the specific components are switch tubes V224, V225, V226 and diodes D224, D225, D226.
  • Inductor L224 is the energy storage element of the second parallel superimposed circuit 5 half-bridge.
  • the current of each switch tube in the second parallel superposition circuit 5 performs work through the load and then flows through the diodes D21, D22 and D23 in the second CSR half-bridge circuit 3 and returns to the power terminal.
  • D14, D15, and D16 are the common diodes for the return current of each group in the upper half
  • D21, D22, and D23 are the common diodes for the output current of each group in the lower half.
  • the present invention reduces the number of working switching tubes in the CSR rectifier circuit to reduce loop losses.
  • the specific method is to install two windings on the low-voltage side of the power distribution transformer. The two windings have the same voltage and are not electrically connected. Each winding has a CSR non-full-bridge circuit, forming two upper and lower circuits.
  • the so-called CSR non-full-bridge circuit is to reduce three switching tubes on the upper bridge arm of one group and the lower bridge arm of the other group.
  • the two sets of circuits work at their own working hours, and the corresponding angle interval of the working time is 60°.
  • the work forms an alternating mode and the time is complementary, so that the current becomes a sine wave without deformation, and completes the full-bridge CSR high-frequency rectification function. See the dotted box 2 and the dotted box 3 in Figure 3 for the upper and lower two sets of CSR half-bridge loops respectively.
  • the two half-bridge circuits work separately, there is one less switch tube than the original CSR full-bridge circuit, thereby reducing circuit losses.
  • the upper and lower half-bridges each have an energy storage inductor.
  • the loop operation is symmetrical, and parallel superposition can be completed well to increase the output power.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

本发明公开了三相CSR整流电路节能和并联叠加的接线方法，包括供电的配电变压器低压侧输出两个绕组，两个绕组分别给两组CSR半桥整流电路供电，两个绕组电压相等，对应相相位相同。所述每个绕组分别各带一组CSR非全桥回路，两组CSR非全桥回路分别在各自的工作时间工作，工作时间对应角度区间为60°，形成交替工作模式且时间互补，完成全桥CSR高频整流功能。本发明提供一种减少开关管，降低功耗，耐压高，功率因数大，谐波小，增大了功率的一种三相CSR整流电路节能和并联叠加的接线方法。

Description

三相CSR整流电路节能和并联叠加的接线方法 技术领域
本发明涉及CSR整流电路技术领域，尤其涉及一种三相CSR整流电路节能和并联叠加的接线方法。
 背景技术
CSR整流电路是高频PWM（脉冲宽度调节）电流源降压型整流电源电路，大功率整流回路都采用三相输入电源，如图1所示为现有技术使用的三相六开关CSR整流电路拓扑图。
现有CSR整流电路具有PFC功能功率因数高，输出功率控制精度高特点；目前CSR整流电路是通过大功率开关管来实现高频工作，回路工作频率高产生的谐波小。
现有CSR整流电路中的开关管的通断控制是由控制回路完成的，控制回路根据负载大小的需要，通过调节导通脉冲宽度即PWM完成的。脉冲宽度的确定是三角波载波由正弦波调制得到的，因为供电电源是正弦波，为了提高功率因数所以用正弦波做调制波，使电流大小与电压大小同步变化，也叫SPWM高频整流电源，S代表正弦波，以下用PWM表示。
现在大功率整流器控制都采用专用DSP数字信号控制器来完成，原理与三角波调制相同。整流回路的损耗主要是开关管开关过程和饱和导通时的损耗，因此减少开关管工作数量是本发明的主要任务。
另外，在许多场合CSR整流电路需要工作在高电压大电流的情况，目前晶体管的制造技术高耐压、大电流的开关管动作速度没有那么快，要达到功率因数高，电路产生的谐波小，功率大的目的，电路工作频率必须大于20千赫兹，就必须用多组CSR整流电路并联叠加来完成。
 技术问题
有鉴于此，本发明提供一种减少开关管，降低功耗，耐压高，功率因数大，谐波小，增大了功率的一种三相CSR整流电路节能和并联叠加的接线方法。
 技术解决方案
为了实现本发明目的，可以采取以下技术方案：
一种三相CSR整流电路节能和并联叠加的接线方法，所述供电的配电变压器低压侧输出两个绕组，两个绕组分别给两组CSR半桥整流电路供电，两个绕组电压相等，对应相相位相同。
所述每个绕组分别各带一组CSR非全桥回路，两组CSR非全桥回路分别在各自的工作时间工作，工作时间对应角度区间为60°，形成交替工作模式且时间互补，完成全桥CSR高频整流功能。
所述两组CSR非全桥回路可并联叠加成多组CSR非全桥回路。
 有益效果
本发明的有益效果是：本发明是在CSR整流电路中减少工作开关管数量来减少回路损耗;具体方法是在供电的配电变压器低压侧出两个绕组，两个绕组电压相等，电气不连接，并且各带一个CSR非全桥回路。两组电路分别在各自的工作时间工作，工作时间对应角度为60°，形成交替模式且工作时间互补，从变压器一次侧输入来看电流正弦波不变形，完成完美的“全桥”CSR高频整流功能；另外，本发明配电变压器低压侧出了两个绕组，并且各带一组CSR半桥回路，上、下两组的半桥都分别带一个储能电感。回路工作具有了对称性，可以很好地完成并联叠加，达到增加输出功率的作用。
 附图说明
图1为本发明实施例三相CSR整流电路节能和并联叠加的接线方法的现有技术三相CSR整流电路拓扑图；
图2为本发明实施例三相CSR整流电路节能和并联叠加的接线方法的三相CSR整流电路的波形图；
图3为本发明实施例三相CSR整流电路节能和并联叠加的接线方法的三相CSR整流电路图。
 本发明的实施方式
下面结合附图及本发明的实施例对发明作进一步详细的说明。
本发明提出一种三相CSR整流电路节能和并联叠加的接线方法。
参看图1，现有的三相CSR 整流电路的特点是换流在相邻相上下桥臂开关管之间进行的，图1是CSR整流电路拓扑图，其中V1、V2、V3为A、B、C三相上桥臂开关管，D1、D2、D3、为A、B、C三相上桥臂二极管；V4、V5、V6为A、B、C三相下桥臂开关管，D4、D5、D6为A、B、C三相下桥臂二极管，L4为储能电感，D7为续流二极管。
现有的三相CSR 整流电路供电电源是由配电变压器的一个绕组提供的。在CSR 整流电路工作过程中的任一时刻，上桥臂的三个开关管和下桥臂的三个开关管分别有而且只能有一个开关管导通，以构成相间整流闭合回路。例如上桥臂的开关管V1导通下桥臂就是开关管V5或V6中的一个导通，以构成电流通路。其它各开关管动作以此类推。
参看图2，该图2为三相CSR 整流电路三相正弦波波形图，图2中，Ua、Ub、Uc代表A、B、C三相电压随时间（或角度）变化曲线，图2中时间轴上任选一点D，此时A、B、C三相对应的电压值分别是点F、G、E。
按照CSR电路工作原理，这一点工作电压应该是Uab（线段FG代表Uab大小）或Ubc(线段EG代表Ubc大小)。以电压Uab工作为例，该图1中对应的开关管V1、V5导通，电流i按照图1虚线所示从A相流出经过V1、D1、L4、负载RL及V5、D5后流回B相。这个过程中在CSR电路中主要产生损耗的器件有V1、D1、V5、D5，两个开关管和两个二极管。同理可以分析出每次导通过程都会产生两个开关管和两个二极管的损耗，开关管的损耗比二极管大的多。减少开关管数量是本发明的主要任务。
本发明是在现有的CSR整流电路中减少工作开关管数量来减少回路损耗。
具体方法是在供电的配电变压器低压侧出两个绕组，两个绕组电压相等，电气不连接，并且各带一个CSR非全桥回路。两组电路分别在各自的工作时间工作，工作时间对应角度为60°，形成交替模式且工作时间互补，从变压器一次侧输入来看电流正弦波不变形，完成完美的“全桥”CSR高频整流功能。
参看图3，配电变压器1，其一次侧接电网高压，二次侧输出两个绕组，分别是第一绕组和第二绕组，这两个绕组电压相等，各相对应相位相同。两个绕组分别带各自的CSR半桥电路。
如图3中，第一个绕组带的第一CSR半桥电路2，配电变压器1和第一CSR半桥电路2组合起来叫做上半区；第二个绕组带的第二CSR半桥电路3，配电变压器1和第二CSR半桥电路3组合起来叫做下半区。
本发明所述CSR半桥电路与传统的CSR全桥电路不同，现有CSR全桥电路如图1，上、下桥臂各有三个对称的开关管和二极管。
本发明所述CSR半桥电路如图3，图3中虚线框2所示为上半区的第一CSR半桥电路2。
该第一CSR半桥电路2中取消了现有电路下桥臂的三个开关管，上半区第一CSR半桥电路2具体构成是上半桥由开关管V11、V12、V13二极管D11、D12、D13组成，下半桥由二极管D14、D15、D16组成。
如图3，所述下半区的第二CSR半桥电路3取消了现有电路上桥臂的三个开关管，该第二CSR半桥电路3具体构成是上半桥由二极管D21、D22、D23组成，下半桥由开关管V24、V25、V26及二极管D24、D25、D26组成。
所述上、下半区工作时段对应的角度是严格界定的，上半区工作区间在0°～60°、120°～180°、240°～300º…；下半区工作区间在60°～120°、180°～240°、300°～360º…。
具体工作过程结合图2、图3分析，图2中设电压运行区间在0°～60°，此时配电变压器1第一绕组上半区CSR半桥电路2工作。变压器第二绕组下半区CSR电路3中开关管全部处在截止状态，此时段下半区不工作，即V24、V25、V26（含V224、V225、V226）全部截止。任选图2中的D点，CSR电路特点此刻工作电压是Uab或Ubc，假设电压Uab工作，工作过程是V11开通，电流从A相流经D11、V11、L14、负荷RL及D15返回B相，如图3，上半区CSR半桥电路2中电流i流向。在D点A、B、C三相对应的电压值分别是点F、G、E，可以看出在0°～60°区间B相电压最低，下桥臂虽然有三相的三个二极管D14、D15、D16，但是电流只能从电位最低相B流回，因此A相电流只能从B相D15流回，不能从C相回。因此Uab工作过程中在CSR电路中主要产生损耗的器件有D11、V11、D15，一个开关管和两个二极管。这个过程就比传统CSR工作减少一个开关管的损耗。
同样假设D点附近电压Ubc工作，此时V13管开通，电流从C相流经D13、V13、L14、负荷RL及D15返回B相。由于在0°～60°区间B相电位最低，因此C相电流只能从B相二极管D15流回，不能从A相走回。
因此Ubc工作过程中在CSR电路中产生损耗的器件有D13、V13、D15，一个开关管和两个二极管。这个过程也比传统CSR工作减少一个开关管的损耗。
如图2，电压运行在区间60°～120°，此时配电变压器1第二绕组和下半区第二CSR半桥电路3工作。配电变压器1第一绕组上半区CSR半桥电路2中的开关管全部截止，即V11、V12、V13（含V121、V122、V123）全部截止，此时段上半区不工作。
在图2中任选一点H点，此时A、B、C三相电压值对应的点分别是K、J、I。上桥臂三相虽然有三个二极管D21、D22、D23，可以看出在60°～120°区间A相电位最高，因此电流只能从A相二极管D21流出，不能从B、C相的二极管D22、D23流出。CSR电路特点此刻工作电压只能是Uab或Uac。以Uab电压工作为例，令V25开通，电流经V25从B相流回，电流流经器件是D21、负荷RL、L24、V25及D25返回B相。这个过程中在CSR半桥电路中产生损耗的器件有D21、V25、D25，一个开关管和两个二极管，比传统CSR整流电路工作减少一个开关管的损耗。同样分析电压Uac工作损耗情况也是一样。
同样的道理，由于在120°～180°区间C相电位最低，CSR电路特点此刻只能是电压Uac、Ubc工作，A、B相电流只能从C相流回。同样的分析电压Uac、Ubc，其工作过程中在CSR半桥电路中产生损耗的器件也是一个开关管和两个二极管。
上、下半桥电路每隔60°就进行一次转换，控制方法依照上述原理安排，圆满完成CSR对称整流工作。原来CSR全桥整流回路中有两个开关管和两个二极管的损耗，本发明CSR半桥整流节约了一个开关管的损耗。
开关管损耗由两部分组成，一个是开关过程损耗，一个是饱和导通压降损耗，其饱和导通压降约为3伏，若回路有50安电流，此时开关管饱和导通损耗是150瓦，开关过程损耗是饱和导通损耗的三倍以上。二极管压降不足1伏，回路50安电流时二极管损耗不足50瓦。因此，本发明CSR半桥整流回路节约一个开关管工作，相当于减少回路损耗30%以上。
依目前晶体管制造工艺，高电压大功率开关管工作频率做不了太高，要使CSR整流回路提高功率因数、减少谐波、提高功率输出，需要多组CSR整流回路并联叠加工作。
现有CSR全桥整流电路桥端输出回路只能有一个储能电感，如图1中的L4，使输出电路不对称，图2中电压工作在正弦波上半周可以并联叠加，下半周不可以并联，造成CSR整流回路不能多组并联叠加。
本发明由于配电变压器1低压侧出了两个绕组，两个绕组电压相等，电气不连接，并且各带一组CSR半桥回路，组成上、下半区，上、下半区的半桥都分别带一个储能电感，这样电压正弦波上、下半周工作平衡，两个半区组合完成全对称CSR整流工作。
如图3，上半区的两个半桥分别带电感L14和L124；下半区的两个半桥分别带电感L24和L224。回路工作具有了对称性，可以很好地完成并联叠加。
如图3，上半区第一CSR半桥电路2包括有第一并联叠加回路4，该第一并联叠加回路4是上半区第二组CSR半桥回路。具体组成是开关管V121、V122、V123和二极管D121、D122、D123，电感L124是第一并联叠加回路4半桥的储能元件。第一并联叠加回路4中各开关管的电流通过负载做功后流经第一CSR半桥电路2中的二极管D14、D15、D16返回电源端。
参看图3，第二CSR半桥电路3包括有第二并联叠加回路5，第二并联叠加回路5是下半区第二组CSR半桥回路。具体组成是开关管V224、V225、V226和二极管D224、D225、D226，电感L224是第二并联叠加回路5半桥的储能元件。
该第二并联叠加回路5中各开关管的电流通过负载做功后流经第二CSR半桥电路3中的二极管D21、D22、D23返回电源端。其中D14、D15、D16是上半区各组返回电流的共用二极管，D21、D22、D23是下半区各组输出电流的共用二极管。
图3中只画了两组并联叠加电路，实际电路可以是多组并联叠加，具体并联组数根据负荷要求确定。后面各组控制相位与第一组有移相关系。假设有N个CSR整流电路并联叠加，每个CSR整流电路都采用载波三角波移相控制，三角波周期内N个三角波移相互相错开的角度为 。N个CSR整流电路都用相同的正弦波进行调制。并联叠加控制技术与现有成熟的电压源VSR整流电路并联叠加技术的原理相同，这里不再赘述。
本发明是在CSR整流电路中减少工作开关管数量来减少回路损耗。具体方法是在供电的配电变压器低压侧出两个绕组，两个绕组电压相等，电气不连接，并且各带一个CSR非全桥回路，形成上下两组回路。所谓CSR非全桥回路是在一组的上桥臂和另一组的下桥臂分别减少三个开关管。两组电路分别在各自的工作时间工作，工作时间对应角度区间为60°，工作形成交替模式且时间互补，使电流为正弦波不变形，完成全桥CSR高频整流功能。见图3中虚线框2和虚线框3分别为上下两组CSR半桥回路。两个半桥回路分别工作时比原有的CSR全桥回路减少一个开关管，从而减少了电路损耗。另外，配电变压器低压侧出了两个绕组，并且各带一组CSR半桥回路，上、下两组的半桥都分别带一个储能电感。回路工作具有了对称性，可以很好地完成并联叠加，达到增加输出功率的作用。

Claims (3)

1、一种三相CSR整流电路节能和并联叠加的接线方法，其特征在于：所述供电的配电变压器低压侧输出两个绕组，两个绕组分别给两组CSR半桥整流电路供电，两个绕组电压相等，对应相相位相同。
根据权利要求1所述三相CSR整流电路节能和并联叠加的接线方法，其特征在于：所述每个绕组分别各带一组CSR非全桥回路，两组CSR非全桥回路分别在各自的工作时间工作，工作时间对应角度区间为60 ，形成交替工作模式且时间互补，完成全桥CSR高频整流功能。
根据权利要求2所述三相CSR整流电路节能和并联叠加的接线方法，其特征在于：所述两组CSR非全桥回路可并联叠加成多组CSR非全桥回路。
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