WO2023197660A1

WO2023197660A1 - Controller for active clamp flyback conversion circuit, power source module, and electronic device

Info

Publication number: WO2023197660A1
Application number: PCT/CN2022/140116
Authority: WO
Inventors: 孙程豪; 伍梁; 戴宝磊; 单浩仁
Original assignee: 华为数字能源技术有限公司
Priority date: 2022-04-11
Filing date: 2022-12-19
Publication date: 2023-10-19
Also published as: CN114759796A

Abstract

Provided in the present application are a controller for an active clamp flyback conversion circuit, a power source module, and an electronic device. After an active clamp flyback conversion circuit operates in a paused operation state, the controller can control a resonant capacitor of the active clamp flyback conversion circuit to discharge, such that the voltage value of an output voltage of a power source circuit is greater than a preset voltage value of low-voltage protection of the controller, thereby preventing the controller from restarting due to low-voltage protection, and improving the stability of a power source module and an electronic device where the active clamp flyback conversion circuit is located. Moreover, when controlling the resonant capacitor to discharge, the controller does not increase the ripples of an output voltage of the active clamp flyback conversion circuit, and also does not introduce noise from an input power source.

Description

Controllers, power modules and electronic equipment for active clamp flyback conversion circuits

This application requests the priority of the Chinese patent application submitted to the China Patent Office on April 11, 2022, with the application number 202210374393.7 and the application name "Controller, power module and electronic equipment for active clamp flyback conversion circuit" , the entire contents of which are incorporated herein by reference.

Technical field

This application relates to power supply technology, and in particular to an active clamp flyback (ACF) controller and the power module and electronic equipment in which it is located.

Background technique

Existing electronic equipment or power modules usually include asymmetrical half-bridge (AHB), active clamp flyback (ACF) and other types of DC conversion circuits and controllers. DC conversion circuits usually include half-bridge circuits, transformers and rectifier circuits. The primary winding circuit of the transformer receives the input voltage from the input power supply through the half-bridge circuit, and the secondary winding circuit is used to provide the output voltage to power the load. Among them, the transformer also includes an auxiliary winding circuit for supplying power to the power circuit of the controller. When the power module is started, the controller's power circuit is generally powered by the input voltage of the input power supply. When the power module is running, the auxiliary winding circuit of the transformer supplies power to the controller's power circuit. Therefore, the operating status of the DC conversion circuit will affect the power supply stability of the controller's power circuit, thereby affecting the stability of the power supply module and electronic equipment where the controller is located.

Contents of the invention

This application provides a controller, power module and electronic equipment for an active clamp flyback conversion circuit, which are used to solve the problem that the operating status of DC conversion circuits such as active clamp flyback conversion circuits affects the power circuit and control of the controller. Technical issues related to the stability of the power module and electronic equipment where the device is located.

Taking the DC conversion circuit as an active clamp flyback conversion circuit as an example, the first aspect of this application provides a controller for the active clamp flyback conversion circuit, which can be used to control the operating status of the active clamp flyback conversion circuit. . Wherein, when the controller controls the active clamp flyback conversion circuit to operate in a continuous working state, the output voltage of the active clamp flyback conversion circuit is the rated output voltage. When the controller determines that the output voltage of the active clamp flyback conversion circuit is higher than the first preset value, it controls the active clamp flyback conversion circuit to run in a suspended working state. Subsequently, after the active clamp flyback conversion circuit operates in the suspended working state, when the controller determines that the output voltage of the auxiliary winding circuit in the active clamp flyback conversion circuit is less than or equal to the second preset value, the control The clamp capacitor of the source clamp flyback converter circuit is discharged. Or, after the active clamp flyback conversion circuit is running in the suspended working state, when the controller determines that the output voltage of the power circuit in the active clamp flyback conversion circuit is less than or equal to the third preset value, the active clamp flyback conversion circuit is controlled to The clamping capacitor of the clamp flyback converter circuit is discharged. Therefore, the controller provided in this embodiment can control the clamping capacitor of the active clamp flyback conversion circuit to discharge after the active clamp flyback conversion circuit is running in the suspended working state, so that the output voltage of the power circuit can be The value is higher than the preset voltage value of the controller's low-voltage protection, thereby preventing the controller from restarting due to low-voltage protection and improving the stability of the power module and electronic equipment where the active clamp flyback conversion circuit is located. Moreover, the controller provided in this embodiment will not increase the ripple of the output voltage of the active clamp flyback conversion circuit when controlling the discharge of the clamp capacitor, nor will it introduce noise from the input power supply.

In an embodiment of the first aspect of the present application, when the controller determines that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the controller controls the active clamp flyback conversion circuit to switch from the suspended operating state. For continuous working status. Therefore, the controller provided in this embodiment can timely control the active clamp flyback conversion circuit to resume continuous operation after the output voltage of the active clamp flyback conversion circuit returns to normal, further improving the efficiency of the active clamp flyback conversion circuit. The stability of the power module and electronic equipment where the conversion circuit is located.

In an embodiment of the first aspect of the present application, the controller controls the active clamp flyback conversion circuit by controlling both the auxiliary power transistor and the main power transistor of the half-bridge conversion circuit in the active clamp flyback conversion circuit to turn off. The conversion circuit runs in a suspended working state. Therefore, the controller provided in this embodiment can control the active clamp flyback conversion circuit to no longer process the received input voltage and provide an output voltage after the load level of the power module in which it is located drops, thus avoiding the need for power supply The output voltage of the module is too high and damages the load.

In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to be turned on to discharge the clamping capacitor in the half-bridge circuit. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased faster, the output voltage of the power module can be reduced faster, and the output voltage of the power module to the load can be reduced as much as possible to be greater than the first preset value. Protect loads more effectively.

In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to be turned on periodically to discharge the clamping capacitor in the half-bridge circuit. Since the clamping capacitor in the half-bridge circuit is periodically discharged, the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased in a stepwise manner, preventing the voltage from increasing too quickly and damaging the circuit components, thereby improving the active clamping The stability of the power module and electronic equipment where the flyback conversion circuit is located.

In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to periodically alternately conduct, so that the clamping capacitor in the half-bridge circuit Discharge. Among them, when the controller controls the auxiliary power tube to turn on and the main power tube to turn off, the clamp capacitor discharges and the output voltage of the controller's power circuit increases; when the controller controls the auxiliary power tube to turn off and the main power tube to turn on , the input voltage generates the primary winding voltage on both sides of the primary winding. The primary winding voltage is coupled through the transformer to produce an auxiliary winding voltage on the auxiliary winding. Correspondingly, the voltage value of the output voltage of the auxiliary winding circuit increases, and the voltage value of the output voltage of the power supply circuit of the controller increases. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit are increased in a stepwise manner to avoid damage to the circuit components due to excessive increase, thereby improving the stability of the power module and electronic equipment where the active clamp flyback conversion circuit is located.

In each of the above embodiments, when the load level of the power module drops, the controller can control the clamping capacitor to start discharging. And when controlling the discharge of the clamp capacitor, the controller only needs to control the conduction or cut-off of the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit, making its configuration simple and more suitable for use in various products.

In an embodiment of the first aspect of the present application, the controller determines that the capacitor voltage of the clamp capacitor drops to less than or equal to the preset capacitor voltage value, and then controls the clamp capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the capacitor voltage of the clamp capacitor from being too low and affect the active clamp flyback conversion circuit from returning to a continuous working state, further improving the efficiency of the power module where the active clamp flyback conversion circuit is located. and the stability of electronic equipment.

In an embodiment of the first aspect of the present application, the controller determines that the voltage value of the output voltage of the auxiliary winding circuit has increased to greater than or equal to the fourth preset value, and then controls the clamping capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the auxiliary winding circuit from being too high and damage the power circuit and the controller, further improving the stability of the power module and electronic equipment where the active clamp flyback conversion circuit is located. sex.

In an embodiment of the first aspect of the present application, the controller can determine that the voltage value of the output voltage of the power circuit has increased to greater than or equal to the fifth preset value, and then controls the clamping capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the power circuit from being too high and damage the controller, further improving the stability of the power module and electronic equipment where the active clamp flyback conversion circuit is located.

In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to turn off, so that the clamping capacitor stops discharging. Therefore, in the scenario where the load level of the power module drops, the controller in this embodiment only needs to control the conduction of the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit to control the clamp capacitor to stop discharging. Pass or cut off, making it simple to configure and more suitable for use in various products.

A second aspect of this application provides a power module, including an active clamp flyback conversion circuit, an auxiliary winding circuit, a power circuit and a controller. Among them, the active clamp flyback conversion circuit includes: half-bridge circuit, transformer and rectifier circuit. The half-bridge circuit includes a main power tube, an auxiliary power tube and a clamping capacitor.

The active clamp flyback conversion circuit is used to receive the input voltage, perform voltage conversion on the input voltage, and then provide the output voltage to the load. The auxiliary winding circuit is used to power the power circuit. A power circuit is used to power the controller. The controller can be used to control the active clamp flyback converter circuit.

Wherein, when the controller controls the active clamp flyback conversion circuit to operate in a continuous working state, the output voltage of the active clamp flyback conversion circuit is the rated output voltage. When the controller determines that the output voltage of the symmetrical half-bridge conversion circuit is higher than the first preset value, it controls the active clamp flyback conversion circuit to run in a suspended working state. Subsequently, after the active clamp flyback conversion circuit operates in the suspended working state, when the controller determines that the output voltage of the auxiliary winding circuit in the active clamp flyback conversion circuit is less than or equal to the second preset value, the control The clamp capacitor of the source clamp flyback converter circuit is discharged. Or, after the active clamp flyback conversion circuit is running in the suspended working state, when the controller determines that the output voltage of the power circuit in the active clamp flyback conversion circuit is less than or equal to the third preset value, the active clamp flyback conversion circuit is controlled to The clamping capacitor of the clamp flyback converter circuit is discharged.

Therefore, in the power module provided by this embodiment, the controller can control the clamping capacitor of the active clamp flyback conversion circuit to discharge after the active clamp flyback conversion circuit is running in the suspended working state, so that the power circuit can The voltage value of the output voltage is higher than the preset voltage value of the controller's low-voltage protection, thereby preventing the controller from restarting due to low-voltage protection and improving the stability of the power module and its electronic equipment. Moreover, the controller provided in this embodiment will not increase the ripple of the output voltage of the active clamp flyback conversion circuit when controlling the discharge of the clamp capacitor, nor will it introduce noise from the input power supply.

In an embodiment of the second aspect of the present application, when the controller determines that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the controller controls the active clamp flyback conversion circuit to switch from the suspended operating state. For continuous working status. Therefore, in the power module provided by this embodiment, the controller can timely control the active clamp flyback conversion circuit to resume continuous operation after the output voltage of the active clamp flyback conversion circuit returns to normal, further improving the power supply The stability of the module and the electronic equipment in which it resides.

In an embodiment of the second aspect of the present application, the controller controls the active clamp flyback conversion circuit by controlling both the auxiliary power transistor and the main power transistor of the half-bridge conversion circuit in the active clamp flyback conversion circuit to turn off. The conversion circuit runs in a suspended working state. Therefore, in the power module provided by this embodiment, the controller can control the active clamp flyback conversion circuit to no longer process the received input voltage and provide an output after the load level of the power module in which it is located drops. voltage to avoid the output voltage of the power module being too high and damaging the load.

In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to be turned on to discharge the clamping capacitor in the half-bridge circuit. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased faster, the output voltage of the power module can be reduced faster, and the output voltage of the power module to the load can be reduced as much as possible to be greater than the first preset value. Protect loads more effectively.

In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to be turned on periodically to discharge the clamping capacitor in the half-bridge circuit. Since the clamping capacitor in the half-bridge circuit discharges periodically, the output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be increased in a stepwise manner, preventing the voltage from increasing too quickly and damaging the circuit components, thus improving the efficiency of the power module and The stability of the electronic equipment in which it is located.

In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to periodically alternately conduct, so that the clamping capacitor in the half-bridge circuit Discharge. Among them, when the controller controls the auxiliary power tube to turn on and the main power tube to turn off, the clamp capacitor discharges and the output voltage of the controller's power circuit increases; when the controller controls the auxiliary power tube to turn off and the main power tube to turn on , the input voltage generates the primary winding voltage on both sides of the primary winding. The primary winding voltage is coupled through the transformer to produce an auxiliary winding voltage on the auxiliary winding. Correspondingly, the voltage value of the output voltage of the auxiliary winding circuit increases, and the voltage value of the output voltage of the power supply circuit of the controller increases. The output voltage of the auxiliary winding circuit and the output voltage of the power circuit are increased in a stepwise manner to avoid damage to the circuit components due to excessive increase, thereby improving the stability of the power module and the electronic equipment in which it is located.

In each of the above embodiments, when the load level of the power module drops, the controller in the power module can control the clamping capacitor to start discharging. And when controlling the discharge of the clamp capacitor, the controller only needs to control the conduction or cut-off of the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit, making its configuration simple and more suitable for use in various products.

In an embodiment of the second aspect of the present application, the controller determines that the capacitor voltage of the clamp capacitor drops to less than or equal to the preset capacitor voltage value, and then controls the clamp capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the capacitance voltage of the clamping capacitor from being too low and affect the active clamp flyback conversion circuit from returning to a continuous working state, further improving the stability of the power module and the electronic equipment in which it is located.

In an embodiment of the second aspect of the present application, the controller determines that the voltage value of the output voltage of the auxiliary winding circuit has increased to greater than or equal to the fourth preset value, and then controls the clamping capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the auxiliary winding circuit from being too high and damaging the power circuit and the controller, further improving the stability of the power module and the electronic equipment in which it is located.

In an embodiment of the second aspect of the present application, the controller can determine that the voltage value of the output voltage of the power circuit has increased to greater than or equal to the fifth preset value, and then controls the clamping capacitor to stop discharging. Therefore, the controller in this embodiment can prevent the output voltage of the power circuit from being too high and damage the controller, further improving the stability of the power module and the electronic equipment in which it is located.

In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor and the main power transistor in the half-bridge circuit of the active clamp flyback conversion circuit to turn off, so that the clamping capacitor stops discharging. Therefore, in this embodiment, when the load level of the power module drops, the controller of the power module only needs to control the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit to control the clamp capacitor to stop discharging. On or off, it is simple to configure and more suitable for use in various products.

It should be noted that in the above embodiments, the DC conversion circuit is an active clamp flyback conversion circuit as an example. The DC conversion circuit may also be an asymmetric half-bridge conversion circuit, etc.

A third aspect of this application provides an electronic device, including a controller of an active clamp flyback conversion circuit as described in any one of the first aspect of this application.

A fourth aspect of this application provides an electronic device, including the power module according to any one of the second aspect of this application.

Description of the drawings

Figure 1 is a schematic diagram of an electronic device provided by this application;

Figure 2 is another schematic diagram of an electronic device provided by this application;

Figure 3 is a schematic diagram of a power module provided by an embodiment of the present application;

Figure 4 is a schematic diagram of a power module;

Figure 5 is a schematic diagram of the voltage waveform of the power module of Figure 4 in a scenario where the load level drops;

Figure 6 is a schematic diagram of another existing controller and its power module;

Figure 7 is a schematic diagram of a power module provided by an embodiment of the present application;

Figure 8 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;

Figure 9 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 10 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 11 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;

Figure 12 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 13 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops;

Figure 14 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application;

Figure 15 is a schematic diagram of an embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit;

Figure 16 is a schematic diagram of changes in the capacitance voltage of the resonant capacitor of the AHB conversion circuit provided by this application;

Figure 17 is a schematic diagram of another embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit;

Figure 18 is a schematic diagram of the half-bridge circuit in another AHB conversion circuit provided by this application;

Figure 19 is a schematic diagram of the half-bridge circuit in another AHB conversion circuit provided by this application;

Figure 20 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 21 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 22 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops;

Figure 23 is a schematic diagram of an embodiment of the power module provided by this application;

Figure 24 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops;

Figure 25 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application;

Figure 26 is a schematic diagram of an embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit;

Figure 27 is a schematic diagram of changes in capacitance voltage of the clamp capacitor of the ACF conversion circuit provided by this application;

Figure 28 is a schematic diagram of another embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit.

Detailed ways

Figure 1 is a schematic diagram of an electronic device provided by this application. As shown in FIG. 1 , the electronic device 10 includes a power module 11 and a load 12 . The power module 11 receives the input voltage V ₁ provided by the input power supply 13 and provides the output voltage V ₂ to power the load 12 . In one embodiment, the electronic device 10 may include multiple power modules 11 , and the multiple power modules 11 provide multiple output voltages V ₂ to power the load 12 . In one embodiment, the electronic device 10 may include multiple loads 12 , and the power module 11 provides multiple output voltages V ₂ to respectively power the multiple loads 12 . In one embodiment, the electronic device 10 may include multiple loads 12 and multiple power modules 11 , and the multiple power modules 11 may respectively supply power to the multiple loads 12 . In one embodiment, the electronic device 10 may receive output voltages V ₁ from multiple input power supplies 13 . In one embodiment, electronic device 10 may include one or more input power supplies 13 . In one embodiment, the electronic device 10 may be an electronic device such as a mobile phone, a computer, a tablet, or a home appliance. In one embodiment, the load 12 includes an internal circuit of the electronic device 10 or an external electronic device of the electronic device 10 .

Figure 2 is another schematic diagram of an electronic device provided by this application. As shown in FIG. 2 , the electronic device 10 includes a power module 11 . The power module 11 receives the input voltage V ₁ provided by the input power supply 13 and provides the output voltage V ₂ to power the load 12 . In one embodiment, the electronic device 10 includes multiple power modules 11 , and the multiple power modules 11 can provide multiple output voltages V ₂ to power the load 12 . In one embodiment, the power module 11 in the electronic device 10 can provide multiple output voltages V ₂ to power multiple loads 12 respectively. In one embodiment, the electronic device 10 may include multiple power modules 11 , and the multiple power modules 11 respectively provide output voltages V ₂ for multiple loads 12 . In one embodiment, electronic device 10 may receive multiple input power supplies 13 . In one embodiment, electronic device 10 may include input power source 13 . In one embodiment, the electronic device 10 may be an adapter, a charging pile, or other equipment. Generally, an adapter can also be called a charger, a charging head, a switching power supply, a power converter, etc. In one embodiment, the load 12 may be an electronic device such as a mobile phone, a computer, a tablet, or a home appliance. In one embodiment, load 12 may be other internal circuitry of electronic device 10 .

FIG. 3 is a schematic diagram of a power module provided by an embodiment of the present application. As shown in FIG. 3 , the power module 11 includes a direct current (DC) conversion circuit 111 , an auxiliary winding circuit 112 , a power circuit 113 and a controller 114 . The DC conversion circuit 111 is used to receive the input voltage V ₁ provided by the input power supply 13 and provide the output voltage V ₂ to the load 12 . In addition, the DC conversion circuit 111 supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112 . Among them, the auxiliary winding circuit 112 is coupled with the DC conversion circuit 111 to generate the auxiliary winding voltage V ₃ on the auxiliary winding. The auxiliary winding circuit 112 converts the auxiliary winding voltage V ₃ into the output voltage V ₄ and provides the output voltage V ₄ to the power supply circuit 113 . The power supply circuit 113 converts the output voltage V ₄ of the auxiliary winding circuit 112 into the output voltage V ₅ and provides the output voltage V ₅ to the control circuit 114 . The controller 114 is used to control the DC conversion circuit 111. In this embodiment of the present application, the DC conversion circuit 111 may include an asymmetrical half-bridge (AHB) conversion circuit or an active clamp flyback (ACF) conversion circuit.

Figure 4 is a schematic diagram of a power module. As shown in Figure 4, the power module 11 includes a DC conversion circuit 111, an auxiliary winding circuit 112, a power circuit 113 and a controller 114. The DC conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifier circuit 1114. Among them, the transformer 1112 includes a primary winding 1111 and a secondary winding 1113. In addition, the transformer 1112 also includes an auxiliary winding 1121 in the auxiliary winding circuit 112 . The secondary winding 1113 is coupled to the primary winding 1111, and the auxiliary winding 1121 is coupled to the primary winding 1111.

The half-bridge circuit 1110 is used to receive the input voltage V ₁ provided by the input power supply 13 and provide the output voltage V ₁₀ according to the control signal of the controller 114 . The input voltage V ₁ and the output voltage V ₁₀ may be in a voltage range. The half-bridge circuit 1110 usually includes a main power transistor, an auxiliary power transistor and a capacitor. According to the connection relationship between the main power tube, the auxiliary power tube and the capacitor, the DC conversion circuit 111 includes an AHB conversion circuit and an ACF conversion circuit. The capacitor in the half-bridge circuit 1110 of the AHB conversion circuit is the resonant capacitor C _r . The capacitor in the half-bridge circuit 1110 of the ACF conversion circuit is the clamping capacitor C _c .

The primary winding 1111 of the transformer 1112 is used to receive the output voltage V ₁₀ of the half-bridge circuit 1110 and generate the primary winding voltage V ₁₁ on the primary winding 1111 . The secondary winding 1113 of the transformer 1112 is coupled with the primary winding 1111 of the transformer 1112, and the secondary winding voltage V ₁₂ is generated on the secondary winding 1113. The winding voltage V ₁₁ and the secondary winding voltage V ₁₂ may be in a voltage range.

The rectifier circuit 1114 is used to receive the secondary winding voltage V ₁₂ generated on the secondary winding 1113 and convert it into an output voltage V ₂ . The output voltage V ₂ can be a voltage range.

The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 . The auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled with the primary winding 1111 of the transformer 1112 . The primary winding voltage V ₁₁ on the primary winding 1112 is coupled to generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121 . After the auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 112 , the output voltage V ₄ is provided to the power supply circuit 113 . Among them, the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122. The auxiliary winding voltage _V3 and the output voltage _V4 can be in a voltage range.

The power circuit 113 is used to power the controller 114 . The power supply circuit 113 receives the output voltage V ₄ of the auxiliary winding circuit 112 and provides the output voltage V ₅ to the controller 114 . Among them, the power circuit 113 may include a voltage stabilizing circuit. The output voltage V ₅ can be a voltage range.

The controller 114 is used to control the operating state of the DC conversion circuit 111. The controller 114 may send the control signal G to the half-bridge circuit 1110 of the DC conversion circuit 111, thereby controlling the operating state of the DC conversion circuit 111. The operating status of the DC changing circuit 111 usually includes a continuous working status and a suspended working status. The continuous working state can also be called the normal working state, the controller's normal wave sending state, etc. The suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.

When the load level of the load 12 of the power module 11 drops, since the primary winding voltage V 11 of the primary winding 1111 in the DC conversion circuit ₁₁₁ does not change, the voltage value of the output voltage V ₂ of the DC conversion circuit 111 will increase rapidly. . Correspondingly, the controller 114 needs to adjust the operating state of the DC conversion circuit 111 to reduce the output voltage V ₂ of the DC conversion circuit 111 to prevent the output voltage V ₂ of the power module 11 from being too high and damaging the load 12 .

FIG. 5 is a schematic diagram of the voltage waveform of the power module of FIG. 4 in a scenario where the load level drops. The impact of the drop of the load level L of the load 12 on the existing controller 114 and the power module 11 in which it is located will be described in detail below with reference to the power module 11 shown in FIG. 4 .

Before time t ₁ , the load level L of the load 12 is the normal load L ₁ . The controller 114 controls the DC conversion circuit 111 to be in a continuous operating state, and the voltage value of the output voltage V ₂ of the DC conversion circuit 111 is the rated output voltage V ₂₀ . The rated output voltage V ₂₀ is the rated output voltage of the DC conversion circuit 111 in a continuous operating state. The rated output voltage V ₂₀ can be a voltage range. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value V ₄₀ is the rated input voltage of the auxiliary winding circuit 112 . The voltage value V ₄₀ may be a voltage range in which the output voltage V ₅ of the power supply circuit 113 has a voltage value V ₅₀ . The voltage value V ₅₀ is the rated input voltage of the controller 114 . The voltage value V ₅₀ may be a voltage range.

At time t ₁ , the load level L of load 12 drops from normal load L ₁ to light load L ₂ .

After time t ₁ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 will increase to greater than the rated output voltage V ₂₀ . In one embodiment, the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. Furthermore, the controller 114 reduces the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1111, so that the voltage value of the primary winding voltage V ₁₁ of the primary winding 1111 decreases. Correspondingly, the voltage value of the secondary winding voltage V ₁₃ decreases, which can reduce the voltage value of the output voltage V ₂ of the DC conversion circuit 111 . Since the auxiliary winding 1121 in the auxiliary winding circuit 112 is coupled with the primary winding 1111, the voltage value of the auxiliary winding voltage _V3 decreases. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

However, the load level drop of the load 12 has a greater impact. The controller 114 usually cannot effectively reduce the output voltage of the DC conversion circuit 111 only by reducing the conduction frequency or conduction time of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1111. The voltage value of _V2 . As a result, after time t ₁ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 will continue to increase.

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 increases to a value greater than or equal to the first preset value V ₂₁ . If the voltage value of the output voltage V ₂ of the conversion circuit 111 is too high, the load 12 will be damaged. In order to prevent the voltage value of the output voltage V ₂ of the DC conversion circuit 111 from continuing to increase, the controller 114 needs to control the DC conversion circuit 111 to operate in a suspended operating state. The voltage value V ₂₁ is recorded as the first preset value, and the voltage value V ₂₁ is the maximum output voltage of the DC conversion circuit 111 . The voltage value V ₂₁ is smaller than the rated output voltage V ₂₀ of the DC conversion circuit 111 and is smaller than the overvoltage protection voltage of the DC conversion circuit 111 .

After time t ₂ , the DC conversion circuit 111 is in a suspended operating state, causing the primary winding voltage V ₁₁ of the primary winding circuit 1111 in the DC conversion circuit 111 to decrease. Accordingly, the voltage value of the output voltage V ₂ of the DC conversion circuit 111 decreases. Since the auxiliary winding 1121 is coupled to the primary winding 1111, the primary winding voltage V ₁₁ of the primary winding 1111 decreases, which causes the voltage value of the auxiliary winding voltage V ₃ of the auxiliary winding 1121 to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

If the voltage value of the output voltage V ₅ of the power circuit 113 is less than the under-voltage protection voltage V ₅₁ of the controller 114, the controller 114 will restart due to low-voltage protection. The voltage value V ₅₁ is the under-voltage protection voltage of the controller 114 . It takes a period of time for the controller 114 to complete the restart process, which results in the controller 14 being unable to control the operating status of the DC transformer circuit 111 during this period, thereby affecting the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

At time t ₃ after time t ₂ , the voltage value of the output voltage V ₅ of the power supply circuit 113 drops to less than or equal to the third preset value V ₅₂ . The third preset value V ₅₂ is greater than the under-voltage protection voltage V ₅₁ of the controller 114 and less than the rated input voltage V ₅₀ of the controller 114 . When the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ , the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. Correspondingly, the voltage value of the primary winding voltage V ₁₁ increases. An increase in the voltage value of the primary winding voltage V ₁₁ can lead to an increase in the voltage value of the auxiliary winding voltage V ₃ . Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases. The voltage value of the output voltage V ₅ of the power supply circuit 113 increases. However, an increase in the voltage value of the primary winding voltage V ₁₁ will also cause an increase in the voltage value of the secondary winding voltage V ₁₂ , thereby increasing the voltage value of the output voltage V ₂ of the DC conversion circuit 111 .

At time t ₄ after time t ₃ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 increases to greater than or equal to the second predetermined value V ₂₁ . At this time, the controller 114 needs to control the DC conversion circuit 111 to operate in a suspended working state. The DC conversion circuit 111 operates in a suspended state, which can cause the voltage value of the primary winding voltage V ₁₁ to drop. Accordingly, the voltage value of the output voltage V ₂ of the DC conversion circuit 111 decreases. However, a drop in the voltage value of the primary winding voltage V ₁₁ will also cause a drop in the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 . Accordingly, the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

At time t ₅ after time t ₄ , the voltage value of the output voltage V ₅ of the power supply circuit 113 drops to less than or equal to the fifth predetermined value V ₅₂ . At this time, the controller 114 needs to control the DC conversion circuit 111 to operate in a continuous working state. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases. The voltage value of the output voltage V ₅ of the power supply circuit 113 increases. However, the DC conversion circuit 111 operates in a continuous operating state, which will increase the voltage value of the output voltage V ₂ of the DC conversion circuit 111 .

Therefore, although the controller 114 in the existing power module 11 can avoid restarting due to under-voltage protection, it will also cause the output voltage V ₂ of the DC conversion circuit 111 to have a large ripple. Therefore, the existing controller 114 and the power module 11 in which it is located will cause the output voltage V ₂ of the DC conversion circuit 111 to have a large ripple, thus affecting the stability of the power module 11 .

Figure 6 is a schematic diagram of another existing controller and its power module. As shown in FIG. 6 , the auxiliary winding circuit 112 in the power module 11 is connected to the input power supply 13 through the switch K. After the change in the load level L of the load 12 causes the voltage value of the output voltage V ₂ of the DC conversion circuit 111 to increase, the controller 114 controls the DC conversion circuit 111 to run in a suspended operating state, and the controller 114 controls the switch K to turn on. The input power supply 13 supplies power to the power circuit 113 through the switch K and the auxiliary winding circuit 112, thereby preventing the controller 114 from restarting due to under-voltage protection. However, the noise of the input power supply 13 will also be transmitted to the inside of the power module 11 through the switch K, affecting the electromagnetic compatibility (EMC) of the power module 11 .

This application provides a controller of a DC conversion circuit and its power module and electronic equipment, which can solve the stability and electromagnetic compatibility problems of the controller, its power module and electronic equipment in the prior art. Defects such as increased output voltage ripple. Detailed description is provided below with specific embodiments. The following specific embodiments can be combined with each other, and the same or similar concepts or processes may not be described again in some embodiments.

FIG. 7 is a schematic diagram of a power module provided by an embodiment of the present application. The power module 11 shown in FIG. 7 can be applied in the electronic device 10 shown in FIG. 1 or 2 . As shown in FIG. 7 , the power module 11 includes a DC conversion circuit 111 , an auxiliary winding circuit 112 , a power circuit 113 and a controller 114 . The DC conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifier circuit 1114. Among them, the transformer 1112 includes a primary winding 1111 and a secondary winding 1113. In addition, the transformer 1112 also includes an auxiliary winding 1121 in the auxiliary winding circuit 112 . The secondary winding 1113 is coupled to the primary winding 1111, and the auxiliary winding 1121 is coupled to the primary winding 1111.

The half-bridge circuit 1110 is used to receive the input voltage V ₁ provided by the input power supply 13 and provide the output voltage V ₁₀ to the primary winding 1111 according to the control signal of the controller 114 . The half-bridge circuit 1110 usually includes a main power transistor, an auxiliary power transistor and a capacitor. According to the connection relationship between the main power tube, the auxiliary power tube and the capacitor, the DC conversion circuit 111 in the embodiment of the present application includes an AHB conversion circuit and an ACF conversion circuit. In one embodiment, the DC conversion circuit 111 includes an AHB conversion circuit, and the capacitor in the half-bridge circuit 1110 is a resonant capacitor C _r . In one embodiment, the DC conversion circuit 111 includes an ACF conversion circuit, and the capacitor in the half-bridge circuit 1110 is a clamping capacitor C _c . In one embodiment, the main power transistor and the auxiliary power transistor are Metal-Oxide-Semiconductor Field-Effect Transistor (MOS). In other embodiments, the main power transistor and the auxiliary power transistor may also be triodes or other types of transistors such as insulated gate bipolar transistors (IGBTs).

The primary winding 1111 of the transformer 1112 is used to receive the output voltage V ₁₀ of the half-bridge circuit 1110 and generate the primary winding voltage V ₁₁ . The secondary winding 1113 of the transformer 1112 is coupled with the primary winding 1111 of the transformer 1112, and the secondary winding voltage V ₃ is generated on the secondary winding 1113.

The rectifier circuit 1114 is used to receive the secondary winding voltage V ₃ on the secondary winding 1113 and convert it into an output voltage V ₂ .

The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 . The auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled with the primary winding 1111 of the transformer 1112 . The primary winding voltage V ₁₁ on the primary winding 1112 is coupled to generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121 . After the auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 112 , the output voltage V ₄ is provided to the power supply circuit 113 . In one embodiment, the auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectifier module 1122.

The power circuit 113 is used to power the controller 114 . The power supply circuit 113 receives the output voltage V ₄ of the auxiliary winding circuit 112 and provides the output voltage V ₅ to the controller 114 . That is, the DC conversion circuit 111 supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112 . In some embodiments, power circuit 113 includes a voltage stabilizing circuit.

The controller 114 is used to control the operating state of the DC conversion circuit 111. The controller 114 is also used to detect the output voltage V ₂ of the DC conversion circuit 111 , the output voltage V ₄ of the winding circuit 112 , the output voltage V ₅ of the power supply circuit 113 or the capacitance voltage V _c of the capacitor in the half-bridge circuit 1110 and other voltages. value changes. The controller 114 is also used to control the operating state of the DC conversion circuit 111 according to changes in the one or more voltage values.

In one embodiment, the control 114 controls the operating state of the DC conversion circuit 111 by controlling the operating state of the half-bridge circuit 1110 in the DC conversion circuit 111 . For example, the controller 114 can control the on and off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, thereby controlling the operating status of the half-bridge circuit 1110. The controller 114 can adjust the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, and accordingly adjust the output voltage V ₁₀ of the half-bridge circuit 1110. Correspondingly, changes in the output voltage V ₁₀ of the half-bridge circuit 1110 will cause changes in the primary winding voltage V ₁₁ . Correspondingly, changes in the primary winding voltage V ₁₁ can cause changes in the secondary winding voltage V ₁₂ and the auxiliary winding voltage V ₃ . Correspondingly, changes in the secondary winding voltage V ₁₂ may cause the output voltage V ₂ of the DC conversion circuit 111 to change. Accordingly, changes in the auxiliary winding voltage V ₃ may cause the output voltage V ₄ of the auxiliary winding circuit 112 to change. Correspondingly, the output voltage V ₄ of the auxiliary winding circuit 112 may cause a change in the output voltage V ₅ of the power supply circuit 113 .

As shown in the F1 direction in FIG. 7 , the DC conversion circuit 111 can provide the output voltage V ₂ to power the load 12 . Among them, the input voltage V ₁ is converted into the output voltage V ₂ through the half-bridge circuit 1110, the primary winding 1111, the secondary winding 1113 and the rectifier circuit 1114 of the DC conversion circuit 111.

As shown in the F2 direction in FIG. 7 , the DC conversion circuit 111 can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 . After the input voltage V ₁ is processed by the half-bridge circuit 1110 of the DC conversion circuit 111 , the primary winding voltage V ₁₁ can be generated in the primary winding 1111 . Correspondingly, the primary winding voltage V ₁₁ can generate an auxiliary winding voltage V ₃ on the auxiliary winding 1121 of the transformer 1112 . The auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 1121 to provide an output voltage V ₄ to power the power supply circuit 113 of the controller 114 .

Figure 8 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIGS. 7 and 8 .

Before time t ₁ , the load level L of the load 12 is the normal load L ₁ . The controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. The controller 114 controls the output voltage V ₂ of the DC conversion circuit 111 to be at the rated voltage value. Output voltage V ₂₀ . The voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value of the output voltage V ₅ of the power supply circuit 113 is V ₅₀ . The voltage value of the capacitor voltage V _c of the capacitor in the half-bridge circuit 1111 is V _C1 . V _C1 is the capacitance voltage of the capacitor when the DC conversion circuit 111 operates in a continuous operating state.

At time t ₁ , the load level L of load 12 drops from normal load L ₁ to light load L ₂ . Correspondingly, after time t ₁ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 will increase to be greater than the rated output voltage V ₂₀ .

In one embodiment, when the voltage value of the output voltage V ₂ of the DC conversion circuit 111 is greater than the rated output voltage V ₂₀ , the controller 114 can control the DC conversion circuit 111 to operate in a continuous operating state. Furthermore, the controller 114 controls the DC conversion circuit 111 to reduce the voltage value of the output voltage V ₂ . That is, the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the DC conversion circuit 111 and the rated output voltage V ₂₀ . The controller 114 controls the DC conversion circuit 111 Reduce the voltage value of the output voltage _V2 . Specifically, the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, so that the voltage value of the primary winding voltage V ₁₁ decreases. In one embodiment, the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor. In one implementation, the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor. In another embodiment, when the voltage value of the output voltage V ₂ of the DC conversion circuit 111 is greater than the rated output voltage V ₂₀ , the controller 114 can control the DC conversion circuit 111 to operate in a suspended state, and can also reduce the output voltage V ₂ voltage value. However, the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V ₂ of the DC conversion circuit 111 , and the voltage value of the output voltage V ₂ of the DC conversion circuit 111 will continue to increase after time t ₁ .

At the same time, after time t ₁ , the drop of the load level L causes the voltage value of the output voltage V ₂ of the DC conversion circuit 111 to be higher than the rated output voltage V ₂₀ . The primary winding voltage V ₁₁ charges the capacitor in the half-bridge circuit 1110 , and the voltage value of the capacitor voltage V _c of the capacitor in the half-bridge circuit 1110 increases from _VC1 to _VC2 . V _C2 is the maximum charging voltage of the capacitor in the half-bridge circuit 1110.

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 increases to the first preset value V ₂₁ . The controller 114 determines that the voltage value of the output voltage V ₂ of the DC conversion circuit 111 is greater than or equal to the first preset value V ₂₁ , and the controller 114 controls the DC conversion circuit 111 to suspend operation. That is, the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V ₂ of the DC conversion circuit 111 and the first preset value V ₂₁ . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110 to turn off. In this embodiment of the present application, the first preset value V ₂₁ may be the peak voltage of the DC conversion circuit 111 . The peak voltage of the DC conversion circuit 111 is greater than the rated output voltage V ₂₀ and less than the overvoltage protection voltage of the DC conversion circuit 111 .

After time t ₂ , the controller 114 controls the DC conversion circuit 111 to operate in a suspended working state. Correspondingly, the voltage value of the output voltage V ₁₀ of the half-bridge circuit 1110 decreases, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 to decrease. The voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 decreases, which will cause the secondary winding voltage V ₁₂ on the secondary winding 1113 to decrease. Accordingly, the voltage value of the output voltage V ₂ of the DC conversion circuit 111 decreases. In addition, the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 decreases, which will cause the voltage value of the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

At time _t3 after time _t2 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 drops to less than or equal to the second preset value _V41 , or the voltage value of the output voltage _V5 of the power supply circuit 113 drops to less than Or equal to the third preset value V ₅₂ . The voltage value V ₄₁ is recorded as the second preset value. The voltage value V ₄₁ is greater than the lowest input voltage of the power circuit 113 and less than the rated input voltage V ₄₀ of the power circuit 113 . The voltage value V ₅₂ is recorded as the third preset value. The voltage value V ₅₂ is greater than the under-voltage protection voltage V ₅₁ of the controller 114 and less than the rated input voltage V ₅₀ of the controller 114

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the second preset value V ₄₁ , and the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 . That is, the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ .

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ , and the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 . That is, the controller 114 controls the capacitor discharge in the half-bridge circuit 1110 based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110 to be turned on, so that the capacitor of the half-bridge circuit 1110 is discharged. When the auxiliary power tube in the half-bridge circuit 1110 is turned on, the primary winding 1111 and the capacitor and auxiliary power tube of the half-bridge circuit 1110 can form a discharge circuit. Correspondingly, the capacitor in the half-bridge circuit 1110 is discharged, generating a primary winding voltage V ₁₁ on the primary winding 1111 .

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110 to be turned on periodically, so that the capacitor of the half-bridge circuit 1110 is discharged. When the auxiliary power in the half-bridge circuit 1110 is turned on, the primary winding 1111, the capacitor of the half-bridge circuit 1110, and the auxiliary power tube of the half-bridge circuit 1110 can form a discharge loop. Correspondingly, the auxiliary power transistor is periodically turned on, which can cause the capacitor in the half-bridge circuit 1110 to be periodically discharged.

In one embodiment, the DC conversion circuit 111 includes an AHB conversion circuit, and the controller 114 controls the discharge of the resonant capacitor in the half-bridge circuit 1110 of the AHB conversion circuit. In one embodiment, the DC conversion circuit 111 includes an ACF conversion circuit, and the controller 114 controls the discharge of the clamp capacitor in the half-bridge circuit 1110 of the ACF conversion circuit. In one embodiment, the half-bridge circuit 1110 of the DC conversion circuit 111 may include multiple capacitors, and the controller 114 controls the discharge of the multiple capacitors in the half-bridge circuit 1110.

After time _t3 , the voltage value of the capacitance voltage _Vc of the capacitor in the half-bridge circuit 1110 decreases. The capacitor in the half-bridge circuit 1110 is discharged, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 to increase. Correspondingly, an increase in the voltage value of the primary winding voltage V ₁₁ will cause an increase in the voltage value of the auxiliary winding voltage V ₃ . Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases. Therefore, in a scenario where the load level of the load 12 changes, the voltage value of the output voltage V ₅ of the power circuit 113 will not drop below the under-voltage protection voltage V ₅₁ of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.

The controller 114 provided in the embodiment of the present application controls the discharge of the capacitor in the primary winding circuit 1111 of the DC conversion circuit 111, so that the voltage value of the output voltage V ₅ of the power supply circuit 113 is higher than the preset value of the low-voltage protection of the controller 114. The voltage value V ₅₁ thus prevents the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

Since the energy stored in the capacitor in the half-bridge circuit 1110 is limited, the voltage value of the primary winding voltage V ₁₁ generated on the primary winding 1111 after discharge is small. At this time, the primary winding voltage V ₁₁ generated on the primary winding 1111 is smaller than the secondary winding voltage V ₁₂ on the secondary winding 1113, which will not cause the output voltage V ₂ of the DC transformer circuit 111 to increase. Therefore, after the controller 114 controls the capacitor in the half-bridge circuit 1110 to discharge, the primary winding voltage V ₁₁ generated on the primary winding 1111 is only used to increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output voltage V ₅ of the power circuit 113 , as shown in the F2 direction in Figure 7. Therefore, the controller 114 and the power module 111 in which it is located can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V ₂ of the DC conversion circuit 111. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

Moreover, the controller 114 provided in the embodiment of the present application controls the discharge of the capacitor in the DC conversion circuit 111 without introducing noise from the input power supply 13, and can prevent the noise from affecting the DC conversion circuit 111, the power module 11 where it is located, and the electronics. Electromagnetic compatibility of device 10. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

In an embodiment of the present application, after the capacitor in the half-bridge circuit 1110 of the DC conversion circuit 111 starts to discharge, the controller 114 can also determine the value of the capacitance voltage V _c of the capacitor in the half-bridge circuit 1110 and the auxiliary winding circuit. The voltage value of the output voltage V ₄ of the power supply circuit 112 or the voltage value of the output voltage V ₅ of the power supply circuit 113 controls the capacitor in the half-bridge circuit 1110 to stop discharging.

In one embodiment, the controller 114 controls the auxiliary power transistor of the half-bridge circuit 1110 to turn off, and the discharge loop formed by the primary winding 1111, the capacitor of the half-bridge circuit 1110, and the auxiliary power transistor is disconnected. Accordingly, the capacitor in the half-bridge circuit 1110 stops discharging.

In one embodiment, the DC conversion circuit 111 includes an AHB conversion circuit, and the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110 to stop discharging. In one embodiment, the DC conversion circuit 111 includes an ACF conversion circuit, and the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110 to stop discharging. In one embodiment, the half-bridge circuit 1110 of the DC conversion circuit 111 may further include multiple capacitors, and the controller 114 controls the multiple capacitors in the half-bridge circuit 1110 to stop discharging.

In the first embodiment, at time t ₄ after time t ₃ , the capacitance voltage V _c of the capacitor in the half-bridge circuit 1110 drops to less than or equal to the preset capacitance voltage value V _C3 . In one embodiment, the controller 114 determines that the capacitor voltage V _c of the capacitor in the half-bridge circuit 1110 drops to less than or equal to the preset capacitor voltage value V _C3 , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. In one embodiment, the preset capacitor voltage value V _C3 may be greater than or equal to the voltage value V _C1 of the capacitor voltage of the capacitor in the half-bridge circuit 1110 when the DC conversion circuit 111 operates in the continuous operating state. That is, the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the capacitance voltage V _c of the capacitor in the half-bridge circuit 1110 and the preset capacitor voltage value V _C3 . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, thereby preventing the capacitor voltage from being too low and affecting the DC conversion circuit 111 to resume continuous operation, further improving the stability of the power module 11 and the electronic device 10 in which it is located.

In the second embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V ₄₂ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V ₄₂ , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. The voltage value V ₄₂ is recorded as the fourth preset value, and the voltage value V ₄₂ may be the highest input voltage of the power circuit 113 . The voltage value V ₄₂ is greater than the rated input voltage V ₄₀ of the power circuit 113 and less than the overvoltage protection voltage of the power circuit 113 . That is, the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the fourth preset value V ₄₂ . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, which can prevent the output voltage _V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114 and its The stability of the power module 11 and the electronic device 10 where it is located.

In the third embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₅ of the power circuit 113 increases to a value greater than or equal to the fifth preset value V ₅₃ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is greater than or equal to the fifth preset value V ₅₃ , and the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. The voltage value V ₅₃ is recorded as the fifth preset value. The voltage value V ₅₃ is greater than the rated input voltage V ₅₀ of the controller 114 and less than the overvoltage protection voltage of the controller 114 . That is, the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the fifth preset value V ₅₃ . Therefore, the controller 114 can control the capacitor in the half-bridge circuit 1110 to stop discharging, thereby preventing the output voltage _V4 of the power circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and the power module where it is located. 11. Stability of the electronic device 10.

After time _t4 , after the capacitor in the half-bridge circuit 1110 stops discharging, the voltage value of the capacitor voltage _Vc stops decreasing. Correspondingly, the voltage value of the primary winding voltage V ₁₁ decreases, causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

In one embodiment of the present application, after time t ₄ , when the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V ₄₁ , or the output voltage V ₅ of the power supply circuit 113 When the voltage value drops to less than or equal to the third preset value V ₅₂ , the controller 114 can control the capacitor of the half-bridge circuit 1110 to discharge again. The specific process is as described in the above embodiment and will not be described again. That is, the controller 114 can control the capacitor of the half-bridge circuit 1110 to discharge again based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ . Alternatively, the controller 114 may control the capacitor of the half-bridge circuit 1110 to discharge again based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In an embodiment of the present application, after the capacitor in the half-bridge circuit 1110 starts to discharge or stops discharging, the controller 114 will also control the operation of the DC conversion circuit 111 according to the voltage value of the output voltage V ₂ of the DC conversion circuit 111 The status switches from suspended working status to continuous working status. After time t ₂ , the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state, and accordingly the voltage value of the output voltage V ₂ of the DC conversion circuit 111 decreases. In one embodiment, after the capacitor in the half-bridge circuit 1110 starts to discharge and before it stops discharging, the voltage value of the output voltage V ₂ of the DC conversion circuit 111 drops to less than or equal to the rated voltage V ₂₀ , and the controller 114 controls the DC The operating state of the conversion circuit 111 switches from the suspended operating state to the continuous operating state. In one embodiment, after the capacitor in the half-bridge circuit 1110 stops discharging and the voltage value of the output voltage V ₂ of the DC conversion circuit 111 drops to less than or equal to the rated voltage V ₂₀ , the controller 114 controls the DC conversion circuit 111 The running state switches from the suspended working state to the continuous working state.

At time t ₅ after time t ₃ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 drops to less than or equal to the rated output voltage V ₂₀ . The controller 114 determines that the voltage value of the output voltage V ₂ of the DC conversion circuit 111 drops to less than or equal to the rated output voltage V ₂₀ , and controls the operating state of the DC conversion circuit 111 to switch from a suspended operating state to a continuous operating state. That is, the controller 114 controls the operation state of the DC conversion circuit 111 to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V ₂ of the DC conversion circuit 111 and the rated output voltage V ₂₀ . That is to say, after time t ₂ and before time t ₅ , the controller 114 controls the DC conversion circuit 111 to operate in a suspended operating state. After time _t5 , the controller 114 controls the DC conversion circuit 111 to operate in a continuous operating state. After time t ₅ , the voltage value of the output voltage V ₂ of the DC conversion circuit 111 increases to the rated output voltage V ₂₀ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to V ₄₀ , and the output voltage V of the power supply circuit 113 The voltage value of ₅ is increased to V ₅₀ .

In some embodiments of the present application, the controller 114 can stop discharging before the capacitor voltage value of the capacitor in the half-bridge circuit 1110 drops to less than V _C1 , so that the operating state of the DC conversion circuit 111 can be changed from the paused state more quickly. The working state is switched to a continuous working state, so the control 114 provided by the embodiment of the present application can improve the performance of the power module 11 and the electronic device 10 where it is located.

Figure 9 is a schematic diagram of an embodiment of the power module provided by this application. The power module 11 shown in FIG. 9 can be applied to the electronic device 10 shown in FIG. 1 or 2 . The power supply module 11 shown in FIG. 9 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power supply circuit 113 and a controller 114. The AHB conversion circuit 111a is used to receive the input voltage V ₁ of the input power supply 13 and provide the output voltage V ₂ to power the load 12 . In addition, the AHB conversion circuit 111a supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112. Among them, the auxiliary winding circuit 112 is coupled with the AHB conversion circuit 111a, and the auxiliary winding voltage V ₃ is generated on the auxiliary winding 1121. The auxiliary winding circuit 112 converts the auxiliary winding voltage V ₃ into an output voltage V ₄ to provide power to the power supply circuit 113 . The power circuit 113 supplies power to the control circuit 114 . The controller 114 is used to control the operating state of the AHB conversion circuit 111a.

Figure 10 is a schematic diagram of an embodiment of the power module provided by this application. As shown in FIG. 10 , the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power circuit 113 and a controller 114. Among them, the AHB conversion circuit 111a in the power module 11 includes a half-bridge circuit 1110a, a transformer 1112a and a rectifier circuit 1114a. Among them, the transformer 1112a includes a primary winding 1111a and a secondary winding 1113a. In addition, the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. The secondary winding 1113a is coupled to the primary winding 1111a, and the auxiliary winding 1121 is coupled to the primary winding 1111a.

The half-bridge circuit 1110a is used to receive the input voltage V ₁ provided by the input power supply 13 and provide the output voltage V ₁₀ to the primary winding 1111a according to the control signal of the controller 114 . The half-bridge circuit 1110a usually includes a main power transistor, an auxiliary power transistor and a resonant capacitor.

The primary winding 1111a of the transformer 1112a is used to receive the output voltage V ₁₀ of the half-bridge circuit 1110a and generate the primary winding voltage V ₁₁ . The secondary winding 1113a of the transformer 1112a is coupled with the primary winding 1111a of the transformer 1112a, and the secondary winding voltage V ₃ is generated on the secondary winding 1113a.

The rectifier circuit 1114a is used to receive the secondary winding voltage V ₃ on the secondary winding 1113a and convert it into an output voltage V ₂ .

The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 . The auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111a of the transformer 1112a. The primary winding voltage V ₁₁ on the primary winding 1112a is coupled to generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121. After the auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 112 , the output voltage V ₄ is provided to the power supply circuit 113 . Among them, the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122.

The power circuit 113 is used to power the controller 114 . The power supply circuit 113 receives the output voltage V ₄ of the auxiliary winding circuit 112 and provides the output voltage V ₅ to the controller 114 . That is, the AHB conversion circuit 111a supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112a. In some embodiments, power circuit 113 includes a voltage stabilizing circuit.

The controller 114 is used to control the operating state of the AHB conversion circuit 111a. The controller 114 is also used to detect the output voltage V ₂ of the AHB conversion circuit 111a, the output voltage V ₄ of the auxiliary winding circuit 112, the output voltage V ₅ of the power supply circuit 113, or the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1110a. voltage value and other changes in multiple voltage values. The controller 114 is also used to control the operating state of the AHB conversion circuit 111a according to changes in the one or more voltage values.

In one embodiment, the control 114 sends the control signal G to control the operating state of the half-bridge circuit 1110a in the AHB conversion circuit 111a, thereby controlling the operating state of the AHB conversion circuit 111a. For example, the operating states of the AHB conversion circuit 111a generally include a continuous operating state and a suspended operating state. The continuous working state can also be called the normal working state, the controller's normal wave sending state, etc. The suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.

In this embodiment of the present application, the controller 114 may send a control signal G to control the turn-on and turn-off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a. The controller 114 adjusts the frequency or duty cycle of the control signal G to control the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a, thereby adjusting the output voltage V ₁₀ of the half-bridge circuit 1110a accordingly. . The output voltage V ₁₀ of the half-bridge circuit 1110a will cause the primary winding voltage V ₁₁ to change. Correspondingly, changes in the primary winding voltage V ₁₁ can cause changes in the secondary winding voltage V ₁₂ and the auxiliary winding voltage V ₃ . Correspondingly, changes in the secondary winding voltage V ₁₂ may cause the output voltage V ₂ of the AHB conversion circuit 111a to change. Accordingly, changes in the auxiliary winding voltage V ₃ may cause the output voltage V ₄ of the auxiliary winding circuit 112 to change. Correspondingly, the output voltage V ₄ of the auxiliary winding circuit 112 may cause a change in the output voltage V ₅ of the power supply circuit 113 .

As shown in the F1 direction in Figure 10, the AHB conversion circuit 111a can provide the output voltage _V2 to power the load 12. Among them, the input voltage V ₁ is converted into the output voltage V ₂ through the half-bridge circuit 1110a, the primary winding 1111a, the secondary winding 1113a and the rectifier circuit 1114a in the AHB conversion circuit 111a.

As shown in the F2 direction in FIG. 10 , the AHB conversion circuit 111a can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 . After the input voltage V ₁ is processed by the half-bridge circuit 1110a in the AHB conversion circuit 111a, the primary winding voltage V ₁₁ can be generated in the primary winding 1111a. Correspondingly, the primary winding voltage V ₁₁ can generate an auxiliary winding voltage V ₃ on the auxiliary winding 1121 of the transformer 1112a. The auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 1121 to provide an output voltage V ₄ to power the power supply circuit 113 of the controller 114 .

Figure 11 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes in detail the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIGS. 10 and 11 .

Before time t ₁ , the load level L of the load 12 is the normal load L ₁ . The controller 114 controls the AHB conversion circuit 111a to run in a continuous operating state. The controller 114 controls the output voltage V ₂ of the AHB conversion circuit 111a to be the rated voltage value. Output voltage V ₂₀ . The voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value of the output voltage V ₅ of the power supply circuit 113 is V ₅₀ . The voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1111a is V _Cr1 . V _Cr1 is the capacitance voltage of the resonant capacitor C _r when the AHB conversion circuit 111a operates in a continuous operating state.

At time t ₁ , the load level of load 12 drops from normal load L ₁ to light load L ₂ . Correspondingly, after time t ₁ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a increases to greater than the rated output voltage V ₂₀ .

In one embodiment, when the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a is greater than the rated output voltage V ₂₀ , the controller 114 can control the AHB conversion circuit 111a to operate in a continuous operating state. Furthermore, the controller controls the AHB conversion circuit 111a to reduce the voltage value of the output voltage _V2 . That is, the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a and the rated output voltage V ₂₀ . The controller 114 controls the AHB conversion circuit 111a Reduce the voltage value of the output voltage _V2 . Specifically, the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a, so that the voltage value of the primary winding voltage V ₁₁ decreases. In one embodiment, the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor. In one implementation, the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor. In another embodiment, when the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a is greater than the rated voltage V ₂₀ , the controller 114 can control the AHB conversion circuit 111a to run in a suspended working state, and can also reduce the output voltage V ₂ Voltage value. However, the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a, and the voltage value of the output voltage _V2 of the AHB conversion circuit 111a will continue to increase after time _t1 .

At the same time, after time t ₁ , the drop of the load level L causes the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a to be higher than the rated voltage V ₂₀ . The primary winding voltage V ₁₁ charges the resonant capacitor C _r in the half-bridge circuit 1110a, and the voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1110a increases from V _Cr1 to V _Cr2 . V _Cr2 is the maximum charging voltage of the resonant capacitor C _r in the half-bridge circuit 1110a.

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a increases to the first preset value V ₂₁ . The controller 114 determines that the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a is greater than or equal to the first preset value V ₂₁ , and the controller 114 controls the AHB conversion circuit 111a to suspend operation. That is, the controller 114 controls the AHB conversion circuit 111a to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a and the first preset value V ₂₁ . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a to turn off. In this embodiment of the present application, the first preset value V ₂₁ may be the peak voltage of the AHB conversion circuit 111a. The peak voltage of the AHB conversion circuit 111a is greater than the rated voltage V ₂₀ and less than the overvoltage protection voltage of the AHB conversion circuit 111a.

After time t ₂ , the controller 114 controls the AHB conversion circuit 111a to run in a suspended working state. Correspondingly, the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 a in the AHB conversion circuit 111 a decreases, causing the secondary winding voltage V ₁₂ to decrease, and causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a decreases, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

At time _t3 after time _t2 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 drops to less than or equal to the second preset value _V41 , or the voltage value of the output voltage _V5 of the power supply circuit 113 drops to less than Or equal to the third preset value V ₅₂ . At this time, the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge.

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the second preset value V ₄₁ , and the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge. That is, the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ .

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ , and the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge. That is, the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110a to be turned on, so that the resonant capacitor C _r in the half-bridge circuit 1110a is discharged. The primary winding 1111a, the resonant capacitor C _r of the half-bridge circuit 1110a, and the auxiliary power transistor of the half-bridge circuit 1110a may form a discharge circuit. Correspondingly, the resonant capacitor C _r of the half-bridge circuit 1110a is discharged, which can generate the primary winding voltage V ₁₁ on the primary winding 1111a.

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110a to be turned on periodically, so that the resonant capacitor C _r in the half-bridge circuit 1110a is discharged. When the auxiliary power transistor of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C _r of the half-bridge circuit 1110a, and the auxiliary power transistor of the half-bridge circuit 1110a can form a discharge loop. Correspondingly, the auxiliary power transistor of the half-bridge circuit 1110a is turned on periodically, which can cause the resonant capacitor C _r in the half-bridge circuit 1110a to be discharged periodically.

After time _t3 , the voltage value of the capacitance voltage V _Cr of the resonant capacitor _Cr in the half-bridge circuit 1110a decreases. The resonant capacitor C _r in the half-bridge circuit 1110a is discharged, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111a to increase. Correspondingly, an increase in the voltage value of the primary winding voltage V ₁₁ will cause an increase in the voltage value of the auxiliary winding voltage V ₃ . Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases. Therefore, in a scenario where the load level of the load 12 changes, the voltage value of the output voltage V ₅ of the power circuit 113 will not drop below the under-voltage protection voltage V ₅₁ of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.

The controller 114 provided in the embodiment of the present application controls the discharge of the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a, so that the voltage value of the output voltage V ₅ of the power supply circuit 113 is higher than the undervoltage protection voltage of the controller 114 V ₅₁ , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

Since the energy stored in the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a is limited, the voltage value of the primary winding voltage V ₁₁ generated on the primary winding 1111a after discharge is small. At this time, the primary winding voltage V ₁₁ generated on the primary winding 1111a is smaller than the secondary winding voltage V ₁₂ on the secondary winding 1113, which will not cause the output voltage V ₂ of the AHB conversion circuit 111a to increase. Therefore, after the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge, the primary winding voltage V ₁₁ generated on the primary winding 1111a is only used to increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output of the power supply circuit 113 Voltage V ₅ , as shown in the F2 direction in Figure 10. Therefore, the controller 114 and the power module 111 provided by the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V ₂ of the AHB conversion circuit 111a. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

Moreover, the controller 114 provided in the embodiment of the present application controls the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a without introducing noise from the input power supply 13, and can avoid the noise from affecting the AHB conversion circuit 111a and its location. Electromagnetic compatibility of power module 11 and electronic equipment 10 . Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

In an embodiment of the present application, after the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a starts to discharge, the controller 114 can also adjust the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1110a. The value of the output voltage V ₄ of the auxiliary winding circuit 112 or the voltage value of the output voltage V ₅ of the power supply circuit 113 controls the resonant capacitor C _r in the half-bridge circuit 1110a to stop discharging. In one embodiment, the controller 114 controls the auxiliary power tube in the half-bridge circuit 1110a to turn off, and the discharge loop formed by the primary winding 1111a, the resonant capacitor C _r of the half-bridge circuit 1110a, and the auxiliary power tube of the half-bridge circuit 1110a is turned off. open. Correspondingly, the resonant capacitor C _r of the half-bridge circuit 1110a stops discharging.

In the first embodiment, at time _t4 after time _t3 , the capacitance voltage V _Cr of the resonant capacitor _Cr of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V _Cr3 . In one embodiment, the controller 114 determines that the capacitance voltage V _Cr of the resonant capacitor C _r of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V _Cr3 , and the controller 114 controls the resonant capacitance C of the half-bridge circuit 1110a _rStop discharging. In one embodiment, the preset capacitance voltage value V _Cr3 may be greater than or equal to the voltage value V _Cr1 of the capacitance voltage of the resonant capacitance _Cr of the half-bridge circuit 1110a when the AHB conversion circuit 111a operates in the continuous operating state. That is, the controller 114 controls the resonant capacitor Cr of the half-bridge circuit 1110a to stop discharging based on the comparison result between the capacitance voltage V _Cr of the resonant capacitor _C _r of the half-bridge circuit 1110a and the preset capacitor voltage value V _Cr3 . Therefore, the controller 114 can stop discharging through the resonant capacitor C _r of the half-bridge circuit 1110a, and can prevent the capacitance voltage V _Cr of the resonant capacitor C _r from being too low and affecting the restoration of the continuous working state of the AHB conversion circuit 111a, further improving the efficiency of the power module 11 and the stability of the electronic device 10 in which it is located.

In the second embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V ₄₂ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V ₄₂ , and the controller 114 controls the resonant capacitor _Cr of the half-bridge circuit 1110a to stop discharging. That is, the controller 114 controls the resonant capacitor C _r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the fourth preset value V ₄₂ . Therefore, the controller 114 can stop discharging through the resonant capacitor C _r of the half-bridge circuit 1110a, and can prevent the output voltage _V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114. and the stability of the power module 11 and the electronic device 10 where it is located.

In the third embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₅ of the power circuit 113 increases to a value greater than or equal to the fifth preset value V ₅₃ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is greater than or equal to the fifth preset value V ₅₃ , and the controller 114 controls the resonant capacitor C _r of the half-bridge circuit 1110a to stop discharging. That is, the controller 114 controls the resonant capacitor C _r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the fifth preset value V ₅₃ . Therefore, the controller 114 can stop discharging by controlling the resonant capacitor C _r of the half-bridge circuit 1110a to prevent the output voltage _V4 of the power supply circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and its power supply. Stability of module 11 and electronic device 10.

After time _t4 , after the resonant capacitor Cr of the half-bridge circuit 1110a stops discharging, the voltage value of the capacitance voltage V _Cr of the resonant capacitor _Cr stops decreasing. Correspondingly, the voltage value of the primary winding voltage V ₁₁ decreases, causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

In one embodiment of the present application, after time t ₄ , when the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V ₄₁ , or the output voltage V ₅ of the power supply circuit 113 When the voltage value of V drops to less than or equal to the third preset value V ₅₂ , the controller 114 may control the resonant capacitor C _r of the half-bridge circuit 1110 a to discharge again. The specific process is as described in the above embodiment and will not be described again. That is, the controller 114 can control the resonant capacitor C _r of the half-bridge circuit 1110a to discharge again based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ . Alternatively, the controller 114 may control the resonant capacitor C _r of the half-bridge circuit 1110a to discharge again based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In an embodiment of the present application, after the resonant capacitor C _r of the half-bridge circuit 1110a starts to discharge or stops discharging, the controller 114 will also control the AHB conversion circuit 111a according to the voltage value of the output voltage _V2 of the AHB conversion circuit 111a. The operating status switches from suspended working status to continuous working status. After time t ₂ , the controller 114 controls the AHB conversion circuit 111 a to operate in a suspended operating state, and accordingly the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a decreases. In one embodiment, after the resonant capacitor C _r of the half-bridge circuit 1110a starts to discharge and before it stops discharging, the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a drops to less than or equal to the rated voltage V ₂₀ , the controller 114 The operating state of the AHB conversion circuit 111a is controlled to switch from the suspended operating state to the continuous operating state. In one embodiment, after the resonant capacitor C _r of the half-bridge circuit 1110a stops discharging, the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a drops to less than or equal to the rated voltage V ₂₀ , and the controller 114 controls the AHB conversion circuit The operating status of 111a switches from the suspended working status to the continuous working status.

At time t ₅ after time t ₃ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a drops to less than or equal to the rated voltage V ₂₀ . The controller 114 determines that the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a drops to less than or equal to the rated voltage V ₂₀ , and controls the operating state of the AHB conversion circuit 111a to switch from the suspended operating state to the continuous operating state. That is, the controller 114 controls the operation state of the AHB conversion circuit 111a to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a and the rated voltage V ₂₀ . After time t ₅ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a returns to the rated voltage V ₂₀ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 returns to V ₄₀ , and the output voltage V ₅ of the power supply circuit 113 The voltage value returns to V ₅₀ .

Figure 12 is a schematic diagram of an embodiment of the power module provided by this application. FIG. 12 shows a schematic diagram of some circuits in the power module 11 shown in FIG. 10 . As shown in FIG. 12 , the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power circuit 113 and a controller 114. Among them, the AHB conversion circuit 111a includes a half-bridge circuit 1110a, a transformer 1112a and a rectifier circuit 1114a. Among them, the transformer 1112a includes a primary winding 1111a and a secondary winding 1113a. In addition, the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. The secondary winding 1113a is coupled to the primary winding 1111a, and the auxiliary winding 1121 is coupled to the primary winding 1111a.

The half-bridge circuit 1110a includes a main power transistor Q _L , an auxiliary power transistor Q _H and a resonant capacitor C _r . The main power tube _QL , the auxiliary power tube _QH and the resonant capacitor _Cr form an asymmetric half-bridge topology. Specifically, the first end of the resonant capacitor C _r is connected to the opposite end of the primary winding 1111a, and the second end of the resonant capacitor C _r is connected to the drain of the auxiliary power tube Q _H. The source of the auxiliary power tube _QH is connected to the same terminal of the primary winding 1111a and the drain of the main power tube _QL . The source of the main power tube Q _L is grounded. In one embodiment, the gate of the main power transistor Q _L is used to receive the second control signal _GH from the controller 114 . The gate of the auxiliary power transistor Q _H is used to receive the first control signal _GL from the controller 114 .

The rectifier circuit 1114a includes a capacitor C ₁ and a diode D ₂ . The anode of diode D ₂ is connected to the same terminal of secondary winding 1113a. The two ends of the capacitor C ₁ are respectively connected to the cathode of the diode D ₂ and the opposite terminal of the secondary winding 1113a.

The auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectifier module 1122. Rectification module 1122 may include diode D ₁ . Among them, the anode of the diode D ₁ is connected to the same terminal of the auxiliary winding 1121 , and the cathode of the diode D ₁ and the different terminal of the auxiliary winding 1121 are connected to the power circuit 113 .

The power circuit 113 may include a boost circuit. In one embodiment, the power circuit 113 may also be a buck (BUCK) circuit, a buck-boost (BUCK-BOOST) circuit, etc. In one embodiment, the power circuit 113 may also be a voltage stabilizing circuit such as a low dropout linear voltage regulator circuit (low dropout regulator, LDO).

The controller 114 includes a detection unit 1141 and a driving unit 1142. In some embodiments, when the driving unit 1142 is a chip, the power circuit 113 may be connected to the power supply pin of the driving unit 1142 . For example, the power supply pin may be the pin labeled " _Vdd " shown in Figure 12.

The detection unit 1141 is used to detect the output voltage V ₂ of the AHB conversion circuit 111a, the voltage value of the output voltage _V4 of the auxiliary winding circuit 112, the voltage value of the output voltage _V5 of the power supply circuit 113, or the half-bridge circuit 1110a of the AHB conversion circuit 111a. Changes in various voltage values among the voltage values of the capacitor voltage V _Cr of the resonant capacitor C _r . The driving circuit 1142 is used to control the operating state of the AHB conversion circuit 111a according to the change of one or more voltage values.

For example, the detection unit 1141 can detect the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a by connecting point A of the output end of the secondary winding circuit 1114 a in FIG. 12 . The detection unit 1141 can detect the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 by connecting point B of the output end of the auxiliary winding circuit 112 in FIG. 12 . The detection unit 1141 can detect the voltage value of the output voltage V ₅ of the power supply circuit 113 by connecting point C of the output end of the power supply circuit 113 in FIG. 12 . The detection unit 1141 can detect the voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r by connecting points D on either side of the resonant capacitor C _r in FIG. 12 .

The driving unit 1142 is used to control the operating state of the AHB conversion circuit 111a. Among them, the driving unit 1142 controls the on and off of the main power transistor Q _L and the auxiliary power transistor Q _H by sending the control signal G _L /G _H , thereby controlling the operating state of the AHB conversion circuit 111a. In some embodiments, when the driving unit 1142 is a chip, the driving unit 1142 shown in FIG. 12 can send the control signal GH through its pin labeled " _GH ", and can send the control signal _GH through its pin labeled " _GL " The pin sends the control signal _GL . The pin numbers in Figure 12 are only examples. In actual applications, other numbered pins of the driving unit 1142 can also be used to implement the functions of the pins shown in Figure 12 .

The driving unit 1142 controls the main power tube _QL to be turned on or off by sending a first control signal _GL to the main power tube _QL . The driving unit 1142 controls the auxiliary power tube _QH to be turned on or off by sending the second control signal _GH to the auxiliary power tube _QH . In this embodiment of the present application, the first control signal _GL and the second control signal _GH sent by the controller 114 may include high-level signals or low-level signals. In one embodiment, the main power transistor _QL is turned on according to the first control signal _GL , and the auxiliary power transistor _QH is turned on according to the second control signal _GH . In one embodiment, the main power transistor _QL is turned off according to the first control signal _GL , and the auxiliary power transistor _QH is turned off according to the second control signal _GH .

Figure 13 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops.

Before time t1, the load level of load 12 is normal load L ₁ . The controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state, and controls the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a to be the rated voltage V ₂₀ . At this time, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value of the output voltage V ₅ of the power supply circuit 113 is V ₅₀ . The voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1111a is V _Cr1 .

Figure 14 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application. As shown in Figure 14, each of the control signals G ₁ , G ₂ , G ₃ ... sent by the controller 114 includes a first control signal GL sent to the main power tube Q _L or a first control signal _GL sent to the auxiliary power tube Q _H Second control signal G _H . The controller 114 controls the main power transistor _QL and the auxiliary power transistor _QH to periodically turn on and off alternately, and the half-bridge circuit 1110a can generate the primary winding voltage V ₁₁ in the primary winding 1111a. After coupling, the primary winding voltage V ₁₁ on the primary winding 1111a can generate the secondary winding voltage V ₁₂ on the secondary winding 1113a, and can generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121. Correspondingly, the rectifier circuit 1114a provides the output voltage V ₂ to the load 12 , the auxiliary winding circuit 112 provides the output voltage V ₄ to the power supply circuit 113 , and the output voltage V ₅ of the power supply circuit 113 to the controller 115 is V ₅₀ . Since the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a to the load 12 is stabilized at the rated voltage V ₂₀ , the voltage value V _Cr of the resonant capacitor C _r in the half-bridge circuit 1110 a is stabilized at V _Cr1 .

At time t1, the load level of load 12 drops from normal load L ₁ to light load L ₂ . After time t1, the voltage value of the output voltage _V2 of the AHB conversion circuit 111a increases to greater than the rated voltage _V20 .

In one embodiment, the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a and the rated voltage V ₂₀ . The controller 114 controls the AHB conversion circuit 111a reduces the voltage value of the output voltage _V2 .

Specifically, the detection unit 1141 of the controller 114 detects the output voltage V ₂ of the AHB conversion circuit 111 a and determines that the output voltage V ₂ of the AHB conversion circuit 111 a is greater than the rated voltage V ₂₀ . Correspondingly, the controller 114 controls the AHB conversion circuit 111a to operate in a continuous working state. The controller 114 reduces the transmission frequency of the first control signal _GL and the second control signal _GH , or reduces the transmission frequency of the first control signal _GL and the second control signal GH. Duty cycle of signal G _H. As shown in FIG. 13 , the frequencies of the control signals G ₄ , G ₅ , and G ₆ sent by the controller 114 after time t ₁ are smaller than the frequencies of the control signals G ₁ , G ₂ , and G ₃ periodically sent before time t ₁ . Correspondingly, the frequency at which the main power transistor _QL and the auxiliary power transistor _QH are turned on and off is reduced, causing the voltage value of the output voltage _V2 of the AHB conversion circuit 111a to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases. However, the above method may not effectively reduce the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a, and the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a will continue to increase.

After time t ₁ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a is higher than the rated voltage V ₂₀ . At this time, the primary winding voltage V ₁₁ charges the resonant capacitor C _r in the half-bridge circuit 1110a, and the voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r in the half-bridge circuit 1110a increases from V _Cr1 to V _Cr2 .

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a increases to greater than or equal to the first preset value V ₂₁ . The controller 114 controls the AHB conversion circuit 111a to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a and the first preset value V ₂₁ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a and determines that the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a is greater than or equal to the first preset value V ₂₁ . Correspondingly, the driving unit 1142 of the controller 114 stops sending the first control signal _GL and the second control signal _GH , thereby controlling the AHB conversion circuit 111a to operate in a suspended working state. Correspondingly, the AHB conversion circuit 111a does not process the input voltage V ₁ it receives, and the output voltage V ₂ of the AHB conversion circuit 111a decreases.

At time _t3 after time _t2 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 drops below the second preset value _V41 , or the voltage value of the output voltage _V5 of the power supply circuit 113 drops below The third preset value V ₅₂ . At this time, the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge.

In one embodiment, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the second preset value. _V41 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn on the auxiliary power transistor _QH . At this time, the resonant capacitor C _r of the half-bridge circuit 1110a, the primary winding 1111a and the power transistor _QH of the half-bridge circuit 1110a form a discharge loop, and the resonant capacitor C _r of the half-bridge circuit 1110a begins to discharge.

In one embodiment, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₅ of the power supply circuit 113 and determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn on the auxiliary power transistor _QH . At this time, the resonant capacitor C _r of the half-bridge circuit 1110a, the primary winding 1111a and the power transistor _QH of the half-bridge circuit 1110a form a discharge loop, and the resonant capacitor C _r of the half-bridge circuit 1110a begins to discharge.

After time _t3 , the voltage value of the capacitance voltage V _Cr of the resonant capacitor _Cr in the half-bridge circuit 1110a decreases. The resonant capacitor C _r in the half-bridge circuit 1110a is discharged, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111a to increase. Correspondingly, the voltage value of the auxiliary winding voltage V ₃ increases, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases. Therefore, in a scenario where the load level of the load 12 changes, the voltage value of the output voltage V ₅ of the power circuit 113 will not drop below the under-voltage protection voltage V ₅₁ of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.

Since the energy stored in the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a is limited, the voltage value of the primary winding voltage V ₁₁ generated on the primary winding 1111a after discharge is small. At this time, the primary winding voltage V ₁₁ generated on the primary winding 1111a is smaller than the secondary winding voltage V ₁₂ on the secondary winding 1113, which will not cause the output voltage V ₂ of the AHB conversion circuit 111a to increase. Therefore, after the controller 114 controls the resonant capacitor C _r in the half-bridge circuit 1110a to discharge, the primary winding voltage V ₁₁ generated on the primary winding 1111a is only used to increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output of the power supply circuit 113 Voltage V ₅ . Therefore, the controller 114 and the power module 111 provided by the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V ₂ of the AHB conversion circuit 111a. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

Moreover, the controller 114 provided in the embodiment of the present application controls the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a, so as not to introduce noise from the input power supply 13 and avoid affecting the AHB conversion circuit 111a and its power supply. Electromagnetic compatibility of module 11 and electronic device 10. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

In an embodiment of the present application, the controller 114 can also control the resonant capacitor C _r in the half-bridge circuit 1110a of the AHB conversion circuit 111a to stop discharging.

In the first embodiment, at time _t4 after time _t3 , the capacitance voltage V _Cr of the resonant capacitor _Cr of the half-bridge circuit 1110a drops to less than or equal to the preset capacitance voltage value V _Cr3 . In one embodiment, the preset capacitance voltage value V _Cr3 may be greater than or equal to the voltage value V _Cr1 of the capacitance voltage of the resonant capacitance _Cr of the half-bridge circuit 1110a when the AHB conversion circuit 111a operates in the continuous operating state. The controller 114 controls the resonant capacitor Cr of the half-bridge circuit 1110a to stop discharging based on the comparison result between the capacitance voltage V _Cr of the resonant capacitor _C _r of the half-bridge circuit 1110a and the preset capacitor voltage value V _Cr3 . Specifically, the detection unit 1141 of the controller 114 detects the capacitance voltage V _Cr of the resonant capacitor C _r of the half-bridge circuit 1110a and determines that the capacitance voltage V _Cr of the resonant capacitor C _r of the half-bridge circuit 1110a is less than or equal to the preset capacitance voltage value V _Cr3 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the resonant capacitor C _r of the half-bridge circuit 1110a, the primary winding 1111a, and the power transistor _QH of the half-bridge circuit 1110a is disconnected, and the resonant capacitor C _r of the half-bridge circuit 1110a stops discharging.

Therefore, the controller 114 can stop discharging through the resonant capacitor C _r of the half-bridge circuit 1110a, and can prevent the capacitance voltage V _Cr of the resonant capacitor C _r from being too low and affecting the restoration of the continuous working state of the AHB conversion circuit 111a, further improving the efficiency of the power module 11 and the stability of the electronic device 10 in which it is located.

In the second embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V ₄₂ . The controller 114 controls the resonant capacitor C _r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the fourth preset value V ₄₂ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the preset capacitor voltage value V _Cr3 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the resonant capacitor C _r of the half-bridge circuit 1110a, the primary winding 1111a, and the power transistor _QH of the half-bridge circuit 1110a is disconnected, and the resonant capacitor C _r of the half-bridge circuit 1110a stops discharging.

Therefore, the controller 114 can stop discharging through the resonant capacitor C _r of the half-bridge circuit 1110a, and can prevent the output voltage _V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller 114. and the stability of the power module 11 and the electronic device 10 where it is located.

In the third embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₅ of the power circuit 113 is increased to greater than or equal to the fifth preset value V ₅₃ . The controller 114 controls the resonant capacitor C _r of the half-bridge circuit 1110a to stop discharging based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the fifth preset value V ₅₃ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₅ of the power supply circuit 113 and determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is greater than or equal to the fifth preset value V ₅₃ . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the resonant capacitor C _r of the half-bridge circuit 1110a, the primary winding 1111a, and the power transistor _QH of the half-bridge circuit 1110a is disconnected, and the resonant capacitor C _r of the half-bridge circuit 1110a stops discharging.

Therefore, the controller 114 can stop discharging by controlling the resonant capacitor C _r of the half-bridge circuit 1110a to prevent the output voltage _V4 of the power supply circuit 113 from being too high and damaging the controller 114, further improving the efficiency of the controller 114 and its power supply. Stability of module 11 and electronic device 10.

After time _t4 , after the resonant capacitor _Cr of the half-bridge circuit 1110a stops discharging, the voltage value of the capacitance voltage V _Cr of the resonant capacitor _Cr stops decreasing. Correspondingly, the voltage value of the primary winding voltage V ₁₁ decreases, causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

In one embodiment of the present application, after time t ₄ , when the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V ₄₁ , or the output voltage V ₅ of the power supply circuit 113 When the voltage value of V drops to less than or equal to the third preset value V ₅₂ , the controller 114 may control the resonant capacitor C _r of the half-bridge circuit 1110 a to discharge again. The specific process is as described in the above embodiment and will not be described again.

At time t ₅ after time t ₃ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a drops to less than or equal to the rated output voltage V ₂₀ . The controller 114 controls the operating state of the AHB converting circuit 111a to switch from the suspended operating state to the continuous operating state based on the comparison result between the voltage value of the output voltage _V2 of the AHB converting circuit 111a and the rated output voltage _V20 . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a and determines that the voltage value of the output voltage V ₂ of the AHB conversion circuit 111 a is less than or equal to the rated output voltage V ₂₀ . The driving unit 1142 of the controller 114 periodically sends the first control signal _GL and the second control signal _GH , and controls the main power tube _QL and the auxiliary power tube _QH to be turned on and off periodically, so that the AHB conversion circuit 111a Restore continuous working status. At this time, the first control signal _GL and the second control signal _GH sent by the controller 114 are recorded as G ₇ , G ₈ , G ₉ . . . The specific implementation of each control signal G ₇ , G ₈ , G ₉ ... is the same as shown in Figure 14 and will not be described again. For another example, the periods of the control signals G ₇ , G ₈ , G ₉ ... may be the same as the periods of the control signals G ₁ , G ₂ , G ₃ ..., or the periods of the control signals G ₄ , G ₅ , G ₆ ... wait. After time t ₅ , the voltage value of the output voltage V ₂ of the AHB conversion circuit 111a returns to the rated output voltage V ₂₀ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 returns to V ₄₀ , and the output voltage V of the power supply circuit 113 The voltage value of ₅ returns to V ₅₀ .

Figure 15 is a schematic diagram of an embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit. The difference between Figure 15 and Figure 13 is that the controller 114 controls the resonant capacitor C _r of the primary winding circuit 1111a in the AHB conversion circuit 111a to periodically discharge. Description will be given below with reference to Figure 11 and Figure 15 .

At time t ₃ , the controller 114 controls the auxiliary power transistor Q _H in the half-bridge circuit 1110a to periodically turn on, so that the resonant capacitor C _r in the half-bridge circuit 1110a discharges. Specifically, the controller 114 does not send the first control signal _GL to the main power tube _QL , so that the main power tube _QL is turned off. Furthermore, the controller 114 periodically sends the second control signal _GH to the auxiliary power transistor _QH , so that the auxiliary power transistor _QH is periodically turned on. When the auxiliary power transistor _QH of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C _r of the half-bridge circuit 1110a, and the auxiliary power transistor _QH of the half-bridge circuit 1110a can form a discharge loop. Correspondingly, the auxiliary power transistor Q _H of the half-bridge circuit 1110a is turned on periodically, which can cause the resonant capacitor C _r in the half-bridge circuit 1110a to be discharged periodically.

In the embodiment of the present application, the controller 114 controls the period T1 during which the auxiliary power transistor Q _H is turned on periodically, which can be pre-configured, or the controller 114 can be based on the capacitance voltage V _Cr of the current resonant capacitor C _r or the stored value. Electric energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r is higher or more electric energy is stored, the period T1 can be set smaller. In an embodiment, the period T1 may also be the same as the period of the control signals G ₁ , G ₂ , G _{3 .} . . or G ₄ , G ₅ , G ₆ . . . In the embodiment of the present application, the duration for which the controller 114 controls the auxiliary power transistor Q _H to be turned on or off in each cycle may be the same or different.

Figure 16 is a schematic diagram of changes in the capacitance voltage of the resonant capacitor of the AHB conversion circuit provided by this application. As shown in Figure 16, the resonant capacitor C _r is periodically discharged, and the capacitance voltage V _Cr of the resonant capacitor C _r decreases stepwise from V _Cr2 . Between time t ₃ and time t ₄ , the capacitance voltage V _Cr of the resonant capacitor C _r decreases stepwise as the auxiliary power transistor Q _H is periodically turned on. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 also shows a step-like increase, and the voltage value of the output voltage V ₅ of the power supply circuit 113 also shows a step-like increase.

Therefore, the controller 114 controls the resonant capacitor C _r in the AHB conversion circuit 111 a to discharge periodically, which can cause the capacitance voltage V _Cr of the resonant capacitor C _r to decrease in a stepwise manner to avoid falling too fast and affecting the operation of the AHB conversion circuit 111 a. Improved the stability of power module 11. Moreover, the controller 114 controls the resonant capacitor C _r in the AHB conversion circuit 111a to periodically discharge, which can increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output voltage V ₅ of the power supply circuit 113 in a stepwise manner, thus preventing the voltage from increasing too quickly. and damage the circuit components, thereby improving the stability of the power module 11.

Figure 17 is a schematic diagram of another embodiment of the controller provided by the present application controlling the resonant capacitor discharge of the AHB conversion circuit. The difference between Figure 17 and Figure 15 is that the controller 114 controls the auxiliary power tube Q _H and the main power tube Q _L in the primary winding circuit 1111a of the AHB conversion circuit 111a to periodically alternately conduct, so that the resonant capacitor C _r periodically discharges .

At time _t3 , the controller 114 periodically controls the main power tube _QL and the auxiliary power tube _QH to turn on alternately, and controls the auxiliary power tube _QH and the main power tube _QL to not turn on at the same time. Specifically, the controller 114 periodically sends the second control signal _GH to _{the auxiliary power tube QH and the first control signal GL} _to _the main power tube QL in sequence, so that the auxiliary power tube _QH and the main power tube Q _L is turned on in sequence, and the auxiliary power tube Q _H and the main power tube Q _L are not turned on at the same time. When the auxiliary power transistor _QH of the half-bridge circuit 1110a is turned on, the primary winding 1111a, the resonant capacitor C _r of the half-bridge circuit 1110a, and the auxiliary power transistor _QH of the half-bridge circuit 1110a can form a discharge loop. The change of the capacitance voltage V _Cr of the resonant capacitor C _r can be seen in Figure 16.

In one embodiment, in each cycle, the controller 114 controls the auxiliary power transistor _QH to turn on first and the main power transistor _QL to turn on later.

First, the controller 114 controls the auxiliary power transistor _QH to turn on and the main power transistor _QL to turn off. Specifically, the controller 114 sends the second control signal _GH to the auxiliary power tube _QH and does not send the first control signal _GL to the main power tube _QL . Correspondingly, the resonant capacitor C _r , the primary winding a and the auxiliary power tube Q _H form a current loop, and the resonant capacitor C _r is discharged. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases.

Then, the controller 114 controls the auxiliary power transistor _QH to turn off and the main power transistor _QL to turn on. Specifically, the controller 114 does not send the second control signal _GH to the auxiliary power tube _QH and sends the first control signal _GL to the main power tube _QL . At this time, the input voltage V ₁ , primary winding a, and main power tube Q _L form a loop. Correspondingly, the input voltage V ₁ generates the primary winding voltage V ₁₁ on both sides of the primary winding a. The primary winding voltage V ₁₁ is coupled through the transformer 1112a to generate the auxiliary winding voltage V ₃ on the auxiliary winding c. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases.

Therefore, the controller 114 controls the resonant capacitor C _r of the primary side winding circuit 1111 a in the AHB conversion circuit 111 a to periodically discharge, which can cause the capacitance voltage V _Cr of the resonant capacitor C _r to decrease in a stepwise manner to avoid falling too fast and affecting the AHB conversion circuit. 111a operation, thus improving the stability of the power module 111. Furthermore, the controller 114 controls the resonant capacitor C _r of the primary winding circuit 1111a in the AHB conversion circuit 111a to periodically discharge, which can increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output voltage V ₅ of the power supply circuit 113 in a stepwise manner. This avoids damage to circuit components due to excessive lifting, thereby improving the stability of the power module 111.

In one embodiment, in each cycle, the controller 114 can control the main power transistor Q _L to turn on first and the auxiliary power transistor Q _H to turn on later. In the embodiment of the present application, the period T2 during which the controller 114 controls the main power transistor Q _L and the auxiliary power transistor Q _H to periodically conduct alternately may be pre-configured, or may be determined by the controller 114 according to the current resonant capacitance C _r The capacitor voltage V _Cr or stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V _Cr of the resonant capacitor C _r is higher or more electric energy is stored, the period T2 can be set smaller. In one embodiment, the period T2 may be the same as the period of the control signals G ₁ , G ₂ , G ₃ . . . or the period of G ₄ , G ₅ , G ₆ . . . In the embodiment of the present application, in each cycle, the controller 114 controls the conduction time of the main power transistor _QL and the conduction time of the auxiliary power transistor _QH , which may be the same or different. In this embodiment of the present application, the duty ratios of the first control signal _GL and the second control signal _GH sent by the controller 114 may be the same or different.

Figure 18 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided by this application. As shown in Figure 18, the half-bridge circuit 1110a1 includes a main power transistor _QL , an auxiliary power transistor _QH and a resonant capacitor _Cr . The source of the main power tube _QL is connected to the opposite end of the primary winding 1111a and the drain of the auxiliary power tube _QH . The source of the auxiliary power tube Q _H is connected to the first end of the resonant capacitor C _r and grounded. The second terminal of the resonant capacitor C _r is connected to the same terminal of the primary winding 1111a. The half-bridge circuit 1110a1 shown in Figure 18 can replace the half-bridge circuit 1110a in Figure 12. The functions and control logic of the half-bridge circuit 1110a1 are the same as those of the half-bridge circuit 1110a.

Figure 19 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided by this application. As shown in Figure 19, the half-bridge circuit 1110a2 includes a main power transistor _QL , an auxiliary power transistor _QH and a resonant capacitor _Cr . The same terminal of the primary winding 1111a is connected to the drain of the main power transistor _QL and the first terminal of the resonant capacitor C _r . The second end of the resonant capacitor C _r is connected to the source of the auxiliary power tube Q _H. The source of the main power tube Q _L is grounded. The drain of the auxiliary power tube Q _H is connected to ground. The half-bridge circuit 1110a2 shown in Figure 19 can replace the half-bridge circuit 1110a in Figure 12. The functions and control logic of the half-bridge circuit 1110a2 are the same as those of the half-bridge circuit 1110a.

The controller 114 provided in the embodiment of the present application only needs to control the on or off of the main power transistor Q _L and the auxiliary power transistor Q _H in the AHB conversion circuit 111 a when the load level L of the power module 11 drops. Therefore, the controller 114 provided by the embodiment of the present application can not only improve the stability of the AHB conversion circuit 111a, power module 11, and electronic device 10 where it is located, but also has a simple configuration and is more suitable for use in various products.

FIG. 20 is a schematic diagram of an embodiment of a power module provided by this application. The power module 11 shown in FIG. 20 can be applied to the electronic device 10 shown in FIG. 1 or 2 . As shown in FIG. 20 , the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114.

The ACF conversion circuit 111b is used to receive the input voltage V ₁ of the input power supply 13 and provide the output voltage V ₂ to power the load 12 . In addition, the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112. Among them, the auxiliary winding circuit 112 is coupled with the ACF conversion circuit 111b, and the auxiliary winding voltage V ₃ is generated on the auxiliary winding 1121. The auxiliary winding circuit 112 converts the auxiliary winding voltage V ₃ into an output voltage V ₄ to provide power to the power supply circuit 113 . The power circuit 113 supplies power to the control circuit 114 . The controller 114 is used to control the operating state of the ACF conversion circuit 111b.

Figure 21 is a schematic diagram of an embodiment of the power module provided by this application. As shown in FIG. 21 , the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114. Among them, the ACF conversion circuit 111b in the power module 11 includes a half-bridge circuit 1110b, a transformer 1112b and a rectifier circuit 1114b. Among them, the transformer 1112b includes a primary winding 1111b and a secondary winding 1113b. In addition, the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. The secondary winding 1113b is coupled to the primary winding 1111b, and the auxiliary winding 1121 is coupled to the primary winding 1111b.

The half-bridge circuit 1110b is used to receive the input voltage V ₁ provided by the input power supply 13 and provide the output voltage V ₁₀ to the primary winding 1111b according to the control signal of the controller 114 . The half-bridge circuit 1110b usually includes a main power transistor, an auxiliary power transistor and a clamping capacitor.

The primary winding 1111b of the transformer 1112b is used to receive the output voltage V ₁₀ of the half-bridge circuit 1110b and generate the primary winding voltage V ₁₁ . The secondary winding 1113b of the transformer 1112b is coupled with the primary winding 1111b of the transformer 1112b, and the secondary winding voltage V ₃ is generated on the secondary winding 1113b.

The rectifier circuit 1114b is used to receive the secondary winding voltage V ₃ on the secondary winding 1113b and convert it into the output voltage V ₂ .

The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113 . The auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111b of the transformer 1112b. The primary winding voltage V ₁₁ on the primary winding 1112b is coupled to generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121. After the auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 112 , the output voltage V ₄ is provided to the power supply circuit 113 . Among them, the auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifier module 1122.

The power circuit 113 is used to power the controller 114 . The power supply circuit 113 receives the output voltage V ₄ of the auxiliary winding circuit 112 and provides the output voltage V ₅ to the controller 114 . That is, the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 coupled with the primary winding 1111 of its transformer 1112b. In some embodiments, power circuit 113 includes a voltage stabilizing circuit.

The controller 114 is used to control the operating state of the ACF conversion circuit 111b. The controller 114 is also used to detect the output voltage V ₂ of the ACF conversion circuit 111b, the output voltage V ₄ of the auxiliary winding circuit 112, the output voltage V ₅ of the power supply circuit 113, or the capacitance voltage V of the clamping capacitor C _c in the half-bridge circuit 1110b. Changes in multiple voltage values such as the voltage value of _Cc . The controller 114 is also used to control the operating state of the ACF conversion circuit 111b according to changes in the one or more voltage values.

In one embodiment, the control 114 sends the control signal G to control the operating state of the half-bridge circuit 1110b in the ACF conversion circuit 111b, thereby controlling the operating state of the ACF conversion circuit 111b. For example, the operating states of the ACF conversion circuit 111b generally include a continuous operating state and a suspended operating state. The continuous working state can also be called the normal working state, the controller's normal wave sending state, etc. The suspended working state can also be called intermittent working state, BURST working state, intermittent wave sending state of the controller, etc.

In this embodiment of the present application, the controller 114 can send a control signal G to control the turn-on and turn-off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b. The controller 114 adjusts the frequency or duty cycle of the control signal G to control the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b, thereby adjusting the output voltage V ₁₀ of the half-bridge circuit 1110b accordingly. . The output voltage V ₁₀ of the half-bridge circuit 1110b will cause the primary winding voltage V ₁₁ to change. Correspondingly, changes in the primary winding voltage V ₁₁ can cause changes in the secondary winding voltage V ₁₂ and the auxiliary winding voltage V ₃ . Correspondingly, changes in the secondary winding voltage V ₁₂ may cause the output voltage V ₂ of the ACF conversion circuit 111b to change. Accordingly, changes in the auxiliary winding voltage V ₃ may cause the output voltage V ₄ of the auxiliary winding circuit 112 to change. Correspondingly, the output voltage V ₄ of the auxiliary winding circuit 112 may cause a change in the output voltage V ₅ of the power supply circuit 113 .

As shown in the F1 direction in Figure 21, the ACF conversion circuit 111b can provide the output voltage _V2 to power the load 12. Among them, the input voltage V ₁ is converted into the output voltage V ₂ through the half-bridge circuit 1110b, the primary winding 1111b, the secondary winding 1113b and the rectifier circuit 1114b in the ACF conversion circuit 111b.

As shown in the F2 direction in FIG. 21 , the ACF conversion circuit 111b can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112 . After the input voltage V ₁ is processed by the half-bridge circuit 1110b in the ACF conversion circuit 111b, the primary winding voltage V ₁₁ can be generated in the primary winding 1111b. Correspondingly, the primary winding voltage V ₁₁ can generate an auxiliary winding voltage V ₃ on the auxiliary winding 1121 of the transformer 1112b. The auxiliary winding voltage V ₃ is processed by the auxiliary winding circuit 1121 to provide an output voltage V ₄ to power the power supply circuit 113 of the controller 114 .

Figure 22 is a schematic diagram of the voltage waveform of the controller and the power module provided by this application in a scenario where the load level drops. The following describes in detail the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIG. 22 and FIG. 21 .

Before time t ₁ , the load level L of the load 12 is the normal load L ₁ . The controller 114 controls the ACF conversion circuit 111b to run in a continuous operating state. The controller 114 controls the output voltage V ₂ of the ACF conversion circuit 111b to be at the rated voltage value. Output voltage V ₂₀ . The voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value of the output voltage V ₅ of the power supply circuit 113 is V ₅₀ . The voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1111b is V _Cc1 . V _Cc1 is the capacitance voltage of the clamping capacitor C _c when the ACF conversion circuit 111b operates in a continuous operating state.

At time t ₁ , the load level of load 12 drops from normal load L ₁ to light load L ₂ . Correspondingly, after time t ₁ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b increases to be greater than the rated output voltage V ₂₀ .

In one embodiment, when the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b is greater than the rated output voltage V ₂₀ , the controller 114 can control the ACF conversion circuit 111 b to operate in a continuous operating state. Furthermore, the controller controls the ACF conversion circuit 111b to reduce the voltage value of the output voltage _V2 . That is, the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and the rated output voltage V ₂₀ . The controller 114 controls the ACF conversion circuit 111 b Reduce the voltage value of the output voltage _V2 . Specifically, the controller 114 sends the control signal G to control the operating status of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b, so that the voltage value of the primary winding voltage V ₁₁ decreases. In one embodiment, the controller 114 can reduce the sending frequency of the control signal G, thereby reducing the conduction frequency of the main power transistor and the auxiliary power transistor. In one implementation, the controller 114 can reduce the duty cycle of the control signal G, thereby reducing the conduction time of the main power transistor and the auxiliary power transistor. In another embodiment, when the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b is greater than the rated voltage V ₂₀ , the controller 114 can control the ACF conversion circuit 111b to run in a suspended working state, and can also reduce the output voltage V ₂ Voltage value. However, the above two embodiments may not be able to effectively reduce the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b. After time t ₁ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b will continue to increase.

At the same time, after time t ₁ , the drop of the load level L causes the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b to be higher than the rated voltage V ₂₀ . The primary winding voltage V ₁₁ charges the clamping capacitor C _c in the half-bridge circuit 1110b, and the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110b increases from V _Cc1 to V _Cc2 . V _Cc2 is the maximum charging voltage of the clamping capacitor C _c in the half-bridge circuit 1110b.

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b increases to the first preset value V ₂₁ . The controller 114 determines that the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b is greater than or equal to the first preset value V ₂₁ , and the controller 114 controls the ACF conversion circuit 111b to suspend operation. That is, the controller 114 controls the ACF conversion circuit 111b to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and the first preset value V ₂₁ . Specifically, the controller 114 controls both the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b to turn off. In this embodiment of the present application, the first preset value V ₂₁ may be the peak voltage of the ACF conversion circuit 111b. The peak voltage of the ACF conversion circuit 111b is greater than the rated voltage V ₂₀ and less than the overvoltage protection voltage of the ACF conversion circuit 111b.

After time t ₂ , the controller 114 controls the ACF conversion circuit 111b to operate in a suspended working state. Correspondingly, the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111 b in the ACF conversion circuit 111 b decreases, causing the secondary winding voltage V ₁₂ to decrease, and causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b decreases, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

At time _t3 after time _t2 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 drops to less than or equal to the second preset value _V41 , or the voltage value of the output voltage _V5 of the power supply circuit 113 drops to less than Or equal to the third preset value V ₅₂ . At this time, the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge.

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the second preset value V ₄₁ , and the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge . That is, the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ .

In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ , and the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge. That is, the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110b to be turned on, so that the clamping capacitor C _c in the half-bridge circuit 1110b is discharged. The primary winding 1111b, the clamping capacitor C _c of the half-bridge circuit 1110b, and the auxiliary power transistor of the half-bridge circuit 1110b can form a discharge circuit. Correspondingly, the clamping capacitor C _c of the half-bridge circuit 1110b is discharged, which can generate the primary winding voltage V ₁₁ on the primary winding 1111b.

In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110b to be turned on periodically, so that the clamping capacitor C _c in the half-bridge circuit 1110b is discharged. When the auxiliary power transistor of the half-bridge circuit 1110b is turned on, the primary winding 1111b, the clamping capacitor C _c of the half-bridge circuit 1110b, and the auxiliary power transistor of the half-bridge circuit 1110b can form a discharge loop. Correspondingly, the auxiliary power transistor of the half-bridge circuit 1110b is turned on periodically, which can cause the clamping capacitor C _c in the half-bridge circuit 1110b to be discharged periodically.

After time _t3 , the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110b decreases. The clamping capacitor C _c in the half-bridge circuit 1110b is discharged, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111b to increase. Correspondingly, an increase in the voltage value of the primary winding voltage V ₁₁ will cause an increase in the voltage value of the auxiliary winding voltage V ₃ . Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases. Therefore, in a scenario where the load level of the load 12 changes, the voltage value of the output voltage V ₅ of the power circuit 113 will not drop below the under-voltage protection voltage V ₅₁ of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.

The controller 114 provided in the embodiment of the present application controls the discharge of the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so that the voltage value of the output voltage V ₅ of the power supply circuit 113 is higher than the under-voltage protection of the controller 114 voltage V ₅₁ , thereby preventing the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

Since the energy stored in the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b is limited, the voltage value of the primary winding voltage V ₁₁ generated on the primary winding 1111b after discharge is small. At this time, the primary winding voltage V ₁₁ generated on the primary winding 1111b is smaller than the secondary winding voltage V ₁₂ on the secondary winding 1113, which will not cause the output voltage V ₂ of the ACF conversion circuit 111b to increase. Therefore, after the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge, the primary winding voltage V ₁₁ generated on the primary winding 1111 b is only used to increase the output voltage V ₄ of the auxiliary winding circuit 112 and the power supply circuit 113 The output voltage V ₅ is shown in the F2 direction in Figure 21. Therefore, the controller 114 and the power module 111 in which it is provided in the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V ₂ of the ACF conversion circuit 111b. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

Moreover, the controller 114 provided in the embodiment of the present application controls the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so as not to introduce noise from the input power supply 13 and avoid the noise from affecting the ACF conversion circuit 111b and its location. The electromagnetic compatibility of the power module 11 and the electronic device 10. Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

In an embodiment of the present application, after the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b begins to discharge, the controller 114 can also adjust the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110b. The voltage value, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 or the voltage value of the output voltage V ₅ of the power supply circuit 113 controls the clamping capacitor C _c in the half-bridge circuit 1110b to stop discharging. In one embodiment, the controller 114 controls the auxiliary power tube in the half-bridge circuit 1110b to turn off, and the discharge loop formed by the primary winding 1111b, the clamping capacitor C _c of the half-bridge circuit 1110b, and the auxiliary power tube of the half-bridge circuit 1110b disconnect. Correspondingly, the clamping capacitor C _c of the half-bridge circuit 1110b stops discharging.

In the first embodiment, at time t ₄ after time t ₃ , the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110 b drops to less than or equal to the preset capacitance voltage value V _Cc3 . In one embodiment, the controller 114 determines that the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110b drops to less than or equal to the preset capacitance voltage value V _Cc3 , and the controller 114 controls the clamping of the half-bridge circuit 1110b Capacitor C _c stops discharging. In one embodiment, the preset capacitor voltage value V _Cc3 may be greater than or equal to the capacitance voltage V _Cc1 of the clamping capacitor C _c of the half-bridge circuit 1110 b when the ACF conversion circuit 111 b operates in the continuous operating state. That is, the controller 114 controls the clamp capacitor C _c of the half-bridge circuit 1110 _b to stop discharging based on the comparison result between the capacitor voltage V _Cc of the clamp capacitor C c of the half-bridge circuit 1110 b and the preset capacitor voltage value V _Cc3 . Therefore, the controller 114 can stop discharging through the clamping capacitor C _c of the half-bridge circuit 1110 b, and can avoid the capacitance voltage V _Cc of the clamping capacitor C _c being too low and affecting the ACF conversion circuit 111 b to resume continuous operation, further improving the power supply mode. The stability of group 11 and the electronic device 10 in which it resides.

In the second embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V ₄₂ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is greater than or equal to the fourth preset value V ₄₂ , and the controller 114 controls the clamping capacitor C _c of the half-bridge circuit 1110b to stop discharging. . That is, the controller 114 controls the clamp capacitor C _c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the fourth preset value V ₄₂ . Therefore, the controller 114 can stop discharging through the clamping capacitor C _c of the half-bridge circuit 1110b, which can prevent the output voltage _V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller. 114 and the stability of the power module 11 and electronic equipment 10 in which it is located.

In the third embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₅ of the power circuit 113 increases to a value greater than or equal to the fifth preset value V ₅₃ . In one embodiment, the controller 114 determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is greater than or equal to the fifth preset value V ₅₃ , and the controller 114 controls the clamping capacitor C _c of the half-bridge circuit 1110b to stop discharging. That is, the controller 114 controls the clamp capacitor C _c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the fifth preset value V ₅₃ . Therefore, the controller 114 can stop discharging by controlling the clamping capacitor C _c of the half-bridge circuit 1110 b to prevent the output voltage V ₄ of the power supply circuit 113 from being too high and damaging the controller 114 , further improving the efficiency of the controller 114 and its location. The stability of the power module 11 and the electronic device 10.

After time t ₄ , after the clamp capacitor C _c of the half-bridge circuit 1110 b stops discharging, the voltage value of the capacitance voltage V _Cc of the clamp capacitor C _c stops decreasing. Correspondingly, the voltage value of the primary winding voltage V ₁₁ decreases, causing the auxiliary winding voltage V ₃ to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases.

In one embodiment of the present application, after time t ₄ , when the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V ₄₁ , or the output voltage V ₅ of the power supply circuit 113 When the voltage value of V drops to less than or equal to the third preset value V ₅₂ , the controller 114 may control the clamping capacitor C _c of the half-bridge circuit 1110 b to discharge again. The specific process is as described in the above embodiment and will not be described again. That is, the controller 114 can control the clamping capacitor C _c of the half-bridge circuit 1110 b to discharge again based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the second preset value V ₄₁ . Alternatively, the controller 114 may control the clamping capacitor C _c of the half-bridge circuit 1110 b to discharge again based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the third preset value V ₅₂ .

In an embodiment of the present application, after the clamping capacitor C _c of the half-bridge circuit 1110 b starts to discharge or stops discharging, the controller 114 will also control the ACF conversion circuit according to the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b The operating status of 111b switches from the suspended working status to the continuous working status. After time t ₂ , the controller 114 controls the ACF conversion circuit 111 b to operate in a suspended operating state, and accordingly the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b decreases. In one embodiment, after the clamping capacitor C _c of the half-bridge circuit 1110b starts to discharge and before it stops discharging, the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b drops to less than or equal to the rated voltage V ₂₀ , the controller 114 controls the operating state of the ACF conversion circuit 111b to switch from the suspended operating state to the continuous operating state. In one embodiment, after the clamping capacitor C _c of the half-bridge circuit 1110 b stops discharging, the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b drops to less than or equal to the rated voltage V ₂₀ , and the controller 114 controls the ACF conversion The operating state of the circuit 111b is switched from the suspended operating state to the continuous operating state.

At time t ₅ after time t ₃ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b drops to less than or equal to the rated voltage V ₂₀ . The controller 114 determines that the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b drops to less than or equal to the rated voltage V ₂₀ , and controls the operating state of the ACF conversion circuit 111b to switch from the suspended operating state to the continuous operating state. That is, the controller 114 controls the operation state of the ACF conversion circuit 111b to switch from the pause operation state to the continuous operation state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and the rated voltage V ₂₀ . After time t ₅ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b returns to the rated voltage V ₂₀ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 returns to V ₄₀ , and the output voltage V ₅ of the power supply circuit 113 The voltage value returns to V ₅₀ .

Figure 23 is a schematic diagram of an embodiment of the power module provided by this application. FIG. 23 shows a schematic diagram of some circuits in the power module 11 shown in FIG. 21 . As shown in FIG. 23 , the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113 and a controller 114. Among them, the ACF conversion circuit 111b includes a half-bridge circuit 1110b, a transformer 1112b and a rectifier circuit 1114b. Among them, the transformer 1112b includes a primary winding 1111b and a secondary winding 1113b. In addition, the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. The secondary winding 1113b is coupled to the primary winding 1111b, and the auxiliary winding 1121 is coupled to the primary winding 1111b.

The half-bridge circuit 1110b includes a main power transistor Q _L , an auxiliary power transistor Q _H and a clamping capacitor C _c . The main power tube Q _L , the auxiliary power tube Q _H and the clamping capacitor C _c form an active clamp flyback half-bridge topology. Specifically, the first end of the clamping capacitor C _c is connected to the opposite end of the primary winding 1111b, and the second end of the clamping capacitor C _c is connected to the drain of the auxiliary power tube Q _H. The source of the auxiliary power tube _QH is connected to the same terminal of the primary winding 1111b and the drain of the main power tube _QL . The source of the main power tube Q _L is grounded. In one embodiment, the gate of the main power transistor Q _L is used to receive the second control signal _GH from the controller 114 . The gate of the auxiliary power transistor Q _H is used to receive the first control signal _GL from the controller 114 .

The rectifier circuit 1114b includes a capacitor C ₁ and a diode D ₂ . The anode of diode D ₂ is connected to the same terminal of secondary winding 1113b. The two ends of the capacitor C ₁ are respectively connected to the cathode of the diode D ₂ and the opposite terminal of the secondary winding 1113b.

The controller 114 includes a detection unit 1141 and a driving unit 1142. In some embodiments, when the driving unit 1142 is a chip, the power circuit 113 may be connected to the power supply pin of the driving unit 1142 . For example, the supply pin may be the pin labeled " _Vdd " shown in Figure 23.

The detection unit 1141 is used to detect the output voltage V ₂ of the ACF conversion circuit 111 b , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 , the voltage value of the output voltage V ₅ of the power supply circuit 113 or the half-bridge circuit 1110 b of the ACF conversion circuit 111 b Changes in various voltage values among the voltage values of the capacitor voltage V _Cc of the medium clamping capacitor C _c . The driving circuit 1142 is used to control the operating state of the ACF conversion circuit 111b according to the change of one or more voltage values.

For example, the detection unit 1141 can detect the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b by connecting point A of the output end of the secondary winding circuit 1114 b in FIG. 23 . The detection unit 1141 can detect the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 by connecting point B of the output end of the auxiliary winding circuit 112 in FIG. 23 . The detection unit 1141 can detect the voltage value of the output voltage V ₅ of the power supply circuit 113 by connecting point C of the output end of the power supply circuit 113 in FIG. 23 . The detection unit 1141 can detect the voltage value of the capacitance voltage V _Cc of the clamp capacitor C _c by connecting points D on either side of the clamp capacitor C _c in FIG. 23 .

The driving unit 1142 is used to control the operating state of the ACF conversion circuit 111b. Among them, the driving unit 1142 controls the on and off of the main power transistor Q _L and the auxiliary power transistor Q _H by sending the control signal G _L /G _H , thereby controlling the operating state of the ACF conversion circuit 111b. In some embodiments, when the driving unit 1142 is a chip, the driving unit 1142 shown in FIG. 23 can send the control signal GH through its pin labeled " _GH ", and can send the control signal _GH through its pin labeled " _GL " The pin sends the control signal _GL . It should be noted that the pin numbers in Figure 23 are only examples, and in actual applications, pins with other numbers on the driving unit 1142 can also be used to implement the functions of the pins shown in Figure 23 .

Figure 24 is a schematic diagram of the control signals of the controller provided by this application in a scenario where the load level of the power module drops. The following describes the operation process of the controller 114 provided by the present application and the power module 11 in which it is located in a scenario where the load level L of the load 12 drops, with reference to FIG. 22 , FIG. 23 and FIG. 24 .

Before time t1, the load level of load 12 is normal load L ₁ . The controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state, and controls the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b to be the rated voltage V ₂₀ . At this time, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is V ₄₀ . The voltage value of the output voltage V ₅ of the power supply circuit 113 is V ₅₀ . The voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1111b is V _Cc1 .

Figure 25 is a schematic diagram of the control signals of the controller provided by the embodiment of the present application. As shown in Figure 25, each of the control signals _G1 , _G2 , _G3 ... sent by the controller 114 includes a first control signal _GL sent to the main power tube QL or a first control signal _GL sent to the auxiliary power tube _QH . Second control signal G _H . The controller 114 controls the main power transistor _QL and the auxiliary power transistor _QH to periodically turn on and off alternately, and the half-bridge circuit 1110b can generate the primary winding voltage V ₁₁ in the primary winding 1111b. After coupling, the primary winding voltage V ₁₁ on the primary winding 1111b can generate the secondary winding voltage V ₁₂ on the secondary winding 1113b, and can generate the auxiliary winding voltage V ₃ on the auxiliary winding 1121. Correspondingly, the rectifier circuit 1114b provides the output voltage V ₂ to the load 12 , the auxiliary winding circuit 112 provides the output voltage V ₄ to the power supply circuit 113 , and the output voltage V ₅ of the power supply circuit 113 to the controller 115 is V ₅₀ . Since the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b to the load 12 is stabilized at the rated voltage V ₂₀ , the voltage value V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110 b is stabilized at V _Cc1 .

At time t1, the load level of load 12 drops from normal load L ₁ to light load L ₂ . After time t1, the voltage value of the output voltage _V2 of the ACF conversion circuit 111b increases to greater than the rated voltage _V20 .

In one embodiment, the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and the rated voltage V ₂₀ . The controller 114 controls the ACF conversion circuit. 111b reduces the voltage value of the output voltage V ₂ .

Specifically, the detection unit 1141 of the controller 114 detects the output voltage V ₂ of the ACF conversion circuit 111 b and determines that the output voltage V ₂ of the ACF conversion circuit 111 b is greater than the rated voltage V ₂₀ . Correspondingly, the controller 114 controls the ACF conversion circuit 111b to operate in a continuous working state, and the controller 114 reduces the transmission frequency of the first control signal _GL and the second control signal _GH , or reduces the transmission frequency of the first control signal _GL and the second control signal GH. Duty cycle of signal G _H. As shown in FIG. 24 , the frequencies of the control signals G ₄ , G ₅ , and G ₆ sent by the controller 114 after time t ₁ are smaller than the frequencies of the control signals G ₁ , G ₂ , and G ₃ periodically sent before time t ₁ . Correspondingly, the frequency at which the main power transistor _QL and the auxiliary power transistor _QH are turned on and off is reduced, causing the voltage value of the output voltage _V2 of the ACF conversion circuit 111b to decrease. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 decreases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 decreases. However, the above method may not effectively reduce the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b, and the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b will continue to increase.

After time t ₁ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b is higher than the rated voltage V ₂₀ . At this time, the primary winding voltage V ₁₁ charges the clamping capacitor C _c in the half-bridge circuit 1110b, and the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110b increases from V _Cc1 to V _Cc2 .

At time t ₂ after time t ₁ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b increases to a value greater than or equal to the first preset value V ₂₁ . The controller 114 controls the ACF conversion circuit 111b to operate in a suspended operating state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and the first preset value V ₂₁ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b, and determines that the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b is greater than or equal to the first preset value V ₂₁ . Correspondingly, the driving unit 1142 of the controller 114 stops sending the first control signal _GL and the second control signal _GH , thereby controlling the ACF conversion circuit 111b to operate in a suspended working state. Correspondingly, the ACF conversion circuit 111b does not process the input voltage V ₁ it receives, and the output voltage V ₂ of the ACF conversion circuit 111b decreases.

At time _t3 after time _t2 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 drops below the second preset value _V41 , or the voltage value of the output voltage _V5 of the power supply circuit 113 drops below The third preset value V ₅₂ . At this time, the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge.

In one embodiment, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the second preset value. _V41 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn on the auxiliary power transistor _QH . At this time, the clamping capacitor C _c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor _QH of the half-bridge circuit 1110b form a discharge loop, and the clamping capacitor C _c of the half-bridge circuit 1110b begins to discharge.

In one embodiment, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₅ of the power supply circuit 113 and determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is less than or equal to the third preset value V ₅₂ . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn on the auxiliary power transistor _QH . At this time, the clamping capacitor C _c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor _QH of the half-bridge circuit 1110b form a discharge loop, and the clamping capacitor C _c of the half-bridge circuit 1110b begins to discharge.

After time _t3 , the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c in the half-bridge circuit 1110b decreases. The clamping capacitor C _c in the half-bridge circuit 1110b is discharged, causing the voltage value of the primary winding voltage V ₁₁ on the primary winding 1111b to increase. Correspondingly, the voltage value of the auxiliary winding voltage V ₃ increases, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases. Therefore, in a scenario where the load level of the load 12 changes, the voltage value of the output voltage V ₅ of the power circuit 113 will not drop below the under-voltage protection voltage V ₅₁ of the controller 114 , thereby preventing the controller 114 from being damaged due to low voltage. protection and restart.

Since the energy stored in the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b is limited, the voltage value of the primary winding voltage V ₁₁ generated on the primary winding 1111b after discharge is small. At this time, the primary winding voltage V ₁₁ generated on the primary winding 1111b is smaller than the secondary winding voltage V ₁₂ on the secondary winding 1113, which will not cause the output voltage V ₂ of the ACF conversion circuit 111b to increase. Therefore, after the controller 114 controls the clamping capacitor C _c in the half-bridge circuit 1110b to discharge, the primary winding voltage V ₁₁ generated on the primary winding 1111 b is only used to increase the output voltage V ₄ of the auxiliary winding circuit 112 and the power supply circuit 113 Output voltage V ₅ . Therefore, the controller 114 and the power module 111 in which it is provided in the embodiment of the present application can not only prevent the controller 114 from restarting due to under-voltage protection, but also avoid increasing the ripple of the output voltage V ₂ of the ACF conversion circuit 111b. Improve the stability of the power module 11 and the electronic device 10 where the controller 114 is located.

Moreover, the controller 114 provided in the embodiment of the present application controls the clamping capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b, so as not to introduce noise from the input power supply 13 and avoid affecting the ACF conversion circuit 111b and its location. Electromagnetic compatibility of power module 11 and electronic equipment 10 . Therefore, the controller 114 provided by the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 in which it is located.

In an embodiment of the present application, the controller 114 can also control the clamp capacitor C _c in the half-bridge circuit 1110b of the ACF conversion circuit 111b to stop discharging.

In the first embodiment, at time t ₄ after time t ₃ , the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110 b drops to less than or equal to the preset capacitance voltage value V _Cc3 . In one embodiment, the preset capacitor voltage value V _Cc3 may be greater than or equal to the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110 b when the ACF conversion circuit 111 b operates in the continuous operating state. The controller 114 controls the clamping capacitor C _c of the half-bridge circuit 1110b to stop discharging based on the comparison result between the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110b and the preset capacitance voltage value V _Cc3 . Specifically, the detection unit 1141 of the controller 114 detects the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110 b and determines that the capacitance voltage V _Cc of the clamping capacitor C _c of the half-bridge circuit 1110 b is less than or equal to the preset capacitance voltage. Value V _Cc3 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the clamping capacitor C _c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q _H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C _c of the half-bridge circuit 1110b stops discharging.

Therefore, the controller 114 can stop discharging through the clamping capacitor C _c of the half-bridge circuit 1110 b, and can avoid the capacitance voltage V _Cc of the clamping capacitor C _c being too low and affecting the ACF conversion circuit 111 b to resume continuous operation, further improving the power supply mode. The stability of group 11 and the electronic device 10 in which it resides.

In the second embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases to greater than or equal to the fourth preset value V ₄₂ . The controller 114 controls the clamping capacitor C _c of the half-bridge circuit 1110b to stop discharging based on the comparison result between the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and the fourth preset value V ₄₂ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 and determines that the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 is less than or equal to the preset capacitor voltage value V _Cc3 . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the clamping capacitor C _c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q _H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C _c of the half-bridge circuit 1110b stops discharging.

Therefore, the controller 114 can stop discharging through the clamping capacitor C _c of the half-bridge circuit 1110b, which can prevent the output voltage _V4 of the auxiliary winding circuit 112 from being too high and damaging the power circuit 113 and the controller 114, further improving the efficiency of the controller. 114 and the stability of the power module 11 and electronic equipment 10 in which it is located.

In the third embodiment, at time t ₄ after time t ₃ , the voltage value of the output voltage V ₅ of the power circuit 113 is increased to greater than or equal to the fifth preset value V ₅₃ . The controller 114 controls the clamping capacitor C _c of the half-bridge circuit 1110 b to stop discharging based on the comparison result between the voltage value of the output voltage V ₅ of the power supply circuit 113 and the fifth preset value V ₅₃ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₅ of the power supply circuit 113 and determines that the voltage value of the output voltage V ₅ of the power supply circuit 113 is greater than or equal to the fifth preset value V ₅₃ . The driving unit 1142 of the controller 114 sends the first control signal _GL to turn off the auxiliary power transistor _QH . At this time, the discharge loop formed by the clamping capacitor C _c of the half-bridge circuit 1110b, the primary winding 1111b and the power transistor Q _H of the half-bridge circuit 1110b is disconnected, and the clamping capacitor C _c of the half-bridge circuit 1110b stops discharging. Therefore, the controller 114 can stop discharging by controlling the clamping capacitor C _c of the half-bridge circuit 1110 b to prevent the output voltage V ₄ of the power supply circuit 113 from being too high and damaging the controller 114 , further improving the efficiency of the controller 114 and its location. The stability of the power module 11 and the electronic device 10.

In one embodiment of the present application, after time t ₄ , when the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 drops to less than or equal to the second preset value V ₄₁ , or the output voltage V ₅ of the power supply circuit 113 When the voltage value of V drops to less than or equal to the third preset value V ₅₂ , the controller 114 may control the clamping capacitor C _c of the half-bridge circuit 1110 b to discharge again. The specific process is as described in the above embodiment and will not be described again.

At time t ₅ after time t ₃ , the voltage value of the output voltage V ₂ of the ACF conversion circuit 111b drops to less than or equal to the rated output voltage V ₂₀ . The controller 114 controls the operating state of the ACF converting circuit 111b to switch from the suspended operating state to the continuous operating state based on the comparison result between the voltage value of the output voltage V ₂ of the ACF converting circuit 111 b and the rated output voltage V ₂₀ . Specifically, the detection unit 1141 of the controller 114 detects the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b and determines that the voltage value of the output voltage V ₂ of the ACF conversion circuit 111 b is less than or equal to the rated output voltage V ₂₀ . The driving unit 1142 of the controller 114 periodically sends the first control signal _GL and the second control signal _GH , and controls the main power tube _QL and the auxiliary power tube _QH to be turned on and off periodically, so that the ACF conversion circuit 111b Restore continuous working status. At this time, the first control signal _GL and the second control signal _GH sent by the controller 114 are recorded as G ₇ , G ₈ , G ₉ . . . The specific implementation of each control signal G ₇ , G ₈ , G ₉ ... is the same as shown in Figure 25 and will not be described again. For another example, the periods of the control signals G ₇ , G ₈ , G ₉ ... may be the same as the periods of the control signals G ₁ , G ₂ , G ₃ ..., or the periods of the control signals G ₄ , G ₅ , G ₆ ... wait. After time _t5 , the voltage value of the output voltage _V2 of the ACF conversion circuit 111b returns to the rated output voltage _V20 , the voltage value of the output voltage _V4 of the auxiliary winding circuit 112 returns to _V40 , and the output voltage V of the power supply circuit 113 The voltage value of ₅ returns to V ₅₀ .

Figure 26 is a schematic diagram of an embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit. The difference between Figure 26 and Figure 24 is that the controller 114 controls the clamp capacitor C _c of the primary winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge. Description will be given below with reference to Figure 22 and Figure 26 .

At time t ₃ , the controller 114 controls the auxiliary power transistor Q _H in the half-bridge circuit 1110b to be turned on periodically, so that the clamping capacitor C _c in the half-bridge circuit 1110b is discharged. Specifically, the controller 114 does not send the first control signal _GL to the main power tube _QL , so that the main power tube _QL is turned off. Furthermore, the controller 114 periodically sends the second control signal _GH to the auxiliary power transistor _QH , so that the auxiliary power transistor _QH is periodically turned on. When the auxiliary power transistor Q _H of the half-bridge circuit 1110b is turned on, the primary winding 1111b, the clamping capacitor C _c of the half-bridge circuit 1110b, and the auxiliary power transistor Q _H of the half-bridge circuit 1110b can form a discharge loop. Correspondingly, the auxiliary power transistor Q _H of the half-bridge circuit 1110b is turned on periodically, which can cause the clamping capacitor C _c in the half-bridge circuit 1110b to be discharged periodically.

In the embodiment of the present application, the controller 114 controls the _period T1 during which the auxiliary power transistor Q _H is periodically turned on, which may be preconfigured, or the controller 114 may be based on the capacitance voltage V _Cc of the current clamping capacitor C c or The stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c is relatively high or more electric energy is stored, the period T1 can be set smaller. In an embodiment, the period T1 may also be the same as the period of the control signals G ₁ , G ₂ , G _{3 .} . . or G ₄ , G ₅ , G ₆ . . . In the embodiment of the present application, the duration for which the controller 114 controls the auxiliary power transistor Q _H to be turned on or off in each cycle may be the same or different.

Figure 27 is a schematic diagram of changes in the capacitance voltage of the clamp capacitor of the ACF conversion circuit provided by this application. As shown in Figure 27, the clamping capacitor _Cc is periodically discharged, and the capacitance voltage V _Cc of the clamping capacitor _Cc decreases stepwise from V _Cc2 . Between time t ₃ and time t ₄ , the capacitance voltage V _Cc of the clamping capacitor C _c decreases stepwise as the auxiliary power transistor Q _H is periodically turned on. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 also shows a step-like increase, and the voltage value of the output voltage V ₅ of the power supply circuit 113 also shows a step-like increase.

Therefore, the controller 114 controls the clamping capacitor C _c in the ACF conversion circuit 111b to periodically discharge, which can cause the capacitance voltage V _Cc of the clamping capacitor C _c to decrease in a stepwise manner, avoiding excessive rapid decline that affects the operation of the ACF conversion circuit 111b. , thereby improving the stability of the power module 11. Moreover, the controller 114 controls the clamping capacitor C _c in the ACF conversion circuit 111b to periodically discharge, which can increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output voltage V ₅ of the power supply circuit 113 in a stepwise manner to avoid excessive voltage increase. The circuit components may be damaged quickly, thereby improving the stability of the power module 11.

Figure 28 is a schematic diagram of another embodiment of the controller provided by the present application controlling the discharge of the clamp capacitor of the ACF conversion circuit. The difference between Figure 28 and Figure 26 is that the controller 114 controls the auxiliary power tube Q _H and the main power tube Q _L in the primary winding circuit 1111b of the ACF conversion circuit 111b to periodically alternately conduct, so that the clamping capacitor C _c periodically Discharge.

At time _t3 , the controller 114 periodically controls the main power tube _QL and the auxiliary power tube _QH to turn on alternately, and controls the auxiliary power tube _QH and the main power tube _QL to not turn on at the same time. Specifically, the controller 114 periodically sends the second control signal _GH to _{the auxiliary power tube QH and the first control signal GL} _to _the main power tube QL in sequence, so that the auxiliary power tube _QH and the main power tube Q _L is turned on in sequence, and the auxiliary power tube Q _H and the main power tube Q _L are not turned on at the same time. When the auxiliary power transistor Q _H of the half-bridge circuit 1110b is turned on, the primary winding 1111b, the clamping capacitor C _c of the half-bridge circuit 1110b, and the auxiliary power transistor Q _H of the half-bridge circuit 1110b can form a discharge loop. The change of the capacitance voltage V _Cc of the clamping capacitor C _c can be seen in Figure 27.

First, the controller 114 controls the auxiliary power transistor _QH to turn on and the main power transistor _QL to turn off. Specifically, the controller 114 sends the second control signal _GH to the auxiliary power tube _QH and does not send the first control signal _GL to the main power tube _QL . Correspondingly, the clamping capacitor C _c , the primary winding a and the auxiliary power tube Q _H form a current loop, and the clamping capacitor C _c discharges. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases.

Then, the controller 114 controls the auxiliary power transistor _QH to turn off and the main power transistor _QL to turn on. Specifically, the controller 114 does not send the second control signal _GH to the auxiliary power tube _QH and sends the first control signal _GL to the main power tube _QL . At this time, the input voltage V ₁ , primary winding a, and main power tube Q _L form a loop. Correspondingly, the input voltage V ₁ generates the primary winding voltage V ₁₁ on both sides of the primary winding a. The primary winding voltage V ₁₁ is coupled through the transformer 1112b to generate the auxiliary winding voltage V ₃ on the auxiliary winding c. Correspondingly, the voltage value of the output voltage V ₄ of the auxiliary winding circuit 112 increases, and the voltage value of the output voltage V ₅ of the power supply circuit 113 increases.

Therefore, the controller 114 controls the clamping capacitor C _c of the primary side winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge, which can cause the capacitance voltage V _Cc of the clamping capacitor C _c to drop in a stepwise manner to avoid falling too fast and affecting the ACF. The operation of the conversion circuit 111b thereby improves the stability of the power module 111. Furthermore, the controller 114 controls the clamping capacitor C _c of the primary winding circuit 1111b in the ACF conversion circuit 111b to periodically discharge, which can increase the output voltage V ₄ of the auxiliary winding circuit 112 and the output voltage V ₅ of the power supply circuit 113 in a stepwise manner. , to avoid damage to circuit components due to excessive lifting, thereby improving the stability of the power module 111.

In one embodiment, in each cycle, the controller 114 can control the main power transistor Q _L to turn on first and the auxiliary power transistor Q _H to turn on later. In the embodiment of the present application, the controller 114 controls the main power transistor Q _L and the auxiliary power transistor Q _H to periodically conduct alternately. The period T2 may be pre-configured, or the controller 114 may control the main power transistor Q L and the auxiliary power transistor Q H according to the current clamping capacitance C _c The capacitor voltage V _Cc or stored electrical energy is calculated. In one embodiment, when the voltage value of the capacitance voltage V _Cc of the clamping capacitor C _c is relatively high or more electric energy is stored, the period T2 can be set smaller. In one embodiment, the period T2 may be the same as the period of the control signals G ₁ , G ₂ , G ₃ . . . or the period of G ₄ , G ₅ , G ₆ . . . In the embodiment of the present application, in each cycle, the controller 114 controls the conduction time of the main power transistor _QL and the conduction time of the auxiliary power transistor _QH , which may be the same or different. In this embodiment of the present application, the duty ratios of the first control signal _GL and the second control signal _GH sent by the controller 114 may be the same or different.

The controller 114 provided in the embodiment of the present application only needs to control the on or off of the main power transistor Q _L and the auxiliary power transistor Q _H in the ACF conversion circuit 111 b when the load level L of the power module 11 drops. Therefore, the controller 114 provided by the embodiment of the present application can not only improve the stability of the ACF conversion circuit 111b, power module 11, and electronic device 10 where it is located, but also has a simple configuration and is more suitable for use in various products.

This application also provides an electronic device, including the controller 114 provided in any embodiment of this application, or the power module 11 provided in any embodiment of this application.

In the foregoing embodiments, the methods executed by the controller 114 provided by the embodiments of the present application are introduced. In order to implement the functions in the methods provided by the above embodiments of the present application, the controller 114 as the execution subject may include a hardware structure. and/or software modules to implement the above functions in the form of hardware structures, software modules, or hardware structures plus software modules. Whether one of the above functions is performed as a hardware structure, a software module, or a hardware structure plus a software module depends on the specific application and design constraints of the technical solution. It should be noted that it should be understood that the division of each module of the above device is only a division of logical functions. In actual implementation, they can be fully or partially integrated into a physical entity, or they can also be physically separated. And these modules can all be implemented in the form of software calling through processing components; they can also all be implemented in the form of hardware; some modules can also be implemented in the form of software calling through processing components, and some modules can be implemented in the form of hardware. It can be a separate processing element, or it can be integrated into a chip of the above-mentioned device. In addition, it can also be stored in the memory of the above-mentioned device in the form of program code, and called and executed by a certain processing element of the above-mentioned device. Determine the function of the module. The implementation of other modules is similar. In addition, all or part of these modules can be integrated together or implemented independently. The processing element described here may be an integrated circuit with signal processing capabilities. During the implementation process, each step of the above method or each of the above modules can be completed by instructions in the form of hardware integrated logic circuits or software in the processor element. For example, the above modules may be one or more integrated circuits configured to implement the above methods, such as: one or more application specific integrated circuits (ASICs), or one or more microprocessors (digital signal processor, DSP), or one or more field programmable gate arrays (field programmable gate array, FPGA), etc. For another example, when one of the above modules is implemented in the form of a processing element scheduler code, the processing element can be a general-purpose processor, such as a central processing unit (Central Processing Unit, CPU) or other processors that can call the program code. For another example, these modules can be integrated together and implemented in the form of a system-on-a-chip (SOC).

In the above embodiments, the steps performed by the controller 114 may be implemented in whole or in part by software, hardware, firmware, or any combination thereof. When implemented using software, it may be implemented in whole or in part in the form of a computer program product. The computer program product includes one or more computer instructions. When the computer program instructions are loaded and executed on a computer, the processes or functions described in the embodiments of the present application are generated in whole or in part. The computer may be a general-purpose computer, a special-purpose computer, a computer network, or other programmable device. The computer instructions may be stored in or transmitted from one computer-readable storage medium to another, e.g., the computer instructions may be transferred from a website, computer, server, or data center Transmission to another website, computer, server or data center by wired (such as coaxial cable, optical fiber, digital subscriber line (DSL)) or wireless (such as infrared, wireless, microwave, etc.) means. The computer-readable storage medium may be any available medium that can be accessed by a computer or a data storage device such as a server, data center, etc. that contains one or more available media integrated. The available media may be magnetic media (eg, floppy disk, hard disk, tape), optical media (eg, DVD), or semiconductor media (eg, solid state disk (SSD)), etc.

This application also provides a computer-readable storage medium. The computer-readable storage medium stores computer instructions. When the computer instructions are executed, they can be used to perform any method performed by the controller 114 in any of the foregoing embodiments of this application.

This embodiment of the present application also provides a chip that runs instructions, and the chip is used to execute any method executed by the controller 114 as mentioned above in this application.

An embodiment of the present application also provides a computer program product. The program product includes a computer program. The computer program is stored in a storage medium. At least one processor can read the computer program from the storage medium. The at least one processor can read the computer program from the storage medium. When a processor executes the computer program, it may implement any method executed by the controller 114 as described above in this application.

Persons of ordinary skill in the art can understand that all or part of the steps to implement the above embodiments can be completed by hardware related to program instructions. The aforementioned program can be stored in a computer-readable storage medium. When the program is executed, the steps including the above-mentioned method embodiments are executed; and the aforementioned storage media include: ROM, RAM, magnetic disks, optical disks and other media that can store program codes.

Those of ordinary skill in the art can understand that in order to facilitate the explanation of the technical solution of the present application, the embodiments of the present application are described separately through functional modules. The circuit devices in each module may partially or completely overlap, which does not limit the scope of protection of the present application.

Finally, it should be noted that the above embodiments are only used to illustrate the technical solution of the present application, but not to limit it; although the present application has been described in detail with reference to the foregoing embodiments, those of ordinary skill in the art should understand that: The technical solutions described in the foregoing embodiments can still be modified, or some or all of the technical features can be equivalently replaced; and these modifications or substitutions do not deviate from the essence of the corresponding technical solutions from the technical solutions of the embodiments of the present application. scope.

Claims

A controller for an active clamp flyback conversion circuit. The active clamp flyback conversion circuit includes a half-bridge circuit, a transformer and a rectifier circuit. The half-bridge circuit includes a main power tube, an auxiliary power tube and Clamping capacitor, the transformer includes a primary winding, a secondary winding and an auxiliary winding circuit, the auxiliary winding circuit supplies power to the power circuit of the controller, characterized in that the controller is used for:

Controlling the active clamp flyback conversion circuit to operate in a continuous operating state so that the output voltage of the active clamp flyback conversion circuit is the rated output voltage;

If it is determined that the output voltage of the active clamp flyback conversion circuit is higher than the first preset value, the active clamp flyback conversion circuit is controlled to run in a suspended working state; the first preset value is less than the first preset value. The overvoltage protection voltage of the active clamp flyback conversion circuit is greater than the rated output voltage of the active clamp flyback conversion circuit;

If it is determined that the output voltage of the auxiliary winding circuit is less than or equal to a second preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the second preset value is less than the rated input voltage of the power circuit and greater than the rated input voltage of the power circuit. The undervoltage protection voltage of the power supply circuit; or,

If it is determined that the output voltage of the power circuit is less than or equal to a third preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the third preset value is less than the rated input voltage of the controller and greater than the rated input voltage of the controller. Controller's undervoltage protection voltage.
The controller according to claim 1, characterized in that the controller is used for:

If it is determined that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the active clamp flyback conversion circuit is controlled to switch from a suspended operating state to a continuous operating state.
The controller according to any one of claims 1-2, characterized in that the controller controls the active clamp flyback conversion circuit to run in a suspended working state, including:

The controller controls both the auxiliary power transistor and the main power transistor of the half-bridge circuit to be turned off.
The controller according to any one of claims 1-3, characterized in that the controller controls the discharge of the clamping capacitor, including:

The controller controls the auxiliary power tube of the half-bridge circuit to be turned on and the main power tube to be turned off; or,

The controller controls the auxiliary power tube of the half-bridge circuit to be periodically turned on and the main power tube to be turned off; or,

The controller controls the auxiliary power transistor and the main power transistor of the half-bridge circuit to periodically alternately turn on and off.
The controller according to any one of claims 1-4, characterized in that the controller is used for:

If it is determined that the capacitance voltage of the clamp capacitor is less than or equal to the preset capacitor voltage value, the clamp capacitor is controlled to stop discharging; the preset capacitor voltage value is when the active clamp flyback conversion circuit operates in continuous operation. The voltage value of the capacitance voltage of the clamping capacitor in the state; or,

If it is determined that the output voltage of the auxiliary winding circuit is greater than or equal to a fourth preset value, the clamp capacitor is controlled to stop discharging; the fourth preset value is less than the overvoltage protection voltage of the power supply circuit and greater than the overvoltage protection voltage of the power supply. The rated input voltage of the circuit; or,

If it is determined that the output voltage of the power circuit is greater than or equal to a fifth preset value, the clamp capacitor is controlled to stop discharging; the fifth preset value is greater than the rated input voltage of the controller and less than the rated input voltage of the controller. Overvoltage protection voltage.
The controller according to claim 5, wherein the controller controls the clamping capacitor to stop discharging, including:

The controller controls the auxiliary power tube of the half-bridge circuit to turn off.
A power module includes an active clamp flyback conversion circuit, an auxiliary winding circuit, a power supply circuit and a controller, and is characterized by including:

The active clamp flyback conversion circuit is used to receive an input voltage, perform voltage conversion processing on the input voltage, and then provide an output voltage to the load; the active clamp flyback conversion circuit includes: a half-bridge circuit, a transformer And a rectifier circuit, the half-bridge circuit includes a main power tube, an auxiliary power tube and a clamping capacitor;

The auxiliary winding circuit is used to supply power to the power circuit;

The power circuit is used to supply power to the controller;

The controller is used for:

Control the active clamp flyback conversion circuit to operate in a continuous working state, and the output voltage of the active clamp flyback conversion circuit is the rated output voltage;

If it is determined that the output voltage of the active clamp flyback conversion circuit is higher than the first preset value, the active clamp flyback conversion circuit is controlled to run in a suspended working state; the first preset value is less than the first preset value. The overvoltage protection voltage of the active clamp flyback conversion circuit is greater than the rated output voltage of the active clamp flyback conversion circuit;

If it is determined that the output voltage of the auxiliary winding circuit is less than or equal to a second preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the second preset value is less than the rated input voltage of the power circuit and greater than the rated input voltage of the power circuit. The undervoltage protection voltage of the power supply circuit; or,

If it is determined that the output voltage of the power circuit is less than or equal to a third preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the third preset value is less than the rated input voltage of the controller and greater than the rated input voltage of the controller. Controller's undervoltage protection voltage.
The power module according to claim 7, characterized in that the controller is used to:

If it is determined that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the active clamp flyback conversion circuit is controlled to switch from a suspended operating state to a continuous operating state.
The power module according to any one of claims 7-8, characterized in that the controller controls the active clamp flyback conversion circuit to run in a suspended working state, including:

The controller controls both the auxiliary power transistor and the main power transistor of the half-bridge circuit to be turned off.
The power module according to any one of claims 7-9, characterized in that the controller controls the discharge of the clamping capacitor, including:

The controller controls the auxiliary power tube of the half-bridge circuit to be turned on and the main power tube to be turned off; or,

The controller controls the auxiliary power tube of the half-bridge circuit to be periodically turned on and the main power tube to be turned off; or,

The controller controls the auxiliary power transistor and the main power transistor of the half-bridge circuit to periodically alternately turn on and off.
The power module according to any one of claims 7-10, characterized in that the controller is used for:

If it is determined that the capacitance voltage of the clamp capacitor is less than or equal to the preset capacitor voltage value, the clamp capacitor is controlled to stop discharging; the preset capacitor voltage value is when the active clamp flyback conversion circuit operates in continuous operation. The voltage value of the capacitance voltage of the clamping capacitor in the state; or,

If it is determined that the output voltage of the auxiliary winding circuit is greater than or equal to a fourth preset value, the clamp capacitor is controlled to stop discharging; the fourth preset value is less than the overvoltage protection voltage of the power supply circuit and greater than the overvoltage protection voltage of the power supply. The rated input voltage of the circuit; or,

If it is determined that the output voltage of the power circuit is greater than or equal to a fifth preset value, the clamp capacitor is controlled to stop discharging; the fifth preset value is greater than the rated input voltage of the controller and less than the rated input voltage of the controller. Overvoltage protection voltage.
The power module according to claim 11, wherein the controller controls the clamping capacitor to stop discharging, including:

The controller controls the auxiliary power tube of the half-bridge circuit to turn off.
An electronic device, including the controller of the active clamp flyback conversion circuit according to any one of claims 1 to 6, or the power module according to any one of claims 7 to 12.