WO2023105896A1 - 電力変換装置およびその制御方法 - Google Patents

電力変換装置およびその制御方法 Download PDF

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Publication number
WO2023105896A1
WO2023105896A1 PCT/JP2022/036012 JP2022036012W WO2023105896A1 WO 2023105896 A1 WO2023105896 A1 WO 2023105896A1 JP 2022036012 W JP2022036012 W JP 2022036012W WO 2023105896 A1 WO2023105896 A1 WO 2023105896A1
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Prior art keywords
switch
control
inductor
period
synchronous rectification
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PCT/JP2022/036012
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English (en)
French (fr)
Japanese (ja)
Inventor
龍介 鹿又
信二 宇治田
健一郎 田中
毅 中屋敷
貴之 廣川
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Panasonic Intellectual Property Management Co Ltd
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Panasonic Intellectual Property Management Co Ltd
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Priority to JP2023566102A priority Critical patent/JPWO2023105896A1/ja
Priority to CN202280081209.8A priority patent/CN118369843A/zh
Priority to US18/713,089 priority patent/US12587100B2/en
Publication of WO2023105896A1 publication Critical patent/WO2023105896A1/ja
Anticipated expiration legal-status Critical
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1588—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load comprising at least one synchronous rectifier element
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0003—Details of control, feedback or regulation circuits
    • H02M1/0009—Devices or circuits for detecting current in a converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present disclosure relates to control of a power conversion device such as a Boost converter.
  • ZVS zero voltage switching
  • SRSW synchronous rectification switch
  • CTLW control switch
  • inductor in order to achieve ZVS, the dead time from when SRSW is turned off to when CTLSW is turned on is set as a resonance period, and the parasitic A resonance phenomenon occurs between the capacitor and the inductor.
  • the amplitude of the resonant voltage can be increased and the drain-source voltage VDS_CTL of CTLSW can reach 0V, thus achieving ZVS.
  • Autonomous search control is a method of detecting a characteristic portion of a waveform indicating circuit operation and performing control based on the detected timing.
  • Patent Document 1 has the following problems. That is, in order to detect the drain-source voltage V DS_CTL of CTLSW, it is necessary to provide a voltage detection circuit. Become. Also, in a device such as a totem-pole PFC converter in which the assignment of CTLSW and SRSW is interchanged, it is necessary to provide a voltage detection circuit for both switches. Therefore, the circuit area of the power converter increases. Also, since the voltage detection circuit detects a voltage that fluctuates sharply, it is susceptible to noise caused by the voltage fluctuation itself.
  • the present disclosure has been made in view of this point, and aims to make it possible to realize autonomous search control for ZVS without causing an increase in circuit area or a decrease in reliability due to the influence of noise for a power conversion device. aim.
  • a power converter includes a main circuit unit that performs a step-up operation or a step-down operation, and a control unit that controls operation of the main circuit unit, the main circuit unit including a first node and a a first switch and a second switch connected in series between two nodes; an inductor connected between a third node and a connection node of the first and second switches; a current detection unit for detecting the positive or negative of the current, wherein the control unit defines one of the first and second switches as a synchronous rectification switch and the other as a control switch; orienting, in each switching cycle, turning on the control switch with the synchronous rectification switch off, then turning off, then turning on the synchronous rectification switch with the control switch off, and then The inductor is turned off, and a detection result is acquired from the current detection unit at detection timing that is a predetermined period before the timing at which the synchronous rectification switch is switched from on to off in the first switching cycle, and the inductor indicated
  • Example of basic configuration of the present disclosure Timing chart showing the operation of the configuration of FIG. (a) to (c) are examples of changes in inductor current Examples of autonomous search control in the present disclosure
  • Configuration example of the power converter according to the first embodiment Configuration example of the current detector (a) and (b) show the operation per switching cycle of the power converter according to the first embodiment.
  • Operation per Control Cycle of Power Conversion Device According to Embodiment 1 Configuration example of power converter according to embodiment 1-1 Operation per switching cycle of power converter according to embodiment 1-1 Operation per switching cycle of power converter according to embodiment 1-1
  • Configuration example of the power conversion device according to the second embodiment are diagrams showing the operation of the power converter according to the third embodiment.
  • Configuration example of power converter according to embodiment 4 (a) and (b) are diagrams showing the operation of the power converter according to the fourth embodiment.
  • a power converter includes a main circuit unit that performs a step-up operation or a step-down operation, and a control unit that controls operation of the main circuit unit, the main circuit unit including a first node and a a first switch and a second switch connected in series between two nodes; an inductor connected between a third node and a connection node of the first and second switches; a current detection unit for detecting the positive or negative of the current, wherein the control unit defines one of the first and second switches as a synchronous rectification switch and the other as a control switch; orienting, in each switching cycle, turning on the control switch with the synchronous rectification switch off, then turning off, then turning on the synchronous rectification switch with the control switch off, and then The inductor is turned off, and a detection result is acquired from the current detection unit at detection timing that is a predetermined period before the timing at which the synchronous rectification switch is switched from on to off in the first switching cycle, and the
  • the positive or negative of the inductor current is detected by the current detection unit at detection timing that is a predetermined period before the timing at which the synchronous rectification switch is switched from on to off. Based on the sensed sign of the inductor current, the on period of the synchronous rectification switch is corrected in the second switching cycle. Therefore, autonomous search control for ZVS can be realized without increasing the circuit area or reducing reliability.
  • control unit may set, as the predetermined period, a period during which the inductor current is estimated to be zero at the detection timing in an ideal operating state.
  • the detection timing of the inductor current can be set appropriately.
  • control unit uses the input voltage value and the output voltage value of the power conversion device, the inductance value of the inductor, the parasitic capacitance value of the first switch, and the parasitic capacitance value of the second switch to determine the A predetermined period may be calculated.
  • the control unit When the inductor current indicated by the detection result is positive, the control unit lengthens the ON period of the synchronous rectification switch, and when the detection result is negative, shortens the ON period of the synchronous rectification switch. good too.
  • control unit may correct the ON period of the control switch according to the correction.
  • the ratio between the ON period of the control switch and the ON period of the synchronous rectification switch can be appropriately maintained.
  • control unit may correct the period from when the synchronous rectification switch is turned off until when the control switch is turned on, according to the correction. .
  • the resonance period can be kept in an appropriate state.
  • the current detection unit may include a shunt resistor connected in series with the inductor, and detect whether the inductor current is positive or negative based on the voltage across the shunt resistor.
  • the second switching cycle may be a cycle immediately following the first switching cycle.
  • the response speed can be increased.
  • control unit operates according to a control cycle including m (m is an integer equal to or greater than 1) switching cycles, and in any switching cycle included in the first control cycle, at the detection timing, the acquiring a detection result from the current detection unit, and correcting the ON period of the synchronous rectification switch in a second control cycle after the first control cycle based on the sign of the inductor current indicated by the detection result; good too.
  • the second control cycle may be a control cycle immediately after the first control cycle.
  • the response speed can be increased.
  • the second control cycle may be a control cycle after the first control cycle.
  • the power conversion device includes a main circuit unit that performs step-up operation or step-down operation, and the main circuit unit includes a first node and a second node. a first switch and a second switch connected in series between; an inductor connected between a third node and a connection node of the first and second switches; and a positive or negative current flowing through the inductor.
  • the control method defines one of the first and second switches as a synchronous rectification switch and the other as a control switch, and detects the positive current of the inductor current.
  • the positive or negative of the inductor current is detected by the current detection unit at detection timing that is a predetermined period before the timing at which the synchronous rectification switch is switched from on to off. Based on the sensed sign of the inductor current, the on period of the synchronous rectification switch is corrected in the second switching cycle. Therefore, autonomous search control for ZVS can be realized without increasing the circuit area or reducing reliability.
  • FIG. 1 (embodiment) The approach of the present disclosure will be described using FIGS. 1 to 4.
  • FIG. 1 is a diagrammatic representation of FIG. 1 to 4.
  • FIG. 1 is an example of the basic configuration of the present disclosure.
  • a synchronous rectification switch (arbitrarily called “SRSW”) 1 and a control switch (arbitrarily called “CTLSW”) 2 are connected in series.
  • One end of an inductor 3 is connected to a connection node between SRSW1 and CTLSW2.
  • a current detection unit (current detection circuit) 4 is provided to detect a current i L (hereinafter referred to as “inductor current”) flowing through the inductor 3 .
  • the configuration of FIG. 1 is included in, for example, a power converter such as a Boost converter.
  • FIG. 2 is a timing chart showing the operation of the configuration of FIG. FIG. 2 shows temporal changes in the gate-source voltage V GS_CTL of CTLSW2, the gate-source voltage V GS_SR of SRSW1, the current i L flowing through the inductor 3, and the drain-source voltage V DS_CTL of CTLSW2.
  • the drain-source voltage V DS_CTL of CTLSW2 is detected, and based on this, the ON period T OFF of SRSW1 is corrected.
  • the current iL flowing through the inductor 3 is sensed instead of the voltage VDS_CTL , and based on this, the ON period TOFF of the SRSW1 is corrected.
  • the timing for detecting the inductor current iL is set to the timing preceding the time when the SRSW1 is turned off by a predetermined period of time Text .
  • This detection timing is the timing at which the inductor current iL is assumed to be zero in the ideal operating state.
  • the control unit determines the ideal The on-period and off-period of each switch and their timing are calculated so as to realize a realistic ZVS.
  • the ideal operating state means a state in which the actual waveform is consistent with the virtual waveform that is considered to be realized by the calculated on-period and off-period and their timing plus the correction by the autonomous search control. do.
  • T1 is the timing at which the SRSW1 turns off
  • T2 is the detection timing that precedes the timing T1 by a predetermined period T ext .
  • i L 0 at detection timing T2
  • a negative current is appropriate at timing T1
  • ideal ZVS can be achieved.
  • FIG. 3B when i L >0 at the detection timing T2, the negative current is insufficient at the timing T1, so the resonance energy is insufficient and ZVS cannot be achieved.
  • FIG. 3C when i L ⁇ 0 at the detection timing T2, the negative current becomes excessive at the timing T1, and the efficiency deteriorates.
  • FIG. 4 shows an example of autonomous search control in this disclosure.
  • the period TOFF during which the SRSW1 is on is lengthened.
  • the correction value ⁇ t is added to the period TOFF_n in a certain switching cycle to determine the period TOFF_n +1 in the next switching cycle.
  • the correction value ⁇ t may be subtracted from the period T OFF_n to determine the period T OFF_n+1 in the next switching cycle.
  • the positive/negative (polarity) of the current iL flowing through the inductor 3 is detected at a timing that is assumed to be zero in the ideal operating state. Then, the deviation from the ideal operation is corrected depending on whether the detected inductor current iL is positive or negative. That is, when the detected inductor current iL is positive, the period TOFF during which CTLSW2 is off and SRSW1 is on is lengthened. When the sensed inductor current iL is negative, the period TOFF is shortened.
  • the use of inductor current detection is superior to voltage detection in terms of circuit scale and reliability. That is, the current detection unit 4 only needs to be able to detect the direction of the current flowing through the inductor 3, so the circuit area is smaller than that of the voltage detection circuit. Also, even in a device such as a totem-pole PFC converter in which CTLSW and SRSW are interchanged, only one current detection unit is required. In addition, since current fluctuations are gentler than voltage fluctuations, noise is less likely to be superimposed during detection.
  • FIG. 5 shows a specific configuration example of a boost converter (DCDC step-up converter) as a power converter according to the first embodiment.
  • a boost converter DCDC step-up converter
  • SRSW synchronous rectification switch
  • CTLSW control switch
  • a gate driver 15 is connected to the gate terminals of the SRSW11 and CTLSW12.
  • An inductor 13 is connected between the node n3 and a connection node n4 between the SRSW11 and the CTLSW12.
  • An output capacitor 16 is arranged between nodes n1 and n2, and an input capacitor 17 is arranged between nodes n3 and n2.
  • the control unit 20 controls switching operations of the SRSW 11 and CTLSW 12 via the gate driver 15 . Further, the main circuit section 10 is provided with a current detection section 14 that detects the direction of the current flowing through the inductor 13 . The control unit 20 acquires the detection result of the current detection unit 14 at a predetermined timing. Here, it is assumed that the current of the inductor 13 is directed to the right in the drawing, that is, the direction toward the connection node n4 of the SRSW11 and the CTLSW12 is the positive direction. In addition, in FIG. 5, the current detection unit 14 is provided between the inductor 13 and the node n3, but the current detection unit 14 may be provided between the inductor 13 and the connection node n4. The same applies to the following examples.
  • An input power supply 21 is connected between the node n3 and the node n2.
  • a load 22 is connected between the node n1 and the node n2.
  • an input voltage detection unit and an output voltage detection unit are provided, and the control unit 20 acquires an input voltage value from the input voltage detection unit and an output voltage value from the output voltage detection unit. do.
  • FIG. 6 is a specific configuration example of the current detection unit 14.
  • the current detector 14 has a shunt resistor 141 provided in series with the inductor 13 , a comparator 142 , an isolator 143 and a D flip-flop 144 .
  • a voltage corresponding to the current flowing through the inductor 13 is generated across the shunt resistor 141 .
  • Comparator 142 determines the direction of the voltage developed across shunt resistor 14 .
  • the isolator 143 changes the reference potential of the output of the comparator 142 so that it can be processed by the signal system.
  • the D flip-flop 144 holds the output of the isolator 143 at a predetermined timing according to an instruction from the control section 20 . Note that the configuration of the current detection unit 14 is not limited to that shown in FIG.
  • FIGS. 7(a) and 7(b) show the operation in an ideal operating state per switching cycle of the Boost converter.
  • the operation shown in FIG. 7 is realized by the control unit 20 controlling the on/off of the SRSW11 and CTLSW12.
  • the CTLSW 12 is on, the SRSW 11 is off, and a positive current i L flows through the inductor 13 (period T on ).
  • inductor current i L gradually increases and energy is stored in inductor 13 .
  • step (2) the CTLSW 12 is turned off, and after the drain-source voltage V DS_CTL of the CTLSW 12 rises to the output voltage V out due to resonance, the SRSW 11 is turned on (period T dbfed ).
  • step (3) the CTLSW 12 is off, the SRSW 11 is on, and a positive current i L flows through the inductor 13 (period T off ). During the period Toff , the inductor current iL gradually decreases and power is transferred to the output side.
  • step (4) a negative-going current i L flows through the inductor 13 and energy is stored in the inductor 13 (period T ext ).
  • step (5) SRSW 11 is turned off and CTLSW 12 is turned on after resonance causes the voltage V DS_CTL to drop to zero (period T dbred ).
  • step (6) the CTLSW 12 is on, the SRSW 11 is off, and the current i L in the negative direction flows through the inductor 13 (period T extoff ). During the period T extoff , the inductor current i L flowing in the negative direction gradually decreases.
  • control unit 20 acquires the sign of the current iL flowing through the inductor 13 detected by the current detection unit 14 at the timing when step (3) is assumed to end.
  • the control unit 20 sets this detection timing to a timing that is a period T ext as a predetermined period before the timing at which the SRSW 11 is switched from on to off (the timing at which step (4) ends).
  • the control unit 20 sets a period during which the inductor current is estimated to be zero at the detection timing as the period T ext .
  • control unit 20 can theoretically calculate the period T ext using the input voltage value and output voltage value of the Boost converter, the inductance value of the inductor 13, the parasitic capacitance value of the SRSW 11, and the parasitic capacitance value of the CTLSW 12. can.
  • control unit 20 controls the period T ext and the period T dbred and the period T based on the resonance period of the inductor 13 and the parasitic capacitances of the SRSW 11 and CTLSW 12, the input voltage, and the difference between the input voltage and the output voltage . extoff can be calculated.
  • the control unit 20 corrects the deviation from the ideal operation according to whether the detected inductor current iL is positive or negative. That is, when the detected inductor current iL is positive, the period during which the SRSW 11 is turned on is lengthened. When the detected inductor current iL is negative, the period during which SRSW 11 is on is shortened.
  • FIG. 8 shows the operation per control cycle of the Boost converter.
  • m is an integer equal to or greater than 1 switching cycles are executed per control cycle.
  • the control unit 20 acquires the input voltage and the output voltage at the start of the control cycle. Then, based on the input voltage value, output voltage value, average output current value, inductance value, etc., the length of each period (referred to as a calculated value) shown in FIG. 7 is calculated so as to realize ideal ZVS. do.
  • the control unit 20 starts executing the control cycle N, and executes m switching cycles using the calculated values for each period. In the mth switching cycle, the polarity (positive or negative) of the inductor current iL is detected. The detection result is held until the detection timing of the next control cycle N+1.
  • the control unit 20 corrects the ON period of the SRSW 11 in the control cycle N+1 based on the detection result of the inductor current polarity in the control cycle N ⁇ 1.
  • the control unit 20 corrects the period Toff .
  • the period T dbred and the period T extoff are also corrected.
  • the correction according to the present disclosure can be performed in units of control cycles. Further, by performing correction in the next control cycle N+1 based on the detection result of the inductor current polarity in the control cycle N ⁇ 1, sufficient calculation time can be secured. It should be noted that, based on the detection result of the inductor current polarity in a certain control cycle, correction may be made in the subsequent control cycles. Also, in FIG. 8, the inductor current polarity is detected in the m-th switching cycle, but the inductor current polarity may be detected in other switching cycles. However, by sensing the inductor current polarity in the last mth switching cycle, the correction is more accurate.
  • the period T extoff in accordance with the correction of the period T off , the ratio between the ON period of the SRSW 11 and the ON period of the CTLSW 12, that is, the duty can be prevented from deviating from the calculated value.
  • the period T_dbred in accordance with the correction of the period Toff , it is possible to maintain an appropriate state for the resonance period. That is, when correcting the ON period of the SRSW 11, it is preferable to correct the ON period of the CTLSW 12 according to the correction. Further, when correcting the ON period of the SRSW 11, it is preferable to correct the period from when the SRSW 11 is turned off until when the CTLSW 12 is turned on, according to the correction.
  • the relationship between the switching cycle for detecting the inductor current polarity and the switching cycle for correcting the ON period of the SRSW 11 is not limited to the one shown above.
  • the inductor current polarity may be detected in one switching cycle, and the ON period of the SRSW 11 may be corrected in the immediately following switching cycle.
  • the ON period of the SRSW 11 is quickly corrected based on the positive/negative of the detected inductor current, so the response speed can be increased.
  • the inductor current polarity may be detected in a switching cycle of a certain control cycle, and the ON period of the SRSW 11 may be corrected in the immediately following control cycle.
  • the ON period of the SRSW 11 in the immediately following control cycle is quickly corrected based on the positive/negative of the detected inductor current, so the response speed can be increased.
  • a minute correction width may be used for one correction, and by repeating the correction, the ON period of the SRSW 11 may be corrected with a correction value obtained by integrating the minute correction width.
  • FIG. 9 shows a specific configuration example of a Boost converter using coupled inductors as a power converter according to Example 1-1.
  • the SRSW 11, CTLSW 12, and inductor 13, which are the components of the Boost converter of FIG. 5, are connected in parallel as one phase. That is, the first phase comprises SRSW1 11a, CTLSW1 12a and inductor L1 13a, and the second phase comprises SRSW2 11b, CTLSW2 12b and inductor L2 13b.
  • Inductor L1 13a and inductor L2 13b are magnetically coupled coupled inductors.
  • the current detector 14 may be provided in at least one phase. In the configuration example of FIG. 9, the current detector 14 is provided only in the first phase.
  • FIG. 10 and 11 illustrate the operation of the Boost converter of FIG. 9 under ideal operating conditions per switching cycle.
  • a Boost converter using a coupled inductor changes its operating waveform depending on the duty and the coupling coefficient.
  • FIG. 10 shows operation waveforms of an example thereof.
  • FIG. 11 shows the operation per switching cycle for the first phase.
  • the Boost converter in FIG. 9 basically operates in the same way as the Boost converter in FIG. In step (1) (period T on ), the CTLSW1 12a is on and the SRSW1 11a is off, and a positive current flows through the inductor L1 13a . It changes according to the direction of the current flowing through the two-phase inductor L2 13b.
  • step (6) (period T extoff ), CTLSW1 12a is on and SRSW1 11a is off, and a negative current flows through inductor L1 13a. It changes according to the direction of the current flowing through the inductor L2 13b of the second phase. The operation of the second phase is shifted from the operation of the first phase by half the switching period.
  • FIG. 12 shows a specific configuration example of a Buck converter (DCDC step-down converter) as a power converter according to the second embodiment.
  • the positions of the input power source 21 and the load 22 are switched, the input power source 21 is connected between the node n1 and the node n2, and the load 22 is connected between the node n3 and the node n2.
  • the current in the inductor 13 assumes that the leftward direction in the drawing, that is, the direction away from the connection node n4 between the CTLSW31 and the SRSW32, is the positive direction.
  • the operation of the Buck converter in FIG. 12 is similar to that of the Boost converter in FIG. 5, and the operations shown in FIGS. 7 and 8 apply as they are.
  • the control section 20B can control the main circuit section 30 in the same manner as the control section 20 of the Boost converter in FIG.
  • FIG. 13 shows a specific configuration example of a totem pole PFC converter (ACDC converter) as a power converter according to the third embodiment.
  • ACDC converter totem pole PFC converter
  • the switches SW2 and SW1 are connected in series between the nodes n1 and n2, and the switches SW4 and SW3 are connected in series.
  • Each of the switches SW1 to SW4 is a transistor having a gate terminal, a drain terminal and a source terminal.
  • a gate driver 45 is connected to the gate terminals of the switches SW1 to SW4.
  • An inductor 13 is connected between the node n3 and the connection node n4 of the switches SW1 and SW2.
  • An AC input power supply 23 is connected between the node n3 and the connection node n5 of the switches SW3 and SW4.
  • An output capacitor 46 is arranged between node n1 and node n2.
  • a load 24 is connected between node n1 and node n2.
  • the control unit 20C controls the switching operations of the switches SW1 to SW4 via the gate driver 45.
  • the switches SW1 and SW2 are assigned CTLSW or SRSW according to the polarity of the AC input power supply 23.
  • FIG. The switches SW3 and SW4 are switched on/off according to the polarity of the AC input power supply 23.
  • the main circuit section 40 is provided with a current detection section 14 that detects the direction of the current flowing through the inductor 13 .
  • 20 C of control parts acquire the detection result of the electric current detection part 14 at a predetermined timing.
  • the direction of the current in the inductor 13 is defined according to the polarity of the AC input power supply 23, as shown in FIG. 14(b).
  • the control unit 20C sets the switches SW1 to SW4 based on the polarity of the AC input power supply 23 when starting the control cycle. For example, when the polarity of the AC input power supply 23 is L: positive and N: negative, the switch SW1 is assigned to CTLSW and the switch SW2 is assigned to SRSW. Also, the switch SW3 is set to ON, and the switch SW4 is set to OFF. In this state, the control section 20C controls the main circuit section 40 in the same manner as the control section 20 of the boost converter in FIG. When the polarity of the AC input power supply 23 is L: negative and N: positive, the switch SW1 is assigned to SRSW, and the switch SW2 is assigned to CTLSW. Also, the switch SW3 is set to OFF, and the switch SW4 is set to ON. In this state, the control section 20C controls the main circuit section 40 in the same manner as the control section 20 of the boost converter in FIG.
  • FIG. 15 shows a specific configuration example of an inverter (DCAC converter) as a power converter according to the fourth embodiment.
  • the switches SW2 and SW1 are connected in series between the nodes n1 and n2, and the switches SW4 and SW3 are connected in series.
  • Each of the switches SW1 to SW4 is a transistor having a gate terminal, a drain terminal and a source terminal.
  • a gate driver 55 is connected to the gate terminals of the switches SW1 to SW4.
  • An inductor 13 is connected between the node n3 and the connection node n4 of the switches SW1 and SW2.
  • a load 24 is connected between the node n3 and the connection node n5 of the switches SW4 and SW3.
  • An input capacitor 56 is arranged between node n1 and node n2.
  • Input power supply 25 is connected between node n1 and node n2.
  • the control unit 20D controls the switching operations of the switches SW1 to SW4 via the gate driver 55.
  • the switches SW1 and SW2 are assigned CTLSW or SRSW depending on the polarity of the AC output voltage to be output.
  • the switches SW3 and SW4 are switched on/off according to the polarity of the AC output voltage to be output.
  • the main circuit section 50 is provided with a current detection section 14 that detects the direction of the current flowing through the inductor 13 .
  • the control unit 20D acquires the detection result of the current detection unit 14 at a predetermined timing.
  • the direction of the current in the inductor 13 is defined according to the polarity of the AC output voltage to be output, as shown in FIG. 16(b).
  • the control unit 20D sets the switches SW1 to SW4 based on the polarity of the AC output voltage to be output. For example, when the polarity of the AC output voltage to be output is L: positive and N: negative, the switch SW1 is assigned to SRSW and the switch SW2 is assigned to CTLSW. Also, the switch SW3 is set to ON, and the switch SW4 is set to OFF. In this state, the control section 20D controls the main circuit section 50 in the same manner as the control section 20B of the Buck converter in FIG. When the polarity of the AC output voltage to be output is L: negative and N: positive, the switch SW1 is assigned to CTLSW and the switch SW2 is assigned to SRSW. Also, the switch SW3 is set to OFF, and the switch SW4 is set to ON. In this state, the control section 20D controls the main circuit section 50 in the same manner as the control section 20B of the Buck converter in FIG.
  • the power conversion device includes a main circuit unit that performs step-up operation or step-down operation, and the main circuit unit is connected in series between the first node and the second node.
  • An inductor connected between the first and second switches, a third node, and a connection node of the first and second switches, and a current detection unit that detects whether the current flowing through the inductor is positive or negative.
  • One of the first and second switches is a synchronous rectification switch and the other is a control switch.
  • the current detection unit detects whether the inductor current is positive or negative at detection timing that is a predetermined period after the timing at which the synchronous rectification switch switches from on to off. Based on the sensed sign of the inductor current, the on duration of the synchronous rectification switch is corrected in subsequent switching cycles. Therefore, in the power conversion device, autonomous search control for ZVS can be realized without causing an increase in circuit area or a decrease in reliability.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)
PCT/JP2022/036012 2021-12-10 2022-09-27 電力変換装置およびその制御方法 Ceased WO2023105896A1 (ja)

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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007151271A (ja) * 2005-11-25 2007-06-14 Matsushita Electric Ind Co Ltd Ｄｃ−ｄｃコンバータ
WO2012144249A1 (ja) * 2011-04-18 2012-10-26 三菱電機株式会社 電力変換装置およびそれを備えた車載電源装置
JP2014011940A (ja) * 2012-07-03 2014-01-20 Tdk Corp 電流共振型ｄｃｄｃコンバータ
WO2020202967A1 (ja) * 2019-04-02 2020-10-08 株式会社オートネットワーク技術研究所 車載用電圧変換装置

Family Cites Families (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7598715B1 (en) * 2007-04-04 2009-10-06 National Semiconductor Corporation Apparatus and method for reverse current correction for a switching regulator
US9325243B2 (en) * 2013-05-23 2016-04-26 Micrel, Inc. Boost regulator incorporating peak inductor current modulation
US9431896B2 (en) 2013-12-19 2016-08-30 Texas Instruments Incorporated Apparatus and method for zero voltage switching in bridgeless totem pole power factor correction converter
US11848608B2 (en) * 2022-03-23 2023-12-19 Alpha And Omega Semiconductor International Lp Circuit and method for controlling switching regulator with ultrasonic mode

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2007151271A (ja) * 2005-11-25 2007-06-14 Matsushita Electric Ind Co Ltd Ｄｃ−ｄｃコンバータ
WO2012144249A1 (ja) * 2011-04-18 2012-10-26 三菱電機株式会社 電力変換装置およびそれを備えた車載電源装置
JP2014011940A (ja) * 2012-07-03 2014-01-20 Tdk Corp 電流共振型ｄｃｄｃコンバータ
WO2020202967A1 (ja) * 2019-04-02 2020-10-08 株式会社オートネットワーク技術研究所 車載用電圧変換装置

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