WO2023102905A1 - 双极化天线 - Google Patents

双极化天线 Download PDF

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Publication number
WO2023102905A1
WO2023102905A1 PCT/CN2021/137141 CN2021137141W WO2023102905A1 WO 2023102905 A1 WO2023102905 A1 WO 2023102905A1 CN 2021137141 W CN2021137141 W CN 2021137141W WO 2023102905 A1 WO2023102905 A1 WO 2023102905A1
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WO
WIPO (PCT)
Prior art keywords
dual
polarized antenna
circuit board
printed circuit
dipole
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PCT/CN2021/137141
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English (en)
French (fr)
Inventor
塔拉年科·弗拉基米尔
李梓萌
斯列德科夫·维克托·阿莱克桑德罗维奇
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广州司南技术有限公司
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Publication of WO2023102905A1 publication Critical patent/WO2023102905A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/50—Feeding or matching arrangements for broad-band or multi-band operation

Definitions

  • the present invention relates to a dual polarized antenna, and more particularly, to an antenna capable of transmitting/receiving two orthogonal polarizations in vertical and horizontal directions or +/- 45 degree inclination.
  • US patent US5940044 describes a dual obliquely polarized antenna with a half power beamwidth of approximately 65 degrees in the horizontal plane.
  • the antenna includes a plurality of dipole arrays, and each sub-array includes four dipoles arranged in a rhombus (diamond shape).
  • US patents US6333720B1 , US6529172B2 and US2010/0309084A1 contain drawings of other radiators with dipole square shapes. The dipole's balun is angled to the center of the dipole square to simplify fabrication, but despite this new shape, the devices are still complex to make.
  • US patent US6313809B1 describes a dual polarized radiator (dual polarized radiator) comprising four dipoles, uniformly arranged above a reflector and in a dipole square matrix form when viewed from a top view. Such dipoles are described in US6940465B2, US7688271B2, CN202423543U, CN202268481U, CN101916910A, CN102097677A, CN102694237A, CN710714, CN717214. Most known dual-polarized radiators of dipole square arrays are excited by four coaxial cables welded to the radiator through their inner and outer conductors, such as the bipolar radiator described in the patent CN102013560A antenna.
  • the first drawback of known dual-polarized antennas is the complex feed network consisting of four cables connecting the four dipoles and the beamforming network, usually placed on the other side of the reflector. Most of these cables are connected in parallel with another cable connected to the beamforming network.
  • the second disadvantage is that since the feeder cable is directly connected to the dipole, the operating frequency band is limited, resulting in this antenna having no matching circuit between the dipole and the feeder cable.
  • aluminum radiators must be covered with tin film to solder the cables.
  • the need to use a tinning process is a third disadvantage, as tinning of large radiators increases manufacturing costs.
  • the object of the present invention is to overcome the disadvantages of the prior art and other known dual polarized antennas.
  • the first purpose of the present invention is to develop a broadband dual-polarized antenna that is simply connected to the beamforming network, and the second purpose is to reduce the production cost of a large antenna whose operating frequency is lower than 1 GHz.
  • the third purpose is to reduce the back radiation of the dual polarized antenna.
  • the invention provides a dual-polarized antenna, which includes a radiation unit composed of four conductive elements, four support elements, a feed unit and a reflector; wherein the cross opening slot at the center of the radiation unit connects the four conductive elements to each other separate, the tops of the four supporting elements are directly connected to the conductive elements one by one, and the bottoms of the four supporting elements are fixed on the reflector; wherein the feeding unit includes a radiation unit placed on the upper surface of the conductive element
  • the printed circuit board in the central area of the printed circuit board and two coaxial cables placed along the support element and connected to the conductive layer covering the lower surface of the printed circuit board through the outer conductor, while passing through Its inner conductor is connected to the first ends of the two striplines on the upper surface of the printed circuit board, and the conductive layer and the two striplines on the printed circuit board form a match with the two coaxial cables.
  • the conductive layer covering the lower surface of the printed circuit board includes a cross opening groove, and the cross opening groove divides the conductive layer into four parts, which are placed correspondingly to the four conductive elements of the radiation unit;
  • the strip line passes through the cross opening slot at the center of the cross opening slot, and the second end of the strip line is connected to the coupling element.
  • the reflective plate includes a cross-shaped open slot disposed between the bottom ends of the support elements.
  • 1-15 illustrate some embodiments of a dual polarized antenna.
  • the dual polarized antenna according to the invention provides a wider frequency band, with the result that the feeding element comprises a matching circuit connected between the radiating means and the feeding coaxial cable. Therefore, by adjusting the size of the stripline forming the matching circuit, it is possible to better match the dual-polarized antenna with the feeding coaxial cable through a wide frequency band.
  • the dual-polarized antenna according to the invention can have the advantage of less back radiation, with the result that the cross-open slots in the reflector between the bottom ends of the support elements generate additional radiation in the back, Thereby suppressing the back radiation generated by the radiation unit.
  • Figure 1 is a side view of a first embodiment of a dual-polarized antenna according to the present invention, wherein the radiating element consists of two crossed dipoles formed by a supporting element on the surface above the reflector The feed unit on the dipole arm is excited.
  • FIG. 2 is a diagrammatic side view of a portion of the dual-polarized antenna shown in FIG. 1 .
  • Figure 3 is a side view of another dipole arm and support element.
  • Figures 4a-4f are top and bottom views, respectively, of a printed circuit board including striplines forming a matching circuit and coupling elements of different configurations.
  • each arm of a crossed dipole comprising two side metal pieces, and a middle metal piece connecting the side metal pieces.
  • the reflector includes cross-opening slots between the support elements.
  • FIG. 6 is a side view of another embodiment of a dual polarized antenna, each crossed dipole arm comprising two side metal pieces connected to the support element, additional metal pieces connected to the two side metal pieces and separated by a dielectric film .
  • Fig. 7 is a side view of another embodiment of the dual-polarized antenna, the radiating element comprises four dipoles arranged in a dipole square array, excited by the feeding element, and connected to the line of symmetry, the line of symmetry is formed by the conductor and Adjacent conductive support elements are formed.
  • Fig. 8 is a side view of another embodiment of a dual-polarized antenna.
  • the dipole arms are arranged in a dipole array and bent from the plane where the line of symmetry lies, pointing towards the direction of the reflector.
  • Figure 9 is a side view of another example of a dual-polarized antenna, the dipole arms are arranged in a dipole array and bent from the plane of the symmetry line, facing away from the reflector.
  • Fig. 10 is a side view of another embodiment of a dual polarized antenna, the arms of each dipole are fed by a line of symmetry, and the arms are bent towards the center of the radiating element, away from the direction of the reflector.
  • Fig. 11 is a partial side view of the radiating element shown in Fig. 10, made of a single metal plate.
  • Fig. 12 is a side view of another embodiment of the dual-polarized antenna.
  • the radiating unit includes four folded dipoles arranged in a square dipole array, connected to the line of symmetry, and excited by the feeding unit.
  • Fig. 13 is another side view of the dual-polarized antenna, the conductor at the end of the folded dipole arm is bent from the plane where the line of symmetry is located, and faces the direction of the reflector.
  • Fig. 14 is a side view of another embodiment of a dual-polarized antenna, the folded dipole includes a dielectric element, and is bent from the plane of the symmetry line, and away from the direction of the reflector.
  • Fig. 15 is a side view of another embodiment of a dual-polarized antenna, the supporting element and the radiating element comprising four folded dipoles are made of a single metal plate.
  • Fig. 1 is a side view of a first embodiment of a dual-polarized antenna of the present invention.
  • the present invention provides a dual-polarized antenna comprising a radiating unit, the radiating unit comprises 1-4 four conductive elements, which are respectively separated independently by a cross opening slot 5 in the center of the radiating unit, and the tops of the four supporting elements 6a-6d are directly connected to The conductive elements are connected, the bottom end is connected with the reflection plate 7 and fixed on the reflection plate, and a feed unit is also included.
  • the feeding unit comprises a printed circuit board 8 placed in the middle of the radiating unit, on the upper surface of the conductive elements 1-4, and two coaxial cables 9a and 9b placed along the supporting elements 6a and 6b, the coaxial cables 9a and 9b passing through
  • the outer conductor is connected to a conductive layer covering the bottom surface of the printed circuit board 8 .
  • the inner conductors 10a and 10b of the coaxial cables 9a and 9b are connected to the first ends 11a and 11b of the strip conductors 12a and 12b placed on the upper surface of the printed circuit board 8, the conductive layer and the strip conductors on the printed circuit board 8
  • the conductors 12a and 12b and the coaxial cables 9a and 9b form two matching circuits that match the radiation elements.
  • the coupling elements 13a and 13b generate capacitive coupling between the second ends of the strip conductors 12a and 12b and the conductive element 3, so that when the coaxial cable 9a is excited, the first radiation unit formed by the conductive elements 1 and 3 radiates electromagnetic waves .
  • the E-vector of the radiated first electromagnetic wave points along the arrow Ea.
  • the second radiation unit formed by the conductive elements 2 and 4 radiates electromagnetic waves.
  • the E-vector of the radiated second electromagnetic wave points along the arrow Eb and is perpendicular to the arrow Ea. Therefore, the dual-polarized antenna according to the present invention radiates two electromagnetic waves having orthogonal polarizations.
  • the shape of the radiation beam depends on the shape of the radiating elements.
  • the provided dual polarized antenna may comprise different kinds of radiating elements.
  • the conductive elements 1-4 shown in Figure 1 form two crossed dipoles.
  • the support elements 6a-6d form two crossed dipoles of these dipoles.
  • the support element 6a is part of the conductive element 1 (dipole arm) shown in Figure 2, which comprises two side metal pieces 14a and 14b.
  • FIG. 3 Another shape of the dipole arms and support elements is shown in Fig. 3, where the side metal pieces 15a and 15b have a rectilinear shape. Metal portions 16a and 16b at their edges are bent downwards to increase the coupling between the crossed dipole arms. The metal portions 17a and 17b at the edges of the support element 18 are bent to increase the coupling with the coaxial cable arranged along the support element 18 and to increase the suppression of leakage waves propagating along the outer conductor of the coaxial cable.
  • a crossed dipole with arms of this shape can be used as the low-band radiating element of a dual-band antenna because space is provided between the low-band and high-band radiating elements.
  • 4a and 4b are respectively a top view and a bottom view of the printed circuit board 8 shown in FIG. 1 .
  • the strip conductors 12a and 12b placed on the upper surface of the printed circuit board 8 form coupling elements 13a and 13b in the shape of a rectangular plate and two matching circuits.
  • Metallized holes 19 connect the strip conductors 12b to the strip conductors 20 provided at the bottom surface of the printed circuit board 8 .
  • a metallized hole 21 connects the strip conductor 20 to the coupling element 13b.
  • the conductive layer covering the bottom of the printed circuit board includes a cross opening groove 22, which divides the conductive layer into four parts 23a-23d, which are respectively placed on the opposite sides of the four conductive elements 1-4.
  • the strip conductor 20 is provided at the center of the cross opening groove 22 .
  • the branch of the cross opening groove 22 is arranged on the opposite side of the branch of the cross opening groove 5 .
  • the printed circuit board 8 is secured to the conductive elements 1-4 arranged in the holes 24 by means of plastic screws or rivets (not shown).
  • the impedance of a radiating element depends on its shape and operating frequency band, so the strip conductors forming the matching circuit and the coupling elements of different radiating elements have different configurations and may comprise different elements.
  • FIG. 4c and 4d are top and bottom views, respectively, of another embodiment of the present invention in which the printed circuit board 25 includes coupling elements 26a and 26b of open stubs, creating a short near the cross-opening slot 22.
  • FIG. Coupling elements 26 a and 26 b respectively connect strip conductors 27 a and 27 b to portions 23 d and 23 c of the conductive layer covering the bottom side of printed circuit board 25 . This frequency-dependent connection produces an attenuation pole at higher frequencies.
  • Shorting stubs 28a and 28b act as matching elements within the frequency band of operation and create attenuation poles at higher frequencies.
  • the coupling elements 26a and 26b and the short-circuit stubs 28a and 28b can thus form a filter that suppresses electromagnetic wave radiation in a frequency band approximately twice higher than the operating frequency band. Therefore, this configuration of the matching circuit can be used for the low-band radiator of the dual-band antenna.
  • 4e and 4f are top and bottom views of another embodiment of the present invention, in which a printed circuit board 30 in which strip conductors 31a and 31b form a matching circuit including shorting stubs 32a and 32b.
  • the cross-opening groove 34 divides the conductive layer into four sections 35a-35d.
  • Metallized holes 33a and 33b connect the ends of stubs 32a and 32b to portions 35a and 35b, respectively.
  • the inner conductor of the coaxial cable is connected to the first ends of the strip conductors 31a and 31b.
  • Coupling elements in the shape of metallized holes 36a and 36b connect the second ends of the strip conductors to portions 35c and 35d, respectively.
  • the outer conductor of the coaxial cable is connected to portions 35a and 35b.
  • the matching circuit can also contain other components to match different radiating elements and feeding coaxial cables.
  • the supplied dual-polarized antenna is well matched to the feed coaxial cable, so it can be connected directly to a printed circuit board containing power splitters, filters, and other components of the matching circuit.
  • the size of the dielectric substrate can be increased.
  • each arm of a crossed dipole consists of two side metal pieces 37a and 37b connected to a support element 38 and connected to side metal pieces 37a and 37b.
  • the intermediate metal piece 39 of 37b is formed.
  • the matching of the dipole with the coaxial cable with the intermediate metal piece 39 is better than the matching of the dipole with the coaxial cable without the intermediate metal piece as shown in Figs. 1-3.
  • the size of the printed circuit board 40 is larger, and its corners are arranged opposite to the branches of the cross opening groove 41 .
  • the coupling elements 42a and 42b have a triangular shape.
  • a dielectric film 43 is provided between the bottom end of the support member 38 and the reflection plate to prevent generation of passive intermodulation products.
  • the reflecting plate 44 includes a cross-opening slot 45 disposed between the bottom ends of the support elements.
  • the cross-opening slots 45 excited by the support elements generate additional radiation at the back.
  • the radiation unit diffuses backward around the reflection plate 44, so the radiation from the cross opening groove 45 partially suppresses the back radiation generated by the radiation unit and improves The front-to-back ratio of the described dual-polarized antenna.
  • Figure 6 is a diagrammatic side view of another embodiment of a dual polarized antenna in which the arms of the crossed dipoles contain side metal pieces 46a and 46b, while being connected to support element 47.
  • Additional metal piece 48 is a separate element from the side metal pieces. Parts are separated by a dielectric film 49.
  • This shape of the intermediate metal piece 48 does not limit the length of the support element 47 in contrast to the intermediate metal piece 39 shown in FIG. 5 . Therefore, the support element 47 in FIG. 6 can therefore be longer.
  • Crossed dipoles placed above the reflector provide wider beamwidth and better matching with the feed coaxial cable.
  • Figure 7 is a side view of another embodiment of a dual polarized antenna in which a printed board circuit 50 is disposed in the middle of the radiating element and consists of four dipoles 51a-51d arranged in a dipole
  • the array is shaped and connected to lines of symmetry 52a-52d formed by metal conductors connected to adjacent support elements 53a-53d. Lines of symmetry 52a - 52d are part of the matching circuit on printed board circuit 50 .
  • a feed coaxial cable (not shown) is connected to the strip conductors 54 a and 54 b provided on the upper surface of the printed board circuit 50 .
  • the radiating elements of the square dipole array provide a narrower beamwidth and therefore provide more gain than crossed dipoles.
  • Figure 8 is a side view of another embodiment of a dual polarized antenna in which the arms of dipoles 55a-55d arranged in a dipole square are inclined from the plane of symmetry lines 56a-56d and towards the direction of the reflector. This tilting of the dipoles 55a-55d increases the gain and improves the front and rear values of the dual polarized antenna.
  • Figure 9 is a side view of another embodiment of a dual polarized antenna in which the arms of the dipoles 57a-57d arranged in a dipole array are bent 90 degrees from the plane of the line of symmetry 58a-58d and towards the direction of the reflector .
  • This shape increases the length of the lines of symmetry 58a-58d and the distance between the dipoles 57a-57d and the reflector, improving the connection between the dual polarized antenna and the coaxial cable (not shown) connected to the strip conductors 59a and 59b. ) matches.
  • FIG. 10 is a side view of another embodiment of a dual-polarized antenna, wherein the arms of dipoles 60a-60d are bent 90 degrees from the plane of symmetry lines 61a-61d, away from the direction of the reflector, and toward the center of the radiating element.
  • the outer contour of this radiating element looks like an octagon. This shape increases the length of the lines of symmetry 61a-61d and the distance between the dipoles 60a-60d and the reflector, improving the connection between the dual polarized antenna and the coaxial cable (not shown) connected to the strip conductors 62a and 62b. ) matches.
  • Fig. 11 is a side view of a part of the radiating element shown in Fig. 10. This part is stamped from a metal plate, so the manufacturing cost of this antenna is very cheap.
  • Figure 12 is a side view of another embodiment of a dual polarized antenna in which the radiating element consists of four folded dipoles 63a-63d arranged in a dipole formation and connected to a symmetrical on-line.
  • the strip conductors 64a-64d connecting the ends of the reduced dipoles increase the impedance of the dipoles so that the lines of symmetry 65a-65d feeding the reduced dipoles are symmetrical to the conventional dipoles shown in Figures 7-10
  • the line has a higher impedance than the line. They have larger gaps between conductors, so impedance is less dependent on production tolerances.
  • a coaxial cable (not shown) is connected to the strip conductors 66a and 66b, which together with the lines of symmetry 65a-65d form a matching circuit.
  • Figure 13 is a diagrammatic side view of another embodiment of a dual polarized antenna in which the strip conductors 67a-67d connecting the ends of the folded dipoles are inclined from the plane of symmetry lines 68a-68d and dipoles 69a-69d , and point in the direction of the reflector.
  • the radiating elements with inclined strips 67a-67d are stronger and smaller in size than the radiating elements shown in FIG. 12 .
  • Figure 14 is a side view of another embodiment of a dual polarized antenna in which folded dipoles 71a-71d are bent from the plane of the line of symmetry and away from the direction of the reflector.
  • a dielectric element 72 is disposed between the arms of the folded dipoles 71a-71d and a dielectric element 73 is disposed between the ends of adjacent folded dipoles to maintain the dimensions of the line of symmetry and increase the durability of the radiating element.
  • Figure 15 is a diagrammatic side view of another embodiment of a dual polarized antenna in which both the support element and the radiating element comprising four folded dipoles are stamped from a single piece of metal.
  • the folded dipole is bent from the plane where the line of symmetry lies and points toward the reflector to improve the front-to-back ratio and increase the gain.
  • Radiating elements with different shapes provide different radiation patterns, thus dual polarized antennas according to the invention can be used to create different antenna arrays.
  • the dual-polarized antenna according to the present invention provides a wider frequency band, and the feeding element includes a matching circuit connected between the radiating unit and the feeding coaxial cable. Therefore, by adjusting the size of the stripline forming the matching circuit, the dual-polarized antenna and the feeding coaxial cable can be well matched over a wide frequency band.
  • the manufacturing costs of the dual-polarized antenna according to the invention are low compared to conventional solutions, so that all elements of the radiating element and supporting elements do not need to be tinned and can be stamped from aluminum sheet.
  • the dual polarized antenna according to the invention provides less back radiation, the cross-open slots in the reflective plate between the bottom ends of the supporting elements generate additional radiation in the back, thereby suppressing the radiating elements produced back radiation.

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Abstract

一种双极化天线，包含由四个导电元件构成的辐射单元、四个支撑元件、馈电单元和反射板；辐射单元中心的十字开口槽把四个导电元件相互分开，四个支撑元件的顶端与导电元件相连，四个支撑元件固定在反射板上；馈电单元包含放置在辐射单元的中心区域的印刷电路板和两个沿着支撑元件放置的同轴电缆，通过外导体连接到覆盖印刷电路板下表面的导电层上，通过内导体连接到位于印刷电路板上表面的两条带状线的第一端，印刷电路板上的导电层及两条带状线与两条同轴电缆形成了匹配辐射单元的两个匹配电路；覆盖印刷电路板下表面的导电层包含十字开口槽，将导电层分成四个部分，与四个导电元件相对应放置；带状线穿过十字开口槽，且第二端与耦合元件相连接。

Description

双极化天线 发明领域
本发明涉及到一种双极化天线，尤其是，涉及到一种可以在垂直和水平方向或者+/-45度倾角发射/接收两个正交极化的天线。
背景技术
在智能手机被广泛使用的今天，市场需要大量的双极化天线，因此，该领域投入了大量的人力和物力，来研发具有指定波束宽度、良好的交叉极化鉴别率和通过宽频带与馈电电缆匹配良好的天线，且这些天线易于生产制造。
由于交叉偶极子在水平面产生过宽的波束，因此发明了更复杂的辐射器来减小波束宽度。美国专利US5940044描述了一种双斜极化天线，在水平面中具有大约65度的半功率波束宽度。该天线包括多个偶极子阵列，每个子阵列包括四个排列成菱形(钻石形)的偶极子。美国专利US6333720B1、US6529172B2和US2010/0309084A1中包含具有偶极方形形状的其他辐射器的图。偶极子的巴伦倾斜到偶极方阵的中心以简化制造，但尽管采用了这种新形状，但这些设备制作起来仍然很复杂。
美国专利了US6313809B1描述了包括四个偶极子的双偏振辐射器(双极化辐射器)，均匀地布置在反射器上方并且从俯视图看是偶极子方阵型。在US6940465B2、US7688271B2、CN202423543U、CN202268481U、CN101916910A、CN102097677A、CN102694237A、CN710714、CN717214中描述了这种偶极子。大多数已知的偶极方阵的双极化辐射器是由四根同轴电缆激发的，这些同轴电缆通过它们的内,外导体焊接到辐射器上，如专利中CN102013560A描述的双极化天线。
已知双极化天线的第一个缺陷是复杂的馈电网络，其包括连接四个偶极子的四根电缆和波束形成网络，通常放置在反射板的另一侧。这些电缆大多数与连接到波束形成网络的另一条电缆并联连接。第二个缺点是由于馈电电缆直接连接到偶极子，因此工作频带受到限制，导致该天线在偶极子和馈电电缆之间没 有匹配电路。此外，铝制辐射器必须用锡膜覆盖以焊接电缆。需要使用镀锡工艺是第三个缺点，因为大型辐射器的镀锡会增加制造成本。
发明内容
本发明的目的就是为了克服现有技术和其他已知双极化天线的缺点。
从之前提到的现有技术出发，本发明的第一个目的是研发一种简单连接波束形成网路的宽带双极化天线，第二个目的就是减少大型天线运行频率低于1GHz制作成本，第三个目的是减少双极化天线的背向辐射。
本发明提供了一种双极化天线，包含由四个导电元件构成的辐射单元、四个支撑元件、馈电单元和反射板；其中所述辐射单元中心的十字开口槽把四个导电元件相互分开，所述四个支撑元件的顶端直接与导电元件一一相连，所述四个支撑元件的底部固定在所述反射板上；其中所述馈电单元包含放置在导电元件上表面的辐射单元的中心区域的印刷电路板和两个同轴电缆，所述两个同轴电缆沿着所述支撑元件放置，并通过外导体连接到覆盖所述印刷电路板下表面的导电层上，同时通过其内导体连接到位于所述印刷电路板上表面的两条带状线的第一端，所述印刷电路板上的导电层及两条带状线与两条同轴电缆形成了匹配所述辐射单元的两个匹配电路；其中覆盖所述印刷电路板下表面的导电层包含了一个十字开口槽，十字开口槽将导电层分成四个部分，与辐射单元的四个导电元件相对应放置；其中所述带状线在十字开口槽的中心穿过十字开口槽，且所述带状线的第二端与耦合元件相连接。
反射板包含设置在支撑元件的底端之间的十字形开口槽。
图1-15示出了一种双极化天线的一些实施例。
与传统解决方案相比，根据本发明的双极化天线提供更宽的频带，结果馈电元件包括连接在辐射装置和馈电同轴电缆之间的匹配电路。因此，通过调整形成匹配电路的带状线的尺寸，可以更好地匹配双极化天线与馈电同轴电缆通过宽频带。
与传统解决方案相比，根据本发明的双极化天线可以具备更少的背向辐射优势，结果是在支撑元件底端之间的反射板中的十字开口槽在背向产生额外的辐射，从而抑制辐射单元所产生的背向辐射。
附图说明
图1是根据本发明的双极化天线的第一实施例的侧视图，其中辐射单元由两个交叉的偶极子组成，两个交叉的偶极子由位于反射板上方的支撑元件表面上的偶极子臂上的馈电单元激发。
图2是图1中所示的双极化天线的一部分的图示侧视图。
图3是另外一个偶极子臂和支撑元件的侧视图。
图4a-4f分别是印刷电路板的俯视图和底视图，包含了形成匹配电路的带状线和不同形态的耦合元件。
图5是双极化天线的另一个实施例的侧视图，交叉偶极子的每一个臂包含两个侧金属件，和一个连接侧金属件的中间金属件。反射板包含支撑元件之间的十字开口槽。
图6是双极化天线的另一个实施例的侧视图，每一个交叉偶极子臂包含两个连接支撑元件的侧金属件，附加金属件与两个侧金属件连接并用介电薄膜隔开。
图7是双极化天线的另一个实施例的侧视图，辐射单元包含以偶极方阵列排列的四个偶极子，被馈电单元激发，并与对称线相连，对称线是由导体和相邻导电支撑元件形成。
图8是双极化天线的另一实施例的侧视图，偶极子臂以偶极阵列排列，并从对称线所在的平面弯曲，指向反射板方向。
图9是双极化天线的另一案例的侧视图，偶极子臂以偶极阵列排列，并从对称线所在的平面弯曲，背离反射板反向。
图10是双极化天线的另一个实施例的侧视图，每个偶极子的臂由对称线馈电，且臂朝向辐射单元中心弯曲，背离反射板方向。
图11是图10所示的辐射单元的一部分侧视图，由一块金属板制成。
图12是双极化天线的另一实施例的侧视图，辐射单元包含四个折合偶极子，并以偶极方阵排列，与对称线相连，由馈电单元激发。
图13是双极化天线的另一种侧视图，折合偶极子臂端部的导体从对称线所在的平面弯曲，且朝向反射板方向。
图14是双极化天线的另一实施例的侧视图，折合偶极子包含介电元件，并从对称线所在的平面弯曲，且背离反射板方向。
图15是双极化天线的另一实施例的侧视图，支撑元件和包含四个折合偶极子的辐射单元是由一块金属板制成。
具体实施方式
包含在说明书中并构成说明书一部分的附图说明了本发明的实施例，并且与下面给出的本发明的总描述一起用于解释本发明的原理。
图1是本发明的双极化天线的第一实施例的侧视图。本发明提供一种双极化天线包含辐射单元，该辐射单元包含1-4四个导电元件，分别被辐射单元中心的十字开口槽5独立隔开，4个支撑元件6a-6d的顶端直接与导电元件相连，底端与反射板7相连并固定在反射板上，还包括馈电单元。馈电单元包含放置在辐射单元中间、位于导电元件1-4上表面的印刷电路板8，和沿着支撑元件6a和6b放置的两条同轴电缆9a和9b，同轴电缆9a和9b通过外导体连接到覆盖印刷电路板8底面的导电层。同轴电缆9a和9b的内导体10a和10b连接到放置在印刷电路板8上表面的带状导体12a和12b的第一端11a和11b，所述印刷电路板8上的导电层及带状导体12a和12b与同轴电缆9a和9b形成与辐射单元相匹配的两个匹配电路。耦合元件13a和13b在带状导体12a和12b的第二端与导电元件3之间产生电容耦合，因此当同轴电缆9a被激发时，由导电元件1和3形成的第一辐射单元辐射电磁波。辐射的第一个电磁波的E矢量沿箭头Ea指向。当同轴电缆9b被激发时，由导电元件2和4形成的第二辐射单元辐射电磁波。辐射的第二个电磁波的E矢量沿着箭头Eb指向并垂直于箭头Ea。因此，根据本发明的双极化天线辐射具有正交极化的两个电磁波。
辐射波束的形状取决于辐射单元的形状。所提供的双极化天线可以包括不同种类的辐射单元。图1所示的导电元件1-4形成两个交叉偶极子。支撑元件6a-6d形成这些偶极子的两个交叉偶极子。支撑元件6a是图2所示的导电元件1(偶极子臂)的一部分，导电元件1(偶极子臂)包含14a和14b两个侧金属件。
偶极子臂和支撑元件的另一种形状如图3所示，其侧金属件15a和15b具有直线形状。在其边缘的金属部分16a和16b向下弯曲以增加交叉偶极子臂之间的耦合。在支撑元件18的边缘处的金属部分17a和17b弯曲以增加与沿支撑元件18布置的同轴电缆的耦合并增加对沿同轴电缆的外导体传播的泄漏波的抑制。具有这种形 状的臂的交叉偶极子可以用作双波段天线的低波段辐射元件，因为在低波段和高波段辐射元件之间提供空间。
图4a和4b分别是是图1所示的印刷电路板8的俯视图和仰视图。放置在印刷电路板8上表面的带状导体12a和12b形成矩形板形状的耦合元件13a和13b和两个匹配电路。金属化孔19将带状导体12b连接到设置在印刷电路板8的底表面处的带状导体20。金属化孔21将带状导体20连接到耦合元件13b。覆盖印刷电路板底部的导电层包含十字开口槽22，将导电层分成四个部分23a-23d，分别放置在四个导电元件1-4的对立面。带状导体20设置在十字开口槽22的中心。十字开口槽22的分支设置在十字开口槽5的分支的对立面。印刷电路板8通过塑料螺钉或铆钉(未示出)固定到导电元件1-4布置在孔24中。
辐射单元的阻抗取决于其形状和运行频带，因此形成匹配电路的带状导体和不同辐射单元的耦合元件具有不同的配置并且可以包括不同的元件。
图4c和4d分别是本发明的另一个实施例的俯视图和仰视图，其中印刷电路板25包括开路枝节的耦合元件26a和26b，在十字开口槽22附近产生短路。耦合元件26a和26b将带状导体27a和27b与覆盖印刷电路板25底面的导电层的部分23d和23c相应地连接。这种依赖于频率的连接在较高频率产生衰减极点。短路枝节28a和28b在工作频带内充当匹配元件并在较高频率产生衰减极点。因此，耦合元件26a和26b以及短路枝节的28a和28b可以形成抑制比工作频带高大约两倍的频带的电磁波辐射的滤波器。因此，匹配电路的这种配置可用于双频带天线的低频带辐射器。
图4e和4f是本发明的另一个实施例的俯视图和底视图，其中印刷电路板30其中带状导体31a和31b形成包括短路枝节32a和32b的匹配电路。十字开口槽34将导电层分成四个部分35a-35d。金属化孔33a和33b相应地将枝节32a和32b的端部连接到部分35a和35b。同轴电缆的内导体连接到带状导体31a和31b的第一端。金属化孔36a和36b形状的耦合元件相应地将带状导体的第二端连接到部分35c和35d。同轴电缆的外导体连接到部分35a和35b。
匹配电路还可以包含其他元件，以匹配不同的辐射单元与馈电同轴电缆。所提供的双极化天线能与馈电同轴电缆很好地匹配，因此可以直接连接到包含功率分配器、滤波器和匹配电路其他元件的印刷电路板。为了可以在匹配电路中添加 更多元件，可以增加介电基板的尺寸。
图5是双极化天线的另一个实施例的图示侧视图，其中交叉偶极子的每个臂由连接到支撑元件38的两个侧金属件37a和37b和连接到侧金属件37a和37b的中间金属件39组成。带有中间金属件39的偶极子与同轴电缆的匹配优于如图1-3中所示的不带中间金属件的偶极子与同轴电缆的匹配。与印刷电路板8的尺寸相比，印刷电路板40的尺寸更大，并且其角部设置在十字开口槽41的枝节相对处。耦合元件42a和42b具有三角形形状。介电薄膜43设置在支撑元件38的底端与反射板之间以防止产生无源互调产物。反射板44包含设置在支撑元件底端之间的十字开口槽45。由支撑元件激发的十字开口槽45在背部产生额外的辐射。与来自辐射单元的辐射相比，这种辐射具有不同的相位，辐射单元围绕反射板44向后扩散，因此来自十字开口槽45的辐射部分抑制了由辐射单元产生的背向辐射，并提高了所描述的双极化天线的前后比。
图6是双极化天线的另一个实施例的图示侧视图，其中交叉偶极子的臂包含侧金属件46a和46b,同时连接到支撑元件47.附加金属件48是独立元件与侧金属件之间用介质薄膜49隔开。与图5所示的中间金属件39相比，中间金属件48的这种形状不限制支撑元件47的长度。因此，因此图6中的支撑元件47可以更长。放在反射板上方的交叉偶极子提供更宽的波束宽度和能与馈电同轴电缆更好的匹配。
图7是双极化天线的另一个实施例的侧视图，其中印刷板电路50设置在辐射单元的中间，由四个偶极子51a-51d组成，这些偶极子51a-51d排列成偶极阵列形状并连接到对称线52a-52d，该对称线由连接到相邻支撑元件53a-53d的金属导体形成。对称线52a-52d是印刷板电路50上的匹配电路的一部分。馈电同轴电缆(未示出)连接到设置在印刷板电路50上表面上的带状导体54a和54b。偶极方阵型的辐射单元提供更窄的波束宽度，因此与交叉偶极子相比，这种天线提供更多增益。
图8是双极化天线的另一个实施例的侧视图，其中以偶极方阵排列的偶极子55a-55d的臂从对称线56a-56d设置的平面朝向倾斜，且朝向反射板方向。偶极子55a-55d的这种倾斜增加增益并改善双极化天线的前后值。
图9是双极化天线的另一个实施例的侧视图，其中以偶极阵列排列的偶极子 57a-57d的臂从对称线58a-58d所在的平面上弯曲90度，且朝向反射板方向。这种形状增加了对称线58a-58d的长度以及偶极子57a-57d与反射板之间的距离，改善了双极化天线与连接到带状导体59a和59b的同轴电缆(未示出)的匹配。
图10是双极化天线的另一个实施例的侧视图，其中偶极子60a-60d的臂从对称线61a-61d所在的平面弯曲90度，且背离反射板方向，并朝向辐射单元中心。这种辐射单元的外轮廓看起来像一个八边形。这种形状增加了对称线61a-61d的长度以及偶极子60a-60d与反射板之间的距离，改善了双极化天线与连接到带状导体62a和62b的同轴电缆(未示出)的匹配。
图11是图10所示的辐射单元的一部分的侧视图，这一部分是由一块金属板冲压而成，因此这种天线的制作成本很便宜。
图12是双极化天线的另一个实施例的侧视图，其中辐射单元由四个折合偶极子63a-63d组成，这些偶极子以偶极阵型排列并连接到由馈电元件激发的对称线上。连接折合偶极子端部的带状导体64a-64d增加了偶极子的阻抗，因此馈电折合偶极子的对称线65a-65d与图7-10中所示的常用偶极子的对称线相比具有更大的阻抗。它们的导体之间的间隙更大，因此阻抗对生产公差的依赖性较小。同轴电缆(未示出)连接到带状导体66a和66b，与对称线65a-65d一起形成匹配电路。
图13是双极化天线的另一个实施例的图示侧视图，其中连接折合偶极子端部的带状导体67a-67d从对称线68a-68d和偶极子69a-69d所在的平面倾斜，且指向向反射板的方向。带有倾斜带状67a-67d的辐射单元更牢固，比图12所示的辐射单元尺寸更小。
图14是双极化天线的另一个实施例的侧视图，其中折合偶极子71a-71d从对称线所在的平面弯曲，且背离反射板方向。介电元件72设置在折叠偶极子71a-71d的臂之间，介电元件73设置在相邻折叠偶极子的端部之间，以保持对称线的尺寸并增加辐射单元的耐用性。
图15是双极化天线的另一个实施例的图示侧视图，其中支撑元件和包括四个折合偶极子的辐射单元都是由一块金属冲压而成。折合偶极子从对称线所在的平面弯曲，且指向反射板方向，以提高前后比并增加增益。
具有不同形状的辐射单元提供不同的辐射模式，因此根据本发明的双极化天 线可用于创建不同的天线阵列。
与传统解决方案相比，根据本发明的双极化天线提供更宽的频带，馈电元件包括连接在辐射单元和馈电同轴电缆之间的匹配电路。因此，通过调整形成匹配电路的带状线的尺寸，可以使双极化天线与馈电同轴电缆通过宽频带进行良好匹配。
根据本发明的双极化天线的制造成本与传统解决方案相比较低，因此辐射单元的所有元件和支撑元件都不需要镀锡并且可以用铝片通过冲压制成。
与传统解决方案相比，根据本发明的双极化天线提供更少的背向辐射，在支撑元件底端之间的反射板中的十字开口槽在背向产生额外辐射，从而抑制辐射单元所产生的背向辐射。
虽然本发明已经通过其实施例的描述进行了说明，并且虽然已经详细描述了实施例，但是申请人的意图不是将所附权利要求的范围限制或以任何方式限制到这样的细节中。本领域的技术人员更容易地理解本发明额外的优点和所作的一些修改。因此，本发明描述更广泛不限于所示和描述的具体细节、代表性装置和说明性示例。因此，在不背离申请人的总体发明构思的精神或范围的情况下，可以偏离这些细节。

Claims (30)

  1. 一种双极化天线，其特征在于，包含由四个导电元件构成的辐射单元、四个支撑元件、馈电单元和反射板；
    其中所述辐射单元中心的十字开口槽把四个导电元件相互分开，所述四个支撑元件的顶端直接与导电元件一一相连，所述四个支撑元件的底部固定在所述反射板上；
    其中所述馈电单元包含放置在导电元件上表面的辐射单元的中心区域的印刷电路板和两个同轴电缆，所述两个同轴电缆沿着所述支撑元件放置，并通过外导体连接到覆盖所述印刷电路板下表面的导电层上，同时通过其内导体连接到位于所述印刷电路板上表面的两条带状线的第一端，所述印刷电路板上的导电层及两条带状线与两条同轴电缆形成了匹配所述辐射单元的两个匹配电路；
    其中所述印刷电路板下表面上的导电层包含了一个十字开口槽，十字开口槽将导电层分成四个部分，且与辐射单元的四个导电元件相对应放置；
    其中所述印刷电路板上的带状线在十字开口槽的中心穿过十字开口槽，且所述带状线的第二端与耦合元件相连接。
  2. 如权利要求1所述的双极化天线，其特征在于，所述匹配电路包含开路枝节线。
  3. 如权利要求1所述的双极化天线，其特征在于，所述匹配电路包含短路枝节线。
  4. 如权利要求1所述的双极化天线，其特征在于，穿过所述导电层的所述十字开口槽的带状线的一部分位于所述印刷电路板下表面，且通过所述印刷电路板上的金属化孔与带状线连接。
  5. 如权利要求1所述的双极化天线，其特征在于，介电薄膜放置在反射板和支撑元件底部之间。
  6. 如权利要求1所述的双极化天线，其特征在于，介电薄膜放置在支撑元件和印刷电路板之间。
  7. 如权利要求1所述的双极化天线，其特征在于，设置在印刷电路板的上表面的耦合元件呈导电板的形态。
  8. 如权利要求1所述的双极化天线，其特征在于，耦合元件具有带开口端的带状线的形态。
  9. 如权利要求1所述的双极化天线，其特征在于，印刷电路板上的耦合元件具有金属化孔的形态。
  10. 如权利要求1所述的双极化天线，其特征在于，反射板包含有位于支撑元件底部之间的十字开口槽。
  11. 如权利要求1所述的双极化天线，其特征在于，辐射单元包含两个交叉偶极子。
  12. 如权利要求11所述的双极化天线，其特征在于，所述交叉偶极子的每个臂包含连接支撑元件的两个侧金属件。
  13. 如权利要求11所述的双极化天线，其特征在于，交叉偶极子的每个臂包含连接支撑元件的两个侧金属件和连接侧金属件的中间金属件。
  14. 如权利要求13所述的双极化天线，其特征在于，介电薄膜放置在中间金属件和侧金属件之间。
  15. 如权利要求1所述的双极化天线，其特征在于，辐射单元包含四个放置在反射板上方的偶极子，并以偶极子阵列排列。
  16. 如权利要求15所述的双极化天线，其特征在于，每一个偶极子连接到由导体形成的对称线上，所述导体连接到相邻的支撑元件。
  17. 如权利要求16所述的双极化天线，其特征在于，偶极子与对称线在同一平面内。
  18. 如权利要求16所述的双极化天线，其特征在于，偶极子从对称线所在的平面弯曲30-90度，且朝向反射板方向。
  19. 如权利要求16所述的双极化天线，其特征在于，偶极子从对称线所在的平面弯曲30-90度，且背离反射板方向。
  20. 如权利要求15-19任一项所述的双极化天线，其特征在于，
    每一个偶极子的臂弯向辐射单元的中心位置。
  21. 如权利要求11-19任一项所述的双极化天线，其特征在于，支撑元件和其所连接的辐射单元的所有部分都是由一块金属板冲压而成。
  22. 如权利要求1所述的双极化天线，其特征在于，辐射单元包含放置在反射板上方的四个折合偶极子，且以偶极子阵列排列。
  23. 如权利要求22所述的双极化天线，其特征在于，每一个折合偶极子连接到由两个导体形成的对称线上，该导体连接到相邻的两个支撑元件上。
  24. 如权利要求23所述的双极化天线，其特征在于，每一个折合偶极子与对称线在同一平面上。
  25. 如权利要求23所述的双极化天线，其特征在于，折合偶极子的末端导体从对称线所在的平面弯曲，且朝向反射板方向。
  26. 如权利要求23所述的双极化天线，其特征在于，折合偶极子从对称线所在的平面弯曲30-90度，且朝向反射板方向。
  27. 如权利要求23所述的双极化天线，其特征在于，折合偶极子从对称线所在的平面弯曲30-90度，且背离反射板方向。
  28. 如权利要求22-27任一项所述的双极化天线，其特征在于，支撑元件和辐射单元是由同一块金属板冲压而成。
  29. 如权利要求22-27任一项所述的双极化天线，介电元件放置在偶极子末端相邻间隙之间。
  30. 一种双极化天线阵列，包含至少两种如权利要求1所述的双极化天线。
PCT/CN2021/137141 2021-12-06 2021-12-10 双极化天线 WO2023102905A1 (zh)

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CN115051148B (zh) * 2022-07-20 2023-09-22 四川领航未来通信技术有限公司 一种超宽带正交极化双频平板天线
WO2024030810A1 (en) * 2022-08-05 2024-02-08 Commscope Technologies Llc Low-cost ultra-wideband cross-dipole radiating elements and base station antennas including arrays of such radiating elements
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