WO2023040225A1 - 频偏估计方法及装置、电子设备、及计算机可读存储介质 - Google Patents

频偏估计方法及装置、电子设备、及计算机可读存储介质 Download PDF

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WO2023040225A1
WO2023040225A1 PCT/CN2022/081933 CN2022081933W WO2023040225A1 WO 2023040225 A1 WO2023040225 A1 WO 2023040225A1 CN 2022081933 W CN2022081933 W CN 2022081933W WO 2023040225 A1 WO2023040225 A1 WO 2023040225A1
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frequency offset
offset estimation
value
estimated
estimation method
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PCT/CN2022/081933
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English (en)
French (fr)
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赵丽娟
卞青
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深圳市中兴微电子技术有限公司
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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes

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  • the embodiments of the present application relate to the technical field of communications, and in particular, to a frequency offset estimation method and device, electronic equipment, and a computer-readable storage medium.
  • V2X Vehicle-to-Everything
  • Vehicle-to-Everything technology is currently in a period of rapid development.
  • the Internet of Vehicles will establish the development direction of new automotive technologies by integrating global positioning and navigation technology, V2X communication technology, wireless communication and remote sensing technology.
  • the industry will develop rapidly.
  • V2X mainly includes the following four types: vehicle-to-vehicle (V2V, Vehicle-to-Vehicle), vehicle-to-road (V2I, Vehicle-to-Infrastructure), vehicle-to-network (V2N, Vehicle-to-Network), and vehicle-to-vehicle People (V2P, Vehicle-to-Pedestrian).
  • V2V Vehicle-to-vehicle
  • V2I Vehicle-to-Vehicle
  • V2I Vehicle-to-Infrastructure
  • V2N Vehicle-to-Network
  • V2P Vehicle-to-Pedestrian
  • V2X In the application of V2X Internet of Vehicles, the moving speed of the vehicle is fast, the fastest supported relative moving speed is about 500 kilometers per hour (km/h), it works in the frequency band from 5855 megahertz (MHz) to 5925MHz, and the largest Doppler The frequency shift is about 2700 hertz (Hz); while considering the maximum carrier frequency deviation of about 0.3 parts per million (ppm), long-term evolution (LTE, Long Term Evolution) and the fifth generation mobile communication technology (5G, 5th Generation Mobile Communication Technology) new radio (NR, New Radio) V2X may work in the frequency band from 5855MHz to 5925MHz, and the maximum carrier frequency deviation is about 1800Hz; from the above, the maximum frequency deviation brought by high-speed mobile and high carrier frequency is about 4500Hz, This will seriously affect the demodulation performance of the system. Therefore, it is necessary to estimate the frequency offset, and then compensate the frequency offset by some specific methods.
  • DMRS demodulation reference signal
  • DMRS Demodulation reference signal
  • half symbol time domain frequency offset estimation method adjacent demodulation reference signal (DMRS, Demodulation reference signal) frequency domain frequency offset estimation method
  • the adjacent DMRS frequency domain frequency offset estimation method has high estimation accuracy, but when the Doppler frequency shift is relatively large, there may be many problems of inversion of the estimated value caused by exceeding the estimated range, resulting in a sharp deterioration of the estimation performance;
  • the estimation range of the frequency offset estimation method in the half-symbol time domain is large enough, but the accuracy is low and the variance is large, which may bring a certain loss to the demodulation performance.
  • the estimation performance of the above frequency offset estimation method is low.
  • the embodiment of the present application provides a frequency offset estimation method, including: using the first frequency offset estimation method to perform frequency offset estimation on a demodulation reference signal (DMRS, Demodulation reference signal) sent by the terminal to obtain the first frequency offset estimation value; using a second frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by the terminal to obtain a second frequency offset estimation value; and determine a confidence factor according to the first frequency offset estimation value and the second frequency offset estimation value, Calibrate the second estimated frequency offset value according to the confidence factor to obtain a final estimated frequency offset value.
  • DMRS demodulation reference signal
  • Demodulation reference signal Demodulation reference signal
  • an embodiment of the present application provides an electronic device, including: at least one processor; and a memory, on which at least one computer program is stored, and when the at least one computer program is executed by the at least one processor, Implement the above frequency offset estimation method.
  • an embodiment of the present application provides a computer-readable storage medium, where a computer program is stored on the computer-readable storage medium, and when the computer program is executed by a processor, the foregoing frequency offset estimation method is implemented.
  • an embodiment of the present application provides a frequency offset estimation device, including: a first frequency offset estimation module configured to perform frequency offset estimation on a DMRS signal sent by a terminal using a first frequency offset estimation method to obtain a first frequency offset estimation value; the second frequency offset estimation module is configured to use the second frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by the terminal to obtain a second frequency offset estimation value; the confidence factor selection module is configured to be based on the first frequency offset estimation value and the second estimated frequency offset value to determine a confidence factor; and a frequency offset calibration module configured to calibrate the second estimated frequency offset value according to the confidence factor to obtain a final estimated frequency offset value.
  • FIG. 1 is a flowchart of a frequency offset estimation method provided in an embodiment of the present application
  • FIG. 2 is a block diagram of an electronic device provided by an embodiment of the present application.
  • FIG. 3 is a block diagram of a frequency offset estimation device provided by an embodiment of the present application.
  • DMRS adjacent demodulation reference signal
  • Demodulation reference signal Demodulation reference signal
  • the adjacent DMRS frequency domain frequency offset estimation method obtains the frequency offset estimation value by calculating the phase change on adjacent DMRS symbols.
  • LTE Long Term Evolution
  • V2X Vehicle-to-Everything
  • the interval between adjacent DMRS symbols is 3 symbols (symbol)
  • the maximum frequency offset range that can be estimated is ⁇ 2336 Hz ( Hz)
  • 5G 5th Generation Mobile Communication Technology
  • NR New Radio
  • the maximum frequency deviation range that can be estimated is ⁇ 4672Hz.
  • the maximum possible frequency offset of V2X is about ⁇ 4500Hz.
  • the V2X frequency offset range exceeds the estimation range of the adjacent DMRS frequency domain frequency offset estimation method, and phase reversal may occur.
  • the frequency offset estimation method in the adjacent DMRS frequency domain may also cause phase inversion and phase inversion.
  • the half-symbol time-domain frequency offset estimation method obtains the frequency offset estimation value by calculating the phase angle of the time-domain correlation results of the signal on the first half symbol and the second half symbol.
  • the frequency offset estimation range of this method is ⁇ f( ⁇ f is the subcarrier spacing), enough to cover the extreme scenarios of V2X, but due to the influence of channel and noise, the estimation accuracy is poor, and due to the service characteristics of V2X, the half-symbol time-domain frequency offset estimation method cannot filter in time and then converges to an exact value.
  • the adjacent DMRS frequency domain frequency offset estimation method has high estimation accuracy, but when the Doppler frequency shift is relatively large, there may be many problems of inversion of the estimated value caused by exceeding the estimation range, resulting in sharp estimation performance. and, the estimation range of the half-symbol time-domain frequency offset estimation method is large enough, but the accuracy is low and the variance is large, which may bring a certain loss to the demodulation performance. In summary, in an application scenario with a large frequency offset range, the estimation performance of the related frequency offset estimation method is low.
  • the frequency offset estimation method of the embodiment of the present application is proposed based on the problems existing in the LTE V2X scenario and the 5G NR V2X scenario, the frequency offset estimation method of the embodiment of the present application can also be applied to any other scenarios frequency offset estimate.
  • the frequency offset estimation method in the embodiment of the present application is proposed based on the problems existing in the adjacent DMRS frequency domain frequency offset estimation method and the half-symbol time domain frequency offset estimation method
  • the frequency offset estimation method in the embodiment of the present application is also applicable to
  • the first frequency offset estimation method and the second frequency offset estimation method have the same problems as the above two methods.
  • the first frequency offset estimation method is similar to the adjacent DMRS frequency domain frequency offset estimation method, both of which are based on the Doppler frequency shift
  • the second frequency offset estimation method is similar to the half-symbol time-domain frequency offset estimation method, which is a frequency offset estimation method with a large frequency offset estimation range but low accuracy method.
  • FIG. 1 is a flowchart of a frequency offset estimation method provided by an embodiment of the present application.
  • an embodiment of the present application provides a method for estimating a frequency offset, including steps 100 to 102 .
  • Step 100 Perform frequency offset estimation on the DMRS signal sent by the terminal by using the first frequency offset estimation method to obtain a first frequency offset estimation value.
  • the first frequency offset estimation method refers to a frequency offset estimation method that may cause phase inversion when the Doppler frequency shift is large, such as an adjacent DMRS frequency offset estimation method.
  • the DMRS signal sent by only one terminal may be received, or the DMRS signal sent by two or more terminals may be received simultaneously. If the DMRS signals sent by two or more terminals are received at the same time, frequency offset estimation is performed on the DMRS signals sent by each terminal respectively.
  • receive DMRS signals sent by terminal 1, terminal 2, and terminal 3 at the same time and use the first frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by terminal 1 to obtain a first frequency offset estimated value 1, using the first frequency offset
  • the estimation method performs frequency offset estimation on the DMRS signal sent by the terminal 2 to obtain a first frequency offset estimation value 2 , and uses the first frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by the terminal 3 to obtain the first frequency offset estimation value 3 .
  • the DMRS signal may be a Physical Sidelink Control Channel (PSCCH, Physical Sidelink Control Channel) DMRS signal, or a Physical Sidelink Shared Channel (PSSCH, Physical Sidelink Shared Channel) DMRS signal.
  • PSCCH Physical Sidelink Control Channel
  • PSSCH Physical Sidelink Shared Channel
  • Step 101 using a second frequency offset estimation method to perform frequency offset estimation on a DMRS signal sent by a terminal to obtain a second frequency offset estimation value.
  • the second frequency offset estimation method refers to a frequency offset estimation method with a larger frequency offset estimation range but lower accuracy, such as a half-symbol time domain frequency offset estimation method.
  • the DMRS signal sent by only one terminal may be received, or the DMRS signal sent by two or more terminals may be received simultaneously. If the DMRS signals sent by two or more terminals are received at the same time, frequency offset estimation is performed on the DMRS signals sent by each terminal respectively.
  • receive DMRS signals sent by terminal 1, terminal 2, and terminal 3 at the same time and use the second frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by terminal 1 to obtain a second frequency offset estimated value 1, and use the second frequency offset
  • the estimation method performs frequency offset estimation on the DMRS signal sent by terminal 2 to obtain a second estimated frequency offset value 2
  • Step 102 Determine a confidence factor according to the first estimated frequency offset value and the second estimated frequency offset value, and calibrate the second estimated frequency offset value according to the confidence factor to obtain a final estimated frequency offset value.
  • the DMRS signal sent by only one terminal may be received, or the DMRS signal sent by two or more terminals may be received simultaneously. If the DMRS signals sent by two or more terminals are received at the same time, the confidence factor is determined according to the first frequency offset estimation value and the second frequency offset estimation value corresponding to each terminal respectively, and the second frequency offset estimation value is calculated according to the confidence factor Perform calibration to obtain the final frequency offset estimate.
  • receiving DMRS signals sent by terminal 1, terminal 2, and terminal 3 at the same time determine the confidence factor 1 according to the first estimated frequency offset value 1 and the second estimated frequency offset value 1, and determine the confidence factor 1 according to the confidence factor 1 for the second
  • the frequency offset estimated value 1 is calibrated to obtain the final frequency offset estimated value 1
  • the confidence factor 2 is determined according to the first frequency offset estimated value 2 and the second frequency offset estimated value 2
  • the second frequency offset estimated value is determined according to the confidence factor 2
  • Value 2 is calibrated to obtain the final frequency offset estimation value 2
  • the confidence factor 3 is determined according to the first frequency offset estimation value 3 and the second frequency offset estimation value 3
  • the second frequency offset estimation value 3 is determined according to the confidence factor 3
  • Calibration is performed to obtain the final frequency offset estimation value 3.
  • the first frequency offset estimation method when used to estimate the frequency offset, there are two cases of phase inversion and no phase inversion. The methods for determining the confidence factor in these two cases are described below.
  • determining the confidence factor according to the first frequency offset estimation value and the second frequency offset estimation value includes: according to the first frequency offset estimation value and When the second frequency offset estimation value determines that there is no phase inversion when the first frequency offset estimation method is used for frequency offset estimation, a positive number is selected from the first optional interval as the confidence factor; the first optional interval is greater than 0 And less than or equal to the interval of 0.5.
  • determining according to the first frequency offset estimation value and the second frequency offset estimation value that there is no phase inversion when the frequency offset estimation is performed using the first frequency offset estimation method includes: according to the first frequency offset estimation value and the second frequency offset estimation value The same positive and negative signs determine that there is no phase inversion when the first frequency offset estimation method is used for frequency offset estimation.
  • the absolute value of the difference between the first frequency offset estimation value and the second frequency offset estimation value is less than or equal to the adaptive threshold value, and the absolute value of the difference between the first estimated frequency offset value and the second estimated frequency offset value is greater than the adaptive threshold value.
  • determining the confidence factor according to the first estimated frequency offset value and the second estimated frequency offset value includes: According to the first frequency offset estimation value and the second frequency offset estimation value, it is determined that there is a phase inversion when the frequency offset estimation is performed using the first frequency offset estimation method, and the absolute value of the difference between the first frequency offset estimation value and the second frequency offset estimation value If it is less than or equal to the adaptive threshold value, select a positive number from the first optional interval as the confidence factor; the first optional interval is an interval greater than 0 and less than or equal to 0.5.
  • determining the confidence factor according to the first estimated frequency offset value and the second estimated frequency offset value includes: The first frequency offset estimation value and the second frequency offset estimation value determine that there is a phase inversion when the first frequency offset estimation method is used for frequency offset estimation, and the absolute value of the difference between the first frequency offset estimation value and the second frequency offset estimation value is greater than the self
  • a positive number is selected from the second optional interval as the confidence factor; the second optional interval is an interval greater than 0.5 and less than or equal to 1.
  • the sign of the first frequency offset estimation value and the second frequency offset estimation value are different as a direct result of phase inversion when the frequency offset estimation is performed using the first frequency offset estimation method. Therefore, according to Whether the signs of the first estimated frequency offset value and the second estimated frequency offset value are the same determines whether phase inversion exists. Specifically, according to the first frequency offset estimation value and the second frequency offset estimation value, determining that there is a phase inversion when the frequency offset estimation is performed using the first frequency offset estimation method includes: according to the first frequency offset estimation value and the second frequency offset estimation value Different signs determine that there is phase inversion when frequency offset estimation is performed using the first frequency offset estimation method.
  • the adaptive threshold value is a value selected from the optional interval of the adaptive threshold, the optional interval of the adaptive threshold is an interval greater than 0 and less than or equal to the target value, the target value and the maximum frequency offset value The absolute value of the difference is less than or equal to the preset threshold.
  • calibrating the second estimated frequency offset value according to the confidence factor to obtain the final estimated frequency offset value includes: multiplying the confidence factor by the second estimated frequency offset value to obtain the final estimated frequency offset value.
  • the frequency offset estimation method uses the first frequency offset estimation method and the second frequency offset estimation method to respectively perform frequency offset estimation on the DMRS signal sent by the terminal to obtain the first frequency offset estimation value and the second frequency offset estimation value, Determine the confidence factor according to the first frequency offset estimation value and the second frequency offset estimation value, and then calibrate the second frequency offset estimation value according to the confidence factor to obtain the final frequency offset estimation value, by combining the first frequency offset estimation method and the second frequency offset estimation method
  • the estimation method performs frequency offset estimation, which can not only satisfy a larger frequency offset range, but also improve the estimation performance.
  • This example describes the process of frequency offset estimation for the PSCCH in the LTE V2X system.
  • the maximum Doppler frequency shift of the Extended Vehicle Channel Model (EVA, Extended Vehicle A model) is 2700 Hz, and the carrier frequency offset is 600 Hz.
  • EVA Extended Vehicle Channel Model
  • the specific implementation process of estimating the frequency offset of the PSCCH DMRS signal by using the frequency offset estimation method provided by the embodiment of the present application includes steps S1 to S3.
  • K is the number of DMRS subcarriers in one symbol, ⁇ means to find the phase angle, and * means to find the conjugate.
  • a coherent accumulation method can be used, as shown in formula (11), or a non-coherent accumulation method can be used, such as real part accumulation and amplitude accumulation.
  • the frequency domain received signal of the DMRS signal to be received Perform N-point inverse discrete Fourier transform (IDFT, Inverse Discrete Fourier Transform) or inverse fast Fourier transform (IFFT, Inverse Fast Fourier Transform) to time domain signal As shown in formula (12).
  • IDFT Inverse Discrete Fourier Transform
  • IFFT inverse fast Fourier transform
  • the frequency domain signal of the local DMRS signal Perform N-point IDFT or IFFT transformation to time domain signal As shown in formula (13).
  • Time domain signal to local DMRS signal Perform time offset estimation to obtain the offset d, for the time domain signal of the local DMRS signal Perform time offset adjustment, as shown in formula (14).
  • Time-domain correlation processing is performed on the first half symbol and the second half symbol of , as shown in formula (15).
  • Time-domain correlation results for 4 DMRS symbols Calculate the phase angle after accumulation to obtain the second frequency offset estimate As shown in formula (16).
  • Time Domain Correlation Results for DMRS Symbols When performing accumulation, a coherent accumulation method can be used, as shown in formula (16), or a non-coherent accumulation method, such as real part accumulation and amplitude accumulation, can also be used.
  • the confidence factor is 0.5; and The signs of are not the same, and If it is less than or equal to the adaptive threshold value, the confidence factor is 0.5; and in and The signs of are not the same, and If it is greater than the adaptive threshold, the confidence factor is 0.75.
  • the adaptive threshold setting can be 2000Hz.
  • the confidence factor can be selected to be 0.75, and the PSCCH demodulation performance can be improved by about 0.8 at the block error rate (BLER, Block Error Ratio) at 1% of the method without calibration.
  • BLER Block Error Ratio
  • dB compared with the method with a fixed confidence factor of 0.5, the signal-to-noise ratio at 1% of the BLER is improved by about 0.5dB. It can be seen from this that the performance of frequency offset estimation using the frequency offset estimation method of the embodiment of the present application is improved.
  • the electronic device 1000 includes: at least one processor 1001; and a memory 1002, on which at least one computer program is stored, When at least one computer program is executed by at least one processor 1001, the above frequency offset estimation method is realized.
  • Processor is a device with data processing capability, including but not limited to central processing unit (CPU), etc.; and memory is a device with data storage capability, including but not limited to random access memory (RAM, more specifically SDRAM, DDR etc.), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), and flash memory (FLASH).
  • RAM random access memory
  • ROM read-only memory
  • EEPROM electrically erasable programmable read-only memory
  • FLASH flash memory
  • the processor 1001 and the memory 1002 are connected to each other through a bus 1003 , and further connected to other components of the computing device.
  • an embodiment of the present application provides a computer-readable storage medium, where a computer program is stored on the computer-readable storage medium, and when the computer program is executed by a processor, the foregoing frequency offset estimation method is implemented.
  • FIG. 3 is a block diagram of a frequency offset estimation device provided by an embodiment of the present application.
  • the frequency offset estimation device includes a first frequency offset estimation module 201 , a second frequency offset estimation module 202 , a confidence factor selection module 203 , and a frequency offset calibration module 204 .
  • the first frequency offset estimation module 201 is configured to use the first frequency offset estimation method to perform frequency offset estimation on the DMRS signal sent by the terminal to obtain a first frequency offset estimation value;
  • the second frequency offset estimation module 202 is configured to use the second frequency offset estimation method Perform frequency offset estimation on the DMRS signal sent by the terminal to obtain a second frequency offset estimate;
  • the confidence factor selection module 203 is configured to determine a confidence factor according to the first frequency offset estimate and the second frequency offset estimate;
  • the frequency offset calibration module 204 is configured To calibrate the second estimated frequency offset value according to the confidence factor to obtain a final estimated frequency offset value.
  • the confidence factor selection module 203 is specifically configured to determine that there is no phase inversion when using the first frequency offset estimation method for frequency offset estimation according to the first frequency offset estimation value and the second frequency offset estimation value, Select a positive number from the first optional interval as the confidence factor; the first optional interval is an interval greater than 0 and less than or equal to 0.5.
  • the confidence factor selection module 203 is specifically configured to realize that there is no phase inversion when the first frequency offset estimation method is used for frequency offset estimation according to the first frequency offset estimation value and the second frequency offset estimation value in the following manner: According to the same sign of the first frequency offset estimation value and the second frequency offset estimation value, it is determined that there is no phase inversion when the first frequency offset estimation method is used for frequency offset estimation.
  • the confidence factor selection module 203 is specifically configured to: when it is determined according to the first frequency offset estimation value and the second frequency offset estimation value that there is a phase inversion when the first frequency offset estimation method is used for frequency offset estimation, and the first When the absolute value of the difference between the estimated frequency offset value and the second estimated frequency offset value is less than or equal to the adaptive threshold value, select a positive number from the first optional interval as the confidence factor; the first optional interval is greater than The interval between 0 and less than or equal to 0.5.
  • the confidence factor selection module 203 is specifically configured to determine the confidence factor according to the first frequency offset estimate and the second frequency offset estimate in the following manner: When the first frequency offset estimation method is used for frequency offset estimation, there is a phase inversion, and the absolute value of the difference between the first frequency offset estimation value and the second frequency offset estimation value is greater than the adaptive threshold value, from the second Select a positive number in the optional interval as the confidence factor; the second optional interval is an interval greater than 0.5 and less than or equal to 1.
  • the confidence factor selection module 203 is specifically configured to use the following method to realize phase inversion when the frequency offset estimation is performed using the first frequency offset estimation method according to the first frequency offset estimation value and the second frequency offset estimation value: according to The signs of the first frequency offset estimation value and the second frequency offset estimation value are different to determine that phase inversion exists when the first frequency offset estimation method is used for frequency offset estimation.
  • the adaptive threshold value is a value selected from the optional interval of the adaptive threshold, the optional interval of the adaptive threshold is an interval greater than 0 and less than or equal to the target value, the target value and the maximum frequency offset value The absolute value of the difference is less than or equal to the preset threshold.
  • the frequency offset calibration module 204 is specifically configured to: multiply the confidence factor by the second estimated frequency offset value to obtain a final estimated frequency offset value.
  • the specific implementation process of the above frequency offset estimation device is similar to the specific implementation process of the frequency offset estimation method in the foregoing embodiments, and will not be repeated here.
  • the division between functional modules/units mentioned in the above description does not necessarily correspond to the division of physical components; for example, one physical component may have multiple functions, or one function or step may be composed of several physical components. Components cooperate to execute.
  • Some or all of the physical components may be implemented as software executed by a processor, such as a central processing unit, digital signal processor, or microprocessor, or as hardware, or as an integrated circuit, such as an application-specific integrated circuit circuit.
  • Such software may be distributed on computer readable media, which may include computer storage media (or non-transitory media) and communication media (or transitory media).
  • computer storage media includes both volatile and nonvolatile media implemented in any method or technology for storage of information, such as computer readable instructions, data structures, program modules, or other data. permanent, removable and non-removable media.
  • Computer storage media include, but are not limited to, RAM, ROM, EEPROM, flash memory or other memory technology, CD-ROM, digital versatile disk (DVD) or other optical disk storage, magnetic cartridges, tape, magnetic disk storage or other magnetic storage, or may be used Any other medium that stores desired information and can be accessed by a computer.
  • communication media typically embodies computer readable instructions, data structures, program modules, or other data in a modulated data signal such as a carrier wave or other transport mechanism, and may include any information delivery media .

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Abstract

一种频偏估计方法、一种频偏估计装置、一种电子设备、以及一种计算机可读存储介质，所述频偏估计方法包括：采用第一频偏估计方法对终端发送的解调参考信号(DMRS信号)进行频偏估计得到第一频偏估计值（100）；采用第二频偏估计方法对所述终端发送的DMRS信号进行频偏估计得到第二频偏估计值（101）；以及根据所述第一频偏估计值和所述第二频偏估计值确定置信因子，根据所述置信因子对所述第二频偏估计值进行校准得到最终频偏估计值（102）。

Description

频偏估计方法及装置、电子设备、及计算机可读存储介质
相关申请的交叉引用
本申请要求于2021年9月18日提交的中国专利申请NO.202111112962.2的优先权，该中国专利申请的内容通过引用的方式整体合并于此。
技术领域
本申请实施例涉及通信技术领域，特别涉及频偏估计方法及装置、电子设备、及计算机可读存储介质。
背景技术
车联万物(V2X，Vehicle-to-Everything)技术目前正处于快速发展期，车联网会通过整合全球定位导航技术、V2X的交流技术、无线通信及远程感应技术奠定新汽车技术的发展方向，相关产业将高速发展。
V2X主要包括以下四种类型：车到车(V2V，Vehicle-to-Vehicle)、车到路(V2I，Vehicle-to-Infrastructure)、车到网(V2N，Vehicle-to-Network)、以及车到人(V2P，Vehicle-to-Pedestrian)。在V2X车联网应用中车辆移动速度快，支持的最快相对移动速度为约500千米每小时(km/h)，工作在5855兆赫兹(MHz)到5925MHz的频段上，最大的多普勒频移为约2700赫兹(Hz)；同时考虑最大载波频偏为约0.3百万分率(ppm)，长期演进(LTE，Long Term Evolution)和第五代移动通信技术(5G，5th Generation Mobile Communication Technology)新无线电(NR，New Radio)V2X可能工作在5855MHz到5925MHz的频段，则最大载波频偏约为1800Hz；由以上所述可知，高速移动和高载频带来的最大频偏约为4500Hz，这将严重影响系统的解调性能。因此，需要对频偏进行估计，然后通过某些特定方法对 频偏进行补偿。
相关的频偏估计方法有两种：相邻解调参考信号(DMRS，Demodulation reference signal)频域频偏估计方法和半符号时域频偏估计方法。相邻DMRS频域频偏估计方法估计准确度高，但当多普勒频移比较大时，可能会出现许多由于超出估计范围而导致的估计值反相的问题，从而导致估计性能急剧恶化；以及，半符号时域频偏估计方法的估计范围足够大，但是准确度较低，方差大，可能会给解调性能带来一定损失。综上，在频偏范围较大的应用场景下，上述的频偏估计方法的估计性能较低。
公开内容
第一方面，本申请实施例提供一种频偏估计方法，包括：采用第一频偏估计方法对终端发送的解调参考信号(DMRS，Demodulation reference signal)进行频偏估计得到第一频偏估计值；采用第二频偏估计方法对终端发送的DMRS信号进行频偏估计得到第二频偏估计值；以及根据所述第一频偏估计值和所述第二频偏估计值确定置信因子，根据所述置信因子对所述第二频偏估计值进行校准得到最终频偏估计值。
第二方面，本申请实施例提供一种电子设备，包括：至少一个处理器；以及存储器，存储器上存储有至少一个计算机程序，当所述至少一个计算机程序被所述至少一个处理器执行时，实现上述频偏估计方法。
第三方面，本申请实施例提供一种计算机可读存储介质，所述计算机可读存储介质上存储有计算机程序，所述计算机程序被处理器执行时实现上述频偏估计方法。
第四方面，本申请实施例提供一种频偏估计装置，包括：第一频偏估计模块，配置为采用第一频偏估计方法对终端发送的DMRS信号进行频偏估计得到第一频偏估计值；第二频偏估计模块，配置为采用第二频偏估计方法对终端发送的DMRS信号进行频偏估计得到第二频偏估计值；置信因子选择模块，配置为根据第一频偏估计值和第二 频偏估计值确定置信因子；以及频偏校准模块，配置为根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。
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图1为本申请实施例提供的频偏估计方法的流程图；
图2为本申请实施例提供的电子设备的组成框图；以及
图3为本申请实施例提供的频偏估计装置的组成框图。
具体实施方式
为使本领域的技术人员更好地理解本申请的技术方案，下面结合附图对本申请提供的频偏估计方法及装置、电子设备、以及计算机可读存储介质进行详细描述。
在下文中将参考附图更充分地描述示例实施例，但是所述示例实施例可以以不同形式来体现，且本公开不应当被解释为限于本文阐述的实施例。提供这些实施例的目的在于使本申请更加透彻和完整，并使本领域技术人员充分理解本申请的范围。
在不冲突的情况下，本申请各实施例及实施例中的各特征可相互组合。
如本文所使用的，术语“和/或”包括至少一个相关列举条目的任何和所有组合。
本文所使用的术语仅用于描述特定实施例，且不意欲限制本申请。如本文所使用的，单数形式“一个”和“该”也意欲包括复数形式，除非上下文另外清楚指出。还将理解的是，当本说明书中使用术语“包括”和/或“由……制成”时，指定存在特定特征、整体、步骤、操作、元件和/或组件，但不排除存在或可添加至少一个其它特征、整体、步骤、操作、元件、组件和/或其群组。
除非另外限定，否则本文所用的所有术语(包括技术和科学术语)的含义与本领域普通技术人员通常理解的含义相同。还将理解，诸如在常用字典中限定的那些术语应当被解释为具有与其在相关技术以及本申请的背景下的含义一致的含义，且将不解释为具有理想化或过 度形式上的含义，除非本文明确如此限定。
相关的频偏估计方法有两种：相邻解调参考信号(DMRS，Demodulation reference signal)频域频偏估计方法和半符号时域频偏估计方法。
相邻DMRS频域频偏估计方法通过计算相邻的DMRS符号上的相位变化来获得频偏估计值。在长期演进(LTE，Long Term Evolution)车联万物(V2X，Vehicle-to-Everything)场景中，相邻DMRS符号间隔为3个符号(symbol)，能估计的最大频偏范围为±2336赫兹(Hz)；以及，在第五代移动通信技术(5G，5th Generation Mobile Communication Technology)新无线电(NR，New Radio)V2X场景中，相邻DMRS符号间隔最小为3个符号，最大为7个符号，能估计的最大频偏范围为±4672Hz。V2X的最大可能频偏约为±4500Hz，则在LTE V2X场景下V2X的频偏范围超出了相邻DMRS频域频偏估计方法的估计范围，可能会发生相位翻转从而出现反相，在5G NR V2X场景下，考虑到噪声的影响，采用相邻DMRS频域频偏估计方法也有可能发生相位翻转而出现反相。
半符号时域频偏估计方法通过对前半个符号和后半个符号上信号的时域相关结果求相位角的方式来获得频偏估计值，该方法的频偏估计范围为±△f(△f为子载波间隔)，足够覆盖V2X的极端场景，但是受信道和噪声的影响，估计准确度较差，且由于V2X的业务特性，半符号时域频偏估计方法无法在时间上进行滤波进而收敛至一个准确的值。
总而言之，相邻DMRS频域频偏估计方法估计准确度高，但当多普勒频移比较大时，可能会出现许多由于超出估计范围而导致的估计值反相的问题，从而导致估计性能急剧恶化；以及，半符号时域频偏估计方法的估计范围足够大，但是准确度较低，方差大，可能会给解调性能带来一定损失。综上，在频偏范围较大的应用场景下，相关的频偏估计方法的估计性能较低。
需要说明的是，本申请实施例的频偏估计方法虽然是基于LTE V2X场景和5G NR V2X场景所存在的问题提出的，但是，本申请实施 例的频偏估计方法也可以应用于其他任何场景的频偏估计。
本申请实施例的频偏估计方法虽然是基于相邻DMRS频域频偏估计方法和半符号时域频偏估计方法存在的问题所提出的，但是本申请实施例的频偏估计方法同样适用于第一频偏估计方法和第二频偏估计方法出现与上述两种方法相同问题的情况，第一频偏估计方法与相邻DMRS频域频偏估计方法类似，均是在多普勒频移量较大时可能出现相位翻转情况的频偏估计方法，第二频偏估计方法与半符号时域频偏估计方法类似，均是频偏估计范围较大，但是准确度较低的频偏估计方法。
图1为本申请实施例提供的频偏估计方法的流程图。
第一方面，参照图1，本申请实施例提供一种频偏估计方法，包括步骤100至步骤102。
步骤100、采用第一频偏估计方法对终端发送的DMRS信号进行频偏估计得到第一频偏估计值。
在一些实施方式中，第一频偏估计方法是指在多普勒频移量较大时可能出现相位翻转情况的频偏估计方法，如相邻DMRS频移频偏估计方法。
在本申请实施例中，可以仅接收一个终端发送的DMRS信号，也可以同时接收两个或两个以上终端发送的DMRS信号。如果同时接收两个或两个以上终端发送的DMRS信号，则分别对每一个终端发送的DMRS信号进行频偏估计。例如同时接收终端1、终端2、以及终端3发送的DMRS信号，并采用第一频偏估计方法对终端1发送的DMRS信号进行频偏估计得到第一频偏估计值1，采用第一频偏估计方法对终端2发送的DMRS信号进行频偏估计得到第一频偏估计值2，以及采用第一频偏估计方法对终端3发送的DMRS信号进行频偏估计得到第一频偏估计值3。
在本申请实施例中，同一个终端发送的DMRS信号可以是一个，也可以是两个或两个以上。如果同一个终端发送的DMRS信号为两个或两个以上，则在分别对每一个终端发送的DMRS信号进行频偏估计时，对同一个终端发送的DMRS信号进行频偏估计。
本申请实施例对DMRS信号不作具体限定。例如，DMRS信号可以是物理直连通信控制信道(PSCCH，Physical Sidelink Control Channel)DMRS信号，也可以是物理直连通信共享信道(PSSCH，Physical Sidelink Shared Channel)DMRS信号。
步骤101、采用第二频偏估计方法对终端发送的DMRS信号进行频偏估计得到第二频偏估计值。
在一些实施方式中，第二频偏估计方法是指频偏估计范围较大，但准确度较低的频偏估计方法，如半符号时域频偏估计方法。
在本申请实施例中，可以仅接收一个终端发送的DMRS信号，也可以同时接收两个或两个以上终端发送的DMRS信号。如果同时接收两个或两个以上终端发送的DMRS信号，则分别对每一个终端发送的DMRS信号进行频偏估计。例如同时接收终端1、终端2、以及终端3发送的DMRS信号，并采用第二频偏估计方法对终端1发送的DMRS信号进行频偏估计得到第二频偏估计值1，采用第二频偏估计方法对终端2发送的DMRS信号进行频偏估计得到第二频偏估计值2，以及采用第二频偏估计方法对终端3发送的DMRS信号进行频偏估计得到第二频偏估计值3。
在本申请实施例中，同一个终端发送的DMRS信号可以是一个，也可以是两个或两个以上。如果同一个终端发送的DMRS信号为两个或两个以上，则在分别对每一个终端发送的DMRS信号进行频偏估计时，对同一个终端发送的DMRS信号进行频偏估计。
步骤102、根据第一频偏估计值和第二频偏估计值确定置信因子，根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。
在本申请实施例中，可以仅接收一个终端发送的DMRS信号，也可以同时接收两个或两个以上终端发送的DMRS信号。如果同时接收两个或两个以上终端发送的DMRS信号，则分别根据每一个终端对应的第一频偏估计值和第二频偏估计值确定置信因子，根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。例如同时接收终端1、终端2、以及终端3发送的DMRS信号，则对于终端1，根据第一频偏估计值1和第二频偏估计值1确定置信因子1，根据置信因子1对第 二频偏估计值1进行校准得到最终频偏估计值1；对于终端2，根据第一频偏估计值2和第二频偏估计值2确定置信因子2，根据置信因子2对第二频偏估计值2进行校准得到最终频偏估计值2；以及对于终端3，根据第一频偏估计值3和第二频偏估计值3确定置信因子3，根据置信因子3对第二频偏估计值3进行校准得到最终频偏估计值3。
在本申请实施例中，采用第一频偏估计方法进行频偏估计时包括存在相位翻转和不存在相位翻转两种情况，针对置信因子在这两种情况下的确定方法，下面分别进行描述。
一、针对采用第一频偏估计方法进行频偏估计时不存在相位翻转的情况，根据第一频偏估计值和第二频偏估计值确定置信因子包括：在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时不存在相位翻转的情况下，从第一可选区间内选择一个正数作为置信因子；第一可选区间为大于0且小于或等于0.5的区间。
在一些实施方式中，由于采用第一频偏估计方法进行频偏估计时不存在相位翻转直接导致的结果就是第一频偏估计值和第二频偏估计值的正负号相同，因此，可以根据第一频偏估计值和第二频偏估计值的正负号是否相同确定采用第一频偏估计方法进行频偏估计时是否存在相位翻转。具体的，根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时不存在相位翻转包括：根据第一频偏估计值和第二频偏估计值的正负号相同确定采用第一频偏估计方法进行频偏估计时不存在相位翻转。
二、针对采用第一频偏估计方法进行频偏估计时存在相位翻转的情况，又可以分为两种情况，即，第一频偏估计值和第二频偏估计值之差的绝对值小于或等于自适应门限值，以及第一频偏估计值和第二频偏估计值之差的绝对值大于自适应门限值。
针对第一频偏估计值和第二频偏估计值之差的绝对值小于或等于自适应门限值的情况，根据第一频偏估计值和第二频偏估计值确定置信因子包括：在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且第一频偏估计值和 第二频偏估计值之差的绝对值小于或等于自适应门限值的情况下，从第一可选区间内选择一个正数作为置信因子；第一可选区间为大于0且小于或等于0.5的区间。
针对第一频偏估计值和第二频偏估计值之差的绝对值大于自适应门限值的情况，根据第一频偏估计值和第二频偏估计值确定置信因子包括：在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且第一频偏估计值和第二频偏估计值之差的绝对值大于自适应门限值的情况下，从第二可选区间内选择一个正数作为置信因子；第二可选区间为大于0.5且小于或等于1的区间。
在一些实施方式中，由于采用第一频偏估计方法进行频偏估计时存在相位翻转直接导致的结果就是第一频偏估计值和第二频偏估计值的正负号不同，因此，可以根据第一频偏估计值和第二频偏估计值的正负号是否相同确定是否存在相位翻转。具体的，根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转包括：根据第一频偏估计值和第二频偏估计值的正负号不同确定采用第一频偏估计方法进行频偏估计时存在相位翻转。
在一些实施方式中，自适应门限值为从自适应门限可选区间中选择的一个值，自适应门限可选区间为大于0且小于或等于目标数值的区间，目标数值和最大频偏值之差的绝对值小于或等于预设阈值。
在一些实施方式中，根据置信因子对第二频偏估计值进行校准得到最终频偏估计值包括：将置信因子和第二频偏估计值相乘得到最终频偏估计值。
本申请实施例提供的频偏估计方法采用第一频偏估计方法和第二频偏估计方法分别对终端发送的DMRS信号进行频偏估计得到第一频偏估计值和第二频偏估计值，根据第一频偏估计值和第二频偏估计值确定置信因子，进而根据置信因子对第二频偏估计值进行校准得到最终频偏估计值，通过结合第一频偏估计方法和第二偏估计方法进行频偏估计，既能满足较大的频偏范围，又提高了估计性能。
下面列举一个示例详细说明本申请实施例的频偏估计方法的具 体实现过程，所列举的示例仅仅是为了更直观的体现本申请实施例的频偏估计方法的实现过程，不用于限定本申请实施例的频偏估计方法的保护范围。
示例
本示例描述对LTE V2X系统中的PSCCH进行频偏估计的过程，LTE V2X系统中，扩展车辆信道模型(EVA，Extended Vehicle A model)的最大多普勒频移为2700Hz，载波频偏为600Hz，假设PSCCH DMRS信号映射在子帧中的第一个时隙的第2个符号(即l 0＝2)和第5个符号(即l 1＝5)、以及子帧中的第二个时隙的第1个符号(即l 2＝1)和第4个符号(即l 3＝4)，则接收到的PSCCH DMRS信号在子载波k上的频域接收信号分别为：
Figure PCTCN2022081933-appb-000001
Figure PCTCN2022081933-appb-000002
Figure PCTCN2022081933-appb-000003
Figure PCTCN2022081933-appb-000004
Figure PCTCN2022081933-appb-000005
表示符号l i的PSCCH DMRS信号在子载波k上的频域接收信号，
Figure PCTCN2022081933-appb-000006
表示符号l i的PSCCH DMRS信号在子载波k上的频域发送信号，
Figure PCTCN2022081933-appb-000007
表示符号l i的信道频域响应，f为载频，t为第一个时隙的第2个符号对应的时间，公式(2)中的△t为第一个时隙的第2个符号和第5个符号之间的相对时间，公式(4)中的△t为第二个时隙的第1个符号和第4个符号之间的相对时间，t′为第二个时隙的第1个符号对应的时间。
本示例采用本申请实施例提供的频偏估计方法对PSCCH DMRS信号进行频偏估计的具体实现过程包括步骤S1至S3。
S1、采用相邻DMRS频域频偏估计方法作为第一频偏估计方法对同一个终端发送的DMRS信号进行频偏估计得到第一频偏估计值。
采用本地PSCCH DMRS信号
Figure PCTCN2022081933-appb-000008
通过公式(5)至(8)对
Figure PCTCN2022081933-appb-000009
进行解扰处理，得到解扰后的信号分别为：
Figure PCTCN2022081933-appb-000010
Figure PCTCN2022081933-appb-000011
Figure PCTCN2022081933-appb-000012
Figure PCTCN2022081933-appb-000013
Figure PCTCN2022081933-appb-000014
表示对符号l i解扰后的信号。
对相邻DMRS符号解扰后的信号
Figure PCTCN2022081933-appb-000015
通过公式(9)和公式(10)进行共轭相乘。
Figure PCTCN2022081933-appb-000016
Figure PCTCN2022081933-appb-000017
假设
Figure PCTCN2022081933-appb-000018
则将所有DMRS子载波共轭相乘得到的结果进行累加，并求相位角,以得到第一频偏估计值
Figure PCTCN2022081933-appb-000019
如公式(11)所示。
Figure PCTCN2022081933-appb-000020
K为一个符号内的DMRS子载波的个数，∠表示求相位角，*表示求共轭。
将所有DMRS子载波共轭相乘得到的结果进行累加时，可以采用相干累加方法，如公式(11)所示，也可以采用非相干累加方法，如实部累加、以及幅度累加等方法。
S2、采用半符号时域频偏估计方法作为第二频偏估计方法对同一个终端发送的DMRS信号进行频偏估计得到第二频偏估计值。
将接收的DMRS信号的频域接收信号
Figure PCTCN2022081933-appb-000021
进行N点反向离散傅里叶变换(IDFT，Inverse Discrete Fourier Transform)或快速傅里叶逆变换(IFFT，Inverse Fast Fourier Transform)变换到时域信 号
Figure PCTCN2022081933-appb-000022
如公式(12)所示。
Figure PCTCN2022081933-appb-000023
将本地DMRS信号的频域信号
Figure PCTCN2022081933-appb-000024
进行N点IDFT或IFFT变换到时域信号
Figure PCTCN2022081933-appb-000025
如公式(13)所示。
Figure PCTCN2022081933-appb-000026
对本地DMRS信号的时域信号
Figure PCTCN2022081933-appb-000027
进行时偏估计得到偏移量d，对本地DMRS信号的时域信号
Figure PCTCN2022081933-appb-000028
进行时偏调整，如公式(14)所示。
Figure PCTCN2022081933-appb-000029
将时偏调整后的信号
Figure PCTCN2022081933-appb-000030
的前半个符号和后半个符号进行时域相关处理，如公式(15)所示。
Figure PCTCN2022081933-appb-000031
对4个DMRS符号的时域相关结果
Figure PCTCN2022081933-appb-000032
进行累加后求相位角，得到第二频偏估计值
Figure PCTCN2022081933-appb-000033
如公式(16)所示。
Figure PCTCN2022081933-appb-000034
对DMRS符号的时域相关结果
Figure PCTCN2022081933-appb-000035
进行累加时，可以采用相干累加方法，如公式(16)所示，也可以采用非相干累加方法，如实部累加、以及幅度累加等方法。
S3、根据第一频偏估计值和第二频偏估计值确定置信因子，根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。
在
Figure PCTCN2022081933-appb-000036
和
Figure PCTCN2022081933-appb-000037
的正负号相同的情况下，置信因子取0.5；在
Figure PCTCN2022081933-appb-000038
和
Figure PCTCN2022081933-appb-000039
的正负号不相同，且
Figure PCTCN2022081933-appb-000040
小于或等于自适应门限值的情况下，置信因子取0.5；以及在
Figure PCTCN2022081933-appb-000041
和
Figure PCTCN2022081933-appb-000042
的正负号不相同，且
Figure PCTCN2022081933-appb-000043
大于自适应门限值的情况下，置信因子取0.75。
自适应门限值设置可为2000Hz。
将置信因子和
Figure PCTCN2022081933-appb-000044
相乘得到最终频偏估计值。
采用本申请实施例的频偏估计方法，可以选择置信因子取0.75， PSCCH解调性能比不做校准的方法在误块率(BLER，Block Error Ratio)取1％处的信噪比提升约0.8dB，比固定置信因子取0.5的方法在BLER取1％处的信噪比提升约0.5dB，由此可以看出，采用本申请实施例的频偏估计方法进行频偏估计时性能得到提升。
第二方面，本申请另一个实施例提供一种电子设备1000，如图2所示，所述电子设备1000包括：至少一个处理器1001；以及存储器1002，存储器1002上存储有至少一个计算机程序，当至少一个计算机程序被至少一个处理器1001执行时，实现上述频偏估计方法。
处理器为具有数据处理能力的器件，包括但不限于中央处理器(CPU)等；以及，存储器为具有数据存储能力的器件，包括但不限于随机存取存储器(RAM，更具体如SDRAM、DDR等)、只读存储器(ROM)、带电可擦可编程只读存储器(EEPROM)、以及闪存(FLASH)。
在一些实施方式中，处理器1001、存储器1002通过总线1003相互连接，进而与计算设备的其它组件连接。
第三方面，本申请实施例提供一种计算机可读存储介质，所述计算机可读存储介质上存储有计算机程序，所述计算机程序被处理器执行时实现上述频偏估计方法。
图3为本申请实施例提供的频偏估计装置的组成框图。
第四方面，本申请实施例提供的频偏估计装置，包括第一频偏估计模块201、第二频偏估计模块202、置信因子选择模块203、以及频偏校准模块204。
第一频偏估计模块201配置为采用第一频偏估计方法对终端发送的DMRS信号进行频偏估计得到第一频偏估计值；第二频偏估计模块202配置为采用第二频偏估计方法对终端发送的DMRS信号进行频偏估计得到第二频偏估计值；置信因子选择模块203配置为根据第一频偏估计值和第二频偏估计值确定置信因子；以及频偏校准模块204配置为根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。
在一些实施方式中，置信因子选择模块203具体配置为在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行 频偏估计时不存在相位翻转的情况下，从第一可选区间内选择一个正数作为置信因子；第一可选区间为大于0且小于或等于0.5的区间。
在一些实施方式中，置信因子选择模块203具体配置为采用以下方式实现根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时不存在相位翻转：根据第一频偏估计值和第二频偏估计值的正负号相同确定采用第一频偏估计方法进行频偏估计时不存在相位翻转。
在一些实施方式中，置信因子选择模块203具体配置为：在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且第一频偏估计值和第二频偏估计值之差的绝对值小于或等于自适应门限值的情况下，从第一可选区间内选择一个正数作为置信因子；第一可选区间为大于0且小于或等于0.5的区间。
在一些实施方式中，置信因子选择模块203具体配置为采用以下方式实现根据第一频偏估计值和第二频偏估计值确定置信因子：在根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且第一频偏估计值和第二频偏估计值之差的绝对值大于自适应门限值的情况下，从第二可选区间内选择一个正数作为置信因子；第二可选区间为大于0.5且小于或等于1的区间。
在一些实施方式中，置信因子选择模块203具体配置为采用以下方式实现根据第一频偏估计值和第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转：根据第一频偏估计值和第二频偏估计值的正负号不同确定采用第一频偏估计方法进行频偏估计时存在相位翻转。
在一些实施方式中，自适应门限值为从自适应门限可选区间中选择的一个值，自适应门限可选区间为大于0且小于或等于目标数值的区间，目标数值和最大频偏值之差的绝对值小于或等于预设阈值。
在一些实施方式中，频偏校准模块204具体配置为：将置信因子和第二频偏估计值相乘得到最终频偏估计值。
上述频偏估计装置的具体实现过程与前述实施例频偏估计方法的具体实现过程类似，这里不再赘述。
本领域普通技术人员可以理解，上文中所公开方法中的全部或某些步骤、及装置中的功能模块/单元可以被实施为软件、固件、硬件及其适当的组合。在硬件实施方式中，在以上描述中提及的功能模块/单元之间的划分不一定对应于物理组件的划分；例如，一个物理组件可以具有多个功能，或者一个功能或步骤可以由若干物理组件合作执行。某些物理组件或所有物理组件可以被实施为由处理器(如中央处理器、数字信号处理器或微处理器)执行的软件，或者被实施为硬件，或者被实施为集成电路，如专用集成电路。这样的软件可以分布在计算机可读介质上，计算机可读介质可以包括计算机存储介质(或非暂时性介质)和通信介质(或暂时性介质)。如本领域普通技术人员公知的，术语计算机存储介质包括在用于存储信息(诸如计算机可读指令、数据结构、程序模块或其它数据)的任何方法或技术中实施的易失性和非易失性、可移除和不可移除介质。计算机存储介质包括但不限于RAM、ROM、EEPROM、闪存或其它存储器技术、CD-ROM、数字多功能盘(DVD)或其它光盘存储、磁盒、磁带、磁盘存储或其它磁存储器、或者可以用于存储期望的信息并且可以被计算机访问的任何其它的介质。此外，本领域普通技术人员公知的是，通信介质通常包含计算机可读指令、数据结构、程序模块或者诸如载波或其它传输机制之类的调制数据信号中的其它数据，并且可包括任何信息递送介质。
本文已经公开了示例实施例，并且虽然采用了具体术语，但它们仅用于并仅应当被解释为一般说明性含义，并且不用于限制的目的。在一些实例中，对本领域技术人员显而易见的是，除非另外明确指出，否则与特定实施例相结合描述的特征、特性和/或元素可单独使用，或可与结合其它实施例描述的特征、特性和/或元件组合使用。因此，本领域技术人员将理解，在不脱离由所附的权利要求阐明的本申请的范围的情况下，可进行各种形式和细节上的改变。

Claims (11)

  1. 一种频偏估计方法，包括：
    采用第一频偏估计方法对终端发送的解调参考信号(DMRS信号)进行频偏估计得到第一频偏估计值；
    采用第二频偏估计方法对所述终端发送的DMRS信号进行频偏估计得到第二频偏估计值；以及
    根据所述第一频偏估计值和所述第二频偏估计值确定置信因子，根据所述置信因子对所述第二频偏估计值进行校准得到最终频偏估计值。
  2. 根据权利要求1所述的频偏估计方法，其中，所述根据所述第一频偏估计值和所述第二频偏估计值确定置信因子包括：
    在根据所述第一频偏估计值和所述第二频偏估计值确定采用第一频偏估计方法进行频偏估计时不存在相位翻转的情况下，从第一可选区间内选择一个正数作为所述置信因子；其中，所述第一可选区间为大于0且小于或等于0.5的区间。
  3. 根据权利要求2所述的频偏估计方法，其中，所述根据所述第一频偏估计值和所述第二频偏估计值确定采用第一频偏估计方法进行频偏估计时不存在相位翻转包括：
    根据所述第一频偏估计值和所述第二频偏估计值的正负号相同确定采用第一频偏估计方法进行频偏估计时不存在相位翻转。
  4. 根据权利要求1所述的频偏估计方法，其中，所述根据所述第一频偏估计值和所述第二频偏估计值确定置信因子包括：
    在根据所述第一频偏估计值和所述第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且所述第一频偏估计值和所述第二频偏估计值之差的绝对值小于或等于自适应门限值的情况下，从第一可选区间内选择一个正数作为所述置信因子；其中， 所述第一可选区间为大于0且小于或等于0.5的区间。
  5. 根据权利要求1所述的频偏估计方法，其中，所述根据所述第一频偏估计值和所述第二频偏估计值确定置信因子包括：
    在根据所述第一频偏估计值和所述第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转，且所述第一频偏估计值和所述第二频偏估计值之差的绝对值大于自适应门限值的情况下，从第二可选区间内选择一个正数作为所述置信因子；其中，所述第二可选区间为大于0.5且小于或等于1的区间。
  6. 根据权利要求4或5所述的频偏估计方法，其中，所述根据所述第一频偏估计值和所述第二频偏估计值确定采用第一频偏估计方法进行频偏估计时存在相位翻转包括：
    根据所述第一频偏估计值和所述第二频偏估计值的正负号不同确定采用第一频偏估计方法进行频偏估计时存在相位翻转。
  7. 根据权利要求4或5所述的频偏估计方法，其中，所述自适应门限值为从自适应门限可选区间中选择的一个值，所述自适应门限可选区间为大于0且小于或等于目标数值的区间，所述目标数值和最大频偏值之差的绝对值小于或等于预设阈值。
  8. 根据权利要求1所述的频偏估计方法，其中，所述根据所述置信因子对所述第二频偏估计值进行校准得到最终频偏估计值包括：
    将所述置信因子和所述第二频偏估计值相乘得到所述最终频偏估计值。
  9. 一种电子设备，包括：
    至少一个处理器；以及
    存储器，所述存储器上存储有至少一个计算机程序，当所述至少一个计算机程序被所述至少一个处理器执行时，实现权利要求1 至8中任意一项所述的频偏估计方法。
  10. 一种计算机可读存储介质，所述计算机可读存储介质上存储有计算机程序，所述计算机程序被处理器执行时实现权利要求1至8中任意一项所述的频偏估计方法。
  11. 一种频偏估计装置，包括：
    第一频偏估计模块，配置为采用第一频偏估计方法对终端发送的DMRS信号进行频偏估计得到第一频偏估计值；
    第二频偏估计模块，配置为采用第二频偏估计方法对终端发送的DMRS信号进行频偏估计得到第二频偏估计值；
    置信因子选择模块，配置为根据第一频偏估计值和第二频偏估计值确定置信因子；以及
    频偏校准模块，配置为根据置信因子对第二频偏估计值进行校准得到最终频偏估计值。
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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116455719A (zh) * 2023-06-16 2023-07-18 南京创芯慧联技术有限公司 频偏估计方法、装置、通信设备和可读存储介质

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2014116944A2 (en) * 2013-01-24 2014-07-31 Blackberry Limited Cell identity design for lte-advanced
CN108337202A (zh) * 2017-01-19 2018-07-27 三星电子株式会社 利用频率偏移偏差去除来进行频率估计的系统和方法
CN110199506A (zh) * 2019-04-18 2019-09-03 北京小米移动软件有限公司 频偏确定方法和装置以及资源块发送方法和装置

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2014116944A2 (en) * 2013-01-24 2014-07-31 Blackberry Limited Cell identity design for lte-advanced
CN108337202A (zh) * 2017-01-19 2018-07-27 三星电子株式会社 利用频率偏移偏差去除来进行频率估计的系统和方法
CN110199506A (zh) * 2019-04-18 2019-09-03 北京小米移动软件有限公司 频偏确定方法和装置以及资源块发送方法和装置

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
DU FENG, LI GUANG-XIA ,XIANG ZHONG-W U ,TANG JING-YU ,ZHANG XUN ,YUN FEI-LONG: "A Feed-forward Frequency Offset Estimation Algorithm Based on Time and Frequency Domain", DIANZI ZHILIANG - ELECTRONICS QUALITY, GUANGZHOU SHI JULIU XINXI KEJI CHUANMEI YOUXIAN GONGSI,DOMINANT INFORMATION TECHNOLOGY MEDIA COMPANY LIMITED, CN, no. 5, 20 May 2016 (2016-05-20), CN , pages 1 - 6, XP093048353, ISSN: 1003-0107 *

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN116455719A (zh) * 2023-06-16 2023-07-18 南京创芯慧联技术有限公司 频偏估计方法、装置、通信设备和可读存储介质
CN116455719B (zh) * 2023-06-16 2023-09-05 南京创芯慧联技术有限公司 频偏估计方法、装置、通信设备和可读存储介质

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