WO2022142278A1 - 超宽范围大功率变换器电路 - Google Patents

超宽范围大功率变换器电路 Download PDF

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Publication number
WO2022142278A1
WO2022142278A1 PCT/CN2021/107056 CN2021107056W WO2022142278A1 WO 2022142278 A1 WO2022142278 A1 WO 2022142278A1 CN 2021107056 W CN2021107056 W CN 2021107056W WO 2022142278 A1 WO2022142278 A1 WO 2022142278A1
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Prior art keywords
network
voltage
module
transformer
primary
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PCT/CN2021/107056
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English (en)
French (fr)
Inventor
刘慧�
Original Assignee
深圳市优优绿能电气有限公司
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Publication of WO2022142278A1 publication Critical patent/WO2022142278A1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • B—PERFORMING OPERATIONS; TRANSPORTING
    • B60—VEHICLES IN GENERAL
    • B60L—PROPULSION OF ELECTRICALLY-PROPELLED VEHICLES; SUPPLYING ELECTRIC POWER FOR AUXILIARY EQUIPMENT OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRODYNAMIC BRAKE SYSTEMS FOR VEHICLES IN GENERAL; MAGNETIC SUSPENSION OR LEVITATION FOR VEHICLES; MONITORING OPERATING VARIABLES OF ELECTRICALLY-PROPELLED VEHICLES; ELECTRIC SAFETY DEVICES FOR ELECTRICALLY-PROPELLED VEHICLES
    • B60L53/00—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles
    • B60L53/20—Methods of charging batteries, specially adapted for electric vehicles; Charging stations or on-board charging equipment therefor; Exchange of energy storage elements in electric vehicles characterised by converters located in the vehicle
    • B60L53/22—Constructional details or arrangements of charging converters specially adapted for charging electric vehicles
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/70—Energy storage systems for electromobility, e.g. batteries
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/60—Other road transportation technologies with climate change mitigation effect
    • Y02T10/72—Electric energy management in electromobility
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02T—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO TRANSPORTATION
    • Y02T10/00—Road transport of goods or passengers
    • Y02T10/80—Technologies aiming to reduce greenhouse gasses emissions common to all road transportation technologies
    • Y02T10/92—Energy efficient charging or discharging systems for batteries, ultracapacitors, supercapacitors or double-layer capacitors specially adapted for vehicles

Definitions

  • the invention relates to the field of power modules, and more particularly, to an ultra-wide range high-power converter circuit.
  • the input is a three-phase AC power grid. Because of the power factor requirements, the pre-stage needs to design a three-phase active power factor correction circuit. Because of the input of the three-phase power grid, the output bus voltage of the three-phase active power factor correction circuit is relatively high. According to the current device situation, electrolytic capacitors are usually connected in series, as shown in Figure 1.
  • Figure 2A connects the mid-point of the DC input bus capacitor and the mid-point of the PFC output bus capacitor, so that the DC converter input bus capacitor does not have the problem of voltage equalization, but the PFC output bus capacitor has a larger capacitor.
  • Equalizing pressure requires equalizing control on the PFC side.
  • the high frequency ripple of the DC converter will enter the PFC output bus capacitor.
  • Figure 2B the mid-point of the DC input bus capacitor and the mid-point of the PFC output bus capacitor are separated by a resistor, so that the PFC side is not affected by DC, and the high-frequency ripple will not affect the PFC output bus capacitor.
  • FIG. 3 A schematic structural diagram of the wide-range constant power converter is shown in FIG. 3 .
  • the circuit components such as resonant capacitor Lr, resonant capacitor Cr, transformer excitation inductance Lm and other resonant component parameters are different, and the deviation of these resonant component parameters is usually in the range of 5% and 10%.
  • four voltage balancing networks are set up on the secondary side of the transformer to solve the voltage balancing problem caused by the difference of circuit parameters in the topology, so as to ensure the voltage balancing capability of the primary and secondary capacitors.
  • the output capacitor has a large bias voltage, which cannot be automatically adjusted, triggering the secondary side bias voltage shutdown. If you just change the load form, change to the CR gear of the electronic load, or the CV gear (current limiting to ensure the same load), the same load will not bias the shutdown with the same output voltage. Under the same load condition, when the output voltage is changed to 500V, there will be no bias shutdown. Or just change the load size and there will be no bias shutdown either. Or with other larger loads, adjust to 0.1A steady state after startup, and there will be no bias shutdown. This kind of bias will only occur under light loads in certain circumstances, and heavy loads will not occur.
  • the primary-side bias shutdown is also similar and will not be described in detail here.
  • the cause of the bias voltage in this particular case is not caused by the parameter deviation of the resonant element, but caused by the change of the wave control of the LLC resonant converter under light load.
  • Range constant power converters cannot solve such a voltage sharing problem.
  • the technical problem to be solved by the present invention is to provide an ultra-wide-range high-power solution that can solve the special voltage-equalizing problem due to the bias problem caused by the change of the LLC resonant converter under light load in the above-mentioned specific situation. converter circuit.
  • the technical solution adopted by the present invention to solve the technical problem is to construct an ultra-wide-range high-power converter circuit, including a first transformer module, a second transformer module, and a first transformer module arranged on the primary side of the first transformer module.
  • the second secondary side output module, and a high and low voltage mode control module for controlling the first secondary side output module and the second secondary side output module to be connected in series in high voltage mode and in parallel in low voltage mode, and for a load output module that receives the series output voltage or the parallel output voltage of the first secondary side output module and the second secondary side output module;
  • the first secondary side output module includes a first rectifier network, a second rectifier network and a first parameter voltage balancing network
  • the second secondary side output module includes a third rectifier network, a fourth rectifier network and
  • the ultra-wide-range high-power converter circuit includes a first resonant voltage balancing network and a second resonant voltage balancing network
  • the first resonant voltage balancing network includes a first resonant voltage balancing unit and a second resonant voltage balancing unit
  • the second resonant voltage balancing network includes a third resonant voltage balancing unit and a fourth resonant voltage balancing unit
  • the first parameter voltage balancing network includes a first parameter balancing unit A voltage equalizing unit and a second parameter voltage equalizing unit
  • the second parameter voltage equalizing network includes a third parameter voltage equalizing unit and a fourth parameter voltage equalizing unit.
  • the first transformer module includes at least a first transformer network and a second transformer network, and the primary sides of the first transformer network and the second transformer network are connected in series, the secondary sides of the first transformer network and the second transformer network are respectively connected to the first secondary side output module
  • the second transformer module includes at least a third transformer network and a fourth transformer network, the first The primary sides of the third transformer network and the fourth transformer network are connected in series, and the secondary sides of the third transformer network and the fourth transformer network are respectively connected to the second secondary side output module.
  • the first input end of the first rectifier network is connected to the secondary side of the first transformer network, and the second input end is connected to the secondary side of the second transformer network.
  • the first output end is connected to the first end of the third rectifier network, the first end of the first parameter voltage balancing unit and the first end of the second parameter voltage balancing unit, the first resonance
  • the first end of the voltage balancing unit and the first end of the second resonant voltage balancing unit, the second output end is connected to the fifth and sixth ends of the third rectifier network, and the first parameter of the voltage balancing unit.
  • the second end and the second end of the second parameter voltage balancing unit, the second end of the first resonant voltage balancing unit and the second end of the second resonant voltage balancing unit; the second end of the second rectifier network The first input terminal is connected to the secondary side of the first transformer network, the second input terminal is connected to the secondary side of the second transformer network, and the first output terminal is connected to the first terminal and the second terminal of the fourth rectifier network, The first end of the third parameter voltage balancing unit and the first end of the fourth parameter voltage balancing unit, the first end of the third resonant voltage balancing unit and the first end of the fourth resonant voltage balancing unit terminal, the second output terminal is connected to the fifth terminal and the sixth terminal of the fourth rectifier network, the second terminal of the third parameter voltage equalizing unit and the second terminal of the fourth parameter voltage equalizing unit, the The second end of the third resonant voltage balancing unit and the second end of the fourth resonant voltage balancing unit; the third end of the
  • the first primary input module includes a first primary voltage balancing network, a first switch module and a first LC module
  • the second primary input The module includes a second primary voltage equalization network, a second switch module and a second LC module, the first primary voltage equalization network is connected between the first input capacitor and the second switch module, and the second primary voltage is The voltage network is connected between the second input capacitor and the first switch module, the first switch module is connected to the first transformer module via the first LC module, and the second switch module is connected via the second The LC module is connected to the second transformer module.
  • the first primary voltage balancing network includes a first primary voltage balancing unit and a second primary voltage balancing unit
  • the first switch module includes a first primary voltage balancing unit.
  • the first LC module includes a first LC network and a second LC network
  • the second primary voltage equalization network includes a third primary voltage equalization unit and a fourth primary voltage equalization unit
  • the second switch module includes a third switch network and a fourth switch network
  • the second LC module includes a third LC network and a fourth LC network.
  • the first end of the first input capacitor is connected to the first end of the first primary voltage equalizing unit and the second primary voltage equalizing unit.
  • the second end of the second input capacitor is connected to the second end of the third switch network and the fourth switch network the second end of the first primary side voltage balancing unit, the second end of the second primary side voltage balancing unit is connected to the first end of the second switch network;
  • the first primary side The third end of the voltage balancing unit is connected to the third end of the third switching network and the third transformer network;
  • each voltage equalizing unit includes at least one diode series voltage dividing branch and at least one LC resonance branch, and the diode series voltage dividing branch includes at least one pair of A series diode, the central connection point of the at least one pair of series diodes is a voltage dividing point, and the two ends of the series voltage dividing branch of the diodes constitute the first end and the second end of the voltage equalizing unit; the LC resonance branch
  • the circuit includes at least one group of resonance inductors and resonance capacitors connected in series. The first end of the LC resonance branch is connected to the voltage dividing point, and the second end forms the third end of the voltage equalizing unit.
  • the high-low voltage mode control module includes a first switch, a second switch and a third switch, the first switch is connected to the high-voltage between the first end and the second end of the low voltage mode control module, the second switch is connected between the first end of the high and low voltage mode control module and the second end of the load output module, the first end A three-way switch is connected between the second end of the high and low voltage mode control module and the first end of the load output module.
  • the first transformer network and the second transformer network respectively include one transformer or more than one transformers connected in series with each other.
  • Fig. 1 is the connection schematic diagram of the three-phase active power factor correction circuit of the charging power module of the prior art
  • 2A is a schematic circuit diagram of a two-stage topology of a charging power supply module in a first manner of the prior art
  • 2B is a schematic circuit diagram of a two-stage topology of a charging power module according to a second mode of the prior art
  • Fig. 3 is the circuit topology diagram of the wide-range constant power converter mentioned in the background art
  • FIG. 4 is a schematic block diagram of an ultra-wide-range high-power converter circuit according to a preferred embodiment of the present invention.
  • FIG. 5 is a circuit schematic diagram of a preferred embodiment of an ultra-wide range high-power converter circuit according to a preferred embodiment of the present invention
  • FIG. 6 is a schematic block diagram of another preferred embodiment of the ultra-wide range high-power converter circuit according to the preferred embodiment of the present invention.
  • FIG. 7 is a circuit schematic diagram of another preferred embodiment of the ultra-wide range high-power converter circuit according to the preferred embodiment of the present invention.
  • FIG. 8 is a circuit schematic diagram of still another preferred embodiment of the ultra-wide range high-power converter circuit according to the preferred embodiment of the present invention.
  • the invention relates to an ultra-wide-range high-power converter circuit, comprising a first transformer module, a second transformer module, a first primary input module arranged on the primary side of the first transformer module, and a first primary input module arranged on the first transformer A first secondary output module on the secondary side of the module, a second primary input module on the primary side of the second transformer module, a second secondary output module on the secondary side of the second transformer module, and a module for A high and low voltage mode control module for controlling the first secondary side output module and the second secondary side output module to be connected in series in high voltage mode and in parallel in low voltage mode, and a high and low voltage mode control module for receiving the first secondary side output module and all A load output module that outputs the voltage in series or in parallel of the second secondary side output module;
  • the first secondary side output module includes a first rectifier network, a second rectifier network and a first parameter voltage equalization network
  • the second The secondary output module includes a third rectification network, a fourth rectification network and a second parameter
  • the secondary side and the output end of a transformer module are connected to the third rectifier network through the second parameter balancing network, and the third rectifier network and the fourth rectifier network are also connected to the secondary side of the second transformer module ;
  • the ultra-wide-range high-power converter circuit further comprises a first resonant voltage sharing network and/or a second resonant voltage sharing network, and the first end and the second end of the first resonant voltage sharing network are respectively connected to the first and second resonant voltage sharing networks.
  • the ultra-wide-range high-power converter circuit of the present invention includes a first transformer module 210 , a second transformer module 220 , and a first primary input module 110 disposed on the primary side of the first transformer module 210 .
  • the first secondary side output module 310 arranged on the secondary side of the first transformer module 210
  • the second primary side input module 120 arranged on the primary side of the second transformer module 220
  • the second primary side input module 120 arranged on the second transformer module 220
  • the second secondary side output module 320 of the secondary side, and the high and low voltage mode control for controlling the first secondary side output module 310 and the second secondary side output module 320 to be connected in series in high voltage mode and in parallel in low voltage mode
  • the module 400, and the load output module 500 for receiving the series output voltage or the parallel output voltage of the first secondary side output module 310 and the second secondary side output module 320. Further as shown in FIG.
  • the first secondary side output module 310 includes a first rectification network 311 , a second rectification network 312 , and a first parameter voltage equalization network 313 .
  • the second secondary output module 320 includes a third rectifier network 321 , a fourth rectifier network 322 and a second parameter voltage equalization network 323 .
  • the first secondary output module 310 further includes a first resonant voltage grading network 314 and a second resonant voltage grading network 315 .
  • the input end of the first rectifier network 311 is connected to the secondary side of the first transformer module 210 , and the output end is connected to the fourth rectifier network 322 via the first parameter voltage balancing network 313 , so
  • the input end of the second rectifier network 312 is connected to the secondary side of the first transformer module 210 , and the output end is connected to the third rectifier network 321 through the second parameter voltage equalizing network 323 .
  • the input terminal and the fourth rectifier network 322 are also connected to the secondary side of the second transformer module 220 .
  • the first end and the second end of the first resonant voltage balancing network 314 are respectively connected to the two output ends of the first rectifier network 311 , and the third end is connected to the input end of the second rectifier network 312 .
  • the first end and the second end of the second resonant voltage balancing network 315 are respectively connected to the two output ends of the second rectifier network 312 , and the third end is connected to the input end of the first rectifier network 311 .
  • only the first resonant voltage grading network 314 or only the second voltage grading resonant network 315 may be provided. Of course, it is more preferable to set the first resonant voltage grading network 314 and the second resonant voltage grading network 315 at the same time.
  • the first primary input module 110 , the second primary input module 120 , the first transformer module 210 , the second transformer module 220 , the high and low voltage mode control module 400 and the load output module 500 It can be constructed using any module known in the art.
  • the ultra-wide-range high-power converter circuit may further include a third transformer module, a third primary side input disposed on the primary side of the third transformer module module, a third secondary output module arranged on the secondary side of the third transformer module, and the high and low voltage mode control module 400 is further configured to control the first secondary output module 310 and the second secondary output module 320 and the third secondary output module are connected in series in high voltage mode and in parallel in low voltage mode, and the load output module 500 is configured to receive the first secondary output module 310, the second secondary output module 320 and the third secondary output module 310.
  • the series output voltage or parallel output voltage of the three secondary output modules may further include a third transformer module, a third primary side input disposed on the primary side of the third transformer module module, a third secondary output module arranged on the secondary side of the third transformer module, and the high and low voltage mode control module 400 is further configured to control the first secondary output module 310 and the second secondary output module 320 and the third secondary output module are connected in series in high voltage mode and in parallel in low
  • the third transformer module the third primary input module and the third secondary output module
  • the first transformer module 210 the second transformer module 220 , the first primary input module 110 , and the second primary input module 120 , respectively.
  • the first secondary side output module 310 and the second secondary side output module 320 are constructed.
  • the first rectifier network 311, the second rectifier network 312, the third rectifier network 321, and the fourth rectifier network 322 may include a diode full-bridge rectifier unit, a switch tube full-bridge rectifier unit, a diode half-bridge rectifier unit, and a diode half-bridge rectifier unit. Bridge rectifier unit, and/or switch tube half-bridge rectifier unit.
  • the first resonant voltage balancing network 314 includes a first resonant voltage balancing unit and a second resonant voltage balancing unit
  • the second resonant voltage balancing network 315 includes a third resonant voltage balancing unit and a fourth resonant voltage balancing unit
  • the first parameter voltage balancing network 313 includes a first parameter voltage balancing unit and a second parameter voltage balancing unit
  • the second parameter voltage balancing network 323 includes a third parameter voltage balancing unit and a third parameter voltage balancing unit Four-parameter equalizing unit.
  • the first resonant voltage balancing network 314 and the second resonant voltage balancing network 315 may respectively include only one resonant voltage balancing unit, or may include three or more resonant voltage balancing units. equalizing unit.
  • the first parameter voltage balancing network 313 and the second parameter voltage balancing network 323 may respectively include only one parameter voltage balancing unit, or may include three or more parameter voltage balancing units.
  • Each voltage equalizing unit may include at least one diode series voltage dividing branch and at least one LC resonance branch.
  • the diode series voltage dividing branch includes at least a pair of series diodes, the central connection point of the at least one pair of series diodes is the voltage dividing point, and the two ends of the diode series voltage dividing branch constitute the first part of the voltage equalizing unit. end and second end.
  • the LC resonance branch includes at least one group of resonance inductors and resonance capacitors connected in series, the first end of the LC resonance branch is connected to the voltage dividing point, and the second end forms the third end of the voltage equalizing unit.
  • the positions of the resonant inductance and the resonant capacitor can be exchanged.
  • the ultra-wide-range high-power converter circuit of the present invention includes a first transformer module 210 , a second transformer module 220 , and a first primary input module 110 disposed on the primary side of the first transformer module 210 .
  • the first secondary side output module 310 arranged on the secondary side of the first transformer module 210
  • the second primary side input module 120 arranged on the primary side of the second transformer module 220
  • the second primary side input module 120 arranged on the second transformer module 220
  • the second secondary side output module 320 of the secondary side, and the high and low voltage mode control for controlling the first secondary side output module 310 and the second secondary side output module 320 to be connected in series in high voltage mode and in parallel in low voltage mode
  • the module 400, and the load output module 500 for receiving the series output voltage or the parallel output voltage of the first secondary side output module 310 and the second secondary side output module 320.
  • the first transformer module 210 includes at least a first transformer network 211 and a first transformer network 212 , and the primary sides of the first transformer network 211 and the first transformer network 212 are connected in series.
  • the secondary sides of the first transformer network 211 and the first transformer network 212 are respectively connected to the first secondary side output module 310
  • the second transformer module 220 includes at least a third transformer network 221 and a fourth transformer network 222, so The primary sides of the third transformer network 221 and the fourth transformer network 222 are connected in series, and the secondary sides of the third transformer network 221 and the fourth transformer network 222 are respectively connected to the second secondary side output module 320 .
  • the first transformer network 211 , the second transformer network 212 , the third transformer network 221 and the fourth transformer network 222 respectively include a transformer whose primary inductance can be respectively the same as the original inductance of the transformer.
  • the side windings are connected in parallel, where the primary side inductance can be a separately designed inductance, or it can be integrated in the transformer.
  • the first transformer network 211 may include a transformer Ta1 whose equivalent inductance is Lma1
  • the second transformer network 212 may include a transformer Ta2 whose equivalent inductance is Lma2, which is finally equivalent to an inductance Lm.
  • the inductance Lm can be integrated or equivalent to the separately designed inductances Lma1 and Lma12, or can be the separately designed inductance Lm, all of which are within the protection scope of this patent.
  • the same is true for the third transformer network 221 and the fourth transformer network 222 .
  • the first transformer network 211 , the second transformer network 212 , the third transformer network 221 and the fourth transformer network 222 may further include multiple transformers, respectively.
  • the primary windings of the transformers Ta1 and Ta2 are connected in series
  • the primary windings of the transformers Ta3 and T1a4 are connected in series
  • the secondary windings of the transformers Ta1 and Ta3 are connected in series
  • the secondary windings of the transformers Ta3 and T1a4 are connected in series.
  • other transformer modules can also be constructed similarly.
  • the actual number of transformers in the transformer network, or the number of transformer networks in the transformer module can be adjusted according to actual needs.
  • each transformer network can be connected in series with each other, and can also be connected in parallel with each other.
  • the first secondary output module 310 includes a first rectifier network 311 , a second rectifier network 312 , a first parameter voltage balancing network 313 , a first resonant voltage balancing network 314 and a second resonant voltage balancing network 313 .
  • the second secondary output module 320 includes a third rectifier network 321 , a fourth rectifier network 322 and a second parameter voltage equalization network 323 .
  • the first rectifier network 311 , the second rectifier network 312 , the third rectifier network 321 , and the fourth rectifier network 322 are full-bridge rectifier networks composed of four diodes.
  • the first resonant voltage grading network 314 includes a first resonant voltage grading unit and a second resonant voltage grading unit, and the second resonant voltage grading network 315 includes a third resonant voltage grading unit and a fourth resonant voltage grading unit;
  • the The first parameter voltage equalization network 313 includes a first parameter voltage equalization unit and a second parameter voltage equalization unit, and the second parameter voltage equalization network 323 includes a third parameter voltage equalization unit and a fourth parameter voltage equalization unit.
  • each voltage equalizing unit may include a diode series voltage dividing branch and an LC resonance branch.
  • the diode series voltage dividing branch includes a pair of series diodes, the central connection point of the series diodes is the voltage dividing point, and the two ends of the diode series voltage dividing branch constitute the first end and the second end of the voltage equalizing unit. end.
  • the LC resonance branch includes a resonance inductor and a resonance capacitor connected in series, a first end of the LC resonance branch is connected to the voltage dividing point, and a second end forms a third end of the voltage equalizing unit.
  • the first input terminal of the first rectifier network 311 is connected to the secondary side of the first transformer network 211, that is, the output terminal of the transformer Ta1; the second input terminal is connected to the second transformer
  • the secondary side of the network 212 is the output terminal of the transformer Ta3;
  • the first output terminal is connected to the first terminal of the third rectifier network 321, the first terminal of the first parameter voltage equalizing unit 31 and the second terminal
  • the second output end is connected to the third rectifier network 321
  • the first input terminal of the second rectifier network 312 is connected to the secondary side of the first transformer network 211, that is, the output terminal of the transformer Ta2; the second input terminal is connected to the secondary side of the second transformer network 212, that is, the transformer The output synonymous terminal of Ta4; the first output terminal is connected to the first terminal and the second terminal of the fourth rectifier network 322, the first terminal of the third parameter voltage equalizing unit 33 and the fourth parameter voltage equalizing unit 34, the first end of the third resonant voltage equalizing unit 43 and the first end of the fourth resonant voltage equalizing unit 44; the second output terminal is connected to the fifth end of the fourth rectifier network 322 and the sixth end, the second end of the third parameter equalizing unit 33 and the second end of the fourth parameter equalizing unit 34, the second end of the third resonant equalizing unit 43 and the third The second end of the quad-resonance equalizing unit 44 .
  • the third end of the first parameter voltage balancing unit 31 is connected to the fourth end of the fourth rectifier network 322 ; the third end of the second parameter voltage balancing unit 32 is connected to the third end of the fourth rectifier network 322 terminal; the third terminal of the third parameter voltage equalizing unit 33 is connected to the third terminal of the third rectifier network 321 ; the third terminal of the fourth parameter voltage equalizing unit 34 is connected to the third terminal of the third rectification network 321 fourth end.
  • the third end of the first resonant voltage equalizing unit 41 is connected to the first input end of the second rectifier network 312 ; Two input terminals; the third terminal of the third resonant voltage equalizing unit 43 is connected to the second input terminal of the first rectifier network 311 ; the third terminal of the fourth resonant voltage equalizing unit 44 is connected to the first rectifier The first input of the network 311 .
  • the first resonant voltage equalizing unit 41 , the second resonant voltage equalizing unit 42 , the third resonant voltage equalizing unit 43 , the fourth resonant voltage equalizing unit 44 , the first parameter voltage equalizing unit 31 , and the second parameter equalizing unit 44 are
  • the voltage unit 32 , the third parameter voltage equalization unit 33 and the fourth parameter voltage equalization unit 34 have the same structure, and each voltage equalization unit includes a diode series voltage dividing branch and an LC resonance branch.
  • the diode series voltage dividing branch includes a pair of series diodes, the central connection point of the pair of series diodes is the voltage dividing point, and the two ends of the diode series voltage dividing branch constitute the first end and the voltage equalizing unit. second end.
  • the LC resonance branch includes at least one group of resonance inductors and resonance capacitors connected in series, the first end of the LC resonance branch is connected to the voltage dividing point, and the second end forms the third end of the voltage equalizing unit.
  • the positions of the resonant inductance and the resonant capacitor can be exchanged.
  • only at least one of the first resonant voltage balancing unit 41 , the second resonant voltage balancing unit 42 , the third resonant voltage balancing unit 43 and the fourth resonant voltage balancing unit 44 may be provided , or both, or all three.
  • the applicant unexpectedly found that the specific secondary side caused by the change of the wave control of the LLC resonant converter under light load
  • the bias problem can be solved perfectly.
  • the high and low voltage mode control module 400 includes a first switch K1, a second switch K2 and a third switch K3, and controls the first switch K1, the second switch K2 and the third switch K3.
  • the first switch K1 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400
  • the second switch K2 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400.
  • the second end of the load R0, the third switch K3 is connected between the second end of the high and low voltage mode control module 400 and the first end of the load R0.
  • the first end of the high and low voltage mode control module 400 is connected to one output end of the first and third rectifier networks 311 and 321 respectively, and the second end is connected to one output end of the second and fourth rectifier networks 321 and 322 respectively .
  • the high-low-voltage mode controller 410 controls the logic to turn off the switch K1 and turn on the switches K2 and K3 to achieve constant power output in the low-voltage mode.
  • the switch K1 is closed, and the K2 and K3 are disconnected to achieve constant power output in the high-voltage mode.
  • the first primary input module 110 includes a first switch module and a first LC module; the second primary input module 120 includes a second switch module and a second LC module.
  • the first switch module includes a first switch network 111 and a second switch network 112 , and the first LC module includes a first LC network 113 and a second LC network 114 .
  • the second switch module includes a third switch network 121 and a fourth switch network 122 , and the second LC module includes a third LC network 123 and a fourth LC network 124 .
  • the first switch network 111 and the second switch network 112 , the third switch network 121 and the fourth switch network 122 are the first and second switch transistor full-bridge networks connected in parallel with each other, respectively.
  • Each switch full-bridge network includes four switches.
  • the first LC network 113, the second LC network 114, the third LC network 123, and the fourth LC network 124 respectively comprise a series-connected set of capacitances and inductances. As shown in FIG.
  • the switch tubes Sa1-Sa8 form a first switch network
  • the switch tubes Sb1-Sb8 form a second switch network
  • the first LC network 113 formed by the capacitor Cra1 and the resistor Lra1 is connected to the output end of the first switch network 111 and the The primary side of the first transformer network 211
  • the second LC network formed by the capacitor Cra2 and the resistor Lra2 connects the output end of the second switch network 112 and the primary side of the second transformer network 212
  • the third LC network formed by the capacitor Cra3 and the resistor Lra3 123 is connected to the output terminal of the third switch network 121 and the primary side of the third transformer network 221
  • the fourth LC network 124 formed by the capacitor Cra4 and the resistor Lra4 is connected to the output terminal of the fourth switch network 122 and the primary side of the fourth transformer network 222 .
  • the ultra-wide-range high-power converter circuit of the present invention by setting the parameter equalizing unit, the problem of serious voltage imbalance caused by the difference of device parameters can be solved, and the demand of high voltage and high power can be met;
  • the unit can solve the specific secondary bias problem caused by the change of the wave control of the LLC resonant converter under light load.
  • FIG. 6 is a schematic block diagram of another preferred embodiment of the ultra-wide-range high-power converter circuit according to the preferred embodiment of the present invention.
  • the ultra-wide-range high-power converter circuit of the present invention includes a first transformer module 210 , a second transformer module 220 , and a first primary input module 110 disposed on the primary side of the first transformer module 210 .
  • the first secondary side output module 310 arranged on the secondary side of the first transformer module 210
  • the second primary side input module 120 arranged on the primary side of the second transformer module 220
  • the second primary side input module 120 arranged on the second transformer module 220
  • the second secondary side output module 320 of the secondary side, and the high and low voltage mode control for controlling the first secondary side output module 310 and the second secondary side output module 320 to be connected in series in high voltage mode and in parallel in low voltage mode
  • the module 400, and the load output module 500 for receiving the series output voltage or the parallel output voltage of the first secondary side output module 310 and the second secondary side output module 320.
  • the first primary input module 110 includes a first primary voltage equalization network 115 , a first switch module 11 and a first LC module 13 .
  • the second primary side input module 120 includes a second primary side voltage balancing network 125, a second switch module 12 and a second LC module 14, and the first primary side voltage balancing network 115 is connected to the first input capacitor Cin1 and the first input capacitor Cin1.
  • the second primary-side voltage balancing network 125 is connected between the second input capacitor Cin2 and the first switch module 11
  • the first switch module 11 passes through the first LC module 13
  • the first transformer module 210 is connected, and the second switch module 12 is connected to the second transformer module 220 via the second LC module 14 .
  • the first transformer module 210, the second transformer module 220, the first secondary output module 310, the second secondary output module 320, the high and low voltage mode control module 400 and the load output module 500 can be based on Any modular construction known in the present invention.
  • the above-mentioned modules may also be constructed with reference to any of the embodiments shown in FIGS. 4-5 .
  • the first switch module 11 and the second switch module 12 may be of the same circuit connection structure, which may be a full-bridge topology, or a symmetrical half-bridge or asymmetrical Half-bridge topology.
  • the first LC module 13 and the second LC module 14 may respectively include a set of capacitors and inductors connected in series.
  • the first primary voltage equalization network 115 may include a first primary voltage equalization unit and a second primary voltage equalization unit, and the second primary voltage equalization network includes a third primary voltage equalization unit.
  • Each voltage equalizing unit includes at least one diode series voltage dividing branch and at least one LC resonance branch, the diode series voltage dividing branch includes at least one pair of series diodes, and the central connection point of the at least one pair of series diodes is a split pressure point, the two ends of the diode series voltage dividing branch constitute the first end and the second end of the voltage equalizing unit; the LC resonant branch includes at least one group of series-connected resonant inductors and resonant capacitors, the LC resonant branch The first end of the resonance branch is connected to the voltage dividing point, and the second end forms the third end of the voltage equalizing unit.
  • the first primary voltage equalization network 115 and the second primary voltage equalization network 125 may also include only one voltage equalization unit.
  • the applicant unexpectedly found that the specific original source caused by the change of the LLC resonant converter's wave control under light load
  • the edge bias problem can be solved perfectly.
  • FIG. 7 is a circuit schematic diagram of another preferred embodiment of the ultra-wide-range high-power converter circuit according to the preferred embodiment of the present invention.
  • the ultra-wide-range high-power converter circuit of the present invention includes a first transformer module 210 , a second transformer module 220 , and a first primary side input disposed on the primary side of the first transformer module 210 .
  • the first transformer module 210 includes at least a first transformer network 211 and a first transformer network 212, the first transformer network 211 and the primary side of the first transformer network 212 are connected in series, and the first transformer network 211 and all The secondary sides of the first transformer network 212 are respectively connected to the first secondary output module 310, and the second transformer module 220 includes at least a third transformer network 221 and a fourth transformer network 222.
  • the third transformer network 221 and The primary sides of the fourth transformer network 222 are connected in series, and the secondary sides of the third transformer network 221 and the fourth transformer network 222 are respectively connected to the second secondary side output module 320 .
  • the first transformer network 211 , the second transformer network 212 , the third transformer network 221 and the fourth transformer network 222 respectively include a transformer whose primary inductance can be respectively the same as the original inductance of the transformer.
  • the side windings are connected in parallel, where the primary side inductance can be a separately designed inductance, or it can be integrated in the transformer.
  • the first transformer network 211 may include a transformer Ta1 whose equivalent inductance is Lma1
  • the second transformer network 212 may include a transformer Ta2 whose equivalent inductance is Lma2, which is finally equivalent to an inductance Lm.
  • the inductance Lm can be integrated or equivalent to the separately designed inductances Lma1 and Lma12, or can be the separately designed inductance Lm, all of which are within the protection scope of this patent.
  • the same is true for the third transformer network 221 and the fourth transformer network 222 .
  • the first transformer network 211 , the second transformer network 212 , the third transformer network 221 and the fourth transformer network 222 may further include multiple transformers, respectively.
  • transformer Ta1 and Ta2 are connected in series
  • the primary windings of transformer Ta3 and T1a4 are connected in series
  • the secondary windings of transformer Ta1 and Ta3 are connected in series
  • the secondary windings of transformer Ta3 and T1a4 are connected in series.
  • other transformer modules can also be constructed similarly.
  • the actual number of transformers in the transformer network, or the number of transformer networks in the transformer module can be adjusted according to actual needs.
  • each transformer network can be connected in series with each other, and can also be connected in parallel with each other.
  • the first secondary side output module 310 includes a first rectification network 311 and a second rectification network 312 .
  • the second secondary side output module 320 includes a third rectifier network 321 and a fourth rectifier network 322 .
  • the first input terminal of the first rectifier network 311 is connected to the secondary side of the first transformer network 211, that is, the output terminal of the transformer Ta1; the second input terminal is connected to the secondary side of the second transformer network 212, that is, the transformer The output synonymous terminal of Ta3; the first output terminal is connected to the first terminal of the third rectification network 321; the second output terminal is connected to the fifth terminal and the sixth terminal of the third rectification network 321.
  • the first input terminal of the second rectifier network 312 is connected to the secondary side of the first transformer network 211, that is, the output terminal of the transformer Ta2; the second input terminal is connected to the secondary side of the second transformer network 212, that is, the transformer The output synonymous terminal of Ta4; the first output terminal is connected to the first terminal and the second terminal of the fourth rectifier network 322; the second output terminal is connected to the fifth terminal and the sixth terminal of the fourth rectifier network 322.
  • the high and low voltage mode control module 400 includes a first switch K1, a second switch K2 and a third switch K3, and controls the high and low voltages of the first switch K1, the second switch K2 and the third switch K3.
  • Mode controller 410 The first switch K1 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400, and the second switch K2 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400.
  • the second end of the load R0, the third switch K3 is connected between the second end of the high and low voltage mode control module 400 and the first end of the load R0.
  • the first end of the high and low voltage mode control module 400 is connected to one output end of the first and third rectifier networks 311 and 321 respectively, and the second end is connected to one output end of the second and fourth rectifier networks 321 and 322 respectively .
  • the high-low-voltage mode controller 410 controls the logic to turn off the switch K1 and turn on the switches K2 and K3 to achieve constant power output in the low-voltage mode.
  • the switch K1 is closed, and the K2 and K3 are disconnected to achieve constant power output in the high-voltage mode.
  • the first primary input module 110 includes a first primary voltage equalization network 115 , a first switch network 111 , a second switch network 112 , a first LC network 113 and a second LC network 114 .
  • the second primary input module 120 includes a second primary voltage equalization network 125 , a third switching network 121 , a fourth switching network 122 , a third LC network 123 and a fourth LC network 124 .
  • the first switch network 111 , the second switch network 112 , the third switch network 121 and the fourth switch network 122 are the first and second switch transistor full-bridge networks connected in parallel with each other, respectively. Each switch full-bridge network includes four switches.
  • the first LC network 113, the second LC network 114, the third LC network 123, and the fourth LC network 124 respectively comprise a series-connected set of capacitances and inductances.
  • switch tubes Sa1-Sa8 form a first switch network
  • switch tubes Sb1-Sb8 form a second switch network
  • a first LC network 113 formed by a capacitor Cra1 and a resistor Lra1 is connected to the output end of the first switch network 111 and the
  • the primary side of the first transformer network 211, the second LC network formed by the capacitor Cra2 and the resistor Lra2 connects the output end of the second switch network 112 and the primary side of the second transformer network 212
  • the third LC network formed by the capacitor Cra3 and the resistor Lra3 123 is connected to the output terminal of the third switch network 121 and the primary side of the third transformer network 221, and the fourth LC network 124 formed by the capacitor Cra4 and the resistor Lra
  • the first primary voltage equalization network 115 includes a first primary voltage equalization unit 51 and a second primary voltage equalization unit 52
  • the second primary voltage equalization network 125 includes a third primary voltage The equalizing unit 61 and the fourth primary equalizing unit 62 .
  • the first end of the first input capacitor Cin1 is connected to the first end of the first primary voltage balancing unit 51 , the first end of the second primary voltage balancing unit 52 , and the The first end of the first switch network 111 and the first end of the second switch network 112 .
  • the second end of the first input capacitor Cin is connected to the first end of the second input capacitor Cin2 , the first end of the third primary voltage balancing unit 61 , and the fourth primary voltage balancing unit 62 .
  • the second end of the second input capacitor Cin2 is connected to the second end of the third switch network 121 and the second end of the fourth switch network 122 .
  • the second end of the first primary voltage balancing unit 51 and the second end of the second primary voltage balancing unit 52 are connected to the first end of the second switch network 112 .
  • the third terminal of the first primary voltage equalizing unit 51 is connected to the third terminal of the third switching network 121 and the third transformer network 221 .
  • the third end of the second primary voltage equalizing unit 52 is connected to the third end of the fourth switch network 122 and the fourth transformer network 222 .
  • the third terminal of the third primary voltage equalizing unit 61 is connected to the third terminal of the second switching network 112 and the second transformer network 212 .
  • the third terminal of the fourth primary voltage equalizing unit 62 is connected to the third terminal of the first switching network 111 and the first transformer network 211 .
  • the fourth end of the first switch network 111 is connected to the first transformer network 211 through the first LC network; the fourth end of the second switch network 112 is connected to the second transformer network 211 through the second LC network Transformer network 212; the fourth end of the third switch network 121 is connected to the third transformer network 221 via the third LC network; the fourth end of the fourth switch network 122 is connected to the fourth LC network The fourth transformer network 222.
  • the first primary voltage equalizing unit 51 , the second primary voltage equalizing unit 52 , the third primary voltage equalizing unit 61 and the fourth primary voltage equalizing unit 62 respectively include a diode series voltage dividing branch and an LC resonance branch
  • the diode series voltage dividing branch includes a pair of series diodes, the central connection point of the pair of series diodes is the voltage dividing point, and the two ends of the diode series voltage dividing branch constitute the the first end and the second end of the voltage equalizing unit
  • the LC resonant branch includes at least one group of series-connected resonant inductors and resonant capacitors, and the first end of the LC resonant branch is connected to the voltage dividing point and the second end constitute the third end of the pressure equalizing unit.
  • the high and low voltage mode control module 400 includes a first switch K1, a second switch K2 and a third switch K3, and controls the first switch K1, the second switch K2 and the third switch K3.
  • the first switch K1 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400
  • the second switch K2 is connected between the first terminal and the second terminal of the high and low voltage mode control module 400.
  • the second end of the load R0, the third switch K3 is connected between the second end of the high and low voltage mode control module 400 and the first end of the load R0.
  • the first end of the high and low voltage mode control module 400 is connected to one output end of the first and third rectifier networks 311 and 321 respectively, and the second end is connected to one output end of the second and fourth rectifier networks 321 and 322 respectively .
  • the high-low-voltage mode controller 410 controls the logic to turn off the switch K1 and turn on the switches K2 and K3 to achieve constant power output in the low-voltage mode.
  • the switch K1 is closed, and the K2 and K3 are disconnected to achieve constant power output in the high-voltage mode.
  • the applicant unexpectedly found that the specific original source caused by the change of the LLC resonant converter's wave control under light load
  • the edge bias problem can be solved perfectly.
  • FIG. 8 is a circuit schematic diagram of still another preferred embodiment of the ultra-wide range high-power converter circuit according to the preferred embodiment of the present invention.
  • it also includes a first primary pressure equalizing unit 51 , a second primary pressure equalizing unit 52 , a third primary pressure equalizing unit 61 and a fourth primary pressure equalizing unit 61 , which are arranged on the primary side.
  • the voltage unit 62 and the first resonance voltage equalization unit 41 , the second resonance voltage equalization unit 42 , the third resonance voltage equalization unit 43 and the fourth resonance voltage equalization unit 44 arranged on the secondary side. Therefore, it can simultaneously solve the specific bias problem of the primary side and the secondary side caused by the change of the wave emission control of the LLC resonant converter under light load.
  • those skilled in the art can implement the embodiment shown in FIG. 8 , which is not repeated here.

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Abstract

一种超宽范围大功率变换器电路，包括变压器模块、原边输入模块、第一和第二副边输出模块、高低压模式控制模块，以及负载输出模块。所述第一副边输出模块包括第一整流网络、第二整流网络和第一参数均压网络，所述第二副边输出模块包括第三整流网络、第四整流网络和第二参数均压网络。该电路还包括第一谐振均压网络和/或第二谐振均压网络。通过设置谐振均压网络，可以解决LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题。

Description

超宽范围大功率变换器电路 技术领域
本发明涉及电源模块领域，更具体地说，涉及一种超宽范围大功率变换器电路。
 背景技术
在大功率应用领域，输入为三相交流电网，因为功率因素的要求，前级需要设计三相有源功率因素校正电路。因为三相电网输入，三相有源功率因素校正电路输出母线电压较高，根据目前器件的情况，通常采用电解电容串联的方式，如图1所示。
在充电电源模块两级拓扑的应用中，前级电路的输出BUS+和BUS-作为后级DC/DC变换器的输入。通常，根据需求不同有两种不同的连接方式，如图2A-2B所示。两个方式各有优缺点，图2A把DC输入母线电容中点和PFC输出母线电容中点连接在一起，这样DC 变换器输入母线电容没有均压的问题，但是PFC输出母线电容有较大的均压压力，需要PFC侧进行均压控制。同时DC变换器高频纹波会进入PFC输出母线电容。图2B中，DC输入母线电容中点和PFC输出母线电容中点经过电阻隔开，这样PFC侧不受DC影响，高频纹波不会影响PFC输出母线电容。
为了实现能够同时兼顾高低压、实现宽范围恒功率输出，我司开发了一种宽范围恒功率变换器，其可以用作图2A-2B中的DC/DC变换器，从而可以实现可以覆盖1000V~250V高低压电动汽车的超宽范围恒功率充电，可以给不同电压等级的车进行快充。图3中示出了该宽范围恒功率变换器的结构示意图。在图3所示的拓扑结构中，电路元件例如谐振电容Lr，谐振电容Cr，变压器励磁电感Lm等谐振元件参数的差异，这些谐振元件参数的偏差通常在5%，10%的范围。为了解决拓扑结构中电路参数差异导致的均压问题，在变压器的副边设置了4个均压网络以解决拓扑中电路参数差异导致的均压问题，从而确保原副边电容的均压能力。
在后期应用中我们发现，当将图3所示的宽范围恒功率变换器应用到图2A所示的拓扑结构中时，其能够正常运行。但是，当将图3所示的宽范围恒功率变换器应用到图2B所示的拓扑结构中时，在轻载或者带轻载启机时，可能会面临原边和副边串联电容均压的问题。
经过长期的研究实验，我们发现，鉴于LLC谐振变换器，在常用的PFM 发波控制下，轻载会存在增益不单调的问题，导致输出电压不稳定。因此，轻载情况下，LLC的发波控制需要改变。不同的人，可能采用不同的发波方式，如改为移相发波（移相全桥拓扑的发波方式），PWM发波，间歇发波（Burst）等。轻载不同的发波方式，有各自的优点，能够解决PFM发波的问题，但也可能带来其他的问题。对于PWM发波或间歇发波等情况，会有一段时间不发波。在不发波的情况下，功率管的寄生参数，PCB寄生参数等会参与和谐振电容Cr，谐振电感Lr，以及变压器励磁电感Lm的自由谐振。在特定输入电压，输出电压，轻载不同的负载，及不同的负载形式（如逆变器负载，电子负载的CC档，CV档，CR档等），在特定的动态过程中，发现图3所示的宽范围恒功率变换器并不能保证原副边电容均压。
例如：在输出电压700V，电子负载CC档带载0.1A时，在启机过程中，输出电容出现较大偏压，不能自动调节，触发副边偏压关机。如果只是更换负载形式，换成电子负载的CR档，或者CV档（限流保证同样负载），同样负载同样输出电压则不会偏压关机。同样负载情况，输出电压换到500V，也不会出现偏压关机。或者只是更改负载大小，也不会出现偏压关机。或者带其它更大的负载，启机后调节到0.1A稳态，也不会出现偏压关机。这种的偏压，只会出现在特定情况下轻载，重载则不会发生。原边偏压关机同样类似，这里不详细描述。
 技术问题
通过进一步地研究发现，这种特定情况偏压的原因，不是因为谐振元件参数偏差导致的，而是因为LLC谐振变换器在轻载下发波控制的变化引起的，因此图3所示的宽范围恒功率变换器无法解决这样的均压问题。
 技术解决方案
本发明要解决的技术问题在于，针对上述的特定情况下，LLC谐振变换器在轻载下发波控制的变化引起偏压问题，提供一种能够解决该特殊均压问题的超宽范围大功率变换器电路。
本发明解决其技术问题所采用的技术方案是，构造一种超宽范围大功率变换器电路，包括第一变压器模块、第二变压器模块、设置在所述第一变压器模块原边的第一原边输入模块、设置在所述第一变压器模块副边的第一副边输出模块、设置在所述第二变压器模块原边的第二原边输入模块、设置在所述第二变压器模块副边的第二副边输出模块、以及用于控制所述第一副边输出模块和所述第二副边输出模块在高压模式下串联且在低压模式下并联的高低压模式控制模块，以及用于接收所述第一副边输出模块和所述第二副边输出模块的串联输出电压或者并联输出电压的负载输出模块；所述第一副边输出模块包括第一整流网络、第二整流网络和第一参数均压网络，所述第二副边输出模块包括第三整流网络、第四整流网络和第二参数均压网络，所述第一副边输出模块或所述第二副边输出模块进一步包括第一谐振均压网络，所述第一整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第一参数均压网络连接所述第四整流网络，所述第二整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第二参数均压网络连接所述第三整流网络，所述第三整流网络和所述第四整流网络还连接所述第二变压器模块的副边；所述超宽范围大功率变换器电路进一步包括第一谐振均压网络和/或第二谐振均压网络，所述第一谐振均压网络的第一端和第二端分别连接所述第一整流网络的两个输出端，第三端连接所述第二整流网络的输入端；所述第二谐振均压网络的第一端和第二端分别连接所述第二整流网络的两个输出端，第三端连接所述第一整流网络的输入端；通过设置谐振均压网络，解决在LLC谐振变换器轻载下发波控制的变化引起的特定的副边偏压问题。
在本发明所述的超宽范围大功率变换器电路中，所述超宽范围大功率变换器电路包括第一谐振均压网络和第二谐振均压网络，所述第一谐振均压网络包括第一谐振均压单元和第二谐振均压单元，所述第二谐振均压网络包括第三谐振均压单元和第四谐振均压单元；所述第一参数均压网络包括第一参数均压单元和第二参数均压单元，所述第二参数均压网络包括第三参数均压单元和第四参数均压单元。
在本发明所述的超宽范围大功率变换器电路中，所述第一变压器模块包括至少第一变压器网络和第二变压器网络，所述第一变压器网络和所述第二变压器网络的原边串联，所述第一变压器网络和所述第二变压器网络的副边分别连接所述第一副边输出模块，所述第二变压器模块包括至少第三变压器网络和第四变压器网络，所述第三变压器网络和所述第四变压器网络的原边串联，所述第三变压器网络和所述第四变压器网络的副边分别连接所述第二副边输出模块。
在本发明所述的超宽范围大功率变换器电路中，所述第一整流网络的第一输入端连接所述第一变压器网络的副边，第二输入端连接所述第二变压器网络的副边，第一输出端连接所述第三整流网络的第一端、所述第一参数均压单元的第一端和所述第二参数均压单元的第一端，所述第一谐振均压单元的第一端和所述第二谐振均压单元的第一端，第二输出端连接所述第三整流网络的第五端和第六端、所述第一参数均压单元的第二端和所述第二参数均压单元的第二端，所述第一谐振均压单元的第二端和所述第二谐振均压单元的第二端；所述第二整流网络的第一输入端连接所述第一变压器网络的副边，第二输入端连接所述第二变压器网络的副边，第一输出端连接所述第四整流网络的第一端和第二端、所述第三参数均压单元的第一端和所述第四参数均压单元的第一端，所述第三谐振均压单元的第一端和所述第四谐振均压单元的第一端，第二输出端连接所述第四整流网络的第五端和第六端、所述第三参数均压单元的第二端和所述第四参数均压单元的第二端，所述第三谐振均压单元的第二端和所述第四谐振均压单元的第二端；所述第一参数均压单元的第三端连接所述第四整流网络的第四端；所述第二参数均压单元的第三端连接所述第四整流网络的第三端；所述第三参数均压单元的第三端连接所述第三整流网络的第三端；所述第四参数均压单元的第三端连接所述第三整流网络的第四端；所述第一谐振均压单元的第三端连接所述第二整流网络的第一输入端；所述第二谐振均压单元的第三端连接所述第二整流网络的第二输入端；所述第三谐振均压单元的第三端连接所述第一整流网络的第二输入端；所述第四谐振均压单元的第三端连接所述第一整流网络的第一输入端。
在本发明所述的超宽范围大功率变换器电路中，所述第一原边输入模块包括第一原边均压网络、第一开关模块和第一LC模块，所述第二原边输入模块包括第二原边均压网络、第二开关模块和第二LC模块，所述第一原边均压网络连接在第一输入电容和第二开关模块之间，所述第二原边均压网络连接在第二输入电容和所述第一开关模块之间，所述第一开关模块经所述第一LC模块连接所述第一变压器模块，所述第二开关模块经所述第二LC模块连接所述第二变压器模块。
在本发明所述的超宽范围大功率变换器电路中，所述第一原边均压网络包括第一原边均压单元和第二原边均压单元，所述第一开关模块包括第一开关网络和第二开关网络，所述第一LC模块包括第一LC网络和第二LC网络，所述第二原边均压网络包括第三原边均压单元和第四原边均压单元，所述第二开关模块包括第三开关网络和第四开关网络，所述第二LC模块包括第三LC网络和第四LC网络。
在本发明所述的超宽范围大功率变换器电路中，所述第一输入电容的第一端连接所述第一原边均压单元的第一端、所述第二原边均压单元的第一端、所述第一开关网络的第一端和所述第二开关网络的第一端；所述第一输入电容的第二端连接所述第二输入电容的第一端、所述第三原边均压单元的第一端、所述第四原边均压单元的第一端、所述第二开关网络的第二端、所述第三开关网络的第一端、所述第四开关网络的第一端和所述第一开关网络的第二端；所述第二输入端电容的第二端连接所述第三开关网络的第二端和所述第四开关网络的第二端；所述第一原边均压单元的第二端、所述第二原边均压单元的第二端连接所述第二开关网络的第一端；所述第一原边均压单元的第三端连接所述第三开关网络的第三端和所述第三变压器网络；所述第二原边均压单元的第三端连接所述第四开关网络的第三端和所述第四变压器网络；所述第三原边均压单元的第三端连接所述第二开关网络的第三端和所述第二变压器网络；所述第四原边均压单元的第三端连接所述第一开关网络的第三端和所述第一变压器网络；所述第一开关网络的第四端经所述第一LC网络连接所述第一变压器网络；所述第二开关网络的第四端经所述第二LC网络连接所述第二变压器网络；所述第三开关网络的第四端经所述第三LC网络连接所述第三变压器网络；所述第四开关网络的第四端经所述第四LC网络连接所述第四变压器网络。
在本发明所述的超宽范围大功率变换器电路中，每个均压单元包括至少一个二极管串联分压支路和至少一个LC谐振支路，所述二极管串联分压支路包括至少一对串联二极管，所述至少一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成所述均压单元的第一端和第二端；所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。
在本发明所述的超宽范围大功率变换器电路中，所述高低压模式控制模块包括第一切换开关、第二切换开关和第三切换开关，所述第一切换开关连接在所述高低压模式控制模块的第一端和第二端之间，所述第二切换开关连接在所述高低压模式控制模块的第一端和所述负载输出模块的第二端之间，所述第三切换开关连接在所述高低压模式控制模块的第二端和所述负载输出模块的第一端之间。
在本发明所述的超宽范围大功率变换器电路中，所述第一变压器网络、所述第二变压器网络分别包括一个变压器或者一个以上彼此串联的变压器。
 有益效果
实施本发明的所述的超宽范围大功率变换器电路，令人惊讶地发现，通过设置谐振均压网络，在LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题可以完美地解决。
 附图说明
下面将结合附图及实施例对本发明作进一步说明，附图中：
图1是现有技术的充电电源模块的三相有源功率因素校正电路的连接示意图；
图2A是现有技术的第一方式的充电电源模块两级拓扑的电路示意图；
图2B是现有技术的第二方式的充电电源模块两级拓扑的电路示意图；
图3是背景技术中提及的宽范围恒功率变换器的电路拓扑图；
图4是根据本发明的优选实施例的超宽范围大功率变换器电路的原理框图；
图5是根据本发明的优选实施例的超宽范围大功率变换器电路的优选实施例的电路原理图；
图6是根据本发明的优选实施例的超宽范围大功率变换器电路的又一优选实施例的原理框图；
图7是根据本发明的优选实施例的超宽范围大功率变换器电路的又一优选实施例的电路原理图；
图8是根据本发明的优选实施例的超宽范围大功率变换器电路的再一优选实施例的电路原理图。
 本发明的最佳实施方式
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图及实施例，对本发明进行进一步详细说明。应当理解，此处所描述的具体实施例仅仅用以解释本发明，并不用于限定本发明。
本发明涉及一种超宽范围大功率变换器电路，包括第一变压器模块、第二变压器模块、设置在所述第一变压器模块原边的第一原边输入模块、设置在所述第一变压器模块副边的第一副边输出模块、设置在所述第二变压器模块原边的第二原边输入模块、设置在所述第二变压器模块副边的第二副边输出模块、以及用于控制所述第一副边输出模块和所述第二副边输出模块在高压模式下串联且在低压模式下并联的高低压模式控制模块，以及用于接收所述第一副边输出模块和所述第二副边输出模块的串联输出电压或者并联输出电压的负载输出模块；所述第一副边输出模块包括第一整流网络、第二整流网络和第一参数均压网络，所述第二副边输出模块包括第三整流网络、第四整流网络和第二参数均压网络，所述第一副边输出模块或所述第二副边输出模块进一步包括第一谐振均压网络，所述第一整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第一参数均压网络连接所述第四整流网络，所述第二整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第二参数均压网络连接所述第三整流网络，所述第三整流网络和所述第四整流网络还连接所述第二变压器模块的副边；所述超宽范围大功率变换器电路进一步包括第一谐振均压网络和/或第二谐振均压网络，所述第一谐振均压网络的第一端和第二端分别连接所述第一整流网络的两个输出端，第三端连接所述第二整流网络的输入端；所述第二谐振均压网络的第一端和第二端分别连接所述第二整流网络的两个输出端，第三端连接所述第一整流网络的输入端。在本发明中，令人惊讶地发现，通过设置谐振均压网络，在LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题可以完美地解决。
图4是根据本发明的优选实施例的超宽范围大功率变换器电路的原理框图。如图4所示，本发明的超宽范围大功率变换器电路，包括第一变压器模块210、第二变压器模块220、设置在所述第一变压器模块210原边的第一原边输入模块110、设置在所述第一变压器模块210副边的第一副边输出模块310、设置在所述第二变压器模块220原边的第二原边输入模块120、设置在所述第二变压器模块220副边的第二副边输出模块320、以及用于控制所述第一副边输出模块310和所述第二副边输出模块320在高压模式下串联且在低压模式下并联的高低压模式控制模块400，以及用于接收所述第一副边输出模块310和所述第二副边输出模块320的串联输出电压或者并联输出电压的负载输出模块500。进一步如图4所示，所述第一副边输出模块310包括第一整流网络311、第二整流网络312、第一参数均压网络313。所述第二副边输出模块320包括第三整流网络321、第四整流网络322和第二参数均压网络323。进一步地，在图4所示实施例中，所述第一副边输出模块310进一步包括第一谐振均压网络314和第二谐振均压网络315。
在本实施例中，所述第一整流网络311的输入端连接所述第一变压器模块210的副边、输出端经所述第一参数均压网络313连接所述第四整流网络322，所述第二整流网络312的输入端连接所述第一变压器模块210的副边、输出端经所述第二参数均压网络323连接所述第三整流网络321，所述第三整流网络321的输入端和所述第四整流网络322还连接所述第二变压器模块220的副边。所述第一谐振均压网络314的第一端和第二端分别连接所述第一整流网络311的两个输出端，第三端连接所述第二整流网络312的输入端。所述第二谐振均压网络315的第一端和第二端分别连接所述第二整流网络312的两个输出端，第三端连接所述第一整流网络311的输入端。在本发明的简化优选实施例中，可以只设置所述第一谐振均压网络314或只设置所述第二均压谐振网络315。当然更加优选的是，同时设置第一谐振均压网络314和第二谐振均压网络315。
在本发明的优选实施例中，第一原边输入模块110、第二原边输入模块120、所述第一变压器模块210、第二变压器模块220、高低压模式控制模块400和负载输出模块500可以采用本领域已知的任何模块构建。
进一步地，在本发明的进一步的优选实施例中，所述的超宽范围大功率变换器电路还可以进一步包括第三变压器模块、设置在所述第三变压器模块原边的第三原边输入模块、设置在所述第三变压器模块副边的第三副边输出模块，所述高低压模式控制模块400进一步用于控制所述第一副边输出模块310、所述第二副边输出模块320和第三副边输出模块在高压模式下串联且在低压模式下并联，所述负载输出模块500用于接收所述第一副边输出模块310、所述第二副边输出模块320和第三副边输出模块的串联输出电压或者并联输出电压。所述第三变压器模块、第三原边输入模块和第三副边输出模块可以分别参考第一变压器模块210、第二变压器模块220、第一原边输入模块110、第二原边输入模块120、第一副边输出模块310和第二副边输出模块320构建。在本发明的一个优选实施例中，第一整流网络311、第二整流网络312、第三整流网络321、第四整流网络322可以包括二极管全桥整流单元、开关管全桥整流单元、二极管半桥整流单元、和/或开关管半桥整流单元。
在本发明的一个优选实施例中，所述第一谐振均压网络314包括第一谐振均压单元和第二谐振均压单元，所述第二谐振均压网络315包括第三谐振均压单元和第四谐振均压单元；所述第一参数均压网络313包括第一参数均压单元和第二参数均压单元，所述第二参数均压网络323包括第三参数均压单元和第四参数均压单元。当然，在本发明的其他优选实施中，所述第一谐振均压网络314和所述第二谐振均压网络315可以分别只包括一个谐振均压单元，也可以包括三个或者更多个谐振均压单元。同理，所述第一参数均压网络313和第二参数均压网络323也可以分别只包括一个参数均压单元，也可以包括三个或者更多个参数均压单元。
上述第一谐振均压单元、第二谐振均压单元、第三谐振均压单元、第四谐振均压单元、第一参数均压单元、第二参数均压单元、第三参数均压单元和第四参数均压单元的构造可以相同。每个均压单元可以包括至少一个二极管串联分压支路和至少一个LC谐振支路。所述二极管串联分压支路包括至少一对串联二极管，所述至少一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成该均压单元的第一端和第二端。所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。在本发明的优选实施例中，所述谐振电感和谐振电容的位置可以交换。
在本发明中，令人惊讶地发现，通过设置谐振均压网络，在LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题可以完美地解决。
图5是根据本发明的优选实施例的超宽范围大功率变换器电路的优选实施例的电路原理图。如图5所示，本发明的超宽范围大功率变换器电路，包括第一变压器模块210、第二变压器模块220、设置在所述第一变压器模块210原边的第一原边输入模块110、设置在所述第一变压器模块210副边的第一副边输出模块310、设置在所述第二变压器模块220原边的第二原边输入模块120、设置在所述第二变压器模块220副边的第二副边输出模块320、以及用于控制所述第一副边输出模块310和所述第二副边输出模块320在高压模式下串联且在低压模式下并联的高低压模式控制模块400，以及用于接收所述第一副边输出模块310和所述第二副边输出模块320的串联输出电压或者并联输出电压的负载输出模块500。
进一步如图5所示，所述第一变压器模块210包括至少第一变压器网络211和第一变压器网络212，所述第一变压器网络211和所述第一变压器网络212的原边串联，所述第一变压器网络211和所述第一变压器网络212的副边分别连接所述第一副边输出模块310，所述第二变压器模块220包括至少第三变压器网络221和第四变压器网络222，所述第三变压器网络221和所述第四变压器网络222的原边串联，所述第三变压器网络221和所述第四变压器网络222的副边分别连接所述第二副边输出模块320。
在本发明的一个优选实施例中，所述第一变压器网络211、第二变压器网络212、第三变压器网络221和第四变压器网络222分别包括一个变压器，其原边电感可分别与变压器的原边绕组并联，这里原边电感可以是单独设计的电感，也可以集成设计在变压器里。例如，所述第一变压器网络211可以包括变压器Ta1，其等效电感为Lma1，第二变压器网络212包括变压器Ta2，其等效电感为Lma2，最终等效为电感Lm。电感Lm可以集成或者单独设计的电感Lma1、Lma12的等效，也可是单独设计的电感Lm，均在本专利保护范围内。对于第三变压器网络221和第四变压器网络222，也是同样的。当然，所述第一变压器网络211、第二变压器网络212、第三变压器网络221和第四变压器网络222还可以分别包括多个变压器。
如图5所示，变压器Ta1和Ta2原边绕组串联，变压器Ta3和T1a4原边绕组串联，变压器Ta1和Ta3副边串联，变压器Ta3和T1a4副边绕组串联。同理，其余变压器模块也可以类似构造。当然，在本发明的其他优选实施例中，可以根据实际需要调整变压器网络中变压器的实际数量，或者变压器模块中变压器网络的数量。在本发明的进一步的优选实施例中，各个变压器网络之间可以彼此串联，也可以彼此并联。
进一步如图5所示，所述第一副边输出模块310包括第一整流网络311、第二整流网络312、第一参数均压网络313、第一谐振均压网络314和第二谐振均压网络315。所述第二副边输出模块320包括第三整流网络321、第四整流网络322和第二参数均压网络323。
在本实施例中，所述第一整流网络311、第二整流网络312和第三整流网络321、第四整流网络322为四个二极管构成的全桥整流网络。所述第一谐振均压网络314包括第一谐振均压单元和第二谐振均压单元，所述第二谐振均压网络315包括第三谐振均压单元和第四谐振均压单元；所述第一参数均压网络313包括第一参数均压单元和第二参数均压单元，所述第二参数均压网络323包括第三参数均压单元和第四参数均压单元。在本实施例中，每个均压单元可以包括二极管串联分压支路和LC谐振支路。所述二极管串联分压支路包括一对串联二极管，所述串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成该均压单元的第一端和第二端。所述LC谐振支路包括串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。
因此，如图5所示，所述第一整流网络311的第一输入端连接所述第一变压器网络211的副边，即变压器Ta1的输出同名端；第二输入端连接所述第二变压器网络212的副边，即变压器Ta3的输出异名端；第一输出端连接所述第三整流网络321的第一端、所述第一参数均压单元31的第一端和所述第二参数均压单元32的第一端，所述第一谐振均压单元41的第一端和所述第二谐振均压单元42的第一端；第二输出端连接所述第三整流网络321的第五端和第六端、所述第一参数均压单元31的第二端、所述第二参数均压单元32的第二端，所述第一谐振均压单元41的第二端和所述第二谐振均压单元42的第二端。所述第二整流网络312的第一输入端连接所述第一变压器网络211的副边，即变压器Ta2的输出同名端；第二输入端连接所述第二变压器网络212的副边，即变压器Ta4的输出异名端；第一输出端连接所述第四整流网络322的第一端和第二端、所述第三参数均压单元33的第一端和所述第四参数均压单元34的第一端，所述第三谐振均压单元43的第一端和所述第四谐振均压单元44的第一端；第二输出端连接所述第四整流网络322的第五端和第六端、所述第三参数均压单元33的第二端和所述第四参数均压单元34的第二端，所述第三谐振均压单元43的第二端和所述第四谐振均压单元44的第二端。所述第一参数均压单元31的第三端连接所述第四整流网络322的第四端；所述第二参数均压单元32的第三端连接所述第四整流网络322的第三端；所述第三参数均压单元33的第三端连接所述第三整流网络321的第三端；所述第四参数均压单元34的第三端连接所述第三整流网络321的第四端。所述第一谐振均压单元41的第三端连接所述第二整流网络312的第一输入端；所述第二谐振均压单元42的第三端连接所述第二整流网络312的第二输入端；所述第三谐振均压单元43的第三端连接所述第一整流网络311的第二输入端；所述第四谐振均压单元44的第三端连接所述第一整流网络311的第一输入端。
如图5所示，第一谐振均压单元41、第二谐振均压单元42、第三谐振均压单元43、第四谐振均压单元44、第一参数均压单元31、第二参数均压单元32、第三参数均压单元33和第四参数均压单元34的构造相同，每个均压单元包括一个二极管串联分压支路和一个LC谐振支路。所述二极管串联分压支路包括一对串联二极管，所述一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成该均压单元的第一端和第二端。所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。在本发明的优选实施例中，所述谐振电感和谐振电容的位置可以交换。在本发明的进一步的优选实施例中，可以仅仅设置第一谐振均压单元41、第二谐振均压单元42、第三谐振均压单元43和第四谐振均压单元44中的至少一者，或者两者，或者三者。
在本发明中，通过在整流网络的输入端和输出端之间交叉设置谐振均压单元，申请人意外地发现，在LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题可以完美地解决。
在本实施例中，所述高低压模式控制模块400包括第一切换开关K1、第二切换开关K2和第三切换开关K3，以及控制该第一切换开关K1、第二切换开关K2和第三切换开关K3的高低压模式控制器410。所述第一切换开关K1连接在所述高低压模式控制模块400的第一端和第二端之间，所述第二切换开关K2连接在所述高低压模式控制模块400的第一端和负载R0的第二端，所述第三切换开关K3连接在所述高低压模式控制模块400的第二端和所述负载R0的第一端之间。同时，所述高低压模式控制模块400的第一端分别连接第一和第三整流网络311和321的一个输出端，第二端分别连接第二和第四整流网络321和322的一个输出端。这样，给低压的电动汽车充电时，选择低压模式，通过高低压模式控制器410控制逻辑，让切换开关K1断开，切换开关K2，K3闭合，实现低压模式恒功率输出。当给高压档的电动汽车充电时，选择高压模式，通过控制逻辑，让切换开关K1闭合，K2，K3断开，实现高压模式恒功率输出。
进一步如图5所示，所述第一原边输入模块110包括第一开关模块和第一LC模块；所述第二原边输入模块120包括第二开关模块和第二LC模块。所述第一开关模块包括第一开关网络111和第二开关网络112，所述第一LC模块包括第一LC网络113和第二LC网络114。所述第二开关模块包括第三开关网络121和第四开关网络122，所述第二LC模块包括第三LC网络123和第四LC网络124。
在本发明的一个优选实施例中，第一开关网络111和第二开关网络112，第三开关网络121和第四开关网络122分别为相互并联的第一和第二开关管全桥网络。每个开关管全桥网络包括四个开关管。第一LC网络113、第二LC网络114、第三LC网络123和第四LC网络124分别包括串联的一组电容和电感。如图5所示，开关管Sa1-Sa8构成第一开关网络，开关管Sb1-Sb8构成第二开关网络，电容Cra1和电阻Lra1构成的第一LC网络113连接第一开关网络111的输出端和第一变压器网络211的原边，电容Cra2和电阻Lra2构成的第二LC网络连接第二开关网络112的输出端和第二变压器网络212的原边，电容Cra3和电阻Lra3构成的第三LC网络123连接第三开关网络121的输出端和第三变压器网络221的原边，电容Cra4和电阻Lra4构成的第四LC网络124连接第四开关网络122的输出端和第四变压器网络222的原边。
实施本发明的所述的超宽范围大功率变换器电路，通过设置参数均压单元，可以解决器件参数差异导致的电压严重不均衡问题，可以满足高压大功率的需求；而同时通过谐振均压单元，可以解决在LLC谐振变换器在轻载下发波控制的变化引起的特定的副边偏压问题。
图6是根据本发明的优选实施例的超宽范围大功率变换器电路的又一优选实施例的原理框图。如图6所示，本发明的超宽范围大功率变换器电路，包括第一变压器模块210、第二变压器模块220、设置在所述第一变压器模块210原边的第一原边输入模块110、设置在所述第一变压器模块210副边的第一副边输出模块310、设置在所述第二变压器模块220原边的第二原边输入模块120、设置在所述第二变压器模块220副边的第二副边输出模块320、以及用于控制所述第一副边输出模块310和所述第二副边输出模块320在高压模式下串联且在低压模式下并联的高低压模式控制模块400，以及用于接收所述第一副边输出模块310和所述第二副边输出模块320的串联输出电压或者并联输出电压的负载输出模块500。
进一步如图6所示，所述第一原边输入模块110包括第一原边均压网络115、第一开关模块11和第一LC模块13。所述第二原边输入模块120包括第二原边均压网络125、第二开关模块12和第二LC模块14，所述第一原边均压网络115连接在第一输入电容Cin1和第二开关模块12之间，所述第二原边均压网络125连接在第二输入电容Cin2和所述第一开关模块11之间，所述第一开关模块11经所述第一LC模块13连接所述第一变压器模块210，所述第二开关模块12经所述第二LC模块14连接所述第二变压器模块220。
在本发明中，所述第一变压器模块210、第二变压器模块220、第一副边输出模块310、第二副边输出模块320、高低压模式控制模块400和所述负载输出模块500可以根据本发明中已知的任何模块构建。又例如，上述各个模块也可以参照图4-5中所示的任意实施例构建。
在本发明的一个优选实施例中，所述第一开关模块11和所述第二开关模块12可以是是相同电路连接的结构，其可以是全桥拓扑，也可以是对称半桥或不对称半桥拓扑。所述第一LC模块13和第二LC模块14可以分别包括串联的一组电容和电感。
在本发明的优选实施例中，所述第一原边均压网络115可以包括第一原边均压单元和第二原边均压单元，所述第二原边均压网络包括第三原边均压单元和第四原边均压单元。每个均压单元包括至少一个二极管串联分压支路和至少一个LC谐振支路，所述二极管串联分压支路包括至少一对串联二极管，所述至少一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成所述均压单元的第一端和第二端；所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。在本发明的其他优选实施例中，所述第一原边均压网络115和所述第二原边均压网络125也可以只包括一个均压单元。
在本发明中，通过在变压器的原边的开关模块和输入电容之间交叉设置均压网络，申请人意外地发现，在LLC谐振变换器在轻载下发波控制的变化引起的特定的原边偏压问题可以完美地解决。
图7是根据本发明的优选实施例的超宽范围大功率变换器电路的又一优选实施例的电路原理图。结合图6-7所示，本发明的超宽范围大功率变换器电路，包括第一变压器模块210、第二变压器模块220、设置在所述第一变压器模块210原边的第一原边输入模块110、设置在所述第一变压器模块210副边的第一副边输出模块310、设置在所述第二变压器模块220原边的第二原边输入模块120、设置在所述第二变压器模块220副边的第二副边输出模块320、以及用于控制所述第一副边输出模块310和所述第二副边输出模块320在高压模式下串联且在低压模式下并联的高低压模式控制模块400，以及用于接收所述第一副边输出模块310和所述第二副边输出模块320的串联输出电压或者并联输出电压的负载输出模块500。
所述第一变压器模块210包括至少第一变压器网络211和第一变压器网络212，所述第一变压器网络211和所述第一变压器网络212的原边串联，所述第一变压器网络211和所述第一变压器网络212的副边分别连接所述第一副边输出模块310，所述第二变压器模块220包括至少第三变压器网络221和第四变压器网络222，所述第三变压器网络221和所述第四变压器网络222的原边串联，所述第三变压器网络221和所述第四变压器网络222的副边分别连接所述第二副边输出模块320。
在本发明的一个优选实施例中，所述第一变压器网络211、第二变压器网络212、第三变压器网络221和第四变压器网络222分别包括一个变压器，其原边电感可分别与变压器的原边绕组并联，这里原边电感可以是单独设计的电感，也可以集成设计在变压器里。例如，所述第一变压器网络211可以包括变压器Ta1，其等效电感为Lma1，第二变压器网络212包括变压器Ta2，其等效电感为Lma2，最终等效为电感Lm。电感Lm可以集成或者单独设计的电感Lma1、Lma12的等效，也可是单独设计的电感Lm，均在本专利保护范围内。对于第三变压器网络221和第四变压器网络222，也是同样的。当然，所述第一变压器网络211、第二变压器网络212、第三变压器网络221和第四变压器网络222还可以分别包括多个变压器。
如图7所示，变压器Ta1和Ta2原边绕组串联，变压器Ta3和T1a4原边绕组串联，变压器Ta1和Ta3副边串联，变压器Ta3和T1a4副边绕组串联。同理，其余变压器模块也可以类似构造。当然，在本发明的其他优选实施例中，可以根据实际需要调整变压器网络中变压器的实际数量，或者变压器模块中变压器网络的数量。在本发明的进一步的优选实施例中，各个变压器网络之间可以彼此串联，也可以彼此并联。
进一步如图7所示，所述第一副边输出模块310包括第一整流网络311、第二整流网络312。所述第二副边输出模块320包括第三整流网络321、第四整流网络322。所述第一整流网络311的第一输入端连接所述第一变压器网络211的副边，即变压器Ta1的输出同名端；第二输入端连接所述第二变压器网络212的副边，即变压器Ta3的输出异名端；第一输出端连接所述第三整流网络321的第一端；第二输出端连接所述第三整流网络321的第五端和第六端。所述第二整流网络312的第一输入端连接所述第一变压器网络211的副边，即变压器Ta2的输出同名端；第二输入端连接所述第二变压器网络212的副边，即变压器Ta4的输出异名端；第一输出端连接所述第四整流网络322的第一端和第二端；第二输出端连接所述第四整流网络322的第五端和第六端。
所述高低压模式控制模块400包括第一切换开关K1、第二切换开关K2和第三切换开关K3，以及控制该第一切换开关K1、第二切换开关K2和第三切换开关K3的高低压模式控制器410。所述第一切换开关K1连接在所述高低压模式控制模块400的第一端和第二端之间，所述第二切换开关K2连接在所述高低压模式控制模块400的第一端和负载R0的第二端，所述第三切换开关K3连接在所述高低压模式控制模块400的第二端和所述负载R0的第一端之间。同时，所述高低压模式控制模块400的第一端分别连接第一和第三整流网络311和321的一个输出端，第二端分别连接第二和第四整流网络321和322的一个输出端。这样，给低压的电动汽车充电时，选择低压模式，通过高低压模式控制器410控制逻辑，让切换开关K1断开，切换开关K2，K3闭合，实现低压模式恒功率输出。当给高压档的电动汽车充电时，选择高压模式，通过控制逻辑，让切换开关K1闭合，K2，K3断开，实现高压模式恒功率输出。
进一步如图7所示，所述第一原边输入模块110包括第一原边均压网络115、第一开关网络111、第二开关网络112、第一LC网络113和第二LC网络114。所述第二原边输入模块120包括第二原边均压网络125、第三开关网络121、第四开关网络122，第三LC网络123和第四LC网络124。如图7所示，第一开关网络111和第二开关网络112，第三开关网络121和第四开关网络122分别为相互并联的第一和第二开关管全桥网络。每个开关管全桥网络包括四个开关管。第一LC网络113、第二LC网络114、第三LC网络123和第四LC网络124分别包括串联的一组电容和电感。如图7所示，开关管Sa1-Sa8构成第一开关网络，开关管Sb1-Sb8构成第二开关网络，电容Cra1和电阻Lra1构成的第一LC网络113连接第一开关网络111的输出端和第一变压器网络211的原边，电容Cra2和电阻Lra2构成的第二LC网络连接第二开关网络112的输出端和第二变压器网络212的原边，电容Cra3和电阻Lra3构成的第三LC网络123连接第三开关网络121的输出端和第三变压器网络221的原边，电容Cra4和电阻Lra4构成的第四LC网络124连接第四开关网络122的输出端和第四变压器网络222的原边。
如图7所示，所述第一原边均压网络115包括第一原边均压单元51和第二原边均压单元52，所述第二原边均压网络125包括第三原边均压单元61和第四原边均压单元62。如图7所示，所述第一输入电容Cin1的第一端连接所述第一原边均压单元51的第一端、所述第二原边均压单元52的第一端、所述第一开关网络111的第一端和所述第二开关网络112的第一端。所述第一输入电容Cin的第二端连接所述第二输入电容Cin2的第一端、所述第三原边均压单元61的第一端、所述第四原边均压单元62的第一端、所述第二开关网络112的第二端、所述第三开关网络121的第一端、所述第四开关网络122的第一端和所述第一开关网络111的第二端。所述第二输入端电容Cin2的第二端连接所述第三开关网络121的第二端和所述第四开关网络122的第二端。所述第一原边均压单元51的第二端、所述第二原边均压单元52的第二端连接所述第二开关网络112的第一端。所述第一原边均压单元51的第三端连接所述第三开关网络121的第三端和所述第三变压器网络221。所述第二原边均压单元52的第三端连接所述第四开关网络122的第三端和所述第四变压器网络222。所述第三原边均压单元61的第三端连接所述第二开关网络112的第三端和所述第二变压器网络212。所述第四原边均压单元62的第三端连接所述第一开关网络111的第三端和所述第一变压器网络211。所述第一开关网络111的第四端经所述第一LC网络连接所述第一变压器网络211；所述第二开关网络112的第四端经所述第二LC网络连接所述第二变压器网络212；所述第三开关网络121的第四端经所述第三LC网络连接所述第三变压器网络221；所述第四开关网络122的第四端经所述第四LC网络连接所述第四变压器网络222。
如图7所示，第一原边均压单元51、第二原边均压单元52、第三原边均压单元61和第四原边均压单元62分别包括一个二极管串联分压支路和一个LC谐振支路，所述二极管串联分压支路包括一对串联二极管，所述一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成所述均压单元的第一端和第二端；所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。
在本实施例中，所述高低压模式控制模块400包括第一切换开关K1、第二切换开关K2和第三切换开关K3，以及控制该第一切换开关K1、第二切换开关K2和第三切换开关K3的高低压模式控制器410。所述第一切换开关K1连接在所述高低压模式控制模块400的第一端和第二端之间，所述第二切换开关K2连接在所述高低压模式控制模块400的第一端和负载R0的第二端，所述第三切换开关K3连接在所述高低压模式控制模块400的第二端和所述负载R0的第一端之间。同时，所述高低压模式控制模块400的第一端分别连接第一和第三整流网络311和321的一个输出端，第二端分别连接第二和第四整流网络321和322的一个输出端。这样，给低压的电动汽车充电时，选择低压模式，通过高低压模式控制器410控制逻辑，让切换开关K1断开，切换开关K2，K3闭合，实现低压模式恒功率输出。当给高压档的电动汽车充电时，选择高压模式，通过控制逻辑，让切换开关K1闭合，K2，K3断开，实现高压模式恒功率输出。
在本发明中，通过在变压器的原边的开关模块和输入电容之间交叉设置均压网络，申请人意外地发现，在LLC谐振变换器在轻载下发波控制的变化引起的特定的原边偏压问题可以完美地解决。
图8是根据本发明的优选实施例的超宽范围大功率变换器电路的再一优选实施例的电路原理图。在图8所示的优选实施例中，其同时包括设置在原边的第一原边均压单元51、第二原边均压单元52、第三原边均压单元61和第四原边均压单元62以及设置在副边的第一谐振均压单元41、第二谐振均压单元42、第三谐振均压单元43和第四谐振均压单元44。因此，其可以同时解决在LLC谐振变换器在轻载下发波控制的变化引起的特定的原边和副边的偏压问题。基于本发明的教导，本领域技术人员能够实现图8所示的实施例，在此就不再累述了。
虽然本发明是通过具体实施例进行说明的，本领域技术人员应当明白，在不脱离本发明范围的情况下，还可以对本发明进行各种变换及等同替代。另外，针对特定情形或材料，可以对本发明做各种修改，而不脱离本发明的范围。因此，本发明不局限于所公开的具体实施例，而应当包括落入本发明权利要求范围内的全部实施方式。
以上所述仅为本发明的较佳实施例而已，并不用以限制本发明，凡在本发明的精神和原则之内所作的任何修改、等同替换和改进等，均应包含在本发明的保护范围之内。

Claims (9)

  1. 一种超宽范围大功率变换器电路，包括第一变压器模块、第二变压器模块、设置在所述第一变压器模块原边的第一原边输入模块、设置在所述第一变压器模块副边的第一副边输出模块、设置在所述第二变压器模块原边的第二原边输入模块、设置在所述第二变压器模块副边的第二副边输出模块、以及用于控制所述第一副边输出模块和所述第二副边输出模块在高压模式下串联且在低压模式下并联的高低压模式控制模块，以及用于接收所述第一副边输出模块和所述第二副边输出模块的串联输出电压或者并联输出电压的负载输出模块；所述第一副边输出模块包括第一整流网络、第二整流网络和第一参数均压网络，所述第二副边输出模块包括第三整流网络、第四整流网络和第二参数均压网络，所述第一副边输出模块或所述第二副边输出模块进一步包括第一谐振均压网络，所述第一整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第一参数均压网络连接所述第四整流网络，所述第二整流网络的输入端连接所述第一变压器模块的副边、输出端经所述第二参数均压网络连接所述第三整流网络，所述第三整流网络和所述第四整流网络还连接所述第二变压器模块的副边；其特征在于，所述超宽范围大功率变换器电路进一步包括第一谐振均压网络和/或第二谐振均压网络，所述第一谐振均压网络的第一端和第二端分别连接所述第一整流网络的两个输出端，第三端连接所述第二整流网络的输入端；所述第二谐振均压网络的第一端和第二端分别连接所述第二整流网络的两个输出端，第三端连接所述第一整流网络的输入端；通过设置谐振均压网络，解决在LLC谐振变换器轻载下发波控制的变化引起的特定的副边偏压问题。
  2. 根据权利要求1所述的超宽范围大功率变换器电路，其特征在于，所述超宽范围大功率变换器电路包括第一谐振均压网络和第二谐振均压网络，所述第一谐振均压网络包括第一谐振均压单元和第二谐振均压单元，所述第二谐振均压网络包括第三谐振均压单元和第四谐振均压单元；所述第一参数均压网络包括第一参数均压单元和第二参数均压单元，所述第二参数均压网络包括第三参数均压单元和第四参数均压单元。
  3. 根据权利要求2所述的超宽范围大功率变换器电路，其特征在于，所述第一变压器模块包括至少第一变压器网络和第二变压器网络，所述第一变压器网络和所述第二变压器网络的原边串联，所述第一变压器网络和所述第二变压器网络的副边分别连接所述第一副边输出模块，所述第二变压器模块包括至少第三变压器网络和第四变压器网络，所述第三变压器网络和所述第四变压器网络的原边串联，所述第三变压器网络和所述第四变压器网络的副边分别连接所述第二副边输出模块。
  4. 根据权利要求3所述的超宽范围大功率变换器电路，其特征在于，所述第一整流网络的第一输入端连接所述第一变压器网络的副边，第二输入端连接所述第二变压器网络的副边，第一输出端连接所述第三整流网络的第一端、所述第一参数均压单元的第一端和所述第二参数均压单元的第一端，所述第一谐振均压单元的第一端和所述第二谐振均压单元的第一端，第二输出端连接所述第三整流网络的第五端和第六端、所述第一参数均压单元的第二端和所述第二参数均压单元的第二端，所述第一谐振均压单元的第二端和所述第二谐振均压单元的第二端；所述第二整流网络的第一输入端连接所述第一变压器网络的副边，第二输入端连接所述第二变压器网络的副边，第一输出端连接所述第四整流网络的第一端和第二端、所述第三参数均压单元的第一端和所述第四参数均压单元的第一端，所述第三谐振均压单元的第一端和所述第四谐振均压单元的第一端，第二输出端连接所述第四整流网络的第五端和第六端、所述第三参数均压单元的第二端和所述第四参数均压单元的第二端，所述第三谐振均压单元的第二端和所述第四谐振均压单元的第二端；所述第一参数均压单元的第三端连接所述第四整流网络的第四端；所述第二参数均压单元的第三端连接所述第四整流网络的第三端；所述第三参数均压单元的第三端连接所述第三整流网络的第三端；所述第四参数均压单元的第三端连接所述第三整流网络的第四端；所述第一谐振均压单元的第三端连接所述第二整流网络的第一输入端；所述第二谐振均压单元的第三端连接所述第二整流网络的第二输入端；所述第三谐振均压单元的第三端连接所述第一整流网络的第二输入端；所述第四谐振均压单元的第三端连接所述第一整流网络的第一输入端。
  5. 根据权利要求4所述的超宽范围大功率变换器电路，其特征在于，所述第一原边输入模块包括第一原边均压网络、第一开关模块和第一LC模块，所述第二原边输入模块包括第二原边均压网络、第二开关模块和第二LC模块，所述第一原边均压网络连接在第一输入电容和第二开关模块之间，所述第二原边均压网络连接在第二输入电容和所述第一开关模块之间，所述第一开关模块经所述第一LC模块连接所述第一变压器模块，所述第二开关模块经所述第二LC模块连接所述第二变压器模块。
  6. 根据权利要求5所述的超宽范围大功率变换器电路，其特征在于，所述第一原边均压网络包括第一原边均压单元和第二原边均压单元，所述第一开关模块包括第一开关网络和第二开关网络，所述第一LC模块包括第一LC网络和第二LC网络，所述第二原边均压网络包括第三原边均压单元和第四原边均压单元，所述第二开关模块包括第三开关网络和第四开关网络，所述第二LC模块包括第三LC网络和第四LC网络。
  7. 根据权利要求6所述的超宽范围大功率变换器电路，其特征在于，所述第一输入电容的第一端连接所述第一原边均压单元的第一端、所述第二原边均压单元的第一端、所述第一开关网络的第一端和所述第二开关网络的第一端；所述第一输入电容的第二端连接所述第二输入电容的第一端、所述第三原边均压单元的第一端、所述第四原边均压单元的第一端、所述第二开关网络的第二端、所述第三开关网络的第一端、所述第四开关网络的第一端和所述第一开关网络的第二端；所述第二输入端电容的第二端连接所述第三开关网络的第二端和所述第四开关网络的第二端；所述第一原边均压单元的第二端、所述第二原边均压单元的第二端连接所述第二开关网络的第一端；所述第一原边均压单元的第三端连接所述第三开关网络的第三端和所述第三变压器网络；所述第二原边均压单元的第三端连接所述第四开关网络的第三端和所述第四变压器网络；所述第三原边均压单元的第三端连接所述第二开关网络的第三端和所述第二变压器网络；所述第四原边均压单元的第三端连接所述第一开关网络的第三端和所述第一变压器网络；所述第一开关网络的第四端经所述第一LC网络连接所述第一变压器网络；所述第二开关网络的第四端经所述第二LC网络连接所述第二变压器网络；所述第三开关网络的第四端经所述第三LC网络连接所述第三变压器网络；所述第四开关网络的第四端经所述第四LC网络连接所述第四变压器网络。
  8. 根据权利要求7所述的超宽范围大功率变换器电路，其特征在于，每个均压单元包括至少一个二极管串联分压支路和至少一个LC谐振支路，所述二极管串联分压支路包括至少一对串联二极管，所述至少一对串联二极管的中央连接点为分压点，所述二极管串联分压支路的两端构成所述均压单元的第一端和第二端；所述LC谐振支路包括至少一组串联的谐振电感和谐振电容，所述LC谐振支路的第一端连接所述分压点、第二端构成所述均压单元的第三端。
  9. 根据权利要求8所述的超宽范围大功率变换器电路，其特征在于，所述第一变压器网络、所述第二变压器网络分别包括一个变压器或者一个以上彼此串联的变压器。
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