WO2022042231A1 - 天线单元、天线阵列及电子设备 - Google Patents

天线单元、天线阵列及电子设备 Download PDF

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Publication number
WO2022042231A1
WO2022042231A1 PCT/CN2021/110352 CN2021110352W WO2022042231A1 WO 2022042231 A1 WO2022042231 A1 WO 2022042231A1 CN 2021110352 W CN2021110352 W CN 2021110352W WO 2022042231 A1 WO2022042231 A1 WO 2022042231A1
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WIPO (PCT)
Prior art keywords
microstrip line
slot
slit
antenna
antenna unit
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PCT/CN2021/110352
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English (en)
French (fr)
Inventor
张瑞
李堃
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华为技术有限公司
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Publication of WO2022042231A1 publication Critical patent/WO2022042231A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements

Definitions

  • the embodiments of the present application relate to the field of antenna technologies, and in particular, to an antenna unit, an antenna array, and an electronic device.
  • Customer Premise Equipment also known as wireless CPE
  • wireless CPE Customer Premise Equipment
  • Outdoor wireless CPEs are usually installed in some remote areas with relatively low population density.
  • Directional high-gain antenna units can be used to increase signal strength toward the base station, which can better ensure the communication experience in remote areas.
  • dipole antenna units are usually used in wireless CPEs.
  • the distance between the antenna unit of the dipole antenna and the reflector is large, so the cross-sectional size is large and the integration difficulty is high.
  • a balun feeding structure needs to be set up, and the process is complicated and the cost is high.
  • Embodiments of the present application provide an antenna unit, an antenna array and an electronic device, which solve the problems of large antenna size and high integration difficulty.
  • an antenna unit comprising: a dielectric board, the dielectric board includes a first surface and a second surface opposite to each other, and the first surface of the dielectric board is provided with There is a microstrip line, a metal layer is arranged on the second surface of the dielectric plate, a slot is arranged on the metal layer, and the slot is opposite to the microstrip line, wherein the microstrip line is used for coupling and feeding the slot . Therefore, the antenna unit adopts a single-board structure, and has a small cross-sectional size, simple wiring, low process complexity, and reduced production cost.
  • a first signal input port and a second signal input port are further provided on the first surface of the dielectric board
  • the microstrip line includes a first microstrip line and a second microstrip line
  • the first microstrip line is connected to the first signal input port
  • the second microstrip line is connected to the second signal input port
  • the slot includes a first slot and a second slot opposite to the first microstrip line
  • the first slot A slot and the second slot are arranged separately
  • the first microstrip line is used for feeding the first slot
  • the second microstrip line is used for feeding the second slot, so that the first slot and the second slot are
  • the polarization directions are orthogonal to each other. Therefore, signals whose polarization directions are orthogonal to each other can be input to the first microstrip line and the second microstrip line respectively through the first signal input port and the second signal input port, thereby improving the polarization performance of the antenna.
  • the projection of the first microstrip line on the metal layer is perpendicular to the intersection of the first slit; the projection of the second microstrip on the metal layer and perpendicular to the second slit line where it intersects.
  • the first microstrip line can transfer energy to the first slot
  • the second microstrip line can transfer energy to the second slot.
  • the first slit and the second slit are arranged in a cross shape. Therefore, setting the first slot and the second slot in a crisscross shape can reduce the length and width of the slot and realize the miniaturization of the horizontal plane size of the antenna unit, which is suitable for scenarios with high integration of the antenna unit.
  • the lengths l of the first slit and the second slit are both: where ⁇ is the wavelength of the radio wave. Therefore, the length of the slot is approximately equal to half the wavelength of the radio wave, and when the length of the slot is equal to half the wavelength, the radiation performance is better.
  • the shapes of the first slit and the second slit include any one of the following: a linear shape, a curved shape, and a broken line shape.
  • the first slit and the second slit intersect, and the first slit and the second slit are perpendicular at the intersection. Therefore, the first slot and the second slot are perpendicular at the intersection, so that the polarization directions of the first slot and the second slot are orthogonal to each other, and dual polarization is realized.
  • the first slit and the second slit form a symmetrical crisscross pattern with respect to the axis. Therefore, the volume of the antenna unit can be reduced by arranging the first slot and the second slot symmetrically with respect to the axis.
  • the metal layer is further provided with a plurality of third slits, the third slits are perpendicular to the first slit or the second slit, and among the plurality of third slits.
  • the at least two third slits are symmetrical about a straight line passing through the cross point. Therefore, by providing the third slit, the length and width of the first slit and the second slit can be reduced, which saves more space.
  • the first slit and the second slit form a symmetrical crisscross pattern with respect to the intersection. Therefore, the first slot and the second slot are symmetrically arranged with respect to the intersection point, so that the volume of the antenna unit can be reduced.
  • the metal layer is further provided with a plurality of third slits, the third slits are perpendicular to the first slit or the second slit, and are symmetrical about the center of the intersection point. . Therefore, by providing the third slit, the length and width of the first slit and the second slit can be reduced, which saves more space.
  • the first microstrip line and the second microstrip line have a "U"-shaped structure, wherein the extension direction of the "1" side of the first microstrip line is the first microstrip line.
  • the extension direction of the strip line, the extension direction of the "1" of the second microstrip line is the extension direction of the first microstrip line, and a "1" side of the first microstrip line is connected to the second microstrip line.
  • One of the " ⁇ " sides is set in a cross shape. Therefore, the first microstrip line and the second microstrip line adopt a "U"-shaped structure, which saves more space.
  • the first microstrip line includes a first sub-microstrip line and a second sub-microstrip line
  • the metal layer is provided with an opening
  • the first sub-microstrip line is disposed on the dielectric plate on the second surface of the microstrip line and located in the opening, wherein the first sub-microstrip line and the second sub-microstrip line are arranged in parallel and alternately connected along the "1" side of the first microstrip line, wherein , the projection of the first sub-microstrip line on the first surface of the dielectric plate intersects the "1" side of the second microstrip line.
  • the first microstrip line and the second microstrip line at the cross position are arranged in different layers, so as to avoid mutual interference of signals transmitted by the first microstrip line and the second microstrip line.
  • the dielectric board is a PCB substrate, and the shape of the dielectric board is a rectangle, a circle, a triangle or other regular shapes.
  • Any of the above-mentioned possible implementation manners can achieve the effects to be achieved by the above-mentioned corresponding possible implementation manners for a dielectric board of any shape, material and structure. Therefore, the shape selection of the medium plate is more flexible, the shape of the medium plate can be adjusted according to the product form, and the application range is wider.
  • an electronic device including a device body, a radio frequency module and the above-mentioned antenna unit, wherein the antenna unit and the radio frequency module are arranged in the device body, and the radio frequency module is used for An electromagnetic signal is sent to the antenna unit, and the antenna unit radiates electromagnetic waves according to the received electromagnetic signal. Therefore, the electronic device adopts the above-mentioned antenna unit, which has a smaller size and a simple structure, which is beneficial to product miniaturization and cost reduction.
  • the electronic device includes customer premise equipment CPE.
  • a third aspect of the present application provides an antenna array comprising at least two antenna units as described above, and a reflector; wherein each of the antenna units is coupled to the reflector, and the antenna units are disposed at On one side of the reflecting plate, the second surface of the dielectric plate is close to the reflecting plate, and the first surface of the dielectric plate is away from the reflecting plate. Therefore, the antenna array using the above-mentioned antenna unit has smaller size and simple structure, which is beneficial to product miniaturization and cost reduction.
  • the distance between the metal layer and the reflector is less than a preset value, an edge of the metal layer and the reflector form a fourth gap, and the microstrip line is coupled to the fourth gap.
  • the radiation performance of the antenna is further improved.
  • the first signal input ports of the at least two antenna units are connected, and the second signal input ports of the at least two antenna units are connected. In this way, the first signal input ports of the multiple antenna units are combined, and the second signal input ports of the multiple antenna units are combined, so as to control the working mode of the antenna.
  • a fourth aspect of the present application provides an electronic device, including a device body, a radio frequency module, and the above-mentioned antenna array, wherein the antenna array and the radio frequency module are arranged in the device body, and the radio frequency module is used for Electromagnetic signals are sent to the antenna array, which radiates electromagnetic waves according to the received electromagnetic signals. Therefore, the electronic device adopts the above-mentioned antenna array, which has a smaller size and a simple structure, which is beneficial to product miniaturization and cost reduction.
  • the electronic device includes customer premise equipment CPE.
  • FIG. 1a is a schematic structural diagram of an antenna unit provided by an embodiment of the present application.
  • Fig. 1b is A-A sectional view in Fig. 1a;
  • FIG. 2 is a bottom view of an antenna unit according to an embodiment of the present application.
  • FIG. 2a is a bottom view of another antenna unit provided by an embodiment of the application.
  • FIG. 2b is a bottom view of another antenna unit provided by an embodiment of the application.
  • FIG. 2c is a bottom view of another antenna unit provided by an embodiment of the present application.
  • FIG. 2d is a bottom view of another antenna unit provided by an embodiment of the application.
  • FIG. 3 is a bottom view of another antenna unit provided by an embodiment of the present application.
  • 3a is a bottom view of another antenna unit provided by an embodiment of the application.
  • 3b is a bottom view of another antenna unit provided by an embodiment of the application.
  • FIG. 4a is a top view of an antenna unit according to an embodiment of the application.
  • FIG. 4b is a top view of another antenna unit provided by an embodiment of the application.
  • FIG. 5a is a schematic projection diagram of an antenna unit according to an embodiment of the present application.
  • FIG. 5b is a schematic projection diagram of an antenna unit according to an embodiment of the present application.
  • 6a is a top view of an antenna array provided by an embodiment of the application.
  • FIG. 6b is a schematic structural diagram of an antenna array provided by an embodiment of the present application.
  • FIG. 7 is a 3D radiation pattern of an antenna array provided by an embodiment of the present application.
  • FIG. 8 is a 2D radiation pattern of an antenna array provided by an embodiment of the present application.
  • 9a-9c are S-parameter curve diagrams of the antenna array according to the embodiment of the present application at 3.3 GHz to 5 GHz;
  • FIG. 10 is a graph of gain parameters of the antenna array according to the embodiment of the present application at 3.3 GHz to 5 GHz;
  • FIG. 11 is a graph showing the efficiency parameters of the antenna array according to the embodiment of the present application in the range of 3.3 GHz to 5 GHz;
  • FIG. 12 is a schematic structural diagram of an electronic device provided by an embodiment of the present application.
  • orientation terms such as “upper” and “lower” are defined relative to the orientation in which the components in the drawings are schematically placed. It should be understood that these directional terms are relative concepts, and they are used for relative In the description and clarification of the drawings, it may change correspondingly according to the change of the orientation in which the components are placed in the drawings.
  • Coupling refers to the phenomenon that there is close cooperation and mutual influence between the input and output of two or more circuit elements or electrical networks, and energy is transmitted from one side to the other through interaction.
  • Antenna Pattern also known as Radiation Pattern. It refers to the graph of the relative field strength (normalized modulus value) of the antenna radiation field changing with the direction at a certain distance from the antenna. It is usually represented by two mutually perpendicular plane patterns in the maximum radiation direction of the antenna.
  • Antenna patterns usually have multiple radiating beams.
  • the radiation beam with the highest radiation intensity is called the main lobe, and the remaining radiation beams are called side lobes or side lobes.
  • the side lobes In the side lobes, the side lobes in the opposite direction to the main lobe are also called back lobes.
  • Beamwidth divided into horizontal beamwidth and vertical beamwidth.
  • the horizontal beamwidth refers to the angle between the two directions in the horizontal direction, on both sides of the maximum radiation direction, the radiated power decreases by 3dB;
  • the vertical beamwidth refers to the vertical direction, on both sides of the maximum radiation direction, the radiated power The angle between the two directions that drop 3dB.
  • Antenna gain used to characterize the degree to which the antenna radiates the input power in a concentrated manner. Generally, the narrower the main lobe of the antenna pattern and the smaller the side lobes, the higher the antenna gain.
  • Antenna system efficiency refers to the ratio of the power radiated by the antenna to the space (that is, the power that effectively converts the electromagnetic wave part) to the input power of the antenna.
  • Antenna radiation efficiency refers to the ratio of the power radiated by the antenna to the space (that is, the power that effectively converts the electromagnetic wave part) to the active power input to the antenna.
  • the active power input to the antenna the input power of the antenna-return loss;
  • the return loss mainly includes the ohmic loss and/or dielectric loss of the metal.
  • Antenna return loss It can be understood as the ratio of the signal power reflected back to the antenna port through the antenna circuit to the transmit power of the antenna port. The smaller the reflected signal, the greater the signal radiated to the space through the antenna, and the greater the radiation efficiency of the antenna. The larger the reflected signal, the smaller the signal radiated to the space through the antenna, and the smaller the radiation efficiency of the antenna.
  • the antenna return loss can be represented by the S11 parameter, which is usually a negative number.
  • S11 the smaller the return loss of the antenna and the greater the radiation efficiency of the antenna; the larger the parameter S11, the greater the return loss of the antenna and the smaller the radiation efficiency of the antenna.
  • Antenna isolation refers to the ratio of the signal power transmitted by one antenna to the signal power received by another antenna. It can be represented by S21 and S12 parameters.
  • FIG. 1a is a schematic structural diagram of an antenna unit provided by an embodiment of the present application.
  • the antenna unit includes: a dielectric plate 10 , a microstrip line 100 and a metal layer 20 .
  • the dielectric plate 10 includes: opposing first and second surfaces a1 and a2. Wherein, the first surface a1 of the dielectric plate 10 is provided with a microstrip line 100, the second surface a2 of the dielectric plate 10 is provided with a metal layer 20, and the metal layer 20 is provided with a slit 200, the slit 200 and the The microstrip lines 100 are disposed opposite to each other, and the vertical projection of the microstrip line 100 on the metal layer 20 intersects the slot 200 , wherein the microstrip line 100 is used for coupling and feeding the slot 200 .
  • the dielectric board 10 is a PCB substrate, and the shape of the dielectric board 10 may be a rectangle, a circle, a triangle or other regular shapes.
  • the material of the metal layer 20 is metal copper, that is, the metal layer 20 is a copper layer disposed on the first surface a1 of the dielectric board 10 .
  • the metal layer 20 is printed on the first surface a1 of the dielectric board 10 .
  • the dielectric board 10 may also be other substrates having a bearing function, and the material of the first functional layer may also be other conductors, which are not specifically limited in this application.
  • the microstrip line 100 can be connected to a signal input port, so that a radio frequency signal can be received from the signal input port, and the radio frequency signal can be transmitted to the position of the slot 200 of the metal layer 20, so that the slot 200 is excited with a radio frequency electromagnetic field, and Radiate electromagnetic waves into space.
  • the microstrip line 100 may be disposed on the first surface a1 of the dielectric board 10 by, for example, printing.
  • the antenna unit is, for example, a directional antenna, wherein the antenna unit is, for example, disposed close to the reflector, the first surface a1 of the dielectric plate 10 is disposed away from the reflector, and the second surface a2 of the dielectric plate 10 is disposed close to the reflector .
  • the antenna unit includes, for example, a front side and a back side.
  • the side of the antenna unit with the microstrip line 100 is, for example, the front side
  • the side of the antenna unit with the metal layer 20 is, for example, the back side.
  • the above-mentioned slits radiate electromagnetic waves toward the reflector toward the back.
  • the radiation direction of the electromagnetic waves changes under the action of the reflector, so that the electromagnetic waves are radiated toward the front to form a directional beam and achieve a directional high. gain effect.
  • the antenna unit may be, for example, a dual-polarized antenna unit.
  • the dielectric board 10 is provided with two signal input ports: a first signal input port 1011 and a second signal input port 1021.
  • the first signal input port 1011 The first polarized signal is input to the strip line 100
  • the second signal input port 1021 can input the second polarized signal to the microstrip line 100 , for example.
  • the polarization directions of the first polarized signal and the second polarized signal are orthogonal, that is, the amplitudes of the first polarized signal and the second polarized signal are equal and differ by 90°.
  • the dual-polarized antenna unit may adopt a ⁇ 45° dual-polarization mode, or a vertical/horizontal dual-polarization mode, which is not limited in this application, and all belong to the protection scope of this application.
  • the microstrip line 100 includes, for example, a first microstrip line 101 and a second microstrip line 102.
  • the first position of the first microstrip line 101 is connected to the first signal input port 1011 and has at least one free end.
  • the second position of the two microstrip lines 102 is connected to the second signal input port 1021 and has at least one free end.
  • the metal layer 20 is provided with, for example, a first ground port 203 and a second ground port 204 .
  • the antenna unit is connected to a radio frequency input end, wherein the radio frequency input end may include: a signal line and a ground line, wherein the signal line of the radio frequency input end may be connected to the first signal input port 1011 and the second signal input port 1021 respectively,
  • the ground wires of the radio frequency input end are respectively connected to the first ground port 203 and the second ground port 204 on the metal layer 20 .
  • the embodiment of the present application does not limit the specific shape of the slit 200 .
  • the slits 200 provided on the metal layer 20 can be divided into first slits 201 and second slits 202 .
  • the first slit 201 and the second slit 202 intersect, and the first slit 201 and the second slit 202 are perpendicular at the intersection. Therefore, the first slot and the second slot are perpendicular at the intersection, so that the polarization directions of the first slot and the second slot are orthogonal to each other, and dual polarization is realized.
  • the relative positions of the first slit 201 and the second slit 202 are not limited in this embodiment of the present application, wherein, as shown in FIG. 2 , the first slit 201 and the second slit 202 may be asymmetric, or as shown in FIG. As shown, the first slit 201 and the second slit 202 may be symmetrical about a line O passing through the intersection of the first slit 201 and the second slit 202, or as shown in FIG. 3, the first slit 201 and the second slit 202 It may be centrally symmetric with respect to the intersection O' of the first slit 201 and the second slit 202 .
  • the embodiments of the present application do not limit the shapes of the first slit 201 and the second slit 202 .
  • the first slit 201 and the second slit 202 are rectangles, such as rectangles with rounded corners.
  • the The first slit 201 and the second slit 202 may also be curved or zigzag.
  • the embodiments of the present application do not limit the lengths of the first slit 201 and the second slit 202.
  • the lengths l of the first slit 201 and the second slit 202 are both: where ⁇ is the wavelength of the radio wave. Therefore, the length of the slot is approximately equal to half the wavelength of the radio wave, and when the length of the slot is equal to half the wavelength, the radiation performance is better.
  • the length l of the first slit 201 and the second slit 202 is the length of the long side of the first slit 201 and the second slit 202.
  • the first slits 201 and the second slits 202 are in a crisscross pattern, and the first slits 201 and the second slits 202 are asymmetrical.
  • the first slit 201 and the second slit 202 are symmetrical about a line passing through the intersection of the first slit 201 and the second slit 202 .
  • the first slits 201 and the second slits 202 are in a symmetrical crisscross pattern with respect to the axis O. As shown in FIG.
  • the metal layer 20 is further provided with a plurality of third slits 206, the third slits 206 are perpendicular to the first slit 201 or the second slit 202, and the At least two of the third slits 206 are symmetrical with respect to the above-mentioned straight line passing through the intersection of the first slit 201 and the second slit 202 . Therefore, by providing the third slit, the length and width of the first slit and the second slit can be reduced, which saves more space.
  • This embodiment of the present application does not limit the number and specific structure of the third slits 206.
  • there are four third slits 206 which are respectively the same as the first slits.
  • 201 and the second slits 202 are perpendicular, and the four third slits 206 are symmetrically arranged with respect to the axis O.
  • the embodiment of the present application does not limit the shape of the third slit 206 .
  • the third slit 206 is a rectangle, such as a rectangle with rounded corners, and in other embodiments of the present application, the third slit 206 may also adopt a curve shape and line structure.
  • the third slit 206 on the metal layer 20
  • the physical length of the first slit 201 and the second slit 202 can be further reduced under the condition of keeping the electrical lengths of the first slit 201 and the second slit 202 unchanged. length and width, reducing the horizontal dimension of the antenna element.
  • This embodiment of the present application does not limit the position of the third slit 206.
  • the first slit 201 and the second slit 202 form a cross-shaped structure, and the third slit 206 are respectively arranged in the middle positions of the four sides of the cross.
  • the first slit 201 and the second slit 202 are centrally symmetric about the intersection O' of the first slit 201 and the second slit 202 . Therefore, by arranging the first slot 201 and the second slot 202 in an intersecting manner, the horizontal plane size of the antenna unit can be further reduced, which is beneficial to the miniaturization of the antenna unit.
  • first slit 201 and the second slit 202 form a symmetrical crisscross pattern with respect to the intersection O'.
  • the metal layer 20 is further provided with a plurality of third slits 206 , and the third slits 206 are perpendicular to the first slit 201 or the second slit 202 . At least two of the third slits 206 are centrally symmetric with respect to the intersection O' of the first slit 201 and the second slit 202 .
  • the embodiment of the present application does not limit the number and specific structure of the third slits 206.
  • there are four third slits 206 which are respectively the same as the first slits.
  • 201 and the second slits 202 are perpendicular, and the four third slits 206 are symmetrically arranged with respect to the intersection O' of the first slits 201 and the second slits 202 crossed by the cross.
  • the embodiment of the present application does not limit the shape of the third slit 206 .
  • the third slit 206 is a rectangle, such as a rectangle with rounded corners.
  • the third slit 206 may also adopt a curve shape and line structure.
  • the third slit 206 on the metal layer 20
  • the physical length of the first slit 201 and the second slit 202 can be further reduced under the condition of keeping the electrical lengths of the first slit 201 and the second slit 202 unchanged. length and width, reducing the horizontal dimension of the antenna element.
  • This embodiment of the present application does not limit the position of the third slit 206.
  • the first slit 201 and the second slit 202 form a cross-shaped structure, and the third slits 206 are respectively provided in the middle of the four sides of the cross.
  • the third slits 206 are respectively provided at both ends of the first slit 201 and the second slit 202 , and the third slits 206 are respectively connected with the first slits 201 , the second slits
  • the slits 202 form an "I"-shaped structure.
  • the embodiments of the present application do not limit the relative positions of the first microstrip line 101 and the second microstrip line 102.
  • the first microstrip line At least one "1" side of the 101 and at least one "1" side of the second microstrip line 102 are arranged in a cross shape. Therefore, the cross arrangement of the first microstrip line 101 and the second microstrip line 102 can further reduce the size of the horizontal plane of the antenna unit, which is beneficial to the miniaturization of the antenna unit.
  • the polarization directions of the signals transmitted by the first microstrip line 101 and the second microstrip line 102 are orthogonal, and the arrangement of the first microstrip line 101 and the second microstrip line 102 is also orthogonal, which improves the antenna performance. Unit isolation.
  • the cross arrangement of the first microstrip line 101 and the second microstrip line 102 can further reduce the size of the horizontal plane of the antenna unit, which is beneficial to the miniaturization of the antenna unit.
  • the first microstrip line 101 includes: a first side 1012, a second side 1013 and a third side 1014, and the first side 1012, the second side 1013 and the third side 1014 together form a " U" shaped structure.
  • the second microstrip line 102 includes a fourth side 1022 , a fifth side 1023 and a sixth side 1024 , and the fourth side 1022 , the fifth side 1023 and the sixth side 1024 together form a “U”-shaped structure.
  • the second side 1013 of the first microstrip line 101 and the fifth side 1023 of the second microstrip line 102 are arranged orthogonally.
  • the second side 1013 of the first microstrip line 101 is orthogonal to the fifth side 1023 of the second microstrip line 102 and the fourth side 1022 of the second microstrip line 102, and the first microstrip line 102
  • the first side 1012 of the strip line 101 is respectively arranged orthogonally to the fourth side 1022 of the second microstrip line 102 and the fifth side 1023 of the second microstrip line 102 .
  • the first microstrip line 101 and the second microstrip line 102 may be intersected Part of the jumper wire is routed to the second surface of the dielectric board to avoid the second microstrip line 102 .
  • the second side 1013 of the first microstrip line 101 and the fifth side 1023 of the second microstrip line 102 are arranged orthogonally, in order to avoid positive
  • the intersecting second side 1013 and the fifth side 1023 interfere with each other.
  • the intersecting portion of the second side 1013 can be jumpered to the second surface of the dielectric board to avoid the fifth side 1023 .
  • the crossing portion of the fifth side 1023 may also be jumpered to the second surface of the dielectric board to avoid the second side 1013 .
  • the first microstrip line 101 includes at least one first sub-microstrip line 103 and at least one second sub-microstrip line Line 104.
  • the first sub-microstrip line 103 and the second sub-microstrip line 104 are arranged in parallel, that is, the first sub-microstrip line 103 and the second sub-microstrip line 104 are arranged in a staggered manner, and they are not on the same extension line.
  • the first sub-microstrip line 103 and the second sub-microstrip line 104 are alternately connected along the extending direction of the first microstrip line 101 .
  • the second sub-microstrip line 104 and the first sub-microstrip line 103 are disposed in different layers, and the first sub-microstrip line 103 and the second microstrip line 102 are disposed in the same layer.
  • the first sub-microstrip line 103 and the second microstrip line 102 in the first microstrip line 101 are arranged on the same layer, and the second sub-microstrip line 104 in the first microstrip line 101 is jumpered to the dielectric board 20 to avoid shorting with the second microstrip line 102 .
  • an opening 205 can be provided on the metal layer 20, and the second sub-microstrip The wire 104 is disposed within the opening 205 .
  • the microstrip lines of adjacent layers are respectively disposed on the first surface and the second surface of the dielectric plate.
  • This application does not limit the material of the dielectric board, and any material that can play an insulating role can be applied to the dielectric board 20 .
  • connection mode of the first sub-microstrip line 103 and the second sub-microstrip line 104 is not limited.
  • the first microstrip line 101 further includes a connecting portion 105.
  • the first sub-microstrip line 103 and the second sub-microstrip line 104 are connected through the connecting portion 105 .
  • the connecting portion 105 can use via holes, wherein the via holes are also called metallized holes, which are used to connect the first sub-microstrip line 103 and the second sub-microstrip line 104.
  • a common hole ie a via hole, is drilled at the intersection of the line 103 and the second sub-microstrip line 104 at the intersection of the dielectric board 10 .
  • a layer of metal may be plated on the cylindrical surface of the hole wall of the via hole, for example, by chemical deposition, so as to connect the first sub-microstrip line 103 and the second sub-microstrip line 104 .
  • the polarization directions of the signals transmitted by the first microstrip line 101 and the second microstrip line 102 are orthogonal, and the arrangement of the first microstrip line 101 and the second microstrip line 102 is also orthogonal, which improves the Isolation of the antenna elements.
  • the second microstrip line 102 is avoided, and the first sub-microstrip line 103 and the second sub-microstrip line are connected through the connecting part 105 104, under the condition that the first microstrip line 101 and the second microstrip line 102 do not interfere with each other, the first microstrip line and the second microstrip line can be set orthogonally to reduce the occupation of the horizontal plane space, there are Conducive to the miniaturization of equipment.
  • first microstrip line 101 is jumped to other layers as an example.
  • second microstrip line 102 can also be crossed with the first microstrip line 101. Part of the jumper wire to other layers, these all belong to the protection scope of this application.
  • the second side 1013 of the first microstrip line 101 is respectively connected to the fifth side 1023 of the second microstrip line 102 and the fourth side of the second microstrip line 102 .
  • the sides 1022 are orthogonally arranged, and the first side 1012 of the first microstrip line 101 is respectively arranged orthogonally to the fourth side 1022 of the second microstrip line 102 and the fifth side 1023 of the second microstrip line 102.
  • the intersecting second side 1013 and the fifth side 1023, the second side 1013 and the fourth side 1022, the first side 1012 and the fifth side 1023, and the first side 1012 and the fourth side 1022 interfere with each other.
  • the part of the second side 1013 that intersects the fifth side 1023 and the part of the second side 1013 that intersects the fourth side 1022 can be jumpered to the second surface of the dielectric board to avoid the The fifth side 1023 and the fourth side 1022, and the part of the first side 1012 that intersects the fifth side 1023 and the part of the first side 1012 that intersects the fourth side 1022 are all jumpered to the second surface of the dielectric board , to avoid the fifth side 1023 and the fourth side 1022.
  • the part of the fifth side 1023 that intersects the first side 1012 and the fifth side 1023 and the second side 1013 can also be jumpered to the second surface of the dielectric board to avoid the first side 1012 and the second side.
  • the first slot 201 is arranged opposite to the first microstrip line 101
  • the second slot 202 is arranged opposite to the second microstrip line 102
  • the first microstrip line 101 is used to feed the first slot 201
  • the second microstrip line 102 is used to feed the second slot 202 .
  • the projection of the first microstrip line 101 on the metal layer 20 is perpendicular to the intersection of the first slit 201 .
  • the projection of the second microstrip line 102 on the metal layer 20 is perpendicular to the intersection of the second slit 202 .
  • first microstrip line 101 and the second microstrip line 102 are not limited in this embodiment of the present application.
  • the first microstrip line 101 and the second microstrip line 102 are, for example, "U” shaped, and the first microstrip line 101 and the second microstrip line 102 pass through “U” respectively.
  • the "1" part of "" feeds the slit 200 provided on the metal layer 20.
  • the above-mentioned first slit 201 is disposed opposite to the first microstrip line 101, which means that the vertical projection of the first microstrip line 101 on the metal layer 20 intersects with the first slit 201, and the above-mentioned second slit 202 and
  • the opposite arrangement of the second microstrip line 102 means that the vertical projection of the second microstrip line 102 on the metal layer 20 intersects the second slit 202 .
  • the first projection 1010 of at least one “1” portion of the first microstrip line 101 on the metal layer 20 intersects the first slit 201 and is perpendicular to the first slit 201 extension direction.
  • the second projection 1020 of at least one “1” portion of the second microstrip line 102 on the metal layer 20 intersects the second slit 202 and is perpendicular to the extending direction of the second slit 202 .
  • the first projections 1010 of the two “1” portions of the first microstrip line 101 on the metal layer 20 both intersect with the first slit 201 and are perpendicular to the extending direction of the first slit 201 .
  • the second projections 1020 of the two "1" portions of the second microstrip line 102 on the metal layer 20 intersect the second slit 202 and are perpendicular to the extending direction of the second slit 202 .
  • the first microstrip line 101 feeds the first slot 201 through the two "1" parts of the "U”
  • the second microstrip line 102 feeds the second slot through the two "1” parts of the "U” 202 is fed to improve the coupling performance.
  • the first projections 1010 of one “1” portion of the first microstrip line 101 on the metal layer 20 all intersect with the first slit 201 and are perpendicular to the extending direction of the first slit 201 .
  • the second projection 1020 of one “1” portion of the second microstrip line 102 on the metal layer 20 intersects with the second slit 202 and is perpendicular to the extending direction of the second slit 202 .
  • the slot can be fed through only one "1" side of the "U"-shaped structure.
  • the first slot 201 and the second slot 202 may be fed respectively through the two "1" sides of "U” in the microstrip line, or only 1 of the "U” in the microstrip line may be fed.
  • Each "1" side feeds the first slot 201 and the second slot 202 respectively, which all belong to the protection scope of the present application.
  • the first slot 201 can be along the first slot 201.
  • the microstrip line 101 is symmetrically arranged, and the second slot 202 is arranged symmetrically along the second microstrip line 102 .
  • the extension direction of the first projection 1010 of the "1" portion of the first microstrip line 101 on the metal layer 20 can be perpendicular to the extension direction of the first slit 201, and the first slit 201 is along the The extending direction of the first projection 1010 is symmetrically arranged. And make the extension direction of the second projection 1020 of the "1" portion of the second microstrip line 102 on the metal layer 20 perpendicular to the extension direction of the second slit 202, and the second slit 202 is along the second projection The extension direction of 1020 is set symmetrically.
  • the first slot 201 is symmetrically arranged along the first projection 1010
  • the second slot 202 is arranged symmetrically along the second projection 1020, which is beneficial to pass the radio frequency energy through the first microstrip line 101 respectively.
  • the second microstrip line 102 are evenly transmitted into the slot 200, so as to avoid impedance mismatch caused by uneven transmission of radio frequency energy.
  • the present application also provides an antenna array comprising at least two antenna units as described above, and a reflector; wherein each of the antenna units is coupled to the reflector.
  • the antenna array includes a reflector 01 , and a first antenna unit 001 and a second antenna unit 002 located on one side of the reflector 01 .
  • each edge of the metal layer 20 of the first antenna unit 001 and the second antenna unit 002 can also form a fourth slot 010 with the reflector, and the microstrip line 100 is also used for coupling and feeding the fourth slot, Under the excitation of the microstrip line 100, the fourth slot also generates radiation.
  • the first antenna unit 001 and the second antenna unit 002 include: a dielectric plate 10 disposed on one side of the reflector, and a metal layer 20 is disposed on the surface of the dielectric plate 10 close to the reflector 01 .
  • the total thickness of the dielectric plate 10 and the metal layer 20 is about 1 mm, the plane size of the dielectric plate 10 and the metal layer 20 is 30 ⁇ 30 mm, and the distance between the antenna unit and the reflector is about 9 mm.
  • the antenna unit works in 5G N77 ⁇ N79 (3.3GHz ⁇ 5GHz) frequency band.
  • the plane size of the antenna array is 30x80mm, and the section height is 10mm.
  • the first signal input port 1011A of the first antenna unit 001 and the first signal input port 1011B of the second antenna unit The second signal input port 1021A and the second signal input port 1021B of the second antenna unit 002 are combined.
  • the first signal input port 1011A of the first antenna unit 001 and the first signal input port 1011B of the second antenna unit 002 are used as the first combination, and the second signal input port 1021A of the first antenna unit 001 and the first signal input port 1011B of the second antenna unit 002 are used as the first combination.
  • the second signal input port 1021B of the two antenna units 002 is the second combiner.
  • FIG. 7 is a 3D radiation pattern at 3.3 GHz when the first combination of the antenna array is turned on and the second combination is matched. It should be noted that the combination circuit is connected means that there is signal transmission in the combination circuit, and the combination circuit matching means that there is no signal transmission in the combination circuit.
  • (b) in FIG. 7 is a 3D radiation pattern at 4.2 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • FIG. 7 is the 3D radiation pattern at 5 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • FIG. 7 is the 3D radiation pattern at 3.3 GHz when the second combination of the antenna array is turned on and the first combination is matched.
  • FIG. 7 is the 3D radiation pattern at 4.2 GHz when the second combination of the antenna array is turned on and the first combination is matched.
  • (f) in FIG. 7 is the 3D radiation pattern at 5 GHz when the second combination of the antenna array is turned on and the first combination is matched.
  • the main lobe beams of the first combiner and the second combiner in the 3.3GHz, 4.2GHz and 5GHz 3D patterns of the antenna array are stable, and the first
  • the projection of the antenna's pattern on the XOY plane is +45°.
  • the antenna's pattern is on the XOY plane.
  • the projection is oriented towards -45°, enabling dual polarization.
  • (a) in FIG. 8 is the horizontal plane radiation pattern at 3.3 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • the half-power beamwidth (HPBW) of the horizontal plane is 61.1°.
  • (b) in FIG. 8 is the horizontal plane radiation pattern at 4.2 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • the half-power beamwidth of the horizontal plane is 60.5°.
  • (c) in FIG. 8 is the horizontal plane radiation pattern at 5 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • (d) in FIG. 8 is the vertical plane radiation pattern at 3.3 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • the half-power beamwidth of the vertical plane is 42.3°.
  • (e) in FIG. 8 is the pattern of the vertical radiation plane at 4.2 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • the half-power beamwidth of the vertical plane is 34.8°.
  • (f) in FIG. 8 is the pattern of the vertical radiation plane at 5 GHz when the first combination of the antenna array is turned on and the second combination is matched.
  • the half-power beamwidth of the vertical plane is 29.9°.
  • the horizontal radiating surface of the above-mentioned antenna array is the xoz plane in Fig. 6a
  • the vertical radiating surface of the above-mentioned antenna array is the yoz plane in Fig. 6a, wherein the z-axis is not shown in Fig. 6a, and the z-axis is vertical in the xoy plane.
  • the 2D pattern shows that the horizontal beamwidth of the antenna array is about 60°, and the vertical plane beamwidth is about 30°.
  • the above-mentioned horizontal beam width and vertical beam width are the half-wave power width, also called 3dB lobe width, which refers to the angle between the two half-power points on the main lobe of the pattern, and can also be relative to the maximum radiation direction.
  • the antenna array includes a total of four ports, the first signal input port 1011A of the first antenna unit 001 is used as port 1, the second signal input port 1021A of the first antenna unit 001 is used as port 2, and the second antenna unit 002 The first signal input port 1011B is used as port 3, and the second signal input port 1021B of the second antenna unit 002 is used as port 4.
  • Figure 9a shows the reflection coefficients, ie return losses, of each port of the two antenna elements.
  • the abscissa at point 1 in Fig. 9a is 3.1793GHz, and the ordinate is -5.2107dB.
  • the abscissa at point 2 in Figure 9a is 5.1809GHz, and the ordinate is -5.3097dB.
  • S(1,1) is the reflection coefficient of port 1
  • S(2,2) is the reflection coefficient of port 2
  • S(3,3) is the reflection coefficient of port 3
  • S(4,4) is port 4
  • S1,1[1,0]+3[1,0] is the reflection coefficient after port 1 and port 3 are combined
  • S2,2[1,0]+4[1,0] is port 2 Reflection coefficient after combining with port 4.
  • FIG. 9b shows the isolation between the ports of the two antenna units.
  • S(2,1) Isolation degree of port 1 and port 2
  • S(3,1) Isolation degree of port 1 and port 3
  • S(4,1) Isolation degree of port 1 and port 4
  • S( 3,2) isolation between port 3 and port 2
  • S(4,2) isolation between port 4 and port 2
  • S(4,3) isolation between port 4 and port 3.
  • Figure 9c shows the combined array reflection coefficient and isolation.
  • port 1 may be a port for inputting signals to the first signal input port 1011A of the first antenna unit 001 and the first signal input port 1011B of the second antenna unit 002
  • port 2 may be a port for inputting signals to the first signal input port 1011A of the first antenna unit 001
  • the signal input port 1021A and the second signal input port 1021B of the second antenna unit 002 are ports to which signals are input.
  • S11 is the reflection coefficient of port 1
  • S22 is the reflection coefficient of port 2.
  • S12 and S21 are the isolation degree between port 1 and port 2, wherein the isolation degree between port 2 and port 4 is equal to the isolation degree between port 3 and port 4.
  • the bandwidth of the antenna unit and the array completely covers the N77-N79 (3.3GHz-5GHz) frequency band, and the isolation between the ports is greater than 15dB.
  • FIG. 10 is a graph showing the gain parameters of the antenna array according to the embodiment of the present application in the range of 3.3 GHz to 5 GHz.
  • the antenna gain refers to the ratio of the power density of the signal generated by the actual antenna and the ideal radiating element at the same point in space under the condition of equal input power.
  • Antenna gain can quantitatively describe the degree to which an antenna concentrates and radiates input power.
  • the antenna gain is closely related to the antenna pattern. The narrower the main lobe and the smaller the side lobe of the pattern, the higher the gain.
  • the gains G(1), G(2), G(3), and G(4) of the antenna unit in this application are peaks at point A, and the gain is about 9dBi.
  • FIG. 11 is a graph showing the efficiency parameters of the antenna array according to the embodiment of the present application in the range of 3.3 GHz to 5 GHz.
  • the efficiency of the antenna system refers to the ratio of the power radiated by the antenna to the space (that is, the power that effectively converts the electromagnetic wave part) to the input power of the antenna.
  • Fig. 11 shows the variation curve of the antenna system efficiency with frequency for port 1, port 2, port 3, port 4, and the combination of port 1 and port 3, and the combination of port 2 and port 4, which are respectively expressed as: T(1), T(2), T(3), T(4), T(1,3), T(1,3).
  • Antenna radiation efficiency refers to the ratio of the power radiated by the antenna to the space (that is, the power that effectively converts the electromagnetic wave part) to the active power input to the antenna.
  • the active power input to the antenna the input power of the antenna - return loss.
  • Fig. 11 also shows the variation curve of the antenna system efficiency with frequency for port 1, port 2, port 3, port 4, and the combination of port 1 and port 3, and the combination of port 2 and port 4, respectively: R (1), R(2), R(3), R(4), R(1,3), R(2,4).
  • the radiation efficiency of the antenna is between -1dB and -2dB.
  • An embodiment of the present application further provides an electronic device, such as a communication device.
  • the communication device 0001 includes, for example, the above-mentioned antenna unit or antenna array 02 .
  • the communication device 0001 provided in this embodiment of the present application includes but is not limited to communication devices such as an outdoor CPE, a cellular base station, and a wireless local area network (WLAN).
  • communication devices such as an outdoor CPE, a cellular base station, and a wireless local area network (WLAN).
  • WLAN wireless local area network
  • the communication device further includes a device body 03 and a radio frequency module 04 .
  • Both the antenna array 02 and the radio frequency module 04 are assembled on the device body 03 .
  • the radio frequency module 04 is electrically connected to the antenna array 02 for receiving and sending electromagnetic signals to the antenna array 02 through the feeding point 1001 .
  • the antenna array 02 radiates electromagnetic waves according to the received electromagnetic signals or sends electromagnetic signals to the radio frequency module 04 according to the received electromagnetic waves, so as to realize the transmission and reception of wireless signals.
  • the radio frequency module (Radio Frequency module, AF module) 04 is a transceiver (transmitter and/or receiver, T/R) and other circuits that can transmit and/or receive radio frequency signals.

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Abstract

本申请实施例公开了一种天线单元、天线阵列及电子设备，该天线单元包括：包括：介质板，该介质板包括相对的第一表面和第二表面，该介质板的第一表面上设有微带线，该介质板的第二表面上设有金属层，该金属层上设有缝隙，其中，该微带线在该金属层上的投影与该缝隙相交，且该微带线用于向该缝隙耦合馈电。

Description

天线单元、天线阵列及电子设备
本申请要求于2020年8月25日提交到国家知识产权局、申请号为202010865514.9，发明名称为“天线单元、天线阵列及电子设备”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请实施例涉及天线技术领域，尤其涉及一种天线单元、天线阵列及电子设备。
背景技术
客户前置设备(Customer Premise Equipment，也称为无线CPE)，是一种接收移动信号并以电磁信号转发出来的移动信号接入设备。室外型无线CPE，通常会安装在一些人口密度相对较低的偏远地区，可以采用定向高增益天线单元朝向基站增加信号强度，能够更好地保证偏远地区的通信体验。
目前，无线CPE中通常采用偶极子天线单元。
其中，偶极子天线的天线单元与反射板之间距离大，因此剖面尺寸较大，集成难度高。同时需要设置巴伦馈电结构，工艺复杂，成本较高。
发明内容
本申请实施例提供一种天线单元、天线阵列及电子设备，解决了天线尺寸大，集成难度高的问题。
为达到上述目的，本申请采用如下技术方案：第一方面，提供一种天线单元，包括：介质板，该介质板包括相对的第一表面和第二表面，该介质板的第一表面上设有微带线，该介质板的第二表面上设有金属层，该金属层上设有缝隙，该缝隙与该微带线相对设置，其中，该微带线用于向该缝隙耦合馈电。由此，该天线单元采用单板结构，剖面尺寸小，走线简单，工艺复杂度低，降低了生产成本。
一种可选的实现方式中，该介质板的第一表面上还设有第一信号输入端口和第二信号输入端口，该微带线包括第一微带线和第二微带线，该第一微带线与第一信号输入端口连接，该第二微带线与该第二信号输入端口连接，该缝隙包括与该第一微带线相对的第一缝隙和第二缝隙，该第一缝隙和该第二缝隙分离设置，该第一微带线用于对该第一缝隙馈电，该第二微带线用于对该第二缝隙馈电，使得第一缝隙和第二缝隙的极化方向相互正交。由此，可以通过第一信号输入端口和第二信号输入端口分别向第一微带线和第二微带线输入极化方向相互正交的信号，提高了天线的极化性能。
一种可选的实现方式中，所述第一微带线在所述金属层上的投影和所述第一缝隙在其相交处垂直；所述第二微带在所述金属层上的投影和所述第二缝隙线在其相交处垂直。由此，该第一微带线能够将能量传递至第一缝隙，以及使得该第二微带线将能量传递至第二缝隙。
一种可选的实现方式中，该第一缝隙和该第二缝隙呈十字形交叉设置。由此，将第一缝隙和第二缝隙设置成十字交叉的形状，能够减小缝隙的长度和宽度，实现天线单元水平面尺寸的小型化，从而适用于对天线单元集成度较高的场景。
一种可选的实现方式中，该第一缝隙和该第二缝隙的长度l均为：
Figure PCTCN2021110352-appb-000001
其中，λ为无 线波的波长。由此，缝隙长度约等于无线波的波长的二分之一，在缝隙的长度与半波长相当时，辐射性能更佳。
一种可选的实现方式中，该第一缝隙和该第二缝隙的形状包括以下中的任一种：直线形、曲线形、折线形。
一种可选的实现方式中，所述第一缝隙和所述第二缝隙交叉，且所述第一缝隙和所述第二缝隙在交叉处垂直。由此，第一缝隙和第二缝隙在交叉处垂直，使得第一缝隙和第二缝隙的极化方向相互正交，实现了双极化。
一种可选的实现方式中，所述第一缝隙和所述第二缝隙关于轴线呈对称的十字交叉图案。由此，将第一缝隙和第二缝隙关于轴线对称设置，可以减小天线单元的体积。
一种可选的实现方式中，所述金属层上还设有多个第三缝隙，所述第三缝隙与所述第一缝隙或所述第二缝隙垂直，所述多个第三缝隙中的至少两个第三缝隙关于一经过十字交叉点的直线对称。由此，通过设置第三缝隙，能够减小该第一缝隙和该第二缝隙的长度和宽度，更节省空间。
一种可选的实现方式中，所述第一缝隙和所述第二缝隙关于交叉点呈对称的十字交叉图案。由此，将第一缝隙和第二缝隙关于交叉点对称设置，可以减小天线单元的体积。
一种可选的实现方式中，所述金属层上还设有多个第三缝隙，所述第三缝隙与所述第一缝隙或所述第二缝隙垂直，且关于所述交叉点中心对称。由此，通过设置第三缝隙，能够减小该第一缝隙和该第二缝隙的长度和宽度，更节省空间。
一种可选的实现方式中，该第一微带线和该第二微带线为“U”形结构，其中，该第一微带线的“丨”边的延伸方向为该第一微带线的延伸方向，该第二微带线的“丨”的延伸方向为该第一微带线的延伸方向，且该第一微带线的一条“丨”边与该第二微带线的一条“丨”边呈十字形交叉设置。由此，第一微带线和第二微带线采用“U”形结构，更节省空间。
一种可选的实现方式中，该第一微带线包括第一子微带线和第二子微带线，该金属层上设有开口，该第一子微带线设置在该介质板的第二表面上，并位于该开口中，其中，该第一子微带线和该第二子微带线平行设置且二者沿该第一微带线的“丨”边交替连接，其中，该第一子微带线在该介质板的第一表面上的投影与该第二微带线的“丨”边交叉。由此，将交叉位置的第一微带线和第二微带线异层设置，避免第一微带线和第二微带线传输的信号相互干扰。
一种可选的实现方式中，该介质板为PCB基板，该介质板的形状为矩形、圆形、三角形或其他的规则形状。上述任一种可能的实现方式对于任一种形状、材质和结构的介质板均可实现上述对应的可能的实现方式所要达到的效果。由此，介质板的形状选择更灵活，可以根据产品形态调整介质板的形状，应用范围更广。
本申请的第二方面，提供一种电子设备，包括设备主体、射频模块和如上所述的天线单元，所述天线单元和所述射频模块设置在所述设备主体内，所述射频模块用于向所述天线单元发送电磁信号，所述天线单元根据接收的电磁信号辐射电磁波。由此，电子设备采用上述天线单元，尺寸更小、结构简单，有利于产品小型化和降低成本。
一种可选的实现方式中，所述电子设备包括客户前置设备CPE。
本申请的第三方面，提供一种天线阵列，该天线阵列包括至少两个如上所述的天线单元，以及反射板；其中，每一个该天线单元耦合至该反射板，所述天线单元设置在所述反射板一侧，所述介质板的第二表面靠近所述反射板，所述介质板的第一表面背离所述反射板。由此，天线阵列采用上述天线单元，尺寸更小、结构简单，有利于产品小型化和降低成本。
一种可选的实现方式中，该金属层与该反射板之间的距离小于预设值，该金属层的边缘与该反射板形成第四缝隙，该微带线与该第四缝隙耦合。由此，进一步提高了天线的辐射性能。
一种可选的实现方式中，该至少两个天线单元的第一信号输入端口连接，且该至少两个天线单元的第二信号输入端口连接。由此，将多个天线单元的第一信号输入端口合路，并将多个天线单元的第二信号输入端口合路，便于控制天线的工作模式。
本申请的第四方面，提供一种电子设备，包括设备主体、射频模块和如上所述的天线阵列，所述天线阵列和所述射频模块设置在所述设备主体内，所述射频模块用于向所述天线阵列发送电磁信号，所述天线阵列根据接收的电磁信号辐射电磁波。由此，电子设备采用上述天线阵列，尺寸更小、结构简单，有利于产品小型化和降低成本。
一种可选的实现方式中，所述电子设备包括客户前置设备CPE。
附图说明
图1a为本申请实施例提供的天线单元的结构示意图；
图1b为图1a中的A-A剖视图；
图2为本申请实施例提供的一种天线单元的仰视图；
图2a为本申请实施例提供的另一种天线单元的仰视图；
图2b为本申请实施例提供的另一种天线单元的仰视图；
图2c为本申请实施例提供的另一种天线单元的仰视图；
图2d为本申请实施例提供的另一种天线单元的仰视图；
图3为本申请实施例提供的另一种天线单元的仰视图；
图3a为本申请实施例提供的另一种天线单元的仰视图；
图3b为本申请实施例提供的另一种天线单元的仰视图；
图4a为本申请实施例提供的一种天线单元的俯视图；
图4b为本申请实施例提供的另一种天线单元的俯视图；
图5a为本申请实施例提供的一种天线单元的投影示意图；
图5b为本申请实施例提供的一种天线单元的投影示意图；
图6a为本申请实施例提供的一种天线阵列的俯视图；
图6b为本申请实施例提供的一种天线阵列的结构示意图；
图7为本申请实施例提供的天线阵列的3D辐射方向图；
图8为本申请实施例提供的天线阵列的2D辐射方向图；
图9a-图9c为本申请实施例天线阵列在3.3GHz～5GHz的S参数曲线图；
图10为本申请实施例天线阵列在3.3GHz～5GHz的增益参数曲线图；
图11为本申请实施例天线阵列在3.3GHz～5GHz的效率参数曲线图；
图12为本申请实施例提供的电子设备的结构示意图。
具体实施方式
为了使本申请的目的、技术方案和优点更加清楚，下面将结合附图对本申请作进一步地详细描述。
以下，术语“第一”、“第二”等仅用于描述目的，而不能理解为指示或暗示相对重要性或者隐含指明所指示的技术特征的数量。由此，限定有“第一”、“第二”等的特征可以明示或者隐含地包括一个或者更多个该特征。在本申请的描述中，除非另有说明，“多个”的含义是两个或两个以上。
此外，本申请中，“上”、“下”等方位术语是相对于附图中的部件示意置放的方位来定义的，应当理解到，这些方向性术语是相对的概念，它们用于相对于的描述和澄清，其可以根据附图中部件所放置的方位的变化而相应地发生变化。
以下，对本申请实施例可能出现的术语进行解释。
耦合：指两个或两个以上的电路元件或电网络的输入与输出之间存在紧密配合与相互影响，并通过相互作用从一侧向另一侧传输能量的现象。
天线方向图：也称辐射方向图。是指在离天线一定距离处，天线辐射场的相对场强(归一化模值)随方向变化的图形，通常采用通过天线最大辐射方向上的两个相互垂直的平面方向图来表示。
天线方向图通常都有多个辐射波束。其中辐射强度最大的辐射波束称为主瓣，其余的辐射波束称为副瓣或旁瓣。在副瓣中，与主瓣相反方向上的副瓣也叫后瓣。
波束宽度：分为水平波束宽度和垂直波束宽度。其中，水平波束宽度是指在水平方向上，在最大辐射方向两侧，辐射功率下降3dB的两个方向的夹角；垂直波束宽度是指在垂直方向上，在最大辐射方向两侧，辐射功率下降3dB的两个方向的夹角。
天线增益：用于表征天线把输入功率集中辐射的程度。通常，天线方向图的主瓣越窄，副瓣越小，天线增益越高。
天线系统效率：指天线向空间辐射出去的功率(即有效地转换电磁波部分的功率)和天线的输入功率之比。
天线辐射效率：指天线向空间辐射出去的功率(即有效地转换电磁波部分的功率)和输入到天线的有功功率之比。其中，输入到天线的有功功率＝天线的输入功率-回波损耗；回波损耗主要包括金属的欧姆损耗和/或介质损耗。
天线回波损耗：可以理解为经过天线电路反射回天线端口的信号功率与天线端口发射功率的比值。反射回来的信号越小，说明通过天线向空间辐射出去的信号越大，天线的辐射效率越大。反射回来的信号越大，说明通过天线向空间辐射出去的信号越小，天线的辐射效率越小。
天线回波损耗可以用S11参数来表示，S11参数通常为负数。S11参数越小，表示天线回波损耗越小，天线的辐射效率越大；S11参数越大，表示天线回波损耗越大，天线的辐射效率越小。
天线隔离度：是指一个天线发射的信号与另一个天线所接收的信号功率的比值。可以用S21、S12参数表示。
首先请参见图1a，图1a是本申请实施例提供的一种天线单元的结构示意图。
如图1a所示，天线单元包括：介质板10、微带线100和金属层20。介质板10包括： 相对的第一表面a1和第二表面a2。其中，该介质板10的第一表面a1上设置有微带线100，该介质板10的第二表面a2上设置有金属层20，该金属层20上设有缝隙200，该缝隙200与该微带线100相对设置，且该微带线100在金属层20上的垂直投影与该缝隙200相交，其中，该微带线100用于向该缝隙200耦合馈电。
本申请实施例对介质板10的结构不做限制，在本申请一些实施例中，该介质板10为PCB基板，该介质板10的形状可以为矩形、圆形、三角形或其他的规则形状。金属层20的材料为金属铜，即金属层20为设于介质板10的第一表面a1上的铜层。
一种实施方式中，金属层20印刷于介质板10的第一表面a1上。在其他实施例中，所述介质板10也可以为其他具有承载作用的基板，所述第一功能层的材料也可以为其他导体，本申请对此不作具体限定。
该微带线100例如可以和信号输入端口连接，从而可以从信号输入端口接收射频信号，并能够将该射频信号传递至金属层20的缝隙200位置，使得该缝隙200上激励有射频电磁场，并向空间辐射电磁波。其中，该微带线100例如可以是通过印刷的方式设置在该介质板10的第一表面a1上。
其中，该天线单元例如为定向天线，其中，该天线单元例如靠近反射板设置，该介质板10的第一表面a1远离该反射板设置，该介质板10的第二表面a2靠近该反射板设置。
该天线单元例如包括正面和背面。其中该天线单元设有微带线100的一面例如为正面，该天线单元设有该金属层20的一面例如为背面。
工作时，上述缝隙朝着背面方向向反射板辐射电磁波，电磁波到达反射板时，在反射板的作用下，电磁波的辐射方向发生改变，使得电磁波朝着正面方向辐射，形成定向波束，达到定向高增益的效果。
该天线单元例如可以为双极化天线单元，该介质板10上例如设有两个信号输入端口：第一信号输入端口1011和第二信号输入端口1021，该第一信号输入端口1011可以向微带线100输入第一极化信号，该第二信号输入端口1021例如可以向微带线100输入第二极化信号。其中，第一极化信号和第二极化信号的极化方向正交，即第一极化信号和第二极化信号振幅相等且相差90°。
需要说明的是，该双极化天线单元可以采用±45°的双极化模式，也可以采用垂直/水平双极化模式，本申请对此不做限制，这些均属于本申请的保护范围。
该微带线100例如包括第一微带线101和第二微带线102，第一微带线101的第一位置与该第一信号输入端口1011连接，并具有至少一个自由端，该第二微带线102的第二位置与第二信号输入端口1021连接，并具有至少一个自由端。
此外，金属层20上例如设有第一接地端口203和第二接地端口204。该天线单元例如和射频输入端连接，其中，该射频输入端可以包括：信号线和地线，其中，射频输入端的信号线可以分别和第一信号输入端口1011、第二信号输入端口1021连接，射频输入端的地线分别和金属层20上的第一接地端口203和第二接地端口204连接。
本申请实施例对缝隙200的具体形状不做限制。可以将设置在金属层20上的缝隙200分为第一缝隙201和第二缝隙202。其中，第一缝隙201和第二缝隙202交叉，且第一缝隙201和第二缝隙202在交叉处垂直。由此，第一缝隙和第二缝隙在交叉处垂直，使得第一缝隙和第二缝隙的极化方向相互正交，实现了双极化。
本申请实施例对该第一缝隙201和第二缝隙202的相对位置不做限制，其中，如图2所示，第一缝隙201和第二缝隙202可以不对称，或者如图2a、图2b所示，第一缝隙201和第二缝隙202可以关于一穿过第一缝隙201和第二缝隙202的交叉点的直线O对称，或者如图3所示，第一缝隙201和第二缝隙202可以关于第一缝隙201和第二缝隙202的交叉点O’中心对称。
本申请实施例对该第一缝隙201和第二缝隙202的形状不做限制。在本申请一些实施例中，如图2a、图2b、图3所示，该第一缝隙201和第二缝隙202为矩形，例如具有圆角的矩形，在本申请另一些实施例中，该第一缝隙201和第二缝隙202还可以曲线形、折线形。
本申请实施例对该第一缝隙201和第二缝隙202的长度不做限制，在本申请一些实施例中，第一缝隙201和第二缝隙202的长度l均为：
Figure PCTCN2021110352-appb-000002
其中，λ为无线波的波长。由此，缝隙长度约等于无线波的波长的二分之一，在缝隙的长度与半波长相当时，辐射性能更佳。
其中，第一缝隙201和第二缝隙202的长度l如图2a、图2b、图3所示，为第一缝隙201和第二缝隙202的长边长度。
在本申请的一些实施例中，如图2所示，第一缝隙201和第二缝隙202呈十字交叉图案，第一缝隙201和第二缝隙202不对称。
在本申请的一些实施例中，第一缝隙201和第二缝隙202关于一经过第一缝隙201和第二缝隙202的交叉点的直线对称。
如图2a、图2b所示，第一缝隙201和第二缝隙202关于轴线O呈对称的十字交叉图案。
如图2c、图2d所示，所述金属层20上还设有多个第三缝隙206，所述第三缝隙206与所述第一缝隙201或所述第二缝隙202垂直，所述多个第三缝隙206中的至少两个第三缝隙206关于上述经过第一缝隙201和第二缝隙202的交叉点的直线对称。由此，通过设置第三缝隙，能够减小该第一缝隙和该第二缝隙的长度和宽度，更节省空间。
本申请实施例对该第三缝隙206的数量和具体结构不做限制，在本申请的一些实施例中，如图2c、图2d所示，第三缝隙206为四个，分别和第一缝隙201和第二缝隙202垂直，且四个第三缝隙206关于轴线O对称设置。
本申请实施例对第三缝隙206的形状不做限制。在本申请一些实施例中，如图2c、图2d所示，该第三缝隙206为矩形，例如具有圆角的矩形，在本申请另一些实施例中，该第三缝隙206还可以采用曲线形、折线形结构。
由此，通过在金属层20上设置第三缝隙206，在保持第一缝隙201和第二缝隙202的电长度不变的情况下，可以进一步减小第一缝隙201和第二缝隙202的物理长度和宽度，减小天线单元的水平面尺寸。
本申请实施例对该第三缝隙206的位置不做限制，在本申请一些实施例中，如图2c、图2d所示，第一缝隙201和第二缝隙202组成十字形结构，第三缝隙206分别设置在该十字形的四条边的中间位置。
在本申请的另一些实施例中，如图3所示，第一缝隙201和第二缝隙202关于第一缝隙201和第二缝隙202的交叉点O’中心对称。由此，将第一缝隙201和第二缝隙202交叉设置，还可以进一步减小该天线单元的水平面尺寸，有利于天线单元的小型 化。
其中，第一缝隙201和第二缝隙202关于交叉点O’呈对称的十字交叉图案。
如图3a、图3b所示，所述金属层20上还设有多个第三缝隙206，所述第三缝隙206与所述第一缝隙201或所述第二缝隙202垂直，所述多个第三缝隙206中的至少两个第三缝隙206关于第一缝隙201和第二缝隙202的交叉点O’中心对称。
本申请实施例对该第三缝隙206的数量和具体结构不做限制，在本申请的一些实施例中，如图3a、图3b所示，第三缝隙206为四个，分别和第一缝隙201和第二缝隙202垂直，且四个第三缝隙206关于该十字形交叉的第一缝隙201和第二缝隙202的交叉点O’对称设置。
本申请实施例对第三缝隙206的形状不做限制。在本申请一些实施例中，如图3a、图3b所示，该第三缝隙206为矩形，例如具有圆角的矩形，在本申请另一些实施例中，该第三缝隙206还可以采用曲线形、折线形结构。
由此，通过在金属层20上设置第三缝隙206，在保持第一缝隙201和第二缝隙202的电长度不变的情况下，可以进一步减小第一缝隙201和第二缝隙202的物理长度和宽度，减小天线单元的水平面尺寸。
本申请实施例对该第三缝隙206的位置不做限制，在本申请一些实施例中，如图3a所示，第一缝隙201和第二缝隙202组成十字形结构，第三缝隙206分别设置在该十字形的四条边的中间位置。
在本申请其他的一些实施例中，如图3b所示，第三缝隙206分别设置在第一缝隙201和第二缝隙202的两端，该第三缝隙206分别和第一缝隙201、第二缝隙202组成“工”字形结构。
本申请实施例对该第一微带线101和第二微带线102的相对位置不做限制，在本申请的一些实施例中，如图4a、图4b所示，该第一微带线101的至少一条“丨”边与该第二微带线102的至少一条“丨”边呈十字形交叉设置。由此，将第一微带线101和第二微带线102交叉设置，还可以进一步减小该天线单元的水平面尺寸，有利于天线单元的小型化。其中，该第一微带线101和该第二微带线102传输的信号极化方向正交，且第一微带线101和第二微带线102的设置方式也正交，提高了天线单元的隔离度。此外，将第一微带线101和第二微带线102交叉设置，还可以进一步减小该天线单元的水平面尺寸，有利于天线单元的小型化。
如图4a、图4b所示，该第一微带线101包括：第一边1012、第二边1013以及第三边1014，第一边1012、第二边1013以及第三边1014共同组成“U”形结构。
该第二微带线102包括：第四边1022、第五边1023以及第六边1024，第四边1022、第五边1023以及第六边1024共同组成“U”形结构。
其中，如图4a所示，第一微带线101的第二边1013和第二微带线102的第五边1023正交设置。
如图4b所示，第一微带线101的第二边1013分别和第二微带线102的第五边1023、第二微带线102的第四边1022正交设置，且第一微带线101的第一边1012分别和第二微带线102的第四边1022、第二微带线102的第五边1023正交设置。
其中，为了避免正交设置的第一微带线101和第二微带线102相干扰，在本申请 的一些实施例中，可以将第一微带线101与第二微带线102相交叉的部分跳线至介质板的第二表面，以避让第二微带线102。
在一种可能的实施例中，如图1a、图4a所示，其中，第一微带线101的第二边1013和第二微带线102的第五边1023正交设置，为了避免正交设置的第二边1013和第五边1023相干扰，在本申请的一些实施例中，可以将第二边1013的交叉部分跳线至介质板的第二表面，以避让第五边1023。当然，在本申请另一些实施例中，也可以将第五边1023的交叉部分跳线至介质板的第二表面，以避让第二边1013。这些均属于本申请的保护范围。
在本申请的一些实施例中，如图1b(沿图1a中A-A向的剖视图)所示，第一微带线101的包括至少一条第一子微带线103和至少一条第二子微带线104。
下面，对第一子微带线103、第二子微带线104以及第二微带线102三者的位置关系进行说明。
第一子微带线103与第二子微带线104平行设置，也就是说，第一子微带线103与第二子微带线104错位排布，二者不在同一延伸线上。
第一子微带线103与第二子微带线104沿第一微带线101的延伸方向交替连接。
在第一种可能的实施例中：
如图1b所示，第二子微带线104与第一子微带线103异层设置，第一子微带线103与第二微带线102同层设置。
也就是说，第一微带线101中的第一子微带线103和第二微带线102同层设置，第一微带线101中的第二子微带线104跳线至介质板20的第二表面，以避免与第二微带线102短路。
此外，由于介质板10的第二表面a2上设有金属层20，为避免第二子微带线104与金属层20短路，可以在金属层20上设置开口205，并将第二子微带线104设置于该开口205内。
如图1b所示，为了避免相邻层之间的微带线发生短路，相邻层微带线分别设置在介质板的第一表面和第二表面上。本申请不对介质板的材料进行限定，能起到绝缘作用的材料都可以适用于介质板20。
其中，不对第一子微带线103与第二子微带线104的连接方式进行限定，例如，如图1b所示，第一微带线101还包括连接部105，在第一子微带线103和第二子微带线104不同层的情况下，第一子微带线103与第二子微带线104通过连接部105连接。
需要说明的是，连接部105可以采用过孔，其中，过孔也称金属化孔，为连通第一子微带线103与第二子微带线104，在需要连通的第一子微带线103与第二子微带线104在介质板10的交汇处钻上一个公共孔，即过孔。其中，过孔的孔壁圆柱面上可以，例如采用化学沉积的方法，镀上一层金属，用以连通第一子微带线103与第二子微带线104。
由此，该第一微带线101和该第二微带线102传输的信号极化方向正交，且第一微带线101和第二微带线102的设置方式也正交，提高了天线单元的隔离度。
此外，通过将第二子微带线104跳线至介质板的第二表面，以避让第二微带线102，并通过连接部105连接第一子微带线103和第二子微带线104，可以在第一微带线101 和第二微带线102互不干扰的情况下，将第一微带线和第二微带线正交设置，减小了对水平面空间的占用，有利于设备的小型化。
上述实施例中仅以将第一微带线101的部分跳线至其他层为例，在本申请另一些实施例中，也可以将第二微带线102与第一微带线101相交叉的部分跳线至其它层，这些均属于本申请的保护范围。
在本申请的另一些实施例中，如图4b所示，第一微带线101的第二边1013分别和第二微带线102的第五边1023、第二微带线102的第四边1022正交设置，且第一微带线101的第一边1012分别和第二微带线102的第四边1022、第二微带线102的第五边1023正交设置，为了避免正交设置的第二边1013和第五边1023、第二边1013和第四边1022、第一边1012和第五边1023、以及第一边1012和第四边1022相干扰，在本申请的一些实施例中，可以将第二边1013上和第五边1023相交叉的部分、第二边1013上和第四边1022相交叉的部分均跳线至介质板的第二表面，以避让第五边1023和第四边1022，并将第一边1012上和第五边1023相交叉的部分、第一边1012上和第四边1022相交叉的部分均跳线至介质板的第二表面，以避让第五边1023和第四边1022。当然，也可以将第五边1023上和第一边1012、第五边1023上和第二边1013相交叉的部分跳线至介质板的第二表面，以避让第一边1012和第二边1013，同时将第四边1022上和第一边1012、第四边1022上和第二边1013相交叉的部分跳线至介质板的第二表面，以避让第一边1012和第二边1013。这些均属于本申请的保护范围。
其中，该第一缝隙201和该第一微带线101相对设置，该第二缝隙202和该第二微带线102相对设置，该第一微带线101用于对该第一缝隙201馈电，该第二微带线102用于对该第二缝隙202馈电。
在本申请一些实施例中，该第一微带线101在该金属层20上的投影和第一缝隙201在其相交处垂直。该第二微带线102在该金属层20上的投影与第二缝隙202在其相交处垂直。
本申请实施例对该第一微带线101和该第二微带线102的具体结构不做限制。在本申请的一些实施例中，该第一微带线101和该第二微带线102例如为“U”形，该第一微带线101和该第二微带线102分别通过“U”的“丨”部对设置在金属层20上的缝隙200进行馈电。
上述第一缝隙201与该第一微带线101相对设置，指的是该第一微带线101在该金属层20上的垂直投影与该第一缝隙201相交，上述该第二缝隙202与该第二微带线102相对设置，指的是该第二微带线102在该金属层20上的垂直投影与该第二缝隙202相交。
如图5a、图5b所示，该第一微带线101的至少一个“丨”部在该金属层20上的第一投影1010与第一缝隙201交叉，且垂直于该第一缝隙201的延伸方向。
该第二微带线102的至少一个“丨”部在该金属层20上的第二投影1020与第二缝隙202交叉，且垂直于该第二缝隙202的延伸方向。
图5a中，第一微带线101的两个“丨”部在该金属层20上的第一投影1010均与第一缝隙201交叉，且垂直于该第一缝隙201的延伸方向。
且第二微带线102的两个“丨”部在该金属层20上的第二投影1020与第二缝隙202交叉，且垂直于该第二缝隙202的延伸方向。由此，第一微带线101通过“U”的两个“丨” 部对第一缝隙201进行馈电，第二微带线102通过“U”的两个“丨”部对第二缝隙202进行馈电，提高了耦合性能。
图5b中，第一微带线101的1个“丨”部在该金属层20上的第一投影1010均与第一缝隙201交叉，且垂直于该第一缝隙201的延伸方向。
且第二微带线102的1个“丨”部在该金属层20上的第二投影1020与第二缝隙202交叉，且垂直于该第二缝隙202的延伸方向。由此，可以仅通过“U”形结构的1个“丨”边对缝隙进行馈电。
本申请实施例中，可以通过微带线中“U”的两个“丨”边分别对第一缝隙201和第二缝隙202进行馈电，也可以仅通过微带线中“U”的1个“丨”边分别对第一缝隙201和第二缝隙202进行馈电，这些均属于本申请的保护范围。
此外，为使得通过该第一微带线101和该第二微带线102的射频能量分别均匀传递至该第一缝隙201和该第二缝隙202，可以将该第一缝隙201沿该第一微带线101对称设置，以及将该第二缝隙202沿该第二微带线102对称设置。
具体设置时，可使得该第一微带线101的“丨”部在该金属层20上的第一投影1010的延伸方向垂直于该第一缝隙201的延伸方向，且该第一缝隙201沿该第一投影1010的延伸方向对称设置。并使得该第二微带线102的“丨”部在该金属层20上的第二投影1020的延伸方向垂直于该第二缝隙202的延伸方向，且该第二缝隙202沿该第二投影1020的延伸方向对称设置。
本申请实施例提供的天线单元，将第一缝隙201沿第一投影1010对称设置，并将第二缝隙202沿第二投影1020对称设置，有利于将该射频能量分别通过第一微带线101和该第二微带线102均匀向缝隙200中传递，避免由射频能量传递不均引起的阻抗失配。
本申请还提供一种天线阵列，该天线阵列包括至少两个如上所述的天线单元，以及反射板；其中，每一个该天线单元耦合至该反射板。
本申请实施例对该天线阵列的具体结构不做限制。在本申请的一些实施例中，如图6a、图6b所示，该天线阵列包括反射板01，以及位于反射板01一侧的第一天线单元001和第二天线单元002。
其中，该第一天线单元001和第二天线单元002的金属层20的各边沿还可以与该反射板形成第四缝隙010，该微带线100还用于对该第四缝隙耦合馈电，在微带线100的激励下，第四缝隙也会产生辐射。
其中，第一天线单元001和第二天线单元002包括：设置在反射板一侧的介质板10，该介质板10靠近反射板01的表面设置有金属层20。
其中，介质板10和金属层20的总厚度约为1mm，介质板10和金属层20的平面尺寸为30x30mm，该天线单元与反射板之间的距离约为9mm，该天线单元例如工作在5G N77～N79(3.3GHz～5GHz)频段。
该天线阵列的平面尺寸为30x80mm，剖面高度为10mm，其中，第一天线单元001的第一信号输入端口1011A和第二天线单元002的第一信号输入端口1011B合路，第一天线单元001的第二信号输入端口1021A和第二天线单元002的第二信号输入端口1021B合路。
其中，以第一天线单元001的第一信号输入端口1011A和第二天线单元002的第一信号输入端口1011B的作为第一合路，以第一天线单元001的第二信号输入端口1021A和第 二天线单元002的第二信号输入端口1021B为第二合路。
图7中的(a)为该天线阵列的第一合路接通，第二合路匹配时，在3.3GHz的3D辐射方向图。需要说明的是，合路接通指的是合路中有信号传输，合路匹配指的是合路中没有信号传输。图7中的(b)为该天线阵列的第一合路接通，第二合路匹配时，在4.2GHz的3D辐射方向图。图7中的(c)为该天线阵列的第一合路接通，第二合路匹配时，在5GHz的3D辐射方向图。图7中的(d)为该天线阵列的第二合路接通，第一合路匹配时，在3.3GHz的3D辐射方向图。图7中的(e)为该天线阵列的第二合路接通，第一合路匹配时，在4.2GHz的3D辐射方向图。图7中的(f)为该天线阵列的第二合路接通，第一合路匹配时，在5GHz时的3D辐射方向图。
如图7中的(a)-(f)所示，该天线阵列中的第一合路和第二合路在3.3GHz、4.2GHz以及5GHz的3D方向图中的主瓣波束稳定，且第一合路接通，第二合路匹配时，天线的方向图在XOY平面的投影朝向+45°，当第二合路接通，第一合路匹配时，天线的方向图在XOY平面的投影朝向-45°，实现了双极化。
图8中的(a)为该天线阵列的第一合路接通，第二合路匹配时，在3.3GHz时的水平面辐射方向图。
如图8中的(a)所示，天线阵列在3.3GHz时，水平面的半功率波束宽度(Half-power beamwidth，HPBW)为61.1°。
图8中的(b)为该天线阵列的第一合路接通，第二合路匹配时，在4.2GHz时的水平面辐射方向图。
如图8中的(b)所示，天线阵列在4.2GHz时，水平面的半功率波束宽度为60.5°。
图8中的(c)为该天线阵列的第一合路接通，第二合路匹配时，在5GHz时的水平面辐射方向图。
如图8中的(c)所示，天线单元在5GHz时，水平面的半功率波束宽度为64.3°。
图8中的(d)为该天线阵列的第一合路接通，第二合路匹配时，在3.3GHz时的垂直面辐射方向图。
如图8中的(d)所示，天线阵列工作在3.3GHz时，垂直面的半功率波束宽度为42.3°。
图8中的(e)为该天线阵列的第一合路接通，第二合路匹配时，在4.2GHz时的垂直辐射面的方向图。
如图8中的(e)所示，天线阵列工作在4.2GHz时，垂直面的半功率波束宽度为34.8°。
图8中的(f)为该天线阵列的第一合路接通，第二合路匹配时，在5GHz时垂直辐射面的方向图。
如图8中的(f)所示，天线阵列工作在5GHz时，垂直面的半功率波束宽度为29.9°。
需要说明的是，上述天线阵列的水平辐射面为图6a中的xoz平面，上述天线阵列的垂直辐射面为图6a中的yoz平面，其中，z轴在图6a中未示出，z轴垂直于xoy平面。
如图8中的(a)-(f)所示，2D方向图显示该天线阵列水平面波束宽度约为60°，垂直面波束宽度约为30°。
其中，上述水平面波束宽度和垂直面波束宽度为半波功率宽度，也称3dB波瓣宽度， 是指方向图主瓣上两个半功率点之间的夹角，也可以是相对于最大辐射方向功率下降一半(3dB)的两点间波束宽度。
图8中的(a)-(f)中主瓣宽度较窄，方向图较尖锐，天线单元辐射能量集中，该天线阵列的定向作用强。
图9a-图9c为本申请实施例天线阵列在3.3GHz～5GHz的S参数曲线图。其中，S参数，又叫散射参数。该天线阵列共包括四个端口，将第一天线单元001的第一信号输入端口1011A作为端口1，将第一天线单元001的第二信号输入端口1021A作为端口2，将第二天线单元002的第一信号输入端口1011B作为端口3，将第二天线单元002的第二信号输入端口1021B作为端口4。
图9a为两个天线单元各端口的反射系数，也即回波损耗。图9a中点1处横坐标为3.1793GHz，纵坐标为-5.2107dB。图9a中点2处横坐标为5.1809GHz，纵坐标为-5.3097dB。其中，S(1,1)为端口1的反射系数，S(2,2)为端口2的反射系数，S(3,3)为端口3的反射系数，S(4,4)为端口4的反射系数，S1,1[1,0]+3[1,0]为端口1和端口3合路后的反射系数，S2,2[1,0]+4[1,0]为端口2和端口4合路后的反射系数。
图9b为两个天线单元各端口两两之间的隔离度。S(2,1)：端口1和端口2的隔离度，S(3,1):端口1和端口3的隔离度，S(4,1)：端口1和端口4的隔离度，S(3,2)：端口3和端口2的隔离度，S(4,2)：端口4和端口2的隔离度，S(4,3)：端口4和端口3的隔离度。
图9c所示为合路后的阵列反射系数和隔离度。其中，端口1可以是向第一天线单元001的第一信号输入端口1011A和第二天线单元002的第一信号输入端口1011B输入信号的端口，端口2可以是向第一天线单元001的第一信号输入端口1021A和第二天线单元002的第二信号输入端口1021B输入信号的端口。S11为端口1的反射系数，S22为端口2的反射系数。S12和S21为端口1和端口2之间的隔离度，其中，端口2和端口4之间的隔离度等于端口3和端口4之间的隔离度。
如图9a、图9b、图9c所示，天线单元及阵列的带宽完全覆盖N77～N79(3.3GHz～5GHz)频段范围，各端口之间的隔离度大于15dB。
图10为本申请实施例天线阵列在3.3GHz～5GHz增益参数曲线图。其中，天线增益是指：在输入功率相等的条件下，实际天线与理想的辐射单元在空间同一点处所产生的信号的功率密度之比。
天线增益可以定量地描述一个天线把输入功率集中辐射的程度。天线增益与天线方向图有密切的关系，方向图主瓣越窄，副瓣越小，增益越高。如图9a所示，本申请中天线单元的增益G(1)、G(2)、G(3)、G(4)，在A点处为峰值，增益约为9dBi，合路之后天线阵列的增益G(1,3)、G(2,4)，在B点处峰值，增益约为11dBi。
图11为本申请实施例天线阵列在3.3GHz～5GHz效率参数曲线图。
其中，天线系统效率(Tot efficiency)是指天线向空间辐射出去的功率(即有效地转换电磁波部分的功率)和天线的输入功率之比。图11中示出了端口1、端口2、端口3、端口4，以及端口1和端口3的合路、端口2和端口4的合路的天线系统效率随频率的变化曲线，分别表示为：T(1)、T(2)、T(3)、T(4)、T(1,3)、T(1,3)。
天线辐射效率(Rad efficiency)指天线向空间辐射出去的功率(即有效地转换电磁波部分的功率)和输入到天线的有功功率之比。其中，输入到天线的有功功率＝天线的输入 功率-回波损耗。图11还示出了端口1、端口2、端口3、端口4，以及端口1和端口3的合路、端口2和端口4的合路的天线系统效率随频率的变化曲线，分别为：R(1)、R(2)、R(3)、R(4)、R(1,3)、R(2,4)。
如图11所示，在3.3GHz～5GHz频段，天线辐射效率在-1dB～-2dB之间。
本申请实施例还提供一种电子设备，例如通讯设备，如图12所示，该通讯设备0001例如包括如上所述的天线单元或天线阵列02。
本申请实施例提供的通讯设备0001包括且不限于室外型CPE、蜂窝基站、无线局域网(WLAN)等通讯设备。
该通讯设备例如还包括设备主体03和射频模块04。天线阵列02和射频模块04均装配于设备主体03上。射频模块04与天线阵列02电连接，用以通过馈电点1001向天线阵列02收发电磁信号。天线阵列02根据接收的电磁信号辐射电磁波或根据接收的电磁波向射频模块04发送电磁信号，从而实现无线信号的收发。其中，射频模块(Radio Frequency module，AF module)04为收发器(transmitter and/or receiver，T/R)等可以发射和/或接收射频信号的电路。
以上所述，仅为本申请的具体实施方式，但本申请的保护范围并不局限于此，任何在本申请揭露的技术范围内的变化或替换，都应涵盖在本申请的保护范围之内。因此，本申请的保护范围应以该权利要求的保护范围为准。

Claims (21)

  1. 一种天线单元，其特征在于，所述天线单元包括：
    介质板，所述介质板包括相对的第一表面和第二表面；
    微带线，设于所述介质板的第一表面上；以及
    金属层，设于所述介质板的第二表面上，所述金属层上设有缝隙，
    其中，所述微带线在所述金属层上的投影与所述缝隙相交，所述微带线用于向所述缝隙耦合馈电。
  2. 根据权利要求1所述的天线单元，其特征在于，所述介质板的第一表面上还设有第一信号输入端口和第二信号输入端口，所述微带线包括第一微带线和第二微带线，所述第一微带线与所述第一信号输入端口连接，所述第二微带线与所述第二信号输入端口连接，所述缝隙包括第一缝隙和第二缝隙，其中，所述第一微带线在所述金属层上的投影和所述第一缝隙相交，所述第二微带线在所述金属层上的投影和所述第二缝隙相交，所述第一微带线用于对所述第一缝隙馈电，所述第二微带线用于对所述第二缝隙馈电。
  3. 根据权利要求2所述的天线单元，其特征在于，所述第一微带线在所述金属层上的投影和所述第一缝隙在其相交处垂直；
    所述第二微带线在所述金属层上的投影和所述第二缝隙在其相交处垂直。
  4. 根据权利要求2或3所述的天线单元，其特征在于，所述第一缝隙和所述第二缝隙的长度l均为：
    Figure PCTCN2021110352-appb-100001
    其中，λ为无线波的波长。
  5. 根据权利要求2-4任一项所述的天线单元，其特征在于，所述第一缝隙和所述第二缝隙交叉，且所述第一缝隙和所述第二缝隙在交叉处垂直。
  6. 根据权利要求5所述的天线单元，其特征在于，所述第一缝隙和所述第二缝隙关于一经过所述第一缝隙和所述第二缝隙的交叉点的直线对称。
  7. 根据权利要求6所述的天线单元，其特征在于，所述金属层上还设有多个第三缝隙，所述第三缝隙与所述第一缝隙或所述第二缝隙垂直，所述多个第三缝隙中的至少两个第三缝隙关于所述一经过所述第一缝隙和所述第二缝隙的交叉点的直线对称。
  8. 根据权利要求5所述的天线单元，其特征在于，所述第一缝隙和所述第二缝隙关于所述第一缝隙和所述第二缝隙的交叉点中心对称。
  9. 根据权利要求8所述的天线单元，其特征在于，所述金属层上还设有多个第三缝隙，所述第三缝隙与所述第一缝隙或所述第二缝隙垂直，且关于所述第一缝隙和所述第二缝隙的交叉点中心对称。
  10. 根据权利要求2-9任一项所述的天线单元，其特征在于，所述第一缝隙和所述第二缝隙的形状包括以下中的任一种：直线形、曲线形、折线形。
  11. 根据权利要求2-10任一项所述的天线单元，其特征在于，所述第一微带线和所述第二微带线为“U”形结构，其中，所述第一微带线的“丨”边在金属层上的投影的延伸方向垂直于所述第一缝隙的延伸方向，所述第二微带线的“丨”边在金属层上的投影的延伸方向垂直于所述第二缝隙的延伸方向，且所述第一微带线的至少一条“丨”边在金属层上的投影与所述第二微带线的至少一条“丨”边在金属层上的投影正交。
  12. 根据权利要求11所述的天线单元，其特征在于，所述第一微带线包括第一子微带线和第二子微带线，所述金属层上设有开口，所述第一子微带线设置在所述介质板的第二表面上，并位于所述开口中，所述第二子微带线设置在所述介质板的第一表面上，其中，所述第一子微带线与所述第二微带线的“丨”边在所述金属层上的投影交叉，且所述第一子微带线和所述第二子微带线沿所述第一微带线的“丨”边交替连接。
  13. 根据权利要求12所述的天线单元，其特征在于，所述第一微带线还包括：连接部，所述第一子微带线和所述第二子微带线通过所述连接部连接。
  14. 根据权利要求1-13任一项所述的天线单元，其特征在于，所述介质板为PCB基板，所述介质板的形状为矩形、圆形、三角形或其他的规则形状。
  15. 一种电子设备，其特征在于，包括设备主体、射频模块和如权利要求1-14任一项所述的天线单元，所述天线单元和所述射频模块设置在所述设备主体内，所述射频模块用于向所述天线单元发送电磁信号，所述天线单元根据接收的电磁信号辐射电磁波。
  16. 根据权利要求15所述的电子设备，其特征在于，所述电子设备为室外型客户前置设备CPE。
  17. 一种天线阵列，其特征在于，所述天线阵列包括至少两个如权利要求1-14任一项所述的天线单元，以及反射板；
    其中，所述天线单元设置在所述反射板一侧，所述介质板的第二表面靠近所述反射板，所述介质板的第一表面背离所述反射板。
  18. 根据权利要求17所述的天线阵列，其特征在于，所述金属层的边缘与所述反射板形成第四缝隙，所述微带线还用于向所述第四缝隙耦合馈电。
  19. 根据权利要求17或18所述的天线阵列，其特征在于，所述至少两个天线单元的第一信号输入端口合路，且所述至少两个天线单元的第二信号输入端口合路。
  20. 一种电子设备，其特征在于，包括设备主体、射频模块和如权利要求17-19任一项所述的天线阵列，所述天线阵列和所述射频模块设置在所述设备主体内，所述射频模块用于向所述天线阵列发送电磁信号，所述天线阵列根据接收的电磁信号辐射电磁波。
  21. 根据权利要求20所述的电子设备，其特征在于，所述电子设备为室外型客户前置设备CPE。
PCT/CN2021/110352 2020-08-25 2021-08-03 天线单元、天线阵列及电子设备 WO2022042231A1 (zh)

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