WO2022028238A1 - 功率转换系统 - Google Patents

功率转换系统 Download PDF

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Publication number
WO2022028238A1
WO2022028238A1 PCT/CN2021/107053 CN2021107053W WO2022028238A1 WO 2022028238 A1 WO2022028238 A1 WO 2022028238A1 CN 2021107053 W CN2021107053 W CN 2021107053W WO 2022028238 A1 WO2022028238 A1 WO 2022028238A1
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WO
WIPO (PCT)
Prior art keywords
power switch
switch tube
module
energy storage
diode
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Application number
PCT/CN2021/107053
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English (en)
French (fr)
Inventor
蒲波宇
甘鸿坚
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浙江鲲悟科技有限公司
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Publication of WO2022028238A1 publication Critical patent/WO2022028238A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/01—Arrangements for reducing harmonics or ripples
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
    • H02M5/40—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc
    • H02M5/42—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters
    • H02M5/44—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac
    • H02M5/453—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M5/458—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M5/4585—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases with intermediate conversion into dc by static converters using discharge tubes or semiconductor devices to convert the intermediate dc into ac using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only having a rectifier with controlled elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
    • H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
    • H02P25/022—Synchronous motors
    • H02P25/024—Synchronous motors controlled by supply frequency
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
    • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
    • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
    • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
    • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
    • H02P27/085—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation wherein the PWM mode is adapted on the running conditions of the motor, e.g. the switching frequency
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/40—Arrangements for reducing harmonics

Definitions

  • the invention relates to the field of power conversion, in particular to a power conversion system.
  • a power conversion system with a PFC (Power Factor Correction) at the front stage is used, the purpose is to reduce the low-order harmonics of the power grid, improve the power factor of the power grid, and at the same time, it can control the DC bus voltage and improve the system efficiency.
  • PFC Power Factor Correction
  • FIG 1 shows the high frequency ripple flowing from the PFC into the energy storage capacitor
  • Figure 2 shows the high frequency ripple flowing from the energy storage capacitor to the inverter IPM
  • Figure 3 shows the actual flow through the two energy storage capacitors high frequency ripple at the end.
  • the capacitor manufacturer will give the ripple current tolerance value of this capacitor in the manual.
  • the larger the capacitor value the stronger the ripple current tolerance.
  • the larger the capacitance value the corresponding increase in its volume and cost, which is very unfavorable to the improvement of the system power density and the reduction of the cost.
  • the purpose of the present invention is to provide a power conversion system for solving the problems of large energy storage capacitor, low power density and high cost in the prior art.
  • the present invention provides a power conversion system, the power conversion system at least includes:
  • a rectifier module that receives an AC input voltage and converts the AC input voltage into a DC bus voltage
  • an inverter module connected to the output end of the rectifier module, to convert the DC bus voltage into an AC output voltage
  • control module connected to the rectifier module and the inverter module, for generating control signals of the rectifier module and the inverter module;
  • the switching frequency of the power switch tube in the rectifier module is an even multiple of the switching frequency of the power switch tube in the inverter module, and the endpoints of the PWM carrier of the power switch tube in the inverter module are respectively connected to the rectifier module. The endpoints of the PWM carrier of the power switch tube in the module are aligned.
  • the rectifier module has a three-level topology.
  • the rectifier module is a VIENNA rectifier module.
  • the VIENNA rectifier module includes first, second, third, fourth, fifth and sixth diodes, first, second and third inductors, first, second and third , the fourth, fifth and sixth power switch tubes, the first group of energy storage capacitors and the second group of energy storage capacitors;
  • the cathodes of the first, third and fifth diodes are connected together, the anode of the first diode is connected to the cathode of the second diode and the AC input is connected via the first inductor
  • the first phase of the voltage the anode of the third diode is connected to the cathode of the fourth diode and the second phase of the AC input voltage is connected via the second inductor
  • the fifth diode The anode of the diode is connected to the cathode of the sixth diode and the third phase of the AC input voltage is connected via the third inductor, and the anodes of the second, fourth and sixth diodes are connected together;
  • the first group of energy storage capacitors and the second group of energy storage capacitors are connected in series with the cathodes of the first, third and fifth diodes and the cathodes of the second, fourth and sixth diodes. between anodes;
  • the first end of the first power switch tube is connected to the connection node of the first diode and the second diode, and the second end is connected to the first end of the second power switch tube;
  • the first end of the three power switch tube is connected to the connection node of the third diode and the fourth diode, and the second end is connected to the first end of the fourth power switch tube;
  • the fifth power switch The first end of the tube is connected to the connection node of the fifth diode and the sixth diode, and the second end is connected to the first end of the sixth power switch tube;
  • each power switch tube is an insulated gate bipolar transistor.
  • the first group of energy storage capacitors and the second group of energy storage capacitors have the same capacitance and ripple voltage.
  • both the first group of energy storage capacitors and the second group of energy storage capacitors include a single capacitor or a combination of multiple capacitors in series and parallel.
  • the inverter module has a two-level topology.
  • the inverter module includes seventh, eighth, ninth, tenth, eleventh and twelfth power switch tubes;
  • the first end of the seventh, ninth, and eleventh power switch tubes is connected to the positive pole of the DC bus voltage, and the second end of the seventh power switch tube is connected to the first end of the eighth power switch tube. terminal and output the first AC output voltage, the second terminal of the ninth power switch tube is connected to the first terminal of the tenth power switch tube and outputs the second AC output voltage, the first terminal of the eleventh power switch tube.
  • the two ends are connected to the first end of the twelfth power switch tube and output a third AC output voltage, and the second ends of the eighth, tenth and twelfth power switch tubes are connected to the negative pole of the DC bus voltage ;
  • the control terminals of the seventh, eighth, ninth, tenth, eleventh and twelfth power switch tubes are respectively connected to the control module.
  • each power switch tube is an insulated gate bipolar transistor.
  • the power conversion system of the present invention has the following beneficial effects:
  • the power conversion system of the present invention adopts the topology structure of the front-stage rectification and the latter-stage inversion, which can greatly reduce the high-frequency ripple current at both ends of the DC bus energy storage capacitor, reduce the loss of the energy storage capacitor, and thus can greatly reduce the direct current The capacity of the bus energy storage capacitor, thereby reducing the volume and cost of the energy storage capacitor, and improving the power density and reliability of the system.
  • FIG. 1 is a schematic diagram showing the high frequency ripple flowing from the PFC into the storage capacitor in the prior art.
  • FIG. 2 shows a schematic diagram of the high frequency ripple flowing from the storage capacitor to the inverter IPM in the prior art.
  • FIG. 3 is a schematic diagram of a high frequency ripple passing through both ends of an energy storage capacitor in the prior art.
  • FIG. 4 is a schematic structural diagram of the power conversion system of the present invention.
  • FIG. 5 is a schematic diagram showing the direction of the working current of the power conversion system of the present invention.
  • FIG. 6 is a schematic diagram showing the working principle of the power conversion system of the present invention.
  • FIG. 7 is a schematic diagram showing the high frequency ripple flowing from the PFC into the storage capacitor according to the present invention.
  • FIG. 8 is a schematic diagram showing the high frequency ripple flowing from the storage capacitor to the inverter IPM according to the present invention.
  • FIG. 9 is a schematic diagram of the high frequency ripple passing through the two ends of the energy storage capacitor according to the present invention.
  • this embodiment provides a power conversion system 1, and the power conversion system 1 includes:
  • a rectifier module 11 an inverter module 12 and a control module 13 .
  • the rectifier module 11 receives an AC input voltage and converts the AC input voltage into a DC bus voltage DC-BUS.
  • the rectifier module 11 is a three-level topology.
  • the rectifier module 11 adopts a VIENNA rectifier module, and various modifications of the VIENNA topology are applicable to the rectifier module 11 of this embodiment.
  • the rectifier module 11 includes a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, a fifth diode D5, and a sixth diode D6 , the first inductor L11, the second inductor L12, the third inductor L13, the first power switch Q1, the second power switch Q2, the third power switch Q3, the fourth power switch Q4, and the fifth power switch Q5 , the sixth power switch tube Q6, the first group of energy storage capacitors C1 and the second group of energy storage capacitors C2.
  • the cathodes of the first diode D1, the third diode D3 and the fifth diode D5 are connected together as the anode DC-BUS+ of the DC bus voltage;
  • the anode of a diode D1 is connected to the cathode of the second diode D2 and is connected to the first phase L1 of the AC input voltage via the first inductor L11;
  • the anode of the third diode D3 is connected to the first phase L1 of the AC input voltage.
  • the cathode of the fourth diode D4 is connected to the second phase L2 of the AC input voltage via the second inductor L12; the anode of the fifth diode D5 is connected to the cathode of the sixth diode D6 and the third phase L3 of the AC input voltage is connected via the third inductor L13; the anodes of the second diode D2, the fourth diode D4, and the sixth diode D6 are connected to Together as the negative DC-BUS- of the DC bus voltage.
  • the first group of energy storage capacitors C1 and the second group of energy storage capacitors C2 are connected in series and then connected in parallel between the positive electrode DC-BUS+ of the DC bus voltage and the negative electrode DC-BUS- of the DC bus voltage; the The first group of energy storage capacitors C1 and the second group of energy storage capacitors C2 include a single capacitor or a combination of multiple capacitors in series and parallel. In this embodiment, the first group of energy storage capacitors C1 and the second group of energy storage capacitors The storage capacitors C2 each include only a single capacitor.
  • the first end of the first power switch transistor Q1 is connected to the connection node of the first diode D1 and the second diode D2, and the second end is connected to the first end of the second power switch transistor Q2 ;
  • the second end of the second power switch tube Q2 is connected to the connection node of the first group of energy storage capacitors C1 and the second group of energy storage capacitors C2;
  • the first end of the third power switch tube Q3 is connected to The connection node of the third diode D3 and the fourth diode D4, the second end is connected to the first end of the fourth power switch transistor Q4;
  • the second end of the fourth power switch transistor Q4 Connect the connection nodes of the first group of energy storage capacitors C1 and the second group of energy storage capacitors C2;
  • the first end of the fifth power switch tube Q5 is connected to the fifth diode D5 and the sixth
  • the connection node of the diode D6, the second end is connected to the first end of the sixth power switch tube Q6;
  • the first power switch transistor Q1, the second power switch transistor Q2, the third power switch transistor Q3, the fourth power switch transistor Q4, the The five power switch transistors Q5 and the sixth power switch transistor Q6 are insulated gate bipolar transistors.
  • the first end of each power switch transistor is the collector, the second end is the emitter, and the control end is the base .
  • the type of each power switch tube can be set as required, which is not limited to this embodiment.
  • the grid power supply in this embodiment is a three-phase four-wire system (three live wires and one ground wire). If it is a three-phase five-wire system (three live wires, one neutral wire and one ground wire), the neutral wire is connected to two sets of capacitors. connection node.
  • the inverter module 12 is connected to the output end of the rectifier module 11 to convert the DC bus voltage DC-BUS into an AC output voltage.
  • the inverter module 12 is a two-level topology.
  • the inverter module 12 includes a seventh power switch Q7, an eighth power switch Q8, a ninth power switch Q9, a tenth power switch Q10, an eleventh power switch Q11 and a twelfth power switch Switch tube power switch tube Q12.
  • the first ends of the seventh power switch transistor Q7, the ninth power switch transistor Q9 and the eleventh power switch transistor Q11 are connected to the positive pole DC-BUS+ of the DC bus voltage; the The second end of the seventh power switch Q7 is connected to the first end of the eighth power switch Q8 and outputs the first AC output voltage U; the second end of the ninth power switch Q9 is connected to the tenth power
  • the first end of the switch tube Q10 outputs the second AC output voltage V;
  • the second end of the eleventh power switch tube Q11 is connected to the first end of the twelfth power switch tube Q12 and outputs the third AC output voltage W;
  • the second ends of the eighth power switch tube Q8, the tenth power switch tube Q10, and the twelfth power switch tube Q12 are connected to the negative electrode DC-BUS- of the DC bus voltage;
  • the seventh power switch tube The control terminals of Q7 , the eighth power switch Q8 , the ninth power switch Q9 , the tenth power switch Q10 , the
  • the seventh power switch Q7, the eighth power switch Q8, the ninth power switch Q9, the tenth power switch Q10, the eleventh power switch Q11 and the Twelve power switch tubes Q12 are insulated gate bipolar transistors.
  • the first end of each power switch tube is the collector, the second end is the emitter, and the control end is the base.
  • the type of each power switch tube can be set as required.
  • the inverter module 12 may select any structure according to requirements, which is not limited to this embodiment.
  • control module 13 is connected to the rectifier module 11 and the inverter module 12 to generate control signals for the rectifier module 11 and the inverter module 12 .
  • the control module 13 generates control signals of the power switch tubes in the rectifier module 11 and the inverter module 12 based on the collected signals.
  • the switching frequency of the power switch tube in the rectifier module 11 is an even multiple of the switching frequency of the power switch tube in the inverter module 12, including but not limited to 2 times, 4 times, 6 times, and 8 times. Not to repeat them one by one; as an example, take the switching frequency of the power switch tube in the rectifier module 11 being twice the switching frequency of the power switch tube in the inverter module 12 as an example, the power switch tube in the rectifier module 11 is taken as an example.
  • the switching frequency of the inverter module 12 is set to 16KHz, and the switching frequency of the power switch tube in the inverter module 12 is set to 8KHz; in actual use, the switching frequency can be set according to actual needs, which is not limited to this embodiment.
  • the endpoints of the PWM carrier of the power switch tube in the inverter module 12 are respectively aligned with the endpoints of the PWM carrier (including but not limited to the triangular carrier and the sawtooth carrier) of the power switch tube in the rectifier module 11 (due to different switching frequencies).
  • each endpoint of the PWM carrier of the power switch tube in the inverter module is aligned with one endpoint of the PWM carrier of the power switch tube in the rectifier module, and each endpoint of the PWM carrier of the power switch tube in the rectifier module is aligned with each other. Not all of them correspond to the endpoints of the PWM carrier of the power switch tube in the inverter module), where the endpoints refer to the top and bottom points of the carrier. As shown in FIG.
  • the bottom point of the PWM triangular carrier of the power switch tube in the inverter module 12 is aligned with the vertex of the PWM triangular carrier of the power switch tube in the rectifier module 11 , and the inverse The vertex of the PWM triangular carrier of the power switch tube in the variable module 12 is aligned with the vertex of the PWM triangular carrier of the power switch tube in the rectifier module 11; it is also possible to make the bottom of the PWM triangular carrier of the power switch tube in the inverter module 12.
  • the point is aligned with the bottom point of the PWM triangular carrier of the power switch tube in the rectifier module 11, and the vertex of the PWM triangular carrier of the power switch tube in the inverter module 12 is aligned with the PWM triangular carrier of the power switch tube in the rectifier module 11. aligned with the bottom point.
  • the bottom point of the PWM sawtooth carrier wave of the power switch tube in the inverter module 12 is aligned with the bottom point of the PWM sawtooth carrier wave of the power switch tube in the rectifier module 11, and the inverter module 12
  • the apex of the PWM sawtooth carrier of the medium power switch tube is aligned with the apex of the PWM sawtooth carrier of the power switch tube in the rectifier module 11 , which is not shown one by one here.
  • the power conversion system 1 is suitable for including, but not limited to, compressor frequency conversion speed regulation, energy storage converter (at this time, a battery needs to be added), and the like.
  • the power conversion system 1 is applied to the frequency conversion speed regulation of the compressor, wherein the motor 2 is connected to the output end of the inverter module 12 and is driven and operated by the AC output voltage.
  • control module 13 generates a control signal based on the AC input voltage and the signal collected from the motor 2 .
  • the motor 2 is a permanent magnet synchronous motor.
  • the motor 2 may also be other three-phase motors such as an AC asynchronous motor, which will not be described in detail here.
  • the parameters of the first group of energy storage capacitors C1 and the second group of energy storage capacitors C2 in the power conversion system 1 are the same, including but not limited to capacitance, rated ripple current and rated voltage, so only the first group of storage capacitors C1 is analyzed.
  • the current directions of the first phase L1 , the second phase L2 and the third phase L3 of the AC input voltage are flowing into the rectifier module 11 from the power grid, flowing out from the rectifier module 11 , Flow out from the rectifier module 11, and the switching frequency of the power switch tube in the rectifier module 11 is 16KHz.
  • the current directions of the first AC output voltage U, the second AC output voltage V, and the third AC output voltage W output by the inverter module 12 flow out from the inverter module 12 and flow into the motor 2 respectively.
  • the inverter module 12 flows into the inverter module 12 from the motor 2 , and the switching frequency of the power switch tube in the inverter module 12 is 8KHz.
  • the rectifier module 11 is aligned with the PWM carrier terminal of the power switch tube in the inverter module 12 .
  • the first power switch tube Q1 and the second power switch tube Q2 can affect the charging and discharging of the first group of energy storage capacitors C1.
  • the first group of energy storage capacitors C1 is not charged (as shown in the shaded area);
  • the inductor current charges the first group of energy storage capacitors C1 through the first diode D1, that is, the rectifier The module 11 will not charge the first group of energy storage capacitors C1 near the apex of the PWM carrier of the power switch tube.
  • the upper and lower power switch tubes in the inverter module 13 are complementarily turned on, at this time, among the six power switch tubes in the inverter module 13, the one that can affect the charging and discharging of the first group of energy storage capacitors C1 is the first power switch tube. Seven power switch transistors Q7, the ninth power switch transistor Q9 and the eleventh power switch transistor Q11.
  • the seventh power switch Q7, the ninth power switch Q9 and the eleventh power switch Q11 are all turned on or not turned on, the first group of energy storage capacitors C1 is not discharged ( As shown in the shaded area); when one of the seventh power switch Q7, the ninth power switch Q9 and the eleventh power switch Q11 is turned on and the other is not turned on, the first The group of energy storage capacitors C1 is discharged, that is, the inverter module 12 will not discharge the first group of energy storage capacitors C1 near the bottom point and the apex of the carrier of the power switch tube.
  • the shaded areas are basically coincident, that is, the charging and discharging times of the rectifier module 11 and the inverter module 12 are basically coincident, so the high-frequency ripple flowing into the energy storage capacitor The currents will cancel each other out, and the actual ripple current of the energy storage capacitor will be greatly reduced.
  • the present invention only uses the first phase L1, the second phase L2, the third phase L3, the first AC output voltage U, and the second AC output voltage of the AC input voltage assumed in this embodiment.
  • the voltage V and the current direction of the third AC output voltage W are explained in principle. The current direction will change in different working states, but the principle is the same, and will not be repeated here.
  • the switching frequency of the rectifier side is 16 kHz (as shown in FIG. 8 ). If the carrier endpoints are aligned, the effective value of the high-frequency ripple current flowing into the energy storage capacitor is 11A (as shown in Figure 9). It can be seen that the high-frequency ripple current flowing into the energy storage capacitor in the present invention is greatly reduced, and the loss of the energy storage capacitor is also reduced. Therefore, an energy storage capacitor with a smaller capacitance can be selected to reduce the volume and cost. Improve power density.
  • the present invention provides a power conversion system, comprising: a rectifier module, which receives an AC input voltage and converts the AC input voltage into a DC bus voltage; an inverter module, which is connected to the output end of the rectifier module, converting the DC bus voltage into an AC output voltage; a control module, connected to the rectifier module and the inverter module, for generating control signals of the rectifier module and the inverter module; wherein the rectifier module
  • the switching frequency of the power switch tube in the inverter module is an even multiple of the switching frequency of the power switch tube in the inverter module, and the endpoints of the PWM carrier of the power switch tube in the inverter module are respectively the same as those of the power switch tube in the rectifier module.
  • the endpoints of the PWM carrier are aligned.
  • the power conversion system of the present invention adopts the topology structure of the front-stage rectification and the latter-stage inversion, which can greatly reduce the high-frequency ripple current at both ends of the DC bus energy storage capacitor, reduce the loss of the energy storage capacitor, and thus can greatly reduce the direct current
  • the capacity of the bus energy storage capacitor thereby reducing the volume and cost of the energy storage capacitor, and improving the power density and reliability of the system. Therefore, the present invention effectively overcomes various shortcomings in the prior art and has high industrial utilization value.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)

Abstract

本发明提供一种功率转换系统，包括：整流模块，将交流输入电压转化为直流母线电压；逆变模块，将直流母线电压转换为交流输出电压；控制模块，产生整流模块及逆变模块的控制信号；其中，所述整流模块中功率开关管的开关频率为所述逆变模块中功率开关管的开关频率的偶数倍，且所述逆变模块中功率开关管的PWM载波的端点分别与所述整流模块中功率开关管的PWM载波的端点对齐。本发明采用前级整流后级逆变的拓扑结构，能够大幅度减小直流母线储能电容两端的高频纹波电流，减小储能电容的损耗，因此可大大减小直流母线储能电容的容量、体积及成本，提高系统的功率密度以及可靠性。

Description

功率转换系统 技术领域
本发明涉及功率变换领域，特别是涉及一种功率转换系统。
背景技术
现有技术中采用前级带PFC(Power Factor Correction，功率因数校正)的功率转换系统，目的是降低电网的低次谐波，提高电网的功率因数，同时能够控制直流母线电压，提高系统效率。
但缺点是PFC整流前端以及IPM逆变后端的功率器件的高频开关动作，会给直流母线电容带来高频的纹波电流。如图1所示为从PFC流入储能电容的高频纹波；如图2所示为从储能电容流向逆变IPM的高频纹波；如图3所示为实际经过储能电容两端的高频纹波。通常电容厂商在说明书中会给出此款电容纹波电流的耐受值，一般的，电容容值越大，纹波电流的耐受能力越强。但是电容容值越大，其体积和成本也相应增加，非常不利于系统功率密度的提高和成本的降低。
因此，如何减小直流母线储能电容、提高功率密度、降低成本，已成为本领域技术人员亟待解决的问题之一。
发明内容
鉴于以上所述现有技术的缺点，本发明的目的在于提供一种功率转换系统，用于解决现有技术中储能电容大、功率密度低、成本高等问题。
为实现上述目的及其他相关目的，本发明提供一种功率转换系统，所述功率转换系统至少包括：
整流模块，接收交流输入电压，并将所述交流输入电压转化为直流母线电压；
逆变模块，连接所述整流模块的输出端，将所述直流母线电压转换为交流输出电压；
控制模块，连接所述整流模块及所述逆变模块，用于产生所述整流模块及所述逆变模块的控制信号；
其中，所述整流模块中功率开关管的开关频率为所述逆变模块中功率开关管的开关频率的偶数倍，且所述逆变模块中功率开关管的PWM载波的端点分别与所述整流模块中功率开关管的PWM载波的端点对齐。
可选地，所述整流模块为三电平拓扑结构。
更可选地，所述整流模块为VIENNA整流模块。
更可选地，所述VIENNA整流模块包括第一、第二、第三、第四、第五、第六二极管，第一、第二、第三电感，第一、第二、第三、第四、第五、第六功率开关管，第一组储能电容及第二组储能电容；
所述第一、第三、第五二极管的阴极连接在一起，所述第一二极管的阳极连接所述第二二极管的阴极并经由所述第一电感连接所述交流输入电压的第一相，所述第三二极管的阳极连接所述第四二极管的阴极并经由所述第二电感连接所述交流输入电压的第二相，所述第五二极管的阳极连接所述第六二极管的阴极并经由所述第三电感连接所述交流输入电压的第三相，所述第二、第四、第六二极管的阳极连接在一起；
所述第一组储能电容与所述第二组储能电容串联后并联于所述第一、第三、第五二极管的阴极与所述二、第四、第六二极管的阳极之间；
所述第一功率开关管的第一端连接所述第一二极管与所述第二二极管的连接节点，第二端连接所述第二功率开关管的第一端；所述第三功率开关管的第一端连接所述第三二极管与所述第四二极管的连接节点，第二端连接所述第四功率开关管的第一端；所述第五功率开关管的第一端连接所述第五二极管与所述第六二极管的连接节点，第二端连接所述第六功率开关管的第一端；所述第二、第四、第六功率开关管的第二端均连接所述第一组储能电容与所述第二组储能电容的连接节点；所述第一、第二、第三、第四、第五及第六功率开关管的控制端分别连接所述控制模块。
更可选地，各功率开关管为绝缘栅双极型晶体管。
更可选地，所述第一组储能电容与所述第二组储能电容的容值、纹波电压相同。
更可选地，所述第一组储能电容及所述第二组储能电容均包括单个电容或多个电容串并联的组合。
可选地，所述逆变模块为两电平拓扑结构。
更可选地，所述逆变模块包括第七、第八、第九、第十、第十一及第十二功率开关管；
所述第七、第九、第十一功率开关管的第一端连接于所述直流母线电压的正极，所述第七功率开关管的第二端连接所述第八功率开关管的第一端并输出第一交流输出电压，所述第九功率开关管的第二端连接所述第十功率开关管的第一端并输出第二交流输出电压，所述第十一功率开关管的第二端连接所述第十二功率开关管的第一端并输出第三交流输出电压，所述第八、第十、第十二功率开关管的第二端连接于所述直流母线电压的负极；所述第七、第八、第九、第十、第十一及第十二功率开关管的控制端分别连接所述控制模块。
更可选地，各功率开关管为绝缘栅双极型晶体管。
如上所述，本发明的功率转换系统，具有以下有益效果：
本发明的功率转换系统采用前级整流后级逆变的拓扑结构，能够大幅度减小直流母线储能电容两端的高频纹波电流，减小储能电容的损耗，因此可以大大减小直流母线储能电容的容量，进而减小储能电容的体积及成本，提高系统的功率密度以及可靠性。
附图说明
图1显示为现有技术中从PFC流入储能电容的高频纹波的示意图。
图2显示为现有技术中从储能电容流向逆变IPM的高频纹波的示意图。
图3显示为现有技术中经过储能电容两端的高频纹波的示意图。
图4显示为本发明的功率转换系统的结构示意图。
图5显示为本发明的功率转换系统的工作电流走向示意图。
图6显示为本发明的功率转换系统的工作原理示意图。
图7显示为本发明从PFC流入储能电容的高频纹波的示意图。
图8显示为本发明从储能电容流向逆变IPM的高频纹波的示意图。
图9显示为本发明经过储能电容两端的高频纹波的示意图。
元件标号说明
1   功率转换系统
11  整流模块
12  逆变模块
13  控制模块
2   电机
具体实施方式
以下通过特定的具体实例说明本发明的实施方式，本领域技术人员可由本说明书所揭露的内容轻易地了解本发明的其他优点与功效。本发明还可以通过另外不同的具体实施方式加以实施或应用，本说明书中的各项细节也可以基于不同观点与应用，在没有背离本发明的精神下进行各种修饰或改变。
请参阅图4～图9。需要说明的是，本实施例中所提供的图示仅以示意方式说明本发明的基本构想，遂图式中仅显示与本发明中有关的组件而非按照实际实施时的组件数目、形状及 尺寸绘制，其实际实施时各组件的型态、数量及比例可为一种随意的改变，且其组件布局型态也可能更为复杂。
如图4所示，本实施例提供一种功率转换系统1，所述功率转换系统1包括：
整流模块11，逆变模块12及控制模块13。
如图4所示，所述整流模块11接收交流输入电压，并将所述交流输入电压转化为直流母线电压DC-BUS。
具体地，在本实施例中，所述整流模块11为三电平拓扑结构。作为示例，所述整流模块11采用VIENNA整流模块，VIENNA拓补的各种变形均适用于本实施例的所述整流模块11。作为示例，所述整流模块11包括第一二极管D1、第二二极管D2、第三二极管D3、第四二极管D4、第五二极管D5、第六二极管D6，第一电感L11、第二电感L12、第三电感L13，第一功率开关管Q1、第二功率开关管Q2、第三功率开关管Q3、第四功率开关管Q4、第五功率开关管Q5、第六功率开关管Q6，第一组储能电容C1及第二组储能电容C2。
更具体地，所述第一二极管D1、所述第三二极管D3及所述第五二极管D5的阴极连接在一起作为所述直流母线电压的正极DC-BUS+；所述第一二极管D1的阳极连接所述第二二极管D2的阴极并经由所述第一电感L11连接所述交流输入电压的第一相L1；所述第三二极管D3的阳极连接所述第四二极管D4的阴极并经由所述第二电感L12连接所述交流输入电压的第二相L2；所述第五二极管D5的阳极连接所述第六二极管D6的阴极并经由所述第三电感L13连接所述交流输入电压的第三相L3；所述第二二极管D2、所述第四二极管D4、所述第六二极管D6的阳极连接在一起作为所述直流母线电压的负极DC-BUS-。所述第一组储能电容C1与所述第二组储能电容C2串联后并联于所述直流母线电压的正极DC-BUS+与所述直流母线电压的负极DC-BUS-之间；所述第一组储能电容C1及所述第二组储能电容C2包括单个电容或多个电容串并联的组合，在本实施例中，所述第一组储能电容C1及所述第二组储能电容C2均仅包括单个电容。所述第一功率开关管Q1的第一端连接所述第一二极管D1与所述第二二极管D2的连接节点，第二端连接所述第二功率开关管Q2的第一端；所述第二功率开关管Q2的第二端连接所述第一组储能电容C1与所述第二组储能电容C2的连接节点；所述第三功率开关管Q3的第一端连接所述第三二极管D3与所述第四二极管D4的连接节点，第二端连接所述第四功率开关管Q4的第一端；所述第四功率开关管Q4的第二端连接所述第一组储能电容C1与所述第二组储能电容C2的连接节点；所述第五功率开关管Q5的第一端连接所述第五二极管D5与所述第六二极管D6的连接节点，第二端连接所述第六功率开关管Q6的第一端；所述第六功率开关管Q6的第二端连接所述第一组储能电容C1与所述 第二组储能电容C2的连接节点；所述第一功率开关管Q1、第二功率开关管Q2、第三功率开关管Q3、第四功率开关管Q4、第五功率开关管Q5及第六功率开关管Q6的控制端分别连接所述控制模块13。
需要说明的是，在本实施例中，所述第一功率开关管Q1、所述第二功率开关管Q2、所述第三功率开关管Q3、所述第四功率开关管Q4、所述第五功率开关管Q5及所述第六功率开关管Q6采用绝缘栅双极型晶体管，则对应地，各功率开关管的第一端为集电极，第二端为发射极，控制端为基极。在实际使用中可根据需要设定各功率开关管的类型，不以本实施例为限。
需要说明的是，本实施例电网电源为三相四线制(三根火线一根地线)，如果是三相五线制(三根火线一根中线一根地线)，则中线连接两组电容的连接节点。
如图4所示，所述逆变模块12连接所述整流模块11的输出端，将所述直流母线电压DC-BUS转换为交流输出电压。
具体地，在本实施例中，所述逆变模块12为两电平拓扑结构。作为示例，所述逆变模块12包括第七功率开关管Q7、第八功率开关管Q8、第九功率开关管Q9、第十功率开关管Q10、第十一功率开关管Q11及第十二功率开关管功率开关管Q12。
更具体地，所述第七功率开关管Q7、所述第九功率开关管Q9及所述第十一功率开关管Q11的第一端连接于所述直流母线电压的正极DC-BUS+；所述第七功率开关管Q7的第二端连接所述第八功率开关管Q8的第一端并输出第一交流输出电压U；所述第九功率开关管Q9的第二端连接所述第十功率开关管Q10的第一端并输出第二交流输出电压V；所述第十一功率开关管Q11的第二端连接所述第十二功率开关管Q12的第一端并输出第三交流输出电压W；所述第八功率开关管Q8、第十功率开关管Q10、第十二功率开关管Q12的第二端连接于所述直流母线电压的负极DC-BUS-；所述第七功率开关管Q7、第八功率开关管Q8、第九功率开关管Q9、第十功率开关管Q10、第十一功率开关管Q11及第十二功率开关管Q12的控制端分别连接所述控制模块13。
需要说明的是，在本实施例中，所述第七功率开关管Q7、第八功率开关管Q8、第九功率开关管Q9、第十功率开关管Q10、第十一功率开关管Q11及第十二功率开关管Q12为绝缘栅双极型晶体管，对应地，各功率开关管的第一端为集电极，第二端为发射极，控制端为基极。在实际使用中可根据需要设定各功率开关管的类型。所述逆变模块12可根据需要选择任意一种结构，不以本实施例为限。
如图4所示，所述控制模块13连接所述整流模块11及所述逆变模块12，产生所述整流 模块11及所述逆变模块12的控制信号。
具体地，所述控制模块13基于采集到的信号，产生所述整流模块11及所述逆变模块12中各功率开关管的控制信号。其中，所述整流模块11中功率开关管的开关频率为所述逆变模块12中功率开关管的开关频率的偶数倍，包括但不限于2倍、4倍、6倍、8倍，在此不一一赘述；作为示例，以所述整流模块11中功率开关管的开关频率为所述逆变模块12中功率开关管的开关频率的2倍为例，所述整流模块11中功率开关管的开关频率设置为16KHz，所述逆变模块12中功率开关管的开关频率设置为8KHz；在实际使用中，可根据实际需要设定开关频率，不以本实施例为限。同时，所述逆变模块12中功率开关管的PWM载波的端点分别与所述整流模块11中功率开关管的PWM载波(包括但不限于三角载波及锯齿载波)的端点对齐(由于开关频率不同，所述逆变模块中功率开关管的PWM载波的各端点与所述整流模块中功率开关管的PWM载波的一端点对应对齐，而所述整流模块中功率开关管的PWM载波的各端点并不是都对应一个所述逆变模块中功率开关管的PWM载波的端点)，其中，端点是指载波的顶点及底点。如图6所示，以三角载波作为示例，所述逆变模块12中功率开关管的PWM三角载波的底点与所述整流模块11中功率开关管的PWM三角载波的顶点对齐，所述逆变模块12中功率开关管的PWM三角载波的顶点与所述整流模块11中功率开关管的PWM三角载波的顶点对齐；也可以使得所述逆变模块12中功率开关管的PWM三角载波的底点与所述整流模块11中功率开关管的PWM三角载波的底点对齐，所述逆变模块12中功率开关管的PWM三角载波的顶点与所述整流模块11中功率开关管的PWM三角载波的底点对齐。而对于PWM锯齿载波的情况，所述逆变模块12中功率开关管的PWM锯齿载波的底点与所述整流模块11中功率开关管的PWM锯齿载波的底点对齐，所述逆变模块12中功率开关管的PWM锯齿载波的顶点与所述整流模块11中功率开关管的PWM锯齿载波的顶点对齐，在此不一一图示。
所述功率转换系统1适用于包括但不限于压缩机变频调速、储能变流器(此时还需要增加电池)等。作为示例，所述功率转换系统1应用于压缩机变频调速，其中，电机2连接于所述逆变模块12的输出端，受所述交流输出电压的驱动运转。
具体地，在本实施例中，所述控制模块13基于所述交流输入电压及所述电机2上采集到的信号产生控制信号。
具体地，在本实施例中，所述电机2为永磁同步电机，当电机的三相定子绕组通入三相交流电后，将产生一个旋转磁场，该旋转磁场带动转子同步旋转。在其他实施例中，所述电机2也可以为交流异步电机等其他三相电机，在此不一一赘述。
在本实施例中，所述功率转换系统1中的所述第一组储能电容C1与所述第二组储能电容C2的参数相同，包括但不限于容值、额定纹波电流及额定电压，因此仅对所述第一组储能电容C1进行分析。
如图5所示，假设：所述交流输入电压的第一相L1、第二相L2、第三相L3的电流方向分别是从电网流入所述整流模块11、从所述整流模块11流出、从所述整流模块11流出，且所述整流模块11中功率开关管的开关频率为16KHz。所述逆变模块12输出的第一交流输出电压U、第二交流输出电压V、第三交流输出电压W的电流方向分别是从所述逆变模块12流出、从所述电机2流入所述逆变模块12、从所述电机2流入所述逆变模块12，且所述逆变模块12中功率开关管的开关频率为8KHz。所述整流模块11与所述逆变模块12中功率开关管的PWM载波端点对齐。
此时，所述整流模块11中六个功率开关管中能影响所述第一组储能电容C1充放电的只能是所述第一功率开关管Q1及所述第二功率开关管Q2。如图5及图6所示，当所述第一功率开关管Q1及所述第二功率开关管Q2导通时，所述第一组储能电容C1不充电(如阴影区域所示)；当所述第一功率开关管Q1及所述第二功率开关管Q2关断时，电感电流通过所述第一二极管D1给所述第一组储能电容C1充电，也就是所述整流模块11在功率开关管的PWM载波顶点附近不会对所述第一组储能电容C1充电。
由于所述逆变模块13中上下功率开关管互补导通，此时，所述逆变模块13中六个功率开关管中能影响所述第一组储能电容C1充放电的是所述第七功率开关管Q7、所述第九功率开关管Q9及所述第十一功率开关管Q11。当所述第七功率开关管Q7、所述第九功率开关管Q9及所述第十一功率开关管Q11均导通或均不导通时，所述第一组储能电容C1不放电(如阴影区域所示)；当第七功率开关管Q7、所述第九功率开关管Q9及所述第十一功率开关管Q11中有一个导通且有一个不导通时，所述第一组储能电容C1放电，也就是所述逆变模块12在功率开关管的载波底点和顶点附近不会对所述第一组储能电容C1放电。
如图6所示，在一个载波周期中，阴影区域都基本重合，即所述整流模块11和所述逆变模块12对电容充放电的时间基本重合，那么流入储能电容的高频纹波电流就会相互抵消，储能电容实际的纹波电流就会大大减小。
需要说明的是，本发明仅以本实施例假设的所述交流输入电压的第一相L1、第二相L2、第三相L3、所述第一交流输出电压U、所述第二交流输出电压V、所述第三交流输出电压W的电流方向做原理说明，在不同的工作状态下电流方向会发生改变，但原理相同，在此不一一赘述。
对比采用现有的前级带PFC的压缩机变频调速以及采用本发明的功率转换系统，参考图3和图9，可以看出本发明中流入储能电容的高频纹波电流有效值大大减小了。基于现有的采用前级带PFC的功率转换系统，逆变侧的开关频率为5.625kHz(如图1所示)，而整流侧的开关频率为16kHz(如图2所示)，则流入储能电容的高频纹波电流有效值为25A(如图3所示)。本发明的功率转换系统1中，逆变侧的开关频率为8kHz(如图7所示)，而整流侧的开关频率为16kHz(如图8所示)，且两者的功率开关管的三角载波端点对齐，则，流入储能电容的高频纹波电流有效值为11A(如图9所示)。可以看出，本发明中流入储能电容的高频纹波电流大大减小，进而储能电容的损耗也减小了，因此可以选择容值较小的储能电容，减小体积和成本，提高功率密度。
综上所述，本发明提供一种功率转换系统，包括：整流模块，接收交流输入电压，并将所述交流输入电压转化为直流母线电压；逆变模块，连接所述整流模块的输出端，将所述直流母线电压转换为交流输出电压；控制模块，连接所述整流模块及所述逆变模块，用于产生所述整流模块及所述逆变模块的控制信号；其中，所述整流模块中功率开关管的开关频率为所述逆变模块中功率开关管的开关频率的偶数倍，且所述逆变模块中功率开关管的PWM载波的端点分别与所述整流模块中功率开关管的PWM载波的端点对齐。本发明的功率转换系统采用前级整流后级逆变的拓扑结构，能够大幅度减小直流母线储能电容两端的高频纹波电流，减小储能电容的损耗，因此可以大大减小直流母线储能电容的容量，进而减小储能电容的体积及成本，提高系统的功率密度以及可靠性。所以，本发明有效克服了现有技术中的种种缺点而具高度产业利用价值。
上述实施例仅例示性说明本发明的原理及其功效，而非用于限制本发明。任何熟悉此技术的人士皆可在不违背本发明的精神及范畴下，对上述实施例进行修饰或改变。因此，举凡所属技术领域中具有通常知识者在未脱离本发明所揭示的精神与技术思想下所完成的一切等效修饰或改变，仍应由本发明的权利要求所涵盖。

Claims (10)

  1. 一种功率转换系统，其特征在于，所述功率转换系统至少包括：
    整流模块，接收交流输入电压，并将所述交流输入电压转化为直流母线电压；
    逆变模块，连接所述整流模块的输出端，将所述直流母线电压转换为交流输出电压；
    控制模块，连接所述整流模块及所述逆变模块，用于产生所述整流模块及所述逆变模块的控制信号；
    其中，所述整流模块中功率开关管的开关频率为所述逆变模块中功率开关管的开关频率的偶数倍，且所述逆变模块中功率开关管的PWM载波的端点分别与所述整流模块中功率开关管的PWM载波的端点对齐。
  2. 根据权利要求1所述的功率转换系统，其特征在于：所述整流模块为三电平拓扑结构。
  3. 根据权利要求2所述的功率转换系统，其特征在于：所述整流模块为VIENNA整流模块。
  4. 根据权利要求3所述的功率转换系统，其特征在于：所述VIENNA整流模块包括第一、第二、第三、第四、第五、第六二极管，第一、第二、第三电感，第一、第二、第三、第四、第五、第六功率开关管，第一组储能电容及第二组储能电容；
    所述第一、第三、第五二极管的阴极连接在一起，所述第一二极管的阳极连接所述第二二极管的阴极并经由所述第一电感连接所述交流输入电压的第一相，所述第三二极管的阳极连接所述第四二极管的阴极并经由所述第二电感连接所述交流输入电压的第二相，所述第五二极管的阳极连接所述第六二极管的阴极并经由所述第三电感连接所述交流输入电压的第三相，所述第二、第四、第六二极管的阳极连接在一起；
    所述第一组储能电容与所述第二组储能电容串联后并联于所述第一、第三、第五二极管的阴极与所述二、第四、第六二极管的阳极之间；
    所述第一功率开关管的第一端连接所述第一二极管与所述第二二极管的连接节点，第二端连接所述第二功率开关管的第一端；所述第三功率开关管的第一端连接所述第三二极管与所述第四二极管的连接节点，第二端连接所述第四功率开关管的第一端；所述第五功率开关管的第一端连接所述第五二极管与所述第六二极管的连接节点，第二端连接所述第六功率开关管的第一端；所述第二、第四、第六功率开关管的第二端均连接所述第一组储能电容与所述第二组储能电容的连接节点；所述第一、第二、第三、第四、第五及第六功 率开关管的控制端分别连接所述控制模块。
  5. 根据权利要求4所述的功率转换系统，其特征在于：各功率开关管为绝缘栅双极型晶体管。
  6. 根据权利要求4所述的功率转换系统，其特征在于：所述第一组储能电容与所述第二组储能电容的参数相同。
  7. 根据权利要求4～6任意一项所述的功率转换系统，其特征在于：所述第一组储能电容及所述第二组储能电容均包括单个电容或多个电容串并联的组合。
  8. 根据权利要求1所述的功率转换系统，其特征在于：所述逆变模块为两电平拓扑结构。
  9. 根据权利要求8所述的功率转换系统，其特征在于：所述逆变模块包括第七、第八、第九、第十、第十一及第十二功率开关管；
    所述第七、第九、第十一功率开关管的第一端连接于所述直流母线电压的正极，所述第七功率开关管的第二端连接所述第八功率开关管的第一端并输出第一交流输出电压，所述第九功率开关管的第二端连接所述第十功率开关管的第一端并输出第二交流输出电压，所述第十一功率开关管的第二端连接所述第十二功率开关管的第一端并输出第三交流输出电压，所述第八、第十、第十二功率开关管的第二端连接于所述直流母线电压的负极；所述第七、第八、第九、第十、第十一及第十二功率开关管的控制端分别连接所述控制模块。
  10. 根据权利要求9所述的功率转换系统，其特征在于：各功率开关管为绝缘栅双极型晶体管。
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