WO2021240813A1

WO2021240813A1 - Phase shifter and distortion compensation circuit

Info

Publication number: WO2021240813A1
Application number: PCT/JP2020/021452
Authority: WO
Inventors: 由文河村; 政毅半谷; 真太郎新庄
Original assignee: 三菱電機株式会社
Priority date: 2020-05-29
Filing date: 2020-05-29
Publication date: 2021-12-02
Also published as: JPWO2021240813A1

Abstract

A phase shifter that comprises a first transmission line (21) through which high-frequency signals applied to one end are propagated to the other end, a second transmission line (23) that is connected at one end to the other end of the first transmission line (21), a third transmission line (24) that is connected at one end to the other end of the second transmission line (23), a coupled line (22) in which an even mode propagation mode and an odd mode propagation mode occur when high-frequency signals that have propagated through the first transmission line (21) are propagated through each of the second transmission line (23) and the third transmission line (24), a fourth transmission line (25) that is connected at one end to the other end of the third transmission line (24) and propagates high-frequency signals that have propagated through the coupled line (22), and a phase adjustment circuit (26) that is connected at one end to at least one transmission line from among the first transmission line (21) and the fourth transmission line (25) and adjusts the propagation speed of even mode high-frequency signals.

Description

Phase shifter and distortion compensation circuit

The present disclosure relates to a phase shifter and a distortion compensation circuit provided with the phase shifter.

The following Non-Patent Document 1 discloses a phase shifter including a coupling line. The coupling line includes a first transmission line and a second transmission line, and the first transmission line and the second transmission line are arranged in parallel with each other. When a high-frequency signal propagates on a coupled line, an even-mode propagation mode in which the current flowing through the first transmission line and the current flowing through the second transmission line are in phase, and the current flowing through the first transmission line, An odd-mode propagation mode occurs in which the current flowing through the second transmission line is out of phase. In the phase shifter, the phase shift of the high frequency signal according to the difference between the propagation speed of the even mode in the high frequency signal and the propagation speed of the odd mode in the high frequency signal is realized.

In the phase shifter disclosed in Non-Patent Document 1, the phase shift amount of the high frequency signal can be increased by increasing the coupling degree of the coupling line. In order to increase the degree of coupling of the coupled lines, it is necessary to narrow the distance between the first transmission line and the second transmission line. However, when a phase shifter is formed on a circuit board, the distance between the first transmission line and the second transmission line cannot be narrowed infinitely, so that the desired phase shift amount may not be achieved. There was a challenge.

The present disclosure has been made to solve the above-mentioned problems, and an object of the present disclosure is to obtain a phase shifter capable of achieving a desired phase shift amount without increasing the coupling degree of the coupling line. ..

The phase shifter according to the present disclosure includes a first transmission line in which a high-frequency signal given to one end propagates to the other end, and a second transmission line in which the other end and one end of the first transmission line are connected. , A third transmission line to which the other end and one end of the second transmission line are connected, and the high frequency signal propagating through the first transmission line is that of the second transmission line and the third transmission line. When propagating each, the coupled line in which the even mode propagation mode and the odd mode propagation mode occur, and the other end and one end of the third transmission line are connected, and the high frequency signal propagating through the coupled line is One end of the propagating fourth transmission line and one or more of the first transmission line and the fourth transmission line are connected to each other, and the phase shift that adjusts the propagation speed of the even mode in the high frequency signal. It is equipped with an adjustment circuit.

According to the present disclosure, a desired phase shift amount can be realized without increasing the degree of coupling of the coupling line.

It is a block diagram which shows the phase shifter 1 which concerns on Embodiment 1. FIG. It is explanatory drawing which shows the reflection coefficient S11e of an even mode. It is explanatory drawing which shows the reflection coefficient S11o of an odd mode. It is explanatory drawing which shows the simulation result about the group delay of the reflection coefficient S11e of the even mode in a relative phase circuit 20. Is an explanatory diagram showing the simulation results of the phase difference Δφ between a passing phase phi ₂ of the passing phase phi ₁ and the relative phase shift circuit 20 of the reference phase circuit 10. It is a block diagram which shows the phase shifter 1 which concerns on Embodiment 2. FIG. FIG. 7A is an explanatory diagram showing a circuit pattern of the reference phase circuit 10, and FIG. 7B is an explanatory diagram showing a relative phase circuit 20 having no first open stub 27a and a second open stub 27b. FIG. 7C is an explanatory diagram showing a relative phase circuit 20 in which each of the first open stub 27a and the second open stub 27b is arranged on the same side as the coupling line 22, and FIG. 7D is an explanatory diagram showing the first open stub. It is explanatory drawing which shows the relative phase circuit 20 which each 27a and the 2nd open stub 27b are arranged on the opposite side to the coupling line 22. It is explanatory drawing which shows the simulation result of each group delay characteristic in the circuit pattern of the reference phase circuit 10, the circuit pattern of the relative phase circuit A, the circuit pattern of the relative phase circuit B, and the circuit pattern of the relative phase circuit C. It is explanatory drawing which shows the simulation result of each passing amplitude characteristic in the circuit pattern of the reference phase circuit 10, the circuit pattern of the relative phase circuit A, the circuit pattern of the relative phase circuit B, and the circuit pattern of the relative phase circuit C. It is explanatory drawing which shows the simulation result of each phase difference Δφ in the phase shifter 1 which has a relative phase circuit A, the phase shifter 1 which has a relative phase circuit B, and the phase shifter 1 which has a relative phase circuit C. It is a block diagram which shows the distortion compensation circuit which concerns on Embodiment 3. It is explanatory drawing which shows the simulation result of the relative gain characteristic of the distortion compensation circuit with respect to the electric power of a high frequency signal RF given to an input terminal 30. It is explanatory drawing which shows the simulation result of the phase characteristic of the distortion compensation circuit with respect to the electric power of a high frequency signal RF given to an input terminal 30. It is explanatory drawing which shows the calculation result of the amplitude fluctuation amount characteristic of the distortion compensation circuit with respect to the standardized frequency. It is explanatory drawing which shows the calculation result of the phase fluctuation amount characteristic of the distortion compensation circuit with respect to the standardized frequency.

Hereinafter, in order to explain the present disclosure in more detail, a mode for carrying out the present disclosure will be described in accordance with the attached drawings.

Embodiment 1.
FIG. 1 is a configuration diagram showing a phase shifter 1 according to the first embodiment.
The phase shifter 1 shown in FIG. 1 includes a reference phase circuit 10 and a relative phase circuit 20.
The input terminal 2a is a terminal to which a high frequency signal is given from the outside.
The output terminal 3a is a terminal for outputting a high frequency signal output from the reference phase circuit 10 to the outside.
The input terminal 2b is a terminal to which a high frequency signal is given from the outside. The high frequency signal given to the input terminal 2a and the high frequency signal given to the input terminal 2b are high frequency signals having the same amplitude and the same phase. However, the amplitudes of the two high-frequency signals are not limited to those having exactly the same amplitude, and may be different within a range where there is no practical problem. Further, the phases of the two high frequency signals are not limited to those having exactly the same phase, and may be different within a range where there is no practical problem.
The output terminal 3b is a terminal for outputting a high frequency signal output from the relative phase circuit 20 to the outside.

The reference phase circuit 10 includes a fifth transmission line 11.
One end of the fifth transmission line 11 is connected to the input terminal 2a, and the other end of the fifth transmission line 11 is connected to the output terminal 3a.
The high frequency signal input from the input terminal 2a propagates on the fifth transmission line 11. The high frequency signal propagating through the fifth transmission line 11 is output to the outside from the output terminal 3a.

The relative phase circuit 20 includes a first transmission line 21, a coupling line 22, a fourth transmission line 25, a first phase shift adjustment circuit 26a, and a second phase shift adjustment circuit 26b.
The coupling line 22 includes a second transmission line 23 and a third transmission line 24.
The phase shifter 1 shown in FIG. 1 includes a first phase shift adjustment circuit 26a and a second phase shift adjustment circuit 26b. However, the phase shifter 1 may include any of the phase shift adjustment circuits 26 of the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b, and the first phase shift adjustment circuit 26a or a second phase shift adjusting circuit 26b may be provided. Hereinafter, when the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b are not distinguished, they are described as the phase shift adjustment circuit 26.

One end of the first transmission line 21 is connected to the input terminal 2b, and the other end of the first transmission line 21 is connected to one end of the second transmission line 23.
The high frequency signal input from the input terminal 2b propagates on the first transmission line 21.

In the coupled line 22, when the high frequency signal propagating on the first transmission line 21 propagates on each of the second transmission line 23 and the third transmission line 24, the propagation mode of the even mode and the propagation mode of the odd mode And occur.
The propagation mode of the even mode is a propagation mode in which when the high frequency signal propagates on the coupled line 22, the current flowing through the second transmission line 23 and the current flowing through the third transmission line 24 are in phase with each other.
The propagation mode of the odd mode is a propagation mode in which when the high frequency signal propagates on the coupled line 22, the current flowing through the second transmission line 23 and the current flowing through the third transmission line 24 are in opposite phases.
One end of the second transmission line 23 is connected to the other end of the first transmission line 21, and the other end of the second transmission line 23 is connected to one end of the third transmission line 24.
One end of the third transmission line 24 is connected to the other end of the second transmission line 23, and the other end of the third transmission line 24 is connected to one end of the fourth transmission line 25.
The second transmission line 23 and the third transmission line 24 are arranged in parallel with each other.

One end of the fourth transmission line 25 is connected to the other end of the third transmission line 24, and the other end of the fourth transmission line 25 is connected to the output terminal 3b.
The high frequency signal propagating on the third transmission line 24 propagates on the fourth transmission line 25.

One end of the first phase shift adjusting circuit 26a is connected to the first transmission line 21.
The first phase shift adjusting circuit 26a adjusts the propagation velocity of the even mode in the high frequency signal.
The first phase shift adjusting circuit 26a is realized by, for example, a capacitive element.
When the first phase shift adjusting circuit 26a is realized by the capacitive element, one end of the capacitive element is connected to the first transmission line 21 and the other end of the capacitive element is grounded.

One end of the second phase shift adjusting circuit 26b is connected to the fourth transmission line 25.
The second phase shift adjusting circuit 26b adjusts the propagation velocity of the even mode in the high frequency signal.
The second phase shift adjusting circuit 26b is realized by, for example, a capacitive element.
When the second phase shift adjusting circuit 26b is realized by the capacitive element, one end of the capacitive element is connected to the fourth transmission line 25, and the other end of the capacitive element is grounded.

Next, the operation of the phase shifter 1 shown in FIG. 1 will be described.
The high frequency signal RF ₁ is given to the input terminal 2a, and the high frequency signal RF ₂ is given to the input terminal 2b.
_{The high frequency signal RF 1} input from the input terminal 2a propagates on the fifth transmission line 11 in the reference phase circuit 10. _{The high frequency signal RF 1} propagating through the fifth transmission line 11 is output to the outside from the output terminal 3a.
In the phase shifter 1 shown in FIG. 1, the passing phase of the reference phase circuit 10 in the high-frequency signal RF ₁ is phi _1.

_{The high frequency signal RF 2} input from the input terminal 2b propagates on each of the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the relative phase circuit 20. _{The high frequency signal RF 2} propagating through each of the first transmission line 21, the coupling line 22, and the fourth transmission line 25 is output to the outside from the output terminal 3b.
When the high frequency signal RF ₂ propagates on the first transmission line 21, the phase velocity of a specific frequency is accelerated by the first phase shift adjustment circuit 26a, and when the high frequency signal RF ₂ propagates on the fourth transmission line 25. , The second phase shift adjustment circuit 26b accelerates the phase velocity of a specific frequency.
Therefore, _{the passing phase φ 2} of the relative phase circuit 20 in the _{high frequency signal RF 2} is different from _{the passing phase φ 1} of the reference phase circuit 10 in the high frequency signal RF _1. The specific frequency is the respective frequency in the high frequency signal RF ₁ and the high frequency signal RF _2.

In the coupled line 22, when the high frequency signal RF ₂ propagating on the first transmission line 21 propagates on each of the second transmission line 23 and the third transmission line 24, the propagation mode of the even mode and the odd mode are used. Propagation mode occurs.
In the phase shifter 1, and the propagation velocity V _e of the even mode in the high-frequency signal RF _2, phase of the high frequency signal RF ₂ is achieved according to the difference ΔV between the propagation velocity V _o of the odd mode in the high-frequency signal RF ₂ .. The phase shift amount ps of the phase shift of the high frequency signal RF ₂ according to the difference ΔV is determined by the coupling degree of the coupling line 22.
Further, each of the first phase adjustment circuit 26a and the second phase adjustment circuit 26b, it is possible to adjust the propagation velocity V _e of the even mode in the high-frequency signal RF _2, propagation velocity V _e of the even mode it is possible to adjust the difference ΔV between the propagation velocity V _o of an odd mode. Therefore, a desired phase shift amount ps can be realized without increasing the degree of coupling of the coupling line 22.
If each of the first phase adjustment circuit 26a and the second phase adjustment circuit 26b is realized by a capacitive element, in accordance with the capacity of the capacitive element, the propagation velocity V _e of the even mode is changed, By changing the capacitance of the capacitive element, a desired phase shift amount ps can be realized.
In the phase shifter 1 shown in FIG. 1, _{the phase difference Δφ between the passing phase φ 1} and the passing phase φ ₂ is adjusted to, for example, 180 degrees × n (n = 1, 2, ...).
The usable capacitance C of the capacitive element is the impedance Zc (= −j × (= −j ×) formed by the frequency f of the high frequency signal RF ₂ and the capacitance C when the electrical length of the coupling line 22 is θ _1. It suffices as long as it satisfies the condition that the passing phase of 2πfC)) is 0.5 × θ _{1 or less.}

FIG. 2 is an explanatory diagram showing a reflection coefficient S11e in the even mode.
FIG. 3 is an explanatory diagram showing the reflection coefficient S11o in the odd mode.
In the phase shifter 1 shown in FIG. 1, the coupling line 22 includes a second transmission line 23 and a third transmission line 24, and the second transmission line 23 and the third transmission line 24 are arranged in parallel with each other. Has been done.
Then, in the phase shifter 1 shown in FIG. 1, the second transmission line 23 and the third transmission line 24 are arranged with the boundary between the second transmission line 23 and the third transmission line 24 as the axis of symmetry. The component on the input terminal 2b side of the connection point and the component on the output terminal 3b side of the connection point are symmetrical.
The components on the input terminal 2b side of the connection point are the first transmission line 21 and the second transmission line 23, and the components on the output terminal 3b side of the connection point are the third transmission line 24 and the second transmission line 23. 4 is the transmission line 25.
Assuming that the boundary between the second transmission line 23 and the third transmission line 24 is a magnetic wall as shown in FIG. 2, the _{reflectance coefficient of the high frequency signal RF 2} with respect to the input terminal 2b is an even mode. Reflection coefficient S11e.
Assuming that the boundary between the second transmission line 23 and the third transmission line 24 is an electric wall as shown in FIG. 3, the _{reflectance coefficient of the high frequency signal RF 2} with respect to the input terminal 2b is an odd mode. Reflection coefficient S11e.

The reflection coefficient S11 of the relative phase circuit 20 is expressed by the following equation (1) by using the reflection coefficient S11e in the even mode and the reflection coefficient S11e in the odd mode.

Further, the transmission coefficient S21 of the relative phase circuit 20 is expressed by the following equation (2) by using the reflection coefficient S11e in the even mode and the reflection coefficient S11e in the odd mode.

Each of the reflection coefficient S11, the transmission coefficient S21, the reflection coefficient S11e, and the reflection coefficient S11e is a complex vector.

Assuming that the magnitude of the reflection coefficient S11 is | S11 | and the phase angle of the reflection coefficient S11 is ∠S11, the reflection coefficient S11 is expressed by the following equation (3).

Assuming that the magnitude of the transmission coefficient S21 is | S21 | and the phase angle of the transmission coefficient S21 is ∠S21, the transmission coefficient S21 is expressed by the following equation (4).

Here, assuming that the magnitude | S11e | of the reflection coefficient S11e in the even mode and the magnitude | S11o | of the reflection coefficient S11e in the odd mode are substantially equal, a condition that does not cause reflection mismatch in the relative phase circuit 20. Is as shown in the following equation (6).
∠S11e ＝－∠S11o (6)
The passing phase ∠S21 at this time is as shown in the following equation (7).
∠S21 = -2 × ∠S11o = 2 × ∠S11e (7)

FIG. 4 is an explanatory diagram showing a simulation result of the group delay of the reflection coefficient S11e in the even mode in the relative phase circuit 20.
The frequency of the high frequency signal according to the simulation result shown in FIG. 4 is in the range of 18 [GHz] to 25 [GHz].
In FIG. 4, the solid line shows the group delay of the reflectance coefficient S11e of the even mode for the relative phase circuit 20 when the phase shifter 1 includes the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. Is shown. The broken line indicates the group delay of the reflectance coefficient S11e of the even mode for the relative phase circuit 20 when the phase shifter 1 does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. ..
If the frequency is, for example, 22 [GHz], the group delay of the reflectance coefficient S11e in even mode is 60 if the phase shifter 1 does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. [Psec]. On the other hand, if the phase shifter 1 includes the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b, the group delay of the reflection coefficient S11e in the even mode is about 100 [psec].
Therefore, the phase shifter 1 provided with the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. compared with vessel 1, it is possible to increase the propagation velocity V _e of the even mode.

Figure 5 is an explanatory diagram showing the simulation results of the phase difference Δφ between a passing phase phi ₂ of the passing phase phi ₁ and the relative phase shift circuit 20 of the reference phase circuit 10.
In FIG. 5, the solid line shows the phase difference Δφ when the phase shifter 1 includes the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. The broken line shows the phase difference Δφ when the phase shifter 1 does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b.
In the simulation of the phase difference Δφ, the even-mode impedance Ze is 85Ω, the odd-mode impedance Zo is 25Ω, the ratio ρ of the even-mode impedance to the odd-mode impedance is 3.4, and the electrical length θ _{1 of the coupling line 22 in the relative phase circuit 20.} Is 90 degrees, and the ratio K of the electric length of the reference phase circuit 10 and the electric length of the relative phase circuit 20 is 4.
Further, the electrical length of the reference phase circuit 10 is adjusted in the range of about K = 4 ± 0.5 so that the phase difference Δφ at the frequency of 22 [GHz] is 180 degrees.
When the phase shifter 1 does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b, the frequency at which the phase difference Δφ = 180 degrees is limited to about 22 [GHz].
On the other hand, when the phase shifter 1 includes the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b, the frequency at which the phase difference Δφ = 180 degrees is 21 [GHz] to 23 [GHz]. It becomes a range.
Therefore, the phase shifter 1 provided with the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b does not include the first phase shift adjustment circuit 26a and the second phase shift adjustment circuit 26b. Compared with the device 1, the frequency at which Δφ = 180 degrees can be maintained becomes wider, and a wide-band phase difference characteristic can be obtained.

In the first embodiment as described above, the first transmission line 21 in which the high frequency signal given to one end propagates to the other end and the second transmission line in which the other end and one end of the first transmission line 21 are connected. 23 and a third transmission line 24 having one end connected to the other end of the second transmission line 23, and a high-frequency signal propagating through the first transmission line 21 is the second transmission line 23 and When propagating through each of the third transmission lines 24, the coupled line 22 in which the propagation mode of the even mode and the propagation mode of the odd mode are generated is connected to the other end and one end of the third transmission line 24. One end of the fourth transmission line 25 through which the high-frequency signal propagating the coupled line 22 propagates is connected to one or more of the first transmission line 21 and the fourth transmission line 25. The phase shifter 1 is configured to include a phase shift adjustment circuit 26 for adjusting the propagation speed of the even mode in a high frequency signal. Therefore, the phase shifter 1 can realize a desired phase shift amount without increasing the degree of coupling of the coupling line 22.

Embodiment 2.
In the second embodiment, the phase shifter 1 in which the first phase shift adjustment circuit 26a includes the first open stub 27a and the second phase shift adjustment circuit 26b includes the second open stub 27b will be described. ..

FIG. 6 is a block diagram showing the phase shifter 1 according to the second embodiment. In FIG. 6, the same reference numerals as those in FIG. 1 indicate the same or corresponding parts, and thus the description thereof will be omitted.
The phase shifter 1 shown in FIG. 6 is assumed to be arranged in the xy plane for convenience of explanation.
The reference phase circuit 10 includes a fifth transmission line 12.
The fifth transmission line 12 includes

transmission lines

12a, 12b, 12c, 12d, 12e.

One end of the transmission line 12a is connected to the input terminal 2a, and the other end of the transmission line 12a is connected to one end of the transmission line 12b.
One end of the transmission line 12b is connected to the other end of the transmission line 12a, and the other end of the transmission line 12b is connected to one end of the transmission line 12c.
One end of the transmission line 12c is connected to the other end of the transmission line 12b, and the other end of the transmission line 12c is connected to one end of the transmission line 12d.
One end of the transmission line 12d is connected to the other end of the transmission line 12c, and the other end of the transmission line 12d is connected to one end of the transmission line 12e.
One end of the transmission line 12e is connected to the other end of the transmission line 12d, and the other end of the transmission line 12e is connected to the output terminal 3a.

The fifth transmission line 12 is bent in the middle. That is, the transmission line 12a is arranged parallel to the x-axis, and _{the propagation direction of the high-frequency signal RF 1} is the + x direction.
The transmission line 12b is arranged in parallel with the y-axis, and _{the propagation direction of the high-frequency signal RF 1} is the + y direction.
The transmission line 12c is arranged parallel to the x-axis, and _{the propagation direction of the high-frequency signal RF 1} is the + x direction.
The transmission line 12d is arranged in parallel with the y-axis, and the propagation direction of the _{high-frequency signal RF 1 is the −y direction.}
The transmission line 12e is arranged parallel to the x-axis, and _{the propagation direction of the high-frequency signal RF 1} is the + x direction.
In the phase shifter 1 shown in FIG. 6, the reference phase circuit 10 includes a fifth transmission line 12 that is bent in the middle. However, this is only an example, and the reference phase circuit 10 may include the fifth transmission line 11 shown in FIG.

The first transmission line 21 is arranged parallel to the x-axis, and the fourth transmission line 25 is arranged parallel to the x-axis.
The second transmission line 23 is arranged parallel to the y-axis, and the third transmission line 24 is arranged parallel to the y-axis.
Each of the arrangement of the first transmission line 21 and the arrangement of the fourth transmission line 25 is not limited to the arrangement exactly parallel to the x-axis, and is not limited to the arrangement of the x-axis within a range where there is no practical problem. They may be arranged in parallel.
Each of the arrangement of the second transmission line 23 and the arrangement of the third transmission line 24 is not limited to those arranged exactly parallel to the y-axis, and is not limited to the arrangement of the y-axis and non-arrangement within a range where there is no practical problem. They may be arranged in parallel.

The first phase shift adjusting circuit 26a includes a first open stub 27a.
One end of the first open stub 27a is connected to the first transmission line 21.
The first open stub 27a is arranged parallel to the y-axis and is arranged on the opposite side of the coupling line 22 with the first transmission line 21 interposed therebetween.
In the phase shifter 1 shown in FIG. 6, since the coupling line 22 is arranged in the + y direction with respect to the first transmission line 21, the first open stub 27a is in the −y direction with respect to the first transmission line 21. Is located in.
The first open stub 27a by binding the second transmission line 23 and the electromagnetic field coupled line 22, acts to increase the propagation velocity V _e of the even mode in the high-frequency signal RF _2.
The first open stub 27a is not limited to the one that is strictly parallel to the y-axis, and may be arranged non-parallel to the y-axis as long as there is no practical problem.

The second phase shift adjusting circuit 26b includes a second open stub 27b.
One end of the second open stub 27b is connected to the fourth transmission line 25.
The second open stub 27b is arranged parallel to the y-axis and is arranged on the opposite side of the coupling line 22 with the fourth transmission line 25 interposed therebetween.
In the phase shifter 1 shown in FIG. 6, since the coupling line 22 is arranged in the + y direction with respect to the first transmission line 21, the second open stub 27b is in the −y direction with respect to the fourth transmission line 25. Is located in.
The second open stub 27b by binding the third transmission line 24 and the electromagnetic field coupled line 22, acts to increase the propagation velocity V _e of the even mode in the high-frequency signal RF _2.
The second open stub 27b is not limited to the one that is strictly parallel to the y-axis, and may be arranged non-parallel to the y-axis as long as there is no practical problem.

Next, the operation of the phase shifter 1 shown in FIG. 6 will be described.
The high frequency signal RF ₁ is given to the input terminal 2a, and the high frequency signal RF ₂ is given to the input terminal 2b.
_{The high frequency signal RF 1} input from the input terminal 2a propagates on the fifth transmission line 12 in the reference phase circuit 10. _{The high frequency signal RF 1} propagating through the fifth transmission line 12 is output to the outside from the output terminal 3a.
In the phase shifter 1 shown in FIG. 6, the passing phase of the reference phase circuit 10 in the high-frequency signal RF ₁ is phi _1.

_{The high frequency signal RF 2} input from the input terminal 2b propagates on each of the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the relative phase circuit 20. _{The high frequency signal RF 2} propagating through each of the first transmission line 21, the coupling line 22, and the fourth transmission line 25 is output to the outside from the output terminal 3b.
When the high frequency signal RF ₂ propagates on the first transmission line 21, the first open stub 27a accelerates the phase velocity of a specific frequency, and when the high frequency signal RF ₂ propagates on the fourth transmission line 25, the first The open stub 27b of 2 increases the phase velocity of a specific frequency.
Therefore, _{the passing phase φ 2} of the relative phase circuit 20 in the _{high frequency signal RF 2} is different from _{the passing phase φ 1} of the reference phase circuit 10 in the high frequency signal RF _1.

In the coupled line 22, when the high frequency signal RF ₂ propagating on the first transmission line 21 propagates on each of the second transmission line 23 and the third transmission line 24, the propagation mode of the even mode and the odd mode are used. Propagation mode occurs.
In the phase shifter 1, and the propagation velocity V _e of the even mode in the high-frequency signal RF _2, phase of the high frequency signal RF ₂ corresponding to the difference ΔV between the propagation velocity V _o of the odd mode in the high-frequency signal is realized.
Further, each of the first open stub 27a and the second open stub 27b, to act as increase the propagation velocity V _e of the even mode in the high-frequency signal RF _2, the even mode propagation velocity V _e and the odd mode it is possible to adjust the difference ΔV between the propagation velocity V _o. Therefore, a desired phase shift amount ps can be realized without increasing the degree of coupling of the coupling line 22.
Depending on the respective stub length of the first open stub 27a and the second open stub 27b, the propagation velocity V _e of the even mode is changed by changing the stub length, to achieve a desired phase shift ps be able to.
In the phase shifter 1 shown in FIG. 6, _{the phase difference Δφ between the passing phase φ 1} and the passing phase φ ₂ is adjusted to, for example, 180 degrees × n (n = 1, 2, ...).
The stub lengths of the first open stub 27a and the second open stub 27b may be any one that satisfies the condition of _{0.5 × θ 1 or less.}

FIG. 7 is an explanatory diagram showing each circuit pattern in the reference phase circuit 10 and the relative phase circuit 20.
FIG. 7A shows the circuit pattern of the reference phase circuit 10.
FIG. 7B shows a relative phase circuit 20 without a first open stub 27a and a second open stub 27b. In FIG. 7B, the relative phase circuit 20 is referred to as “relative phase circuit A”.
FIG. 7C shows a relative phase circuit 20 in which each of the first open stub 27a and the second open stub 27b is arranged on the same side as the coupling line 22. In FIG. 7C, the relative phase circuit 20 is referred to as “relative phase circuit B”.
FIG. 7D shows a relative phase circuit 20 in which each of the first open stub 27a and the second open stub 27b is arranged on the opposite side of the coupling line 22, as in the relative phase circuit 20 shown in FIG. ing. In FIG. 7D, the relative phase circuit 20 is referred to as “relative phase circuit C”.

FIG. 8 is an explanatory diagram showing simulation results of each group delay characteristic in the circuit pattern of the reference phase circuit 10, the circuit pattern of the relative phase circuit A, the circuit pattern of the relative phase circuit B, and the circuit pattern of the relative phase circuit C. ..
In FIG. 8, the horizontal axis is frequency and the vertical axis is group delay.
As shown in FIG. 8, the group delay of the relative phase circuit B is larger than the group delay of the relative phase circuit A.
Further, as shown in FIG. 8, the group delay of the relative phase circuit C is further larger than the group delay of the relative phase circuit B. The group delay of the relative phase circuit C is a frequency of about 20 [GHz], which is 65 [psec], which is substantially the same as the group delay of the reference phase circuit 10.
The group delay of the relative phase circuit A <the group delay of the relative phase circuit B <the group delay of the relative phase circuit C The phenomenon that the group delay of the relative phase circuits B and C becomes larger than the group delay of the relative phase circuit A is the first phenomenon. Each of the open stub 27a and the second open stub 27b is generated by the electromagnetic field coupling with the coupling line 22 so that the propagation speed of the even-mode current flowing into the coupling line 22 becomes high.

FIG. 9 is an explanatory diagram showing simulation results of each passing amplitude characteristic in the circuit pattern of the reference phase circuit 10, the circuit pattern of the relative phase circuit A, the circuit pattern of the relative phase circuit B, and the circuit pattern of the relative phase circuit C. ..
In FIG. 9, the horizontal axis is the frequency and the vertical axis is the passing amplitude.
At a frequency of 21 [GHz] or less, the passing amplitude of the relative phase circuits B and C is larger than the passing amplitude of the relative phase circuit A. At a frequency of 21 [GHz] or less, the passing amplitude of the relative phase circuit A is −1.0 [dB] or more. On the other hand, at a frequency of 21 [GHz] or less, the passing amplitude of the relative phase circuits B and C is −0.5 [dB] or more.
Therefore, at a frequency of 21 [GHz] or less, the reflection mismatch of the relative phase circuits B and C is improved as compared with the reflection mismatch of the relative phase circuit A.

FIG. 10 is an explanatory diagram showing simulation results of the respective phase differences Δφ in the phase shifter 1 provided with the relative phase circuit A, the phase shifter 1 provided with the relative phase circuit B, and the phase shifter 1 provided with the relative phase circuit C. be.
In FIG. 10, the horizontal axis is the frequency and the vertical axis is the phase difference Δφ.
In FIG. 10, the phase shifter 1 provided with the relative phase circuit A is referred to as “phase shifter A”, the phase shifter 1 provided with the relative phase circuit B is referred to as “phase shifter B”, and the relative phase circuit C is indicated. The phase shifter 1 provided with the above is referred to as "phase shifter C".
As shown in FIG. 10, the phase difference Δφ of the phase shifter A is 180 degrees at a frequency of about 16.5 [GHz], and the phase difference Δφ of the phase shifter B is as shown in FIG. , 180 degrees at a frequency of about 17.4 [GHz].
As shown in FIG. 10, the phase difference Δφ of the phase shifter C is 180 degrees at a frequency of 19 [GHz] to 21 [GHz].
As shown in FIG. 10, the phase shifter C can realize a phase difference of 180 degrees in a wider band than each of the phase shifter A and the phase shifter B.

In the second embodiment as described above, the first phase shift adjustment circuit 26a is connected to one end of the first transmission line 21 and is electromagnetically coupled to the coupling line 22 to propagate an even mode in a high frequency signal. A first open stub 27a for accelerating the speed is provided, and a second phase shift adjusting circuit 26b is connected to a fourth transmission line 25 at one end and is electromagnetically coupled to the coupling line 22 in a high frequency signal. The phase shifter 1 shown in FIG. 6 is configured to include a second open stub 27b that increases the propagation speed of the even mode. Therefore, the phase shifter 1 shown in FIG. 6 can realize a desired phase shift amount without increasing the degree of coupling of the coupling line 22 as in the phase shifter 1 shown in FIG.

The phase shifter 1 shown in FIG. 6 includes a relative phase circuit C as the relative phase circuit 20. Phase shifter 1, a relative phase circuit 20, even if provided with a relative phase circuit B, as shown in FIG. 8, it is possible to increase the propagation velocity V _e of the even mode in the high-frequency signal RF _2.
Therefore, the phase shifter 1 may include the relative phase circuit B as the relative phase circuit 20.

Embodiment 3.
In the third embodiment, the phase shifter 1 shown in FIG. 1 or the strain compensation circuit including the phase shifter 1 shown in FIG. 6 will be described.

FIG. 11 is a configuration diagram showing a strain compensation circuit according to the third embodiment.
The distortion compensation circuit shown in FIG. 11 includes a power distributor 31, a first phase shifter 32, a sixth transmission line 33, a seventh transmission line 34, a second phase shifter 35, a power combiner 36, and a direct current. It includes a bias supply resistor 39, a diode 40, and a DC bias supply resistor 41.
The input terminal 30 is a terminal to which a high frequency signal RF is given from the outside.

The power distributor 31 is realized by, for example, a T-branch line or a Wilkinson distributor.
The power distributor 31 distributes the high frequency signal RF given to the input terminal 30 into two.
_{The power distributor 31 outputs the high frequency signal RF 1} , which is one of the high frequency signals after the two distributions, to the fifth transmission line 12 of the first phase shifter 32 via the input terminal 2a. do.
_{The power distributor 31 outputs the high frequency signal RF 2} , which is the other high frequency signal among the high frequency signals after the two distributions, to the first transmission line 21 of the first phase shifter 32 via the input terminal 2b. do.

The first phase shifter 32 is a phase shifter having the same configuration as the phase shifter 1 shown in FIG.
_{The high frequency signal RF 1} output from the power distributor 31 propagates in the fifth transmission line 12 in the first phase shifter 32.
_{The high frequency signal RF 2} output from the power distributor 31 propagates in each of the first transmission line 21, the coupling line 22, and the fourth transmission line 25 in the first phase shifter 32.
In the distortion compensation circuit shown in FIG. 11, the first phase shifter 32 is a phase shifter having the same configuration as the phase shifter 1 shown in FIG. However, this is only an example, and the first phase shifter 32 may be a phase shifter having the same configuration as the phase shifter 1 shown in FIG.

The sixth transmission line 33 includes

DC block capacitors

33a and 33b.
In the sixth transmission line 33, the high frequency signal RF ₁ propagating through the fifth transmission line 12 in the first phase shifter 32 propagates.
One end of the DC block capacitor 33a is connected to the other end of the fifth transmission line 12 in the first phase shifter 32 via the output terminal 3a, and the other end of the DC block capacitor 33a is for the DC block. It is connected to one end of the capacitor 33b and the like.
The DC block capacitor 33a blocks the flow of DC current so that the DC current does not flow to the first phase shifter 32.
One end of the DC block capacitor 33b is connected to the other end of the DC block capacitor 33a and the like, and the other end of the DC block capacitor 33b is the first in the second phase shifter 35 via the input terminal 2a. It is connected to one end of the transmission line 21.
The DC block capacitor 33b blocks the flow of DC current so that the DC current does not flow to the second phase shifter 35.

The seventh transmission line 34 includes

DC block capacitors

34a and 34b.
_{In the seventh transmission line 34, the high frequency signal RF 2} propagating through each of the first transmission line 21, the coupling line 22, and the fourth transmission line 25 in the first phase shifter 32 propagates.
One end of the DC block capacitor 34a is connected to the other end of the fourth transmission line 25 in the first phase shifter 32 via the output terminal 3b, and the other end of the DC block capacitor 34a is for the DC block. It is connected to one end of the capacitor 34b and the like.
The DC block capacitor 34a blocks the flow of DC current so that the DC current does not flow to the first phase shifter 32.
One end of the DC block capacitor 34b is connected to the other end of the DC block capacitor 34a and the like, and the other end of the DC block capacitor 34b is the fifth phase shifter 35 in the second phase shifter 35 via the input terminal 2b. It is connected to one end of the transmission line 12.
The DC block capacitor 34b blocks the flow of DC current so that the DC current does not flow to the second phase shifter 35.

The second phase shifter 35 is a phase shifter having the same configuration as the phase shifter 1 shown in FIG.
_{The high frequency signal RF 1} that has propagated through the sixth transmission line 33 propagates in each of the first transmission line 21, the coupling line 22, and the fourth transmission line 25 in the second phase shifter 35.
_{The high frequency signal RF 2} propagating through the seventh transmission line 34 propagates in the fifth transmission line 12 in the second phase shifter 35.
In the distortion compensation circuit shown in FIG. 11, the second phase shifter 35 is a phase shifter having the same configuration as the phase shifter 1 shown in FIG. However, this is only an example, and the second phase shifter 35 may be a phase shifter having the same configuration as the phase shifter 1 shown in FIG.

The power synthesizer 36 is realized by, for example, a Wilkinson synthesizer.
One end of the power combiner 36 is connected to the other end of the fourth transmission line 25 in the second phase shifter 35 via the output terminal 3a, and the other end of the power combiner 36 is connected via the output terminal 3b. It is connected to the other end of the fifth transmission line 12 in the second phase shifter 35.
_{The power combiner 36 is in the high frequency signal RF 1} and the second phase shifter 35 that have propagated through the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the second phase shifter 35, respectively. _{The high frequency signal RF 2} propagating on the fifth transmission line 12 is combined with the high frequency signal RF 2.
The power synthesizer 36 outputs the combined signal RF'of the _{high frequency signal RF 1} and the high frequency signal RF _{2 to the output terminal 37.}
The output terminal 37 is a terminal for outputting the combined signal RF'to the outside.

The DC power supply 38 applies a positive DC voltage to the anode terminal of the diode 40 via the DC bias supply resistor 39.
One end of the DC bias supply resistor 39 is connected to the DC power supply 38.
The other end of the DC bias supply resistor 39 is connected to the anode terminal of the diode 40, the other end of the DC block capacitor 33a, and one end of the DC block capacitor 33b.

The diode 40 is inserted between the sixth transmission line 33 and the seventh transmission line 34.
That is, the anode terminal of the diode 40 is connected to the other end of the DC bias supply resistor 39, the other end of the DC block capacitor 33a, and one end of the DC block capacitor 33b. The cathode terminal of the diode 40 is connected to one end of the DC bias supply resistor 41, the other end of the DC block capacitor 34a, and one end of the DC block capacitor 34b.
A direct current supplied from the direct current power source 38 is applied to the diode 40 in the forward direction.
One end of the DC bias supply resistor 41 is connected to the cathode terminal of the diode 40, the other end of the DC block capacitor 34a, and one end of the DC block capacitor 34b.
The other end of the DC bias supply resistor 41 is connected to the ground.
A direct current supplied from the direct current power source 38 may be applied to the diode 40 in the forward direction, and a negative direct current voltage from the direct current power source 38 may be applied to the cathode terminal of the diode 40.

Next, the operation of the distortion compensation circuit shown in FIG. 11 will be described.
The power distributor 31 distributes the high frequency signal RF given to the input terminal 30 into two.
_{The power distributor 31 outputs the high frequency signal RF 1} , which is one of the high frequency signals after the two distributions, to the fifth transmission line 12 of the first phase shifter 32 via the input terminal 2a. do.
_{The power distributor 31 outputs the high frequency signal RF 2} , which is the other high frequency signal among the high frequency signals after the two distributions, to the first transmission line 21 of the first phase shifter 32 via the input terminal 2b. do.

The first phase shifter 32 operates in the same manner as the phase shifter 1 shown in FIG.
Therefore, the high frequency signal RF ₁ output from the power distributor 31 propagates through the fifth transmission line 12 in the first phase shifter 32 and reaches the sixth transmission line 33.
Further, the high frequency signal RF ₂ output from the power distributor 31 propagates through each of the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the first phase shifter 32, and the seventh It reaches the transmission line 34.
Each of the first open stub 27a and the second open stub 27b of the first phase shifter 32, acts to increase the propagation velocity V _e of the even mode in the high-frequency signal RF _2.

The high frequency signal RF ₁ that has reached the sixth transmission line 33 propagates on the sixth transmission line 33.
At this time, the DC block capacitor 33a blocks the flow of the DC current so that the DC current supplied from the DC power supply 38 does not flow to the first phase shifter 32.
Further, the DC block capacitor 33b blocks the flow of the DC current so that the DC current supplied from the DC power supply 38 does not flow to the second phase shifter 35.

The high frequency signal RF ₂ that has reached the seventh transmission line 34 propagates through the seventh transmission line 34.
At this time, the DC block capacitor 34a blocks the flow of the DC current so that the DC current supplied from the DC power supply 38 does not flow to the first phase shifter 32.
Further, the DC block capacitor 34b blocks the flow of the DC current so that the DC current supplied from the DC power supply 38 does not flow to the second phase shifter 35.

The second phase shifter 35 operates in the same manner as the phase shifter 1 shown in FIG.
_{The high-frequency signal RF 1} propagating through the sixth transmission line 33 propagates through each of the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the second phase shifter 35, and is a power combiner. Reach 36.
_{Further, the high frequency signal RF 2} propagating through the seventh transmission line 34 propagates through the fifth transmission line 12 in the second phase shifter 35 and reaches the power combiner 36.
Each of the first open stub 27a and the second open stub 27b in the second phase shifter 35 acts to increase the propagation velocity V _e of the even mode in the high-frequency signal RF _1.

_{The power combiner 36 includes a high frequency signal RF 1} propagating on each of the first transmission line 21, the coupling line 22 and the fourth transmission line 25 in the second phase shifter 35, and the second phase shifter 35. _{The high frequency signal RF 2} propagating through the fifth transmission line 12 in the above is combined with the high frequency signal RF 2.
The power synthesizer 36 outputs the combined signal RF'of the _{high frequency signal RF 1} and the high frequency signal RF _{2 to the output terminal 37.}
In the distortion compensation circuit shown in FIG. 11, the degree of coupling of the coupling line 22 in the first phase shifter 32 and the degree of coupling of the coupling line 22 in the second phase shifter 35 are the same. _{Further, the phase shift amount of the high frequency signal RF 2} by the first open stub 27a and the second open stub 27b in the first phase shifter 32, and the first open stub 27a and the second in the second phase shifter 35. It is assumed that the phase shift amount of the _{high frequency signal RF 1} by the open stub 27b of 2 is the same as the phase shift amount. In this case, the high frequency signal RF ₁ and the high frequency signal RF ₂ synthesized by the power synthesizer 36 are signals having the same phase.

The DC current output from the DC power supply 38 flows to the ground via the DC bias supply resistor 39, the diode 40, and the DC bias supply resistor 41.
For example, the pre-distortion signal for compensating the distortion of the high-frequency signal RF given to the input terminal 30 by the DC current output from the DC power supply 38 flowing through the diode 40 is the high-frequency signal RF ₁ and the high-frequency signal RF ₂ , respectively. Can be given to.
For example, if the high frequency signal RF given to the input terminal 30 is a high frequency signal amplified by an amplifier (not shown), the high frequency signal RF may be distorted.
The pre-distortion signal is a signal having an amplitude distortion characteristic opposite to the amplitude distortion characteristic of the high-frequency signal RF and having a phase distortion characteristic opposite to the phase distortion characteristic of the high-frequency signal RF.
Each of the amplitude and the phase in the pre-distortion signal can be controlled by the direct current supplied from the direct current power source 38 to the diode 40. Further, each of the amplitude and the phase in the pre-distortion signal can also be controlled by the respective resistance values of the DC bias supply resistor 39 and the DC bias supply resistor 41.

In the distortion compensation circuit shown in FIG. 11, a direct current flows through the diode 40 to compensate for the distortion of the high frequency signal RF after amplification by an amplifier (not shown). However, this is only an example, and the DC current flows through the diode 40 to compensate for the distortion of the signal after amplification by an amplifier (not shown) that amplifies the combined signal RF'output from the output terminal 37, for example. You can also.

FIG. 12 is an explanatory diagram showing a simulation result of the relative gain characteristic of the distortion compensation circuit with respect to the electric power of the high frequency signal RF given to the input terminal 30.
FIG. 13 is an explanatory diagram showing a simulation result of the phase characteristic of the distortion compensation circuit for the power of the high frequency signal RF given to the input terminal 30.
The frequency of the high-frequency signal according to the simulation results shown in FIGS. 12 and 13 has a center frequency of about 20 [GHz] as a center frequency of f ₀ and a specific band of _{0.8f 0} to 1.25f _{0 as 45%.} Then, the relative gain characteristic is calculated every _{0.25f 0 step.}
Further, the power of the high frequency signal RF given to the input terminal 30 is in the range of −20 [dBm] to +10 [dBm].

FIG. 14 is an explanatory diagram showing a calculation result of the amplitude fluctuation amount characteristic of the distortion compensation circuit with respect to the normalized frequency. The calculation result of the amplitude fluctuation amount characteristic is calculated based on the simulation result shown in FIG.
FIG. 15 is an explanatory diagram showing a calculation result of the phase fluctuation amount characteristic of the distortion compensation circuit with respect to the normalized frequency. The calculation result of the phase fluctuation amount characteristic is calculated based on the simulation result shown in FIG.
In FIGS. 14 and 15, the solid line indicates the strain compensation circuit shown in FIG. 11, and the broken line indicates the strain compensation circuit described in Patent Document 1.
The distortion compensation circuit described in Patent Document 1 is a general distortion compensation circuit that does not include the first phase shifter 32 and the second phase shifter 35.
[Patent Document 1] Japanese Unexamined Patent Publication No. 2010-233055

As shown in FIG. 14, the amplitude fluctuation amount of the distortion compensation circuit shown in FIG. 11 takes a positive value of 0.5 [dB / dB] or more in the range of _{0.8f 0} to 1.25f _0. Therefore, the amplitude distortion characteristic of monotonically increasing is obtained.
Phase variation amount of the distortion compensation circuit shown in FIG. 11, as shown in FIG. 15, in the range of 0.85F ₀ of fractional bandwidth of 30% 1.15F _0, can be realized about -5 [deg / dB] There is. Therefore, the strain compensation circuit shown in FIG. 11 has a wide band characteristic.
Distortion compensating circuit described in Patent Document 1, the largest amount of phase change at the center frequency f ₀ has become (-13 [degrees / dB]), farther from the center frequency f _0, and the amount of phase variation becomes smaller There is.
From the above, the distortion compensation circuit shown in FIG. 11 can realize a wide-band amplitude distortion characteristic and a phase distortion characteristic in a high frequency band.

In the present disclosure, any combination of the embodiments can be freely combined, any component of the embodiment can be modified, or any component can be omitted in each embodiment.

The present disclosure is suitable for a phase shifter and a strain compensation circuit provided with the phase shifter.

1 Phase shifter, 2a, 2b input terminal, 3a, 3b output terminal, 10 reference phase circuit, 11 fifth transmission line, 12a, 12b, 12c, 12d, 12e transmission line, 20 relative phase circuit, 21 first Transmission line, 22 coupled line, 23 second transmission line, 24 third transmission line, 25 fourth transmission line, 26 phase shift adjustment circuit, 26a first phase shift adjustment circuit, 26b second phase shift adjustment Circuit, 27a 1st open stub, 27b 2nd open stub, 30 input terminal, 31 power distributor, 32 1st phase shifter, 33 6th transmission line, 33a, 33b DC block capacitor, 34th 7 transmission lines, 34a, 34b DC block capacitors, 35 second phase shifters, 36 power synthesizers, 37 output terminals, 38 DC power supplies, 39 DC bias supply resistors, 40 diodes, 41 DC bias supply resistors ..

Claims

A first transmission line in which a high-frequency signal given to one end propagates to the other end,
It has a second transmission line to which the other end and one end of the first transmission line are connected, and a third transmission line to which the other end and one end of the second transmission line are connected. When a high-frequency signal propagating through the first transmission line propagates through each of the second transmission line and the third transmission line, a coupled line in which an even mode propagation mode and an odd mode propagation mode occur. ,
A fourth transmission line in which the other end and one end of the third transmission line are connected and a high frequency signal propagating through the coupled line propagates.
Of the first transmission line and the fourth transmission line, one end is connected to one or more transmission lines, and the transfer is provided with a phase shift adjustment circuit for adjusting the propagation speed of even mode in a high frequency signal. Ai device.
The phase shift adjustment circuit is
A first phase shift adjustment circuit, which is connected to one end of the first transmission line and adjusts the propagation speed of even mode in a high frequency signal,
The phase shifter according to claim 1, wherein one end is connected to the fourth transmission line, and a second phase shift adjustment circuit for adjusting the propagation speed of an even mode in a high frequency signal is provided. ..
The first phase shift adjustment circuit is
One end is connected to the first transmission line, and the first open stub is provided, which accelerates the propagation speed of the even mode in a high frequency signal by electromagnetically coupling with the coupled line.
The second phase shift adjustment circuit is
A claim characterized in that one end is connected to the fourth transmission line, and a second open stub is provided which increases the propagation speed of the even mode in a high frequency signal by electromagnetically coupling with the coupled line. Item 1. The phase shifter according to item 1.
The first open stub is arranged on the opposite side of the coupling line with the first transmission line interposed therebetween.
The phase shifter according to claim 3, wherein the second open stub is arranged on the opposite side of the coupling line with the fourth transmission line interposed therebetween.
The phase shifter according to claim 1, further comprising a fifth transmission line in which a high frequency signal given to one end propagates to the other end.
A power distributor that divides high-frequency signals into two,
A phase shifter having the same configuration as that of the phase shifter according to claim 5, wherein one of the high frequency signals after the two distributions by the power distributor propagates through the fifth transmission line and the other. A first phase shifter in which a high-frequency signal propagates through the first transmission line, the coupling line, and the fourth transmission line, respectively.
A sixth transmission line propagating the high frequency signal propagating through the fifth transmission line in the first phase shifter, and a sixth transmission line propagating.
A seventh transmission line propagating a high frequency signal propagating through each of the first transmission line, the coupling line, and the fourth transmission line in the first phase shifter.
A phase shifter having the same configuration as that of the phase shifter according to claim 5, wherein the high frequency signal propagating through the sixth transmission line is the first transmission line, the coupling line, and the fourth transmission line. A second phase shifter in which a high-frequency signal propagating through each of the above 7th transmission lines propagates through the fifth transmission line, and
The high frequency signal propagating in each of the first transmission line, the coupling line, and the fourth transmission line in the second phase shifter and the fifth transmission line in the second phase shifter are propagated. A power synthesizer that synthesizes the high-frequency signals that have been used,
Distortion compensation inserted between the sixth transmission line and the seventh transmission line and comprising a diode to which a direct current supplied from a direct current is applied in the forward direction. circuit.