WO2021218800A1 - 电子设备 - Google Patents

电子设备 Download PDF

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Publication number
WO2021218800A1
WO2021218800A1 PCT/CN2021/089245 CN2021089245W WO2021218800A1 WO 2021218800 A1 WO2021218800 A1 WO 2021218800A1 CN 2021089245 W CN2021089245 W CN 2021089245W WO 2021218800 A1 WO2021218800 A1 WO 2021218800A1
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WO
WIPO (PCT)
Prior art keywords
strip conductor
antenna
current
resonance
projection
Prior art date
Application number
PCT/CN2021/089245
Other languages
English (en)
French (fr)
Inventor
王汉阳
侯猛
余冬
吴鹏飞
张小伟
师传波
Original Assignee
华为技术有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 华为技术有限公司 filed Critical 华为技术有限公司
Priority to CN202180028880.1A priority Critical patent/CN115413387A/zh
Priority to US17/921,273 priority patent/US20230170609A1/en
Priority to EP21796532.6A priority patent/EP4131651A4/en
Publication of WO2021218800A1 publication Critical patent/WO2021218800A1/zh

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H01Q1/243—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use with built-in antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/12—Supports; Mounting means
    • H01Q1/22—Supports; Mounting means by structural association with other equipment or articles
    • H01Q1/24—Supports; Mounting means by structural association with other equipment or articles with receiving set
    • H01Q1/241—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM
    • H01Q1/242—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use
    • H01Q1/245—Supports; Mounting means by structural association with other equipment or articles with receiving set used in mobile communications, e.g. GSM specially adapted for hand-held use with means for shaping the antenna pattern, e.g. in order to protect user against rf exposure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/10—Resonant slot antennas
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/307—Individual or coupled radiating elements, each element being fed in an unspecified way
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/307—Individual or coupled radiating elements, each element being fed in an unspecified way
    • H01Q5/342—Individual or coupled radiating elements, each element being fed in an unspecified way for different propagation modes
    • H01Q5/357—Individual or coupled radiating elements, each element being fed in an unspecified way for different propagation modes using a single feed point
    • H01Q5/364—Creating multiple current paths
    • H01Q5/371—Branching current paths
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q5/00—Arrangements for simultaneous operation of antennas on two or more different wavebands, e.g. dual-band or multi-band arrangements
    • H01Q5/30—Arrangements for providing operation on different wavebands
    • H01Q5/378—Combination of fed elements with parasitic elements
    • H01Q5/385—Two or more parasitic elements
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/30—Resonant antennas with feed to end of elongated active element, e.g. unipole
    • H01Q9/42—Resonant antennas with feed to end of elongated active element, e.g. unipole with folded element, the folded parts being spaced apart a small fraction of the operating wavelength

Definitions

  • This application relates to the field of antenna technology, in particular to an electronic device.
  • the antenna of the electronic device provided by the technical solution of the present application can excite multiple resonant modes, and each resonant mode can meet the requirement of low SAR value.
  • the electronic device includes a back cover, a circuit board, a bracket, a radio frequency transceiver circuit, a first antenna and a second antenna.
  • the circuit board and the radio frequency transceiver circuit are located on the same side of the back cover, and the bracket is fixed between the circuit board and the back cover. It is understandable that the bracket can be fixed to the circuit board or the back cover.
  • the first antenna includes a first strip conductor.
  • the first strip-shaped conductor is fixed to the bracket. It is understandable that the first strip conductor can be fixed on the surface of the bracket or embedded in the bracket.
  • the first strip conductor includes a first grounding portion, a second grounding portion, and a feeding portion.
  • the first grounding part and the second grounding part are the two ends of the first strip conductor respectively. Both the first grounding part and the second grounding part are grounded through the circuit board.
  • the feeding part is located between the first grounding part and the second grounding part, and is electrically connected to the radio frequency transceiver circuit.
  • the clearance area of the first antenna is formed between the surface of the circuit board facing the back cover and the first strip conductor.
  • the second antenna includes a second strip conductor.
  • the second strip conductor is fixed to the back cover or bracket. It is understandable that the second strip conductor can be fixed on the surface of the back cover or embedded in the back cover. The second strip conductor can be fixed on the surface of the bracket or embedded in the bracket.
  • the second strip conductor includes a first end and a second end disposed away from the first end.
  • the first end of the second strip conductor is electrically connected to the first ground part of the first strip conductor.
  • the second end of the second strip conductor is not grounded, that is, the second end of the second strip conductor is an open end.
  • the clearance area of the second antenna is formed between the surface of the circuit board facing the back cover and the second strip conductor.
  • the first antenna can excite a differential mode antenna mode.
  • the current distribution of the differential mode mode excited by the first antenna is mainly as follows: the first current flowing from the first grounding part to the feeding part on the first strip conductor and the second current flowing from the second grounding part to the feeding part .
  • the direction of the first current and the second current on the first strip of conductor are opposite, and the current intensity of the first current and the current intensity of the second current can be roughly the same.
  • the phase of the magnetic field at the feeding part is opposite, and the The amplitude can be roughly cancelled out.
  • the magnetic field is mainly distributed on both sides of the feeding part, and two SAR hot spots are formed on both sides of the feeding part.
  • the energy of the radiated electromagnetic waves is relatively dispersed, and the SAR value of the differential mode mode excited by the first antenna is relatively low.
  • the second antenna can excite a common mode antenna mode.
  • the current distribution of the common mode mode excited by the second antenna is mainly as follows: a third current flowing on the second strip conductor from the second end of the second strip conductor to the first end of the second strip conductor. It is understandable that the third current on the second strip conductor can flow into the circuit board through the first grounding part, so that the intensity of the current on the second strip conductor can be greatly reduced. At this time, the intensity of the magnetic field generated by the second strip conductor is also relatively small, and the SAR value of the common mode mode excited by the second antenna is relatively low.
  • the composite antenna can excite two resonant modes under power feeding, so as to achieve broadband coverage while also realizing two modes.
  • the SAR value of is low, and the resonant mode of the first antenna can generate two SAR hot spots.
  • the first end of the second strip conductor and the first ground part of the first strip conductor feed directly. It is understandable that the direct feed refers to that the first end of the second strip conductor is connected to the first ground part of the first strip conductor, and the radio frequency signal is directly fed to the second strip conductor through the first ground part.
  • the first end of the second strip conductor is indirectly coupled to the first ground part of the first strip conductor for power feeding.
  • the distance between the first grounding portion and the end surface of the first strip conductor is in the range of 0 to 5 millimeters.
  • the distance between the first ground portion and the end surface of the first strip conductor is in the range of 0 to 2.5 mm.
  • the distance between the first grounding portion and the end surface of the first strip conductor is 0 to 0.12 ⁇ .
  • ⁇ is the wavelength of the signal radiated by the antenna.
  • the distance between the first grounding portion and the end surface of the first strip conductor is 0 to 0.06 ⁇ .
  • ⁇ is the wavelength of the signal radiated by the antenna.
  • the distance between the second ground portion and the end surface of the first strip conductor is in the range of 0 to 5 mm.
  • the distance between the second ground portion and the end surface of the first strip conductor is in the range of 0 to 2.5 mm.
  • the distance between the second ground portion and the end surface of the first strip conductor is 0 to 0.12 ⁇ .
  • ⁇ is the wavelength of the signal radiated by the antenna.
  • the distance between the second ground portion and the end surface of the first strip conductor is 0 to 0.06 ⁇ .
  • ⁇ is the wavelength of the signal radiated by the antenna.
  • the center distance between the feeding part and the first grounding part is a first value.
  • the center distance between the feeding part and the second grounding part is the second value.
  • the ratio of the first value to the second value is in the range of 0.8 to 1.2.
  • the ratio of the first value to the second value is in the range of 0.8 to 1.2, the overall symmetry of the first strip conductor is better.
  • the current intensity of the first current on the first strip conductor is approximately the same as the current intensity of the second current.
  • the phase of the magnetic field at the feeding portion is opposite, and the amplitude of the magnetic field is roughly cancelled out.
  • the magnetic field is mainly distributed on both sides of the feeding part.
  • the SAR value of the differential mode mode excited by the first antenna is relatively low.
  • the ratio of the first value to the second value may not be in the range of 0.8 to 1.2.
  • the overall symmetry of the first-shaped conductor is poor. At this time, this structural asymmetry can be compensated by the matching circuit of the first antenna, so that in the current distribution of the differential mode mode excited by the first antenna, the current intensity of the first current on the first strip conductor is equal to The current intensity of the second current can be approximately the same, thereby ensuring that the SAR value of the differential mode mode excited by the first antenna is relatively low.
  • the projection of the first strip conductor on the surface of the circuit board is the first projection.
  • the projection of the second strip conductor on the surface of the circuit board is the second projection.
  • the area of the overlapping area of the first projection and the second projection is in the range of 0-16 square millimeters. It can be understood that, under this size, the stability of the electrical connection between the first end of the second strip conductor and the first ground part of the first strip conductor is better.
  • the third current on the second strip conductor can better flow into the circuit board through the first grounding part, so that the SAR value of the common mode mode excited by the second antenna is lower.
  • the second antenna further includes a third strip conductor.
  • the third strip conductor is fixed to the back cover or bracket. It is understandable that the third strip-shaped conductor can be fixed on the surface of the back cover or embedded in the back cover. The third strip conductor can be fixed on the surface of the bracket or embedded in the bracket.
  • the third strip conductor includes a first end and a second end disposed away from the first end.
  • the first end of the third strip conductor is electrically connected to the second ground part of the first strip conductor.
  • the second end of the third strip conductor is not grounded, that is, the second end of the third strip conductor is an open end.
  • the clearance area of the second antenna is formed between the surface of the circuit board facing the back cover and the third strip conductor.
  • the third strip conductor also excites a common mode antenna mode .
  • the main current distribution of the common mode mode is as follows: a fourth current flowing on the third strip conductor from the second end of the third strip conductor to the first end of the third strip conductor.
  • the fourth current on the third strip conductor can flow into the circuit board through the second ground part, so that the current intensity on the third strip conductor is greater The degree is weakened.
  • the intensity of the magnetic field generated by the third strip conductor is also lower, and the SAR value of the common mode mode excited by the second antenna is also lower.
  • the third current on the second strip conductor is in the opposite direction to the fourth current on the third strip conductor, and the current intensity can be
  • the realization is roughly the same.
  • the phase of the magnetic field at the feeding part is opposite, and the amplitude of the magnetic field is roughly cancelled out.
  • the magnetic field is mainly distributed on both sides of the feeding part, and two SAR hot spots are formed on both sides of the feeding part.
  • the energy of the radiated electromagnetic waves is relatively dispersed, and the SAR value of the common mode mode is relatively low.
  • the third current on the second strip conductor can flow into the circuit board through the first ground part, and the third strip conductor
  • the fourth current on the upper part can flow into the circuit board through the second grounding part, so that the current intensity on the second strip conductor and the third strip conductor is greatly reduced.
  • the intensity of the magnetic field generated by the second strip conductor and the third strip conductor is also lower, and the SAR value of the common mode mode excited by the second antenna is also lower.
  • the first end of the third strip conductor and the second ground part of the first strip conductor feed directly. It is understandable that the direct feed refers to that the first end of the third strip conductor of the third strip conductor is connected to the second ground part of the first strip conductor, and the radio frequency signal is directly fed to the second ground part through the second ground part.
  • the second strip conductor refers to that the first end of the third strip conductor of the third strip conductor is connected to the second ground part of the first strip conductor, and the radio frequency signal is directly fed to the second ground part through the second ground part.
  • the second angle is in the range of 90° to 270°
  • the second end of the third strip conductor is arranged in a direction away from the first strip conductor.
  • the first strip conductor and the third strip conductor transmit and receive electromagnetic wave signals
  • the first strip conductor and the third strip conductor are not easy to interfere and influence each other, thereby ensuring that the first antenna and the second antenna have a relatively high Good radiation performance.
  • the first angle and the second angle are both equal to 180°.
  • the length of the second strip conductor is equal to the length of the third strip conductor.
  • the second strip conductor and the third strip conductor are related to the feeder Partially symmetrical.
  • the resonant frequency of the common mode mode excited by the third strip conductor is equal to the resonant frequency of the common mode mode excited by the second strip conductor.
  • the second antenna can excite a common mode mode resonance mode: the second strip conductor and the third strip conductor jointly excite a common mode mode. In this way, in this implementation manner, the first antenna and the second antenna excite two antenna modes, which is beneficial for the antennas to achieve broadband coverage settings.
  • the second antenna further includes a fourth strip conductor and a fifth strip conductor.
  • the fourth strip conductor and the fifth strip conductor are both fixed to the back cover or bracket. It is understandable that the fourth strip conductor and the fifth strip conductor can be fixed on the surface of the back cover or embedded in the back cover. The fourth strip conductor and the fifth strip conductor can be fixed on the surface of the bracket or embedded in the bracket.
  • the fourth strip conductor and the fifth strip conductor jointly excite the current distribution in the common mode.
  • the fifth current on the fourth strip conductor flows into the circuit board through the second grounding part, and the current on the sixth strip conductor flows into the circuit board.
  • the sixth current flows into the circuit board through the second grounding part, so that the current intensity on the fourth strip conductor and the fifth strip conductor is greatly reduced.
  • the strength of the magnetic field generated by the fourth strip conductor and the fifth strip conductor is also small, and the SAR value of the common mode mode excited by the second antenna is low.
  • the connecting end of the fourth strip conductor and the fifth strip conductor and the second grounding part are directly fed.
  • the projection of the fourth strip conductor on the surface of the circuit board is the fourth projection.
  • the angle between the fourth projection and the first projection is equal to 90°.
  • the projection of the fifth strip conductor on the surface of the circuit board is the fifth projection.
  • the angle between the fifth projection and the first projection is equal to 90°.
  • the second strip conductor and the third strip conductor can be symmetrical to the fourth strip conductor and the fifth strip conductor with respect to the feeding part.
  • the current excited by the first strip conductor includes a first current flowing from the first grounding part to the feeding part, and a first current flowing from the second grounding part to the feeding part. Two current.
  • Fig. 5b shows the current distribution diagram of the common mode mode of the wire antenna provided by the present application
  • FIG. 8 is a partial structural diagram of an embodiment of the composite antenna of the electronic device shown in FIG. 1; FIG.
  • Fig. 11b is a schematic diagram of the current flow of the composite antenna shown in Fig. 8 at resonance "1";
  • FIG. 11f is a schematic projection view of another embodiment of the first strip conductor, the second strip conductor, and the third strip conductor shown in FIG. 7 on the circuit board;
  • Fig. 11g is a diagram showing the relationship between reflection coefficient and frequency of the composite antenna shown in Fig. 11f in the frequency band of 3 to 6 GHz;
  • Fig. 11i is a diagram showing the relationship between reflection coefficient and frequency of the composite antenna shown in Fig. 11h in the frequency band of 3 to 6 GHz;
  • Fig. 16b is a schematic diagram of the current flow of the composite antenna shown in Fig. 15 at resonance "1";
  • Fig. 16c is a schematic diagram of the current flow of the antenna shown in Fig. 15 at resonance "2";
  • Fig. 16e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 15 at resonance "1";
  • Fig. 16f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 15 at resonance "2";
  • FIG. 17 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. 1; FIG.
  • Fig. 18b is a schematic diagram of the current flow of the composite antenna shown in Fig. 17 at resonance "1";
  • Fig. 18c is a schematic diagram of the current flow of the antenna shown in Fig. 17 at resonance "2";
  • Fig. 18d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 17 at resonance "1";
  • Fig. 18e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 17 at resonance "2";
  • FIG. 19 is a schematic partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. 1;
  • Fig. 22a is a diagram showing the relationship between reflection coefficient and frequency of the composite antenna shown in Fig. 19 in the frequency band of 3 to 6 GHz;
  • Fig. 22c is a schematic diagram of the current flow of the antenna shown in Fig. 19 at resonance "2";
  • Fig. 22d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 19 at resonance "1";
  • Fig. 22e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 19 at resonance "2";
  • FIG. 23 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. 1; FIG.
  • FIG. 24 is a schematic structural diagram of the composite antenna shown in FIG. 23 at another angle
  • FIG. 25 is a schematic projection view of the first strip conductor, the second strip conductor, and the third strip conductor shown in FIG. 23 on the circuit board;
  • Fig. 26b is a schematic diagram of the current flow of the composite antenna shown in Fig. 23 at resonance "1";
  • Fig. 26c is a schematic diagram of the current flow of the antenna shown in Fig. 23 at resonance "2";
  • Fig. 26e is a schematic diagram of the SAR hotspot distribution of the composite antenna shown in Fig. 23 at resonance "2";
  • FIG. 27 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. 1; FIG.
  • Fig. 28a is a diagram showing the relationship between reflection coefficient and frequency of the composite antenna shown in Fig. 27 in the frequency band of 3 to 6 GHz;
  • Fig. 28b is a schematic diagram of the current flow of the composite antenna shown in Fig. 27 at resonance "1";
  • Figure 28d is a schematic diagram of the current flow of the composite antenna shown in Figure 27 at resonance "3"
  • Fig. 28e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 27 at resonance "1";
  • Fig. 28f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 27 at resonance "2";
  • Fig. 28g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 27 at resonance "3".
  • FIG. 1 is a schematic structural diagram of an implementation manner of an electronic device according to an embodiment of the present application.
  • the electronic device 100 can be a mobile phone, a watch, a tablet computer, a laptop computer, a personal digital assistant (PDA), a camera, a personal computer, a notebook computer, a vehicle-mounted device, and a wearable.
  • the electronic device 100 of the embodiment shown in FIG. 1 is described by taking a mobile phone as an example.
  • the width direction of the electronic device 100 is defined as the X axis.
  • the length direction of the electronic device 100 is the Y axis.
  • the thickness direction of the electronic device 100 is the Z axis.
  • the back cover 11 can be fixedly connected to the frame 12 by glue.
  • the back cover 11 and the frame 12 are integrally formed, that is, the back cover 11 and the frame 12 are integrated.
  • FIG. 1 illustrates a structure in which the screen 20 and the casing 10 enclose a substantially rectangular parallelepiped.
  • the screen 20 can be used to display images, text, and the like.
  • the screen 20 includes a protective cover 21 and a display screen 22.
  • the protective cover 21 is laminated on the display screen 22.
  • the protective cover 21 can be arranged close to the display screen 22, and can be mainly used to protect the display screen 22 from dust.
  • the material of the protective cover 21 can be, but is not limited to, glass.
  • FIG. 3 is a partial cross-sectional view of the electronic device shown in FIG. 1 at the line M-M.
  • the circuit board 30 is installed inside the electronic device 100, and the circuit board 30 and the back cover 11 are spaced apart, that is, there is a space between the circuit board 30 and the back cover 11.
  • the housing 10 further includes a middle plate 13.
  • the middle plate 13 is located inside the electronic device 100, and the middle plate 13 is connected to the inner side of the frame 12.
  • the circuit board 30 and the display screen 22 of the screen 20 are respectively fixed on opposite sides of the middle board 13.
  • the circuit board 30 faces the rear cover 11.
  • the middle board 13 can be used to carry the screen 20 and also can be used to carry the circuit board 30.
  • the housing 10 may not include the middle plate 13. At this time, the circuit board 30 can be directly fixed on the screen 20.
  • the electronic device 100 further includes multiple antennas.
  • “plurality” means at least two.
  • the antenna is used to transmit and receive electromagnetic wave signals.
  • the electronic device 100 may communicate with a network or other devices by using one or more of the following communication technologies through an antenna.
  • communication technology includes Bluetooth (BT) communication technology, global positioning system (GPS) communication technology, wireless fidelity (Wi-Fi) communication technology, global system for mobile communications , GSM) communication technology, wideband code division multiple access (WCDMA) communication technology, long term evolution (LTE) communication technology, 5G communication technology, SUB-6G communication technology and other future communication technologies, etc.
  • the electronic device 100 can implement mobile data traffic sharing or wireless network sharing with other devices (for example, mobile phones, watches, tablets, or other devices capable of transmitting and receiving electromagnetic wave signals) through an antenna. For example, when other devices turn on the data traffic sharing network, the electronic device 100 can access the data traffic sharing network of other devices by receiving antenna signals of other devices. In this way, the electronic device 100 will not affect the user experience of the electronic device 100 due to insufficient traffic or the traffic has been stopped.
  • devices for example, mobile phones, watches, tablets, or other devices capable of transmitting and receiving electromagnetic wave signals
  • the electronic device 100 can access the data traffic sharing network of other devices by receiving antenna signals of other devices. In this way, the electronic device 100 will not affect the user experience of the electronic device 100 due to insufficient traffic or the traffic has been stopped.
  • the electronic device 100 may adopt a full-screen industrial design (ID).
  • ID means a huge screen-to-body ratio (usually above 90%).
  • the width of the frame 12 of the full screen is greatly reduced, and the internal components of the electronic device 100, such as the front camera, receiver, fingerprint reader, antenna, etc., need to be re-arranged.
  • the headroom area is reduced, and the antenna space is further compressed.
  • the size, bandwidth, and efficiency of the antenna are interrelated and affect each other. If the size (space) of the antenna is reduced, the efficiency-bandwidth product of the antenna is bound to decrease.
  • a composite antenna composed of a slot antenna and a wire antenna is provided, so that in an environment where the antenna arrangement is tight, the composite antenna of the electronic device 100 can generate multiple resonance modes to achieve wideband coverage, and can Ensure that multiple resonance modes meet the requirements of low SAR values to reduce the impact of electromagnetic wave radiation on the human body.
  • Fig. 4a shows a schematic structural diagram of the slot antenna provided by the present application.
  • the slot antenna may include: a first strip conductor 41 and a circuit board 30.
  • the first strip-shaped conductor 41 is spaced apart from the circuit board 30.
  • the surface 33 of the circuit board 30 and the first strip conductor 41 facing the surface 411 of the circuit board 30 form a first gap 42.
  • Two ends of the first strip conductor 41 are electrically connected to the ground layer of the circuit board 30, and the two ends of the first strip conductor 41 form a first ground portion B and a second ground portion C, respectively.
  • the first strip-shaped conductor 41 includes a feeding portion A.
  • the feeding portion A is located between the first ground portion B and the second ground portion C. Among them, the feeding part A is the part of the first strip conductor 41 where the signal is fed.
  • Figure 4a illustrates the position of the RF signal feed through the arrow.
  • FIG. 4b shows a current distribution diagram of the slot antenna differential mode mode provided by the present application.
  • Figure 4b shows the current distribution of the slot antenna.
  • the current presents a reverse distribution on both sides of the feeding portion A of the first strip conductor 41.
  • the feed structure shown in FIG. 4a may be referred to as a symmetric feed structure.
  • the slot antenna mode shown in Fig. 4b can be called a slot antenna differential mode mode.
  • the current distribution shown in Fig. 4b is called the current of the slot antenna differential mode mode.
  • Fig. 5a shows a schematic structural diagram of the wire antenna provided by the present application.
  • the wire antenna may include a second strip conductor 51 and a circuit board 30.
  • the second strip conductor 42 is spaced apart from the circuit board 30.
  • the surface 33 of the circuit board 30 and the surface 519 of the second strip conductor 51 facing the circuit board 30 form a second gap 31.
  • the middle portion of the second strip conductor 51 forms a feeding portion A.
  • the feeding part A is the part where the radio frequency signal in the second strip conductor 51 is fed.
  • Figure 5a illustrates the position of the RF signal feed through the arrow.
  • both ends of the second strip conductor 51 are open ends, that is, both ends of the second strip conductor 51 are not grounded.
  • Fig. 5b shows the current distribution diagram of the common mode mode of the wire antenna provided by the present application.
  • the current presents a reverse distribution on both sides of the feeding part A of the second strip conductor 51.
  • the feed structure shown in FIG. 5a may be referred to as a symmetric feed structure.
  • the wire antenna mode shown in Fig. 5b can be referred to as a wire antenna common mode mode.
  • the current distribution shown in Figure 5b is called the current of the wire antenna common mode mode.
  • FIG. 6 is a partial structural diagram of the electronic device shown in FIG. 1.
  • Fig. 7 is a schematic partial cross-sectional view of an embodiment of the electronic device shown in Fig. 1 along the N-N line.
  • Fig. 6 also illustrates the line N-N shown in Fig. 1, that is, the position of the cross-sectional view of Fig. 7.
  • the electronic device 100 includes a first strip conductor 41.
  • the material of the first strip conductor 41 can be, but is not limited to, copper, gold, silver or graphene.
  • the first strip-shaped conductor 41 is the radiator of the slot antenna, that is, the first strip-shaped conductor 41 can radiate electromagnetic wave signals according to radio frequency signals.
  • first strip conductor 41 can also receive electromagnetic wave signals and convert the electromagnetic wave signals into radio frequency signals.
  • 6 and 7 show that the first strip conductor 41 extends in the direction of the Y axis. In other embodiments, the first strip conductor 41 may also extend in the direction of the X axis. Specifically, this embodiment is not limited.
  • the first strip conductor 41 is located between the back cover 11 and the circuit board 30 or is fixed to the back cover 11.
  • FIG. 7 shows that the first strip conductor 41 is located between the back cover 11 and the circuit board 30.
  • a first gap 42 is formed between the first strip conductor 41 and the circuit board 30.
  • the first slot 42 is the clearance area of the slot antenna.
  • FIG. 7 also shows that the circuit board 30 is fixed to the side of the display screen 22 of the middle board 13 facing away from the screen 20.
  • the electronic device 100 further includes a bracket 50.
  • the material of the bracket 50 is an insulating material.
  • the bracket 50 has a frame structure.
  • the bracket 50 is fixed on the side of the circuit board 30 facing the rear cover 11, and the bracket 50 and the circuit board 30 define a hollow area.
  • the first strip conductor 41 is formed on the surface of the support 50 facing the rear cover 11 by laser direct structuring (LDS).
  • LDS laser direct structuring
  • the first strip-shaped conductor 41 is formed on the surface of the bracket 50 facing the back cover 11 by printing direct molding technology.
  • the first strip conductor 41 is formed on the surface of the support 50 facing the circuit board 30 by LDS or direct printing technology. At this time, the first strip conductor 41 is located between the support 50 and the circuit board 30. Within the hollow area.
  • the first strip conductor 41 is injection molded inside the bracket 50 through an in-mold injection process.
  • the material of the bracket 50 may also be partly an insulating material and partly a metal material. Part of the insulating material forms the insulating part. Part of the metal material forms the metal part. At this time, the first strip conductor 41 is formed on the insulating part of the bracket 50.
  • the specific formation method can refer to the above-mentioned various embodiments.
  • the bracket 50 may also be plate-shaped or block-shaped. At this time, the bracket 50 no longer encloses a hollow area with the circuit board 30.
  • the material of the bracket 50 is an insulating material.
  • the first strip conductor 41 is fixed on the surface of the bracket 50 facing the rear cover 11.
  • the electronic device 100 may not include the bracket 50.
  • the first strip conductor 41 may be fixed to the back cover 11.
  • the first strip conductor 41 is fixed on the surface of the back cover 11 facing the circuit board 30, or the first strip conductor 41 is embedded in the inside of the back cover 11, or fixed on the surface of the back cover 11 facing away from the circuit board 30.
  • the first strip conductor 41 includes a feeding part A.
  • the feeding part A refers to the part of the first strip conductor 41 where the radio frequency signal is fed.
  • the electronic device 100 further includes a first elastic piece 43.
  • the first elastic piece is fixed to the circuit board 30, and the first elastic piece elastically contacts the first strip conductor 41.
  • the part of the first strip-shaped conductor 41 in contact with the first elastic piece 43 is the feeding part A.
  • FIG. 7 only schematically shows the feeding part A. However, the actual shape, actual size, and actual structure of the power feeding section A are not limited by Fig. 7 and the following figures.
  • the electronic device 100 further includes a radio frequency transceiver circuit 46.
  • FIG. 7 only schematically shows the radio frequency transceiving circuit 46, and the actual shape, actual size, and actual structure of the radio frequency transceiving circuit 46 are not limited by FIG. 7.
  • the radio frequency transceiver circuit 46 is mounted on the circuit board 30.
  • the radio frequency transceiver circuit 46 is electrically connected to the first elastic piece 43. In this way, when the radio frequency transceiver circuit 46 transmits radio frequency signals, the radio frequency signals are transmitted to the first strip conductor 41 through the first elastic sheet 43.
  • the first strip conductor 41 radiates electromagnetic wave signals based on radio frequency signals.
  • the radio frequency signal is transmitted to the radio frequency transceiver circuit 46 via the first elastic sheet 43.
  • the radio frequency transceiver circuit 46 includes a radio frequency transceiver chip (not shown) and a first matching circuit (not shown). Among them, the radio frequency transceiver chip, the first matching circuit, and the first elastic piece 43 are electrically connected in sequence. In other words, the first matching circuit is electrically connected between the radio frequency transceiver chip and the first elastic piece 43.
  • the radio frequency transceiver chip is used to transmit and receive radio frequency signals.
  • the first matching circuit can be used to adjust the frequency band of the slot antenna to receive and transmit electromagnetic waves, or to match the impedance of the slot antenna.
  • the first matching circuit includes electronic devices such as antenna switches, capacitors, inductors, or resistors.
  • the radio frequency transceiver circuit 46 can also be electrically connected to the first strip conductor 41 through the first electrical connector, that is, the first elastic piece 43 is replaced with the first electrical connector. At this time, the part of the first strip conductor 41 that is in contact with the first electrical connector is the power feeding part A.
  • the first strip conductor 41 includes a first grounding portion B and a second grounding portion C.
  • the first grounding portion B and the second grounding portion C are respectively located on both sides of the feeding portion A, and the first grounding portion B and the second grounding portion C are two ends of the first strip conductor 41 respectively.
  • the first ground portion B and the second ground portion C refer to the ground portion of the first strip conductor 41. It can be understood that the first grounding portion B and the second grounding portion C can also be reversed. In other words, the first ground part B may also be located on the right side of the power feeding part A. The second ground part C may also be located on the left side of the power feeding part A. It can be understood that FIG. 7 only schematically shows the first grounding portion B and the second grounding portion C. However, the actual shape, actual size, and actual structure of the first grounding portion B and the second grounding portion C are not limited by FIG. 7 and the following drawings.
  • the electronic device 100 further includes a second elastic piece 44 and a third elastic piece 45. Both the second elastic piece 44 and the third elastic piece 45 are fixed to the circuit board 30. Both the second elastic piece 44 and the third elastic piece 45 elastically contact the first strip conductor 41. In addition, the second elastic piece 44 and the third elastic piece 45 are electrically connected to the ground layer of the circuit board 30. In this case, the portion of the first strip conductor 41 that contacts the second elastic piece 44 is the first ground portion B. The portion of the first strip-shaped conductor 41 that contacts the third elastic piece 45 is the second ground portion C.
  • the electronic device 100 further includes a second matching circuit (not shown).
  • the second matching circuit is electrically connected between the second elastic sheet 44 and the ground layer of the circuit board 30.
  • the second matching circuit includes an inductor, a capacitor, a resistor, or an antenna switch.
  • the second matching circuit is used to tune the frequency band of the slot antenna to receive and transmit electromagnetic wave signals.
  • the second matching circuit can also be used for impedance matching of the antenna.
  • the circuit board 30 also includes a third matching circuit.
  • the third matching circuit is electrically connected between the third elastic piece 45 and the ground layer of the circuit board 30.
  • the third matching circuit includes an inductor, a capacitor, a resistor, or an antenna switch.
  • the third matching circuit is used to tune the frequency band of the slot antenna to receive and transmit electromagnetic wave signals.
  • the third matching circuit can also be used for impedance matching of the antenna.
  • the first strip conductor 41 may also be grounded through the second electrical connector and the third electrical connector, respectively. At this time, the part of the first strip conductor 41 that is in contact with the second electrical connector is the first ground part B. The portion of the first strip conductor 41 that contacts the third electrical connector is the second ground portion C.
  • FIG. 8 is a partial structural diagram of an embodiment of the composite antenna of the electronic device shown in FIG. 1.
  • the center distance between the first ground portion B and the power feeding portion A is a first value d1. It can be understood that the center distance between the first grounding portion B and the feeding portion A refers to the distance between the center of the first grounding portion B and the center of the feeding portion A.
  • the center distance between the second ground portion C and the power feeding portion A is a second value d2.
  • the ratio of the first value d1 to the second value d2 is in the range of 0.8 to 1.2.
  • the ratio of the first value d1 to the second value d2 in this embodiment is 1.
  • the first strip conductor 41 of the present embodiment has a symmetrical pattern with respect to the feeding portion A.
  • the ratio of the first value d1 to the second value d2 may also be 0.8, 0.88, 0.9, 1.1, or 1.2.
  • the ratio of the first value d1 to the second value d2 may not be in the range of 0.8 to 1.2. At this time, the overall symmetry of the first strip conductor 41 is low, and the first matching circuit can be adjusted to compensate for this structural imbalance.
  • FIG. 9a is a partial structural diagram of another embodiment of the composite antenna of the electronic device shown in FIG. 1.
  • the distance d3 between the first ground portion B and the end surface of the first strip conductor 41 is in the range of 0 to 5 mm.
  • d3 is equal to 0.1 mm, 0.8 mm, 1.9 mm, 3.8 mm, 4.1 mm, and 5 mm.
  • the distance d4 between the second ground portion C and the end surface of the first strip conductor 41 is in the range of 0 to 5 mm.
  • d3 is equal to 0.1 mm, 0.8 mm, 1.9 mm, 3.8 mm, 4.1 mm, and 5 mm.
  • the distance d3 between the first ground portion B and the end surface of the first strip conductor 41 is in the range of 0 to 2.5 mm.
  • d3 is equal to 0.5 mm, 0.8 mm, 1.6 mm, 1.8 mm, 2.1 mm, and 2.5 mm.
  • the distance d4 between the second ground portion C and the end surface of the first strip conductor 41 is in the range of 0 to 2.5 mm.
  • d4 is equal to 0.5 mm, 0.8 mm, 1.6 mm, 1.8 mm, 2.1 mm, and 2.5 mm.
  • the distance d3 between the first ground portion B and the end surface of the first strip conductor 41 is 0 to 0.12 ⁇ .
  • the distance d4 between the second ground portion C and the end surface of the first strip conductor 41 is 0 to 0.12 ⁇ .
  • ⁇ is the wavelength of the signal radiated by the antenna.
  • an antenna can generate a resonance at a frequency of 3.0 GHz, where the wavelength ⁇ refers to the wavelength at which the antenna radiates a signal at a frequency of 3.0 GHz.
  • the wavelength of the radiation signal in the medium can be calculated as follows: Among them, ⁇ is the relative permittivity of the medium, and frequency is the frequency of the radiation signal.
  • the distance d3 between the first ground portion B and the end surface of the first strip conductor 41 is 0 to 0.06 ⁇ .
  • the distance d4 between the second ground portion C and the end surface of the first strip conductor 41 is 0 to 0.06 ⁇ .
  • FIG. 9b is a schematic structural diagram of the back cover, the second strip conductor, and the third strip conductor of the electronic device shown in FIG. Fig. 9b also shows the line N-N shown in Fig. 1, that is, the position of the cross-sectional view of Fig. 7.
  • the electronic device 100 further includes a second strip conductor 51 and a third strip conductor 52.
  • the material of the second strip conductor 51 and the third strip conductor 52 can be, but not limited to, copper, gold, silver or graphene.
  • the second strip conductor 51 and the third strip conductor 52 are the radiators of the wire antenna, that is, both the second strip conductor 51 and the third strip conductor 52 can radiate electromagnetic wave signals according to the radio frequency signal.
  • the second strip conductor 51 and the third strip conductor 52 can also receive electromagnetic wave signals, convert the electromagnetic wave signals into radio frequency signals, and transmit the radio frequency signals to the radio frequency transceiver circuit 46.
  • the second strip conductor 51 and the third strip conductor 52 are fixed to the back cover 11. Specifically, the second strip conductor 51 and the third strip conductor 52 are both fixed to the surface of the back cover 11 facing the circuit board 30. At this time, the second strip conductor 51 and the third strip conductor 52 are both located on the side of the first strip conductor 41 facing away from the circuit board 30, that is, in the Z-axis direction, the second strip conductor 51 and the third strip conductor The strip conductors 52 all have a height difference with the first strip conductor 41.
  • a second gap 31 is formed between the second strip conductor 51 and the circuit board 30.
  • a third gap 32 is formed between the third strip conductor 52 and the circuit board 30.
  • the second slot 31 and the third slot 32 form a clearance area of the wire antenna.
  • the second strip conductor 51 and the third strip conductor 52 may also be embedded in the back cover 11, or both may be fixedly connected to the surface of the back cover 11 facing away from the circuit board 30.
  • the first strip conductor 41 when the first strip conductor 41 is fixed to the surface of the bracket 50 facing the circuit board 30.
  • the second strip conductor 51 and the third strip conductor 52 may also be fixed on the surface of the bracket 50 facing the back cover 11, or both are embedded in the bracket 50, or both are fixed on the back cover 11 facing the circuit board 30.
  • the surface of the back cover 11 is either embedded in the inside of the back cover 11, or both are fixed to the surface of the back cover 11 facing away from the circuit board 30.
  • the second strip conductor 51 and the third strip conductor 52 can also be embedded in the back cover 11 , Or both are fixed to the surface of the back cover 11 facing away from the circuit board 30.
  • the second strip conductor 51 and the third strip conductor 52 may also be provided in the same layer as the first strip conductor 41. At this time, in the Z-axis direction, there is no height difference between the second strip conductor 51 and the third strip conductor 52 and the first strip conductor 41.
  • the second strip conductor 51 includes a first end 511 and a second end 512 disposed away from the first end 511.
  • the first end 511 of the second strip conductor 51 is electrically connected to the first ground portion B of the first strip conductor 41. It can be understood that the first end 511 of the second strip conductor 51 is electrically connected to the first ground portion B of the first strip conductor 41.
  • the first method is that the second strip conductor 51 It is spaced apart from the first strip conductor 41, that is, in the Z-axis direction, there is a height difference between the second strip conductor 51 and the first strip conductor 41.
  • the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 at the first ground portion B of the first strip conductor 41 through magnetic field coupling.
  • the second way is that the second strip conductor 51 and the first strip conductor 41 are arranged in the same layer, and the first end 511 of the second strip conductor 51 is connected to the first ground portion B of the first strip conductor 41 .
  • the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 through the first ground portion B.
  • the first method is taken as an example for description. The second method will be described in detail below in conjunction with related drawings. I won't repeat it here.
  • the second end 512 of the second strip conductor 51 is an open end, that is, the second end 512 of the second strip conductor of the second strip conductor 51 is not grounded.
  • the second end 512 of the second strip conductor 51 is electrically connected to the first ground portion B of the first strip conductor 41.
  • the first end 511 of the second strip conductor 51 is an open end, that is, the first end 511 of the second strip conductor 51 is not grounded.
  • the third strip conductor 52 includes a first end 521 and a second end 522 far from the first end 521.
  • the first end 521 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41. It can be understood that the first end 521 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41.
  • the first method is that the third strip conductor 52 It is spaced apart from the first strip conductor 41, that is, in the Z-axis direction, there is a height difference between the third strip conductor 52 and the first strip conductor 41.
  • the radio frequency signal can be fed to the first end 521 of the third strip conductor 52 at the second ground portion C of the first strip conductor 41 through magnetic field coupling.
  • the second way is that the third strip conductor 52 and the first strip conductor 41 are arranged in the same layer, and the first end 521 of the third strip conductor 52 is connected to the second ground part C of the first strip conductor 41 .
  • the radio frequency signal can be fed to the first end 521 of the third strip conductor 52 through the second ground portion C.
  • the first method is taken as an example for description. The second method will be described in detail below in conjunction with related drawings. I won't repeat it here.
  • the second end 522 of the third strip conductor 52 is an open end, that is, the second end 522 of the third strip conductor 52 is not grounded.
  • the second end 522 of the third strip conductor 52 is electrically connected to the second ground portion C of the first strip conductor 41.
  • the first end 521 of the third strip conductor 52 is an open end, that is, the first end 521 of the third strip conductor 52 is not grounded.
  • the electrical connection position between the first end 511 of the second strip conductor 51 and the first strip conductor 41 is the same as the first end 521 of the third strip conductor 52 and the first strip conductor 41
  • the electrical connection position can be reversed. Specifically, the first end 511 of the second strip conductor 51 is electrically connected to the second ground portion C of the first strip conductor 41.
  • the first end 521 of the third strip conductor 52 is electrically connected to the first ground portion B of the first strip conductor 41.
  • the length of the second strip conductor 51 is the first length L1.
  • the length of the third strip conductor 52 is the second length L2.
  • the first length L1 is equal to the second length L2. It can be understood that, when tolerances and errors are taken into consideration, within an allowable range, the first length L1 may be slightly larger than the second length L2, or slightly smaller than the second length L2. In other words, the first length L1 is substantially equal to the second length L2.
  • the second length L2 may also be greater than or less than the first length L1. Specifically, it will be described in detail below in conjunction with related drawings.
  • FIG. 10 is a schematic projection view of an embodiment of the first strip conductor, the second strip conductor and the third strip conductor shown in FIG. 7 on the circuit board.
  • the projection of the first strip conductor 41 on the surface of the circuit board 30 is the first projection S1.
  • the projection of the second strip conductor 51 on the surface of the circuit board 30 is the second projection S2.
  • the angle between the second projection S2 and the first projection S1 is ⁇ .
  • ⁇ is equal to 180°.
  • ⁇ may also be equal to 40°, 90°, 100°, 125°, 152°, 200°, 270°, or 300°.
  • ⁇ is in the range of 90° to 270°. At this time, the first strip conductor 41 and the second strip conductor 51 are not likely to interfere with each other and influence each other when transmitting and receiving electromagnetic wave signals.
  • the projection of the third strip conductor 52 on the surface of the circuit board 30 is the third projection S3.
  • the angle between the third projection S3 and the first projection S1 is ⁇ .
  • ⁇ is equal to 180°.
  • ⁇ may also be equal to 40°, 90°, 100°, 125°, 150°, 200°, 270°, or 300°.
  • ⁇ is in the range of 90° to 270°. At this time, the first strip conductor 41 and the third strip conductor 52 are not likely to interfere with each other and influence each other when transmitting and receiving electromagnetic wave signals.
  • the second strip conductor 51 and the third strip conductor 52 have a symmetrical pattern with respect to the feeding portion A.
  • the area of the overlapping area R1 of the first projection S1 and the second projection S2 is in the range of 0-16 square millimeters.
  • the area of the overlapping region R1 is 0 mm, 3 mm, 7 mm, 10 mm, or 12 mm.
  • the area of the overlapping region R1 of the first projection S1 and the second projection S2 is 8 square millimeters. It is understandable that FIG. 10 only schematically shows that the overlapping area R1 of the first projection S1 and the second projection S2 is rectangular.
  • the overlapping area R1 of the first projection S1 and the second projection S2 may also have other shapes, such as irregular patterns or trapezoids.
  • the first projection S1 and the second projection S2 in the X-axis direction are not limited to the overlap as shown in FIG. 10, and the first projection S1 and the second projection S2 may be partially offset in the X-axis direction.
  • the Y-axis direction of the first projection S1 and the second projection S2 is not limited to the overlap as shown in FIG. 10, and the first projection S1 and the second projection S2 may be partially offset in the Y-axis direction.
  • the area of the overlapping region R1 of the first projection S1 and the second projection S2 may not be in the range of 0-16 square millimeters.
  • the area of the overlapping area R2 of the first projection S1 and the third projection S3 is in the range of 0-16 square millimeters.
  • the area of the overlapping region R2 is 0 mm, 3 mm, 7 mm, 10 mm, or 16 mm.
  • the area of the overlapping region R2 of the first projection S1 and the third projection S3 is 8 square millimeters. It can be understood that the overlapping area of the first projection S1 and the third projection S3 is a rectangle.
  • the overlapping area of the first projection S1 and the third projection S3 may also have other shapes, such as irregular patterns or trapezoids.
  • the X-axis direction of the first projection S1 and the third projection S3 is not limited to the overlap as shown in FIG. 10, and the first projection S1 and the third projection S3 may be partially offset in the X-axis direction.
  • the first projection S1 and the third projection S3 in the Y-axis direction are not limited to the overlap as shown in FIG. 10, and the first projection S1 and the third projection S3 may be partially offset in the Y-axis direction.
  • the area of the overlapping region R2 of the first projection S1 and the third projection S3 may not be in the range of 0-16 square millimeters.
  • FIG. 11a is a diagram showing the relationship between the reflection coefficient (that is, the return loss) and the frequency of the composite antenna shown in FIG. 8 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.73GHz) and resonance "2" (4.78GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2” is generated by the common mode of the wire antenna of the composite antenna. It is understandable that in addition to the 3.73 GHz and 4.78 GHz frequency bands shown in FIG.
  • the composite antenna of this embodiment can also generate resonances in other frequency bands (for example: 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz). It is possible to adjust the size of the first strip conductor 41, or adjust the size of the second strip conductor 51, or adjust the size of the third strip conductor 52, or adjust the first strip conductor 41 and the second strip conductor 51 at the same time. Set with the size of the third strip conductor 52.
  • Fig. 11b is a schematic diagram of the current flow of the composite antenna shown in Fig. 8 at resonance "1”.
  • Fig. 11c is a schematic diagram of the current flow of the composite antenna shown in Fig. 8 at resonance "2".
  • the current distribution of resonance "1" (3.73GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51, and the third current flowing in the second strip conductor 51
  • the fourth current flowing on the shaped conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance “1” (3.73 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.73GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (4.78 GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A, the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third The fourth current on the strip conductor 52 flows from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (4.78 GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (4.78GHz) is the current of the common mode of the wire antenna.
  • FIG. 11d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 8 at resonance "1".
  • Figure 11d illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" (3.73 GHz)
  • there are two SAR hotspots at 5 mm of the back cover 11 ( Figure 11d simply shows the two SAR hotspots by arrow 1 and arrow 2).
  • the SAR hot spot refers to the ratio of the average value of the SAR value in an area to the average value of the SAR value around the area is greater than or equal to 1.2. At this time, the area is called a SAR hot spot.
  • the SAR value area distributed around the maximum SAR value is called the SAR hot spot.
  • the SAR hot spot is more prominent than the surrounding SAR distribution area.
  • the directions of the first current and the second current on the first strip conductor 41 are opposite.
  • the current intensity of the first current is the same as the current intensity of the second current. It can be understood that the better the symmetry of the first strip conductor is, the closer the current intensity of the first current is to the current intensity of the second current. In this way, the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, and the SAR value of resonance "1" (3.73GHz) is relatively low. It is understandable that when the current intensity of the first current is closer to the current intensity of the second current, the SAR value of the resonance "1" (3.73 GHz) is lower.
  • FIG. 11e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 8 at resonance "2".
  • Figure 11e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "2" (4.78 GHz)
  • two SAR hotspots also appear at 5 mm of the back cover 11 ( Figure 11e simply shows the two SAR hotspots by arrow 1 and arrow 2).
  • the third current on the second strip conductor 51 and the fourth current on the third strip conductor 52 have opposite directions.
  • the current intensity of the third current is the same as the current intensity of the fourth current. It can be understood that the better the symmetry between the second strip conductor 51 and the third strip conductor 52 is, the closer the current intensity of the third current is to the current intensity of the fourth current.
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, and the SAR value of resonance "2" (4.78GHz) is low. It can be understood that the closer the current intensity of the third current and the current intensity of the fourth current are, the lower the SAR value of resonance "2" (4.78 GHz).
  • the feeding stability of the second strip conductor 51 through the first strip conductor 41 is better.
  • the third current on the second strip conductor 51 can flow into the circuit board 30 through the first ground portion B.
  • the area of the overlapping area R2 of the first projection S1 and the third projection S3 is 8 square millimeters, the stability of the feeding of the third strip conductor 52 through the first strip conductor 41 is better.
  • the fourth current of the third strip conductor 52 can better flow into the circuit board 30 through the second grounding portion C. In this way, the current intensity on the second strip conductor 51 and the third strip conductor 52 is relatively weakened. At this time, the intensity of the magnetic field generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of the resonance "2" (4.78 GHz) is low.
  • Table 1a shows the SAR value of the electronic device 100 using the composite antenna provided in the first embodiment.
  • Table 1a shows the SAR value of the 10g standard. It can be seen that when the output power is 24 dBm, the SAR value of the electronic device 100 using the composite antenna provided by the first embodiment at a distance of 5 mm from the back cover, regardless of resonance "1" or resonance "2", the overall Lower. Considering that the antenna efficiency of resonance “1” and resonance “2" are not consistent, the antenna efficiency of resonance “1” and resonance “2” are normalized by normalizing resonance “1” and resonance “2". At this time, when the efficiency is normalized to -5dB, the composite antenna provided by the first embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1” or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.5.
  • the antenna design scheme provided by the first embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites two resonant modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve two SAR hot spots in both modes, and the SAR value of the two modes is lower.
  • Figure 11f is the first strip conductor, the second strip conductor and the third strip conductor shown in Figure 7 A schematic projection view of another embodiment of the circuit board.
  • the area of the overlapping area R1 of the first projection S1 and the second projection S2 is 4 square millimeters.
  • the area of the overlapping area R2 of the first projection S1 and the third projection S3 is 4 square millimeters.
  • FIG. 11g is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 11f in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.78GHz) and resonance "2" (4.95GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2" is generated by the common mode of the wire antenna of the composite antenna.
  • the composite antenna can also have two SAR hot spots at 5 mm of the back cover 11.
  • resonance "2" (4.95GHz) two SAR hot spots also appeared at 5mm of the back cover 11.
  • Table 1b shows the SAR value of the electronic device 100 using the composite antenna provided in the first extended embodiment.
  • Table 1b shows the SAR value of the 10g standard. It can be seen that when the output power is 24 dBm, the SAR value of the electronic device 100 using the composite antenna provided in the extended embodiment 1 at a distance of 5 mm from the back cover, whether it is at resonance "1" or resonance "2", the overall SAR value is relatively high. Low. When the efficiency is normalized to -5dB, the composite antenna provided by the extended implementation has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.5.
  • Figure 11h is the first strip conductor, the second strip conductor and the third strip conductor shown in Figure 7 A schematic projection view of another embodiment of the circuit board.
  • the area of the overlapping area R1 of the first projection S1 and the second projection S2 is 16 square millimeters.
  • the area of the overlapping area R2 of the first projection S1 and the third projection S3 is 16 square millimeters.
  • FIG. 11i is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 11h in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (4.65GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2" is generated by the common mode of the wire antenna of the composite antenna.
  • the composite antenna can also have two SAR hot spots at 5 mm of the back cover 11.
  • resonance “2” (4.65GHz)
  • two SAR hot spots also appeared at 5mm of the back cover 11.
  • Table 1c shows the SAR value of the electronic device 100 using the composite antenna provided in the extended second embodiment.
  • Table 1c shows the SAR value of the 10g standard. It can be seen that when the output power is 24 dBm, the SAR value of the electronic device 100 using the composite antenna provided in the extended embodiment 2 at a distance of 5 mm from the back cover, whether at resonance "1" or resonance "2", the overall SAR value is relatively high. Low. When the efficiency is normalized to -5dB, the composite antenna provided by the extended implementation has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.5.
  • the extended embodiment one, and the extended embodiment two the area of the overlapping area R1 of the first projection S1 and the second projection S2, and the overlapping area of the first projection S1 and the third projection S3
  • the area of R2 has a small effect on the SAR value produced by resonance "1".
  • the area of the overlapping area R1 of the first projection S1 and the second projection S2, and the area of the overlapping area R2 of the first projection S1 and the third projection S3 have a greater influence on the SAR value generated by the resonance "2".
  • the area of the overlapping area R1 of the first projection S1 and the second projection S2 is in the range of 0-16 square millimeters
  • the area of the overlapping area R2 of the first projection S1 and the third projection S3 is in the range of 0-16 square millimeters
  • the SAR value produced by resonance "2" is small.
  • FIG. 12 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG.
  • the first end 511 of the second strip conductor 51 is connected to the first ground B of the first strip conductor 41. At this time, the first end 511 of the second strip conductor 51 is grounded.
  • the radio frequency signal can be fed to the second strip conductor 51 through the first ground portion B of the first strip conductor 41.
  • the second end 512 of the second strip conductor 51 is an open end, that is, the second end 512 of the second strip conductor 51 is not grounded.
  • the first end portion 521 of the third strip conductor 52 is connected to the second ground portion C of the first strip conductor 41. At this time, the first end 521 of the third strip conductor 52 is grounded.
  • the radio frequency signal can be fed to the third strip conductor 52 through the second ground portion C of the first strip conductor 41.
  • the second end 522 of the third strip conductor 52 is an open end, that is, the second end 522 of the third strip conductor 52 is not grounded.
  • FIG. 13 is a partial cross-sectional schematic diagram of another embodiment of the electronic device shown in FIG. 1 along the N-N line.
  • the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 are arranged in the same layer.
  • FIG. 13 shows that the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 are all fixed on the surface of the bracket 50 facing the back cover 11.
  • first strip conductor 41, the second strip conductor 51, and the third strip conductor 52 may also be fixed on the surface of the bracket 50 facing the circuit board 30, or they may all be embedded in the bracket 50, or It is fixed on the surface of the back cover 11 facing the circuit board 30, or is embedded in the back cover 11, or fixed on the surface of the back cover 11 facing away from the circuit board 30.
  • FIG. 14a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 12 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.57GHz) and resonance "2" (4.46GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2” is generated by the common mode of the wire antenna of the composite antenna. It is understandable that in addition to the 3.57 GHz and 4.46 GHz frequency bands shown in FIG.
  • the composite antenna of this embodiment can also generate resonances in other frequency bands (for example, 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz). It is possible to adjust the size of the first strip conductor 41, or adjust the size of the second strip conductor 51, or adjust the third strip conductor 52, or adjust the first strip conductor 41, the second strip conductor 51, and the third strip conductor at the same time.
  • the size of the strip conductor 52 is set.
  • Fig. 14b is a schematic diagram of the current flow of the composite antenna shown in Fig. 12 at resonance "1”.
  • Fig. 14c is a schematic diagram of the current flow of the antenna shown in Fig. 12 at resonance "2".
  • the current distribution of resonance "1" (3.57GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51, and the third current flowing in the second strip conductor 51
  • the fourth current flowing on the shaped conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance “1” (3.57 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.57GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (4.46GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third current flowing on the second strip conductor 51.
  • the fourth current flowing on the shaped conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (4.46 GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (4.46GHz) is the current of the common mode of the wire antenna.
  • FIG. 14d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 12 at resonance "1".
  • Figure 14d illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" (3.57 GHz)
  • there are two SAR hotspots at 5 mm of the back cover 11 ( Figure 14d simply shows the two SAR hotspots by arrow 1 and arrow 2).
  • the composite antenna when the composite antenna is at resonance "1", the direction of the first current and the second current on the first strip conductor 41 are opposite.
  • the first strip conductor 41 since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current.
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, and the SAR value of resonance "1" (3.57GHz) is relatively low.
  • FIG. 14e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 12 at resonance "2".
  • Figure 11e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "2" (4.46 GHz)
  • two SAR hotspots also appear at 5 mm of the back cover 11 (Figure 14e simply shows the two SAR hotspots by arrow 1 and arrow 2).
  • the direction of the third current on the second strip conductor 51 is opposite to the direction of the fourth current on the third strip conductor 52.
  • the current intensity of the third current is the same as the current intensity of the fourth current.
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, and the SAR value of resonance "2" (4.46GHz) is relatively low.
  • the third current on the second strip conductor 51 flows into the circuit board through the first ground portion B 30.
  • the first end 521 of the third strip conductor 52 is connected to the second ground portion C of the first strip conductor 41, the fourth current of the third strip conductor 52 flows into the circuit board 30 through the second ground portion C. .
  • the current intensity on the second strip conductor 51 and the third strip conductor 52 is greatly reduced.
  • the intensity of the magnetic field generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of the resonance "2" (4.46 GHz) is low.
  • Table 2 shows the SAR value of the electronic device 100 using the composite antenna provided by the second embodiment.
  • Table 2 shows the SAR value of the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the second embodiment at a distance of 5mm from the back cover, regardless of resonance "1" or resonance "2", the overall Lower. When the efficiency is normalized to -5dB, the composite antenna provided by the second embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.5.
  • the antenna design solution provided by the second embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites two resonant modes (slot antenna differential mode). (And wire antenna common mode), while wideband coverage, it can also achieve two SAR hot spots in both modes, and the SAR value of both modes is low.
  • FIG. 15 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. The difference from the first embodiment is that the length L1 of the second strip conductor 51 is smaller than the length L2 of the third strip conductor 52.
  • FIG. 16a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 15 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce three resonances at 3 to 6GHz, resonance "1" (3.86GHz), resonance "2" (4.46GHz) and resonance “3” (5.08GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Both resonance "2" and resonance "3” are produced by the common mode of the wire antenna of the composite antenna. It is understandable that, in addition to the frequency bands of 3.86 GHz, 4.46 GHz, and 5.08 GHz shown in FIG.
  • the composite antenna of this embodiment can also generate other frequency bands (for example: 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz)
  • the resonance can be specifically adjusted by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the third strip conductor 52, or adjusting the first strip conductor 41 and the second strip conductor at the same time.
  • the size of the conductor 51 and the third strip conductor 52 is set.
  • Fig. 16b is a schematic diagram of the current flow of the composite antenna shown in Fig. 15 at resonance "1”.
  • Fig. 16c is a schematic diagram of the current flow of the antenna shown in Fig. 15 at resonance "2”.
  • Fig. 16d is a schematic diagram of the current flow of the composite antenna shown in Fig. 15 at resonance "3”.
  • the current distribution of resonance "1" (3.86GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51, and the third current flowing in the second strip conductor 51
  • the fourth current flowing on the shaped conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance “1” (3.86 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.86GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (4.46GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third current flowing on the second strip conductor 51.
  • the fourth current flowing on the shaped conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 and the second strip conductor 51 are both smaller than the current intensity of the third strip conductor 52.
  • the current of resonance “2” (4.46 GHz) is mainly the current of the third strip conductor 52.
  • the current of resonance "2" (4.46GHz) is the current of the common mode of the wire antenna.
  • the current distribution of resonance "3" includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the first current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, the third current
  • the second current flowing on the shaped conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 and the third strip conductor 52 are both smaller than the current intensity of the second strip conductor 51.
  • the current of resonance “3” is mainly the current of the second strip conductor 51.
  • the current of resonance "3" (5.08GHz) is the current of the common mode of the wire antenna.
  • FIG. 16e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 15 at resonance "1".
  • Figure 16e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" 3.86 GHz
  • there are two SAR hotspots at 5 mm of the back cover 11 ( Figure 16e simply shows the two SAR hotspots by arrow 1 and arrow 2). It can be understood that, when the composite antenna is at resonance "1", the direction of the first current on the first strip conductor 41 is opposite to that of the second current.
  • the first strip conductor 41 has a symmetrical pattern
  • the first current The current intensity of is the same as the current intensity of the second current.
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, so the SAR value of resonance "1" (3.86GHz) is relatively low.
  • FIG. 16f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 15 at resonance "2".
  • FIG. 16f illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot appears at 5 mm of the back cover 11 ( Figure 16f simply indicates a SAR hot spot by arrow 1).
  • the fourth current of the third strip conductor 52 can better flow into the circuit board 30 through the second grounding portion C. In this way, the current intensity on the third strip conductor 52 is greatly reduced, and the third strip conductor The intensity of the magnetic field generated by 52 is also small, and the SAR value of resonance "2" (4.46GHz) is low. Therefore, although a SAR hot spot appears at resonance "2" (4.46GHz), the SAR value of resonance "2" (4.46GHz) is also low.
  • FIG. 16g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 15 at resonance "3".
  • Figure 16g illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot also appears at 5 mm of the back cover 11 ( Figure 16g simply shows a SAR hot spot by arrow 1).
  • the third current on the second strip conductor 51 can better flow into the circuit board 30 through the first grounding portion B.
  • Table 3 shows the SAR value of the electronic device 100 using the composite antenna provided by the third embodiment.
  • Table 3 shows the SAR value of the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the third embodiment at a distance of 5mm from the back cover, regardless of resonance "1", resonance "2" and resonance “ 3", which is lower overall. When the efficiency is normalized to -5dB, the composite antenna provided by the third embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1", resonance "2" and resonance "3", the SAR value at a distance of 5mm from the rear cover is less than 0.9.
  • the antenna design solution provided by the third embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites three resonance modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve lower SAR values for the three modes, and one of the resonant modes can generate two SAR hot spots.
  • the arrangement of the second strip conductor 51 in this embodiment can also refer to the arrangement of the second strip conductor 51 in the second embodiment.
  • the arrangement of the third strip conductor 52 in this embodiment can also refer to the arrangement of the third strip conductor 52 in the second embodiment. I won't repeat it here.
  • FIG. 17 is a partial structural diagram of still another embodiment of the composite antenna of the electronic device shown in FIG. 1.
  • the electronic device 100 includes a second strip conductor 51.
  • the electronic device 100 no longer includes the third strip conductor 52.
  • the formation and arrangement of the second strip conductor 51 can refer to the formation and arrangement of the first conductor 51 in the first embodiment. I won't repeat it here.
  • FIG. 18a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 17 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (4.76GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2” is generated by the common mode of the wire antenna of the composite antenna. It is understandable that in addition to the 3.68 GHz and 4.76 GHz frequency bands shown in FIG.
  • the composite antenna of this embodiment can also generate resonances in other frequency bands (for example, 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz). It can be set by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the sizes of the first strip conductor 41 and the second strip conductor 51 at the same time.
  • other frequency bands for example, 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz.
  • the current distribution of resonance "1" includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in the portion A and the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51.
  • the current of resonance “1” (3.68 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.68GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (4.76GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in the portion A and the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51.
  • the current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51.
  • the current of resonance “2” (4.76 GHz) is mainly the current of the second strip conductor 51.
  • the current of resonance "2" (4.76GHz) is the current of the common mode of the wire antenna.
  • FIG. 18d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 17 at resonance "1".
  • Figure 18d illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" 3.68 GHz
  • two SAR hotspots appear at 5 mm of the back cover 11 ( Figure 18d simply shows the two SAR hotspots by arrows 1 and 2).
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, so the SAR value of resonance "1" (3.68GHz) is relatively low.
  • FIG. 18e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 17 at resonance "2".
  • Figure 18e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot appears at 5 mm of the back cover 11 ( Figure 18e simply indicates the SAR hot spot by arrow 1).
  • the third current on the second strip conductor 51 can better flow into the circuit board 30 through the first ground portion B, so that the intensity of the current on the second strip conductor 51 is relatively weakened.
  • the intensity of the magnetic field generated by the second strip conductor 51 is also small, and the SAR value of resonance "2" (4.76 GHz) is low. Therefore, although a SAR hot spot appears at resonance "2" (4.76GHz), the SAR value of resonance "2" (4.76GHz) is also low.
  • Table 4 shows the SAR value of the electronic device 100 using the composite antenna provided by the fourth embodiment.
  • Table 4 shows the SAR value of the 10g standard. It can be seen that when the output power is 24 dBm, the SAR value of the electronic device 100 using the composite antenna provided by the fourth embodiment at a distance of 5 mm from the back cover, regardless of resonance "1" or resonance "2", the overall value is Lower. When the efficiency is normalized to -5dB, the composite antenna provided by the fourth embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.8.
  • the antenna design scheme provided by the fourth embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites two resonant modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve lower SAR values for the two modes, and one of the resonant modes can generate two SAR hot spots.
  • the arrangement of the second strip conductor 51 in this embodiment can also refer to the arrangement of the second strip conductor 51 in the second embodiment. I won't repeat it here.
  • FIG. 19 is a partial structural diagram of another embodiment of the composite antenna of the electronic device shown in FIG. 1.
  • the electronic device 100 includes a first strip conductor 41, a second strip conductor 51 and a third strip conductor 52.
  • the formation and arrangement of the first strip conductor 41, the second strip conductor 51 and the third strip conductor 52 can all refer to the first strip conductor 41, the second strip conductor 51 and the first embodiment.
  • FIG. 20 is a schematic structural diagram of the composite antenna shown in FIG. 19 at another angle.
  • the second strip conductor 51 includes a first end 511 and a second end 512 disposed away from the first end 511.
  • the third strip conductor 52 includes a first end 521 and a second end 522 away from the first end 521.
  • the first end 511 of the second strip conductor 51 is connected to the first end 521 of the third strip conductor 52.
  • the first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 are electrically connected to the first ground portion B of the first strip conductor 41 together. It can be understood that the first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 are electrically connected to the first ground portion B in two embodiments: the first method is , The first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 are spaced apart from the first ground portion B, that is, in the Z-axis direction, the second strip conductor 51 There is a height difference between the first strip conductor 41 and the third strip conductor 52 and the first strip conductor 41.
  • the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 and the first end 511 of the third strip conductor 52 at the first ground portion B of the first strip conductor 41 through magnetic field coupling. ⁇ 521.
  • the second way is that the first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 are commonly connected to the first ground portion B of the first strip conductor 41, that is, at In the Z-axis direction, the second strip conductor 51 and the third strip conductor 52 are arranged in the same layer as the first strip conductor 41.
  • the radio frequency signal can be fed to the first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 through the first ground portion B.
  • the first method is taken as an example for description.
  • the second end 512 of the second strip conductor 51 is an open end, that is, the second end 512 of the second strip conductor 51 is not grounded.
  • the second end 522 of the third strip conductor 52 is an open end, that is, the second end 522 of the third strip conductor 52 is not grounded.
  • first end 511 of the second strip conductor 51 and the first end 521 of the third strip conductor 52 are electrically connected to the second ground portion C of the first strip conductor 41 together.
  • the center distance between the first ground part B and the power feeding part A and the center distance between the second ground part C and the power feeding part A can refer to the first value d1 and The relationship of the second value d2.
  • the length L1 of the second strip conductor 51 is equal to the length L2 of the third strip conductor 52. It can be understood that, when tolerances and errors are taken into consideration, the length L1 of the second strip conductor 51 is slightly larger or slightly smaller than the length L2 of the third strip conductor 52 within an allowable range.
  • the length L1 of the second strip conductor 51 is greater than or less than the length L2 of the third strip conductor 52.
  • FIG. 21 is a schematic projection view of the first strip conductor, the second strip conductor, and the third strip conductor shown in FIG. 19 on the circuit board.
  • the projection of the first strip conductor 41 on the surface of the circuit board 30 is the first projection S1.
  • the projection of the second strip conductor 51 on the surface of the circuit board 30 is the second projection S2.
  • the angle between the second projection S2 and the first projection S1 is ⁇ .
  • ⁇ is equal to 90°.
  • ⁇ may also be equal to 10°, 60°, 125°, 150°, or 200°.
  • ⁇ is in the range of 0° to 180°.
  • the projection of the third strip conductor 52 on the surface of the circuit board 30 is the third projection S3.
  • the angle between the third projection S3 and the first projection S1 is ⁇ .
  • ⁇ is equal to 90°.
  • ⁇ may also be equal to 30°, 60°, 125°, 150°, or 200°.
  • ⁇ may also be in the range of 0° to 180°.
  • the second strip conductor 51 and the third strip conductor 52 have a symmetrical pattern with respect to the first ground portion B.
  • the area of the overlapping area of the first projection S1, the second projection S2, and the third projection S3 is in the range of 0-16 square millimeters, such as 0 millimeters, 3 millimeters, 7 millimeters, 10 millimeters, or 12 millimeters.
  • the area of the overlapping area of the first projection S1, the second projection S2, and the third projection S3 is 8 square millimeters. It is understandable that FIG. 21 only schematically shows that the overlapping areas of the first projection S1, the second projection S2, and the third projection S3 are rectangular.
  • the overlapping area of the first projection S1, the second projection S2, and the third projection S3 can also have other shapes. , Such as irregular graphics, or trapezoids, etc.
  • the area of the overlapping area of the first projection S1, the second projection S2, and the third projection S3 may not be in the range of 0-16 square millimeters.
  • FIG. 22a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 19 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.78GHz) and resonance "2" (5.34GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2” is generated by the common mode of the wire antenna of the composite antenna.
  • the composite antenna of this embodiment can also generate resonances in other frequency bands (for example: 0GHz to 3GHz, 6GHz to 8GHz, or 8GHz to 11GHz).
  • Fig. 22b is a schematic diagram of the current flow of the composite antenna shown in Fig. 19 at resonance "1”.
  • Fig. 22c is a schematic diagram of the current flow of the antenna shown in Fig. 19 at resonance "2".
  • the current distribution of resonance "1" (3.78GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51, and the third current flowing in the second strip conductor 51
  • the fourth current flowing on the shaped conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance “1” (3.78 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.78GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third The fourth current on the strip conductor 52 flows from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52.
  • the current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (5.34 GHz) is mainly the current of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "2" (5.34GHz) is the current of the common mode of the wire antenna.
  • FIG. 22d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 19 at resonance "1".
  • Figure 22d illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" 3.78 GHz
  • two SAR hotspots appear at 5 mm of the back cover 11 ( Figure 22d simply shows the two SAR hotspots by arrows 1 and 2).
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, so the SAR value of resonance "1" (3.78GHz) is relatively low.
  • FIG. 22e is a schematic diagram of the SAR hotspot distribution of the composite antenna shown in FIG. 19 at resonance "2".
  • Figure 22e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot appears at 5 mm of the back cover 11 ( Figure 22e simply indicates the SAR hot spot by arrow 1).
  • the third current on the second strip conductor 51 and the fourth current on the third strip conductor 52 have opposite directions.
  • the current intensity of the third current is the same as the current intensity of the fourth current. It can be understood that the better the symmetry between the second strip conductor 51 and the third strip conductor 52 is, the closer the current intensity of the third current is to the current intensity of the fourth current.
  • the magnetic fields on both sides of the first grounding portion B weaken each other, and the energy of the radiated electromagnetic waves is relatively dispersed.
  • the composite antenna has a SAR hot spot at resonance "2"
  • the SAR value of resonance "2" (4.78GHz) is also low. It can be understood that the closer the current intensity of the third current and the current intensity of the fourth current are, the lower the SAR value of resonance "2" (4.78 GHz).
  • the area of the overlapping area of the first projection S1, the second projection S2, and the third projection S3 is 8 square millimeters, and the second strip conductor 51 is preferably fed by the first strip conductor 41 , The feeding of the third strip conductor 52 through the first strip conductor 41 is better.
  • the third current on the second strip conductor 51 can better flow into the circuit board 30 through the first ground part B, and the fourth current on the third strip conductor 52 can better flow through the first ground part B.
  • the current intensity on the second strip conductor 51 and the third strip conductor 52 is greatly reduced.
  • the intensity of the magnetic field generated by the second strip conductor 51 and the third strip conductor 52 is also small, and the SAR value of resonance "2" (5.34 GHz) is low.
  • Table 5 shows the SAR value of the electronic device 100 using the composite antenna provided in the fifth embodiment.
  • Table 5 shows the SAR value of the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the fifth embodiment at a distance of 5mm from the back cover, regardless of resonance "1" or resonance "2", the overall Lower. When the efficiency is normalized to -5dB, the composite antenna provided by the fifth embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.7.
  • the antenna design scheme provided by the fifth embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites two resonant modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve lower SAR values for the two modes, and one of the resonant modes can generate two SAR hot spots.
  • the arrangement of the second strip conductor 51 in this embodiment can also refer to the arrangement of the second strip conductor 51 in the second embodiment.
  • the arrangement of the third strip conductor 52 in this embodiment can also refer to the arrangement of the third strip conductor 52 in the second embodiment. I won't repeat it here.
  • FIG. 23 is another implementation of the composite antenna of the electronic device shown in FIG. 1 Schematic diagram of part of the method.
  • the electronic device 100 further includes a fourth strip conductor 53 and a fifth strip conductor 54.
  • the fourth strip conductor 53 is located on the side of the feeding part A facing away from the second strip conductor 51.
  • the fifth strip conductor 54 is located on the side of the feeding part A facing away from the third strip conductor 52.
  • FIG. 24 is a schematic structural diagram of the composite antenna shown in FIG. 23 at another angle.
  • the fourth strip conductor 53 includes a first end 531 and a second end 532 away from the first end 531.
  • the fifth strip conductor 54 includes a first end 541 and a second end 542 away from the first end 541.
  • the first end 531 of the fourth strip conductor 53 is connected to the first end 541 of the fifth strip conductor 54.
  • first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are electrically connected to the second ground portion C of the first strip conductor 41 together. It can be understood that the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are electrically connected to the second grounding portion C.
  • the first method is .
  • the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are spaced apart from the second grounding portion C, that is, in the Z-axis direction, the fourth strip conductor 53 There is a height difference between the first strip conductor 41 and the fifth strip conductor 54 and the first strip conductor 41.
  • the radio frequency signal can be fed to the first end 531 of the fourth strip conductor 53 and the first end of the fifth strip conductor 54 at the second ground portion C of the first strip conductor 41 through magnetic field coupling. ⁇ 541.
  • the second way is that the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 are commonly connected to the second ground portion C of the first strip conductor 41, that is, at In the Z-axis direction, the fourth strip conductor 53 and the fifth strip conductor 54 and the first strip conductor 41 are arranged in the same layer.
  • the radio frequency signal can be fed to the first end 531 of the fourth strip conductor 53 and the first end 541 of the fifth strip conductor 54 through the second ground portion C.
  • the first method is taken as an example for description.
  • the second end 532 of the fourth strip conductor 53 is an open end, that is, the second end 532 of the fourth strip conductor 53 is not grounded.
  • the second end 542 of the fifth strip conductor 54 is an open end, that is, the second end 542 of the fifth strip conductor 54 is not grounded.
  • the center distance between the first ground part B and the power feeding part A and the center distance between the second ground part C and the power feeding part A can refer to the first value d1 and The relationship of the second value d2. I won't repeat it here.
  • the length of the second strip conductor 51 is the first length L1.
  • the length of the third strip conductor 52 is the second length L2.
  • the first length L1 is equal to the second length L2. It can be understood that, when tolerances and errors are taken into consideration, within an allowable range, the first length L1 may be slightly larger than the second length L2, or slightly smaller than the second length L2. In other words, the first length L1 is substantially equal to the second length L2.
  • the length of the fourth strip conductor 53 is the third length L3.
  • the length of the fifth strip conductor 54 is the fourth length L4.
  • the third length L3 is equal to the fourth length L4. It can be understood that, when tolerances and errors are taken into consideration, the third length L3 may be slightly larger than the fourth length L4, or slightly smaller than the fourth length L4 within an allowable range. In other words, the third length L3 is substantially equal to the fourth length L4.
  • the sum of the first length L1 and the second length L2 is equal to the sum of the third length L3 and the fourth length L4.
  • FIG. 25 is a schematic projection view of the first strip conductor, the second strip conductor, and the third strip conductor shown in FIG. 23 on the circuit board.
  • the projection S1 of the first strip conductor 41 on the surface of the circuit board 30, the projection S2 of the second strip conductor 51 on the surface of the circuit board 30, and the projection S3 of the third strip conductor 52 on the surface of the circuit board 30 For the setting manner of the first projection S1, the second projection S2, and the third projection S3 of the fifth embodiment, please refer to the setting manner. I won't repeat it here.
  • the projection of the fourth strip conductor 53 on the surface of the circuit board 30 is the fourth projection S4.
  • the angle between the fourth projection S4 and the first projection S1 is ⁇ .
  • ⁇ is equal to 90°.
  • ⁇ may also be equal to 30°, 60°, 125°, 150°, or 200°.
  • ⁇ is in the range of 0° to 180°.
  • the projection of the fifth strip conductor 54 on the surface of the circuit board 30 is the fifth projection S5.
  • the angle between the fifth projection S5 and the first projection S1 is ⁇ .
  • ⁇ is equal to 90°.
  • ⁇ may also be in the range of 0° to 180°.
  • ⁇ can also be equal to 30°, 60°, 125°, 150° or 170°.
  • ⁇ is in the range of 0° to 180°.
  • the fourth strip conductor 53 and the fifth strip conductor 54 have a symmetrical pattern with respect to the second ground portion C.
  • the second strip conductor 51 and the third strip conductor 52 have a symmetrical pattern with respect to the feeding portion A and the fourth strip conductor 53 and the fifth strip conductor 54.
  • the area of the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 is in the range of 0-16 square millimeters, for example, the area of the overlapping area is 0 mm, 3 mm, 7 mm, 10 mm, or 12 mm. Mm etc.
  • the area of the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 is 8 square millimeters. It is understandable that FIG. 25 only schematically shows that the overlapping areas of the first projection S1, the fourth projection S4, and the fifth projection S5 are rectangular.
  • the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 can also have other shapes. , Such as irregular graphics, or trapezoids, etc.
  • the area of the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 may not be in the range of 0-16 square millimeters.
  • FIG. 26a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 23 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce two resonances at 3 to 6GHz, resonance "1" (3.68GHz) and resonance "2" (5.38GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Resonance "2” is generated by the common mode of the wire antenna of the composite antenna. It is understandable that in addition to the 3.68 GHz and 5.38 GHz frequency bands shown in FIG.
  • the composite antenna of this embodiment can also generate resonances in other frequency bands (for example, 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz). It is possible to adjust the size of the first strip conductor 41, or adjust the size of the second strip conductor 51, or adjust the size of the third strip conductor 52, or adjust the size of the fourth strip conductor 53, or adjust the fifth strip. Or adjust the size of the first strip conductor 41, the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53 and the fifth strip conductor 54 at the same time. .
  • Fig. 26b is a schematic diagram of the current flow of the composite antenna shown in Fig. 23 at resonance "1”.
  • Fig. 26c is a schematic diagram of the current flow of the antenna shown in Fig. 23 at resonance "2".
  • the current distribution of resonance "1" (3.68GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the first end 511 of the second strip conductor 51 to the second end 512 of the second strip conductor 51, and the third current flowing in the second strip conductor 51
  • the fourth current flowing on the third strip conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52, and the fourth current on the fourth strip conductor 53 from the fourth strip conductor 53
  • the sixth current flows through the second end 542 of the conductor 54.
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54.
  • the current of resonance “1” (3.68 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.68GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (5.38GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third current flowing on the second strip conductor 51.
  • the fourth current flowing on the third strip conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52, and the fourth current on the fourth strip conductor 53 from the fourth strip conductor 53 The fifth current flowing from the second end 532 of the fifth strip conductor to the first end 531 of the fourth strip conductor 53, and in the fifth strip conductor 54 from the second end 542 of the fifth strip conductor 54 to the fifth strip
  • the sixth current flows through the first end 541 of the conductor 54.
  • the current intensity of the first strip conductor 41 is smaller than the current intensity of the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54.
  • the current of resonance "2" is mainly the current of the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54.
  • the current of resonance "2" (5.38GHz) is the current of the common mode of the wire antenna.
  • FIG. 26d is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 23 at resonance "1".
  • Figure 26d illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" (3.68 GHz)
  • two SAR hotspots appear at 5 mm of the back cover 11 (Figure 26d simply shows the two SAR hotspots by arrows 1 and 2).
  • the composite antenna when the composite antenna is at resonance "1", the direction of the first current and the second current on the first strip conductor 41 are opposite.
  • the first strip conductor 41 since the first strip conductor 41 has a symmetrical pattern, the current intensity of the first current is the same as the current intensity of the second current. In this way, the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled. In this way, the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A. At this time, the energy of radiated electromagnetic waves is relatively dispersed, so the SAR value of resonance "1" (3.68GHz) is relatively low.
  • FIG. 26e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 23 at resonance "2".
  • Figure 26e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "2" 5.38 GHz
  • two SAR hotspots also appear at 5 mm of the back cover 11 ( Figure 26e simply shows the two SAR hotspots by arrow 1 and arrow 2).
  • the third current on the second strip conductor 51 and the fourth current on the third strip conductor 52 are in opposite directions, and the fifth current on the fourth strip conductor 53 It is opposite to the sixth current direction of the fifth strip conductor 54.
  • the second strip conductor 51 and the third strip conductor 54 have a symmetrical pattern with respect to the first ground portion B, the current intensity of the third current is the same as the current intensity of the fourth current.
  • the fourth strip conductor 53 and the fifth strip conductor 54 are symmetrical with respect to the second ground portion C, the current intensity of the fifth current is the same as the current intensity of the sixth current.
  • the second strip conductor 51 and the third strip conductor 52 have a symmetrical pattern with respect to the feeding portion A and the fourth strip conductor 53 and the fifth strip conductor 54.
  • the phase of the magnetic field at the feeding portion A is On the contrary, the magnitude of the magnetic field is roughly cancelled out.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, and the SAR value of resonance "2" (5.38GHz) is also low.
  • the area of the overlapping area of the first projection S1, the second projection S2, and the third projection S3 is 8 square millimeters.
  • the second strip conductor 51 is preferably fed by the first strip conductor 41, and the third strip conductor The power feeding 52 through the first strip conductor 41 is better. At this time, both the third current and the fourth current can flow into the circuit board 30 through the first ground portion B.
  • the area of the overlapping area of the first projection S1, the fourth projection S4, and the fifth projection S5 is 8 square millimeters.
  • the fourth strip conductor 53 is better fed by the first strip conductor 41, and the fifth strip conductor The power feeding of 54 through the first strip conductor 41 is better.
  • both the fifth current and the sixth current can flow into the circuit board through the second ground portion C.
  • the current intensity on the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54 is greatly reduced.
  • the intensity of the magnetic field generated by the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54 is also small, and the SAR value of resonance "2" (5.38 GHz) is also low. Lower.
  • Table 6 shows the SAR value of the electronic device 100 using the composite antenna provided by the sixth embodiment.
  • Table 1 shows the SAR value of the 10g standard. It can be seen that when the output power is 24 dBm, the SAR value of the electronic device 100 using the composite antenna provided by the sixth embodiment at a distance of 5 mm from the back cover, regardless of resonance "1" or resonance "2", the overall SAR value is Lower. When the efficiency is normalized to -5dB, the composite antenna provided by the sixth embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1" or resonance "2", the SAR value at a distance of 5mm from the rear cover is less than 0.5.
  • the antenna design scheme provided by the sixth embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites two resonant modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve two SAR hot spots in both modes, and the SAR value of the two modes is lower.
  • the arrangement of the second strip conductor 51 in this embodiment can also refer to the arrangement of the second strip conductor 51 in the second embodiment.
  • the arrangement of the third strip conductor 52 in this embodiment can also refer to the arrangement of the third strip conductor 52 in the second embodiment. I won't repeat it here.
  • first end portion 531 of the fourth strip conductor 53 is connected to the second ground portion C of the first strip conductor 41.
  • the first end portion 541 of the fifth strip conductor 54 is connected to the second ground portion C of the first strip conductor 41.
  • FIG. 27 is another embodiment of the composite antenna of the electronic device shown in FIG. 1 Schematic diagram of part of the structure.
  • the length of the second strip conductor 51 is the first length L1.
  • the length of the third strip conductor 52 is the second length L2.
  • the first length L1 is equal to the second length L2.
  • the length of the fourth strip conductor 53 is the third length L3.
  • the length of the fifth strip conductor 54 is the fourth length L4.
  • the third length L3 is equal to the fourth length L4.
  • the sum of the first length L1 and the second length L2 is less than the sum of the third length L3 and the fourth length L4.
  • FIG. 28a is a diagram showing the relationship between the reflection coefficient and the frequency of the composite antenna shown in FIG. 27 in the frequency band of 3 to 6 GHz.
  • the composite antenna can produce three resonances at 3 to 6GHz, resonance "1" (3.62GHz), resonance "2" (4.95GHz) and resonance “3” (5.75GHz).
  • Resonance "1” is produced by the differential mode of the slot antenna of the composite antenna.
  • Both resonance "2" and resonance "3” are produced by the common mode of the wire antenna of the composite antenna. It is understandable that, in addition to the 3.62 GHz, 4.95 GHz, and 5.75 GHz frequency bands shown in FIG.
  • the composite antenna of this embodiment can also generate other frequency bands (for example: 0 GHz to 3 GHz, 6 GHz to 8 GHz, or 8 GHz to 11 GHz)
  • the resonance can be specifically adjusted by adjusting the size of the first strip conductor 41, or adjusting the size of the second strip conductor 51, or adjusting the size of the third strip conductor 52, or adjusting the size of the fourth strip conductor 53, or Adjust the size of the fifth strip conductor 54 or adjust the dimensions of the first strip conductor 41, the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53 and the fifth strip conductor 54 at the same time To set the size.
  • Fig. 28b is a schematic diagram of the current flow of the composite antenna shown in Fig. 27 at resonance "1”.
  • Fig. 28c is a schematic diagram of the current flow of the antenna shown in Fig. 27 at resonance "2”.
  • Fig. 28d is a schematic diagram of the current flow of the composite antenna shown in Fig. 27 at resonance "3”.
  • the current distribution of resonance "1" (3.62GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the fourth current flowing on the conductor 52 from the first end 521 of the third strip conductor 52 to the second end 522 of the third strip conductor 52, and the fourth current on the fourth strip conductor 53 from the fourth strip conductor 53
  • the current intensity of the first strip conductor 41 is greater than the current intensity of the second strip conductor 51, the third strip conductor 52, the fourth strip conductor 53, and the fifth strip conductor 54.
  • the current of resonance “1” (3.62 GHz) is mainly the current of the first strip conductor 41.
  • the current of resonance "1" (3.62GHz) is the current of the slot antenna's differential mode.
  • the current distribution of resonance "2" (4.95GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the second current flowing in part A the third current flowing on the second strip conductor 51 from the second end 512 of the second strip conductor 51 to the first end 511 of the second strip conductor 51, and the third current flowing on the second strip conductor 51.
  • the fourth current flowing on the third strip conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52, and the fourth current on the fourth strip conductor 53 from the fourth strip conductor 53 The fifth current flowing from the second end 532 of the fifth strip conductor to the first end 531 of the fourth strip conductor 53, and in the fifth strip conductor 54 from the second end 542 of the fifth strip conductor 54 to the fifth strip.
  • the current intensities of the first strip conductor 41, the second strip conductor 51, and the third strip conductor 52 are smaller than the current intensities of the fourth strip conductor 53 and the fifth strip conductor 54.
  • the current of resonance “2” (4.95 GHz) is mainly the current of the fourth strip conductor 53 and the fifth strip conductor 54.
  • the current of resonance "2" (4.95GHz) is the current of the common mode of the wire antenna.
  • the current distribution of resonance "3" (5.75GHz) includes the first current flowing from the first grounding part B to the feeding part A on the first strip conductor 41 and the feeding from the second grounding part C to the feeding part A.
  • the fourth current flowing on the third strip conductor 52 from the second end 522 of the third strip conductor 52 to the first end 521 of the third strip conductor 52, and the fourth current on the fourth strip conductor 53 from the fourth strip conductor 53 The fifth current flowing from the second end 532 of the fifth strip conductor to the first end 531 of the fourth strip conductor 53, and in the fifth strip conductor 54 from the second end 542 of the fifth strip conductor 54 to the fifth strip.
  • the current intensities of the first strip conductor 41, the fourth strip conductor 53, and the fifth strip conductor 54 are smaller than the current intensities of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "3" is mainly the current of the second strip conductor 51 and the third strip conductor 52.
  • the current of resonance "3" (5.75GHz) is the current of the common mode of the wire antenna.
  • FIG. 28e is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 27 at resonance "1".
  • FIG. 28e illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • resonance "1" 3.62 GHz
  • two SAR hotspots appear at 5 mm of the back cover 11 ( Figure 28e simply shows the two SAR hotspots by arrows 1 and 2).
  • the phase of the magnetic field at the power feeding portion A is opposite, and the amplitude of the magnetic field is approximately canceled.
  • the magnetic field is mainly distributed on both sides of the feeding part A, and two SAR hot spots are formed on both sides of the feeding part A.
  • the energy of radiated electromagnetic waves is relatively dispersed, so the SAR value of resonance "1" (3.62GHz) is relatively low.
  • FIG. 28f is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in FIG. 27 at resonance "2".
  • FIG. 28f illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot also appears at 5 mm of the back cover 11 ( Figure 28f simply shows a SAR hot spot by arrow 1).
  • the fifth current of the fourth strip conductor 53 and the sixth current of the fifth strip conductor 54 can better flow into the circuit board 30 through the second grounding portion C. In this way, the fourth strip conductor 53 and the fifth The current intensity on the strip conductor 54 is greatly reduced.
  • the strength of the magnetic field generated by the fourth strip conductor 53 and the fifth strip conductor 54 is also relatively small.
  • the SAR value of resonance "2" is also low.
  • Fig. 28g is a schematic diagram of the SAR hot spot distribution of the composite antenna shown in Fig. 27 at resonance "3".
  • FIG. 28g illustrates the SAR value measured at a distance of 5 mm from the back cover 11 of the human tissue.
  • a SAR hot spot also appears at 5 mm of the back cover 11 ( Figure 28g simply shows a SAR hot spot by arrow 1).
  • both the third current on the second strip conductor 51 and the fourth current on the third strip conductor 52 can flow into the circuit board 30 through the first ground portion B. In this way, the second strip conductor 51 and the fourth current The current intensity on the three strip conductors 52 is greatly reduced.
  • the intensity of the magnetic field generated by the second strip conductor 51 and the third strip conductor 52 is also relatively small.
  • the SAR value of resonance "3" (5.75GHz) is low.
  • Table 7 shows the SAR value of the electronic device 100 using the composite antenna provided by the seventh embodiment.
  • Table 7 shows the SAR value of the 10g standard. It can be seen that when the output power is 24dBm, the SAR value of the electronic device 100 using the composite antenna provided by the seventh embodiment at a distance of 5mm from the back cover, regardless of resonance "1", resonance "2" and resonance " 3", which is lower overall. When the efficiency is normalized to -5dB, the composite antenna provided by the seventh embodiment has more obvious advantages in terms of low SAR value. Regardless of resonance "1", resonance "2" and resonance "3", the SAR value at a distance of 5 mm from the rear cover is less than 0.7.
  • the antenna design scheme provided by the seventh embodiment is to design a composite antenna of a slot antenna and a wire antenna, so that under feeding, the composite antenna excites three resonant modes (slot antenna differential mode). (And wire antenna common mode), while achieving broadband coverage, it can also achieve lower SAR values for the three modes, and one of the resonant modes can generate two SAR hot spots.
  • the above specifically introduces the implementation of the structure of the composite antenna in which seven types of slot antennas and wire antennas are combined. It is understandable that each of the above implementations can be implemented.
  • the composite antenna separately excites multiple resonant modes (including slot antenna differential mode and line antenna common mode). While achieving broadband coverage, multiple modes can also be implemented.
  • the SAR value is low.

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Abstract

本申请提供一种电子设备，涉及天线技术领域。电子设备包括一种槽天线和线天线组成的复合天线。其中，槽天线的第一条形导体包括第一接地部分、第二接地部分及馈电部分，第一接地部分与第二接地部分分别为第一条形导体的两个端部。馈电部分位于第一接地部分与第二接地部分之间。线天线的第二条形导体包括第一端部与第二端部。第二条形导体的第一端部电连接于第一接地部分。第二条形导体的第二端部为开放端。槽天线与线天线组成的复合天线既能够产生多个谐振模式，以实现宽频覆盖，又能够保证多个谐振模式均满足低SAR值的要求，以降低电磁波辐射对人体的影响。

Description

电子设备
本申请要求于2020年04月27日提交中国专利局、申请号为202010346611.7、申请名称为“电子设备”的中国专利申请的优先权，其全部内容通过引用结合在本申请中。
技术领域
本申请涉及天线技术领域，特别涉及一种电子设备。
背景技术
随着全面屏等关键技术的快速发展，电子设备的轻薄化、极致屏占比已成为一种趋势，这种设计大大压缩了天线排布空间。在这种天线排布紧张的环境，传统天线很难满足多通信频段的性能需求。此外，在手机天线设计中，还要关注电磁波辐射对人体的影响。电磁波被人体吸收的能量用电磁波比吸收率(specific absorption ratio，SAR)来量化。SAR值小代表电磁辐射对人体的影响小。故而，如何在手机上实现多个谐振模式同时满足低SAR值的要求成为当务之急。
发明内容
本申请技术方案提供的电子设备的天线可以激励出多个谐振模式，且每个谐振模式均能够满足低SAR值的要求。
本申请提供一种电子设备。电子设备包括后盖、电路板、支架、射频收发电路、第一天线及第二天线。电路板与射频收发电路位于后盖的同一侧，所述支架固定于所述电路板与所述后盖之间。可以理解的是，支架可以固定于电路板，也可以固定于后盖。
其中，第一天线包括第一条形导体。第一条形导体固定于支架。可以理解的是，第一条形导体可以固定于支架的表面，也可以内嵌于支架内。
另外，第一条形导体包括第一接地部分、第二接地部分及馈电部分。第一接地部分与第二接地部分分别为第一条形导体的两个端部。第一接地部分与第二接地部分均通过电路板接地。馈电部分位于第一接地部分与第二接地部分之间，且电连接于射频收发电路。电路板朝向后盖的板面与第一条形导体之间形成第一天线的净空区域。
其中，第二天线包括第二条形导体。第二条形导体固定于后盖，或者支架。可以理解的是，第二条形导体可以固定于后盖的表面，也可以内嵌于后盖内。第二条形导体可以固定于支架的表面，也可以内嵌于支架内。
另外，第二条形导体包括第一端部及远离第一端部设置的第二端部。第二条形导体的第一端部与第一条形导体的第一接地部分电连接。第二条形导体的第二端部未接地，也即第二条形导体的第二端部为开放端。电路板朝向后盖的板面与第二条形导体之间形成第二天线的净空区域。
可以理解的是，第一天线能够激励出一个差模模式的天线模式。第一天线激励的差模模式的电流主要分布呈如下：第一条形导体上自第一接地部分向馈电部分流动的第一电流以及自第二接地部分向馈电部分流动的第二电流。第一条形导体上的第一电流与第二电流的方向相反，第一电流电流强度与第二电流的电流强度能够实现大致相同，此时，馈电部 分处的磁场的相位相反，磁场的幅度能够大致被抵消。这样，磁场主要分布在馈电部分的两侧，在馈电部分的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，第一天线激励的差模模式的SAR值比较低。
另外，第二天线能够激励出一个共模模式的天线模式。第二天线激励的共模模式的电流主要分布呈如下：第二条形导体上自第二条形导体的第二端部向第二条形导体的第一端部流动的第三电流。可以理解的是，第二条形导体上的第三电流能够经第一接地部分流入电路板，这样，第二条形导体上的电流强度能够较大程度被减弱。此时，第二条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值较低。
另外，本实现方式通过设计一种第一天线与第二天线的复合天线，从而在馈电下，复合天线能够激励出两个谐振模式，从而在实现宽频覆盖的同时，还可实现两个模式的SAR值较低，且第一天线的谐振模式能够产生两个SAR热点。
一种实现方式中，第二条形导体的第一端部与第一条形导体的第一接地部分直馈。可以理解的是，直馈指的是第二条形导体的第一端部连接于第一条形导体的第一接地部分，射频信号经第一接地部分直接馈电至第二条形导体。
一种实现方式中，第二条形导体的第一端部与第一条形导体的第一接地部分间接耦合馈电。
一种实现方式中，第一接地部分与第一条形导体的端面之间的距离在0至5毫米的范围内。
一种实现方式中，第一接地部分与第一条形导体的端面之间的距离在0至2.5毫米的范围内。
一种实现方式中，第一接地部分与第一条形导体的端面之间的距离在0至0.12λ。λ是该天线辐射的信号的波长。
一种实现方式中，第一接地部分与第一条形导体的端面之间的距离在0至0.06λ。λ是该天线辐射的信号的波长。
一种实现方式中，第二接地部分与第一条形导体的端面之间的距离在0至5毫米的范围内。
一种实现方式中，第二接地部分与第一条形导体的端面之间的距离在0至2.5毫米的范围内。
一种实现方式中，第二接地部分与第一条形导体的端面之间的距离在0至0.12λ。λ是该天线辐射的信号的波长。
一种实现方式中，第二接地部分与第一条形导体的端面之间的距离在0至0.06λ。λ是该天线辐射的信号的波长。
一种实现方式中，馈电部分与第一接地部分的中心距离为第一值。馈电部分与第二接地部分的中心距离为第二值。第一值与第二值的比值在0.8至1.2的范围内。
可以理解的是，当第一值与第二值的比值在0.8至1.2的范围内时，第一条形导体的整体对称性较佳。此时，在第一天线激励的差模模式的电流分布上，第一条形导体上的第一电流的电流强度与第二电流的电流强度大致相同。这样，馈电部分处的磁场的相位相反，磁场的幅度大致被抵消。磁场主要分布在馈电部分的两侧。第一天线所激励的差模模式的 SAR值比较低。
在其他可实现方式中，第一值与第二值的比值也可以不在0.8至1.2的范围内。第一条形导体的整体对称性较差。此时，可通过第一天线的匹配电路来补偿这种结构上的不对称，从而在第一天线激励的差模模式的电流分布上，第一条形导体上的第一电流的电流强度与第二电流的电流强度能够达到大致相同，进而保证第一天线所激励的差模模式的SAR值比较低。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第二条形导体在电路板的板面的投影为第二投影。第一投影与第二投影的重合区域的面积在0-16平方毫米的范围内。可以理解的是，在该尺寸下，第二条形导体的第一端部与第一条形导体的第一接地部分电连接的稳定性较佳。此时，第二条形导体上的第三电流能够经第一接地部分较好地流入电路板，从而使得第二天线激励的共模模式的SAR值较低。
一种实现方式中，第二天线还包括第三条形导体。第三条形导体固定于后盖，或者支架。可以理解的是，第三条形导体可以固定于后盖的表面，也可以内嵌于后盖内。第三条形导体可以固定于支架的表面，也可以内嵌于支架内。
第三条形导体包括第一端部及远离第一端部设置的第二端部。第三条形导体的第一端部与第一条形导体的第二接地部分电连接。第三条形导体的第二端部未接地，也即第三条形导体的第二端部为开放端。电路板朝向后盖的板面与第三条形导体之间形成第二天线的净空区域。
可以理解的是，通过设置第三条形导体，并通过第三条形导体的第一端部与第二接地部分电连接，从而使得第三条形导体也激励出一个共模模式的天线模式。该共模模式的电流主要分布呈如下：第三条形导体上自第三条形导体的第二端部向第三条形导体的第一端部流动的第四电流。
一种情况下，当第三条形导体激励出共模模式的谐振频率与第二条形导体激励出共模模式的谐振频率不相等时，第二天线能够激励两个共模模式的天线模式：第二条形导体激励的共模模式和第三条形导体激励的共模模式。这样，在本实现方式中，第一天线与第二天线能够激励出三个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第三条形导体激励出共模模式的电流分布，第三条形导体上的第四电流能够经第二接地部分流入电路板，这样，第三条形导体上的电流强度较大程度被减弱。第三条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值也较低。
另一种情况下，当第三条形导体激励出共模模式的谐振频率与第二条形导体激励出共模模式的谐振频率相等时，第二天线激励出一个共模模式的天线模式：第二条形导体与第三条形导体共同激励出一个共模模式。这样，在本实现方式中，第一天线与第二天线能够激励出两个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第二条形导体与第三条形导体共同激励出的共模模式的电流，第二条形导体上的第三电流与第三条形导体的第四电流方向相反，电流强度能够实现大致相同，此时，馈电部分处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分的两侧，在馈电部分的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，该共模模式的SAR值较低。
另外，对于第二条形导体与第三条形导体共同激励出的共模模式的电流分布，第二条形导体上的第三电流能够经第一接地部分流入电路板，第三条形导体上的第四电流能够经第二接地部分流入电路板，这样，第二条形导体与第三条形导体上的电流强度较大程度被减弱。第二条形导体与第三条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值也较低。
一种实现方式中，第三条形导体的第一端部与第一条形导体的第二接地部分直馈。可以理解的是，直馈指的是第三条形导体的第三条形导体的第一端部连接于第一条形导体的第二接地部分，射频信号经第二接地部分直接馈电至第二条形导体。
一种实现方式中，第三条形导体的第一端部与第一条形导体的第二接地部分间接耦合馈电。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第三条形导体在电路板的板面的投影为第三投影。第一投影与第三投影的重合区域的面积在0-16平方毫米的范围内。可以理解的是，在该尺寸下，第三条形导体的第一端部与第一条形导体的第二接地部分电连接的稳定性较佳。此时，第三条形导体上的第四电流能够经第二接地部分较好地流入电路板，从而使得第二天线激励的共模模式的SAR值较低。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第二条形导体在电路板的板面的投影为第二投影。第二投影与第一投影的夹角为第一角度。第一角度在90°至270°的范围内。第三条形导体在电路板的板面的投影为第三投影。第三投影与第一投影的夹角为第二角度。第二角度在90°至270°的范围内。
可以理解的是，当第一角度在90°至270°的范围内时，第二条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第一条形导体与第二条形导体收发电磁波信号时，第一条形导体与第二条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
另外，当第二角度在90°至270°的范围内时，第三条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第一条形导体与第三条形导体收发电磁波信号时，第一条形导体与第三条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
一种实现方式中，第一角度与第二角度均等于180°。第二条形导体的长度等于第三条形导体的长度。
可以理解的是，当第一角度与第二角度均等于180°，且第二条形导体的长度等于第三条形导体的长度时，第二条形导体与第三条形导体关于馈电部分对称。此时，第三条形导体激励出共模模式的谐振频率与第二条形导体激励出共模模式的谐振频率相等。第二天线能够激励出一个共模模式的谐振模式：第二条形导体与第三条形导体共同激励出一个共模模式。这样，在本实现方式中，第一天线与第二天线激励两个天线模式，有利于天线实现宽频覆盖设置。
此外，对于第二条形导体与第三条形导体共同激励出的共模模式的电流，第二条形导体上的第三电流与第三条形导体的第四电流方向相反，电流强度实现大致相同，此时，馈电部分处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分的 两侧，在馈电部分的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，该共模模式的SAR值较低。
一种实现方式中，第一角度与第二角度均等于180°。第二条形导体的长度小于第三条形导体的长度。
可以理解的是，当第一角度与第二角度均等于180°，且第二条形导体的长度小于第三条形导体的长度时，第二条形导体与第三条形导体未关于馈电部分对称。此时，第三条形导体激励出共模模式的谐振频率与第二条形导体激励出共模模式的谐振频率不相等。第二天线能够激励两个共模模式的谐振模式：第二条形导体激励的共模模式和第三条形导体激励的共模模式。这样，在本实现方式中，第一天线与第二天线能够激励三个谐振模式，有利于天线实现宽频覆盖设置。
另外，对于第三条形导体激励出共模模式的电流分布，第三条形导体上的第四电流经第二接地部分流入电路板，这样，第三条形导体上的电流强度较大程度被减弱。第三条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值较低。
一种实现方式中，第二天线还包括第三条形导体。第三条形导体固定于后盖，或者支架。可以理解的是，第三条形导体可以固定于后盖的表面，也可以内嵌于后盖内。第三条形导体可以固定于支架的表面，也可以内嵌于支架内。
第三条形导体包括第一端部及远离第一端部设置的第二端部。第三条形导体的第一端部连接于第二条形导体的第一端部。第三条形导体的第一端部与第一接地部分电连接。第三条形导体的第二端部未接地，也即第三条形导体的第二端部为开放端。电路板朝向后盖的板面与第三条形导体之间形成第二天线的净空区域。
可以理解的是，通过设置第三条形导体的第一端部连接于第二条形导体的第一端部，并通过第三条形导体的第一端部与第一接地部分电连接，从而使得第二天线激励出一个共模模式的天线模式：第二条形导体与第三条形导体共同激励出一个共模模式的天线模式。这样，在本实现方式中，第一天线与第二天线能够激励两个谐振模式，有利于天线实现宽频覆盖设置。
此外，第二条形导体与第三条形导体共同激励出的共模模式的电流主要分布呈如下：第二条形导体上自第二条形导体的第二端部向第二条形导体的第一端部流动的第三电流，以及第三条形导体上自第三条形导体的第二端部向第三条形导体的第一端部流动的第四电流。此时，第三条形导体上的第四电流与第二条形导体上的第三电流的方向能够实现相反，电流强度能够实现大致相同，此时，第三条形导体与第二条形导体之间的磁场的幅度能够被抵消，辐射电磁波的能量较为分散，第二天线激励出的共模模式的SAR值比较低。
另外，第二条形导体上的第三电流经第一接地部分流入电路板，第三条形导体上的电流经第二接地部分流入电路板。这样，第二条形导体与第三条形导体上的电流强度较大程度被减弱。此时，第二条形导体与第三条形导体产生的磁场强度也较小，第二天线的共模模式的SAR值进一步地降低。
一种实现方式中，第三条形导体的第一端部与第一条形导体的第一接地部分直馈。可以理解的是，直馈指的是第三条形导体的第一端部连接于第一条形导体的第一接地部分，射频信号经第一接地部分直接馈电至第二条形导体。
一种实现方式中，第三条形导体的第一端部与第一条形导体的第一接地部分间接耦合馈电。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第二条形导体在电路板的板面的投影为第二投影。第三条形导体在电路板的板面的投影为第三投影。第一投影、第二投影及第三投影的重合区域的面积在0-16平方毫米的范围内。可以理解的是，在该尺寸下，第二条形导体的第一端部与第一条形导体的第一接地部分电连接的稳定性较佳。第三条形导体的第一端部与第一条形导体的第一接地部分电连接的稳定性较佳。此时，第二条形导体上的第三电流能够经第一接地部分较好地流入电路板，第三条形导体上的第四电流能够经第一接地部分较好地流入电路板，从而使得第二天线激励的共模模式的SAR值较低。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第二条形导体在电路板的板面的投影为第二投影。第二投影与第一投影的夹角为第一角度。第三条形导体在电路板的板面的投影为第三投影。第三投影与第一投影的夹角为第二角度。第一角度与第二角度均等于90°。
可以理解的是，当第一角度等于90°时，第二条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第一条形导体与第二条形导体收发电磁波信号时，第一条形导体与第二条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
另外，当第二角度等于90°时，第三条形导体的第三条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第一条形导体与第三条形导体收发电磁波信号时，第一条形导体与第三条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
另外，当第一角度与第二角度等于90°时，对于第二条形导体与第三条形导体共同激励出的共模模式的电流，第一条形导体与第三条形导体上电流方向相反。此时，第三条形导体与第二条形导体之间的磁场的幅度能够实现被抵消，辐射电磁波的能量较为分散，第二天线激励出的共模模式的SAR值降低。
一种实现方式中，第二条形导体的长度等于第三条形导体的长度。此时，第二条形导体与第三条形导体关于第一接地部分对称。此时，对于第二条形导体与第三条形导体共同激励出的共模模式的电流，第一条形导体与第三条形导体上电流强度相同。此时，第三条形导体与第二条形导体之间的磁场的幅度被抵消，辐射电磁波的能量较为分散，第二天线激励出的共模模式的SAR值降低。
一种实现方式中，第二天线还包括第四条形导体及第五条形导体。第四条形导体与第五条形导体均固定于后盖，或者支架。可以理解的是，第四条形导体与第五条形导体可以固定于后盖的表面，也可以内嵌于后盖内。第四条形导体与第五条形导体可以固定于支架的表面，也可以内嵌于支架内。
另外，电路板朝向后盖的板面与第四条形导体之间形成第二天线的净空区域。电路板朝向后盖的板面与第五条形导体形成第二天线的净空区域。
第四条形导体的一端连接于第五条形导体的一端。第四条形导体与第五条形导体的连 接端共同电连接于第二接地部分。第四条形导体远离第五条形导体的一端与第五条形导体远离第四条形导体的一端均未接地，也即第四条形导体远离第五条形导体的一端与第五条形导体远离第四条形导体的一端均为开放端。
可以理解的是，通过设置第四条形导体与第五条形导体，并通过第四条形导体与第五条形导体的连接端与第二接地部分电连接，从而使得第四条形导体与第五条形导体共同激励出一个共模模式的天线模式。该共模模式的电流主要分布呈如下：第四条形导体上自第四条形导体的第二端部向第四条形导体的第一端部流动的第五电流、第五条形导体中自第五条形导体的第二端部向第五条形导体的第一端部流动的第六电流。
一种情况下，当第四条形导体及第五条形导体共同激励出的共模模式的谐振频率与第二条形导体与第三条形导体共同激励出共模模式的谐振频率不相等时，第二天线能够激励两个共模模式的谐振模式：第二条形导体与第三条形导体共同激励出共模模式、第四条形导体及第五条形导体共同激励出的共模模式。这样，在本实现方式中，第一天线与第二天线能够激励三个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第四条形导体及第五条形导体共同激励出共模模式的电流分布，第四条形导体上的第五电流经第二接地部分流入电路板，第六条形导体上的第六电流经第二接地部分流入电路板，这样，第四条形导体及第五条形导体上的电流强度较大程度被减弱。第四条形导体及第五条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值较低。
另一种情况下，当第四条形导体及第五条形导体共同激励出的共模模式的谐振频率与第二条形导体与第三条形导体共同激励出共模模式的谐振频率相等时，第二天线能够激励一个共模模式的谐振模式：第二条形导体、第三条形导体、第四条形导体及第五条形导体共同激励出一个共模模式。这样，在本实现方式中，第一天线与第二天线能够激励两个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第二条形导体、第三条形导体、第四条形导体及第五条形导体共同激励出的共模模式的电流，第二条形导体上的第三电流与第三条形导体的第四电流方向能够实现相反，电流强度能够实现大致相同，第四条形导体上的第五电流与第五条形导体的第六电流方向能够实现相反，电流强度能够实现大致相同，此时，馈电部分处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分的两侧，在馈电部分的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，该共模模式的SAR值较低。
一种实现方式中，第四条形导体与第五条形导体的连接端与第二接地部分直馈。
一种实现方式中，第四条形导体与第五条形导体的连接端与第二接地部分间接耦合馈电。
一种实现方式中，第一条形导体在电路板的板面的投影为第一投影。第四条形导体在电路板的板面的投影为第四投影。第五条形导体在电路板的板面的投影为第五投影。第一投影、第四投影及第五投影的重合区域的面积在0-16平方毫米的范围内。可以理解的是，在该尺寸下，第四条形导体的第一端部与第一条形导体的第二接地部分电连接的稳定性较佳。第五条形导体的第一端部与第一条形导体的第二接地部分电连接的稳定性较佳。此时，第四条形导体上的第五电流能够经第二接地部分较好地流入电路板，第五条形导体上的第六电流能够经第二接地部分较好地流入电路板，从而使得第二天线激励的共模模式的SAR 值较低。
一种实现方式中，第四条形导体在电路板的板面的投影为第四投影。第四投影与第一投影之间的夹角等于90°。第五条形导体在电路板的板面的投影为第五投影。第五投影与第一投影之间的夹角等于90°。
可以理解的是，当第四投影与第一投影之间的夹角等于90°时，第四条形导体的第四条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第四条形导体收发电磁波信号时，第四条形导体与第一条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
另外，当第五投影与第一投影之间的夹角等于90°时，第五条形导体的第五条形导体的第二端部朝远离第一条形导体的方向设置。此时，当第五条形导体收发电磁波信号时，第五条形导体与第一条形导体不容易相互干扰和相互影响，从而保证第一天线以及第二天线具有较佳的辐射性能。
另外，当第四投影与第一投影之间的夹角，与第五投影与第一投影之间的夹角均等于90°时，对于第四条形导体与第五条形导体共同激励出的共模模式的电流分布，第四条形导体与第五条形导体上电流方向相反。此时，第四条形导体与第五条形导体之间的磁场的幅度能够实现被抵消，辐射电磁波的能量较为分散，第二天线激励出的共模模式的SAR值降低。
一种实现方式中，第四条形导体的长度与第五条形导体的长度之和等于第二条形导体与第三条形导体的长度之和。
可以理解的是，当第四条形导体的长度与第五条形导体的长度之和等于第二条形导体与第三条形导体的长度之和时，第二条形导体及第三条形导体能够关于馈电部分与第四条形导体及第五条形导体对称。此时，第四条形导体及第五条形导体共同激励出的共模模式的谐振频率与第二条形导体与第三条形导体共同激励出共模模式的谐振频率相等，第二天线能够激励一个共模模式的谐振模式：第二条形导体、第三条形导体、第四条形导体及第五条形导体共同激励出一个共模模式。这样，在本实现方式中，第一天线与第二天线能够激励两个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第二条形导体、第三条形导体、第四条形导体及第五条形导体共同激励出的共模模式的电流，第二条形导体上的第三电流的电流强度与第三条形导体的第四电流的电流强度能够实现相同，第四条形导体上的第五电流的电流强度与第五条形导体的第六电流的电流强度能够实现相同，此时，馈电部分处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分的两侧，在馈电部分的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，该共模模式的SAR值较低。
一种实现方式中，第四条形导体的长度与第五条形导体的长度之和小于第二条形导体与第三条形导体的长度之和。
可以理解的是，第二条形导体及第三条形导体关于馈电部分与第四条形导体及第五条形导体未对称。第四条形导体及第五条形导体共同激励出的共模模式的谐振频率与第二条形导体与第三条形导体共同激励出共模模式的谐振频率不相等，第二天线能够激励两个共模模式的谐振模式：第二条形导体与第三条形导体共同激励出共模模式、第四条形导体及 第五条形导体共同激励出的共模模式。这样，在本实现方式中，第一天线与第二天线能够激励三个谐振模式，有利于天线实现宽频覆盖设置。
此外，对于第四条形导体及第五条形导体共同激励出共模模式的电流分布，第四条形导体上的第五电流经第二接地部分流入电路板，第六条形导体上的第六电流经第二接地部分流入电路板，这样，第四条形导体及第五条形导体上的电流强度较大程度被减弱。第四条形导体及第五条形导体产生的磁场强度也较小，第二天线激励的共模模式的SAR值较低
一种实现方式中，第一天线与第二天线产生多个谐振模式，且第一天线的谐振模式产生两个SAR热点。
一种实现方式中，第一天线的谐振模式的SAR值小于0.5。
一种实现方式中，第一天线与第二天线产生多个谐振模式，且每个谐振模式的SAR值均小于1。
一种实现方式中，第一条形导体激励出的电流包括自所述第一接地部分流向所述馈电部分的第一电流，以及自所述第二接地部分流向所述馈电部分的第二电流。
一种实现方式中，第二条形导体激励出的电流包括自所述第二条形导体的第二端部流向所述第二条形导体的第一端部的电流。
附图说明
图1是本申请实施例提供的电子设备的一种实施方式的结构示意图；
图2是图1所示的电子设备的部分分解示意图；
图3是图1所示的电子设备在M-M线处的部分剖面图；
图4a示出了本申请提供的槽天线的结构示意图；
图4b示出了本申请提供的槽天线差模模式的电流分布图；
图5a示出了本申请提供的线天线的结构示意图；
图5b示出了本申请提供的线天线共模模式的电流分布图；
图6是图1所示的电子设备的部分结构示意图；
图7是图1所示的电子设备在N-N线的一种实施方式的部分剖面示意图；
图8是图1所示的电子设备的复合天线的一种实施方式的部分结构示意图；
图9a是图1所示的电子设备的复合天线的另一种实施方式的部分结构示意图；
图9b是图1所示的电子设备的后盖、第二条形导体以及第三条形导的结构示意图；
图10是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的一种实施方式的投影示意图；
图11a是图8所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图11b是图8所示的复合天线在谐振“1”下的电流的流向示意图；
图11c是图8所示的复合天线在谐振“2”下的电流的流向示意图；
图11d是图8所示的复合天线在谐振“1”下的SAR热点分布示意图；
图11e是图8所示的复合天线在谐振“2”下的SAR热点分布示意图；
图11f是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的另一种实施方式的投影示意图；
图11g是图11f所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图11h是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的再一种实施方式的投影示意图；
图11i是图11h所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图12是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图13是图1所示的电子设备在N-N线的另一种实施方式的部分剖面示意图；
图14a是图12所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图14b是图12所示的复合天线在谐振“1”下的电流的流向示意图；
图14c是图12所示的天线在谐振“2”下的电流的流向示意图；
图14d是图12所示的复合天线在谐振“1”下的SAR热点分布示意图；
图14e是图12所示的复合天线在谐振“2”下的SAR热点分布示意图；
图15是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图16a是图15所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图16b是图15所示的复合天线在谐振“1”下的电流的流向示意图；
图16c是图15所示的天线在谐振“2”下的电流的流向示意图；
图16d是图15所示的复合天线在谐振“3”下的电流的流向示意图；
图16e是图15所示的复合天线在谐振“1”下的SAR热点分布示意图；
图16f是图15所示的复合天线在谐振“2”下的SAR热点分布示意图；
图16g是图15所示的复合天线在谐振“3”下的SAR热点分布示意图；
图17是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图18a是图17所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图18b是图17所示的复合天线在谐振“1”下的电流的流向示意图；
图18c是图17所示的天线在谐振“2”下的电流的流向示意图；
图18d是图17所示的复合天线在谐振“1”下的SAR热点分布示意图；
图18e是图17所示的复合天线在谐振“2”下的SAR热点分布示意图；
图19是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图20是图19所示的复合天线在另一种角度的结构示意图；
图21是图19所示的第一条形导体、第二条形导体以及第三条形导体在电路板的投影示意图；
图22a是图19所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图22b是图19所示的复合天线在谐振“1”下的电流的流向示意图；
图22c是图19所示的天线在谐振“2”下的电流的流向示意图；
图22d是图19所示的复合天线在谐振“1”下的SAR热点分布示意图；
图22e是图19所示的复合天线在谐振“2”下的SAR热点分布示意图；
图23是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图24是图23所示的复合天线在另一种角度的结构示意图；
图25是图23所示的第一条形导体、第二条形导体以及第三条形导体在电路板的投影示意图；
图26a是图23所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图26b是图23所示的复合天线在谐振“1”下的电流的流向示意图；
图26c是图23所示的天线在谐振“2”下的电流的流向示意图；
图26d是图23所示的复合天线在谐振“1”下的SAR热点分布示意图；
图26e是图23所示的复合天线在谐振“2”下的SAR热点分布示意图；
图27是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图；
图28a是图27所示的复合天线在频段为3至6GHz的反射系数与频率的关系图；
图28b是图27所示的复合天线在谐振“1”下的电流的流向示意图；
图28c是图27所示的天线在谐振“2”下的电流的流向示意图；
图28d是图27所示的复合天线在谐振“3”下的电流的流向示意图
图28e是图27所示的复合天线在谐振“1”下的SAR热点分布示意图；
图28f是图27所示的复合天线在谐振“2”下的SAR热点分布示意图；
图28g是图27所示的复合天线在谐振“3”下的SAR热点分布示意图。
具体实施方式
请参阅图1，图1是本申请实施例提供的电子设备的一种实施方式的结构示意图。电子设备100可以为手机、手表、平板电脑(tablet personal computer)、膝上型电脑(laptop computer)、个人数码助理(personal digital assistant，PDA)、照相机、个人计算机、笔记本电脑、车载设备、可穿戴设备、增强现实(augmented reality，AR)眼镜、AR头盔、虚拟现实(virtual reality，VR)眼镜、VR头盔或者能够接收和发射电磁波的其他形态的设备。图1所示实施例的电子设备100以手机为例进行阐述。为了便于描述，定义电子设备100的宽度方向为X轴。电子设备100的长度方向为Y轴。电子设备100的厚度方向为Z轴。
请参阅图2，并结合图1所示，图2是图1所示的电子设备的部分分解示意图。电子设备100包括壳体10、屏幕20及电路板30。可以理解的是，图1及图2仅示意性的示出了电子设备100包括的一些部件，这些部件的实际形状、实际大小和实际构造不受图1及图2限定。
其中，壳体10可用于支撑屏幕20以及电子设备100的相关器件。壳体10包括后盖11及边框12。后盖11与屏幕20相对设置。后盖11与屏幕20安装于边框12的相背两侧，此时，后盖11、边框12与屏幕20共同围设出电子设备100的内部。电子设备100的内部可用于放置电子设备100的电子器件，例如电池、扬声器、麦克风或者听筒。
在一种实施方式中，后盖11可通过粘胶固定连接于边框12上。
在另一种实施方式中，后盖11与边框12为一体成型结构，即后盖11与边框12为一个整体。
其中，屏幕20安装于壳体10。结合附图1所示，附图1示意了屏幕20与壳体10围成大致呈长方体的结构。此外，屏幕20可用于显示图像、文字等。
在本实施方式中，屏幕20包括保护盖板21和显示屏22。保护盖板21层叠于显示屏22。保护盖板21可以紧贴显示屏22设置，可主要用于对显示屏22起到保护防尘作用。保护盖板21的材质可以为但不仅限于为玻璃。显示屏22可以采用有机发光二极管(organic  light-emitting diode，OLED)显示屏，有源矩阵有机发光二极体或主动矩阵有机发光二极体(active-matrix organic light-emitting diode，AMOLED)显示屏，迷你发光二极管(mini organic light-emitting diode)显示屏，微型发光二极管(micro organic light-emitting diode)显示屏，微型有机发光二极管(micro organic light-emitting diode)显示屏，量子点发光二极管(quantum dot light emitting diodes，QLED)显示屏。
请参阅图3，并结合图2所示，图3是图1所示的电子设备在M-M线处的部分剖面图。电路板30安装于电子设备100的内部，且电路板30与后盖11间隔设置，也即电路板30与后盖11之间存在一空间。
在本实施方式中，壳体10还包括中板13。中板13位于电子设备100的内部，且中板13连接于边框12的内侧。电路板30与屏幕20的显示屏22分别固定于中板13的相背两侧。电路板30朝向后盖11。此时，中板13既能够用于承载屏幕20，也能够用于承载电路板30。
在其他实施方式，壳体10也可以不包括中板13。此时，电路板30可以直接固定于屏幕20上。
此外，电路板30可用于安装电子设备100的电子元器件。例如，中央处理器(central processing unit，CPU)、电池管理单元和基带处理单元。另外，电路板30可以为硬质电路板，也可以为柔性电路板，也可以为软硬结合电路板。电路板30可以采用FR-4介质板，也可以采用罗杰斯(Rogers)介质板，也可以采用Rogers和FR-4的混合介质板，等等。这里，FR-4是一种耐燃材料等级的代号，Rogers介质板为一种高频板。
此外，电子设备100还包括多个天线。在本申请中，“多个”是指至少两个。天线用于发射和接收电磁波信号。可以理解的是，电子设备100可以通过天线，以利用以下一种或多种通信技术与网络或其他设备通信。其中，通信技术包括蓝牙(bluetooth，BT)通信技术、全球定位系统(global positioning system，GPS)通信技术、无线保真(wirelessfidelity，Wi-Fi)通信技术、全球移动通讯系统(global system for mobile communications，GSM)通信技术、宽频码分多址(wideband codedivision multiple access，WCDMA)通信技术、长期演进(long term evolution，LTE)通信技术、5G通信技术、SUB-6G通信技术以及未来其他通信技术等。
另外，电子设备100可以通过天线与其他设备(例如，手机、手表、平板电脑或者能够发射和接收电磁波信号的其他形态设备)实现移动数据流量共享或无线网络共享。举例而言，当其他设备开启数据流量共享网络时，电子设备100能够通过接收其他设备的天线信号，以接入其他设备的数据流量共享网络。这样，电子设备100不会因自身流量不够或者流量已经停止使用而影响电子设备100的用户体验性。
此外，为了给用户带来更为舒适的视觉感受，电子设备100可以采用全面屏工业设计(industry design，ID)。全面屏意味着极大的屏占比(通常在90％以上)。全面屏的边框12宽度大幅缩减，需要对电子设备100内部器件，如前置摄像头、受话器、指纹识别器、天线等，进行重新布局。尤其对于天线设计来说，净空区域缩减，天线空间进一步被压缩。而天线的尺寸、带宽、效率是相互关联、相互影响的，减小天线尺寸(空间)，天线的效率 带宽积(efficiency-bandwidth product)势必减小。再者，在手机天线设计中，还要关注电磁波辐射对人体的影响。当电磁波被人体吸收的能量越多，电磁辐射对人体的影响越大。
在本申请中，通过设置一种槽天线和线天线组成的复合天线，从而在天线排布紧张的环境下，电子设备100的复合天线既能够产生多个谐振模式，以实现宽频覆盖，又能够保证多个谐振模式均满足低SAR值的要求，以降低电磁波辐射对人体的影响。
首先，介绍本申请涉及两个天线模式。
1.槽天线差模(differential mode，DM)模式
如图4a所示，图4a示出了本申请提供的槽天线的结构示意图。槽天线可包括：第一条形导体41及电路板30。第一条形导体41与电路板30间隔设置。电路板30的板面33以及第一条形导体41朝向电路板30的表面411形成第一缝隙42。第一条形导体41的两个端部分别电连接于电路板30的接地层，第一条形导体41的两个端部分别形成第一接地部分B和第二接地部分C。第一条形导体41包括馈电部分A。馈电部分A位于第一接地部分B和第二接地部分C之间。其中，馈电部分A为第一条形导体41中信号馈入的部分。图4a通过箭头示意了射频信号馈入的位置。
请参阅图4b，图4b示出了本申请提供的槽天线差模模式的电流分布图。图4b示出了槽天线的电流分布。如图4b所示，电流在第一条形导体41的馈电部分A两侧呈现反向分布。图4a中示出的这种馈电结构可以称为对称馈电结构。图4b所示的这种槽天线模式可以称为槽天线差模模式。图4b所示的电流分布称为槽天线差模模式的电流。
2.线天线共模(Common mode，CM)模式
如图5a所示，图5a示出了本申请提供的线天线的结构示意图。线天线可包括第二条形导体51及电路板30。第二条形导体42与电路板30间隔设置。电路板30的板面33以及第二条形导体51朝向电路板30的表面519形成第二缝隙31。第二条形导体51的中部形成馈电部分A。馈电部分A为第二条形导体51中的射频信号馈入的部分。图5a通过箭头示意了射频信号馈入的位置。此外，第二条形导体51的两端为开放端，也即第二条形导体51的两端未接地。
如图5b所示，图5b示出了本申请提供的线天线共模模式的电流分布图。电流在第二条形导体51的馈电部分A两侧呈现反向分布。图5a中示出的这种馈电结构可以称为对称馈电结构。图5b所示的这种线天线模式可以称为线天线共模模式。图5b所示的电流分布称为线天线共模模式的电流。
可以理解的是，槽天线与线天线组成的复合天线的设置方式具有多种。下文将结合相关附图具体介绍几种槽天线与线天线组成的复合天线的设置方式。
第一种实施方式，首先结合相关附图介绍一下槽天线的具体结构：
请参阅图6及图7所示，图6是图1所示的电子设备的部分结构示意图。图7是图1所示的电子设备在N-N线的一种实施方式的部分剖面示意图。附图6也示意了图1所示意的N-N线，也即图7剖面图的位置。电子设备100包括第一条形导体41。第一条形导体41 的材质可以为但不仅限于为铜、金、银或者石墨烯。第一条形导体41为槽天线的辐射体，也即第一条形导体41能够根据射频信号辐射电磁波信号。另外，第一条形导体41也能够接收电磁波信号，并将电磁波信号转换成射频信号。附图6及图7示意了第一条形导体41沿Y轴的方向延伸。在其他实施方式中，第一条形导体41也可以沿X轴的方向延伸。具体的，本实施方式不做限定。
另外，第一条形导体41位于后盖11与电路板30之间，或者固定于后盖11。附图7示意了第一条形导体41位于后盖11与电路板30之间。此时，在Z轴方向上，第一条形导体41与电路板30存在高度差。在Z轴方向上，第一条形导体41与电路板30之间形成第一缝隙42。第一缝隙42为槽天线的净空区域。此外，附图7也示意了电路板30固定于中板13背向屏幕20的显示屏22的一侧。
可以理解的是，第一条形导体41的形成方式及设置位置具有多种方式：
请再次参阅图6及图7所示，电子设备100还包括支架50。支架50的材质为绝缘材料。支架50呈框状结构。支架50固定于电路板30朝向后盖11的一侧，且支架50与电路板30围设出一镂空区域。此时，通过激光镭射成型技术(laser directstructuring，LDS)在支架50朝向后盖11的表面上形成第一条形导体41。这时，第一条形导体41位于支架50与后盖11之间。在后续的各个实施方式中，均以本实施方式为例进行描述。
在另一种实施方式中，通过印刷直接成型技术在支架50朝向后盖11的表面上形成第一条形导体41。
在另一种实施方式中，通过LDS或者印刷直接成型技术在支架50朝向电路板30的表面形成第一条形导体41，此时，第一条形导体41位于支架50与电路板30围成的镂空区域内。
在另一种实施方式中，通过模内注塑工艺在支架50的内部注塑出第一条形导体41。
在另一种实施方式中，支架50的材质也可以部分为绝缘材料，部分为金属材料。部分绝缘材料形成绝缘部。部分金属材料形成金属部。此时，第一条形导体41形成在支架50的绝缘部上。具体的形成方式可参阅上述各个实施方式。
一种实施方式中，支架50也可以为板状或者块状。此时，支架50不再与电路板30围出一镂空区域。支架50的材质为绝缘材料。第一条形导体41固定于支架50朝向后盖11的表面。
一种实施方式中，电子设备100也可以不包括支架50。此时，第一条形导体41可以固定于后盖11。例如，第一条形导体41固定于后盖11朝向电路板30的表面，或者第一条形导体41嵌设于后盖11的内部，或者固定于后盖11背向电路板30的表面。
请再次参阅图7，第一条形导体41包括馈电部分A。可以理解的是，馈电部分A指的是第一条形导体41中射频信号馈入的部分。电子设备100还包括第一弹片43。第一弹片固定于电路板30，且第一弹片弹性接触于第一条形导体41。第一条形导体41接触于第一弹片43的部分为馈电部分A。可以理解的是，附图7仅示意性地给出了馈电部分A。但馈电部分A的实际形状、实际大小和实际构造不受图7以及下列各图限定。
此外，电子设备100还包括射频收发电路46。可以理解的是，图7仅示意性的示出了射频收发电路46，射频收发电路46的实际形状、实际大小和实际构造不受图7限定。射 频收发电路46安装于电路板30。射频收发电路46电连接于第一弹片43。这样，当射频收发电路46发射射频信号时，射频信号通过第一弹片43传输至第一条形导体41。第一条形导体41根据射频信号辐射电磁波信号。此外，当第一条形导体41将接收的电磁波信号转换成射频信号之后，射频信号经第一弹片43传输至射频收发电路46。
一种实施方式中，射频收发电路46包括射频收发芯片(图未示)以及第一匹配电路(图未示)。其中，射频收发芯片、第一匹配电路、第一弹片43依次电连接。换言之，第一匹配电路电连接于射频收发芯片与第一弹片43之间。射频收发芯片用于发射和接收射频信号。第一匹配电路可以用于调整槽天线接收和发射电磁波的频段，或者用于槽天线的阻抗匹配。第一匹配电路包括天线开关、电容、电感或者电阻等电子器件。
在其他实施方式中，射频收发电路46也可以通过第一电连接器电连接于第一条形导体41，也即第一弹片43替换成第一电连接器。此时，第一条形导体41接触于第一电连接器的部分为馈电部分A。
请再次参阅图7，第一条形导体41包括第一接地部分B以及第二接地部分C。第一接地部分B以及第二接地部分C分别位于馈电部分A的两侧，且第一接地部分B以及第二接地部分C分别为第一条形导体41的两个端部。第一接地部分B与第二接地部分C指的是第一条形导体41的接地部分。可以理解的是，第一接地部分B与第二接地部分C也可以对调。换言之，第一接地部分B也可以位于馈电部分A的右侧。第二接地部分C也可以位于馈电部分A的左侧。可以理解的是，附图7仅示意性地给出了第一接地部分B与第二接地部分C。但第一接地部分B与第二接地部分C的实际形状、实际大小和实际构造不受图7以及下列各图限定。
请再次参阅图7，电子设备100还包括第二弹片44及第三弹片45。第二弹片44及第三弹片45均固定于电路板30。第二弹片44与第三弹片45均弹性接触于第一条形导体41。此外，第二弹片44及第三弹片45均电连接于电路板30的接地层。在这种情况下，第一条形导体41接触于第二弹片44的部分为第一接地部分B。第一条形导体41接触于第三弹片45的部分为第二接地部分C。
在其他实施方式中，电子设备100还包括第二匹配电路(图未示)。第二匹配电路电连接于第二弹片44与电路板30的接地层之间。第二匹配电路包括电感、电容、电阻或者天线开关。第二匹配电路用于调谐槽天线接收和发射电磁波信号的频段。第二匹配电路还可以用于天线的阻抗匹配。
此外，电路板30还包括第三匹配电路。第三匹配电路电连接于第三弹片45与电路板30的接地层之间。第三匹配电路包括电感、电容、电阻或者天线开关。第三匹配电路用于调谐槽天线接收和发射电磁波信号的频段。第三匹配电路还可以用于天线的阻抗匹配。
在其他实施方式中，第一条形导体41也可以分别通过第二电连接器以及第三电连接器接地。此时，第一条形导体41接触于第二电连接器的部分为第一接地部分B。第一条形导体41接触于第三电连接器的部分为第二接地部分C。
请参阅图8，图8是图1所示的电子设备的复合天线的一种实施方式的部分结构示意图。第一接地部分B与馈电部分A之间的中心距离为第一值d1。可以理解的是，第一接地部分B与馈电部分A之间的中心距离指的是第一接地部分B的中心与馈电部分A的中心之 间的距离。
此外，第二接地部分C与馈电部分A之间的中心距离为第二值d2。第一值d1与第二值d2的比值在0.8至1.2的范围内。本实施方式的第一值d1与第二值d2的比值为1。这样，本实施方式的第一条形导体41关于馈电部分A呈对称图形。在其他实现方式中，第一值d1与第二值d2的比值也可以为0.8、0.88、0.9、1.1或者1.2。
在其他实施方式中，第一值d1与第二值d2的比值也可以不在0.8至1.2的范围内。此时，第一条形导体41的整体对称性较低，可以调整第一匹配电路等来补偿这种结构上的不平衡。
在本实施方式中，第一接地部分B与第二接地部分C分别与第一条形导体41的两个端面平齐。在其他实施方式中，第一接地部分B也可以与第一条形导体41的端面未平齐。第二接地部分C也可以与第一条形导体41的端面未平齐。请参阅图9a，图9a是图1所示的电子设备的复合天线的另一种实施方式的部分结构示意图。第一接地部分B与第一条形导体41的端面之间的距离d3在0至5毫米的范围内。例如，d3等于0.1毫米、0.8毫米、1.9毫米、3.8毫米、4.1毫米以及5毫米。第二接地部分C与第一条形导体41的端面之间的距离d4在0至5毫米的范围内。例如，d3等于0.1毫米、0.8毫米、1.9毫米、3.8毫米、4.1毫米以及5毫米。
一种实施方式中，第一接地部分B与第一条形导体41的端面之间的距离d3在0至2.5毫米的范围内。例如，d3等于0.5毫米、0.8毫米、1.6毫米、1.8毫米、2.1毫米以及2.5毫米。第二接地部分C与第一条形导体41的端面之间的距离d4在0至2.5毫米的范围内。例如，d4等于0.5毫米、0.8毫米、1.6毫米、1.8毫米、2.1毫米以及2.5毫米。
在其他实施方式中，第一接地部分B与第一条形导体41的端面之间的距离d3在0至0.12λ。第二接地部分C与第一条形导体41的端面之间的距离d4在0至0.12λ。λ是该天线辐射的信号的波长。例如，天线可产生3.0GHz频率的谐振，其中波长λ是指天线辐射3.0GHz频率的信号的波长。应理解的是，辐射信号在空气中的波长可以如下计算：波长＝光速/频率，其中频率为辐射信号的频率。辐射信号在介质中的波长可以如下计算：
Figure PCTCN2021089245-appb-000001
其中，ε为该介质的相对介电常数，频率为辐射信号的频率。
在其他实施方式中，第一接地部分B与第一条形导体41的端面之间的距离d3在0至0.06λ。第二接地部分C与第一条形导体41的端面之间的距离d4在0至0.06λ。
下文结合相关附图介绍一下线天线的结构。
请参阅图9b，并结合图7所示，图9b是图1所示的电子设备的后盖、第二条形导体以及第三条形导的结构示意图。附图9b也示意了图1所示意的N-N线，也即图7剖面图的位置。电子设备100还包括第二条形导体51及第三条形导体52。第二条形导体51与第三条形导体52的材质均可以为但不仅限于为铜、金、银或者石墨烯。第二条形导体51与第三条形导体52为线天线的辐射体，也即第二条形导体51与第三条形导体52均能够根据射频信号辐射电磁波信号。另外，第二条形导体51与第三条形导体52也能够接收电磁波信号，并将电磁波信号转换成射频信号，并将射频信号传输至射频收发电路46。
另外，第二条形导体51与第三条形导体52固定于后盖11，具体的，第二条形导体51与第三条形导体52均固定于后盖11朝向电路板30的表面。此时，第二条形导体51与第 三条形导体52均位于第一条形导体41背向电路板30的一侧，也即在Z轴方向上，第二条形导体51与第三条形导体52均与第一条形导体41存在高度差。此外，在Z轴方向上，第二条形导体51与电路板30之间形成第二缝隙31。第三条形导体52与电路板30之间形成第三缝隙32。第二缝隙31与第三缝隙32形成线天线的净空区域。
在其他实施方式中，第二条形导体51与第三条形导体52也可以均内嵌于后盖11内，或者均固定连接于后盖11背向电路板30的表面。
在其他实施方式中，当第一条形导体41固定于支架50朝向电路板30的表面。此时，第二条形导体51与第三条形导体52也可以均固定于支架50朝向后盖11的表面，或者均内嵌于支架50内，或者均固定于后盖11朝向电路板30的表面，或者均内嵌于后盖11的内部，或者均固定于后盖11背向电路板30的表面。
在其他实施方式中，当第一条形导体41固定于后盖11朝向电路板30的表面时，第二条形导体51与第三条形导体52也可以均内嵌于后盖11的内部，或者均固定于后盖11背向电路板30的表面。
在其他实施方式中，第二条形导体51与第三条形导体52也可以与第一条形导体41同层设置。此时，在Z轴方向上，第二条形导体51与第三条形导体52均与第一条形导体41不存在高度差。
请再次参阅图8，第二条形导体51包括第一端部511及远离第一端部511设置的第二端部512。第二条形导体51的第一端部511电连接于第一条形导体41的第一接地部分B。可以理解的是，第二条形导体51的第一端部511电连接于第一条形导体41的第一接地部分B包括两种实施方式：第一种方式是，第二条形导体51与第一条形导体41间隔设置，也即在Z轴方向上，第二条形导体51与第一条形导体41存在高度差。此时，射频信号能够在第一条形导体41的第一接地部分B处通过磁场耦合馈电至第二条形导体51的第一端部511。第二种方式是，第二条形导体51与第一条形导体41同层设置，且第二条形导体51的第一端部511连接于第一条形导体41的第一接地部分B。此时，射频信号能够经第一接地部分B馈电至第二条形导体51的第一端部511。在本实施方式中，以第一种方式为例进行描述。关于第二种方式将在下文结合相关附图具体描述。这里不再赘述。
另外，第二条形导体51的第二端部512为开放端，也即第二条形导体51的第二条形导体的第二端部512未接地。
在其他实施方式中，第二条形导体51的第二端部512电连接于第一条形导体41的第一接地部分B。第二条形导体51的第一端部511为开放端，也即第二条形导体51的第一端部511未接地。
请再次参阅图8，第三条形导体52包括第一端部521及远离第一端部521的第二端部522。第三条形导体52的第一端部521电连接于第一条形导体41的第二接地部分C。可以理解的是，第三条形导体52的第一端部521电连接于第一条形导体41的第二接地部分C包括两种实施方式：第一种方式是，第三条形导体52与第一条形导体41间隔设置，也即在Z轴方向上，第三条形导体52与第一条形导体41存在高度差。此时，射频信号能够在第一条形导体41的第二接地部分C处通过磁场耦合馈电至第三条形导体52的第一端部521。第二种方式是，第三条形导体52与第一条形导体41同层设置，且第三条形导体52的第一 端部521连接于第一条形导体41的第二接地部分C。此时，射频信号能够经第二接地部分C馈电至第三条形导体52的第一端部521。在本实施方式中，以第一种方式为例进行描述。关于第二种方式将在下文结合相关附图具体描述。这里不再赘述。
另外，第三条形导体52的第二端部522为开放端，也即第三条形导体52的第二端部522未接地。
在其他实施方式中，第三条形导体52的第二端部522电连接于第一条形导体41的第二接地部分C。第三条形导体52的第一端部521为开放端，也即第三条形导体52的第一端部521未接地。
在其他实施方式中，第二条形导体51的第一端部511与第一条形导体41的电连接位置，与第三条形导体52的第一端部521与第一条形导体41的电连接位置可以对调。具体的，第二条形导体51的第一端部511电连接于第一条形导体41的第二接地部分C。第三条形导体52的第一端部521电连接于第一条形导体41的第一接地部分B。
请再次参阅图8，第二条形导体51的长度为第一长度L1。第三条形导体52的长度为第二长度L2。第一长度L1等于第二长度L2。可以理解的是，当考虑到公差与误差的存在时，在可允许的范围内，第一长度L1可以略大于第二长度L2，或者略小于第二长度L2。换言之第一长度L1大致等于第二长度L2。
在其他实施方式中，第二长度L2也可以大于或者小于第一长度L1。具体的，下文将结合相关附图具体介绍。
请参阅图10，并结合图7所示，图10是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的一种实施方式的投影示意图。第一条形导体41在电路板30的板面的投影为第一投影S1。第二条形导体51在电路板30的板面的投影为第二投影S2。第二投影S2与第一投影S1之间的夹角为α。本实施方式中，α等于180°。在其他实施方式中，α也可以等于40°、90°、100°、125°、152°、200°、270°或者300°。
一种实施方式中，α在90°至270°的范围内。此时，第一条形导体41与第二条形导体51在收发电磁波信号时，不容易相互干扰，相互影响。
此外，第三条形导体52在电路板30的板面的投影为第三投影S3。第三投影S3与第一投影S1之间的夹角为β。本实施方式中，β等于180°。在其他实施方式中，β也可以等于40°、90°、100°、125°、150°、200°、270°或者300°。
一种实施方式中，β在90°至270°的范围内。此时，第一条形导体41与第三条形导体52在收发电磁波信号时，不容易相互干扰，相互影响。
这样，在本实施方式中，第二条形导体51与第三条形导体52关于馈电部分A呈对称图形。
请再次参阅图10，第一投影S1与第二投影S2的重合区域R1的面积在0-16平方毫米的范围内。例如重合区域R1的面积为0毫米、3毫米、7毫米、10毫米或者12毫米等。在本实施方式中，第一投影S1与第二投影S2的重合区域R1的面积为8平方毫米。可以理解的是，附图10仅示意性地给出了第一投影S1与第二投影S2的重叠区域R1为长方形。但当第一条形导体41与第二条形导体51的形状发生变化时，第一投影S1与第二投影S2的重叠区域R1也可以为其他形状，例如不规则图形，或者梯形等。另外，第一投影S1与 第二投影S2在X轴方向并不局限于附图10所示意的重合，第一投影S1与第二投影S2在X轴方向也可以部分错开。另外，第一投影S1与第二投影S2在Y轴方向也并不局限于附图10所示意的重合，第一投影S1与第二投影S2在Y轴方向也可以部分错开。
在其他实施方式中，第一投影S1与第二投影S2的重合区域R1的面积也可以不在0-16平方毫米的范围内。
另外，第一投影S1与第三投影S3的重合区域R2的面积在0-16平方毫米的范围内。例如重合区域R2的面积为0毫米、3毫米、7毫米、10毫米或者16毫米等。在本实施方式中，第一投影S1与第三投影S3的重合区域R2的面积为8平方毫米。可以理解的是，第一投影S1与第三投影S3的重叠区域为长方形。但当第一条形导体41与第三条形导体52的形状发生变化时，第一投影S1与第三投影S3的重叠区域也可以为其他形状，例如不规则图形，或者梯形等。另外，第一投影S1与第三投影S3在X轴方向并不局限于附图10所示意的重合，第一投影S1与第三投影S3在X轴方向也可以部分错开。另外，第一投影S1与第三投影S3在Y轴方向也并不局限于附图10所示意的重合，第一投影S1与第三投影S3在Y轴方向也可以部分错开。
在其他实施方式中，第一投影S1与第三投影S3的重合区域R2的面积也可以不在0-16平方毫米的范围内。
下面结合附图说明第一种实施方式提供的复合天线的仿真。
请参阅图11a，图11a是图8所示的复合天线在频段为3至6GHz的反射系数(也即回波损耗)与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.73GHz)和谐振“2”(4.78GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。可以理解的是，除了图11a中示出的3.73GHz、4.78GHz频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者调整第三条形导体52的尺寸，或者同时调整第一条形导体41、第二条形导体51与第三条形导体52的尺寸来设置。
以下结合图11b和图11c来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.73GHz)和谐振“2”(4.78GHz)的电流分布。图11b是图8所示的复合天线在谐振“1”下的电流的流向示意图。图11c是图8所示的复合天线在谐振“2”下的电流的流向示意图。
请参阅图11b，谐振“1”(3.73GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流。第一条形导体41的电流强度大于第二条形导体51与第三条形导体52的电流强度。这样，谐振“1”(3.73GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.73GHz)的电流为槽天线差模的电流。
请参阅图11c，谐振“2”(4.78GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511 流动的第三电流，以及第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流。第一条形导体41的电流强度小于第二条形导体51与第三条形导体52的电流强度。这样，谐振“2”(4.78GHz)的电流主要为第二条形导体51与第三条形导体52的电流。谐振“2”(4.78GHz)的电流为线天线共模的电流。
请参阅图11d，图11d是图8所示的复合天线在谐振“1”下的SAR热点分布示意图。图11d示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.73GHz)，后盖11的5mm处，出现了两个SAR热点(附图11d通过箭头1和箭头2简单地示意出了两个SAR热点)。可以理解的是，SAR热点指的是一个区域内的SAR值的平均值与该区域周边的SAR值的平均值的比值大于或等于1.2。此时，该区域称为SAR热点。或者说，在一个SAR值分布区域内，出现了SAR值的最大值。此时，围绕最大SAR值分布的SAR值区域称为SAR热点。此时，在附图11d中，SAR热点相较于周边的SAR分布的区域较为突出。
复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。可以理解的是，第一条形导体的对称性越好，第一电流的电流强度与第二电流的电流强度越接近。这样，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，谐振“1”(3.73GHz)的SAR值比较低。可以理解的是，当第一电流的电流强度与第二电流的电流强度越接近时，谐振“1”(3.73GHz)的SAR值越低。
请参阅图11e，图11e是图8所示的复合天线在谐振“2”下的SAR热点分布示意图。图11e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(4.78GHz),在后盖11的5mm处，也出现了两个SAR热点(附图11e通过箭头1和箭头2简单地示意出了两个SAR热点)。
复合天线在谐振“2”(4.78GHz)下，第二条形导体51上的第三电流与第三条形导体52的第四电流方向相反。另外，由于第二条形导体51与第三条形导体52关于馈电部分A呈对称结构，第三电流的电流强度与第四电流的电流强度相同。可以理解的是，第二条形导体51与第三条形导体52的对称性越好，第三电流的电流强度与第四电流的电流强度越接近。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。辐射电磁波的能量较为分散，谐振“2”(4.78GHz)的SAR值较低。可以理解的是，第三电流的电流强度与第四电流的电流强度越接近，谐振“2”(4.78GHz)的SAR值越低。
在本实施方式中，由于第一投影S1与第二投影S2的重合区域R1的面积为8平方毫米，第二条形导体51通过第一条形导体41的馈电稳定性较佳。此时，第二条形导体51上的第三电流能够经第一接地部分B较好地流入电路板30。另外，由于第一投影S1与第三投影S3的重合区域R2的面积为8平方毫米，第三条形导体52通过第一条形导体41的馈电稳定性较佳。第三条形导体52的第四电流能够经第二接地部分C较好地流入电路板30，这样，第二条形导体51以及第三条形导体52上的电流强度较大程度被减弱。此时，第二条形导体51与第三条形导体52产生的磁场强度也较小，谐振“2”(4.78GHz)的SAR值较低。
另外，表1a示出了采用第一种实施方式提供的复合天线的电子设备100的SAR值。
表1a
Figure PCTCN2021089245-appb-000002
表1a中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第一种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。考虑到谐振“1”与谐振“2”的天线效率不一致，通过将谐振“1”与谐振“2”进行归一化，以使谐振“1”与谐振“2”的天线效率相一致。此时，在效率归一化到-5dB时，第一种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.5。
在本实施方式中，第一种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出两个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现两个模式均能够出现两个SAR热点，且两个模式的SAR值较低。
扩展实施方式一，与第一种实施方式相同的技术内容不再赘述：请参阅图11f，图11f是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的另一种实施方式的投影示意图。第一投影S1与第二投影S2的重合区域R1的面积为4平方毫米。第一投影S1与第三投影S3的重合区域R2的面积为4平方毫米。
下面结合附图说明扩展实施方式一提供的复合天线的仿真。
请参阅图11g，图11g是图11f所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.78GHz)和谐振“2”(4.95GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。
可以理解的是，本实施方式的复合天线在谐振“1”(3.78GHz)的电流分布，以及在谐振“2”(4.95GHz)的电流分布与第一种实施方式的复合天线在谐振“1”(3.73GHz)的电流分布，以及在谐振“2”(4.78GHz)的电流分布相同。这里不再赘述。
另外，对于谐振“1”(3.78GHz)，复合天线在后盖11的5mm处，也能够出现了两个SAR热点。对于谐振“2”(4.95GHz),在后盖11的5mm处，也出现了两个SAR热点。
另外，表1b示出了采用扩展实施方式一提供的复合天线的电子设备100的SAR值。
表1b
Figure PCTCN2021089245-appb-000003
表1b中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用扩展实施方式一提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”， 还是谐振“2”，整体均较低。在效率归一化到-5dB时，扩展实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.5。
扩展实施方式二，与第一种实施方式相同的技术内容不再赘述：请参阅图11h，图11h是图7所示的第一条形导体、第二条形导体以及第三条形导体在电路板的再一种实施方式的投影示意图。第一投影S1与第二投影S2的重合区域R1的面积为16平方毫米。第一投影S1与第三投影S3的重合区域R2的面积为16平方毫米。
下面结合附图说明扩展实施方式二提供的复合天线的仿真。
请参阅图11i，图11i是图11h所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.68GHz)和谐振“2”(4.65GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。
可以理解的是，本实施方式的复合天线在谐振“1”(3.68GHz)的电流分布，以及在谐振“2”(4.65GHz)的电流分布与第一种实施方式的复合天线在谐振“1”(3.73GHz)的电流分布，以及在谐振“2”(4.78GHz)的电流分布相同。这里不再赘述。
另外，对于谐振“1”(3.68GHz)，复合天线在后盖11的5mm处，也能够出现了两个SAR热点。对于谐振“2”(4.65GHz),在后盖11的5mm处，也出现了两个SAR热点。
另外，表1c示出了采用扩展实施方式二提供的复合天线的电子设备100的SAR值。
表1c
Figure PCTCN2021089245-appb-000004
表1c中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用扩展实施方式二提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。在效率归一化到-5dB时，扩展实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.5。
可以理解的是，根据第一实施方式、扩展实施方式一以及扩展实施方式二，第一投影S1与第二投影S2的重合区域R1的面积，以及第一投影S1与第三投影S3的重合区域R2的面积对谐振“1”产生的SAR值的影响较小。
另外，第一投影S1与第二投影S2的重合区域R1的面积，以及第一投影S1与第三投影S3的重合区域R2的面积对谐振“2”产生的SAR值的影响较大。当第一投影S1与第二投影S2的重合区域R1的面积在0-16平方毫米的范围内，以及第一投影S1与第三投影S3的重合区域R2的面积在0-16平方毫米的范围内时，谐振“2”产生的SAR值较小。
第二种实施方式，与第一种实施方式相同的技术内容不再赘述：请参阅图12，图12是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。第二条形导体51的第一端部511连接于第一条形导体41的第一接地部B。此时，第二条形导体51的第一 端部511接地。射频信号能够经第一条形导体41的第一接地部分B馈电至第二条形导体51。
另外，第二条形导体51的第二端部512为开放端，也即第二条形导体51的第二端部512未接地。
第三条形导体52的第一端部521连接于第一条形导体41的第二接地部C。此时，第三条形导体52的第一端部521接地。射频信号能够经第一条形导体41的第二接地部分C馈电至第三条形导体52。另外，第三条形导体52的第二端部522为开放端，也即第三条形导体52的第二端部522未接地。
请参阅图13，并结合图12所示，图13是图1所示的电子设备在N-N线的另一种实施方式的部分剖面示意图。第一条形导体41、第二条形导体51与第三条形导体52同层设置。附图13示意了第一条形导体41、第二条形导体51与第三条形导体52均固定在支架50朝向后盖11的表面。在其他实施方式中，第一条形导体41、第二条形导体51与第三条形导体52也可以均固定在支架50朝向电路板30的表面，或者均嵌设在支架50内，或者固定在后盖11朝向电路板30的表面，或者内嵌于后盖11内，或者固定于后盖11背向电路板30的表面。
下面结合附图说明第二种实施方式提供的复合天线的仿真。
请参阅图14a，图14a是图12所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.57GHz)和谐振“2”(4.46GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。可以理解的是，除了图14a中示出的3.57GHz、4.46GHz频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者调整第三条形导体52或者同时调整第一条形导体41、第二条形导体51以及第三条形导体52的尺寸来设置。
以下结合图14b和图14c来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.57GHz)和谐振“2”(4.46GHz)的电流分布。图14b是图12所示的复合天线在谐振“1”下的电流的流向示意图。图14c是图12所示的天线在谐振“2”下的电流的流向示意图。
请参阅图14b，谐振“1”(3.57GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流。第一条形导体41的电流强度大于第二条形导体51与第三条形导体52的电流强度。这样，谐振“1”(3.57GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.57GHz)的电流为槽天线差模的电流。
请参阅图14c，谐振“2”(4.46GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体 52的第一端部521流动的第四电流。第一条形导体41的电流强度小于第二条形导体51与第三条形导体52的电流强度。这样，谐振“2”(4.46GHz)的电流主要为第二条形导体51与第三条形导体52的电流。谐振“2”(4.46GHz)的电流为线天线共模的电流。
请参阅图14d，图14d是图12所示的复合天线在谐振“1”下的SAR热点分布示意图。图14d示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.57GHz)，后盖11的5mm处，出现了两个SAR热点(附图14d通过箭头1和箭头2简单地示意出了两个SAR热点)。
可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，谐振“1”(3.57GHz)的SAR值比较低。
请参阅图14e，图14e是图12所示的复合天线在谐振“2”下的SAR热点分布示意图。图11e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(4.46GHz),在后盖11的5mm处，也出现了两个SAR热点(附图14e通过箭头1和箭头2简单地示意出了两个SAR热点)。
可以理解的是，第二条形导体51上的第三电流与第三条形导体52的第四电流方向相反。另外，由于第二条形导体51与第三条形导体52关于馈电部分A呈对称结构，第三电流的电流强度与第四电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，谐振“2”(4.46GHz)的SAR值比较低。
此外，由于第二条形导体51的第一端部511连接于第一条形导体41的第一接地部B，第二条形导体51上的第三电流经第一接地部分B流入电路板30。另外，由于第三条形导体52的第一端部521连接于第一条形导体41的第二接地部C，第三条形导体52的第四电流经第二接地部分C流入电路板30。这样，第二条形导体51以及第三条形导体52上的电流强度较大程度被减弱。此时，第二条形导体51与第三条形导体52产生的磁场强度也较小，谐振“2”(4.46GHz)的SAR值较低。
另外，表2示出了采用第二种实施方式提供的复合天线的电子设备100的SAR值。
表2
Figure PCTCN2021089245-appb-000005
表2中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第二种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。当效率归一化到-5dB时，第二种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.5。
在本实施方式中，第二种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出两个谐振模式(槽天线差模和线天线共模)，在宽频覆盖的同时，还可实现两个模式均能够出现两个SAR热点，且两个模式的SAR值均较低。
第三种实施方式，与第一种实施方式相同的技术内容不再赘述：请参阅图15，图15是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。与第一种实施方式不同的是，第二条形导体51的长度L1小于第三条形导体52的长度L2。
下面结合附图说明第三种实施方式提供的复合天线的仿真。
请参阅图16a，图16a是图15所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生三个谐振，谐振“1”(3.86GHz)、谐振“2”(4.46GHz)和谐振“3”(5.08GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”和谐振“3”均是复合天线的线天线共模产生的。可以理解的是，除了图16a中示出的3.86GHz、4.46GHz以及5.08GHz的频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者调整第三条形导体52，或者同时调整第一条形导体41、第二条形导体51以及第三条形导体52的尺寸来设置。
以下结合图16b、图16c和图16d来具体描述一下复合天线的三个谐振的电流：谐振“1”(3.86GHz)、谐振“2”(4.46GHz)和谐振“3”(5.08GHz)的电流分布。图16b是图15所示的复合天线在谐振“1”下的电流的流向示意图。图16c是图15所示的天线在谐振“2”下的电流的流向示意图。图16d是图15所示的复合天线在谐振“3”下的电流的流向示意图。
请参阅图16b，谐振“1”(3.86GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流。第一条形导体41的电流强度大于第二条形导体51与第三条形导体52的电流强度。这样，谐振“1”(3.86GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.86GHz)的电流为槽天线差模的电流。
请参阅图16c，谐振“2”(4.46GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流。第一条形导体41的电流强度与第二条形导体51均小于第三条形导体52的电流强度。这样，谐振“2”(4.46GHz)的电流主要为第三条形导体52的电流。谐振“2”(4.46GHz)的电流为线天线共模的电流。
请参阅图16d，谐振“3”(5.08GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511 流动的第一电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第二电流。第一条形导体41的电流强度与第三条形导体52均小于第二条形导体51的电流强度。这样，谐振“3”(5.08GHz)的电流主要为第二条形导体51的电流。谐振“3”(5.08GHz)的电流为线天线共模的电流。
请参阅图16e，图16e是图15所示的复合天线在谐振“1”下的SAR热点分布示意图。图16e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.86GHz)，后盖11的5mm处，出现了两个SAR热点(附图16e通过箭头1和箭头2简单地示意出了两个SAR热点)。可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反，另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，所以谐振“1”(3.86GHz)的SAR值比较低。
请参阅图16f，图16f是图15所示的复合天线在谐振“2”下的SAR热点分布示意图。图16f示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(4.46GHz),在后盖11的5mm处，出现了一个SAR热点(附图16f通过箭头1简单地示意出了一个SAR热点)。另外，第三条形导体52的第四电流能够经第二接地部分C较好地流入电路板30，这样，第三条形导体52上的电流强度较大程度被减弱，第三条形导体52产生的磁场强度也较小，谐振“2”(4.46GHz)的SAR值较低。故而，虽然谐振“2”(4.46GHz)出现了一个SAR热点，但是谐振“2”(4.46GHz)的SAR值也较低。
请参阅图16g，图16g是图15所示的复合天线在谐振“3”下的SAR热点分布示意图。图16g示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“3”(5.08GHz),在后盖11的5mm处，也出现了一个SAR热点(附图16g通过箭头1简单地示意出了一个SAR热点)。另外，第二条形导体51上的第三电流能够经第一接地部分B较好地流入电路板30，这样，第二条形导体51上的电流强度较大程度被减弱，第二条形导体51产生的磁场强度也较小，谐振“3”(5.08GHz)的SAR值较低。故而，虽然谐振“3”(5.08GHz)出现了一个SAR热点，但是谐振“3”(5.08GHz)的SAR值也较低。
另外，表3示出了采用第三种实施方式提供的复合天线的电子设备100的SAR值。
表3
Figure PCTCN2021089245-appb-000006
表3中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第三种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”以及谐振“3”，整体均较低。当效率归一化到-5dB时，第三种实施方式提 供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”以及谐振“3”，在距离后盖5mm的SAR值均小于0.9。
在本实施方式中，第三种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出三个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现三个模式的SAR值较低，且其中一个谐振模式能够产生两个SAR热点。
可以理解的是，本实施方式的第二条形导体51的设置方式也可以参阅第二种实施方式的第二条形导体51的设置方式。本实施方式的第三条形导体52的设置方式也可以参阅第二种实施方式的第三条形导体52的设置方式。这里不再赘述。
第四种实施方式，与第一种实施方式相同的技术内容不再赘述：请参阅图17，图17是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。电子设备100包括第二条形导体51。电子设备100不再包括第三条形导体52。第二条形导体51的形成方式及设置方式可以参阅第一种实施方式的第一导体51的形成方式及设置方式。这里不再赘述。
下面结合附图说明第四种实施方式提供的复合天线的仿真。
请参阅图18a，图18a是图17所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.68GHz)和谐振“2”(4.76GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。可以理解的是，除了图18a中示出的3.68GHz、4.76GHz频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者同时调整第一条形导体41与第二条形导体51的尺寸来设置。
以下结合图18b和图18c来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.68GHz)和谐振“2”(4.76GHz)的电流分布。图18b是图17所示的复合天线在谐振“1”下的电流的流向示意图。图18c是图17所示的天线在谐振“2”下的电流的流向示意图。
请参阅图18b，谐振“1”(3.68GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流。第一条形导体41的电流强度大于第二条形导体51的电流强度。这样，谐振“1”(3.68GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.68GHz)的电流为槽天线差模的电流。
请参阅图18c，谐振“2”(4.76GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流。第一条形导体41的电流强度小于第二条形导体51的电流强度。这样，谐振“2”(4.76GHz)的电流主要为第二条形导体51的电流。谐振“2”(4.76GHz)的电流 为线天线共模的电流。
请参阅图18d，图18d是图17所示的复合天线在谐振“1”下的SAR热点分布示意图。图18d示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.68GHz)，后盖11的5mm处，出现了两个SAR热点(附图18d通过箭头1和箭头2简单地示意出了两个SAR热点)。可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样,磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，所以谐振“1”(3.68GHz)的SAR值比较低。
请参阅图18e，图18e是图17所示的复合天线在谐振“2”下的SAR热点分布示意图。图18e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(4.76GHz),在后盖11的5mm处，出现了一个SAR热点(附图18e通过箭头1简单地示意出了该SAR热点)。另外，第二条形导体51上的第三电流能够经第一接地部分B较好地流入电路板30，这样，第二条形导体51上的电流强度较大程度被减弱。此时，第二条形导体51产生的磁场强度也较小，谐振“2”(4.76GHz)的SAR值较低。故而，虽然谐振“2”(4.76GHz)出现了一个SAR热点，但是谐振“2”(4.76GHz)的SAR值也较低。
另外，表4示出了采用第四种实施方式提供的复合天线的电子设备100的SAR值。
表4
Figure PCTCN2021089245-appb-000007
表4中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第四种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。当效率归一化到-5dB时，第四种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.8。
在本实施方式中，第四种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出两个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现两个模式的SAR值较低，且其中一个谐振模式能够产生两个SAR热点。
可以理解的是，本实施方式的第二条形导体51的设置方式也可以参阅第二种实施方式的第二条形导体51的设置方式。这里不再赘述。
第五种实施方式，与第一种实施方式相同的技术内容不再赘述：请参阅图19，图19是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。电子设备100包括第一条形导体41、第二条形导体51及第三条形导体52。第一条形导体41、第二条形导体51及第三条形导体52的形成方式及设置方式均可参阅第一种实施方式的第一条形导体41、第二条形导体51及第三条形导体52的形成方式及设置方式。这里不再赘述。
请参阅图20，图20是图19所示的复合天线在另一种角度的结构示意图。第二条形导体51包括第一端部511及远离第一端部511设置的第二端部512。第三条形导体52包括第一端部521及远离第一端部521的第二端部522。第二条形导体51的第一端部511连接于第三条形导体52的第一端部521。
第二条形导体51的第一端部511与第三条形导体52的第一端部521共同电连接于第一条形导体41的第一接地部分B。可以理解的是，第二条形导体51的第一端部511与第三条形导体52的第一端部521共同电连接于第一接地部分B包括两种实施方式：第一种方式是，第二条形导体51的第一端部511与第三条形导体52的第一端部521共同与第一接地部分B间隔设置，也即在Z轴方向上，第二条形导体51与第一条形导体41存在高度差，第三条形导体52与第一条形导体41存在高度差。此时，射频信号能够在第一条形导体41的第一接地部分B处通过磁场耦合馈电至至第二条形导体51的第一端部511，以及第三条形导体52的第一端部521。第二种方式是，第二条形导体51的第一端部511与第三条形导体52的第一端部521共同连接于第一条形导体41的第一接地部分B，也即在Z轴方向上，第二条形导体51、第三条形导体52与第一条形导体41同层设置。此时，射频信号能够经第一接地部分B馈电至第二条形导体51的第一端部511与第三条形导体52的第一端部521。在本实施方式中，以第一种方式为例进行描述。
另外，第二条形导体51的第二端部512为开放端，也即第二条形导体51的第二端部512未接地。第三条形导体52的第二端部522为开放端，也即第三条形导体52的第二端部522未接地。
在其他实施方式中，第二条形导体51的第一端部511与第三条形导体52的第一端部521共同电连接于第一条形导体41的第二接地部分C。
在本实施方式中，第一接地部分B与馈电部分A之间的中心距离和第二接地部分C与馈电部分A之间的中心距离可参阅第一种实施方式的第一值d1与第二值d2的关系。
请再次参阅图20，第二条形导体51的长度L1等于第三条形导体52的长度L2。可以理解的是，当考虑到公差与误差的存在时，在可允许的范围内，第二条形导体51的长度L1略大于或者略小于第三条形导体52的长度L2。
在其他实施方式中，第二条形导体51的长度L1大于或者小于第三条形导体52的长度L2。
请参阅图21，并结合图20所示，图21是图19所示的第一条形导体、第二条形导体以及第三条形导体在电路板的投影示意图。第一条形导体41在电路板30的板面的投影为第一投影S1。第二条形导体51在电路板30的板面的投影为第二投影S2。第二投影S2与第一投影S1之间的夹角为α。在本实施方式中，α等于90°。在其他实施方式中，α也可以等于10°、60°、125°、150°或者200°。
一种实施方式中，α在0°至180°的范围内。
此外，第三条形导体52在电路板30的板面的投影为第三投影S3。第三投影S3与第一投影S1之间的夹角为β。在本实施方式中，β等于90°。在其他实施方式中，β也可以等于30°、60°、125°、150°或者200°。
一种实施方式中，β也可以在0°至180°的范围内。
这样，在本实施方式中，第二条形导体51与第三条形导体52关于第一接地部分B呈对称图形。
另外，第一投影S1、第二投影S2以及第三投影S3的重合区域的面积在0-16平方毫米的范围内，例如0毫米、3毫米、7毫米、10毫米或者12毫米等。在本实施方式中，第一投影S1、第二投影S2以及第三投影S3的重合区域的面积为8平方毫米。可以理解的是，附图21仅示意性地给出了第一投影S1、第二投影S2以及第三投影S3的重叠区域为长方形。但当第一条形导体41、第二条形导体51以及第三条形导体52的形状发生变化时，第一投影S1、第二投影S2以及第三投影S3的重叠区域也可以为其他形状，例如不规则图形，或者梯形等。在其他实施方式中，第一投影S1、第二投影S2以及第三投影S3的重合区域的面积也可以不在0-16平方毫米的范围内。
下面结合附图说明第五种实施方式提供的复合天线的仿真。
请参阅图22a，图22a是图19所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.78GHz)和谐振“2”(5.34GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。可以理解的是，除了图22a中示出的3.78GHz、5.34GHz频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者调整第三条形导体52的尺寸，或者同时调整第一条形导体41、第二条形导体51与第三条形导体52的尺寸来设置。
以下结合图22b和图22c来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.78GHz)和谐振“2”(5.34GHz)的电流分布。图22b是图19所示的复合天线在谐振“1”下的电流的流向示意图。图22c是图19所示的天线在谐振“2”下的电流的流向示意图。
请参阅图22b，谐振“1”(3.78GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流。第一条形导体41的电流强度大于第二条形导体51与第三条形导体52的电流强度。这样，谐振“1”(3.78GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.78GHz)的电流为槽天线差模的电流。
请参阅图22c，谐振“2”(5.34GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流，以及第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流。第一条形导体41的电流强度小于第二条形导体51与第三条形导体52的电流强度。这样，谐振“2”(5.34GHz)的电流主要为第二条形导体51与第三条形导体52的电流。谐振“2”(5.34GHz)的电流为线天线共模的电流。
请参阅图22d，图22d是图19所示的复合天线在谐振“1”下的SAR热点分布示意图。 图22d示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.78GHz)，后盖11的5mm处，出现了两个SAR热点(附图22d通过箭头1和箭头2简单地示意出了两个SAR热点)。可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，所以谐振“1”(3.78GHz)的SAR值比较低。
请参阅图22e，图22e是图19所示的复合天线在谐振“2”下的SAR热点分布示意图。图22e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(5.34GHz),在后盖11的5mm处，出现了一个SAR热点(附图22e通过箭头1简单地示意出了该SAR热点)。
可以理解的是，复合天线在谐振“2”下，第二条形导体51上的第三电流与第三条形导体52的第四电流方向相反。另外，由于第二条形导体51与第三条形导体52关于第一接地部分B呈对称结构，第三电流的电流强度与第四电流的电流强度相同。可以理解的是，第二条形导体51与第三条形导体52的对称性越好，第三电流的电流强度与第四电流的电流强度越接近。此时，第一接地部分B的两侧的磁场相互减弱，辐射电磁波的能量较为分散。故而，虽然复合天线在谐振“2”下出现了一个SAR热点，但是谐振“2”(4.78GHz)的SAR值也较低。可以理解的是，第三电流的电流强度与第四电流的电流强度越接近，谐振“2”(4.78GHz)的SAR值越低。
另外，在本实施方式中，第一投影S1、第二投影S2以及第三投影S3的重合区域的面积为8平方毫米，第二条形导体51通过第一条形导体41的馈电较佳，第三条形导体52通过第一条形导体41的馈电较佳。此时，第二条形导体51上的第三电流能够经第一接地部分B较好地流入电路板30，第三条形导体52上的第四电流能够经第一接地部分B较好地流入电路板30，这样，第二条形导体51以及第三条形导体52上的电流强度较大程度被减弱。此时，第二条形导体51以及第三条形导体52产生的磁场强度也较小，谐振“2”(5.34GHz)的SAR值较低。
另外，表5示出了采用第五种实施方式提供的复合天线的电子设备100的SAR值。
表5
Figure PCTCN2021089245-appb-000008
表5中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第五种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。当效率归一化到-5dB时，第五种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.7。
在本实施方式中，第五种实施方式提供的天线设计方案，通过设计一种槽天线与线天 线的复合天线，从而在馈电下，复合天线分别激励出两个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现两个模式的SAR值较低，且其中一个谐振模式能够产生两个SAR热点。
可以理解的是，本实施方式的第二条形导体51的设置方式也可以参阅第二种实施方式的第二条形导体51的设置方式。本实施方式的第三条形导体52的设置方式也可以参阅第二种实施方式的第三条形导体52的设置方式。这里不再赘述。
第六种实施方式，与第一种实施方式至第五种实施方式的相同的技术内容不再赘述：请参阅图23，图23是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。电子设备100还包括第四条形导体53及第五条形导体54。第四条形导体53位于馈电部分A背向第二条形导体51的一侧。第五条形导体54位于馈电部分A背向第三条形导体52的一侧。
请参阅图24，图24是图23所示的复合天线在另一种角度的结构示意图。第四条形导体53包括第一端部531及远离第一端部531的第二端部532。此外，第五条形导体54包括第一端部541及远离第一端部541的第二端部542。第四条形导体53的第一端部531连接于第五条形导体54的第一端部541。
另外，第四条形导体53的第一端部531与第五条形导体54的第一端部541共同电连接于第一条形导体41的第二接地部分C。可以理解的是，第四条形导体53的第一端部531与第五条形导体54的第一端部541共同电连接于第二接地部分C包括两种实施方式：第一种方式是，第四条形导体53的第一端部531与第五条形导体54的第一端部541共同与第二接地部分C间隔设置，也即在Z轴方向上，第四条形导体53与第一条形导体41存在高度差，第五条形导体54与第一条形导体41存在高度差。此时，射频信号能够在第一条形导体41的第二接地部分C处通过磁场耦合馈电至至第四条形导体53的第一端部531与第五条形导体54的第一端部541。第二种方式是，第四条形导体53的第一端部531与第五条形导体54的第一端部541共同连接于第一条形导体41的第二接地部分C，也即在Z轴方向上，第四条形导体53、第五条形导体54与第一条形导体41同层设置。此时，射频信号能够经第二接地部分C馈电至第四条形导体53的第一端部531与第五条形导体54的第一端部541。在本实施方式中，以第一种方式为例进行描述。
另外，第四条形导体53的第二端部532为开放端，也即第四条形导体53的第二端部532未接地。第五条形导体54的第二端部542为开放端，也即第五条形导体54的第二端部542未接地。
在本实施方式中，第一接地部分B与馈电部分A之间的中心距离和第二接地部分C与馈电部分A之间的中心距离可参阅第一种实施方式的第一值d1与第二值d2的关系。这里不再赘述。
此外，第二条形导体51的长度为第一长度L1。第三条形导体52的长度为第二长度L2。第一长度L1等于第二长度L2。可以理解的是，当考虑到公差与误差的存在时，在可允许的范围内，第一长度L1可以略大于第二长度L2，或者略小于第二长度L2。换言之第一长度L1大致等于第二长度L2。
此外，第四条形导体53的长度为第三长度L3。第五条形导体54的长度为第四长度L4。第三长度L3等于第四长度L4。可以理解的是，当考虑到公差与误差的存在时，在可允许的范围内，第三长度L3可以略大于第四长度L4，或者略小于第四长度L4。换言之第三长度L3大致等于第四长度L4。
在本实施方式中，第一长度L1与第二长度L2之和等于第三长度L3与第四长度L4之和。
请参阅图25，并结合图24所示，图25是图23所示的第一条形导体、第二条形导体以及第三条形导体在电路板的投影示意图。第一条形导体41在电路板30的板面的投影S1、第二条形导体51在电路板30的板面的投影S2以及第三条形导体52在电路板30的板面的投影S3的设置方式可以参阅第五种实施方式的第一投影S1、第二投影S2以及第三投影S3的设置方式。这里不再赘述。
另外，第四条形导体53在电路板30的板面的投影为第四投影S4。第四投影S4与第一投影S1之间的夹角为γ。在本实施方式中，γ等于90°。在其他实施方式中，γ也可以等于30°、60°、125°、150°或者200°。
一种实施方式中，γ在0°至180°的范围内。
此外，第五条形导体54在电路板30的板面的投影为第五投影S5。第五投影S5与第一投影S1之间的夹角为δ。在本实施方式中，δ等于90°。在其他实施方式中，δ也可以在0°至180°的范围内。例如：δ也可以等于30°、60°、125°、150°或者170°。
一种实施方式中，δ在0°至180°的范围内。
这样，在本实施方式中，第四条形导体53及第五条形导体54关于第二接地部分C呈对称图形。另外，第二条形导体51及第三条形导体52关于馈电部分A与第四条形导体53及第五条形导体54呈对称图形。
另外，第一投影S1、第四投影S4以及第五投影S5的重合区域的面积在0-16平方毫米的范围内，例如重合区域的面积为0毫米、3毫米、7毫米、10毫米或者12毫米等。在本实施方式中，第一投影S1、第四投影S4以及第五投影S5的重合区域的面积为8平方毫米。可以理解的是，附图25仅示意性地给出了第一投影S1、第四投影S4以及第五投影S5的重叠区域为长方形。但当第一条形导体41、第四条形导体53及第五条形导体54的形状发生变化时，第一投影S1、第四投影S4以及第五投影S5的重叠区域也可以为其他形状，例如不规则图形，或者梯形等。
在其他实施方式中，第一投影S1、第四投影S4以及第五投影S5的重合区域的面积也可以不在0-16平方毫米的范围内。
下面结合附图说明第六种实施方式提供的复合天线的仿真。
请参阅图26a，图26a是图23所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生两个谐振，谐振“1”(3.68GHz)和谐振“2”(5.38GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”是复合天线的线天线共模产生的。可以理解的是，除了图26a中示出的3.68GHz、5.38GHz频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或 者调整第三条形导体52的尺寸，或者调整第四条形导体53的尺寸，或者调整第五条形导体54的尺寸，或者调整同时调整第一条形导体41、第二条形导体51、第三条形导体52、第四条形导体53的尺寸与第五条形导体54的尺寸来设置。
以下结合图26b和图26c来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.68GHz)和谐振“2”(5.38GHz)的电流分布。图26b是图23所示的复合天线在谐振“1”下的电流的流向示意图。图26c是图23所示的天线在谐振“2”下的电流的流向示意图。
请参阅图26b，谐振“1”(3.68GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流、第四条形导体53上自第四条形导体53的第一端部531向第四条形导体53的第二端部532流动的第五电流、第五条形导体54中自第五条形导体54的第一端部541向第五条形导体54的第二端部542流动的第六电流。第一条形导体41的电流强度大于第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54的电流强度。这样，谐振“1”(3.68GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.68GHz)的电流为槽天线差模的电流。
请参阅图26c，谐振“2”(5.38GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流、第四条形导体53上自第四条形导体53的第二端部532向第四条形导体53的第一端部531流动的第五电流、第五条形导体54中自第五条形导体54的第二端部542向第五条形导体54的第一端部541流动的第六电流。第一条形导体41的电流强度小于第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54的电流强度。这样，谐振“2”(5.38GHz)的电流主要为第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54的电流。谐振“2”(5.38GHz)的电流为线天线共模的电流。
请参阅图26d，图26d是图23所示的复合天线在谐振“1”下的SAR热点分布示意图。图26d示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.68GHz)，后盖11的5mm处，出现了两个SAR热点(附图26d通过箭头1和箭头2简单地示意出了两个SAR热点)。
可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。这样，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，所以谐振“1”(3.68GHz)的SAR值比较低。
请参阅图26e，图26e是图23所示的复合天线在谐振“2”下的SAR热点分布示意图。 图26e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(5.38GHz),在后盖11的5mm处，也出现了两个SAR热点(附图26e通过箭头1和箭头2简单地示意出了两个SAR热点)。
可以理解的是，复合天线在谐振“2”下，第二条形导体51上的第三电流与第三条形导体52的第四电流方向相反，第四条形导体53上的第五电流与第五条形导体54的第六电流方向相反。另外，由于第二条形导体51及第三条形导体54关于第一接地部分B呈对称图形，第三电流的电流强度与第四电流的电流强度相同。另外，由于第四条形导体53及第五条形导体54关于第二接地部分C呈对称图形，第五电流的电流强度与第六电流的电流强度相同。另外，第二条形导体51及第三条形导体52关于馈电部分A与第四条形导体53及第五条形导体54呈对称图形，此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，谐振“2”(5.38GHz)的SAR值也较低。
此外，第一投影S1、第二投影S2以及第三投影S3的重合区域的面积为8平方毫米，第二条形导体51通过第一条形导体41的馈电较佳，第三条形导体52通过第一条形导体41的馈电较佳。此时，第三电流与第四电流均能够经第一接地部分B较好地流入电路板30。另外，第一投影S1、第四投影S4以及第五投影S5的重合区域的面积为8平方毫米，第四条形导体53通过第一条形导体41的馈电较佳，第五条形导体54通过第一条形导体41的馈电较佳。此时，第五电流与第六电流均能够经第二接地部分C较好地流入电路板。这样，第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54上的电流强度较大程度被减弱。此时，第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54产生的磁场强度也较小，谐振“2”(5.38GHz)的SAR值也较低。
另外，表6示出了采用第六种实施方式提供的复合天线的电子设备100的SAR值。
表6
Figure PCTCN2021089245-appb-000009
表1中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第六种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”，整体均较低。当效率归一化到-5dB时，第六种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”，在距离后盖5mm的SAR值均小于0.5。
在本实施方式中，第六种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出两个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现两个模式均能够出现两个SAR热点，且两个模式的SAR值较低。
可以理解的是，本实施方式的第二条形导体51的设置方式也可以参阅第二种实施方式的第二条形导体51的设置方式。本实施方式的第三条形导体52的设置方式也可以参阅第 二种实施方式的第三条形导体52的设置方式。这里不再赘述。
在其他实施方式中，第四条形导体53的第一端部531连接于第一条形导体41的第二接地部C。第五条形导体54的第一端部541连接于第一条形导体41的第二接地部C。
第七种实施方式，与第一种实施方式至第六种实施方式相同的技术内容不再赘述：请参阅图27，图27是图1所示的电子设备的复合天线的再一种实施方式的部分结构示意图。第二条形导体51的长度为第一长度L1。第三条形导体52的长度为第二长度L2。第一长度L1等于第二长度L2。第四条形导体53的长度为第三长度L3。第五条形导体54的长度为第四长度L4。第三长度L3等于第四长度L4。此外，第一长度L1与第二长度L2之和小于第三长度L3与第四长度L4之和。
下面结合附图说明第七种实施方式提供的复合天线的仿真。
请参阅图28a，图28a是图27所示的复合天线在频段为3至6GHz的反射系数与频率的关系图。复合天线在3至6GHz可以产生三个谐振，谐振“1”(3.62GHz)、谐振“2”(4.95GHz)和谐振“3”(5.75GHz)。谐振“1”是复合天线的槽天线差模产生的。谐振“2”和谐振“3”均是复合天线的线天线共模产生的。可以理解的是，除了图28a中示出的3.62GHz、4.95GHz以及5.75GHz的频段，本实施方式的复合天线还可以产生其他频段(例如：0GHz至3GHz，6GHz至8GHz，或者8GHz至11GHz)的谐振，具体可通过调整第一条形导体41的尺寸，或者调整第二条形导体51的尺寸，或者调整第三条形导体52的尺寸，或者调整第四条形导体53的尺寸，或者调整第五条形导体54的尺寸，或者调整同时调整第一条形导体41、第二条形导体51、第三条形导体52、第四条形导体53的尺寸与第五条形导体54的尺寸来设置。
以下结合图28b、图28c和图28d来具体描述一下复合天线的两个谐振的电流：谐振“1”(3.62GHz)、谐振“2”(4.95GHz)和谐振“3”(5.75GHz)的电流分布。图28b是图27所示的复合天线在谐振“1”下的电流的流向示意图。图28c是图27所示的天线在谐振“2”下的电流的流向示意图。图28d是图27所示的复合天线在谐振“3”下的电流的流向示意图。
请参阅图28b，谐振“1”(3.62GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体的第一端部511向第二条形导体51的第二端部512流动的第三电流、第三条形导体52上自第三条形导体52的第一端部521向第三条形导体52的第二端部522流动的第四电流、第四条形导体53上自第四条形导体53的第一端部531向第四条形导体53的第二端部532流动的第五电流、第五条形导体54中自第五条形导体54的第一端部541向第五条形导体54的第二端部542流动的第六电流。第一条形导体41的电流强度大于第二条形导体51、第三条形导体52、第四条形导体53以及第五条形导体54的电流强度。这样，谐振“1”(3.62GHz)的电流主要为第一条形导体41的电流。此外，谐振“1”(3.62GHz)的电流为槽天线差模的电流。
请参阅图28c，谐振“2”(4.95GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511 流动的第三电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流、第四条形导体53上自第四条形导体53的第二端部532向第四条形导体53的第一端部531流动的第五电流、第五条形导体54中自第五条形导体54的第二端部542向第五条形导体54的第一端部541流动的第六电流。第一条形导体41、第二条形导体51以及第三条形导体52的电流强度小于第四条形导体53以及第五条形导体54的电流强度。这样，谐振“2”(4.95GHz)的电流主要为第四条形导体53以及第五条形导体54的电流。谐振“2”(4.95GHz)的电流为线天线共模的电流。
请参阅图28d，谐振“3”(5.75GHz)的电流分布包括第一条形导体41上自第一接地部分B向馈电部分A流动的第一电流以及自第二接地部分C向馈电部分A流动的第二电流、第二条形导体51上自第二条形导体51的第二端部512向第二条形导体51的第一端部511流动的第三电流、第三条形导体52上自第三条形导体52的第二端部522向第三条形导体52的第一端部521流动的第四电流、第四条形导体53上自第四条形导体53的第二端部532向第四条形导体53的第一端部531流动的第五电流、第五条形导体54中自第五条形导体54的第二端部542向第五条形导体54的第一端部541流动的第六电流。第一条形导体41、第四条形导体53以及第五条形导体54的电流强度小于第二条形导体51以及第三条形导体52的电流强度。这样，谐振“3”(5.75GHz)的电流主要为第二条形导体51以及第三条形导体52的电流。谐振“3”(5.75GHz)的电流为线天线共模的电流。
请参阅图28e，图28e是图27所示的复合天线在谐振“1”下的SAR热点分布示意图。图28e示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“1”(3.62GHz)，后盖11的5mm处，出现了两个SAR热点(附图28e通过箭头1和箭头2简单地示意出了两个SAR热点)。可以理解的是，复合天线在谐振“1”下，第一条形导体41上的第一电流与第二电流的方向相反。另外，由于第一条形导体41呈对称图形，使得第一电流的电流强度与第二电流的电流强度相同。此时，馈电部分A处的磁场的相位相反，磁场的幅度大致被抵消。这样，磁场主要分布在馈电部分A的两侧，在馈电部分A的两侧形成两个SAR热点。此时，辐射电磁波的能量较为分散，所以谐振“1”(3.62GHz)的SAR值比较低。
请参阅图28f，图28f是图27所示的复合天线在谐振“2”下的SAR热点分布示意图。图28f示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“2”(4.95GHz),在后盖11的5mm处，也出现了一个SAR热点(附图28f通过箭头1简单地示意出了一个SAR热点)。但是，第四条形导体53的第五电流与第五条形导体54的第六电流均能够经第二接地部分C较好地流入电路板30，这样，第四条形导体53与第五条形导体54上的电流强度较大程度被减弱。此时，第四条形导体53与第五条形导体54产生的磁场强度也较小。此时，虽然谐振“2”(4.95GHz)出现了一个SAR热点，但是谐振“2”的SAR值也较低。
请参阅图28g，图28g是图27所示的复合天线在谐振“3”下的SAR热点分布示意图。图28g示意了在人体组织距离后盖11的5mm处测量到的SAR值。对于谐振“3”(5.75GHz),在后盖11的5mm处，也出现了一个SAR热点(附图28g通过箭头1简单地示意出了一个SAR热点)。但是，第二条形导体51上的第三电流以及第三条形导体52的第四电流均能够经第一接地部分B较好地流入电路板30，这样，第二条形导体51以及第三条形导体52上的电流强度较大程度被减弱。此时，第二条形导体51以及第三条形导体52产生的磁场强 度也较小。此时，虽然谐振“3”(5.75GHz)出现了一个SAR热点，但是谐振“3”(5.75GHz)的SAR值较低。
另外，表7示出了采用第七种实施方式提供的复合天线的电子设备100的SAR值。
表7
Figure PCTCN2021089245-appb-000010
表7中示出的是10g标准的SAR值。可以看出，在输出功率都为24dBm时，采用第七种实施方式提供的复合天线的电子设备100在距离后盖5mm的SAR值，不管在谐振“1”，还是谐振“2”以及谐振“3”，整体均较低。当效率归一化到-5dB时，第七种实施方式提供的复合天线在低SAR值方面的优势更明显。不管在谐振“1”，还是谐振“2”以及谐振“3”，在距离后盖5mm的SAR值均小于0.7。
在本实施方式中，第七种实施方式提供的天线设计方案，通过设计一种槽天线与线天线的复合天线，从而在馈电下，复合天线分别激励出三个谐振模式(槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现三个模式的SAR值较低，且其中一个谐振模式能够产生两个SAR热点。
上文具体介绍了七种槽天线与线天线组合的复合天线的结构的实施方式。可以理解的是，上述的每个实施方式均能够实现，复合天线分别激励出多个谐振模式(包括槽天线差模和线天线共模)，在实现宽频覆盖的同时，还可实现多个模式的SAR值较低。
以上所述，仅为本申请的具体实施方式，但本申请的保护范围并不局限于此，任何熟悉本技术领域的技术人员在本申请揭露的技术范围内，可轻易想到变化或替换，都应涵盖在本申请的保护范围之内。因此，本申请的保护范围应以所述权利要求的保护范围为准。

Claims (13)

  1. 一种电子设备，其特征在于，包括后盖、电路板、射频收发电路、支架、第一天线及第二天线，所述电路板与所述射频收发电路位于所述后盖的同一侧，所述支架固定于所述电路板与所述后盖之间；
    所述第一天线包括第一条形导体，所述第一条形导体固定于所述支架，所述第一条形导体包括第一接地部分、第二接地部分及馈电部分，所述第一接地部分与所述第二接地部分分别为所述第一条形导体的两个端部，所述第一接地部分与所述第二接地部分均通过所述电路板接地，所述馈电部分位于所述第一接地部分与所述第二接地部分之间，且电连接于所述射频收发电路，所述电路板朝向所述后盖的板面与所述第一条形导体之间形成所述第一天线的净空区域；
    所述第二天线包括第二条形导体，所述第二条形导体固定于所述后盖或者所述支架，所述第二条形导体包括第一端部及第二端部，所述第二条形导体的第一端部与所述第一接地部分电连接，所述第二条形导体的第二端部为开放端，所述电路板朝向所述后盖的板面与所述第二条形导体之间形成所述第二天线的净空区域。
  2. 根据权利要求1所述的电子设备，其特征在于，所述第二天线还包括第三条形导体，所述第三条形导体固定于所述后盖或者所述支架，所述第三条形导体包括第一端部及第二端部，所述第三条形导体的第一端部与所述第二接地部分电连接，所述第三条形导体的第二端部为开放端，所述电路板朝向所述后盖的板面与所述第三条形导体之间形成所述第二天线的净空区域。
  3. 根据权利要求2所述的电子设备，其特征在于，所述第一条形导体在所述电路板的板面的投影为第一投影，所述第二条形导体在电路板的板面的投影为第二投影，所述第二投影与所述第一投影的夹角为第一角度，所述第一角度在90°至270°的范围内，所述第三条形导体在所述电路板的板面的投影为第三投影，所述第三投影与所述第一投影的夹角为第二角度，所述第二角度在90°至270°的范围内。
  4. 根据权利要求3所述的电子设备，其特征在于，所述第一角度与所述第二角度均等于180°，且所述第二条形导体的长度等于所述第三条形导体的长度。
  5. 根据权利要求1所述的电子设备，其特征在于，所述第二天线还包括第三条形导体，所述第三条形导体固定于所述后盖或者所述支架，所述第三条形导体包括第一端部及第二端部，所述第三条形导体的第一端部连接于所述第二条形导体的第一端部，所述第三条形导体的第一端部与所述第一接地部分电连接，所述第三条形导体的第二端部为开放端，所述电路板朝向所述后盖的板面与所述第三条形导体之间形成所述第二天线的净空区域。
  6. 根据权利要求5所述的电子设备，其特征在于，所述第二天线还包括第四条形导体 及第五条形导体，所述第四条形导体与所述第五条形导体均固定于所述后盖或者所述支架，所述电路板朝向所述后盖的板面与所述第四条形导体之间形成所述第二天线的净空区域，所述电路板朝向所述后盖的板面与所述第五条形导体形成所述第二天线的净空区域；
    所述第四条形导体的一端连接于所述第五条形导体的一端，所述第四条形导体与所述第五条形导体的连接端共同电连接于所述第二接地部分，所述第四条形导体远离所述第五条形导体的一端与所述第五条形导体远离所述第四条形导体的一端均为开放端。
  7. 根据权利要求6所述的电子设备，其特征在于，所述第四条形导体的长度与所述第五条形导体的长度之和等于所述第二条形导体与所述第三条形导体的长度之和。
  8. 根据权利要求1至7中任一项所述的电子设备，其特征在于，所述馈电部分与所述第一接地部分的中心距离为第一值，所述馈电部分与所述第二接地部分的中心距离为第二值，所述第一值与所述第二值的比值在0.8至1.2的范围内。
  9. 根据权利要求1至8中任一项所述的电子设备，其特征在于，所述第一天线与所述第二天线产生多个谐振模式，且所述第一天线的谐振模式产生两个SAR热点。
  10. 根据权利要求1至8中任一项所述的电子设备，其特征在于，所述第一天线与所述第二天线产生多个谐振模式，且每个所述谐振模式的SAR值均小于1。
  11. 根据权利要求1至8中任一项所述的电子设备，其特征在于，所述第一条形导体激励出的电流包括自所述第一接地部分流向所述馈电部分的第一电流，以及自所述第二接地部分流向所述馈电部分的第二电流。
  12. 根据权利要求1至8中任一项所述的电子设备，其特征在于，所述第二条形导体激励出的电流包括自所述第二条形导体的第二端部流向所述第二条形导体的第一端部的电流。
  13. 根据权利要求1至8中任一项所述的电子设备，其特征在于，所述第二条形导体的第一端部与所述第一接地部分直馈；或者，所述第二条形导体的第一端部与所述第一接地部分间接耦合馈电。
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EP4131651A1 (en) 2023-02-08
US20230170609A1 (en) 2023-06-01

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