WO2021204084A1 - 频偏估计方法及装置、电子设备、计算机可读介质 - Google Patents

频偏估计方法及装置、电子设备、计算机可读介质 Download PDF

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WO2021204084A1
WO2021204084A1 PCT/CN2021/085304 CN2021085304W WO2021204084A1 WO 2021204084 A1 WO2021204084 A1 WO 2021204084A1 CN 2021085304 W CN2021085304 W CN 2021085304W WO 2021204084 A1 WO2021204084 A1 WO 2021204084A1
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Prior art keywords
frequency offset
offset estimation
sample point
set interval
angle data
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PCT/CN2021/085304
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English (en)
French (fr)
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李双喜
姚扬中
曹南山
李运鹏
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中兴通讯股份有限公司
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Priority to EP21783743.4A priority Critical patent/EP4135277A4/en
Priority to US17/916,327 priority patent/US11894966B2/en
Publication of WO2021204084A1 publication Critical patent/WO2021204084A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/26—Systems using multi-frequency codes
    • H04L27/2601—Multicarrier modulation systems
    • H04L27/2647—Arrangements specific to the receiver only
    • H04L27/2655—Synchronisation arrangements
    • H04L27/2657—Carrier synchronisation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/60—Receivers
    • H04B10/61—Coherent receivers
    • H04B10/616—Details of the electronic signal processing in coherent optical receivers
    • H04B10/6164—Estimation or correction of the frequency offset between the received optical signal and the optical local oscillator
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/38—Synchronous or start-stop systems, e.g. for Baudot code
    • H04L25/40—Transmitting circuits; Receiving circuits
    • H04L25/49—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems
    • H04L25/4917—Transmitting circuits; Receiving circuits using code conversion at the transmitter; using predistortion; using insertion of idle bits for obtaining a desired frequency spectrum; using three or more amplitude levels ; Baseband coding techniques specific to data transmission systems using multilevel codes
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/32—Carrier systems characterised by combinations of two or more of the types covered by groups H04L27/02, H04L27/10, H04L27/18 or H04L27/26
    • H04L27/34—Amplitude- and phase-modulated carrier systems, e.g. quadrature-amplitude modulated carrier systems
    • H04L27/38—Demodulator circuits; Receiver circuits
    • H04L27/3845—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier
    • H04L27/3881—Demodulator circuits; Receiver circuits using non - coherent demodulation, i.e. not using a phase synchronous carrier using sampling and digital processing, not including digital systems which imitate heterodyne or homodyne demodulation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/0014—Carrier regulation
    • H04L2027/0024—Carrier regulation at the receiver end
    • H04L2027/0026—Correction of carrier offset
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00—Modulated-carrier systems
    • H04L27/01—Equalisers

Definitions

  • the embodiments of the present disclosure relate to the field of communication technology, and in particular to frequency offset estimation methods and devices, electronic equipment, and computer-readable media.
  • embodiments of the present disclosure provide a frequency offset estimation method, which includes:
  • Sample points are extracted from the input signal according to a set interval to obtain a plurality of sample point groups, and the set interval of each sample point group is different;
  • the frequency offset estimation value of the current input signal is determined by using the complex angle data corresponding to the set interval.
  • a frequency offset estimation device which includes:
  • the sampling module is configured to extract sample points from the input signal at a set interval to obtain multiple sample point groups, and the set interval of each sample point group is different;
  • An angle data obtaining module configured to process the current sample point and the sample points in each of the sample point groups separately to obtain the complex angle data corresponding to the set interval;
  • the frequency offset estimation module is configured to determine the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval.
  • an electronic device which includes:
  • One or more processors are One or more processors;
  • a memory having one or more programs stored thereon, and when the one or more programs are executed by the one or more processors, the one or more processors are caused to execute the above-mentioned frequency offset estimation method;
  • One or more I/O interfaces are connected between the processor and the memory, and are configured to implement information interaction between the processor and the memory.
  • an embodiment of the present disclosure provides a computer-readable medium on which a computer program is stored, and the computer program implements the frequency offset estimation method described above when the computer program is executed by a processor.
  • Figure 1 is a correlation method frequency offset estimation device
  • FIG. 2 is a flowchart of a frequency offset estimation method provided by an embodiment of the disclosure
  • FIG. 3 is a specific flowchart of step 202 in the frequency offset estimation method provided by an embodiment of the disclosure
  • FIG. 4 is a specific flowchart of step 203 in the frequency offset estimation method provided by an embodiment of the disclosure.
  • FIG. 5 is a schematic diagram of frequency offset calculation in a frequency offset estimation method provided by an embodiment of the disclosure.
  • FIG. 6 is a flowchart of another frequency offset estimation method provided by an embodiment of the disclosure.
  • FIG. 7 is a schematic diagram of a frequency offset estimation device provided by an embodiment of the disclosure.
  • FIG. 8 is a schematic diagram of an angle data obtaining module in the frequency offset estimation device provided by an embodiment of the disclosure.
  • FIG. 9 is a schematic diagram of a part of the structure of a frequency offset estimation device provided by an embodiment of the disclosure.
  • FIG. 10 is a block diagram of an electronic device provided by an embodiment of the disclosure.
  • the 400Gb/s PM-16QAM (Polarization Multiplexing-Quad Phase Shift Keying) coherent optical communication receiver obtains two signals after equalization and polarization demultiplexing, namely X polarization signal and Y polarization signal. Since the frequency of the laser in the coherent optical communication transmitter is not completely consistent with the frequency of the laser in the coherent optical communication receiver, the two polarization signals output by the equalizer have frequency deviations. The frequency offset needs to be estimated to obtain the frequency offset estimation signal to compensate the frequency of the coherent optical communication receiver, thereby improving the signal quality of the optical communication system.
  • Figure 1 is a correlation method frequency offset estimation device.
  • the input complex signal is divided into two paths. One complex signal is input to the register 101, and the other complex signal is directly input to the multiplier 102.
  • the register 101 delays and conjugates the complex signal to obtain a delayed conjugate signal, and the conjugate signal is input to the multiplier 102.
  • the multiplier 102 multiplies the complex signal and the conjugate signal to obtain the multiplication result signal, and the multiplication result signal is transmitted to the fourth power generator 103.
  • the fourth power generator 103 performs a fourth power operation on the multiplication result signal, and then outputs the result to the summer 104.
  • the summer 104 is used to reduce the influence of noise on the frequency offset estimation.
  • the 1/4 argument is taken by the 1/4 argument 105 on the output result of the summer 104, and the frequency offset estimation signal is output.
  • the delay amount D of the register 101 is an integer greater than or equal to 1.
  • the delay amount D is equal to 1
  • the frequency offset estimation range is large, but the estimation accuracy is low; when the delay amount D increases, the frequency offset estimation The range becomes smaller, and the estimation accuracy is improved.
  • the value of the delay amount D is increased. This single adjustment method often exists when the frequency offset estimation has not reached the required accuracy, and the delay amount D has been switched to a large value, which leads to fuzzy frequency offset estimation and may output wrong frequency offset estimation results.
  • the embodiments of the present disclosure provide a frequency offset estimation method, which is applied to a coherent optical communication receiver to estimate the difference between the frequency of the laser in the coherent optical communication transmitter and the frequency of the laser in the coherent optical communication receiver. Frequency offset, to compensate or correct the frequency of the coherent optical communication receiver.
  • the frequency offset estimation method of the embodiment of the present disclosure can estimate the frequency offset of any one of the X polarization signal and the Y polarization signal, and then apply the frequency offset estimation result to the other polarization signal; alternatively, it can perform the frequency offset estimation on the X polarization signal and the Y polarization signal.
  • the frequency offset of the Y-polarized signal is estimated at the same time.
  • the following embodiments are described by taking the simultaneous frequency offset estimation of the X-polarized signal and the Y-polarized signal as an example.
  • FIG. 2 is a flowchart of a frequency offset estimation method provided by an embodiment of the disclosure. 2, the frequency offset estimation method includes the following steps 201 to 203.
  • step 201 samples are extracted from the input signal according to a set interval to obtain a plurality of sample point groups, and the set interval of each sample point group is different.
  • the input signal may be a time-domain signal after equalizing and filtering the digital baseband electrical signal, and the equalizing and filtering signal is a signal with a parallelism of 64.
  • the input signal can be stored first.
  • the length of the stored input signal at least meets the requirement of sample extraction, that is, it must ensure that the required number of samples can be extracted, for example, the stored input signal
  • the length can be expressed by the number of samples, which can be the number of samples required to be sampled plus the set interval between the samples to be sampled.
  • the setting interval is also called the delay interval, which can be set arbitrarily as required. If the interval is set to 4, one sample will be sampled every 4 samples.
  • the number of sampling points can also be set arbitrarily according to needs, such as sampling 20, 50, and 80 samples. More specifically, when one sample is extracted every 4 samples, and each sample group includes 5 samples, the length of the stored input signal should include at least 21 samples.
  • the set interval of each sample point group is different, in other words, each sample point group uses a different set interval for extraction.
  • the set interval can be 1, including 32 samples.
  • the set interval can be 4, including 32 samples.
  • the set interval can be 16, including 32 samples.
  • sampling objects of each sample point group in the embodiments of the present disclosure are the same, that is, different sample point groups are extracted from the input signal in the same sampling period.
  • Step 202 Process the current sample point and the sample points in each sample point group separately to obtain complex angle data corresponding to a set interval.
  • the current sample point is any sample point in the current input signal, and the current input signal and the input signal used to extract the sample point group are input signals in the same sampling period.
  • step 202 the current sample point and the sample point in the sample point group are respectively processed, such as fourth power operation, summation, filtering, and angle calculation, to obtain complex angle data.
  • each sample point group corresponds to one complex angle data. For example, when there are three sample point groups, three complex angle data can be obtained. Of course, when there are a large number of sample point groups, it is also possible to obtain complex angle data less than the number of sample point groups.
  • Step 203 Determine the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval.
  • step 203 the frequency offset estimation value of the current input signal is determined by using the complex angle data.
  • the frequency offset estimation value may be determined by estimating the frequency offset value step by step with respect to the complex angle data corresponding to the set interval, and the estimation range of each stage is 1/4 of the previous stage.
  • FIG. 3 is a specific flowchart of step 202 in the frequency offset estimation method provided by an embodiment of the disclosure. As shown in FIG. 3, the following steps 301 to 304 are performed on the current sample point and the sample points in each sample point group.
  • Step 301 Perform conjugate multiplication, amplitude multiplication, and phase subtraction on the current sample point and the sample point in the sample point group, and perform an M-th power operation to obtain an M-th power correlation value.
  • step 301 for the X-polarized signal and Y-polarized signal, perform conjugate multiplication, amplitude multiplication, and phase subtraction of the current sample point with the sample point in the sample point group, and perform the M-th power operation to obtain M times Square correlation value, M is an integer greater than 2.
  • the current sample point is conjugate multiplied, amplitude multiplied and phase subtracted with the three sample point groups, and processed to the fourth power to obtain the fourth power correlation values R1, R2, and R3.
  • R 1 represents the fourth power correlation value with the set interval of 1
  • R 2 represents the fourth power correlation value with the set interval of 4
  • R 3 represents the fourth correlation value with the set interval of 16.
  • value Represents the signal amplitude
  • t is the sample point extraction time
  • e j4 represents fourth power processing
  • x represents the X-polarized signal
  • y represents the Y-polarized signal.
  • so on Represents the signal amplitude of the X polarization signal of the current sample and the sample extracted at (t+1)
  • this embodiment takes the fourth power processing as an example for description. In fact, other power processing can also be performed, and the present disclosure does not specifically limit it.
  • step 302 the correlation value is added once every N beats to the M power to obtain accumulated data.
  • N is an integer greater than 2
  • the N-beat M-th power correlation value represents N M-th power correlation values, that is, N consecutive M-th power correlation values can be accumulated.
  • N can be selected as 32, that is, every 32 consecutive M-th power correlation values can be accumulated once.
  • R sum,1 represents the accumulated data corresponding to the sample group with the set interval of 1
  • R 1 [count] represents the fourth power correlation value with the set interval of 1
  • R sum,2 represents the set
  • R 2 [count] represents the fourth power correlation value with the set interval of 4
  • R sum,3 represents the accumulated data corresponding to the sample group with the set interval of 16
  • R 3 [ count] represents the correlation value of the fourth power with the set interval of 16.
  • Step 303 Filter the accumulated data to obtain filtered data.
  • a first-order IIR digital filter is used for low-pass filtering to smooth the accumulated data.
  • ⁇ 1 , ⁇ 2 , and ⁇ 3 are the configured filter coefficients
  • Ravg,1 represents the filter data corresponding to the sample group with a set interval of 1
  • Ravg,2 represents the set of filter data with a set interval of 4.
  • the filter data corresponding to the sample group, Ravg,16 represents the filter data corresponding to the sample group with a set interval of 16.
  • Step 304 Obtain complex angle data corresponding to the set interval according to the filtered data and the set interval.
  • step 304 a complex angle is calculated according to the filtered filter data and the set interval.
  • F 1 , F 2 , F 3 represent complex angle data
  • Arg() represents the complex angle
  • the unit is turns
  • the value range is usually [-0.5,0.5] turns
  • 4. 16 and 64 are numerical values related to the set interval.
  • the frequency offset value is estimated step by step with respect to the complex angle data corresponding to the set interval to obtain the frequency offset estimation value of the current input signal.
  • the estimation range of each level is 1/4 of the previous level.
  • FIG. 4 is a specific flowchart of step 203 in the frequency offset estimation method provided by an embodiment of the disclosure. As shown in FIG. 4, determining the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval (that is, step 203) includes the following steps 401 and 402.
  • Step 401 Classify the complex angle data according to the set interval, and the smaller the set interval, the lower the level of the complex angle data.
  • the complex data angle F 1 with the set interval of 1 is the first level
  • the complex data angle F 2 with the set interval of 4 is the second level
  • the set interval is The complex data angle F 3 of 16 is the third level, respectively.
  • Step 402 Estimating the frequency offset value step by step with respect to the complex angle data to obtain the frequency offset estimation value of the current input signal.
  • the first-level intermediate frequency offset estimation value is obtained based on the adjacent two-level complex angle data; the next-level intermediate frequency offset estimation value is obtained based on the previous-level intermediate frequency offset estimation value and the next-stage complex angle data, Until the final estimate of the frequency offset of the current input signal is obtained.
  • the complex angle data of two adjacent levels can be truncated at a high level to obtain the angle truncated data; and the first-level intermediate frequency offset estimation value can be obtained based on the angle truncated data and the complex angle data.
  • the frequency offset estimate of the current input signal is determined by using the complex angle data through two adders.
  • the output bit width of the adder is the same as the adder bit width of its input, and the excess high-end bits (bits) are truncated.
  • the fixed-point bit width of the complex angle is expressed as (sign, bit_eff, bit_least), sign represents the number of symbols, bit_eff represents the effective bit width, and bit_least represents the weight of the lowest bit.
  • bit_eff the effective bit width
  • bit_least represents the weight of the lowest bit.
  • bit_efff the effective bit width
  • bit_least represents the weight of the lowest bit.
  • bit_least represents the weight of the lowest bit.
  • using the complex angle data to determine the frequency offset estimation value of the current input signal includes: straightforwardly cutting the adjacent n-1th level complex angle value F n-1 and the nth level complex angle value F n high to obtain The intercept angle value; add the intercept angle value and the n-1th level complex angle value F n-1 to obtain the n-1th level angle intermediate value M n-1 ; combine the n+1th level complex angle value with the nth -1 level angle intermediate value M n-1 is high straight to obtain a new intercept angle value; add the new intercept angle value and the n-1th level angle intermediate value M n-1 , and so on, until the current Estimated value of the frequency offset of the input signal.
  • the following takes three complex angle values F 1 , F 2 , and F 3 as examples to introduce.
  • the first complex angle value F 1 is (1, 12, 14)
  • the second complex angle value F 2 is (1, 12, 16)
  • the third complex angle value F 1 is (1, 12, 18).
  • the first-level intercept angle value (1,12,16) is obtained; the first-level intercept angle value (1,12,16) is added to F 1 to obtain the intermediate value of the angle M 1 , the fixed-point bit width of the intermediate value M 1 of the angle is (1,14,16); F 3 -M 1 is the second-level intercept angle value obtained after high-level interception (1,12,18); the second level after straightforward angle value (1,12,18) and adding the M 1, M 2 value to obtain an intermediate angle, the intermediate point M of the angle value is 2 bits wide (1,16,18).
  • M 2 is the final frequency offset estimation value. If there are other complex angle values, continue to calculate according to the frequency offset estimation procedure shown in FIG. 3.
  • FIG. 6 is a flowchart of another frequency offset estimation method provided by an embodiment of the disclosure. As shown in FIG. 6, the frequency offset estimation method includes the following steps 601 to 606.
  • Step 601 Preprocess the input signal according to the set threshold to obtain an effective input signal.
  • the set threshold is a threshold set according to the characteristics of the sample point, that is, set according to the degree of dispersion of the input signal.
  • the preprocessing performs circle processing on the input signal. Specifically, according to the characteristics of the sample points, the set threshold value of the circle dividing process is set, and the sample points suitable for the fourth power estimation are found. For example, for a 16QAM input signal, according to the distance between the sample points and the coordinate axis, the 4 samples in the inner circle and the 4 samples in the outermost circle in the constellation diagram are extracted, and the other samples are set to 0.
  • Step 602 Perform conjugate multiplication, amplitude multiplication, and phase subtraction on the current sample point and the sample point in the sample point group, and perform an M-th power operation to obtain an M-th power correlation value.
  • step 602 the current sample point and the sample points in the sample point group all come from the sample points after the dividing process.
  • Other processing methods are the same as those of step 301 in the foregoing embodiment, and will not be repeated here.
  • step 603 the correlation value is added once every N beats to the M power to obtain accumulated data.
  • Step 604 Filter the accumulated data to obtain filtered data.
  • Step 605 Obtain complex angle data corresponding to the set interval according to the filtered data and the set interval.
  • step 603 to step 605 is the same as that of step 302 to step 304 in the foregoing embodiment, and will not be repeated here.
  • Step 606 Determine the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval.
  • step 606 is the same as that of step 203, and will not be repeated here.
  • samples are extracted from the input signal according to a set interval to obtain multiple sample point groups, and the set interval of each sample point group is different;
  • the sample points in the sample point group are processed separately to obtain the complex angle data corresponding to the set interval;
  • the frequency offset estimation value of the current input signal is determined based on the complex angle data corresponding to the set interval.
  • the frequency offset estimation method uses sample points with different set intervals to participate in the calculation of the frequency offset estimation value at the same time.
  • the estimation range and accuracy of the frequency offset can be set in advance, and the calculation structure is all forward, and there is no need to be in the frequency offset estimation process. Switching the frequency offset estimation avoids the ambiguity of the frequency offset estimation caused by the loop, thereby realizing a large-scale, high-precision frequency offset estimation.
  • embodiments of the present disclosure provide a frequency offset estimation device, which can be applied to a coherent optical communication receiver to estimate the frequency of a laser in a coherent optical communication transmitter and the frequency of a laser in a coherent optical communication receiver. To compensate or correct the frequency of the coherent optical communication receiver.
  • FIG. 7 is a schematic diagram of a frequency offset estimation device provided by an embodiment of the disclosure. As shown in FIG. 7, the frequency offset estimation device includes a sampling module 701, an angle data obtaining module 702, and a frequency offset estimation module 703.
  • the sampling module 701 is configured to extract samples from the input signal according to a set interval to obtain a plurality of sample point groups, and the set interval of each sample point group is different.
  • sampling module 701 is the same as that of step 201 in the foregoing embodiment, and will not be repeated here.
  • the angle data obtaining module 702 is configured to separately process the current sample point and the sample points in each sample point group to obtain complex angle data corresponding to a set interval.
  • angle data obtaining module 702 is the same as that of step 202 in the foregoing embodiment, and will not be repeated here.
  • the frequency offset estimation module 703 is configured to determine the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval.
  • the frequency offset estimation module 703 estimates the frequency offset value step by step with respect to the complex angle data corresponding to the set interval, so as to obtain the frequency offset estimation value of the current input signal.
  • the angle data obtaining module 702 may include:
  • the fourth power calculation unit 801 is configured to perform conjugate multiplication, amplitude multiplication, and phase subtraction on the current sample point and the sample point in the sample point group, and perform M-th power operation to obtain the M-th power correlation value, M Is an integer greater than 2;
  • the summation unit 802 is configured to add once every N beats to the M-th power correlation value to obtain accumulated data, where N is an integer greater than 2;
  • the filtering unit 803 is configured to filter the accumulated data to obtain filtered data
  • the complex angle calculation unit 804 is configured to obtain the complex angle data corresponding to the set interval according to the filter data and the set interval.
  • the angle data obtaining module 702 may further include a preprocessing unit configured to preprocess the input signal according to a set threshold to obtain a valid input signal.
  • the angle data obtaining module 702 may include multiple fourth power calculation units, multiple summation units, multiple filtering units, and multiple complex numbers.
  • Angle calculation unit each sample point group corresponds to a fourth power calculation unit, a summation unit, a filter unit and a complex angle calculation unit.
  • the angle data obtaining module 702 may include a preprocessing unit 901, three fourth power calculation units 902, three summation units 903, three filtering units 904, and three complex angle calculation units.
  • the fourth power calculation unit 902, the summation unit 903, the filtering unit 904, and the complex angle calculation unit 905 obtain complex angle data corresponding to a set interval for the samples in each sample group, and then send the complex angle data to the frequency offset estimation Block 906 to calculate the frequency offset estimation value.
  • the frequency offset estimation method and device provided in the above embodiments do not require a training sequence, nor do they depend on the synchronization state of the system, and can also be applied in an asynchronous state.
  • the sampling module extracts samples from the input signal at a set interval to obtain multiple sample point groups, and the set interval of each sample point group is different; the angle data obtaining module pairs The current sample point and the sample points in each sample point group are processed separately to obtain the complex angle data corresponding to the set interval; the frequency offset estimation module determines the frequency offset estimation value of the current input signal based on the complex angle data corresponding to the set interval.
  • the frequency offset estimation device uses sample points with different set intervals to participate in the calculation of the frequency offset estimation value at the same time, and the estimation range and accuracy of the frequency offset can be pre-set, and the calculation structure is all forward, and there is no need to be in the frequency offset estimation process. Switching the frequency offset estimation avoids the ambiguity of the frequency offset estimation caused by the loop, thereby realizing a large-scale, high-precision frequency offset estimation.
  • an electronic device which includes:
  • the memory 1002 has one or more programs stored thereon, and the frequency offset estimation method of the one or more programs;
  • One or more I/O interfaces 1003 are connected between the processor 1001 and the memory 1002, and are configured to implement information interaction between the processor 1001 and the memory 1002.
  • the processor 1001 is a device with data processing capability, which includes but is not limited to a central processing unit (CPU), etc.;
  • the memory 1002 is a device with data storage capability, which includes but is not limited to a random access memory (RAM, more specifically such as SDRAM, DDR, etc.), read-only memory (ROM), electrically erasable programmable read-only memory (EEPROM), flash memory (FLASH); I/O interface (read-write interface) 1003 is connected to processor 1001
  • RAM random access memory
  • ROM read-only memory
  • EEPROM electrically erasable programmable read-only memory
  • FLASH flash memory
  • I/O interface (read-write interface) 1003 is connected to processor 1001
  • the information interaction between the processor 1001 and the memory 1002 can be realized between the memory 1002 and the memory 1002, which includes but is not limited to a data bus (Bus) and the like.
  • Buss data bus
  • the processor 1001, the memory 1002, and the I/O interface 1003 are connected to each other through a bus, and further connected to other components of the computing device.
  • embodiments of the present disclosure provide a computer-readable medium on which a computer program is stored, and when the computer program is executed by a processor, any one of the above-mentioned frequency offset estimation methods is implemented.
  • Such software may be distributed on a computer-readable medium
  • the computer-readable medium may include a computer storage medium (or a non-transitory medium) and a communication medium (or a transitory medium).
  • the term computer storage medium includes volatile and non-volatile memory implemented in any method or technology for storing information (such as computer-readable instructions, data structures, program modules, or other data).
  • Information such as computer-readable instructions, data structures, program modules, or other data.
  • Computer storage media include but are not limited to RAM, ROM, EEPROM, flash memory, CD-ROM, digital versatile disk (DVD), magnetic cassettes, magnetic tapes, disk storage, or any that can be used to store desired information and can be accessed by a computer Other media.
  • a communication medium usually contains computer readable instructions, data structures, program modules, or data in a modulated data signal such as a carrier wave or other transmission mechanism, and may include any information delivery medium.

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  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Physics & Mathematics (AREA)
  • Spectroscopy & Molecular Physics (AREA)
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  • Complex Calculations (AREA)

Abstract

一种频偏估计方法，包括：按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个样点组的设定间隔不同；对当前样点与每个样点组内的抽取样点分别进行处理，获得设定间隔对应的复数角度数据；利用设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。本申请还提供了一种频偏估计装置、一种电子设备及一种计算机可读介质。

Description

频偏估计方法及装置、电子设备、计算机可读介质
相关申请的交叉引用
本申请要求于2020年4月7日提交的中国专利申请NO.202010268523.X的优先权，该中国专利申请的内容通过引用的方式整体合并于此。
技术领域
本公开实施例涉及通信技术领域，特别涉及频偏估计方法及装置、电子设备、计算机可读介质。
背景技术
在光通信系统中，相干光发射机与相干光接收机中激光器的频率存在频偏，不能完全一致，需要对相干光接收机中的频偏进行估计，以对其进行控制或补偿。
公开内容
第一方面，本公开实施例提供一种频偏估计方法，其包括：
按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个所述样点组的设定间隔不同；
对当前样点与每个所述样点组内的样点分别进行处理，获得所述设定间隔对应的复数角度数据；以及
利用所述设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
第二方面，本公开实施例提供一种频偏估计装置，其包括：
抽样模块，配置为按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个所述样点组的设定间隔不同；
角度数据获得模块，配置为对当前样点与每个所述样点组内的样点 分别进行处理，获得所述设定间隔对应的复数角度数据；以及
频偏估计模块，配置为基于所述设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
第三方面，本公开实施例提供一种电子设备，其包括：
一个或多个处理器；
存储器，其上存储有一个或多个程序，所述一个或多个程序被所述一个或多个处理器执行时，使得所述一个或多个处理器执行上述的频偏估计方法；以及
一个或多个I/O接口，连接在所述处理器与所述存储器之间，配置为实现所述处理器与所述存储器的信息交互。
第四方面，本公开实施例提供一种计算机可读介质，其上存储有计算机程序，所述计算机程序被处理器执行时实现上述的频偏估计方法。
附图说明
附图用来提供对本公开实施例的进一步理解，并且构成说明书的一部分，与本公开的实施例一起用于解释本公开，并不构成对本公开的限制。通过参考附图对详细示例实施例进行描述，本公开的特征和优点对本领域技术人员将变得更加清楚，在附图中：
图1为一种相关法频偏估计装置；
图2为本公开实施例提供的一种频偏估计方法的流程图；
图3为本公开实施例提供的频偏估计方法中步骤202的具体流程图；
图4为本公开实施例提供的频偏估计方法中步骤203的具体流程图；
图5为本公开实施例提供的频偏估计方法中频偏计算的原理图；
图6为本公开实施例提供的另一种频偏估计方法的流程图；
图7为本公开实施例提供的一种频偏估计装置的原理图；
图8为本公开实施例提供的频偏估计装置中角度数据获得模块的原理图；
图9为本公开实施例提供的一种频偏估计装置的部分结构示意图；以及
图10为本公开实施例提供的一种电子设备的组成框图。
具体实施方式
为使本领域的技术人员更好地理解本公开的技术方案，下面结合附图对本公开提供的频偏估计方法及装置、电子设备、计算机可读介质进行详细描述。
在下文中将参考附图更充分地描述示例实施例，但是所述示例实施例可以以不同形式来体现且不应当被解释为限于本文阐述的实施例。提供的实施例仅用于使本领域技术人员充分理解本公开的范围。
在不冲突的情况下，本公开各实施例及实施例中的各特征可相互组合。
如本文所使用的术语“和/或”包括一个或多个相关列举条目的任何和所有组合。
本文所使用的术语仅用于描述特定实施例，且不意欲限制本公开。如本文所使用的单数形式“一个”和“该”意欲包括复数形式，即，表示至少一个，除非上下文另外清楚地限定。还将理解的是，当本说明书中使用术语“包括”和/或“由……制成”时，指定存在所列举特征、整体、步骤、操作、元件和/或组件，但不排除还存在或可添加一个或多个其它特征、整体、步骤、操作、元件、组件和/或其群组。
除非另外限定，否则本文所用的所有术语(包括技术术语和科学术语)的含义与本领域普通技术人员通常理解的含义相同。还将理解，诸如在常用字典中限定的那些术语应当被解释为具有与其在相关技术以及本公开的背景下的含义一致的含义，且将不解释为具有理想化或过度形式上的含义，除非本文明确如此限定。
400Gb/s PM-16QAM(偏振复用－四相相移键控)相干光通信接收机在均衡和偏振解复用后，获得两路信号，即X偏振信号和Y偏振信号。由于相干光通信发射机中激光器的频率与相干光通信接收机中激光器的频率不完全一致，均衡器输出的两路偏振信号存在频偏。需要对频偏进行估计来获得频偏估计信号，以补偿相干光通信接收机的频率，从而提高光通信系统的信号质量。
图1为一种相关法频偏估计装置。输入的复信号被分成两路，其中 一路复信号被输入寄存器101，另一路复信号被直接输入乘法器102。寄存器101对复信号进行延时、共轭处理后得到延迟的共轭信号，该共轭信号被输入乘法器102。乘法器102将复信号与共轭信号相乘，获得相乘结果信号，相乘结果信号被传输至四次方器103。四次方器103对相乘结果信号进行四次方运算，再将结果输出给求和器104。求和器104用于减小噪声对频偏估计的影响。最后，由取1/4辐角器105对求和器104的输出结果进行取1/4辐角操作，并输出频偏估计信号。
在实际应用中，寄存器101的延迟量D为大于或等于1的整数，当延迟量D等于1时，频偏估计范围大，但估计精度较低；当延迟量D增大时，频偏估计范围变小，而估计精度较提高。为了使频偏估计兼顾大范围和高精度，通常以延迟量D＝1开始，当频偏估计收敛到一定精度时，再增大延迟量D的值。这种单一调整方式常存在频偏估计还未达到要求精度时，延迟量D已经被切换到大的值，导致频偏估计模糊，可能输出错误的频偏估计结果。
第一方面，本公开实施例提供一种频偏估计方法，该频偏估计方法应用于相干光通信接收机，估计相干光通信发射机中激光器的频率与相干光通信接收机中激光器的频率的频偏，以对相干光通信接收机的频率进行补偿或修正。
本公开实施例的频偏估计方法可以对X偏振信号和Y偏振信号中的任意一路偏振信号进行频偏估计，然后将频偏估计结果应用于另一路偏振信号；或者，可以对X偏振信号和Y偏振信号同时进行频偏估计。为了方便描述，以下实施例是以对X偏振信号和Y偏振信号同时进行频偏估计为例进行介绍。
图2为本公开实施例提供的一种频偏估计方法的流程图。参照图2，所述频偏估计方法包括以下步骤201至203。
步骤201，按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个样点组的设定间隔不同。
本公开实施例中，输入信号可以为将数字基带电信号进行均衡滤波后的时域信号，且该均衡滤波后的信号是并行度为64的信号。
为了从输入信号抽取样点，可以对先对输入信号进行存储，存储的 输入信号的长度至少满足抽取样点的需求，即，须保证能够抽取要求数量的样点，例如，存储的输入信号的长度可以用样点数量表示，可以为要求抽取的样点数量加上各待抽取样点之间的设定间隔。设定间隔也被称为延时间隔，其可以根据需要任意设定。如设定间隔为4，则每间隔4个样点抽取一个样点。另外，抽取样点的数量也可以根据需要任意设定，如抽取20、50、80个样点。更具体地，当每间隔4个样点抽取一个样点、而且每个样点组包括5个样点时，则存储的输入信号的长度至少应该包含有21个样点。
在本实施例中，每个样点组的设定间隔不同，换言之，每个样点组采用不同的设定间隔抽取。例如，对于第一样点组，设定间隔可以为1，包括32个样点。对于第二样点组，设定间隔可以为4，包括32个样点。对于第三样点组，设定间隔可以为16，包括32个样点。
需要说明的是，本公开实施例的每个样点组的抽样对象相同，即不同的样点组是从相同采样周期内的输入信号中抽取。
步骤202，对当前样点与每个样点组内的样点分别进行处理，获得设定间隔对应的复数角度数据。
本公开实施例中，当前样点是当前输入信号中的任意一个样点，当前输入信号与用于抽取样点组的输入信号为相同采样周期内的输入信号。
在步骤202中，对当前样点与样点组内的样点分别进行处理，如四次方运算、求和、滤波和角度计算等处理，获得复数角度数据。
对当前样点与每个样点组内的样点进行处理，获得多个复数角度数据，即每个样点组对应一个复数角度数据。例如，当存在三个样点组时，可以获得三个复数角度数据。当然，存在较多数量的样点组时，也可以获得少于样点组数量的复数角度数据。
步骤203，基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
在步骤203中，利用复数角度数据确定当前输入信号的频偏估计值。
在一些实施方式中，频偏估计值可以通过针对设定间隔对应的复数角度数据逐级估计频偏值而确定，每一级的估计范围是上一级的1/4。
图3为本公开实施例提供的频偏估计方法中步骤202的具体流程图。 如图3所示，对当前样点与每个样点组内的样点均进行如下步骤301至304的处理。
步骤301，将当前样点与样点组内的样点进行共轭相乘、幅度相乘和相位相减，做M次方运算，获得M次方相关值。
在步骤301中，针对X偏振信号和Y偏振信号，将当前样点与样点组内的样点进行共轭相乘、幅度相乘和相位相减，并做M次方运算，获得M次方相关值，M为大于2的整数。
当前样点与三个样点组进行共轭相乘、幅度相乘和相位相减，并做四次方处理，获得四次方相关值R1、R2和R3。
例如，利用以下公式(1)计算四次方相关值R1、R2和R3。
Figure PCTCN2021085304-appb-000001
在公式(1)中，R 1表示设定间隔为1的四次方相关值，R 2表示设定间隔为4的四次方相关值，R 3表示设定间隔为16的四次方相关值，
Figure PCTCN2021085304-appb-000002
表示信号幅度，
Figure PCTCN2021085304-appb-000003
表示抽取样点的相位，t为抽取样点时间，e j4表示四次方处理，x表示X偏振信号，y表示Y偏振信号，
Figure PCTCN2021085304-appb-000004
表示当前样点和(t+1)时抽取的样点的X偏振信号的信号幅度相乘，
Figure PCTCN2021085304-appb-000005
表示当前样点和(t+1)时抽取的样点的X偏振信号的相位相减，以此类推。
需要说明的是，本实施例是以4次方处理为例进行说明，实际上，也可以进行其它次方处理，本公开不进行具体限定。
步骤302，每N拍M次方相关值进行一次相加，获得累加数据。
本公开实施例中，N为大于2的整数，N拍M次方相关值表示N个M次方相关值，即可对连续的N个M次方相关值进行累加。在本实施例中，N可以选择32，即每32个连续的M次方相关值可以进行一次累加。
例如，利用公式(2)对32个四次方相关值进行相加求和，获得累加数据。
Figure PCTCN2021085304-appb-000006
在公式(2)中，R sum,1表示设定间隔为1的样品组对应的累加数据，R 1[count]表示设定间隔为1的四次方相关值，R sum,2表示设定间隔为4的样品组对应的累加数据，R 2[count]表示设定间隔为4的四次方相关值，R sum,3表示设定间隔为16的样品组对应的累加数据，R 3[count]表示设定间隔为16的四次方相关值。
步骤303，对累加数据进行滤波，获得滤波数据。
在步骤303中，采用一阶IIR数字滤波器进行低通滤波，以对累加数据进行平滑处理。
例如：利用公式(3)计算滤波数据。
Figure PCTCN2021085304-appb-000007
在公式(3)中，α 1、α 2、α 3为配置的滤波系数，R avg,1表示设定间隔为1的样品组对应的滤波数据，R avg,2表示设定间隔为4的样品组对应的滤波数据，R avg,16表示设定间隔为16的样品组对应的滤波数据。
步骤304，根据滤波数据和设定间隔获得设定间隔对应的复数角度数据。
在步骤304中，根据滤波后的滤波数据和设定间隔计算复数角度。
例如，利用公式(4)计算复数角度。
Figure PCTCN2021085304-appb-000008
在公式(4)中，F 1、F 2、F 3表示复数角度数据，Arg()表示求复数角度，单位为圈(turns)，取值范围通常为[-0.5,0.5]turns，4、16和64是与设定间隔相关的数值。
在一些实施方式中，针对设定间隔对应的复数角度数据逐级估计频偏值，以获得当前输入信号的频偏估计值。在逐级估计频偏值时，每一级 的估计范围是上一级的1/4。
图4为本公开实施例提供的频偏估计方法中步骤203的具体流程图。如图4所示，基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值(即步骤203)包括以下步骤401和402。
步骤401，按照设定间隔对复数角度数据进行分级，且设定间隔越小，复数角度数据的等级越低。
例如，当设定间隔为1、4、16时，设定间隔为1的复数数据角度F 1为第一级，设定间隔为4的复数数据角度F 2为第二级，设定间隔为16的复数数据角度F 3分别为第三级。
步骤402，针对复数角度数据逐级估计频偏值，以获得当前输入信号的频偏估计值。
在一些实施方式中，基于相邻两级复数角度数据获得第一级中间频偏估计值；基于上一级中间频偏估计值和下一级复数角度数据获得下一级中间频偏估计值，直至获得最终的当前输入信号的频偏估计值。
具体地，可以将相邻两级复数角度数据进行高位直截，获得角度直截数据；基于角度直截数据和复数角度数据获得第一级中间频偏估计值。
如图5所示，利用复数角度数据通过两个加法器来确定当前输入信号的频偏估计值。本公开实施例中，加法器的输出位宽同其输入的加数位宽，多余的高端位(bit)被截去。假设复数角度定点化位宽表示为(sign，bit_eff，bit_least)，sign表示符号数，bit_eff表示有效位宽，bit_least表示最低位的权重。例如，在定点化位宽(1，12，18)中，“1”表示符号数，“12”表示有效位宽，“18”表示最低位为2 -18。
在一些实施方式中，利用复数角度数据确定当前输入信号的频偏估计值包括：将相邻的第n-1级复数角度值F n-1和第n级复数角度值F n高位直截，获得直截角度值；将直截角度值与第n-1级复数角度值F n-1相加，获得第n-1级角度中间值M n-1；将第n+1级复数角度值与第n-1级角度中间值M n-1高位直截，获得新的直截角度值；将新的直截角度值和第n-1级角度中间值M n-1相加，以此类推，直至最后获得当前输入信号的频偏估计值。
下面以三个复数角度值F 1、F 2、F 3为例进行介绍。例如，第一复数角 度值F 1为(1，12，14)、第二复数角度值F 2为(1，12，16)、第三复数角度值F 1为(1，12，18)。
将F 2-F 1高位直截后，获得的第一级直截角度值(1,12,16)；将第一级直截角度值(1,12,16)与F 1相加，获得角度中间值M 1，该角度中间值M 1的定点化位宽为(1，14，16)；F 3-M 1高位直截后获得的第二级直截角度值(1,12,18)；第二级直截角度值(1,12,18)与M 1相加后，获得角度中间值M 2，角度中间值M 2的定点化位宽为(1,16,18)。当没有其他复数角度值时，M 2即为最终的频偏估计值。若还有其他复数角度值，则按照图3所示的频偏估计流程继续计算。
图6为本公开实施例提供的另一种频偏估计方法的流程图。如图6所示，所述频偏估计方法包括以下步骤601至606。
步骤601，根据设定阈值对输入信号进行预处理，获得有效输入信号。
本公开实施例中，设定阈值是根据样点特性设定的阈值，即根据输入信号的离散程度设定。
在一些实施方式中，预处理对输入信号进行分圈处理。具体地，根据样点特性设置分圈处理的设定阈值，找出适合进行四次方估计的样点。例如，对16QAM输入信号，根据样点距离坐标轴的远近，把星座图中的内圈4个样点和最外圈4个样点抽取出来，其它样点设置为0。
步骤602，将当前样点与样点组内的样点进行共轭相乘、幅度相乘和相位相减，做M次方运算，获得M次方相关值。
在步骤602中，当前样点和样点组内的样点均是来自于分圈处理后的样点。其它处理方式与上述实施例中步骤301的相同，在此不再赘述。
步骤603，每N拍M次方相关值进行一次相加，获得累加数据。
步骤604，对累加数据进行滤波，获得滤波数据。
步骤605，根据滤波数据和设定间隔获得设定间隔对应的复数角度数据。
步骤603至步骤605的具体实施方式与上述实施例中步骤302至步骤304的相同，在此不再赘述。
步骤606，基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
步骤606的具体实施方式与步骤203的相同，在此不再赘述。
本公开实施例提供的频偏估计方法中，按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个样点组的设定间隔不同；对当前样点与每个样点组内的样点分别进行处理，获得设定间隔对应的复数角度数据；基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。该频偏估计方法利用不同设定间隔的样点组同时参与频偏估计值的计算，可预先设定频偏的估计范围和精度，而且计算结构全正向，不需要在频偏估计过程中切换频偏估计，避免了环路引起的频偏估计模糊，从而实现了大范围、高精度的频偏估计。
第二方面，本公开实施例提供一种频偏估计装置，该频偏估计装置可应用于相干光通信接收机，估计相干光通信发射机中激光器的频率与相干光通信接收机中激光器的频率的频偏，以对相干光通信接收机的频率进行补偿或修正。
图7为本公开实施例提供的一种频偏估计装置的原理图。如图7所示，所述频偏估计装置包括抽样模块701、角度数据获得模块702和频偏估计模块703。
抽样模块701配置为按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个样点组的设定间隔不同。
抽样模块701的具体实施方式与上述实施例中步骤201的相同，在此不再赘述。
角度数据获得模块702配置为对当前样点与每个样点组内的样点分别进行处理，以获得设定间隔对应的复数角度数据。
角度数据获得模块702的具体实施方式与上述实施例中步骤202的相同，在此不再赘述。
频偏估计模块703配置为基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
在一些实施方式中，频偏估计模块703针对设定间隔对应的复数角度数据逐级估计频偏值，以获得当前输入信号的频偏估计值。
频偏估计模块703的具体实施方式与上述实施例中步骤203的相同， 在此不再赘述。
如图8所示，角度数据获得模块702可包括：
四次方计算单元801，配置为将当前样点与样点组内的样点进行共轭相乘、幅度相乘和相位相减，并做M次方运算，获得M次方相关值，M为大于2的整数；
求和单元802，配置为对每N拍M次方相关值进行一次相加，获得累加数据，N为大于2的整数；
滤波单元803，配置为对累加数据进行滤波，获得滤波数据；
复数角度计算单元804，配置为根据滤波数据和设定间隔获得设定间隔对应的复数角度数据。
在一些实施方式中，角度数据获得模块702还可包括预处理单元，配置为根据设定阈值对输入信号进行预处理，以获得有效输入信号。
在一些实施方式中，如图9所示，在所述频偏估计装置中，角度数据获得模块702可包括多个四次方计算单元、多个求和单元、多个滤波单元和多个复数角度计算单元，每个样点组对应一个四次方计算单元、一个求和单元、一个滤波单元和一个复数角度计算单元。例如，当有三个样点组时，角度数据获得模块702可包括一个预处理单元901、三个四次方计算单元902、三个求和单元903、三个滤波单元904、三个复数角度计算单元905，、以及一个频偏估计模块906。四次方计算单元902、求和单元903、滤波单元904和复数角度计算单元905针对每个样品组内的样点获得对应设定间隔的复数角度数据，然后将复数角度数据发送至频偏估计模块906，以计算频偏估计值。
需要说明的是，上述实施例提供的频偏估计方法和装置不需要训练序列，也不依赖于系统的同步状态，异步状态下也可应用。
本公开实施例提供的频偏估计装置中，抽样模块按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个样点组的设定间隔不同；角度数据获得模块对当前样点与每个样点组内的样点分别进行处理，获得设定间隔对应的复数角度数据；频偏估计模块基于设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。该频偏估计装置利用不同设定间隔的样点组同时参与频偏估计值的计算，可预先设定频偏的估计范围和精 度，而且计算结构全正向，不需要在频偏估计过程中切换频偏估计，避免了环路引起的频偏估计模糊，从而实现了大范围、高精度的频偏估计。
第三方面，参照图10，本公开实施例提供一种电子设备，其包括：
一个或多个处理器1001；
存储器1002，其上存储有一个或多个程序，所述一个或多个程序被的频偏估计方法；
一个或多个I/O接口1003，连接在处理器1001与存储器1002之间，配置为实现处理器1001与存储器1002的信息交互。
本公开实施例中，处理器1001为具有数据处理能力的器件，其包括但不限于中央处理器(CPU)等；存储器1002为具有数据存储能力的器件，其包括但不限于随机存取存储器(RAM，更具体如SDRAM、DDR等)、只读存储器(ROM)、带电可擦可编程只读存储器(EEPROM)、闪存(FLASH)；I/O接口(读写接口)1003连接在处理器1001与存储器1002间，能实现处理器1001与存储器1002的信息交互，其包括但不限于数据总线(Bus)等。
在一些实施方式中，处理器1001、存储器1002和I/O接口1003通过总线相互连接，进而与计算设备的其它组件连接。
第四方面，本公开实施例提供一种计算机可读介质，其上存储有计算机程序，所述计算机程序被处理器执行时实现上述任意一种频偏估计方法。
本领域普通技术人员可以理解，上文中所公开方法中的全部或某些步骤、系统、装置中的功能模块/单元可以被实施为软件、固件、硬件及其适当的组合。在硬件实施方式中，在以上描述中提及的功能模块/单元之间的划分不一定对应于物理组件的划分；例如，一个物理组件可以具有多个功能，或者一个功能或步骤可以由若干物理组件合作执行。某些物理组件或所有物理组件可以被实施为由处理器(如中央处理器、数字信号处理器或微处理器)执行的软件，或者被实施为硬件，或者被实施为集成电路，如专用集成电路。这样的软件可以分布在计算机可读介质上，计算机 可读介质可以包括计算机存储介质(或非暂时性介质)和通信介质(或暂时性介质)。如本领域普通技术人员公知的，术语计算机存储介质包括在用于存储信息(诸如计算机可读指令、数据结构、程序模块或其它数据)的任何方法或技术中实施的易失性和非易失性、可移除和不可移除介质。计算机存储介质包括但不限于RAM、ROM、EEPROM、闪存、CD-ROM、数字多功能盘(DVD)、磁盒、磁带、磁盘存储、或者可以用于存储期望的信息并且可以被计算机访问的任何其它的介质。此外，本领域普通技术人员公知的是，通信介质通常包含计算机可读指令、数据结构、程序模块或者诸如载波或其它传输机制之类的调制数据信号中的数据，并且可包括任何信息递送介质。
本文已经公开了示例实施例，并且虽然采用了具体术语，但它们仅用于并仅应当被解释为一般说明性含义，并且不用于限制的目的。对本领域技术人员显而易见的是，除非另外明确指出，否则，与特定实施例相结合描述的特征、特性和/或元素可单独使用，或可与结合其它实施例描述的特征、特性和/或元素组合使用。因此，本领域技术人员将理解，在不脱离由所附的权利要求阐明的本公开的范围的情况下，可进行各种形式和细节上的改变。

Claims (10)

  1. 一种频偏估计方法，包括：
    按照设定间隔从输入信号中抽取样点，获得多个样点组，且每个所述样点组的所述设定间隔不同；
    对当前样点与每个所述样点组内的样点进行处理，获得所述设定间隔对应的复数角度数据；以及
    利用所述设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
  2. 根据权利要求1所述的方法，其中，对当前样点与所述样点组内的样点进行处理获得所述设定间隔对应的复数角度数据包括对所述当前样点与每个样点组内的样点均进行如下处理：
    将所述当前样点与所述样点组内的样点进行共轭相乘、幅度相乘和相位相减，并进行M次方运算，获得M次方相关值，其中，M为大于2的整数；
    每N拍所述M次方相关值进行一次相加，获得累加数据，其中，N为大于2的整数；
    对所述累加数据进行滤波，获得滤波数据；以及
    根据所述滤波数据和所述设定间隔获得所述设定间隔对应的复数角度数据。
  3. 根据权利要求2所述的方法，其中，所述M次方运算为四次方运算，所述M次方相关值为四次方相关值。
  4. 根据权利要求1所述的方法，其中，利用所述设定间隔对应的复数角度数据确定当前输入信号的频偏估计值包括：
    按照所述设定间隔对所述复数角度数据进行分级；以及
    对所述复数角度数据逐级估计频偏值，以获得当前输入信号的频偏估计值。
  5. 根据权利要求4所述的方法，其中，对所述复数角度数据逐级估计频偏值以获得当前输入信号的频偏估计值包括：
    基于相邻两级所述复数角度数据获得第一级中间频偏估计值；以及
    基于上一级所述中间频偏估计值和下一级所述复数角度数据获得下一级中间频偏估计值，直至获得最终的所述当前输入信号的频偏估计值。
  6. 根据权利要求5所述的方法，其中，基于相邻两级所述复数角度数据获得第一级中间频偏估计值包括：
    将相邻两级所述复数角度数据进行高位直截，获得角度直截数据；以及
    基于所述角度直截数据和所述复数角度数据获得所述第一级中间频偏估计值。
  7. 根据权利要求1至6中任意一项所述的方法，还包括：
    按照设定间隔从输入信号中抽取样点以获得多个样点组之前，根据设定阈值对所述输入信号进行预处理，获得有效输入信号，其中，所述设定阈值是根据所述输入信号的离散程度设定。
  8. 一种频偏估计装置，包括：
    抽样模块，配置为按照设定间隔从输入信号中抽取样点，获得多个样点组，而且每个所述样点组的设定间隔不同；
    角度数据获得模块，配置为对当前样点与每个所述样点组内的样点分别进行处理，获得所述设定间隔对应的复数角度数据；以及
    频偏估计模块，配置为基于所述设定间隔对应的复数角度数据确定当前输入信号的频偏估计值。
  9. 一种电子设备，包括：
    一个或多个处理器；
    存储装置，其上存储有一个或多个程序，所述一个或多个程序被所 述一个或多个处理器执行时，使得所述一个或多个处理器实现根据权利要求1至7中任意一项所述的方法；以及
    一个或多个I/O接口，连接在所述处理器与所述存储器之间，配置为实现所述处理器与所述存储器的信息交互。
  10. 一种计算机可读介质，其上存储有计算机程序，所述计算机程序被处理器执行时实现根据权利要求1至7中任意一项所述的方法。
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