WO2021184467A1 - 一种宽输出电压范围谐振变换器拓扑及其控制方法 - Google Patents

一种宽输出电压范围谐振变换器拓扑及其控制方法 Download PDF

Info

Publication number
WO2021184467A1
WO2021184467A1 PCT/CN2020/084667 CN2020084667W WO2021184467A1 WO 2021184467 A1 WO2021184467 A1 WO 2021184467A1 CN 2020084667 W CN2020084667 W CN 2020084667W WO 2021184467 A1 WO2021184467 A1 WO 2021184467A1
Authority
WO
WIPO (PCT)
Prior art keywords
resonant
output voltage
bridge arm
rectifier circuit
bridge
Prior art date
Application number
PCT/CN2020/084667
Other languages
English (en)
French (fr)
Inventor
杨得秋
张军明
徐德鸿
王泽峰
胡长生
梅营
金佑燮
Original Assignee
浙江大学
乐金电子研发中心(上海)有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 浙江大学, 乐金电子研发中心(上海)有限公司 filed Critical 浙江大学
Publication of WO2021184467A1 publication Critical patent/WO2021184467A1/zh

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to a topology and a control method of a power electronic converter, and more particularly to a resonant converter topology with a wide output voltage range and a control method for realizing a wide voltage output range through mode switching.
  • the purpose of the present invention is to overcome the shortcomings of the existing power electronic resonant converter topology, provide a resonant converter topology with a wide output voltage range and a control method for achieving a wide voltage output range through mode switching, and realize a wide adaptability
  • the resonant converter in the voltage output range improves the performance of the resonant converter in a wide output voltage range, reduces the difficulty of parameter design of the wide-range resonant converter, and improves the efficiency and power density.
  • a resonant converter topology with a wide output voltage range which includes an input voltage source;
  • the upper and lower switches of one bridge arm and their anti-parallel diodes are S1, S6, Ds1, and Ds6 respectively.
  • the upper and lower switches of the second bridge arm and their anti-parallel diodes are S2, S5, Ds2, Ds5, and the third bridge.
  • the upper and lower switches of the arm and their anti-parallel diodes are respectively S3, S4, Ds3, and Ds4; they also include a first resonant branch bridged between the midpoint of the first bridge arm and the midpoint of the second bridge arm.
  • the resonant branch is composed of the first resonant capacitor Cr1, the first resonant inductor Lr1 and the primary side of the first transformer T1 in series; the second resonant branch is connected between the midpoint of the second bridge arm and the midpoint of the third bridge arm,
  • the second resonant branch is composed of a second resonant capacitor Cr2, a second resonant inductor Lr2, and the primary side of the second transformer T2 in series; it also includes a first full-bridge rectifier circuit connected to the secondary side of the first resonant transformer T1.
  • the diodes used in the bridge rectifier circuit are D1, D2, D3, D4; the second full bridge rectifier circuit connected to the secondary side of the second resonant transformer T2, and the diodes used in the second full bridge rectifier circuit are D5, D6, D7, D8 respectively
  • the output capacitor Co connected to the positive terminal of the first full-bridge rectifier circuit and the negative terminal of the first full-bridge rectifier circuit, and the positive terminal of the first rectifier circuit is connected to the positive terminal of the second rectifier circuit, the first rectifier circuit The negative terminal is connected to the negative terminal of the second rectifier circuit.
  • the fully-controlled switch includes, but is not limited to: MOSFET, IGBT, and GTR; the anti-parallel diode may be an internal integrated diode of the fully-controlled switch.
  • the full-bridge rectifier circuit on the secondary side of the transformer includes but is not limited to: diode uncontrolled rectification and synchronous rectification; the rectifier circuit may be full-bridge rectification, voltage doubler rectification, and full-wave rectification.
  • the above-mentioned wide output voltage range resonant converter control method, and its work mode switching method obtain the required gain Greq based on the output voltage value and the input voltage value, and compare it with a set threshold, the set threshold has a first threshold And a second threshold, the first threshold is higher than the second threshold; when the required gain is higher than the first threshold, the circuit works in mode 1, specifically: the switch tubes S2 and S5 of the second bridge arm are turned off; If the required gain is lower than the second threshold, the circuit works in mode 2, specifically: the switch tubes S1, S6, S2, and S5 of the first bridge arm and the second bridge arm are switched according to a fixed duty cycle and frequency modulation method. At the same time, the switching tubes S3 and S4 of the third bridge arm are switched synchronously with the switching tubes S1 and S6 of the first bridge arm, respectively.
  • the comparison with the set threshold is realized by using a hysteresis comparator.
  • the present invention has the following beneficial effects:
  • the voltage gain range of the traditional resonant converter is doubled, and a wide voltage range output is realized.
  • the present invention improves the performance of the resonant converter under wide output voltage range working conditions, reduces the difficulty of designing the parameters of the resonant cavity, improves the efficiency, and improves the power density.
  • Figure 1 shows the wide output voltage range resonant converter topology.
  • Figure 2 is a control schematic diagram of a resonant converter with a wide output voltage range.
  • Figure 3 is a schematic diagram of the mode selection module.
  • each bridge arm contains two in series including anti-parallel
  • the full control diode switch is composed of: the upper and lower switches of the first bridge arm and their anti-parallel diodes are respectively S1, S6, Ds1, Ds6, and the upper and lower switches of the second bridge arm and their anti-parallel diodes are respectively S2, S5, Ds2, Ds5, the upper and lower switches of the third bridge arm and their anti-parallel diodes are respectively S3, S4, Ds3, and Ds4; in one embodiment, the switching tube adopts MOSFET, and the inside of the switching tube includes anti-parallel Of the diode.
  • the second rectifier circuit is a full-bridge rectifier circuit, and the diodes used are D5, D6, D7, and D8; connected to the first rectifier circuit
  • the positive terminal of and the output capacitor Co of the negative terminal of the first rectifier circuit, the positive terminal of the first rectifier circuit is connected with the positive terminal of the second rectifier circuit, and the negative terminal of the first rectifier circuit is connected with the negative terminal of the second rectifier circuit.
  • the first rectifier circuit and the second rectifier circuit can be other rectifier circuits known in the art, such as a voltage doubler rectifier circuit, a full-wave rectifier circuit, and the like.
  • the arrangement order of the resonant inductor Lr1, resonant capacitor Cr1, and the primary side of the resonant transformer T1 can be freely changed; the resonant inductor Lr2 of the second LLC resonant branch, the resonant capacitor Cr2
  • the arrangement order of the three components on the primary side of the resonant transformer T2 can be freely changed; Lr1 can be integrated in the resonant transformer T1, and Lr2 can be integrated in the resonant transformer T2.
  • the gain required by the circuit is obtained.
  • the calculation of the gain is common knowledge in the field.
  • the set output voltage is converted to the primary side of the transformer and divided by the input voltage to get The desired circuit gain Greq.
  • Greq is less than (or not greater than) Gset
  • the circuit works in the first mode, that is, the switching tubes S2 and S5 of the second bridge arm are turned off. Not working, it is equivalent to two resonant branches connected in series, and then form a full bridge circuit with S1, S6, S3 and S4.
  • the switch tubes S1, S6, S3, S4 of the first bridge arm and the third bridge arm are switched according to a fixed duty cycle and frequency modulation method. At this time, half of the input voltage is applied to each resonant branch. .
  • Greq is not less than (or greater than) Gset
  • the circuit works in the second mode. In this mode, all three bridge arms work.
  • the switching tubes S1, S6, S2, and S5 of the first bridge arm and the second bridge arm are switched according to a fixed duty cycle and frequency modulation method, while the switching tubes S3 and S4 of the third bridge arm are The switching tubes S1 and S6 of the first bridge arm are switched synchronously, which is equivalent to the parallel connection of two full-bridge circuits.
  • the input voltage is directly applied to each resonant branch, and the gain can be doubled.
  • the above-mentioned comparator with gain size uses a comparator with a return difference (Schmidt comparator), and Gset can be changed to two thresholds Gh, Gl, usually Gh is slightly Greater than Gset, Gl is slightly smaller than Gset.
  • a control method of a wide output voltage range resonant converter is implemented based on the following modules: sampling module, mode selection module, feedback control module, variable frequency PWM drive module; specifically, the set output voltage value and sampling module are selected
  • sampling module the mode selection module
  • feedback control module variable frequency PWM drive module
  • the required gain Greq is obtained by calculation, which is compared with the upper limit Gh and the lower limit Gl of the hysteresis comparison of the hysteresis comparator in the mode selection module.
  • the circuit works in mode 1, specifically: the switching tubes S2 and S5 of the second bridge arm are turned off, and the switching tubes S1 of the first bridge arm and the third bridge arm are turned off.
  • S6, S3, and S4 are switched on and off according to the fixed duty cycle and frequency modulation method; if the output of the hysteresis comparator is 1, it is judged that the required output voltage gain is larger, and the circuit works in mode 2, specifically:
  • the switch tubes S1, S6, S2, S5 of the first bridge arm and the second bridge arm switch according to the fixed duty ratio and frequency modulation method, while the switch tubes S3 and S4 of the third bridge arm are respectively the same as those of the first bridge arm.
  • the mode selection module divides the peak value, or average value, or effective value of the input voltage collected by the sampling module, or a pre-set fixed value and the set output voltage (required output voltage) to obtain Demand gain Greq, input hysteresis comparator, get working mode.
  • the sampling module includes an input voltage sampling sub-module, an output voltage sampling sub-module, and an input current sampling sub-module; in addition to the output voltage sampling sub-module, the other sub-modules input signals to feedback control according to the control needs of the feedback control module Module is not required.
  • the sampling module samples two signals, voltage and current.
  • the specific methods for sampling voltage include but are not limited to: resistance voltage dividing method and voltage sensor; the specific methods for sampling current include but are not limited to: Hall sensor and resistance sampling method.
  • the variable frequency PWM driving module can be a digital circuit or an analog circuit, and the specific working mode is: converting the input frequency and duty cycle information into a corresponding PWM signal, and driving the full control switch through the driving circuit.

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

本发明公开一种宽输出电压范围谐振变换器拓扑及其调制方法，其拓扑包括了输入滤波电容、六个开关管构成的三个开关桥臂、两组谐振支路、两组全桥整流电路、以及输出滤波电容，其控制方法包括谐振变换器的变频控制和应对不同输出电压工况的模式切换控制，具体的方式是在需求输出电压增益较小的工况下，将中间桥臂的开关管全部关断，两侧桥臂采取变频的谐振变换器控制方法，而在需求输出电压增益较大的工况下，三个桥臂同时采用变频的谐振变换器控制方法，通过模式切换的控制提高谐振变换器的电压增益范围。

Description

一种宽输出电压范围谐振变换器拓扑及其控制方法 技术领域
本发明涉及电力电子变换器的拓扑以及控制方法，更具体地涉及一种宽输出电压范围的谐振变换器拓扑以及一种通过模式切换实现宽电压输出范围的控制方法。
背景技术
常规的LLC谐振变换器和串联谐振变换器的拓扑已被公开，但常规LLC变换器和串联谐振变换器的只适合用于输出电压增益范围较窄的情况，在输出电压增益范围较宽的工作场合，例如LED调光电路、电动汽车充电机等，此类谐振变换的工作点会偏离额定工作点较远，从而导致变换器的参数难以优化，出现功率密度下降、效率下降、成本上升等问题。
发明内容
本发明目的在于克服现有电力电子谐振变换器拓扑中的缺点，提供一种宽输出电压范围的谐振变换器拓扑以及一种通过模式切换实现宽电压输出范围的控制方法，实现了一种适应宽电压输出范围的谐振变换器，提升了谐振变换器在宽输出电压范围内的性能，降低了宽范围谐振变换器参数设计的难度，提升了效率和功率密度。
本发明内容的一个方面，提供了一种宽输出电压范围的谐振变换器拓扑，包括输入电压源；三组由两个串联的包含反并二极管的全控型开关构成的桥臂，其中：第一桥臂的上、下开关及其反并二极管分别为S1、S6、Ds1、Ds6,第二桥臂的上、下开关及其反并二极管分别为S2、S5、Ds2、Ds5，第三桥臂的上、下开关及其反并二极管分别为S3、S4、Ds3、Ds4；还包括跨接在第一桥臂中点与第二桥臂中点之间的第一谐振支路，第一谐振支路由第一谐振电容Cr1、第一谐振电感Lr1和第一变压器T1的一次侧串联组成；跨接在第二桥臂中点与第三桥臂中点之间的第二谐振支路，第二谐振支路由第二谐振电容Cr2、第二谐振电感Lr2和第二变压器T2的一次侧串联组成；还包括连接在第一谐振变压器T1二次侧的第一全桥整流电路,第一全桥整流电路所用二极管分别为D1,D2,D3,D4；连接在第二谐振变压器T2二次侧的第二全桥整流电路,第二全桥整流电路所用二 极管分别为D5,D6,D7,D8；以及连接在第一全桥整流电路的正端和第一全桥整流电路的负端的输出电容Co，且第一整流电路的正端和第二整流电路的正端连接，第一整流电路的负端和第二整流电路的负端连接。
上述技术方案中，进一步的，所述的全控型开关包括且不仅限于：MOSFET、IGBT、GTR；所述反并二极管可以是全控型开关的内部集成二极管。变压器二次侧全桥整流电路包括且不仅限于：二极管不控整流，同步整流；所述整流电路，可以是全桥整流，倍压整流，全波整流。
上述宽输出电压范围谐振变换器的控制方法，其工作模式切换方法：基于输出电压值和输入电压值得到所需增益Greq,与所设定阈值进行比较，所述的设定阈值具有第一阈值和第二阈值，所述第一阈值高于所述第二阈值；当所需增益高于第一阈值，电路工作于模式一，具体是：第二桥臂的开关管S2、S5关断；若所需增益低于第二阈值，电路工作于模式二，具体是：第一桥臂和第二桥臂的开关管S1、S6、S2、S5按照固定占空比，频率调制的方法开关，同时第三桥臂的开关管S3、S4分别和第一桥臂的开关管S1、S6同步开关。
所述的与所设定阈值进行比较采用滞回比较器实现。
与现有技术相比，本发明具有如下的有益效果：
根据本发明所述的谐振变换器拓扑和控制方法，使得传统谐振变换器的电压增益范围翻倍，实现了宽电压范围的输出。
同时，本发明提高了谐振变换器在宽输出电压范围工况下的性能，降低了谐振腔参数的设计难度，提高了效率，提高了功率密度。
附图说明
图1为宽输出电压范围谐振变换器拓扑。
图2为宽输出电压范围谐振变换器的控制示意图。
图3为模式选择模块的示意图。
具体实施方式
下面结合附图对本发明进行详细说明。
参考图1为一种具体的宽输出电压范围谐振变换器拓扑，包括一个直流输入电源，三个开关桥臂，分别跨接在直流输入电源两端，每个桥臂两个串联的包含反并二极管的全控型开关构成，其中：第一桥臂的上、下开关及其反并二极管 分别为S1、S6、Ds1、Ds6,第二桥臂的上、下开关及其反并二极管分别为S2、S5、Ds2、Ds5，第三桥臂的上、下开关及其反并二极管分别为S3、S4、Ds3、Ds4；在一个实施例中，开关管采用MOSFET，开关管内部包括了反并联的二极管。跨接在第一桥臂中点与第二桥臂中点之间的第一谐振支路，第一谐振支路由第一谐振电容Cr1、第一谐振电感Lr1和第一谐振变压器T1的一次侧串联组成；跨接在第二桥臂中点与第三桥臂中点之间的第二谐振支路，第二谐振支路由第二谐振电容Cr2、第二谐振电感Lr2和第二谐振变压器T2的一次侧串联组成；连接在第一谐振变压器T1二次侧的第一整流电路,在一个实施例中，第一整流电路为全桥整流电路，所用二极管分别为D1,D2,D3,D4；连接在第二谐振变压器T2二次侧的第二整流电路,在一个实施例中，第二整流电路为全桥整流电路，所用二极管分别为D5,D6,D7,D8；连接在第一整流电路的正端和第一整流电路的负端的输出电容Co，且第一整流电路的正端和第二整流电路的正端连接，第一整流电路的负端和第二整流电路的负端连接。本领域技术人员可知，在不改变本发明本质的前提下，第一整流电路和第二整流电路可以是本领域所公知的其他整流电路，如倍压整流电路，全波整流电路等。
上述拓扑中，所述第一谐振支路的谐振电感Lr1、谐振电容Cr1、谐振变压器T1的一次侧三个元件的排列顺序可以自由变化；第二LLC谐振支路的谐振电感Lr2、谐振电容Cr2、谐振变压器T2的一次侧三个元件的排列顺序可以自由变化；Lr1可以集成在谐振变压器T1中，Lr2可以集成在谐振变压器T2中。
基于输入电压和设定的输出电压(或者所需的输出电压)得到电路所需的增益，增益的计算为本领域常识，将设定的输出电压折算到变压器的一次侧，除以输入电压得到所需的电路增益Greq。当电路所需的增益，与一个设定的增益阈值Gset比较，当Greq小于(或者不大于)Gset时，电路工作在第一模态，即第二桥臂的开关管S2、S5关断，不工作，相当于两个谐振支路串联后，然后与S1、S6、S3和S4构成了全桥电路。在一个实施例中，第一桥臂和第三桥臂的开关管S1、S6、S3、S4按照固定占空比，频率调制的方法开关，此时输入电压的一半施加在每个谐振支路上。当Greq不小于(或者大于)Gset时，电路工作在第二模态，这个模态下，三个桥臂均工作。在一个实施方式中，第一桥臂和第二桥臂的开关管S1、S6、S2、S5按照固定占空比，频率调制的方法开关，同时第 三桥臂的开关管S3、S4分别和第一桥臂的开关管S1、S6同步开关，相当于两个全桥电路的并联，相对前述两个谐振支路串联模式，输入电压直接施加在每个谐振支路上，增益可以提升一倍。
在实际应用中，为了避免扰动带来的模式频繁切换，上述增益大小的比较器采用带回差的比较器(施密特比较器),Gset可以变化成两个阈值Gh,Gl，通常Gh略大于Gset，Gl略小于Gset。参考图2，一种宽输出电压范围谐振变换器的控制方法基于以下模块实现：采样模块、模式选择模块、反馈控制模块、变频PWM驱动模块；具体是将设定的输出电压值和采样模块采得的输入电压值传输给模式选择模块，经过计算得到所需增益Greq,与模式选择模块中的滞回比较器的滞回比较上限Gh和滞回比较下限Gl比较，若滞回比较器的输出为0，则判断所需的输出电压增益较小，电路工作在模态1，具体是：第二桥臂的开关管S2、S5关断，第一桥臂和第三桥臂的开关管S1、S6、S3、S4按照固定占空比，频率调制的方法开关；若滞回比较器的输出为1，则判断所需的输出电压增益较大，电路工作在模态2，具体是：第一桥臂和第二桥臂的开关管S1、S6、S2、S5按照固定占空比，频率调制的方法开关，同时第三桥臂的开关管S3、S4分别和第一桥臂的开关管S1、S6同步开关。
参考图3，模式选择模块将采样模块采得的输入电压的峰值、或者平均值、或有效值、或事先设定好的固定值与设定的输出电压(需要的输出电压)做除法，得到需求增益Greq，输入滞回比较器，得到工作模式。
参考表1为滞回比较器真值表，根据需求增益Greq和滞回比较上限Gh、滞回比较下限Gl的关系、当前输出状态；滞回比较器得出下次输出的值，输出给反馈控制模块，确定工作模式。
Greq＞Gl？ Greq＞Gh？ 当前输出值 下次输出值 下次工作模式
0 0 0 0 工作模式1
1 0 0 0 工作模式1
1 1 0 1 工作模式2
0 0 1 0 工作模式1
1 0 1 1 工作模式2
1 1 1 1 工作模式2
表1滞回比较器真值表
所述的采样模块包括输入电压采样子模块、输出电压采样子模块、输入电流采样子模块；除输出电压采样子模块外，其他各个子模块根据所述反馈控制模块的控制需要将信号输入反馈控制模块，并非必需。采样模块采样电压、电流两种信号，其采样电压的具体方式包括且不仅限于：电阻分压法、电压传感器；其采样电流的具体方式包括且不仅限于：霍尔传感器，电阻采样法。
所述的变频PWM驱动模块可以为数字电路或模拟电路，具体的工作方式是：将输入的频率和占空比信息转化为对应的的PWM信号，并通过驱动电路驱动全控开关。

Claims (6)

  1. 一种宽输出电压范围谐振变换器拓扑，其特征在于：所述宽输出电压范围谐振变换器拓扑包括输入电压源；三组由两个串联的包含反并二极管的全控型开关构成的桥臂，其中：第一桥臂的上、下开关及其反并二极管分别为S1、S6、Ds1、Ds6,第二桥臂的上、下开关及其反并二极管分别为S2、S5、Ds2、Ds5，第三桥臂的上、下开关及其反并二极管分别为S3、S4、Ds3、Ds4；还包括跨接在第一桥臂中点与第二桥臂中点之间的第一谐振支路，第一谐振支路由第一谐振电容Cr1、第一谐振电感Lr1和第一变压器T1的一次侧串联组成；跨接在第二桥臂中点与第三桥臂中点之间的第二谐振支路，第二谐振支路由第二谐振电容Cr2、第二谐振电感Lr2和第二变压器T2的一次侧串联组成；还包括连接在第一谐振变压器T1二次侧的第一全桥整流电路,第一全桥整流电路所用二极管分别为D1,D2,D3,D4；连接在第二谐振变压器T2二次侧的第二全桥整流电路,第二全桥整流电路所用二极管分别为D5,D6,D7,D8；以及连接在第一全桥整流电路的正端和第一全桥整流电路的负端的输出电容Co，且第一整流电路的正端和第二整流电路的正端连接，第一整流电路的负端和第二整流电路的负端连接。
  2. 根据权利要求1所述的宽输出电压范围谐振变换器拓扑，其特征在于：全控型开关包括且不仅限于：MOSFET、IGBT、GTR；所述反并二极管可以是全控型开关的内部集成二极管。
  3. 根据权利要求1所述的宽输出电压范围谐振变换器拓扑，其特征在于：变压器二次侧整流电路包括且不仅限于：二极管不控整流，同步整流；整流电路可以是全桥整流、倍压整流或全波整流。
  4. 根据权利要求1所述的宽输出电压范围谐振变换器拓扑，其特征在于：第一谐振电感Lr1可以集成在第一谐振变压器T1中，第二谐振电感Lr2可以集成在第二谐振变压器T2中。
  5. 一种宽输出电压范围谐振变换器的控制方法，其特征在于：针对如权利要求1-4任一项所述的宽输出电压范围谐振变换器，其工作模式切换方法：基于输出电压值和输入电压值得到所需增益Greq,与所设定阈值进行比较，所述设定阈值具有第一阈值和第二阈值，所述第一阈值高于所述第二阈值；当所需增益高于第一阈值，电路工作于模式一，具体是：第二桥臂的开关管S2、S5关断；若 所需增益低于第二阈值，电路工作于模式二，具体是：第一桥臂和第二桥臂的开关管S1、S6、S2、S5按照固定占空比，频率调制的方法开关，同时第三桥臂的开关管S3、S4分别和第一桥臂的开关管S1、S6同步开关。
  6. 根据权利要求5所述的控制方法，所述的与所设定阈值进行比较采用滞回比较器实现。
PCT/CN2020/084667 2020-03-16 2020-04-14 一种宽输出电压范围谐振变换器拓扑及其控制方法 WO2021184467A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN202010182238.6 2020-03-16
CN202010182238.6A CN111262447B (zh) 2020-03-16 2020-03-16 一种宽输出电压范围谐振变换器拓扑及其控制方法

Publications (1)

Publication Number Publication Date
WO2021184467A1 true WO2021184467A1 (zh) 2021-09-23

Family

ID=70953392

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2020/084667 WO2021184467A1 (zh) 2020-03-16 2020-04-14 一种宽输出电压范围谐振变换器拓扑及其控制方法

Country Status (2)

Country Link
CN (1) CN111262447B (zh)
WO (1) WO2021184467A1 (zh)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113037095B (zh) * 2021-04-07 2022-06-14 湖北工业大学 具有超宽输出范围的混合dps双全桥llc谐振变换器
CN113098289B (zh) * 2021-04-30 2024-04-19 漳州科华技术有限责任公司 高压直流输电装置、充电桩、谐振变换器及其控制方法
CN115360924B (zh) * 2022-09-23 2024-04-16 湖南华阵电子科技有限公司 一种开关复用型变换器拓扑结构及其调制方法
CN115864859B (zh) * 2023-03-02 2023-05-09 南京杰芯源科技有限公司 一种新型pwm控制软开关半桥dc-dc变换器

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101572488A (zh) * 2009-06-09 2009-11-04 华中科技大学 复用桥臂的双输出直流-直流变换器
US7742318B2 (en) * 2008-06-10 2010-06-22 Virginia Tech Intellectual Properties, Inc. Multi-element resonant converters
CN102324852A (zh) * 2011-08-30 2012-01-18 深圳麦格米特电气股份有限公司 一种多相错相并联双级变换器

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7742318B2 (en) * 2008-06-10 2010-06-22 Virginia Tech Intellectual Properties, Inc. Multi-element resonant converters
CN101572488A (zh) * 2009-06-09 2009-11-04 华中科技大学 复用桥臂的双输出直流-直流变换器
CN102324852A (zh) * 2011-08-30 2012-01-18 深圳麦格米特电气股份有限公司 一种多相错相并联双级变换器

Also Published As

Publication number Publication date
CN111262447A (zh) 2020-06-09
CN111262447B (zh) 2021-06-08

Similar Documents

Publication Publication Date Title
WO2021184467A1 (zh) 一种宽输出电压范围谐振变换器拓扑及其控制方法
CN105576983B (zh) 一种谐振直流/直流变换器
CN109067219B (zh) 一种三相交直流变换器及其控制方法
US20140111016A1 (en) Staggered parallel three-level dc/dc converter and ac/dc converter
TWI539737B (zh) 五電平變換裝置
CN102522896B (zh) 并联连接的谐振转换器电路及其控制方法
CN112865560B (zh) 一种多二极管串联型的背对背无桥三电平整流器
CN106059294B (zh) 一种开关电源及变换方法
TWI539736B (zh) 五電平變換裝置
US10159125B1 (en) LED power supply device
CN113394990A (zh) 一种三相升降压整流变换器及其控制方法
Coccia et al. Wide input voltage range compensation in DC/DC resonant architectures for on-board traction power supplies
CN113507226B (zh) 一种三相整流变换器及其控制方法
CN208299694U (zh) 一种多路输入并联且多路输出并联的功率变换器
CN109672340A (zh) 一种多路输入并联且多路输出并联的功率变换器
Lai et al. Design and implementation of a single-stage LLC resonant converter with high power factor
CN108683343B (zh) 伪连续导电模式Buck-Boost无桥PFC变换器
WO2022179564A1 (zh) 无桥降压功率因素校正电路
CN113193768B (zh) 四开关管串联型的背靠背式三电平整流器
US11817795B2 (en) Switching power supply circuit
WO2022110685A1 (zh) 中点箝位逆变器及光伏供电系统
CN212435587U (zh) 恒流输出控制电路、开关电源控制器及开关电源系统
US20210218347A1 (en) TT Control Zero-Voltage-Switching Power Inversion Circuits
CN205249076U (zh) 一种全桥型z源逆变器和光伏并网电路
Brinker et al. Comparison of Modulation Techniques for a Single-Phase Full-Bridge Photovoltaic Micro-Inverter Considering Reactive Power Capability

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 20925197

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 20925197

Country of ref document: EP

Kind code of ref document: A1