WO2021039362A1 - Dispositif d'antenne et dispositif à réseau en sandwich - Google Patents

Dispositif d'antenne et dispositif à réseau en sandwich Download PDF

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Publication number
WO2021039362A1
WO2021039362A1 PCT/JP2020/030389 JP2020030389W WO2021039362A1 WO 2021039362 A1 WO2021039362 A1 WO 2021039362A1 JP 2020030389 W JP2020030389 W JP 2020030389W WO 2021039362 A1 WO2021039362 A1 WO 2021039362A1
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WIPO (PCT)
Prior art keywords
antenna
directivity
signal
array
incoming wave
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PCT/JP2020/030389
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English (en)
Japanese (ja)
Inventor
和博 本田
小川　晃一
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国立大学法人富山大学
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Priority to JP2021542702A priority Critical patent/JPWO2021039362A1/ja
Publication of WO2021039362A1 publication Critical patent/WO2021039362A1/fr

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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S3/00—Direction-finders for determining the direction from which infrasonic, sonic, ultrasonic, or electromagnetic waves, or particle emission, not having a directional significance, are being received
    • G01S3/02—Direction-finders for determining the direction from which infrasonic, sonic, ultrasonic, or electromagnetic waves, or particle emission, not having a directional significance, are being received using radio waves
    • G01S3/14—Systems for determining direction or deviation from predetermined direction
    • G01S3/46—Systems for determining direction or deviation from predetermined direction using antennas spaced apart and measuring phase or time difference between signals therefrom, i.e. path-difference systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/20—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a curvilinear path
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/44—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the electric or magnetic characteristics of reflecting, refracting, or diffracting devices associated with the radiating element
    • H01Q3/46—Active lenses or reflecting arrays

Definitions

  • the present invention relates to an antenna device and a sandwich array device.
  • flying cars As a vehicle that can be used for commuting to work or school avoiding traffic congestion in the city, new means of transportation in remote islands or mountainous areas, emergency transportation in the event of a disaster, or quick transportation of goods. Is expected. In the practical application of flying cars, much interest has been focused on the realization of communication between flying cars (between flying cars).
  • Patent Document 1 discloses a receiving antenna device capable of detecting the direction of arrival of a received radio wave in a horizontal plane. According to this, by using a circular array phased array antenna consisting of antenna elements arranged at equal intervals on a circle and antenna elements arranged in the center, it can be configured to be compact and lightweight, and the direction of arrival of received radio waves can be determined. An antenna device that can detect with high accuracy can be realized.
  • Patent Document 1 has a problem that the arrival wave direction in the horizontal direction can be estimated, but the arrival wave direction in the elevation angle direction cannot be estimated.
  • a flying car can freely change its flight direction in the horizontal and vertical directions, and unlike a conventional car, the target for communication is not limited to the horizontal plane, so that the radiation characteristics over all solid angles. An antenna with is required.
  • the present invention has been made in view of the above circumstances, and an object of the present invention is to provide an antenna device and a sandwich array device capable of high-speed communication by estimating the incoming wave direction not only in the horizontal direction but also in the elevation angle direction.
  • the antenna device includes N first antenna elements (N is a natural number of 3 or more) arranged at equal intervals on a circle and a substantially center of the circle.
  • the first antenna element and the second antenna element are provided with a circular array phased array antenna composed of one second antenna element arranged in the antenna and a circular main plate having a variable radius by switching control. Consists of a monopole antenna mounted on the main plate.
  • the first antenna element and the second antenna element are composed of a 1/4 wavelength monopole antenna.
  • the N first antenna elements are orthogonal to the incoming wave direction according to the direction of the incoming wave that is parallel to the main plate of the incoming wave that arrives at the circular array phased array antenna.
  • a sub-array control unit may be provided which is divided into N / 2 sub-arrays and independently forms the N / 2 beams directed in the direction of the incoming wave by controlling the directivity of the sub-array.
  • the directivity can be controlled with respect to the estimated arrival wave direction.
  • the optimum received signal can always be obtained, and high-speed communication can be realized.
  • each of the N / 2 sub-arrays is composed of a combination of two antenna elements whose arrangement directions are parallel, and the combination may be changed according to the arrival wave direction.
  • a directivity control unit for controlling the directivity of the circularly arranged phased array antenna is provided in a predetermined angle range including the elevation angle direction by giving to the two first antenna elements closest to the communication direction of the above.
  • the directivity is a directivity that reduces the radiation gain by realizing the anti-phase excitation in the elevation angle direction
  • the sigma directivity is a directivity that increases the radiation gain by realizing the in-phase excitation in the elevation angle direction. It may be.
  • the directivity can be formed in the angle range in the predetermined direction, so that it is possible to communicate only with the target.
  • the first signal and the second signal obtained by multiplying the received signals of the first antenna elements by two weights according to the arrangement of the first antenna elements and summing them, and the received signals of the second antenna element.
  • the direction of the incoming wave which is the direction in which the incoming wave arriving at the circular array phased array antenna is formed with the main plate.
  • a calculation unit for estimating is provided, and the calculation unit calculates the phase angle of the voltage of the third signal by averaging the phase angle of the voltage of the first signal and the phase angle of the voltage of the second signal. Then, the phase difference between the first signal and the third signal may be calculated, and the phase difference may be substantially proportional to the direction of the incoming wave.
  • the sandwich array device includes a first antenna device and a second antenna device which are two antenna devices of any of the above embodiments, and the first antenna.
  • the device is arranged at the zenith of the flying vehicle, the second antenna device is arranged at the top of the flying vehicle, and the circular arrangement phased seen from the main plate in the first antenna device and the second antenna device.
  • the direction in which the array antenna is erected is opposite.
  • the antenna device or the like of the present invention it is possible to estimate the arrival wave direction not only in the horizontal direction but also in the elevation angle direction and perform high-speed communication.
  • FIG. 1 is a diagram showing an example of an outline configuration of an antenna device according to an embodiment.
  • FIG. 2 is a diagram showing a specific configuration example of the circular array phased array antenna shown in FIG.
  • FIG. 3A is a diagram showing an example of the configuration of the main plate having a variable size in the embodiment.
  • FIG. 3B is a diagram showing a specific configuration used for switching the size of the main plate shown in FIG. 3A.
  • FIG. 4 is a diagram showing a specific configuration example of a sub array when radio waves arrive from the + X axis direction of the circular array phased array antenna according to the embodiment.
  • FIG. 5A is a diagram showing an example of an outline configuration of the sandwich array device according to the embodiment.
  • FIG. 5A is a diagram showing an example of an outline configuration of the sandwich array device according to the embodiment.
  • FIG. 5B is a diagram showing a use case of the sandwich array device shown in FIG. 5A.
  • FIG. 6 is a diagram showing a concept in a case where communication between flying vehicles is performed using the sandwich array device according to the embodiment.
  • FIG. 7A is a diagram showing the positional relationship of the first antenna element excited to form the monopulse directivity in the XY plane.
  • FIG. 7B is a diagram showing the path difference in the elevation angle direction used for designing the delta directivity and the sigma directivity.
  • FIG. 7C is a diagram showing an angle used to obtain the electrical length of the excited first antenna element shown in FIG. 7A.
  • FIG. 8 is a diagram showing the relationship between the phase and the elevation angle of the first antenna elements # 1 and # 8 required to form the sigma directivity and the delta directivity.
  • FIG. 9A is a diagram showing an example of sigma directivity and delta directivity forming monopulse directivity that realizes the space division monopulse method.
  • FIG. 9B is a diagram illustrating the concept of two pulses transmitted to form monopulse directivity.
  • FIG. 10A is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10B is a diagram showing an example of the analysis results of the sigma directivity and the delta directivity of the circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10C is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10D is a diagram showing an example of the analysis results of the sigma directivity and the delta directivity of the circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10B is a diagram showing an example of the analysis results of the sigma directivity and the delta directivity of the circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10C is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10E is a diagram showing an example of the analysis results of the sigma directivity and the delta directivity of the circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 10F is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in the directional scan in the elevation angle direction in the embodiment.
  • FIG. 11A is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11B is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan in the embodiment.
  • FIG. 11C is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11D is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11E is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11F is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan in the embodiment.
  • FIG. 11D is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11E is a diagram showing an example of analysis results of
  • FIG. 11G is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan according to an embodiment.
  • FIG. 11H is a diagram showing an example of analysis results of sigma directivity and delta directivity of a circular array phased array antenna formed in a horizontal directional scan in an embodiment.
  • FIG. 12 is a diagram showing the voltage of the signal induced by the circular array phased array antenna in the comparative example.
  • FIG. 13A is a diagram showing directivity characteristics of the first signal and the third signal in the XY plane in the comparative example.
  • FIG. 13B is a diagram showing the phase characteristics of the first signal and the third signal in the XY plane in the comparative example.
  • FIG. 14 is a diagram showing two weighting functions of the first antenna element of the circular array phased array antenna according to the embodiment.
  • FIG. 15A shows the elevation directivity of the first signal obtained by performing electromagnetic field analysis using the moment method.
  • FIG. 15B shows the elevation directivity of the third signal obtained by performing electromagnetic field analysis using the moment method.
  • FIG. 16 is a schematic diagram for explaining the principle of the phase inversion weighting method.
  • FIG. 17 is a diagram showing three-dimensional directivity of the first signal and the third signal in the embodiment.
  • FIG. 18A shows the directivity when the elevation angle direction is 30 degrees and the angle characteristics in the estimated arrival wave direction.
  • FIG. 18B shows the directivity when the elevation angle direction is 80 degrees and the angle characteristics in the estimated arrival wave direction.
  • FIG. 18A shows the directivity when the elevation angle direction is 30 degrees and the angle characteristics in the estimated arrival wave direction.
  • FIG. 18B shows the directivity when the elevation angle direction is 80 degrees and the angle characteristics in the estimated arrival wave direction.
  • FIG. 19 is a diagram showing a change in the transmission capacity with respect to the elevation angle direction of the incoming wave when the radius of the main plate in the embodiment is changed.
  • FIG. 20A is a diagram showing the three-dimensional radiation directivity of the dipole array antenna in the comparative example.
  • FIG. 20B is a diagram showing the three-dimensional radiation directivity of the monopole array antenna in the embodiment.
  • FIG. 21A is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 21B is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 21C is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 20A is a diagram showing three-dimensional radiation directivity of the dipole array antenna in the comparative example.
  • FIG. 20B is a diagram showing the three-dimensional radiation directivity of the monopole array
  • FIG. 21D is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22A is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22B is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22C is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22D is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22A is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22B is a diagram showing three-dimensional directivity when the sandwich array device according to the embodiment is subjected to directivity scanning.
  • FIG. 22C is a diagram showing three-dimensional directivity when the
  • FIG. 23 is a diagram showing the elevation characteristic of the transmission capacity of the MIMO array antenna using the half-wavelength dipole array antenna in the comparative example.
  • FIG. 24A is a diagram showing the azimuth characteristics of the transmission capacity of the MIMO array antenna using the sandwich array device according to the embodiment.
  • FIG. 24B is a diagram showing the elevation characteristic of the transmission capacity of the MIMO array antenna using the sandwich array device according to the embodiment.
  • FIG. 25 is a diagram showing a three-dimensional transmission capacity over the entire solid angle of the MIMO array antenna using the half-wavelength dipole array antenna in the comparative example.
  • FIG. 26 is a diagram showing a three-dimensional transmission capacity over the entire solid angle of a MIMO array antenna using the sandwich array device according to the embodiment.
  • FIG. 27 is a diagram showing the communication cutoff probability over the entire solid angle of the MIMO array antenna using the sandwich array device in the embodiment.
  • FIG. 28 is a diagram showing an example of a multi-element MIMO array antenna in a modified example.
  • FIG. 29A is a diagram showing an example of a 4 ⁇ 4 MIMO array antenna in the modified example.
  • FIG. 29B is a diagram showing an example of an 8 ⁇ 8 MIMO array antenna in the modified example.
  • FIG. 29C is a diagram showing an example of a 16 ⁇ 16 MIMO array antenna in a modified example.
  • FIG. 29D is a diagram showing an example of a 32 ⁇ 32 MIMO array antenna in the modified example.
  • FIG. 29A is a diagram showing an example of a 4 ⁇ 4 MIMO array antenna in the modified example.
  • FIG. 29B is a diagram showing an example of an 8 ⁇ 8 MIMO array antenna in the modified example.
  • FIG. 29C is a diagram showing an example of a 16 ⁇
  • 29E is a diagram showing an example of a 64 ⁇ 64 MIMO array antenna in the modified example.
  • FIG. 29F is a diagram showing an example of a 128 ⁇ 128 MIMO array antenna in a modified example.
  • FIG. 29G is a diagram showing an example of a 256 ⁇ 256 MIMO array antenna in the modified example.
  • FIG. 1 is a diagram showing an example of an outline configuration of the antenna device 10 according to the present embodiment.
  • the antenna device 10 in the present embodiment includes a circular array phased array antenna 1, a main plate 2, a control unit 3, and a calculation unit 4.
  • the antenna device 10 in the present embodiment is mounted on, for example, a flying vehicle (also referred to as a flying vehicle).
  • the circular array phased array antenna 1 has nine antenna elements.
  • ⁇ shown in FIG. 1 represents the elevation angle.
  • FIG. 2 is a diagram showing a specific configuration example of the circular array phased array antenna 1 shown in FIG. ⁇ shown in FIG. 2 is a direction formed with the X axis in the horizontal plane (XY plane), and represents the direction of the incoming wave (arriving wave direction) in the XY plane.
  • the circular array phased array antenna 1 has N first antenna elements (N is a natural number of 3 or more) arranged at equal intervals on a circle and substantially at the center of the circle. It consists of one arranged second antenna element.
  • the first antenna element and the second antenna element are monopole antennas mounted on the main plate 2 and are configured on the main plate 2.
  • the first antenna element and the second antenna element a 1/4-wavelength monopole antenna, and it is configured on the base plate 2 of radius r g.
  • the circular array phased array antenna 1 not only has the directivity of the plane (in the horizontal plane) including the region of the circle substantially in all directions, but also points in the zenith direction (+ Z-axis direction in FIG. 1). Has characteristics.
  • N 8
  • the circular array phased array antenna 1 includes eight first antenna elements
  • the circular arrangement phased antenna 1 includes eight antenna elements (first antenna elements: # 1 to # 8) arranged at intervals of 45 degrees on the circumference of radius a and a circle. It is composed of an antenna element (second antenna element: # 9) which is one non-feeding element arranged in the center of the above.
  • the radius a is, for example, 4.9 cm.
  • These nine antenna elements is 1/4-wavelength monopole antenna, and is configured on the base plate 2 of radius r g.
  • the phase is also in the elevation angle direction.
  • the direction of the incoming wave of the received signal having an angle can be estimated. The details of the estimation method will be described later, but the phase angle of the voltage of the signal induced in the second antenna element (# 9) by the incoming received radio wave is synthesized by the phase inversion weighting method described later.
  • the circular array phased array antenna 1 in the circular array phased array antenna 1, four sets of eight antenna elements (first antenna elements: # 1 to # 8) are orthogonal to the incoming wave direction according to the incoming wave direction by the control unit 3. Divided control (phased difference feeding) is performed on a sub array composed of paired elements. As a result, the circular array phased array antenna 1 can be operated as a directional scanning array antenna such as a MIMO (Multiple Input Multiple Output) array antenna.
  • MIMO Multiple Input Multiple Output
  • the radiation directivity of the circular array phased array antenna 1 in the elevation angle direction is optimized by switching the size of the radius of the main plate 2. That is, when the circular array phased array antenna 1 is operated as a MIMO array antenna, the size of the radius of the main plate 2 is different from that in the case of estimating the direction of the incoming wave.
  • the directivity in the elevation angle direction is controlled within a predetermined angle range including the elevation angle direction by being controlled by the control unit 3 using the space division monopulse method described later.
  • the main plate 2 is a circular main plate radius r g is variable by switching control.
  • the main plate 2 is a planar (plate-shaped) conductor, for example, as shown in FIG.
  • the size of the radius r g of the base plate 2 is variable, optimal ground plane and the case of performing the operation of estimating the direction of arrival using a circular array phased array antenna 1, in the case of operating as a MIMO array antenna This is because the sizes of 2 are different.
  • FIG. 3A is a diagram showing an example of the configuration of the main plate 2 having a variable size in the present embodiment.
  • FIG. 3B is a diagram showing a specific configuration used for switching the size of the main plate 2 shown in FIG. 3A.
  • Radius r g of the base plate 2, the control unit 3, are switching-controlled.
  • the radius r g of the base plate 2 is changed, for example, 7cm or 10 cm.
  • the size of the main plate 2 is controlled by connecting the diode 301 and the choke coil 302 to the main plate 2 and applying a bias voltage V d of 5 V or 0 V to the diode 301. You may.
  • the bias voltage V d of 5V is given, the diode 301 is turned on, the radius r g of the base plate 2 and the current flows to the outside of the base plate 2a is changed to 10 cm. Further, for example, 0V bias voltage V d is applied, the diode 301 is turned off, no current flows to the outside of the base plate 2a, since only the inside of the base plate 2b is effective, the radius r g of the base plate 2 is 7cm Is changed to.
  • the radius r g of the base plate 2 is not limited to being a switching control to any of 7cm and 10 cm, may be employed to the switching control to be configured to an appropriate size depending on the system to be realized.
  • the control unit 3 has a sub-array control function for dividing and controlling the circular array phased array antenna 1 into sub-arrays. More specifically, the control unit 3 shifts the N first antenna elements in the direction of the incoming wave according to the direction of the incoming wave, which is the direction parallel to the main plate 2 of the incoming wave arriving at the circular array phased array antenna 1. Divide into N / 2 sub-arrays so that they are orthogonal to each other. Then, the control unit 3 independently forms N / 2 beams directed in the direction of the incoming wave by controlling the directivity of the sub-array in this way.
  • each of the N / 2 sub-arrays is composed of a combination of two antenna elements whose arrangement directions are parallel, and the combination is changed according to the direction of the incoming wave.
  • the control unit 3 selects a pattern of a combination of two antenna elements that is parallel to the direction of the incoming wave within a predetermined angle range from the combinations of N / 2 patterns, so that the combination can be set in the direction of the incoming wave. Change accordingly.
  • FIG. 4 is a diagram showing a specific configuration example of a sub array when a radio wave arrives from the + X axis direction of the circular array phased array antenna 1 in the present embodiment.
  • the control unit 3 since the control unit 3 has eight first antenna elements constituting the circular array phased array antenna 1, one of the four pattern combinations is selected according to the direction of the incoming wave.
  • the first antenna elements # 2 and # 3, the first antenna elements # 1 and # 4, the first antenna elements # 5 and # 8, and the first antenna elements # 6 and # 7 Is shown as a sub-array (sub-arrays 1 to 4), respectively.
  • the control unit 3 divides the eight first antenna elements of the circularly arranged phased array antenna 1 into four so as to form a combination of sub-arrays arranged perpendicular to the direction of the incoming wave, so that four received signals are received. Has a low correlation. Further, in the circular array phased array antenna 1, eight first antenna elements are arranged in a circle at intervals of 45 degrees, so that the control unit 3 switches the power supply of the sub array according to the direction of the incoming wave by switching. , Sub-array combinations can be rotated every 45 degrees.
  • control unit 3 has an all-solid angle directivity control function that controls the directivity of the circular array phased array antenna 1 within a predetermined angle range including the elevation angle direction by using the space division monopulse method. More specifically, the control unit 3 includes an elevation angle direction by giving the phase given to form the delta directivity and the sigma directivity to the two first antenna elements closest to the desired communication direction. The directivity of the circular array phased array antenna 1 is controlled within a predetermined angle range.
  • the delta directivity is the directivity that reduces the radiation gain by realizing the anti-phase excitation in the elevation angle direction
  • the sigma directivity is the directivity that increases the radiation gain by realizing the in-phase excitation in the elevation angle direction. It is sex.
  • the delta directivity and the sigma directivity are calculated using the path difference in the elevation angle direction, which is the direction formed by the ground plate 2 of the incoming wave arriving at the circular array phased array antenna 1.
  • the space division monopulse method is a method for realizing the SLS function (Side Lobe Suppression), that is, the side lobe suppression function, based on sigma directivity and delta directivity. Details will be described later.
  • control unit 3 has a switching control function for controlling the radius size of the main plate 2.
  • the control unit 3 may control the radius size of the main plate 2 by controlling the bias voltage V d applied to the diode 301 to 0 V or 5 V.
  • the calculation unit 4 has an incoming wave direction estimation function for estimating the incoming wave direction, which is the direction of the incoming wave coming to the circular array phased array antenna 1. More specifically, the calculation unit 4 has the first signal and the second signal obtained by multiplying the received signals of the first antenna elements by two weights according to the arrangement of the first antenna elements, and the second antenna. Statistical analysis is performed with the third signal, which is the received signal of the element, and the phase difference between the first signal and the third signal is calculated. Here, the phase difference is substantially proportional to the direction of the incoming wave.
  • the calculation unit 4 estimates the incoming wave direction having an angle in the elevation angle direction of the incoming wave arriving at the circular array phased array antenna 1 by calculating the phase difference between the first signal and the third signal. ..
  • the calculation unit 4 calculates the phase angle of the voltage of the third signal by averaging the phase angle of the voltage of the first signal and the phase angle of the voltage of the second signal. The phase difference between the 1st signal and the 3rd signal is calculated.
  • the calculation for obtaining the average value is performed as the statistical analysis, but the calculation is not limited to the calculation for obtaining the average value, and may be combined with the calculation performed for adapting to the multiple wave environment.
  • each of the eight first antenna elements has two weights according to the arrangement of the first antenna elements, as shown in FIG. Therefore, the calculation unit 4 acquires the first signal obtained by multiplying the weight (counterclockwise weight) of each of the eight first antenna elements by each of the received signals of the eight first antenna elements. Further, the calculation unit 4 acquires a second signal obtained by multiplying the other weight (clockwise weight) of each of the eight first antenna elements by each of the received signals of the eight first antenna elements. Further, the calculation unit 4 acquires a third signal from the second antenna element.
  • the calculation unit 4 can estimate the arrival wave direction of the received signal having an angle in the elevation angle direction by obtaining the difference between the phase of the voltage of the first signal and the phase of the voltage of the third signal.
  • the phase of the voltage of the third signal is calculated by applying the phase inversion weighting method and synthesizing, that is, averaging the phase of the voltage of the first signal and the phase of the voltage of the second signal.
  • the antenna device 10 of the present embodiment is composed of a plurality of first antenna elements arranged at equal intervals on a circle and one second antenna element arranged substantially at the center of the circle.
  • a circular array phased array antenna 1 is configured on the main plate 2.
  • the first antenna element and the second antenna element are monopole antennas mounted on the main plate 2.
  • the antenna device 10 of the present embodiment can estimate the incoming wave direction not only in the horizontal direction but also in the elevation angle direction.
  • the antenna device 10 of the present embodiment can control the directivity with respect to the estimated arrival wave direction. As a result, the optimum received signal can always be obtained, so that high-speed communication can be realized.
  • the directivity can be controlled in an angle range in a predetermined direction including the elevation angle direction, it is possible to communicate only with the target communication partner.
  • the second antenna element which is one non-feeding element formed at the center of the circle of the circular array phased array antenna 1, contributes to the gain improvement by utilizing electromagnetic coupling.
  • the radiation directivity of the antenna device 10 of the present embodiment in the elevation angle direction is optimized by switching and controlling the size of the main plate 2.
  • the antenna device 10 of the present embodiment has directivity not only in the horizontal direction but also in the zenith direction (+ Z-axis direction in FIG. 1), but in the downward direction of the main plate 2 (-Z direction in FIG. 1). It has no directivity. Therefore, by arranging the antenna devices 10 vertically in a sandwich shape, it is possible to give directivity to all solid angles.
  • the sandwich array device 100 in which the antenna devices 10 are arranged vertically in a sandwich shape will be described.
  • FIG. 5A is a diagram showing an example of an outline configuration of the sandwich array device 100 according to the present embodiment.
  • the sandwich array device 100 includes two antenna devices 10 described above, and is arranged vertically (in the Z-axis direction in FIG. 5A) in a sandwich shape. More specifically, the sandwich array device 100 includes two antenna devices 10, a first antenna device 10A and a second antenna device 10B.
  • the erection direction of the circularly arranged phased array antenna 1A seen from the main plate 2A of the first antenna device 10A is opposite to the erection direction of the circularly arranged phased array antenna 1B seen from the main plate 2B of the second antenna device 10B. .
  • the sandwich array device 100 can have radiation characteristics over all solid angles.
  • FIG. 5B is a diagram showing a use case of the sandwich array device 100 shown in FIG. 5A.
  • the sandwich array device 100 is mounted on the flying vehicle 300 as a use case. More specifically, the first antenna device 10A is arranged at the zenith of the flying vehicle 300, and the second antenna device 10B is arranged at the zenith of the flying vehicle 300.
  • the erection direction of the circular array phased array antenna 1A seen from the main plate 2A of the first antenna device 10A is opposite to the erection direction of the circular array phased array antenna 1B seen from the main plate 2B of the second antenna device 10B. Is.
  • the flying vehicle 300 is also called a flying vehicle, and can freely change the flight direction in the horizontal direction and the vertical direction (vertical direction).
  • MIMO communication between the flying vehicles needs to be achieved in any direction. That is, the flying vehicle 300 requires an antenna having radiation characteristics over all solid angles. Therefore, the flying vehicle 300 can perform communication between the flying vehicles by mounting the sandwich array device 100 on the flying vehicle 300.
  • the flying vehicle 300 communication between the upper and lower parts can be realized by switching the antenna devices 10A and 10B of the sandwich array device 100 according to the direction of the arrival wave of the received signal. Further, the radiation directivity of the antenna devices 10A and 10B in the elevation angle direction can be controlled by changing the sizes of the main plate 2 and the main plate 2B.
  • the flying vehicle 300 may use only the upper antenna device 10A. Further, when the communication partner is fixed to the nadir side, the flying vehicle 300 may use only the lower antenna device 10B.
  • the arrival wave direction of the received signal can be estimated over all solid angles, and the directivity can be directed to the estimated arrival wave direction. Therefore, highly reliable communication can be realized between flying vehicles.
  • the antenna device 10 constituting the sandwich array device 100 can estimate the arrival wave direction by a simple method by processing in the RF unit. More specifically, as shown in FIG. 5A, eight first antenna elements constituting the circularly arranged phased array antennas 1A and 1B are arranged in a circle at intervals of 45 degrees. Therefore, the flying vehicle 300 rotates the combination of sub-arrays every 45 degrees by switching the power supply for dividing and controlling the eight first antenna elements into sub-arrays according to the direction of the incoming wave. Can be done.
  • the combination of sub-arrays arranged perpendicular to the direction of the incoming wave can be appropriately selected, so that the transmission capacity can be increased. It can be improved.
  • the flying vehicle 300 can direct the beam in the direction of the arrival wave of the estimated received signal by using the sandwich array device 100, it can be networked with other flying vehicles to prevent collision with other flying vehicles. It is possible to exchange high-quality video content.
  • the flying vehicle 300 uses the sandwich array device 100 to form directivity while sequentially shifting the angle range in a predetermined direction (while dividing the space), thereby dividing the directivity over the entire solid angle. Can be formed. As a result, the flying vehicle 300 can eliminate the synchronous interference and communicate only with the target flying vehicle even if there are a plurality of other flying vehicles capable of communicating in the space.
  • FIG. 6 is a diagram showing a concept in the case of performing communication between flying vehicles using the sandwich array device 100 in the present embodiment.
  • FIG. 6 shows four flying vehicles 300 whose flight directions can be freely changed, and are referred to as flying vehicles 300a, 300b, 300c, and 300d, respectively.
  • Each of the flying vehicles 300a to 300d is equipped with a sandwich array device 100 composed of antenna devices 10A and 10B.
  • each sandwich array device 100 in order to communicate between a plurality of flying vehicles 300 (between flying vehicles), each sandwich array device 100 needs to have radiation characteristics over all solid angles. However, if there is synchronous interference, communication cannot be performed correctly, and there is a risk that a plurality of flying vehicles 300 will collide with each other. In other words, for example, in order for the flying vehicle 300a to communicate with the flying vehicles 300b, 300c and 300d, it is necessary to realize communication with the flying vehicles 300b to 300d in any direction. On the other hand, when the flying vehicle 300a communicates with the flying vehicles 300b, 300c and 300d at the same time (synchronously), the flying vehicles 300b, 300c and 300d cannot be distinguished, and in the worst case, there is a risk of collision. Therefore, a collision prevention function is required.
  • This collision prevention function is applied to the sandwich array device 100, that is, the antenna device 10, by using the space division monopulse method to sequentially shift the angle range in a predetermined direction (while dividing the space) and to provide directivity to the angle range in the predetermined direction. It is realized by controlling.
  • FIG. 7A is a diagram showing the positional relationship of the first antenna element excited to form the monopulse directivity in the XY plane.
  • FIG. 7B is a diagram showing the path difference in the elevation angle direction used for designing the delta directivity and the sigma directivity.
  • FIG. 7C is a diagram showing an angle used to obtain the electrical length of the excited first antenna element shown in FIG. 7A.
  • first antenna elements for example, four first antenna elements (# 1, # 2, # 7, # 8) out of the eight first antenna elements shown in FIG. 7A are excited, and the other elements are excited.
  • the first antenna element (# 3, # 4, # 5, # 6) is terminated with 50 ⁇ .
  • the electrical length between the first antenna element # 1 and the first antenna element # 2, or the first antenna element # 7 and the first antenna element # 8 The electrical length between and is obtained by (Equation 1).
  • the sigma directivity can be expressed by the following (Equation 2)
  • the delta directivity can be expressed by the following (Equation 3).
  • the sigma directivity is the directivity that increases the radiation gain by realizing in-phase excitation in the elevation angle direction
  • the delta directivity is the directivity that increases the radiation gain by realizing the anti-phase excitation in the elevation angle direction. It is a directivity to make it smaller.
  • FIG. 8 is a diagram showing the relationship between the phase and the elevation angle of the first antenna elements # 1 and # 8 required to form the sigma directivity and the delta directivity.
  • the phases of the first antenna elements # 2 and # 7 are set to 0.
  • the frequency used for analysis is 2 GHz
  • the radius a of the circular array phased array antenna 1 of the present embodiment as a 4.9 cm has a 7cm radius r g of the main plate 2.
  • the elevation angle is 0 degrees in the horizontal plane (XY plane in FIG. 2), +90 degrees in the zenith direction (+ Z-axis direction in FIG. 1), and -Z-axis direction in the nadir direction (-Z-axis direction in FIG. 1). An angle defined at -90 degrees.
  • the azimuth direction is an angle defined in FIG. 2 or 7B as 0 degrees in the + X-axis direction and 90 degrees in the + Y-axis direction, and is represented by ⁇ in FIG.
  • FIG. 9A is a diagram showing an example of sigma directivity and delta directivity forming monopulse directivity that realizes the space division monopulse method.
  • FIG. 9B is a diagram showing the concept of two pulses P 1 and P 2 transmitted to form monopulse directivity.
  • the space division monopulse method is a method for realizing the sidelobe suppression function by sigma directivity and delta directivity.
  • the interrogator transmits two pulses P 1 and P 2 as shown in FIG. 9B to the surrounding target aircraft.
  • the pulses P 1 and P 2 are transmitted with the same power, the pulse P 1 is transmitted by sigma directivity, and the pulse P 2 is transmitted by delta directivity.
  • the target machine responds by giving an ID code or the like only when the pulse P 2 is 9 dB smaller than the pulse P 1. That is, in TCAS II, only the transponder of the target machine existing in this predetermined angle range responds. As a result, the interrogator can communicate only with the target aircraft existing in the predetermined angle range shown in FIG. 9A, so that synchronous interference can be eliminated. Further, in TCAS II, by selectively performing spatial division and communicating, it is possible to carry out a sequence of question answering over the entire space.
  • the predetermined angle range ⁇ is around 70 degrees at all elevation angles. This means that it is possible to capture a target in a certain angle range in the azimuth direction regardless of the elevation angle (elevation angle). Further, this value of around 70 degrees is suitable because the superposition of adjacent directivity occurs appropriately when the directional scan in the azimuth direction is performed.
  • FIGS. 11A to 11H are diagrams showing an example of the analysis results of the sigma directivity and the delta directivity of the circular array phased array antenna 1 formed in the horizontal directivity scanning in the present embodiment.
  • FIG. 11C 90 degrees
  • the sandwich array device 100 can use sigma directivity and delta directivity to form monopulse directivity, which is directivity in an angle range in a predetermined direction, and perform three-dimensional scanning.
  • the flying vehicle 300 equipped with the sandwich array device 100 can eliminate the synchronous interference and selectively communicate with other flying vehicles, so that collision prevention with other flying vehicles can be realized.
  • phase inversion weighting method for obtaining the phase of the voltage of the signal induced in the second antenna element (# 9) by the received radio wave having an angle in the elevation angle direction by synthesis will be described.
  • the circular array phased array antenna 1 will be described as having eight first antenna elements.
  • FIG. 12 is a diagram showing the voltage of the signal induced by the circular array phased array antenna 1 in the comparative example.
  • FIG. 12 shows the voltage of the signal induced in the circular array phased array antenna 1 in the comparative example by the received radio wave in the arrival wave direction having no angle in the elevation angle direction.
  • the direction of the incoming wave can be estimated by using the phase difference between the voltages of the antenna elements arranged on the center and the circle. More specifically, by obtaining the difference between the phase when the received signals of the eight first antenna elements are added together and the phase of the received signals of the one second antenna element arranged at the center, the difference is obtained. The direction of the incoming wave of the received signal can be estimated.
  • the received radio wave arrives only from the direction forming ⁇ with the X axis of the XY plane which is the plane of the circular array phased array antenna 1.
  • the signal induced in the i-th first antenna element by the received radio wave that is, the voltage Ei ( ⁇ ) can be calculated from the following (Equation 4).
  • the weighting function that reflects this is weighted by the voltage Ei calculated from (Equation 4), and all the first antenna elements on the circle are weighted. 1 Add the signals of the antenna elements.
  • the voltage E ⁇ ( ⁇ ) of the first signal which is the total of the received signals of each of the eight first antenna elements, can be obtained.
  • the voltage E ⁇ ( ⁇ ) of this first signal can be calculated from (Equation 5).
  • Equation 5 the element shown in (Equation 5) is 8, but if the number of the first antenna elements becomes infinite in order to understand the property of the voltage E ⁇ ( ⁇ ) of the first signal, the voltage E ⁇ ( ⁇ ) can be expressed by the following (Equation 6) using the Bessel function.
  • the voltage of the signal (third signal) induced in the second antenna element (# 9) by the received radio wave arriving from the direction forming ⁇ with the X axis is defined as E ⁇ ( ⁇ ).
  • the phase angle of the voltage E ⁇ ( ⁇ ) of the third signal is ⁇ E ⁇ and the phase angle of the voltage E ⁇ ( ⁇ ) of the first signal is ⁇ E ⁇
  • the phase difference ⁇ m is as follows (Equation). It can be calculated using 7).
  • the phase difference ⁇ m between the first signal and the third signal is a value substantially proportional to the incoming wave angle ⁇ of the received radio wave having no angle in the elevation angle direction.
  • FIG. 13A is a diagram showing the directivity characteristics of the first signal and the third signal in the XY plane in the comparative example.
  • FIG. 13B is a diagram showing the phase characteristics of the first signal and the third signal in the XY plane in the comparative example.
  • 13A and 13B show the analysis results of electromagnetic field analysis using the moment method, assuming that the received radio wave arrives only from the comparative example, that is, the direction forming ⁇ with the X axis.
  • the frequency used for the analysis is 2 GHz, and the radius a of the circular array phased array antenna 1 is 4.9 cm.
  • the directivity of the first signal and the directivity of the third signal that is, the directivity when the reception signals of the first antenna element are added together and the directivity of the reception signal of the second antenna element are It can be seen that it is omnidirectional in the XY plane. From FIG. 13B, it can be seen that the directivity phase characteristic of the first signal changes according to the azimuth angle. From this, it can be seen that the difference between the directional phase characteristic of the first signal and the directional phase characteristic of the third signal is proportional to the direction of the incoming wave.
  • FIG. 14 is a diagram showing two weighting functions of the first antenna element of the circular array phased array antenna 1 according to the present embodiment.
  • two weight functions a counterclockwise weight function (weight) and a clockwise weight function (weight), are shown for each of the first antenna elements (# 1 to # 8).
  • the received radio wave having an angle in the elevation angle direction arrives from the direction forming ⁇ with the X axis.
  • the signal that is, the voltage Vi ( ⁇ ) induced in the i-th first antenna element located on the circumference by the received radio wave can be calculated from the following (Equation 8).
  • the voltage E ⁇ a of the first signal which is the sum of the received signals of each of the eight first antenna elements, and the voltage E ⁇ b of the second signal.
  • the voltage E ⁇ a of the first signal can be calculated from (Equation 11)
  • the voltage E ⁇ b of the second signal can be calculated from (Equation 12).
  • FIG. 15A shows the elevation directivity of the first signal obtained by performing electromagnetic field analysis using the moment method.
  • FIG. 15B shows the elevation directivity of the third signal obtained by performing electromagnetic field analysis using the moment method.
  • the frequency used for analysis is 2 GHz
  • the radius a of the circular array phased array antenna 1 and 4.9 cm has a 7cm radius r g of the main plate.
  • the directivity characteristics when the sum of the received signal of the first antenna element is weighted in the directivity characteristic of the first signal or the weighting function W i a is the zenith direction (+ Z-axis direction), including, It can be seen that it has good radiation characteristics at high elevation angles.
  • the directivity characteristic of the third signal that is, the directivity characteristic of the received signal of the second antenna element, has a deep null formed in the zenith direction.
  • the phase angle of the voltage E ⁇ of the third signal induced in the second antenna element is calculated from the phase angle of the first signal E ⁇ a and the phase angle of the voltage E ⁇ b of the second signal.
  • FIG. 16 is a schematic diagram for explaining the principle of the phase inversion weighting method.
  • Figure 16 is a phase angle ⁇ E ⁇ a voltage E delta a of the first signal, and phase angle ⁇ E ⁇ b of the voltage E delta b of the second signal is shown.
  • the phase angle ⁇ E ⁇ a and phase angle ⁇ E ⁇ b and has an opposite inclination to the incoming wave direction. That is, the phase angle ⁇ E ⁇ a and the phase angle ⁇ E ⁇ b have symmetry. Therefore, the phase angle ⁇ E ⁇ (also referred to as the reference phase) of the voltage E ⁇ of the third signal used for estimating the direction of the incoming wave is defined as shown in the following (Equation 13). Thereby, the angle ⁇ m representing the direction of the incoming wave having an angle in the elevation angle direction can be expressed by (Equation 14).
  • both the voltage E ⁇ a of the first signal and the voltage E ⁇ b of the second signal have the elevation directivity shown in FIG. 15A.
  • the directivity of the voltage E ⁇ of the third signal is the average value of the directivity of the voltage E ⁇ a of the first signal and the voltage E ⁇ b of the second signal. Therefore, the directivity of the voltage E ⁇ of the third signal is the same as that of FIG. 15A, and the directivity is good, so that it is possible to estimate the direction of the incoming wave at a high elevation angle.
  • FIG. 17 is a diagram showing the three-dimensional directivity of the first signal and the third signal in the present embodiment.
  • FIG. 17 shows the three-dimensional directivity of the first signal and the third signal obtained by performing electromagnetic field analysis using the moment method.
  • FIG. 18A shows the directivity when the elevation angle direction is 30 degrees and the angle characteristics in the estimated arrival wave direction.
  • the directivity of the voltage E Omega voltage E delta a third signal of the first signal is shown in the case the elevation angle direction is 30 degrees.
  • FIG. 18A (b) shows an angle ⁇ m defined by the above (Equation 14), that is, an angle ⁇ m representing the direction of the incoming wave having 30 degrees in the elevation angle direction.
  • FIG. 18B shows the directivity when the elevation angle direction is 80 degrees and the angle characteristics in the estimated arrival wave direction.
  • the directivity of the voltage E Omega voltage E delta a third signal of the first signal is shown in the case the elevation angle direction is 80 degrees.
  • FIG. 18B (b) shows an angle ⁇ m defined by the above (Equation 14), that is, an angle ⁇ m representing the direction of the incoming wave having 80 degrees in the elevation angle direction.
  • the eight first antenna elements of the circular array phased array antenna 1 are divided and controlled into four so as to form a combination of sub-arrays arranged perpendicular to the direction of the incoming wave.
  • the MIMO array antenna function is realized.
  • the antenna device 10 of the present embodiment can improve the transmission capacity by realizing the MIMO array antenna function.
  • the radiation directivity of the monopole antenna mounted at the center of the circular main plate in the elevation direction can be controlled by changing the size of the main plate.
  • the effect of the base plate size on the transmission capacity of the MIMO array antenna has not been sufficiently investigated so far. Therefore, the result of confirming the relationship between the transmission capacity and the main plate size will be described below.
  • Figure 19 is a graph showing changes in transmission capacity for the elevation direction of the incoming wave when changing the radius r g of the ground plate 2 in this embodiment.
  • FIG. 19 shows the results of Monte Carlo simulation using a channel model of a cluster propagation environment in which both the azimuth angle and the elevation angle have Gaussian distribution arrival waves in three-dimensional coordinates.
  • the radiation characteristics of the entire MIMO array antenna were calculated by the moment method.
  • the analysis frequency is 2 GHz.
  • All antenna elements constituting the circular array phased array antenna 1 were 1/4 wavelength monopole antennas having a length of 37.5 mm and a radius of 0.5 mm.
  • the radius a of the circular array phased array antenna 1 that functions as a 4 ⁇ 4 MIMO array antenna is 4.9 cm, and the distance between the first antenna elements # 2 and # 3 is set to 1/4 wavelength at 2 GHz, resulting in cardioid directivity. Formed.
  • the transmission capacity in elevation is changed by the radius r g of the main plate 2. More specifically, from FIG. 19, the radius r g ranging elevation angle 0-15 degrees base plate is 13cm, 15 ⁇ 60 degrees in the range of the main plate 2 radius r g is 10 cm, 60 ⁇ 90 degrees range transmission capacity when the radius r g is the 13cm of the main plate is the largest. Therefore, it can be seen that it is necessary to control the radius r g optimal ground plane in accordance with the elevation angle to be communicating.
  • the transmission capacity is increased significantly in the high elevation angle of 30 degrees to 60 degrees. From this result, in consideration of the elevation properties and practical antenna shape, one of the radius r g of the main plate 2 is variable in the present embodiment was 10 cm.
  • the three-dimensional radiation directivity in the sub-array will be described.
  • three-dimensional radiation directivity will be described when the first antenna elements # 1 and # 4 are sub-arrays 2 (hereinafter, also referred to as monopole array antennas) in the circular array phased array antenna 1.
  • the first antenna elements # 1 and # 4 are sub-arrays 2 (hereinafter, also referred to as dipole array antennas).
  • the three-dimensional radiation directivity of is also described.
  • FIG. 20A is a diagram showing the three-dimensional radiation directivity of the dipole array antenna in the comparative example.
  • FIG. 20B is a diagram showing the three-dimensional radiation directivity of the monopole array antenna according to the present embodiment.
  • the three-dimensional radiation directivity of the dipole array antenna shown in FIG. 20A has a deep null formed in the zenith direction (+ Z direction), and the radiation in the high elevation angle direction is significantly reduced. doing.
  • the monopole array antenna shown in FIG. 20B a deep null is not formed in the zenith direction (+ Z direction), and a significant improvement in radiation gain at a high elevation angle can be seen as compared with the dipole array antenna shown in FIG. 20A. Be done.
  • the sandwich array device 100 has a function of performing directional scanning at intervals of 45 degrees, but below, only three-dimensional radiation directivity at intervals of 90 degrees will be described as an example.
  • FIGS. 21A to 22D are diagrams showing three-dimensional directivity when the sandwich array device 100 in the present embodiment is subjected to directivity scanning.
  • FIG 21A ⁇ FIG 21D in the upper part of the antenna device 10A sandwich the array device 100, the radius r g of the base plate 2 and 10 cm, when the first antenna element # 1, and # 4 as the sub-array 2, azimuth To communicate The three-dimensional radiation directivity when the angle is changed is shown.
  • FIG 22A ⁇ FIG 22D in the lower part of the antenna device 10B of the sandwich array device 100, the radius r g of the base plate 2 and 10 cm, when the first antenna element # 1, and # 4 as the sub-array 2, azimuth To communicate The three-dimensional radiation directivity when the angle is changed is shown.
  • FIGS. 21A to 21D and 22A to 22D show three-dimensional radiation directivity at 90 degree intervals.
  • the directivity gain in the depression angle direction can be improved and the entire solid angle can be covered by complementarily linking the upper antenna device 10A and the lower antenna device 10B.
  • FIG. 23 is a diagram showing the elevation characteristic of the transmission capacity of the MIMO array antenna using the half-wavelength dipole array antenna in the comparative example.
  • the analysis frequency is 2 GHz
  • the SNR is 30 dB
  • the XPR (cross-polarized power ratio) is 10 dB.
  • ⁇ shown in FIG. 23 represents the spread angle (standard deviation) of the Gaussian arrival wave in the azimuth direction (horizontal direction) and the elevation direction (elevation angle direction).
  • ⁇ represents the angle in the elevation direction, that is, the arrival wave elevation angle.
  • FIG. 24A is a diagram showing the azimuth characteristics of the transmission capacity of the MIMO array antenna using the sandwich array device according to the embodiment.
  • FIG. 24B is a diagram showing the elevation characteristic of the transmission capacity of the MIMO array antenna using the sandwich array device 100 in the present embodiment.
  • FIG. 24A shows the elevation characteristic of the transmission capacity with respect to the azimuth angle
  • FIG. 24B shows the elevation characteristic of the transmission capacity with respect to the elevation angle.
  • the analysis frequency is 2 GHz
  • the SNR is 30 dB
  • the XPR is 10 dB.
  • LOS line-of-sight
  • the upper antenna device 10A is selected as the MIMO array antenna with an elevation angle target of 0 to 90 degrees
  • the lower antenna device 10B is selected with a depression angle target of ⁇ 90 degrees to 0 degrees. And said.
  • the transmission capacity of the MIMO array antenna is almost constant in all azimuth directions for any spread angle. From this, it can be seen that a stable transmission capacity can be realized by controlling the beam (directivity) of the MIMO array antenna using the sandwich array device 100 to the incoming wave azimuth angle.
  • the transmission capacity of the MIMO array antenna has a characteristic symmetrical with respect to the elevation angle of 0 degrees by the switching operation between the upper antenna device 10A and the lower antenna device 10B. Further, it can be seen in FIG. 24B that the fluctuation of the transmission capacity of the MIMO array antenna with respect to the elevation angle is small. From this, it can be seen that a stable transmission capacity can be realized by controlling the beam (directivity) of the MIMO array antenna using the sandwich array device 100 to the arrival wave elevation angle.
  • the transmission capacity of the MIMO array antenna using the sandwich array device 100 generally maintains the maximum transmission capacity of the MIMO array antenna using the half-wavelength dipole array antenna.
  • FIG. 25 is a diagram showing a three-dimensional transmission capacity over the entire solid angle of the MIMO array antenna using the half-wavelength dipole array antenna in the comparative example.
  • FIG. 26 is a diagram showing a three-dimensional transmission capacity over the entire solid angle of the MIMO array antenna using the sandwich array device 100 in the present embodiment.
  • the transmission capacity of the MIMO array antenna using the half-wave dipole array antenna has deep nulls formed in the zenith direction and the nadir direction.
  • the transmission capacity of the MIMO array antenna using the sandwich array device 100 in the present embodiment has a spherical shape having an equal radius. From this, it can be seen that the MIMO array antenna using the sandwich array device 100 in the present embodiment has an ability to connect to the target in any direction.
  • the above-mentioned characteristics of the transmission capacity of the MIMO array antenna using the sandwich array device 100 in the present embodiment can be obtained by appropriate power synthesis of the ⁇ component and the ⁇ component of the radiation directivity.
  • the ⁇ component arises from the current distribution induced in the main plate 2. Therefore, in principle, the ⁇ component does not exist in the half-wavelength dipole array antenna composed of the dipole antenna.
  • the communication cutoff probability is defined as the probability that the transmission capacity is lower than the specified threshold value, as shown in (Equation 15) below.
  • Equation 15 p ( ⁇ , ⁇ ) indicates the probability density function (PDF) of the transmission capacity over all solid angles.
  • Cth indicates the threshold value of the transmission capacity.
  • ⁇ th indicates the azimuth angle corresponding to C th , and ⁇ th indicates the elevation angle corresponding to C th.
  • FIG. 27 is a diagram showing the communication cutoff probability over the entire solid angle of the MIMO array antenna using the sandwich array device 100 in the present embodiment.
  • the present disclosure shown in FIG. 27 represents a MIMO array antenna using the sandwich array device 100.
  • the comparative example shown in FIG. 27 represents a MIMO array antenna using the above-mentioned half-wave dipole array antenna.
  • the horizontal axis is the transmission capacity standardized by the maximum value C max of the transmission capacity defined by the following (Equation 16).
  • the MIMO array antenna using the sandwich array device 100 according to the present disclosure is capable of high-speed communication of 87% of the maximum transmission capacity over all directions in the three-dimensional space.
  • the sandwich array device 100 of the present embodiment can 1) form monopulse directivity by the space division monopulse method, 2) can estimate the direction of the incoming wave over all solid angles, and 3) MIMO array antenna. It became clear that it has the function of. Also, the sandwich array apparatus 100 of the present embodiment, a case where the formation of monopulse directional, the the case of estimating the direction of arrival over the entire solid angle, radius r g of the base plate 2 and 7 cm, MIMO when realizing the functions of the array antenna, the radius r g of the base plate 2 is set to 10 cm. That is, in a sandwich array apparatus 100 of the present embodiment, 1) for realizing a single device all the functions of ⁇ 3), switches the radius r g of the ground plate 2 by the on-off operation of the diode.
  • a multi-element MIMO array antenna may be formed by modularizing and combining the sandwich array device 100. This case will be described below.
  • FIG. 28 is a diagram showing an example of a multi-element MIMO array antenna in a modified example.
  • FIG. 28 shows an example in which five sandwich array devices 100a, 100b, 100c, 100d, and 100e are combined to form a multi-element MIMO array antenna.
  • a multi-element MIMO array antenna may be formed by modularizing and combining the antenna devices 10. This case will be described below.
  • FIG. 29A is a diagram showing an example of a 4 ⁇ 4 MIMO array antenna in a modified example.
  • FIG. 29B is a diagram showing an example of an 8 ⁇ 8 MIMO array antenna in the modified example.
  • FIG. 29C is a diagram showing an example of a 16 ⁇ 16 MIMO array antenna in a modified example.
  • FIG. 29D is a diagram showing an example of a 32 ⁇ 32 MIMO array antenna in the modified example.
  • FIG. 29E is a diagram showing an example of a 64 ⁇ 64 MIMO array antenna in the modified example.
  • FIG. 29F is a diagram showing an example of a 128 ⁇ 128 MIMO array antenna in a modified example.
  • FIG. 29G is a diagram showing an example of a 256 ⁇ 256 MIMO array antenna in the modified example.
  • 29A to 29G each show a combination of antenna devices 10 when a multi-element MIMO array antenna is viewed from above.
  • each component may be configured by dedicated hardware, or a component that can be realized by software may be realized by executing a program.
  • the modules constituting the antenna device 10 are realized in the form of IC (integrated circuit), ASIC (integrated circuit for specific applications), LSI (large-scale integrated), or based on a CPU such as ARM. It may be realized by a processor and a machine such as a PC (personal computer). Each of these modules may be included in many single-function LSIs or one LSI.
  • the name used here is LSI, but it may also be called IC, system LSI, super LSI or ultra LSI depending on the degree of integration.
  • the integration method is not limited to LSI, and can be integrated by a dedicated circuit, a general-purpose processor, or the like.
  • DSPs digital signal processors
  • An FPGA Field Programmable Gate Array
  • a reconfigurable processor capable of reconfiguring the connection or arrangement of the LSI can be used for the same purpose.
  • completely new technologies may be replaced by LSIs. Integration can be achieved by such technology.
  • the present invention can be used for an antenna device or the like that estimates the arrival wave direction of a received radio wave and controls the directivity in the estimated arrival wave direction to realize highly reliable communication, and is particularly used for a flying vehicle, a MIMO antenna, or the like. It can be used for antenna devices and the like.

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Abstract

L'invention concerne un dispositif d'antenne qui comprend : une antenne réseau à commande de phase circulaire (1) comprenant un nombre N (N étant un entier naturel supérieur ou égal à 3) de premiers éléments d'antenne agencés à intervalles réguliers sur un cercle et un second élément d'antenne agencé approximativement au centre du cercle ; et une plaque inférieure circulaire (2) ayant un rayon qui peut être modifié par commande de commutation. Les premiers éléments d'antenne et le second élément d'antenne comprennent une antenne monopôle montée sur la plaque inférieure (2).
PCT/JP2020/030389 2019-08-26 2020-08-07 Dispositif d'antenne et dispositif à réseau en sandwich WO2021039362A1 (fr)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113406561A (zh) * 2021-05-31 2021-09-17 中国电子科技集团公司第三十六研究所 一种测向方法和装置

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS6125304A (ja) * 1984-07-02 1986-02-04 カナダ国 小型適応型アレイアンテナ
JP2001024431A (ja) * 1999-07-08 2001-01-26 Atr Adaptive Communications Res Lab アレーアンテナ装置
JP2004214863A (ja) * 2002-12-27 2004-07-29 Murata Mfg Co Ltd アンテナ装置および通信端末装置
JP2019039920A (ja) * 2017-08-25 2019-03-14 国立大学法人富山大学 方向推定装置および方向推定方法

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS6125304A (ja) * 1984-07-02 1986-02-04 カナダ国 小型適応型アレイアンテナ
JP2001024431A (ja) * 1999-07-08 2001-01-26 Atr Adaptive Communications Res Lab アレーアンテナ装置
JP2004214863A (ja) * 2002-12-27 2004-07-29 Murata Mfg Co Ltd アンテナ装置および通信端末装置
JP2019039920A (ja) * 2017-08-25 2019-03-14 国立大学法人富山大学 方向推定装置および方向推定方法

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113406561A (zh) * 2021-05-31 2021-09-17 中国电子科技集团公司第三十六研究所 一种测向方法和装置

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