WO2020237889A1 - 通过副边调制实现pfc的无线电能传输系统 - Google Patents

通过副边调制实现pfc的无线电能传输系统 Download PDF

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WO2020237889A1
WO2020237889A1 PCT/CN2019/103793 CN2019103793W WO2020237889A1 WO 2020237889 A1 WO2020237889 A1 WO 2020237889A1 CN 2019103793 W CN2019103793 W CN 2019103793W WO 2020237889 A1 WO2020237889 A1 WO 2020237889A1
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voltage
secondary side
current
pfc
primary
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French (fr)
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钟文兴
李豪
徐德鸿
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Zhejiang University
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Zhejiang University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—ELECTRIC POWER NETWORKS; CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4258—Arrangements for improving power factor of AC input using a single converter stage both for correction of AC input power factor and generation of a regulated and galvanically isolated DC output voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters

Definitions

  • the invention belongs to the technical field of wireless power transmission, and relates to a wireless power transmission system that implements PFC through secondary side modulation.
  • the traditional wireless charging system topology is shown in Figure 1.
  • the grid voltage is rectified into a DC voltage through a PFC (Power Factor Correction) circuit, and the coil is powered by a full-bridge inverter, and the secondary receiving end is output after passing through the rectifier bridge.
  • PFC Power Factor Correction
  • the original and secondary sides all use SS compensation network structure.
  • the present invention provides a wireless charging system topology that realizes PFC only through secondary side modulation, so as to save additional PFC circuits, simplify the structure and reduce costs.
  • the purpose of the present invention is to provide a wireless power transmission system that realizes PFC through secondary side modulation. Compared with the traditional topology, the traditional PFC circuit is omitted, and the structure is simple, the efficiency is high, and the cost is low.
  • a wireless power transmission system that realizes PFC through secondary side modulation. This system is based on the topology of the traditional wireless charging system, removing the traditional PFC circuit, so that the grid voltage is uncontrolled rectified into a 100Hz voltage directly to the primary side of the wireless charging system Inverter power supply, the secondary side adopts an active full-bridge rectifier structure, and the PFC function is realized only through secondary side modulation.
  • phase shift angle of the primary inverter ⁇ (the phase shift angle is generally defined as the phase difference between the upper and lower tubes of the two bridge arms, and the upper and lower tubes of each bridge arm are complementary
  • the switching action of 50% switching period is performed on the ground)
  • the phase shift angle ⁇ of the secondary side rectifier, the control voltage of the upper tube of the first bridge arm of the secondary side rectifier u gs5 is ahead of the control voltage of the upper tube of the first bridge arm of the primary side inverter
  • the phase angle ⁇ of u gs1 (the phase shift angle is generally defined as the phase difference between the upper and lower tubes of the two bridge arms, and the upper and lower tubes of each bridge arm are complementary
  • phase shift angle ⁇ of the primary side adjusts the phase shift angle ⁇ of the secondary side as follows:
  • V O is the output DC voltage
  • R L is the equivalent load resistance at the output
  • M is the original The mutual inductance value of the secondary coil
  • the 50Hz harmonic of the input current of the primary side rectifier bridge is in phase with the input voltage.
  • the grid-side voltage and current power factor is close to 1.
  • the system of the present invention saves the traditional PFC circuit, and can realize the PFC only through secondary side modulation, and has simple structure, high efficiency and low cost.
  • Figure 1 shows the traditional wireless charging system topology.
  • Figure 2 is a schematic diagram of the wireless power transmission system of the present invention.
  • Figure 3 shows the primary inverter output voltage v 1 , its envelope v 1blx and its 85kHz fundamental wave component envelope v 10blx .
  • Figure 4 shows the input voltage v 2 of the secondary side rectifier and its 85kHz fundamental component envelope as v 20blx .
  • Figure 5 shows the timing of the primary and secondary control signals.
  • Figure 6 shows the ⁇ (t) and ⁇ (t) waveforms when the maximum voltage is output.
  • Figure 7 shows the coil part of the experimental platform.
  • Figure 8 shows the grid side voltage and current (v grid , i grid ) and its power factor in the case of the maximum output voltage.
  • Figure 9 shows the voltage and current (V in , i in ) after uncontrolled rectification in the case of the maximum output voltage.
  • Figure 10 shows the output voltage V 1 , current i 1 of the primary inverter and its amplified waveforms in the case of the maximum output voltage.
  • Figure 11 shows the input voltage V 2 and current i 2 of the secondary side rectifier and their amplified waveforms under the condition of the maximum output voltage.
  • Figure 12 shows the primary and secondary currents i 1 and i 2 under the condition of the maximum output voltage.
  • Figure 13 shows the secondary active rectifier output current i 3 under the maximum output voltage.
  • Figure 14 shows the output DC voltage U O when the maximum voltage is output.
  • Figure 15 shows the ⁇ (t) and ⁇ (t) waveforms of the power control scheme.
  • Figure 16 shows the grid side voltage and current (v grid , i grid ) and its power factor of the power control scheme.
  • Figure 17 shows the voltage and current (V in , i in ) after uncontrolled rectification of the power control scheme.
  • Figure 18 shows the output voltage V 1 , current i 1 of the primary inverter and their amplified waveforms in the power control scheme.
  • Figure 19 shows the secondary side rectifier input voltage V 2 , current i 2 and their amplified waveforms in the power control scheme.
  • Figure 20 shows the primary and secondary currents i 1 and i 2 of the power control scheme.
  • Figure 21 shows the secondary active rectifier output current i 3 of the power control scheme.
  • Figure 22 shows the output DC voltage U O under the maximum output voltage of the power control scheme.
  • Figure 23 shows the ⁇ (t) and ⁇ (t) waveforms under the second power control scheme.
  • Figure 24 shows the grid-side voltage and current (v grid , i grid ) and its power factor in the second power control scheme.
  • Figure 25 shows the voltage and current (V in , i in ) after uncontrolled rectification in the second power control scheme.
  • Fig. 26 shows the output voltage V 1 , current i 1 of the primary inverter in the second power control scheme and their amplified waveforms.
  • Figure 27 shows the input voltage V 2 and current i 2 of the secondary side rectifier in the second power control scheme and their amplified waveforms.
  • Figure 28 shows the primary and secondary currents i 1 and i 2 in the second power control scheme.
  • Figure 29 shows the secondary active rectifier output current i 3 of the second power control scheme.
  • Figure 30 shows the output DC voltage U O in the case of the maximum output voltage in the second power control scheme.
  • Figure 31 shows the ⁇ (t) and ⁇ (t) waveforms under the third power control scheme.
  • Figure 32 shows the grid-side voltage and current (v grid , i grid ) and its power factor under the third power control scheme.
  • Figure 33 shows the voltage and current (V in , i in ) after three uncontrolled rectification of the power control scheme.
  • Figure 34 shows the output voltage V 1 , current i 1 of the primary inverter in the third power control scheme and their amplified waveforms.
  • Figure 35 shows the input voltage V 2 , current i 2 and their amplified waveforms of the secondary side rectifier in the third power control scheme.
  • Figure 36 shows the three primary and secondary side currents i 1 and i 2 of the power control scheme.
  • Figure 37 shows the secondary active rectifier output current i 3 in the third power control scheme.
  • Figure 38 shows the output DC voltage U O when the maximum voltage is output in the third power control scheme.
  • FIG. 2 is a schematic structural diagram of the wireless charging system of the present invention; compared with the traditional wireless charging topology, the PFC circuit is omitted, and the grid voltage is uncontrolled rectified into a 100Hz voltage to directly supply power to the primary side inverter of the wireless charging system.
  • the operating frequency of the system is 85kHz
  • the secondary side adopts an active full-bridge rectifier structure
  • the grid-side EMI filter filters out 85kHz high frequency components.
  • Cp is a small-capacity high-frequency filter capacitor
  • Co is a low-frequency large-capacity filter capacitor.
  • the PFC function can be realized only through secondary side modulation.
  • the original secondary side adopts full bridge phase shift. After the primary side grid voltage is rectified, it presents a 100Hz pulsating voltage, which directly supplies power to the primary side inverter of the wireless charging system.
  • the secondary side adjusts v 2 by phase shifting so that the 85kHz fundamental voltage component presents a 100Hz in-phase low frequency pulsation, and its envelope is v 20blx , as shown in Figure 4. Therefore, the 50Hz harmonics of the input current of the primary side rectifier bridge are in phase with the input voltage. After passing through the EMI filter, the grid-side voltage and current power factor is close to 1.
  • the control signal sequence is shown in Figure 5.
  • the phase shift angle of the primary inverter is ⁇
  • v 1 and i 1 are the inverter output voltage and current respectively
  • the phase shift angle of the secondary rectifier is ⁇
  • the upper tube u gs5 exceeds
  • the inverter phase shift angle ⁇ is determined to be a fixed value, and the rectifier phase shift angle ⁇ is low-frequency pulsation modulation, so that the primary current i 1 exhibits low-frequency pulsation, while ⁇ follows ⁇ low-frequency pulsation changes to ensure the input voltage of the rectifier v 2 is in phase with the secondary current i 2 .
  • ⁇ is the inverter phase shift angle
  • V 1 is the inverter output voltage 85kHz fundamental wave
  • I 2 is the effective value of the secondary coil current
  • M is the mutual inductance value of the primary and secondary coil.
  • the input voltage of the secondary rectifier is phase-shifted to make the fundamental voltage present 100Hz low-frequency pulsation, the primary current also presents 100Hz low-frequency pulsation, and the 50Hz harmonic of the input current of the primary rectifier bridge It is in phase with the input voltage, and after passing through the EMI filter, the power factor of the grid-side voltage and current is close to 1.
  • V 2 is the effective value of the fundamental wave of the rectifier input terminal voltage
  • A is the amplitude of the 85kHz fundamental wave of the 100Hz envelope of the rectifier input terminal voltage.
  • ⁇ (t) is the phase shift angle of the secondary rectifier
  • I 1 is the effective value of the fundamental wave of the primary coil current.
  • ⁇ (t) and ⁇ (t) waveforms are shown in Fig. 6, and the periods are both 100Hz, and the linear changes present low-frequency pulsation.
  • the output voltage and current of the inverter are shown in Figure 10. Limited by the input pulsating voltage, the inverter output voltage V 1 and current i 1 both present 100 Hz pulsation, and the modulation frequency is 85 kHz, and the voltage and current are in the same phase.
  • the input voltage V 2 and current i 2 of the secondary side rectifier are shown in Fig. 11, both present 100 Hz pulsation, and the modulation frequency is 85 kHz.
  • the phase shift angle of the voltage V 2 is modulated in real time, and the voltage and current are in the same phase.
  • the primary and secondary coil currents i 1 and i 2 are shown in Figure 12. After active rectification, the current waveform i 3 is shown in Figure 13, showing a pulsating form, the output voltage is shown in Figure 14, the average output voltage is 180V, and the peak-to-peak ripple takes up 1.55%.
  • V O is a function of ⁇ and ⁇ .
  • adjustment schemes 1. Adjust ⁇ , keep ⁇ unchanged 2. Adjust ⁇ , keep ⁇ not Change 3. Regulate ⁇ , regulate ⁇ .
  • ⁇ (t) and ⁇ (t) waveforms are shown in Fig. 15.
  • the periods are both 100Hz, and the linear changes present low-frequency pulsation.
  • Input voltage and grid-side current shown in FIG. 16 the power factor of 0.982; after controlled rectifier circuit, a voltage v in and the current i in shown in FIG. 17, showed a 100Hz ripple.
  • the output voltage and current of the inverter are shown in Fig. 18, and the input voltage V 2 and current i 2 of the secondary side rectifier are shown in Fig. 19, and the voltage and current are all in the same phase.
  • the primary and secondary coil currents i 1 and i 2 are shown in Figure 20.
  • the current waveform i 3 is shown in Figure 21, showing a pulsating form
  • the output voltage is shown in Figure 22, the average output voltage is 92V, and the peak-to-peak ripple takes up 1.64%.
  • ⁇ (t) and ⁇ (t) waveforms are shown in Figure 23, and the periods are both 100Hz, and the approximate sine changes present low-frequency pulsation.
  • the inverter output voltage and current are shown in Figure 26, and the voltage and current are in phase.
  • the input voltage V 2 and current i 2 of the secondary side rectifier are shown in Fig. 27, and the voltage and current are in the same phase.
  • the primary and secondary coil currents i 1 and i 2 are shown in Figure 28.
  • the current waveform i 3 is shown in Figure 29, showing a pulsating form
  • the output voltage is shown in Figure 30, the average output voltage is 91V, and the peak-to-peak ripple ratio is 1.65%.
  • ⁇ (t) and ⁇ (t) waveforms are shown in Figure 31, and the periods are both 100Hz, which are approximately sinusoidal and exhibit low-frequency pulsation.
  • the theoretical and simulation results are shown in Table 5.
  • the output voltage 90V theory is basically consistent with the simulation, and the primary and secondary current envelopes are basically the same, which proves that the power can be adjusted according to the third option, and the theoretical derivation is correct.
  • the inverter output voltage and current are shown in Fig. 34, the inverter output voltage V 1 and current i 1 both present 100 Hz pulsation, and the modulation frequency is 85 kHz, and the voltage and current are in the same phase.
  • the input voltage V 2 and current i 2 of the secondary side rectifier are shown in Fig.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Inverter Devices (AREA)
  • Rectifiers (AREA)

Abstract

本发明公开了一种通过副边调制实现PFC的无线电能传输系统，该系统是在传统无线充电系统拓扑的基础上，去除传统PFC电路，使电网电压经过不控整流成100Hz电压直接给无线充电系统的原边逆变器供电，副边采用有源全桥整流结构，仅通过副边调制实现PFC功能，具体是在给定原边逆变器移相角α的情况下，按一定的规律调控副边整流器移相角β和副边整流器第一个桥臂上管的控制电压u gs5超前原边逆变器第一个桥臂上管的控制电压u gs1的相位角γ；最终实现原边整流桥输入电流的50Hz谐波与输入电压同相，经过EMI滤波器后，实现网侧电压电流功率因数接近1。本发明的系统相比于传统拓扑，省去了额外的PFC电路，仅通过副边调制即可实现PFC，结构简单、效率高、成本低。

Description

通过副边调制实现PFC的无线电能传输系统 技术领域
本发明属于无线电能传输技术领域，涉及一种通过副边调制实现PFC的无线电能传输系统。
背景技术
随着电动汽车产业的迅速发展，无线充电技术凭借着其安全、灵活、方便等优势正受到越来越多的关注。传统的无线充电系统拓扑如图1所示，电网电压经过PFC(Power Factor Correction，功率因数校正)电路整流成直流电压，通过全桥逆变器为线圈供电，副边接收端经过整流桥后输出，其中原副边均采用SS补偿网络结构。
本发明提供一种仅通过副边调制即实现PFC的无线充电系统拓扑，以省去额外的PFC电路，简化结构，降低成本。
发明内容
本发明的目的在于提供一种通过副边调制实现PFC的无线电能传输系统，相比于传统拓扑省去传统PFC电路，结构简单、效率高、成本低。
本发明采用的技术方案如下：
一种通过副边调制实现PFC的无线电能传输系统，该系统是在传统无线充电系统拓扑的基础上，去除传统PFC电路，使电网电压经过不控整流成100Hz电压直接给无线充电系统的原边逆变器供电，副边采用有源全桥整流结构，仅通过副边调制实现PFC功能。
通过副边调制实现PFC功能具体为：
该系统中控制自由度共有3个，依次为原边逆变器移相角α(移相角一般定义为两桥臂上管或下管开通的相位差，其中每一桥臂的上下管互补地进行50％开关周期的开关动作)、副边整流器移相角β、副边整流器第一个桥臂上管的控制电压u gs5超前原边逆变器第一个桥臂上管的控制电压u gs1的相位角γ；
给定原边移相角α，按下式调控副边移相角β：
Figure PCTCN2019103793-appb-000001
其中，V O为输出直流电压，R L为输出端等效负载电阻，ω 0＝2πf 0＝2π·85kHz为系统谐振角频率，ω＝2πf＝2π·50Hz为电网电压角频率，M为原副边线圈互感值；
按下式调控相位角γ：
Figure PCTCN2019103793-appb-000002
在此条件下，原边整流桥输入电流的50Hz谐波与输入电压同相，经过EMI滤波器后，实现网侧电压电流功率因数接近1。
本发明的有益效果是：
本发明的系统相比于传统拓扑，省去传统PFC电路，仅通过副边调制即可实现PFC，结构简单、效率高、成本低。
附图说明
图1为传统的无线充电系统拓扑。
图2为本发明的无线电能传输系统示意图。
图3为原边逆变器输出电压v 1、其包络线v 1blx及其85kHz基波分量包络线为v 10blx。
图4为副边整流器入端电压v 2及其85kHz基波分量包络线为v 20blx。
图5为原副边控制信号时序。
图6为输出最大电压情况下的β(t)与γ(t)波形。
图7为实验平台线圈部分。
图8为输出最大电压情况下电网侧电压电流(v grid、i grid)及其功率因数。
图9为输出最大电压情况下不控整流后电压电流(V in、i in)。
图10为输出最大电压情况下原边逆变器输出电压V 1、电流i 1及其放大波形。
图11为输出最大电压情况下副边整流器输入电压V 2、电流i 2及其放大波形。
图12为输出最大电压情况下原副边电流i 1、i 2。
图13为输出最大电压情况下副边有源整流输出电流i 3。
图14为输出最大电压情况下输出直流电压U O。
图15为功率控制方案一下的β(t)与γ(t)波形。
图16为功率控制方案一下电网侧电压电流(v grid、i grid)及其功率因数。
图17为功率控制方案一下不控整流后电压电流(V in、i in)。
图18为功率控制方案一下原边逆变器输出电压V 1、电流i 1及其放大波形。
图19为功率控制方案一下副边整流器输入电压V 2、电流i 2及其放大波形。
图20为功率控制方案一下原副边电流i 1、i 2。
图21为功率控制方案一下副边有源整流输出电流i 3。
图22为功率控制方案一下输出最大电压情况下输出直流电压U O。
图23为功率控制方案二下的β(t)与γ(t)波形。
图24为功率控制方案二下电网侧电压电流(v grid、i grid)及其功率因数。
图25为功率控制方案二下不控整流后电压电流(V in、i in)。
图26为功率控制方案二下原边逆变器输出电压V 1、电流i 1及其放大波形。
图27为功率控制方案二下副边整流器输入电压V 2、电流i 2及其放大波形。
图28为功率控制方案二下原副边电流i 1、i 2。
图29为功率控制方案二下副边有源整流输出电流i 3。
图30为功率控制方案二下输出最大电压情况下输出直流电压U O。
图31为功率控制方案三下的β(t)与γ(t)波形。
图32为功率控制方案三下电网侧电压电流(v grid、i grid)及其功率因数。
图33为功率控制方案三下不控整流后电压电流(V in、i in)。
图34为功率控制方案三下原边逆变器输出电压V 1、电流i 1及其放大波形。
图35为功率控制方案三下副边整流器输入电压V 2、电流i 2及其放大波形。
图36为功率控制方案三下原副边电流i 1、i 2。
图37为功率控制方案三下副边有源整流输出电流i 3。
图38为功率控制方案三下输出最大电压情况下输出直流电压U O。
具体实施方式
下面详细说明本发明的技术方案。
图2为本发明的无线充电系统的一种结构示意图；相对于传统的无线充电拓扑，省去PFC电路，电网电压经过不控整流成100Hz电压直接给无线充电系统的原边逆变器供电，系统工作频率为85kHz，副边采用有源全桥整流结构，网侧EMI滤波器滤除85kHz高频分量。其中Cp为小容量高频滤波电容，Co为低频大容量滤波电容。对于该拓扑，仅通过副边调制即可实现PFC功能。
控制方法
原副边均采用全桥移相。原边电网电压经过整流后，呈现100Hz脉动电压，直接向无线充电系统的原边逆变器供电，在逆变器移相角α＝180°情况时，逆变器输出方波电压v 1如图3所示，其包络线v 1blx为电网脉动电压，85kHz基波分量包络线为v 10blx。副边通过移相调整v 2使得85kHz基波电压分量呈现100Hz同相低频脉动，其包络线为v 20blx，如图4所示。因此，原边整流桥输入电流的50Hz谐波与输入电压同相，经过EMI滤波器后，实现网侧电 压电流功率因数接近1。
对于图2所示无线充电系统结构，控制自由度共有3个，依次为原边逆变器移相角α、副边整流器移相角β、副边控制信号超前原边控制信号角度γ。控制信号时序如图5所示，原边逆变器移相角为α，v 1、i 1分别是逆变器输出电压与电流；副边整流器移相角为β，其上管u gs5超前原边逆变器上管u gs1相位角γ＝90-α/2+β/2，在此条件下，整流器输入端电压v 2与副边电流i 2同相，且超前i 1与v 1角度为90°。
实际中，逆变器移相角α确定之后为定值，整流器移相角β低频脉动调制，以使得原边电流i 1呈现低频脉动，同时γ跟随β低频脉动变化，以保证整流器输入端电压v 2与副边电流i 2同相。比如，当α＝180°，β＝180°，则γ＝90°，此时输出最大电压，且满足整流器输入端电压v 2与副边电流i 2同相，超前i 1与v 1角度为90°；当α＝180°，β＝90°，则γ＝45°，同样满足整流器输入端电压v 2与副边电流i 2同相，超前i 1与v 1角度为90°。
理论推导
Figure PCTCN2019103793-appb-000003
Figure PCTCN2019103793-appb-000004
其中，ω 0＝2πf 0＝2π·85kHz为系统谐振角频率，ω＝2πf＝2π·50Hz为电网电压角频率，α为逆变器移相角，V 1为逆变器输出电压85kHz基波有效值，I 2为副边线圈电流有效值，M为原副边线圈互感值。
为使得网侧功率因数为1，通过移相调制副边整流器入端电压，使得其基波电压呈现100Hz低频脉动，则原边电流同样呈现100Hz低频脉动，原边整流桥输入电流的50Hz谐波与输入电压同相，经过EMI滤波器后，实现网侧电压电流功率因数接近1。
假设
Figure PCTCN2019103793-appb-000005
其中，V 2为整流器入端电压基波有效值，A为整流器入端电压85kHz基波100Hz包络线的幅值。
由于副边电压电流同相，那么
Figure PCTCN2019103793-appb-000006
其中P O为输出功率，V O为输出直流电压，R L为负载等效电阻。
因此可以解得低频包络线幅值A，
Figure PCTCN2019103793-appb-000007
则有
Figure PCTCN2019103793-appb-000008
Figure PCTCN2019103793-appb-000009
其中，β(t)为副边整流器移相角，I 1为原边线圈电流基波有效值。
计算得到
Figure PCTCN2019103793-appb-000010
Figure PCTCN2019103793-appb-000011
Figure PCTCN2019103793-appb-000012
仿真验证
假设原边移相角α＝180°，副边整流器入端电压基波包络线的幅值为
Figure PCTCN2019103793-appb-000013
那么根据式(8)及(9)计算得到，
β(t)＝2arcsin(sinωt)   (11)
Figure PCTCN2019103793-appb-000014
β(t)与γ(t)波形如图6所示，周期均为100Hz，线性变化呈现低频脉动。
为验证整个调制方式，系统框图如图2所示，控制波形如图5所示，实验平台线圈部分如图7所示，实验平台参数如表1所示。
表1
L 1/uH L 2/uH C 1/nF C 2/nF R 1/Ω
490 490 7.2 7.2 1
R 2/Ω M/uH f 0/kHz V O/V R L/Ω
1 65 84.73 180 50
选取EMI滤波器参数C F1、C F2、L F1依次为1uF、1uF、600uH,逆变器前端小容量滤波电容C P＝100nF，输出端大容量滤波C O＝4mF。
理论与仿真结果如表2所示，输出电压180V理论与仿真基本相符，且原副边电流包络线基本一致，证明理论公式推导正确。
表2
  I 1max/A I 2max/A Vo/V
理论 6.6 11.4 182
仿真 7.1 10.9 180
电网侧输入电压与电流如图8所示，功率因数为0.997；经过不控整流电路后，电压v in与电流i in如图9所示，其中85kHz电流i in电流呈现出100Hz脉动。逆变器输出电压电流如图10所示，受输入脉动电压的限制，逆变输出电压V 1与电流i 1均呈现100Hz脉动，且调制频率为85kHz，电压电流同相位。副边整流器入端电压V 2与电流i 2如图11所示，均呈现100Hz脉动，且调制频率为85kHz，电压V 2移相角实时调制变化，电压电流同相位。原副边线圈电流i 1,i 2如图12所示。经有源整流后，电流波形i 3如图13所示，呈现脉动形式，输出电压如图14，输出电压均值为180V，纹波峰峰值占比1.55％。
功率调节验证
根据式(10)
Figure PCTCN2019103793-appb-000015
可以得到调节V O的方式，假设R L，M已知，则V O是关于α，β的函数，则有三种调节方案：1.调节α，保持β不变 2.调节β，保持α不变 3.调节α，调节β。
现在以调节至V O＝90V为例进行验证。
方案一：调节α，保持β不变
α＝60°   (13)
β(t)＝2arcsin(sinωt)   (14)
Figure PCTCN2019103793-appb-000016
β(t)与γ(t)波形如图15所示，周期均为100Hz，线性变化呈现低频脉动。
理论与仿真结果如表3所示，输出电压90V理论与仿真基本相符，且原副边电流包络线基本一致，证明可以按方案一进行功率调节，理论推导正确。
表3
  I 1max/A I 2max/A V O/V
理论 3.3 5.7 90
仿真 3.6 5.7 91
电网侧输入电压与电流如图16所示，功率因数为0.982；经过不控整流电路后，电压v in与电流i in如图17所示，均呈现100Hz脉动。逆变器输出电压电流如图18所示，副边整流器入端电压V 2与电流i 2如图19所示，电压电流均同相位。原副边线圈电流i 1,i 2如图20所示。经有源整流后，电流波形i 3如图21所示，呈现脉动形式，输出电压如图22，输出电压均值为92V，纹波峰峰值占比1.64％。
方案二：调节β，保持α不变
α＝180°   (16)
Figure PCTCN2019103793-appb-000017
Figure PCTCN2019103793-appb-000018
β(t)与γ(t)波形如图23所示，周期均为100Hz，近似正弦变化呈现低频脉动。
理论与仿真结果如表4所示，输出电压90V理论与仿真基本相符，且原副边电流包络线基本一致，证明可以按方案二进行功率调节，理论推导正确。
表4
  I 1max/A I 2max/A Vo/V
理论 1.7 11.4 90
仿真 2 11.3 91
电网侧输入电压与电流如图24所示，功率因数为0.986；经过不控整流电路后，电压v in与电流i in如图25所示，其中85kHz电流i in电流呈现出100Hz脉动。逆变器输出电压电流如图26所示，电压电流同相位。副边整流器入端电压V 2与电流i 2如图27所示，电压电流同相位。原副边线圈电流i 1,i 2如图28所示。经有源整流后，电流波形i 3如图29所示，呈 现脉动形式，输出电压如图30，输出电压均值为91V，纹波峰峰值占比1.65％。
方案三：调节α，调节β
α＝120°   (19)
Figure PCTCN2019103793-appb-000019
Figure PCTCN2019103793-appb-000020
β(t)与γ(t)波形如图31所示，周期均为100Hz，近似正弦变化且呈现低频脉动。
理论与仿真结果如表5所示，输出电压90V理论与仿真基本相符，且原副边电流包络线基本一致，证明可以按方案三进行功率调节，理论推导正确。
表5
  I 1max/A I 2max/A V O/V
理论 1.9 9.9 90
仿真 2.2 9.8 92
电网侧输入电压与电流如图32所示，功率因数为0.987；经过不控整流电路后，电压v in与电流i in如图33所示，其中85kHz电流i in电流呈现出100Hz脉动。逆变器输出电压电流如图34所示，逆变输出电压V 1与电流i 1均呈现100Hz脉动，且调制频率为85kHz，电压电流同相位。副边整流器入端电压V 2与电流i 2如图35所示，均呈现100Hz脉动，且调制频率为85kHz，电压V 2移相角实时调制变化，电压电流同相位。原副边线圈电流i 1,i 2如图36所示。经有源整流后，电流波形i 3如图37所示，呈现脉动形式，输出电压如图38，输出电压均值为92V。

Claims (2)

  1. 通过副边调制实现PFC的无线电能传输系统，其特征在于，该系统在传统无线充电系统拓扑的基础上，去除传统PFC电路，使电网电压经过不控整流成100Hz电压直接给无线充电系统的原边逆变器供电，副边采用有源全桥整流结构，仅通过副边调制实现PFC功能。
  2. 根据权利要求1所述的通过副边调制实现PFC的无线电能传输系统，其特征在于，通过副边调制实现PFC功能具体为：
    该系统中控制自由度共有3个，依次为原边逆变器移相角α、副边整流器移相角β、副边整流器第一个桥臂上管的控制电压u gs5超前原边逆变器第一个桥臂上管的控制电压u gs1的相位角γ；
    给定原边移相角α，按下式调控副边移相角β：
    Figure PCTCN2019103793-appb-100001
    其中，V O为输出直流电压，R L为输出端等效负载电阻，ω 0＝2πf 0＝2π·85kHz为系统谐振角频率，ω＝2πf＝2π·50Hz为电网电压角频率，M为原副边线圈互感值；
    按下式调控相位角γ：
    Figure PCTCN2019103793-appb-100002
    在此条件下，原边整流桥输入电流的50Hz谐波与输入电压同相，经过EMI滤波器后，实现网侧电压电流功率因数接近1。
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