WO2020177605A1 - 一种微型双频威尔金森功分器 - Google Patents

一种微型双频威尔金森功分器 Download PDF

Info

Publication number
WO2020177605A1
WO2020177605A1 PCT/CN2020/076904 CN2020076904W WO2020177605A1 WO 2020177605 A1 WO2020177605 A1 WO 2020177605A1 CN 2020076904 W CN2020076904 W CN 2020076904W WO 2020177605 A1 WO2020177605 A1 WO 2020177605A1
Authority
WO
WIPO (PCT)
Prior art keywords
transmission line
microstrip transmission
output
coplanar waveguide
input
Prior art date
Application number
PCT/CN2020/076904
Other languages
English (en)
French (fr)
Inventor
钟国麟
李言胜
刘瑞琦
王萌
Original Assignee
青岛理工大学
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 青岛理工大学 filed Critical 青岛理工大学
Publication of WO2020177605A1 publication Critical patent/WO2020177605A1/zh

Links

Images

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port

Definitions

  • the invention relates to an electronic device for transmitting and receiving signals in the field of communication and radar, in particular to a miniature dual-frequency Wilkinson power divider.
  • the traditional power splitter can be divided into three types: branch line directional coupler, Wilkinson power splitter and two-wire two-way splitter.
  • the branch line directional coupler has the disadvantages of narrow frequency band and high output loss. Wide but no output isolation.
  • the Wilkinson power divider has obvious advantages due to its bandwidth, low output loss, output isolation and in-phase output.
  • the traditional Wilkinson power splitter inevitably needs to use two quarter-wavelength ( ⁇ /4) microstrip transmission lines, which leads to a larger size of the power splitter, which limits the Wilkinson power splitter to a certain extent. Miniaturized applications.
  • the present invention provides a miniature dual-frequency Wilkinson power divider, which can effectively solve the problem of excessively large Wilkinson power dividers in the prior art.
  • a miniature dual-frequency Wilkinson power splitter including a dielectric plate, a first transmission group, a second transmission group, an input microstrip transmission line and an isolation resistor, the input microstrip
  • the tape transmission line is pasted on the top layer of the dielectric board, its input end is connected to the input interface, and its output end is divided into two parallel ends for connecting to the first and second transmission groups respectively;
  • the structure of the first transmission group and The structure of the second transmission group is arranged axisymmetrically with the horizontal central axis of the dielectric plate;
  • the first transmission group includes a coplanar waveguide transmission line pasted on the bottom layer of the dielectric plate, and an output microstrip transmission line pasted on the top layer of the dielectric plate and the middle
  • the end microstrip transmission line, the shape of the middle end microstrip transmission line is the same as the shape of the coplanar waveguide transmission line, and the center lines of the two are aligned up and down.
  • the input end A of the coplanar waveguide transmission line is conducted through a metal through a dielectric plate
  • the hole A is upwardly connected to the output end of the input microstrip transmission line.
  • the coplanar waveguide transmission line starts from the input end A and turns inward to the output end A of the coplanar waveguide transmission line.
  • the output end A passes through a penetrating dielectric plate
  • the metal conductive via B is upwardly connected to the input end B of the mid-end microstrip transmission line, and the mid-end microstrip transmission line starts from the input end B and turns outward to the output end B of the mid-end microstrip transmission line.
  • the end of the output end B is connected to the input end of the output microstrip transmission line, the output end of the output microstrip transmission line is connected to the output interface, and the isolation resistance is arranged at the output end B of the first transmission group and the output end of the second transmission group. Between output B.
  • spiral turning angle of the mid-end microstrip transmission line and the spiral turning angle of the coplanar waveguide transmission line are both 90°.
  • the mid-end microstrip transmission line forms 7 line segments from the input end B to the output end B through a spiral and twisting, and the distances between the center lines of two parallel and adjacent line segments are equal.
  • the output microstrip transmission line in the first transmission group and the output terminal B form a 90° turning angle and extend in a direction away from the second transmission group.
  • the resistance value of the isolation resistor is 100 ⁇ .
  • the width W2 of the middle-end microstrip transmission line is changed.
  • the width S1 of the central conductor strip of the coplanar waveguide transmission line and the slit width S2 is changed.
  • width W3 of the output microstrip transmission line is wider than the width W2 of the middle end microstrip transmission line.
  • metal conductive via A and the metal conductive via B are both vertically arranged through the dielectric plate.
  • the present invention has the following beneficial effects: the present invention arranges the mid-end microstrip transmission line and the coplanar waveguide transmission line that have the same shape and adopts a spiral and twisting structure on the top and bottom layers of the dielectric plate, and connects the two in series through metal conductive vias. It is a structural layout form of a transmission line, which makes full use of the area of the dielectric plate. It is easy to obtain good performance parameters by adjusting the size of the transmission line, and realizes the ultra-miniaturization of the Wilson power splitter circuit. Microwave/RF components realize miniaturized circuit size or PCB board area.
  • Figure 1 is a schematic diagram of the top-level structure of an embodiment provided by the present invention.
  • Figure 2 is an enlarged schematic diagram of the structure of part A in Figure 1;
  • Figure 3 is a schematic diagram of the underlying structure of an embodiment provided by the present invention.
  • Fig. 4 is an enlarged schematic diagram of the structure of part B in Fig. 3;
  • Figure 5 is a partial longitudinal sectional view of an embodiment of the present invention.
  • FIG. 6 is a schematic diagram of S parameter simulation of an embodiment provided by the present invention.
  • Dielectric board Dielectric board 2. First transmission group 3. Second transmission group 4. Input microstrip transmission line 5. Isolation resistance 61, input interface 62, output interface 7, coplanar waveguide transmission line 71, input terminal A 72, Output terminal A 8, output microstrip transmission line 9, mid-end microstrip transmission line 91, input terminal B 92, output terminal B 10, metal conductive via A 11, and metal conductive via B.
  • the miniature dual-frequency Wilkinson power divider of the present invention includes a dielectric plate 1, a first transmission group 2, a second transmission group 3, an input microstrip transmission line 4 and an isolation Resistor 5.
  • the input microstrip transmission line 4 is pasted on the top layer of the dielectric board 1, its input end is connected to the input interface 61, and its output end is divided into two parallel ends for connecting to the first and second transmission groups respectively
  • the structure of the first transmission group 2 and the structure of the second transmission group 3 are arranged axisymmetrically with the horizontal central axis of the dielectric plate 1;
  • the first transmission group 2 includes a coplanar waveguide attached to the bottom layer of the dielectric plate 1
  • the transmission line 7 and the output microstrip transmission line 8 and the middle end microstrip transmission line 9 attached to the top layer of the dielectric board 1, the shape of the middle end microstrip transmission line 9 and the shape of the coplanar waveguide transmission line 7 are the same, and the center line of the two is up and down Aligned, the input end A
  • the coplanar waveguide transmission line 7 starts from the input end A71.
  • the inner circle turns to the output end A72 of the coplanar waveguide transmission line 7.
  • the output end A72 is upwardly connected to the input end B91 of the mid-end microstrip transmission line 9 through a metal conductive via B11 that penetrates the dielectric plate.
  • the belt transmission line 9 starts from the input end B91 and turns outward to the output end B92 of the mid-end microstrip transmission line 9.
  • the end of the output end B92 is connected to the input end of the output microstrip transmission line 8.
  • the output terminal of the transmission line 8 is connected to the output interface 62, and the isolation resistor 5 is arranged between the output terminal B92 of the first transmission group 2 and the output terminal B92 of the second transmission group 3.
  • the ground metal plate in the microstrip transmission line structure is changed to a coplanar waveguide transmission line
  • the ground metal plate of the coplanar waveguide transmission line 7 serves as the connection between the microstrip transmission lines on the top layer of the dielectric plate 1 and the coplanar waveguide transmission line 7. floor.
  • the respective coplanar waveguide transmission lines 7 in the first and second transmission groups are connected in series with the middle-end microstrip transmission line 9 through the metal conductive via B11 to form a transmission line.
  • the upper and lower center lines of the coplanar waveguide transmission line 7 and the middle-end microstrip transmission line 9 are aligned,
  • the length is increased from the inside to the outside through the way of turning and turning.
  • the area of the dielectric plate 1 is fully utilized, and the ultra-miniaturization of the power divider circuit is realized.
  • the structure is simple, the yield is high, and the batch Good consistency and low cost.
  • spiral turning angle of the mid-end microstrip transmission line 9 and the spiral turning angle of the coplanar waveguide transmission line 7 are both 90°.
  • each of the mid-end microstrip transmission lines 9 forms 7 line segments from the input terminal B91 to the output terminal B92 after being twisted and turned, and the distances between the center lines of two parallel and adjacent line segments are equal.
  • the output microstrip transmission line 8 in the first transmission group 2 and the output terminal B92 form a turning angle of 90° and extend in a direction away from the second transmission group 3.
  • the resistance value of the isolation resistor 5 is 100 ⁇ .
  • the width W2 of the middle-end microstrip transmission line 9 the width S1 of the central conductor strip of the coplanar waveguide transmission line 7, and the slit width S2
  • the impedance of the middle-end microstrip transmission line 9 and the impedance of the coplanar waveguide transmission line 7 are changed. impedance.
  • width W3 of the output microstrip transmission line 8 is wider than the width W2 of the middle end microstrip transmission line 9.
  • metal conductive via A10 and the metal conductive via B11 are both vertically arranged through the dielectric plate 1.
  • the respective coplanar waveguide transmission lines 7 in the first and second transmission groups are connected in series with the mid-end microstrip transmission line 9 through the metal conductive via B11 to form a transmission line.
  • the mid-end, input and output microstrip transmission lines are connected to the coplanar waveguide.
  • the top and bottom transmission lines of the micro dual-frequency Wilkinson power divider are in the mid-end microstrip transmission line 9
  • the impedance of and the impedance of the coplanar waveguide transmission line 7 are both 70.7 ⁇ ; the process of obtaining the required impedance is obtained through parameter optimization and adjustment.
  • the dielectric plate 1 in this embodiment can be a rectangular Rogers4003c dielectric plate with a thickness of 0.305mm, a relative dielectric constant of 3.55, and a size of 9.1mm ⁇ 5.4mm.
  • the microstrip transmission line and the coplanar waveguide transmission line in the top and bottom layers are used
  • the thickness of the copper skin is 0.035mm;
  • the diameter D1 of the metal conductive via A10 is 0.1mm,
  • the diameter D2 of the metal conductive via B11 is 0.05mm,
  • the length L1 of the input microstrip transmission line 4 is 0.5mm, and the middle end microstrip transmission line 9
  • the sequence is set as follows: the length of the center line of the first section (that is, the innermost line section of the mid-end microstrip transmission line 9 that is twisted and twisted) is 4.48mm, the centerline of the second section is 5.05mm, and the centerline of the third section Length 5.69mm, the length of the center line of the fourth section is 5.81mm, the gap width W4 between the two adjacent sections of the above four sections is 0.2mm, the width W1 of the input microstrip transmission line section 4 is 0.7mm, the middle end microstrip The width W2 of the transmission line segment 9 is 0.44 mm, the width W3 of the output microstrip transmission line segment is 0.7 mm, the width S1 of the central conduction band of the coplanar waveguide transmission line 7 is 0.1 mm, and the slit width S2 is 0.05 mm.
  • the power divider in this embodiment has an input interface 61 and two output interfaces 62.
  • the miniature dual-frequency Wilkinson power divider can transfer the signal input from the input port 61
  • a miniaturized circuit size or PCB board area can be achieved for various microwave/RF components at a lower frequency.
  • the twisted mid-end microstrip transmission line 9 and the coplanar waveguide transmission line 7 aligned with the center line gradually increase in length from the inside to the outside, so as to make full use of the area of the dielectric plate 1 and realize the ultra-small power divider circuit ⁇ .

Landscapes

  • Waveguides (AREA)

Abstract

本发明涉及一种通信和雷达领域收发信号的电子器件，尤其涉及一种微型双频威尔金森功分器，包括介质板，输入微带传输线贴覆于介质板的顶层，其输出端分别与结构呈轴对称设置的第一、二传输组相连；第一传输组包括串联于一起的贴覆于介质板底层的共面波导传输线以及贴覆于介质板顶层的输出微带传输线和中端微带传输线，中端微带传输线的形状和共面波导传输线的形状相同且两者的中心线上下对齐，共面波导传输线的输入端A与输入微带传输线相连，其以输入端A为起点向内盘旋折转至输出端A，并通过金属导电过孔B与中端微带传输线相连，中端微带传输线通过输出微带传输线连接至输出接口。本发明能有效解决现有技术中威尔金森功分器体积过大的问题。

Description

一种微型双频威尔金森功分器 技术领域
本发明涉及一种通信和雷达领域收发信号的电子器件，尤其涉及一种微型双频威尔金森功分器。
背景技术
随着多路射频技术的快速发展，元件和馈电电路在无线电子通信行业中发挥着非常重要的作用，天线阵列、混频器、移相器等对低成本、小体积的功分器有很高的需求。传统的功分器可以分为分支线定向耦合器、威尔金森功分器和双线二分线三类，分支线定向耦合器存在频带窄、输出损耗高的弊病，双线二分线虽然频带较宽但没有输出隔离。与前述两类功分器不同，威尔金森功分器的频带宽、输出损耗小、存在输出隔离且为同相位输出，具有比较明显的优势。但传统的威尔金森功分器不可避免的需要使用两个四分之一波长(λ/4)微带传输线导致功分器体积较大，在一定程度上限制了威尔金森功分器的微型化应用。
发明内容
根据以上现有技术的不足，本发明提供了一种微型双频威尔金森功分器，其能有效解决现有技术中威尔金森功分器体积过大的问题。
本发明解决的技术问题采用的技术方案为：一种微型双频威尔金森功分器，包括介质板、第一传输组、第二传输组、输入微带传输线和隔离电阻，所述输入微带传输线贴覆于介质板的顶层，其输入端与输入接口相连，其输出端分为并联的两个端部用于分别与第一、二传输组相连；所述第一传输组的结构和第二传输组的结构以介质板的水平中心轴呈轴对称设置；所述第一传输组包括贴 覆于介质板底层的共面波导传输线以及贴覆于介质板顶层的输出微带传输线和中端微带传输线，所述中端微带传输线的形状和共面波导传输线的形状相同且两者的中心线上下对齐，所述共面波导传输线的输入端A通过一贯穿介质板的金属导电过孔A向上与输入微带传输线的输出端相连，所述共面波导传输线以输入端A为起点向内盘旋折转至共面波导传输线的输出端A，所述输出端A通过一贯穿介质板的金属导电过孔B向上与中端微带传输线的输入端B相连，所述中端微带传输线以输入端B为起点向外盘旋折转至中端微带传输线的输出端B，所述输出端B的端部与输出微带传输线的输入端相连，所述输出微带传输线的输出端与输出接口相连，所述隔离电阻设置于第一传输组的输出端B和第二传输组的输出端B之间。
进一步地，所述中端微带传输线的盘旋折转角和共面波导传输线的盘旋折转角均为90°。
进一步地，所述中端微带传输线从输入端B到输出端B之间经过盘旋折转形成了7个线段，平行且相邻的两线段的中心线之间的距离均相等。
进一步地，所述第一传输组中的输出微带传输线与输出端B构成90°的折转角，并向远离第二传输组的方向延伸。
进一步地，所述隔离电阻的阻值为100Ω。
进一步地，通过调整所述中端微带传输线的宽度W2、共面波导传输线的中心导体带的宽度S1和缝隙宽度S2以改变中端微带传输线的阻抗及共面波导传输线的阻抗。
进一步地，所述输出微带传输线的宽度W3比中端微带传输线的宽度W2宽。
进一步地，所述金属导电过孔A和金属导电过孔B均垂直贯穿介质板设置。
本发明具有以下有益效果：本发明通过将形状相同的均采用盘旋折转结构的中端微带传输线与共面波导传输线分别布置于介质板的顶层和底层，并通过金属导电过孔将两者串联为一条传输线的结构布局形式，充分利用了介质板的面积，通过调整传输线尺寸容易获得良好的性能参数，实现了威尔森功分器电路的超小型化，能够在较低频率下为各种微波/射频元件实现微型化的电路尺寸或PCB板面积。
附图说明
图1是本发明所提供实施例的顶层结构示意图；
图2是图1中A部分的结构放大示意图；
图3是本发明所提供实施例的底层结构示意图；
图4是图3中B部分的结构放大示意图；
图5是本发明所提供实施例的部分纵向剖视示意图；
图6是本发明所提供实施例的S参数模拟示意图；
图中：1、介质板 2、第一传输组 3、第二传输组 4、输入微带传输线 5、隔离电阻 61、输入接口 62、输出接口 7、共面波导传输线 71、输入端A 72、输出端A 8、输出微带传输线 9、中端微带传输线 91、输入端B 92、输出端B 10、金属导电过孔A 11、金属导电过孔B。
具体实施方式
下面结合附图对本发明做进一步描述。
实施例一：
如图1～图6所示，本发明所述的一种微型双频威尔金森功分器，包括介质板1、第一传输组2、第二传输组3、输入微带传输线4和隔离电阻5，所述输入微带传输线4贴覆于介质板1的顶层，其输入端与输入接口61相连，其输出 端分为并联的两个端部用于分别与第一、二传输组相连；所述第一传输组2的结构和第二传输组3的结构以介质板1的水平中心轴呈轴对称设置；所述第一传输组2包括贴覆于介质板1底层的共面波导传输线7以及贴覆于介质板1顶层的输出微带传输线8和中端微带传输线9，所述中端微带传输线9的形状和共面波导传输线7的形状相同且两者的中心线上下对齐，所述共面波导传输线7的输入端A71通过一贯穿介质板的金属导电过孔A10向上与输入微带传输线4的输出端相连，所述共面波导传输线7以输入端A71为起点向内盘旋折转至共面波导传输线7的输出端A72，所述输出端A72通过一贯穿介质板的金属导电过孔B11向上与中端微带传输线9的输入端B91相连，所述中端微带传输线9以输入端B91为起点向外盘旋折转至中端微带传输线9的输出端B92，所述输出端B92的端部与输出微带传输线8的输入端相连，所述输出微带传输线8的输出端与输出接口62相连，所述隔离电阻5设置于第一传输组2的输出端B92和第二传输组3的输出端B92之间。
在本实施例中，将微带传输线结构中的接地金属板改为了共面波导传输线，共面波导传输线7的接地金属板作为介质板1顶层的各个微带传输线和共面波导传输线7的接地板。第一、二传输组中各自的共面波导传输线7通过金属导电过孔B11与中端微带传输线9串联为一条传输线，共面波导传输线7和中端微带传输线9的上下中心线对齐，并且通过盘旋折转的方式从内到外增加了长度，与现有技术相比，充分利用了介质板1的面积，实现了功分器电路的超小型化，结构简单、成品率高，批量一致性好，造价低廉。
进一步地，所述中端微带传输线9的盘旋折转角和共面波导传输线7的盘旋折转角均为90°。
进一步地，每个所述中端微带传输线9从输入端B91到输出端B92之间经 过盘旋折转形成了7个线段，平行且相邻的两线段的中心线之间的距离均相等。
进一步地，所述第一传输组2中的输出微带传输线8与输出端B92构成90°的折转角，并向远离第二传输组3的方向延伸。
进一步地，所述隔离电阻5的阻值为100Ω。
进一步地，通过调整所述中端微带传输线9的宽度W2、共面波导传输线7的中心导体带的宽度S1和缝隙宽度S2以改变中端微带传输线9的阻抗及共面波导传输线7的阻抗。
进一步地，所述输出微带传输线8的宽度W3比中端微带传输线9的宽度W2宽。
进一步地，所述金属导电过孔A10和金属导电过孔B11均垂直贯穿介质板1设置。
在一个实施例中，第一、二传输组中各自的共面波导传输线7通过金属导电过孔B11与中端微带传输线9串联为一条传输线，中端、输入和输出微带传输线与共面波导传输线7之间存在耦合作用，通过调节输入微带传输线4与输入接口61连接处的微带传输线的宽度W1，使端口与阻抗匹配为50Ω，通过调节输出微带传输线8的宽度W3，使端口阻抗匹配为50Ω；
通过调节中端微带传输线9的宽度W2、共面波导传输线7的中心导体带的宽度S1和缝隙宽度S2使微型双频威尔金森功分器的顶、底层传输线在中端微带传输线9的阻抗和共面波导传输线7的阻抗均为70.7Ω；得到所需阻抗的过程是通过参数优化调整得出。
本实施例中的介质板1可以是厚度为0.305mm、相对介电常数为3.55、尺寸为9.1mm×5.4mm的矩形Rogers4003c介质板，顶层和底层中微带传输线和共面波导传输线所使用的铜皮选用厚度为0.035mm；金属导电过孔A10的直径D1 为0.1mm，金属导电过孔B11的直径D2为0.05mm，输入微带传输线4的长度L1为0.5mm，中端微带传输线9通过盘旋折转共具有7个线段，其中与介质板1的水平中心轴线相平行的线段有4个，并且从内向外该四段传输线的长度依次增加，按长度由最内侧的最短的线段开始依次设置如下：第一段(即盘旋折转的中端微带传输线9的最内部的一个线段)的中心线长4.48mm，第二段的中心线长为5.05mm，第三段的中心线长5.69mm，第四段的中心线长为5.81mm，上述四段的相邻两段之间的空隙宽度W4为0.2mm，输入微带传输线段4的宽度W1为0.7mm，中端微带传输线段9的宽度W2为0.44mm，输出微带传输线段的宽度W3为0.7mm，共面波导传输线7的中心导带的宽度S1为0.1mm，缝隙宽度S2为0.05mm。
本实施例中的功分器具有一个输入接口61和两个输出接口62，图6为使用HFSS仿真软件模拟微型双频威尔金森功分器的S参数仿真结果，其中模拟的频段1为0.7GHz-1.1GHz，中心频率为0.9GHz，中心频率对应插入损耗为S12＝-3.06dB，S13＝-3.06dB，可见，所述微型双频威尔金森功分器可将输入端口61输入的信号能量分成能量相等的两路，分别输出到第一传输组2和第二传输组3的输出端口62，回波损耗为S11＝-19.65dB，S22＝-21.73dB，S33＝-21.42dB，可见，所述微型双频威尔金森功分器的回波损耗较低，隔离度S32＝-24.01dB；模拟的回波损耗大于-15dB的工作频段从0.7GHz到1.1GHz；频段2为2.6GHz-3GHz，中心频率为2.8GHz，中心频率对应插入损耗为S12＝-3.02dB，S13＝-3.04dB，回波损耗为S11＝-24.71dB，S22＝-25.66dB，S33＝-25.47dB，隔离S32＝-26.57dB；模拟的回波损耗大于-15dB的工作频段从2.6GHz到3GHz。
利用这种微型化技术，可以在较低的频率下为各种微波/射频元件实现微型化的电路尺寸或PCB板的面积。盘旋折转的中端微带传输线9和与之中心线对 齐的共面波导传输线7从内到外逐渐增加长度，以此来充分利用介质板1的面积，实现了功分器电路的超小型化。
以上所述为本发明的实施例，并非因此限制本发明的专利范围，凡是利用本发明说明书以及附图内容所作的等效结构或等效流程变换，或直接或间接运用在其他相关的技术领域，均同理包括在本发明的专利保护范围内。

Claims (8)

  1. 一种微型双频威尔金森功分器，其特征在于：包括介质板、第一传输组、第二传输组、输入微带传输线和隔离电阻，所述输入微带传输线贴覆于介质板的顶层，其输入端与输入接口相连，其输出端分为并联的两个端部用于分别与第一、二传输组相连；所述第一传输组的结构和第二传输组的结构以介质板的水平中心轴呈轴对称设置；所述第一传输组包括贴覆于介质板底层的共面波导传输线以及贴覆于介质板顶层的输出微带传输线和中端微带传输线，所述中端微带传输线的形状和共面波导传输线的形状相同且两者的中心线上下对齐，所述共面波导传输线的输入端A通过一贯穿介质板的金属导电过孔A向上与输入微带传输线的输出端相连，所述共面波导传输线以输入端A为起点向内盘旋折转至共面波导传输线的输出端A，所述输出端A通过一贯穿介质板的金属导电过孔B向上与中端微带传输线的输入端B相连，所述中端微带传输线以输入端B为起点向外盘旋折转至中端微带传输线的输出端B，所述输出端B的端部与输出微带传输线的输入端相连，所述输出微带传输线的输出端与输出接口相连，所述隔离电阻设置于第一传输组的输出端B和第二传输组的输出端B之间。
  2. 根据权利要求1所述的微型双频威尔金森功分器，其特征在于：所述中端微带传输线的盘旋折转角和共面波导传输线的盘旋折转角均为90°。
  3. 根据权利要求2所述的微型双频威尔金森功分器，其特征在于：每个所述中端微带传输线从输入端B到输出端B之间经过盘旋折转形成了7个线段，平行且相邻的两线段的中心线之间的距离均相等。
  4. 根据权利要求3所述的微型双频威尔金森功分器，其特征在于：所述第一传输组中的输出微带传输线与输出端B构成90°的折转角，并向远离第二传输组的方向延伸。
  5. 根据权利要求4所述的微型双频威尔金森功分器，其特征在于：所述隔 离电阻的阻值为100Ω。
  6. 根据权利要求1所述的微型双频威尔金森功分器，其特征在于：通过调整所述中端微带传输线的宽度W2、共面波导传输线的中心导体带的宽度S1和缝隙宽度S2以改变中端微带传输线的阻抗及共面波导传输线的阻抗。
  7. 根据权利要求1所述的微型双频威尔金森功分器，其特征在于：所述输出微带传输线的宽度W3比中端微带传输线的宽度W2宽。
  8. 根据权利要求1所述的微型双频威尔金森功分器，其特征在于：所述金属导电过孔A和金属导电过孔B均垂直贯穿介质板设置。
PCT/CN2020/076904 2019-03-01 2020-02-27 一种微型双频威尔金森功分器 WO2020177605A1 (zh)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CN201910156341.0 2019-03-01
CN201910156341.0A CN109904577A (zh) 2019-03-01 2019-03-01 一种微型双频威尔金森功分器

Publications (1)

Publication Number Publication Date
WO2020177605A1 true WO2020177605A1 (zh) 2020-09-10

Family

ID=66946055

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/CN2020/076904 WO2020177605A1 (zh) 2019-03-01 2020-02-27 一种微型双频威尔金森功分器

Country Status (2)

Country Link
CN (1) CN109904577A (zh)
WO (1) WO2020177605A1 (zh)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN109904577A (zh) * 2019-03-01 2019-06-18 青岛理工大学 一种微型双频威尔金森功分器

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070046393A1 (en) * 2005-09-01 2007-03-01 Clifton Quan Power divider
CN104051822A (zh) * 2014-05-28 2014-09-17 西安电子科技大学 一种用于四臂螺旋天线馈电的功分移相器
CN108232397A (zh) * 2018-03-26 2018-06-29 青岛理工大学 一种小型化功分器
CN109904577A (zh) * 2019-03-01 2019-06-18 青岛理工大学 一种微型双频威尔金森功分器

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20070046393A1 (en) * 2005-09-01 2007-03-01 Clifton Quan Power divider
CN104051822A (zh) * 2014-05-28 2014-09-17 西安电子科技大学 一种用于四臂螺旋天线馈电的功分移相器
CN108232397A (zh) * 2018-03-26 2018-06-29 青岛理工大学 一种小型化功分器
CN109904577A (zh) * 2019-03-01 2019-06-18 青岛理工大学 一种微型双频威尔金森功分器

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
陈彦斌等 (CHEN, YANBIN ET AL.): "在射频识别中双频功分器的设计 (Non-official translation: Design of Dual Frequency Power Divider in RFID)", 材料导报 (MATERIALS REVIEW), vol. 21, no. 11A, 30 November 2007 (2007-11-30), XP55731999, DOI: 20200515171505A *

Also Published As

Publication number Publication date
CN109904577A (zh) 2019-06-18

Similar Documents

Publication Publication Date Title
CN102763269B (zh) 使用衬底集成波导的移相器
US7307493B2 (en) Broadband 180° degree hybrid microwave planar transformer
CN103022616B (zh) 基于低温共烧陶瓷技术的双频四路功率分配器
JP6280985B2 (ja) セルラー用途向けの小型無線方向性結合器
CN110994107B (zh) 基于交叉型复合左右手传输线的共面波导双频功分器
US9154105B2 (en) Dual-band microstrip-to-slotline transition circuit
CN112864549B (zh) 一种新型多路宽带小型化差分移相器
CN108448221B (zh) 一种宽带多层微带Butler波束成形网络矩阵装置
CN105789802A (zh) 一种基于新型互联结构的超宽带巴伦
EP0984504B1 (en) Transverse electric or quasi-transverse electric mode to waveguide mode transformer
CN109802213A (zh) 一种3dB三端口90度平面电桥
WO2020177605A1 (zh) 一种微型双频威尔金森功分器
CN214153150U (zh) 蟹形双频带负群时延电路
CN108091973B (zh) 一种小型化宽带功分网络
CN111525222B (zh) 基于交叉型慢波传输线的小型化共面波导等分功分器
CN113193322A (zh) 一种改进型威尔金森功分器
CN115548615B (zh) 基于巴伦的人工表面等离激元片上双模传输线
CN215869737U (zh) 一种基于ipd的高平衡度宽带巴伦
CN114171872B (zh) 一种宽带小型化毫米波双通道交叉电桥
CN113764851B (zh) 基于ipd的小型化低插损宽带巴伦
CN113224494B (zh) 基于微带-槽线耦合线的双频带功率不等分定向耦合器
CN210379359U (zh) 新型90°宽带差分移相器
CN105932387A (zh) 一种基于siw的双结环行器
Wu et al. Analysis and design of compact planar crossover
CN111262027A (zh) 小型化宽带正交馈电网络

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 20765497

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 20765497

Country of ref document: EP

Kind code of ref document: A1