WO2020177341A1 - 一种低剖面双极化滤波磁电偶极子天线 - Google Patents

一种低剖面双极化滤波磁电偶极子天线 Download PDF

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Publication number
WO2020177341A1
WO2020177341A1 PCT/CN2019/113146 CN2019113146W WO2020177341A1 WO 2020177341 A1 WO2020177341 A1 WO 2020177341A1 CN 2019113146 W CN2019113146 W CN 2019113146W WO 2020177341 A1 WO2020177341 A1 WO 2020177341A1
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Prior art keywords
dielectric substrate
shaped
slot
low
dipole antenna
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PCT/CN2019/113146
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English (en)
French (fr)
Inventor
章秀银
杨圣杰
张志杰
潘咏梅
曹云飞
张垚
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华南理工大学
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Priority to US17/046,315 priority Critical patent/US11296418B2/en
Publication of WO2020177341A1 publication Critical patent/WO2020177341A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/16—Resonant antennas with feed intermediate between the extremities of the antenna, e.g. centre-fed dipole
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H01Q21/26—Turnstile or like antennas comprising arrangements of three or more elongated elements disposed radially and symmetrically in a horizontal plane about a common centre
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors

Definitions

  • the invention relates to the field of radio frequency communication, in particular to a low-profile dual-polarization filtering magnetoelectric dipole antenna.
  • Wong and Luk invented a new complementary antenna called a magnetoelectric dipole, which combines a short patch antenna and an electric dipole.
  • This antenna has the advantages of wide bandwidth, high directivity, low cross-polarization, low backlobe radiation, etc.
  • due to the large thickness of the magnetoelectric dipole about 0.25 ⁇ 0 , it is inconvenient to use in many applications.
  • the design of filter antennas can be roughly divided into the following categories.
  • the first design is to design the filter and the antenna feed part together or to simply cascade the filter and the traditional antenna through an impedance converter.
  • the second design It is to cut holes in the patch antenna or add a metal probe to combine to make the radiator itself have filtering characteristics.
  • the third design is to add a non-radiative parasitic structure to make the antenna's radiation filter effect.
  • the low-profile dipole antenna in the prior art is realized by using two orthogonal H-shaped feeders and a laminated patch.
  • the antenna has a lower profile, only 0.09 wavelength, but a narrow bandwidth. Only 11%.
  • the present invention provides a low-profile dual-polarization filter magnetoelectric dipole antenna.
  • the radiation performance of the antenna can not only achieve high roll-off filtering characteristics and high polarization isolation, but also ensure that no additional insertion loss and redundancy are introduced.
  • the occupied area brought by the new structure can expand the bandwidth and reduce the height.
  • the present invention provides a low-profile dual-polarization filter magnetoelectric dipole antenna.
  • the radiation performance of the antenna can achieve both high roll-off filtering characteristics and high polarization isolation. , It can ensure that no additional insertion loss and the occupied area caused by the redundant structure are introduced, and the bandwidth can be expanded and the height can be reduced.
  • the invention excites the radiator structure with low profile and high selective filtering response by using the slot-coupled feed network with the fusion filtering function to produce good broadband radiation characteristics and high roll-off band-pass filtering effect.
  • a low-profile dual-polarization filter magnetoelectric dipole antenna comprising an upper dielectric substrate and a lower dielectric substrate, the upper surface of the upper dielectric substrate is printed with a radiator structure, and the lower dielectric substrate is printed with a slot-coupled feeding network structure;
  • the radiator structure includes four parasitic patches loaded with symmetrical slots, and the parasitic patches are loaded with short-circuit probes;
  • the slot-coupled feeder network structure includes two sets of orthogonally placed Y-shaped feeders and cross-shaped slots, the cross-shaped slots are printed on the metal floor, and the metal floor and the Y-shaped feeder are printed on the lower dielectric substrate. On different surfaces, the parasitic patch is connected to the metal floor through a short-circuit probe.
  • the Y-shaped feeder line includes a one-to-two power divider, and the output end of the one-to-two power divider is connected to two microstrip lines.
  • the two microstrip lines extend after passing through a cross-shaped gap, and carry out the extension part. By bending, the parasitic patch of the upper dielectric substrate is coupled through the cross-shaped gap to introduce a radiation suppression zero point.
  • the length of the extension part is the equivalent wavelength of one-half of the frequency at the zero position of the radiation suppression.
  • the symmetrical slot structure includes a rectangular slot that is diagonally symmetrical about the parasitic patch.
  • the invention also includes two through holes and an air bridge formed by a strip line, which are arranged at the intersection of the two groups of Y-shaped feeders.
  • the dipole antenna has a simple structure and low cost. It can increase the bandwidth by parasitizing a new slot structure on the radiator and at the same time can introduce a high roll-off edge filtering effect;
  • the filter antenna unit has good radiation performance in the passband, and has a bandpass filtering effect with high roll-off and good out-of-band suppression outside the passband.
  • the way to achieve filtering performance does not bring additional processing costs and is applicable Wide range, and no additional insertion loss is introduced;
  • the filter antenna unit has the characteristics of low profile, wide operating frequency and high gain, and the pattern lobe is stable in the passband, and the cross polarization is low.
  • the feed structure of the different polarization ports is almost completely symmetrical and the isolation is relatively good. high.
  • Figure 1 is a side view of the antenna structure of the present invention
  • FIG. 2 is a structural diagram of the radiator of the present invention.
  • FIG. 3 is a structural diagram of the slot-coupled feed network of the present invention.
  • 4(a) and 4(b) are schematic diagrams of the structure of the symmetrical gap of the present invention.
  • Fig. 5 is a result diagram of reflection coefficient S11-frequency when the present invention works in simulation and measurement state
  • Figure 6 is a graph of actual gain-frequency results of the present invention working in simulation and measurement states
  • Fig. 7 is a result diagram of the transmission coefficient S21-frequency of the present invention working in the simulation and measurement state.
  • a low-profile dual-polarization filter magnetoelectric dipole antenna includes two layers of an upper dielectric substrate and a lower dielectric substrate separated by a certain distance.
  • the upper surface of the upper dielectric substrate is printed with a radiator structure, so
  • the lower dielectric substrate is printed with a slot-coupled feed network structure, and a slot-coupled feed network with fusion filtering function is used to excite a radiator structure with low profile and high selective filter response, resulting in good broadband radiation characteristics and high roll-off bandpass Filtering effect.
  • the radiator structure includes four parasitic patches 3 loaded with symmetrical slots 1 and short-circuit probes 2.
  • the four parasitic patches form a rectangular structure.
  • the symmetrical slots in this embodiment are Each parasitic patch has two diagonally symmetrical gaps about the parasitic patch.
  • the parasitic patch is rectangular.
  • a short-circuit probe is set at one corner of the parasitic patch to form a new type of low-profile filter magnetoelectric
  • the four short-circuit probes in this embodiment are all set at the corners close to the center point of the upper dielectric substrate.
  • the parasitic patch is connected to the metal floor 4 through a short-circuit probe;
  • the working mode of the magnetic dipole is formed by combining the magnetic dipole mode formed by the radiation aperture of the gap between the short-circuit patches and the planar electric dipole mode of the patch, which is higher than the traditional magnetoelectric dipole antenna It can be greatly reduced, and by etching a symmetrical slot structure on the metal patch, the additional resonant mode is introduced to offset the deterioration of impedance matching caused by reducing the height of the antenna. At the same time, a radiation suppression zero point is introduced on the right side of the passband to improve the pass. Frequency selectivity with edge and out-of-band suppression.
  • Symmetrical slits can be other symmetrical different shapes, including structures with different geometric shapes hollowed out in the middle of the patch and four slits with a certain length along the four edges, which can improve the frequency selectivity of the upper edge of the passband.
  • the slot-coupled feeder network structure includes two sets of orthogonally placed Y-shaped feeders and cross-shaped slots 8.
  • the cross-shaped slots are printed on a metal floor, and the metal floor and the Y-shaped feeder
  • the wires are printed on different surfaces of the underlying dielectric substrate.
  • the metal floor is on the lower surface of the lower dielectric substrate, and the metal floor is printed with a cross-shaped gap.
  • the cross-shaped gap is symmetrical about the center of the lower dielectric substrate.
  • the Y-shaped feeder is printed on the upper surface of the lower dielectric substrate.
  • one Y-type feeder The wires are located on the left side of the lower dielectric substrate, and one is located on the lower end of the lower dielectric substrate.
  • the Y-shaped feeder line includes a one-to-two power divider, two output ends of the one-to-two power divider are connected to two microstrip lines, and the two microstrip lines are extended after passing through a cross-shaped gap vertically To a certain length and bend the extension part for miniaturization, the two microstrip lines of the two power divider at one end vertically pass through the transverse gap of the cross-shaped gap, and the other two microstrip lines pass through the cross vertically.
  • the longitudinal gap of the type gap The four extensions of the two one-to-two power dividers have the same length and the same bending treatment method.
  • the specific length of the extended part after the slit is the equivalent wavelength of one-half of the frequency at the zero position of the radiation suppression.
  • the end length of the conventional slot-coupled microstrip line is only used to adjust the antenna impedance matching, but in this embodiment, the end of the microstrip line is extended. Since the end of the microstrip line is in an open state, it is still equivalent to an open state after one-half of the equivalent wavelength to the feed gap, and the amplitude of the input current is zero, so energy cannot be coupled from the transmission line to the patch above the gap. At this frequency, a high-rejection transmission zero point will be produced.
  • the position of the radiation suppression zero point can be adjusted to the lower edge of the passband to realize the high-pass filtering characteristics of wide stopband and high roll-off. Combining the high-pass filtering characteristics of the extended feed microstrip line and the low-pass filtering characteristics of the parasitic patch loaded with the slot structure, the antenna finally achieves a good band-pass filtering performance.
  • the extended microstrip line 6 is located under the metal floor loaded with the cross-shaped gap 8. Energy is fed to the upper patch through the coupling with the gap.
  • the length of the extension of the microstrip line after passing through the gap It is the equivalent wavelength of one-half of the frequency at the zero position of the radiation suppression.
  • the air bridge 5 formed by two through holes and a strip line avoids the crossing of two orthogonal feed networks.
  • Fig. 5 to Fig. 6 it is a simulation and measurement result diagram of the reflection coefficient S11-frequency and gain curve-frequency of the dual-polarization filter dipole antenna provided by an embodiment of the present invention.
  • the impedance matching in the passband is good ,
  • the impedance bandwidth is 3.3-4.36GHz, the return loss is below -15dB;
  • the gain in the working frequency band is about 8.2dBi, both sides of the passband have high roll-off filtering characteristics, and the filtering suppression from 0-3GHz is more than 20dB ,
  • the out-of-band filtering suppression from 4.7-5.5GHz exceeds 25dB.
  • Fig. 7 it is the result of simulation and measurement of the transmission coefficient S21-frequency of the dual-polarization filter dipole antenna provided by an embodiment of the present invention.
  • the isolation of the two ports in the passband is better, and both are in- Below 25dB.
  • the dipole antenna has a simple structure and low cost. It can increase the bandwidth by parasitizing a new slot structure on the radiator and at the same time can introduce a high roll-off edge filtering effect;
  • the filter antenna unit has good radiation performance in the passband, and has a bandpass filtering effect with high roll-off and good out-of-band suppression outside the passband.
  • the way to achieve filtering performance does not bring additional processing costs and is applicable Wide range, and no additional insertion loss is introduced;
  • the filter antenna unit has the characteristics of low profile, wide working frequency and high gain, and the pattern lobe in the passband is stable, the cross polarization is low, the feed structure of different polarization ports is almost completely symmetrical and the isolation is high .
  • the embodiments provided by the present invention can adjust the size of related structures according to requirements and adapt to different frequency bands in the receiving and transmitting equipment of wireless communication systems. Due to the filtering characteristics of the present invention, it is particularly suitable for open and complex communication scenarios. At the same time, benefiting from the integration of filtering characteristics and radiation characteristics, the present invention is also suitable for the integration and integration of wireless mobile communication system equipment.

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Abstract

本发明公开了一种低剖面双极化滤波磁电偶极子天线，包括上层介质基板及下层介质基板，所述上层介质基板的上表面印刷辐射体结构，所述下层介质基板印刷缝隙耦合馈电网络结构；所述辐射体结构包括四块加载对称缝隙的寄生贴片，所述寄生贴片加载短路探针，所述缝隙耦合馈电网络结构包括两组正交放置的Y型馈电线及十字型缝隙，所述十字型缝隙印刷在金属地板上。通过在辐射体上寄生新型的缝隙结构增加带宽的同时能引入高滚降的边沿滤波效果，并结合具有滤波功能的缝隙耦合馈电网络实现良好的带通滤波特性且几乎不引入额外的插损。

Description

一种低剖面双极化滤波磁电偶极子天线 技术领域
本发明涉及射频通信领域，具体涉及一种低剖面双极化滤波磁电偶极子天线。
背景技术
近年来，现代无线通信系统的快速发展要求低剖面天线有高性能。多频带基站是移动通信的必需品，对于移动通信的要求很高，天线单元之间的强互耦导致辐射模式急剧退化。为了解决这个问题，这里有很多种典型方法，例如和全带天线阵列连接一个双工器，或者在不同阵列单元之间利用去耦网络来增强端口和端口之间的隔离。然而，这些方式要求的额外单元不可避免的增大了馈电网络的复杂性和引入了额外的插入损耗。最近，滤波天线单元被用来抑制工作在不同频带的单元间的互耦。当滤波天线单元的带外辐射也被抑制时，就不需要额外的双工器和去耦网络。2006年，Wong and Luk发明了一种新的互补天线，称为磁电偶极子，它结合了一个短贴片天线和一个电偶极子。这种天线具有宽带宽、方向性高、低交叉极化、低后瓣辐射等优点，但由于磁电偶极子的厚度较大，约为0.25λ 0，在许多应用中使用不便。
近些年来，滤波天线的设计大致可分为以下几种，第一种设计是将滤波器与天线馈电部分协同设计或者是滤波器和传统天线通过阻抗变换器简单级联，第二种设计是在贴片天线上开缝挖孔或者加金属探针结合而使辐射器本身具有滤波特性，第三种设计是通过添加非辐射的寄生结构使天线的辐射产生滤波效果。
现有技术中的低剖面偶极子天线是通过利用两个正交的H型馈电线和一个叠层贴片来实现，该天线有更低的剖面，仅为0.09波长，但带宽较窄，仅有11％。还有低剖面偶极子天线包括四个蚀刻有U形和方形缝隙的方形辐射贴片，四个矩形金属短壁，两个交叉r形馈线和一个盒形反射器，结构较为复杂，不易实现小型化；
在现有的双极化滤波偶极子天线设计中，要考虑如何扩展带宽，降低高度并实现通带边沿具有快速滚降的频率选择性和一定的带外抑制能力。此外，还要求 双极化天线单元的两个端口之间实现高极化隔离度以及天线单元具备小型化特点。
在现有的双极化滤波偶极子天线设计中，要考虑如何扩展带宽，降低高度并实现通带边沿具有快速滚降的频率选择性和一定的带外抑制能力。此外，还要求双极化天线单元的两个端口之间实现高极化隔离度以及天线单元具备小型化特点。
发明概述
技术问题
本发明提供一种低剖面双极化滤波磁电偶极子天线，该天线的辐射性能既能实现高滚降的滤波特性和高极化隔离度，又能保证不引入额外的插损以及多余的结构带来的占用面积，可以扩展带宽及降低高度。
解决了现有技术中的双极化滤波偶极子天线设计中，如何扩展带宽，降低高度并实现通带边沿具有快速滚降的频率选择性和一定的带外抑制能力的问题
问题的解决方案
技术解决方案
为了克服现有技术天线存在的缺点与不足，本发明提供一种低剖面双极化滤波磁电偶极子天线，该天线的辐射性能既能实现高滚降的滤波特性和高极化隔离度，又能保证不引入额外的插损以及多余的结构带来的占用面积，可以扩展带宽及降低高度。
本发明通过使用融合滤波功能的缝隙耦合馈电网络激励具有低剖面和高选择性滤波响应的辐射体结构，产生良好的宽带辐射特性以及高滚降的带通滤波效果。
本发明采用如下技术方案：
一种低剖面双极化滤波磁电偶极子天线，包括上层介质基板及下层介质基板，所述上层介质基板的上表面印刷辐射体结构，所述下层介质基板印刷缝隙耦合馈电网络结构；
所述辐射体结构包括四块加载对称缝隙的寄生贴片，所述寄生贴片加载短路探针；
所述缝隙耦合馈电网络结构包括两组正交放置的Y型馈电线及十字型缝隙，所述十字型缝隙印刷在金属地板上，所述金属地板与Y型馈电线印刷在下层介质基板的不同表面，所述寄生贴片通过短路探针与金属地板连接。
所述Y型馈电线包括一个一分二功分器，一分二功分器的输出端连接两路微带线，所述两路微带线经过十字型缝隙后延伸，并将延伸部分进行弯折，通过十字型缝隙耦合上层介质基板的寄生贴片，引入辐射抑制零点。
所述延伸部分的长度为该辐射抑制零点位置频率的二分之一等效波长。
所述对称缝隙结构包括关于寄生贴片对角线对称的矩形缝隙。
本发明还包括两个通孔及由带状线形成的空气桥，设置在两组Y型馈电线交叉位置。
发明的有益效果
有益效果
本发明的有益效果：
(1)该偶极子天线结构简单，成本低廉，通过在辐射体上寄生新型的缝隙结构增加带宽的同时能引入高滚降的边沿滤波效果；
(2)滤波天线单元在通带内有良好的辐射性能，通带外具有高滚降和良好的带外抑制能力的带通滤波效果，实现滤波性能的方式没有带来额外的加工成本且适用面广，并且未引入额外的插损；
(3)滤波天线单元具有低剖面，工作频带宽，高增益的特点，且在通带内方向图波瓣稳定，交叉极化低，不同极化端口的馈电结构几乎完全对称且隔离度较高。
对附图的简要说明
附图说明
图1是本发明的天线结构的侧视图；
图2是本发明的辐射体结构图；
图3是本发明的缝隙耦合馈电网络结构图；
图4(a)及图4(b)是本发明对称缝隙的结构示意图；
图5是本发明工作在仿真和测量状态的反射系数S11-频率的结果图；
图6是本发明工作在仿真和测量状态的实际增益-频率的结果图；
图7是本发明工作在仿真和测量状态的传输系数S21-频率的结果图。
发明实施例
本发明的实施方式
下面结合实施例及附图，对本发明作进一步地详细说明，但本发明的实施方式不限于此。
实施例
如图1所示，一种低剖面双极化滤波磁电偶极子天线，包括两层间隔一定距离的上层介质基板及下层介质基板，所述上层介质基板的上表面印刷辐射体结构，所述下层介质基板印刷缝隙耦合馈电网络结构，使用融合滤波功能的缝隙耦合馈电网络激励具有低剖面和高选择性滤波响应的辐射体结构，产生良好的宽带辐射特性以及高滚降的带通滤波效果。
如图2所示，所述辐射体结构包括四块加载对称缝隙1及短路探针2的寄生贴片3，所述四块寄生贴片构成一个矩形结构，本实施例中的对称缝隙为在每一块寄生贴片上，开有两条关于寄生贴片对角线对称的缝隙，寄生贴片为矩形，在寄生贴片的一个角设置短路探针，形成一种新型的低剖面滤波磁电偶极子天线，本实施例中的四个短路探针均设置在靠近上层介质基板中心点的角上。所述寄生贴片通过短路探针与金属地板4连接；
通过将短路贴片之间缝隙辐射口径形成的磁偶极子模式以及贴片的平面电偶极子模式结合形成的磁电偶极子工作模式，其高度相较于传统磁电偶极子天线可以大幅度降低，且通过在金属贴片上蚀刻对称的缝隙结构，引入的额外谐振模式来抵消由降低天线高度带来的阻抗匹配恶化的同时在通带右侧引入一个辐射抑制零点，提高通带边沿的频率选择性和带外抑制。
如图4(a)及图4(b)所示，是本发明所述的寄生贴片上加载的其他不同形状缺陷结构的一个样本案例。
对称缝隙可以为其他具有对称的不同形状，包括在贴片中间挖空不同几何形状的结构以及四周边沿切开四道一定长度的缝隙，均能改善通带上侧边沿的频率选择性。
如图3所示，所述缝隙耦合馈电网络结构包括两组正交放置的Y型馈电线及十字型缝隙8，所述十字型缝隙印刷在金属地板上，所述金属地板与Y型馈电线印刷在下层介质基板的不同表面。本实施例中金属地板在下层介质基板的下表面，金属地板上印刷十字型缝隙，十字型缝隙关于下层介质基板中心点对称，所述Y型馈电线印刷在下层介质基板的上表面。
所述两组正交放置的Y型馈电线7，一组Y型馈电线位于下层介质基板的一侧，另一组Y型馈电线位于下层介质基板的一端，本实施例中一个Y型馈电线位于下层介质基板的左侧，一个位于下层介质基板的下端。所述Y型馈电线包括一个一分二功分器，所述一分二功分器的两个输出端连接两路微带线，所述两路微带线垂直经过十字型缝隙后被延伸至一定的长度，并将延伸部分弯折以小型化处理，所述位于一端的二功分器的两路微带线垂直经过十字型缝隙的横向缝隙，另外的两条微带线垂直经过十字型缝隙的纵向缝隙。两个一分二功分器的四个延伸部分长度相同，弯折处理方式相同，其通过上层中间位置的十字型缝隙耦合上层的寄生贴片，能引入一个辐射抑制零点，且微带线经过缝隙后的延长部分具体长度为该辐射抑制零点位置频率的二分之一等效波长，其产生滤波效果的原理如下：
传统缝隙耦合的微带线末端长度只是用来调天线阻抗匹配，而在本实施例中将微带线末端延长。由于微带线末端是开路状态，经过二分之一等效波长至馈电缝隙处仍然等效为开路状态，输入电流的幅值为零，因而能量无法从传输线耦合至缝隙上方的贴片，在该频率会产生一个高抑制的传输零点，通过调整微带线延长端长度能调整辐射抑制零点的位置至通带下侧边沿，实现宽阻带高滚降的高通滤波特性。结合延长型馈电微带线的高通滤波特性以及加载缝隙结构的寄生贴片的低通滤波特性，最终使天线实现了良好的带通滤波性能。
如图3所示，延长的微带线6位于加载十字型缝隙8的金属地板的下方，通过与缝隙的耦合作用使能量馈给上层的贴片，微带线经过缝隙后的延长部分的长度为辐射抑制零点位置频率的二分之一等效波长。
如图3所示，利用两个通孔和带状线形成的空气桥5避免两个正交的馈电网络交叉。
如图5-图6所示，是本发明一个实施例提供的双极化滤波偶极子天线的反射系数S11-频率和增益曲线-频率的仿真和测量的结果图，通带内阻抗匹配良好，阻抗带宽为3.3-4.36GHz，回波损耗均在-15dB以下；工作频段内增益约为8.2dBi，通带两侧具有高滚降滤波特性，且实现了从0-3GHz超过20dB的滤波抑制，以及从4.7-5.5GHz超过25dB的带外滤波抑制。
如图7所示，是本发明一个实施例提供的双极化滤波偶极子天线的传输系数S21-频率的仿真和测量的结果图，通带内两个端口的隔离较好，均在-25dB以下。
本发明实施例具有如下优点：
(1)该偶极子天线结构简单，成本低廉，通过在辐射体上寄生新型的缝隙结构增加带宽的同时能引入高滚降的边沿滤波效果；
(2)滤波天线单元在通带内有良好的辐射性能，通带外具有高滚降和良好的带外抑制能力的带通滤波效果，实现滤波性能的方式没有带来额外的加工成本且适用面广，并且未引入额外的插损；
(3)滤波天线单元具有低剖面，工作频带宽，高增益的特点，且在通带内方向图波瓣稳定，交叉极化低，不同极化端口的馈电结构几乎完全对称且隔离度高。
本发明提供的实施例可根据需求对相关结构的尺寸进行调整而适应不同的频带的无线通信系统的接收和发射设备中，由于本发明的滤波特性，特别适用于在开阔复杂的通信场景中。同时受益于滤波特性与辐射特性的集成，本发明也适用于无线移动通信系统设备的一体化和集成化。
上述实施例为本发明较佳的实施方式，但本发明的实施方式并不受所述实施例的限制，其他的任何未背离本发明的精神实质与原理下所作的改变、修饰、替代、组合、简化，均应为等效的置换方式，都包含在本发明的保护范围之内。

Claims (5)

  1. 一种低剖面双极化滤波磁电偶极子天线，其特征在于，包括上层介质基板及下层介质基板，所述上层介质基板的上表面印刷辐射体结构，所述下层介质基板印刷缝隙耦合馈电网络结构；
    所述辐射体结构包括四块加载对称缝隙的寄生贴片，所述寄生贴片加载短路探针；
    所述缝隙耦合馈电网络结构包括两组正交放置的Y型馈电线及十字型缝隙，所述十字型缝隙印刷在金属地板上，所述金属地板与Y型馈电线印刷在下层介质基板的不同表面，所述寄生贴片通过短路探针与金属地板连接。
  2. 根据权利要求1所述的低剖面双极化滤波磁电偶极子天线，其特征在于，所述Y型馈电线包括一个一分二功分器，一分二功分器的输出端连接两路微带线，所述两路微带线经过十字型缝隙后延伸，并将延伸部分进行弯折，通过十字型缝隙耦合上层介质基板的寄生贴片，引入辐射抑制零点。
  3. 根据权利要求2所述的低剖面双极化滤波磁电偶极子天线，其特征在于，所述延伸部分的长度为该辐射抑制零点位置频率的二分之一等效波长。
  4. 根据权利要求1所述的低剖面双极化滤波磁电偶极子天线，其特征在于，所述对称缝隙结构包括关于寄生贴片对角线对称的矩形缝隙。
  5. 根据权利要求1所述的低剖面双极化滤波磁电偶极子天线，其特征在于，还包括两个通孔及由带状线形成的空气桥，设置在两组Y型馈电线交叉位置。
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Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108232434A (zh) * 2017-12-15 2018-06-29 华南理工大学 一种低剖面全向辐射滤波偶极子天线
CN108336491A (zh) * 2018-04-02 2018-07-27 安徽大学 基于微带巴伦馈电的双频双极化叠层贴片天线及其设计方法
US20190020110A1 (en) * 2017-07-14 2019-01-17 Apple Inc. Multi-Band Millimeter Wave Patch Antennas
CN109390699A (zh) * 2018-11-19 2019-02-26 华南理工大学 一种基于可重构寄生单元的小型波束可控贴片天线
CN109860996A (zh) * 2019-03-01 2019-06-07 华南理工大学 一种低剖面双极化滤波磁电偶极子天线

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20110260941A1 (en) * 2008-10-15 2011-10-27 Argus Technologies (Australia) Pty Ltd. Wideband radiating elements
US11303026B2 (en) * 2015-12-09 2022-04-12 Viasat, Inc. Stacked self-diplexed dual-band patch antenna
CN108923124B (zh) * 2018-07-10 2020-01-31 华为技术有限公司 宽带外抑制高交叉极化比的双极化滤波天线
CN110401026B (zh) 2019-06-10 2021-03-23 西安电子科技大学 一种具有近似椭圆滤波响应的磁电偶极子滤波天线
CN110233341A (zh) 2019-06-14 2019-09-13 西安电子科技大学 一种槽缝低剖面的宽带双极化天线
CN110364818B (zh) 2019-07-30 2020-04-24 大连理工大学 一种宽带小型化双极化天线
CN110544819A (zh) 2019-08-16 2019-12-06 西安电子科技大学 一种宽带圆极化交叉磁电偶极子天线
CN110534890B (zh) 2019-09-07 2020-11-27 电子科技大学 低剖面双极化超表面天线

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20190020110A1 (en) * 2017-07-14 2019-01-17 Apple Inc. Multi-Band Millimeter Wave Patch Antennas
CN108232434A (zh) * 2017-12-15 2018-06-29 华南理工大学 一种低剖面全向辐射滤波偶极子天线
CN108336491A (zh) * 2018-04-02 2018-07-27 安徽大学 基于微带巴伦馈电的双频双极化叠层贴片天线及其设计方法
CN109390699A (zh) * 2018-11-19 2019-02-26 华南理工大学 一种基于可重构寄生单元的小型波束可控贴片天线
CN109860996A (zh) * 2019-03-01 2019-06-07 华南理工大学 一种低剖面双极化滤波磁电偶极子天线

Cited By (24)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
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CN114614260A (zh) * 2022-02-24 2022-06-10 西安电子科技大学 一种底板开槽宽带圆极化微带天线及卫星通信终端
CN114883793A (zh) * 2022-04-24 2022-08-09 西安交通大学 一种基于容性耦合馈电的宽频带、高功率容量贴片天线
CN114883793B (zh) * 2022-04-24 2023-03-28 西安交通大学 一种基于容性耦合馈电的宽频带、高功率容量贴片天线
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