WO2020115820A1 - Waveguide planar line converter and high-frequency module - Google Patents

Waveguide planar line converter and high-frequency module Download PDF

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Publication number
WO2020115820A1
WO2020115820A1 PCT/JP2018/044591 JP2018044591W WO2020115820A1 WO 2020115820 A1 WO2020115820 A1 WO 2020115820A1 JP 2018044591 W JP2018044591 W JP 2018044591W WO 2020115820 A1 WO2020115820 A1 WO 2020115820A1
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WO
WIPO (PCT)
Prior art keywords
waveguide
metal block
line converter
cross
plane line
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Application number
PCT/JP2018/044591
Other languages
French (fr)
Japanese (ja)
Inventor
森本　康夫
秀憲 湯川
英次 竹田
高橋　徹
Original Assignee
三菱電機株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 三菱電機株式会社 filed Critical 三菱電機株式会社
Priority to JP2020558715A priority Critical patent/JP6851556B2/en
Priority to PCT/JP2018/044591 priority patent/WO2020115820A1/en
Priority to CN201880099449.4A priority patent/CN113169434B/en
Publication of WO2020115820A1 publication Critical patent/WO2020115820A1/en

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/10—Coupling devices of the waveguide type for linking dissimilar lines or devices for coupling balanced lines or devices with unbalanced lines or devices
    • H01P5/107—Hollow-waveguide/strip-line transitions

Definitions

  • the present invention relates to a waveguide plane line converter including a rectangular waveguide and a plane line and a high frequency module.
  • Patent Document 1 discloses a connection structure between a plane line and a waveguide.
  • the connection structure disclosed in Patent Document 1 includes a post wall waveguide formed on a dielectric substrate, and an end portion of the post wall waveguide is inserted into a hollow portion of the waveguide.
  • the connection structure disclosed in Patent Document 1 prevents leakage of a high-frequency signal to the outside through a gap between the ground conductor layer on the upper side of the post wall waveguide and the upper wide wall of the waveguide.
  • a conductor such as a metal (hereinafter referred to as “closed conductor”) is arranged in the gap.
  • a gap is formed between the closed conductor and the post wall waveguide. May occur.
  • the width of the gap is the wide dimension of the waveguide and is not less than half the effective wavelength of the high frequency signal.
  • the high-frequency signal may leak to the outside because the high-frequency signal is not blocked.
  • the present invention has been made to solve the above problems, and to obtain a waveguide plane line converter and a high-frequency module capable of preventing leakage of electromagnetic waves to the outside without using a closed conductor. With the goal.
  • a waveguide plane line converter according to the present invention has a first cross-sectional shape that is a cross-sectional shape of a conduit on the first opening side and a second cross-sectional shape that is a cross-sectional shape of a conduit on the second opening side.
  • the longitudinal direction of the first cross-sectional shape and the lateral direction of the second cross-sectional shape are arranged in parallel, and the lateral direction of the first cross-sectional shape and the longitudinal direction of the second cross-sectional shape are Rectangular waveguides arranged in parallel, a post wall waveguide part of which is arranged in the second opening side conduit, and a tip thereof arranged in the first opening side conduit, A balanced probe whose proximal end is connected to the end of the post wall waveguide on the side of the first opening, and a second end of the balanced probe which is disposed outside the second opening in the rectangular waveguide.
  • the flat line is connected to the end on the opening side.
  • the first cross-sectional shape which is the cross-sectional shape of the first opening-side conduit and the second cross-sectional shape which is the cross-sectional shape of the second opening-side conduit are different from each other.
  • a waveguide planar line converter was constructed to include a waveguide. Therefore, the waveguide plane line converter according to the present invention can prevent leakage of electromagnetic waves to the outside without using a closed conductor.
  • FIG. 3 is a perspective transparent view showing the waveguide plane line converter according to the first embodiment.
  • FIG. 2 is an exploded perspective transparent view of the waveguide plane line converter shown in FIG. 1.
  • FIG. 2 is a top transparent view of the waveguide plane line converter shown in FIG. 1.
  • 4 is a cross-sectional view showing an x 1 -x 1 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 4 is a cross-sectional view showing an x 2 -x 2 ′ cross section in the waveguide plane line converter shown in FIG.
  • FIG. 4 is a cross-sectional view showing an x 3 -x 3 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 3 is a perspective transparent view showing the waveguide plane line converter according to the first embodiment.
  • FIG. 2 is an exploded perspective transparent view of the waveguide plane line converter shown in FIG. 1.
  • FIG. 2 is a top transparent view of the waveguide plane line converter shown in FIG. 1.
  • 4
  • FIG. 4 is a cross-sectional view showing an x 4 -x 4 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 4 is a cross-sectional view showing an x 5 -x 5 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • 4 is a cross-sectional view showing an x 6 -x 6 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 4 is a sectional view showing a section taken along line x 7 -x 7 ′ in the waveguide plane line converter shown in FIG. 3.
  • FIG. 4 is a cross-sectional view showing an x 8 -x 8 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 3 is a cross-sectional view showing an x 8 -x 8 ′ cross section in the waveguide plane line converter shown in FIG. 3.
  • FIG. 4 is a cross-sectional view showing an x 9 -x 9 ′ cross section in the waveguide plane line converter shown in FIG. 3. It is explanatory drawing which shows the electromagnetic field analysis result of the attenuation constant of the electromagnetic wave which propagates the space 3b by TE10 mode. It is explanatory drawing which shows the electromagnetic field analysis result of the reflection amplitude of the electromagnetic wave in the waveguide plane line converter shown in FIG.
  • FIG. 6 is a cross-sectional view showing a waveguide plane line converter according to a second embodiment.
  • FIG. 6 is a cross-sectional view showing a high frequency module according to a third embodiment. It is sectional drawing which shows the other high frequency module which concerns on Embodiment 3.
  • FIG. 9 is a perspective transparent view showing a waveguide plane line converter according to a fifth embodiment.
  • FIG. 20 is a perspective transparent view showing a waveguide plane line converter as a comparison target with the waveguide plane line converter shown in FIG. 19. It is explanatory drawing which shows the electromagnetic field analysis of the passage phase of the electromagnetic wave in the waveguide plane line converter shown in FIG. It is explanatory drawing which shows the electromagnetic field analysis of the reflection amplitude of the electromagnetic wave in the waveguide plane line converter shown in FIG.
  • FIG. 1 is a perspective transparent view showing a waveguide plane line converter according to the first embodiment.
  • FIG. 2 is an exploded perspective transparent view of the waveguide plane line converter shown in FIG.
  • FIG. 3 is a top transparent view of the waveguide plane line converter shown in FIG.
  • Figure 4 is a sectional view showing the x 1 -x 1 'cross-section in the waveguide planar line converter shown in FIG. 3
  • FIG. 5 is x 2 -x in waveguide planar line converter shown in FIG. 3 it is a sectional view showing a 2 'section.
  • Figure 6 is a sectional view showing the x 3 -x 3 'section of waveguide planar line converter shown in FIG. 3, FIG. 7, x 4 -x in waveguide planar line converter shown in FIG. 3 4 'is a cross-sectional view showing a cross section.
  • 8 is a sectional view showing a section taken along line x 5 -x 5 ′ in the waveguide plane line converter shown in FIG. 3
  • FIG. 9 is a sectional view taken along line x 6 -x in the waveguide plane line converter shown in FIG. 6 'is a cross-sectional view showing a cross section.
  • 10 is a sectional view showing a section taken along line x 7 -x 7 ′ in the waveguide plane line converter shown in FIG. 3, and FIG.
  • FIG. 11 is a sectional view taken along line x 8 -x in the waveguide plane line converter shown in FIG. 8 'is a cross-sectional view showing a cross section.
  • FIG. 12 is a sectional view showing an x 9 -x 9 ′ section in the waveguide plane line converter shown in FIG.
  • the rectangular waveguide 1 includes a first metal block 1a and a second metal block 1b.
  • the first metal block 1a and the second metal block 1b are connected between the first metal block 1a and the second metal block 1b so that the space 3a and the space 3b are formed.
  • the space 3a is a conduit on the side of the first opening 2a in the rectangular waveguide 1.
  • the space 3b is a conduit on the side of the second opening 2b in the rectangular waveguide 1.
  • the space 3b includes a space 3c, and the space 3c is a space between the inner wall surface 1a′ of the conduit on the second opening 2b side and the post wall waveguide 6, as shown in FIG.
  • a second cross section that is a cross-sectional shape in the direction parallel to the yz plane in the first opening 2a side and a cross-sectional shape in the direction parallel to the yz plane in the second opening 2b side conduit.
  • the shape is different.
  • the shape of each space 3a in the x 1 -x 1 ′ cross section, the x 2 ⁇ x 2 ′ cross section, and the x 3 ⁇ x 3 ′ cross section is the first cross sectional shape.
  • the shape of the respective spaces 3b in x 4 -x 4 'cross-section and x 5 -x 5' section is a second cross-sectional shape.
  • the second cross-sectional shape is a rectangle having a longitudinal direction of 5a and a lateral direction of 5b.
  • the longitudinal direction 4a and the lateral direction 4b in the first cross-sectional shape are orthogonal to each other, as shown in FIGS. 4 to 6.
  • the longitudinal direction 5a and the lateral direction 5b in the second cross-sectional shape are orthogonal to each other, as shown in FIGS.
  • the longitudinal direction 4a of the first cross-sectional shape and the lateral direction 5b of the second cross-sectional shape are arranged parallel to each other, as shown in FIGS. 4 to 8.
  • the short-side direction 4b of the first cross-sectional shape and the longitudinal direction 5a of the second cross-sectional shape are arranged in parallel with each other, as shown in FIGS. 4 to 8.
  • a part of the post wall waveguide 6 is arranged in the space 3b such that the longitudinal direction in the yz plane is parallel to the longitudinal direction 5a of the second cross-sectional shape. ing.
  • the post wall waveguide 6 may extend to the outside of the second opening 2b in the rectangular waveguide 1, as shown in FIG.
  • the post wall waveguide 6 includes a dielectric substrate 7, a first ground conductor 8, a second ground conductor 9, a first columnar conductor 10, and a second columnar conductor 11.
  • the dielectric substrate 7 is arranged such that the longitudinal direction in the yz plane is parallel to the longitudinal direction 5a, and in a part of the space 3a, the longitudinal direction in the yz plane is the first.
  • the dielectric substrate 7 is arranged so as to be parallel to the lateral direction 4b of the cross-sectional shape. Further, the dielectric substrate 7 is arranged outside the second opening 2b in the rectangular waveguide 1 so that the longitudinal direction in the yz plane is parallel to the y-axis direction.
  • the first plane 7a is the xy plane on the ⁇ z axis direction side of the two xy planes on the dielectric substrate 7.
  • the second plane 7b is the xy plane on the +z axis direction side of the two xy planes on the dielectric substrate 7.
  • the first ground conductor 8 is formed on the first plane 7 a of the dielectric substrate 7.
  • the second ground conductor 9 is formed on the second plane 7b of the dielectric substrate 7.
  • the dielectric substrate 7 is arranged so that the second ground conductor 9 is in contact with the second metal block 1b.
  • the first columnar conductor 10 electrically connects between the first ground conductor 8 and the second ground conductor 9.
  • the second columnar conductor 11 is arranged on the +y-axis direction side of the first columnar conductor 10, and electrically connects the first ground conductor 8 and the second ground conductor 9.
  • the waveguide width 6 a of the post wall waveguide 6 is the length between the first columnar conductor 10 and the second columnar conductor 11.
  • the screws 12a and 12b are members for fixing the dielectric substrate 7 to the second metal block 1b.
  • the balanced probe 13 includes a first probe 13a and a second probe 13b.
  • the balance probe 13 has a tip arranged in the space 3a and a base end connected to the end of the post wall waveguide 6 on the first opening 2a side.
  • the space of the dielectric substrate 7 is arranged so that the tip of the first probe 13a is arranged in the space 3a and the base of the first probe 13a is connected to the end 8a of the first ground conductor 8 on the side of the first opening 2a. It is formed on the first flat surface 7a of the dielectric substrate 7 in the portion arranged on 3a.
  • the tip of the first probe 13a is an end on the ⁇ x axis side, and the base end of the first probe 13a is an end on the +x axis side.
  • the second probe 13b has a distal end arranged in the space 3a and a proximal end connected to the end portion 9a of the second ground conductor 9 on the first opening 2a side. It is formed on the second plane 7b of the dielectric substrate 7 in the portion arranged on 3a.
  • the tip of the second probe 13b is an end on the ⁇ x axis side, and the base end of the second probe 13b is an end on the +x axis side.
  • the position of the base end of the first probe 13a in the y-axis direction is substantially the same as the position of the base end of the second probe 13b in the y-axis direction.
  • the position of the tip of the first probe 13a in the y-axis direction is different from the position of the tip of the second probe 13b in the y-axis direction, and the first probe 13a and the second probe 13b are The distance from each other increases in the direction from the proximal end to the distal end.
  • the plane line 14 includes a signal line conductor 14a and a ground conductor 14b.
  • the plane line 14 is arranged outside the second opening 2b in the rectangular waveguide 1, and one end thereof is connected to the end of the post wall waveguide 6 on the side of the second opening 2b.
  • the signal line conductor 14a is realized by, for example, a microstrip line.
  • the signal line conductor 14a is formed on the first plane 7a of the dielectric substrate 7 in a portion of the dielectric substrate 7 that is arranged outside the second opening 2b.
  • the ground conductor 14b is formed on the second plane 7b of the dielectric substrate 7 in a portion of the dielectric substrate 7 that is arranged outside the second opening 2b.
  • the screws 15a and 15b are members for fixing the portion of the dielectric substrate 7, which is arranged outside the second opening 2b, of the dielectric substrate 7 to the second metal block 1b.
  • the space 16a is a cavity formed so that the screw 12a does not come into contact with the first metal block 1a.
  • the space 16b is a cavity formed so that the screw 12b does not come into contact with the first metal block 1a.
  • the dimension of the first cross-sectional shape in the longitudinal direction 4a is equal to or longer than a half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1.
  • the dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than a half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1.
  • the waveguide width 6a of the post wall waveguide 6 is a length equal to or longer than half the effective wavelength of the electromagnetic wave propagated by the rectangular waveguide 1. Since the post wall waveguide 6 has the dielectric substrate 7 and the electromagnetic wave passes through the dielectric substrate 7, the effective wavelength is shorter than the wavelength of the electromagnetic wave passing through the space such as the space 3a.
  • the substrate thickness of the dielectric substrate 7 is assumed to include the conductor thickness of the first ground conductor 8 and the conductor thickness of the second ground conductor 9 in addition to the thickness of the dielectric substrate 7.
  • the longitudinal direction 4a of the first cross-sectional shape and the lateral direction 5b of the second cross-sectional shape are arranged parallel to each other, as shown in FIGS. 4 to 8. Further, the lateral direction 4b of the first cross-sectional shape and the longitudinal direction 5a of the second cross-sectional shape are arranged in parallel with each other, as shown in FIGS. 4 to 8. Therefore, the wide wall surface in the space 3a and the wide wall surface in the space 3b are orthogonal to each other, and the narrow wall surface in the space 3a and the narrow wall surface in the space 3b are orthogonal to each other.
  • the post wall waveguide 6 is arranged in the space 3b.
  • the basic mode in the space 3a is the TE01 mode
  • the basic mode in the space 3b is the TE10 mode. Since the TE01 mode and the TE10 mode are modes orthogonal to each other, the coupling between the TE01 mode and the TE10 mode is small. Since the coupling between the TE01 mode and the TE10 mode is small, it is possible to prevent the electromagnetic wave from leaking from the second opening 2b in the rectangular waveguide 1 to the outside.
  • the electromagnetic wave input from the outside into the first opening 2a is It is propagated in the space 3a in the TE01 mode.
  • the first probe 13a and the second probe 13b which are the balanced probes 13 arranged in the space 3a, cause the first ground conductor 8 and the second ground conductor 9 as a balanced line. Is converted into a mode capable of propagating in the post wall waveguide 6. Since the waveguide width 6a of the post wall waveguide 6 is a length equal to or longer than a half wavelength of the effective wavelength of the electromagnetic wave, the electromagnetic wave propagates through the post wall waveguide 6 in the TE10 mode.
  • the dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than the half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1, so the space 3b has a blocking structure at the frequency of the electromagnetic wave. .. Therefore, the electromagnetic wave is not substantially propagated in the space 3b. Since one end of the planar line 14 arranged outside the second opening 2b in the rectangular waveguide 1 is connected to the central portion of the post wall waveguide 6 in the y-axis direction, the post wall waveguide 6 is The propagated electromagnetic wave propagates through the plane line 14 in the quasi-TEM mode.
  • FIG. 13 is an explanatory diagram showing an electromagnetic field analysis result of an attenuation constant of an electromagnetic wave propagating in the space 3b in the TE10 mode.
  • the finite element method is used for electromagnetic field analysis.
  • the horizontal axis of FIG. 13 is the center frequency of the electromagnetic wave propagated by the rectangular waveguide 1, and the center frequency of the electromagnetic wave is standardized by the X band which is the 9.7 GHz band.
  • the vertical axis of FIG. 13 is the attenuation constant [N ⁇ s/m] of the electromagnetic wave propagated in the TE10 mode.
  • the substrate thickness of the dielectric substrate 7 including the conductor thickness of the first ground conductor 8 and the conductor thickness of the second ground conductor 9 is fixed at 0.54 [mm].
  • the length 5c shown in FIG. 8 is set in the range of 0.2 [mm] to 0.8 [mm].
  • 30 indicates the analysis result when the length 5c is 0.2 [mm]
  • 31 indicates the analysis result when the length 5c is 0.27 [mm]
  • 32 indicates the length 5c.
  • 33 shows the analysis result when the length 5c is 0.4 [mm]
  • 34 shows the analysis when the length 5c is 0.5 [mm].
  • 35 shows the analysis result when the length 5c is 0.6 [mm]
  • 36 shows the analysis result when the length 5c is 0.7 [mm]
  • 37 shows the length 5c.
  • the analysis result in the case of 0.8 [mm] is shown.
  • the length 5c of 0.27 [mm] according to the analysis result 31 is half the length of 0.54 [mm] that is the substrate thickness of the dielectric substrate 7.
  • the space 3b including the dielectric substrate 7 cannot block the electromagnetic wave having the normalized frequency of 1.
  • the attenuation constant at the normalized frequency 1 is about 50 or more [N ⁇ s/m]. ]. Therefore, the space 3b including the dielectric substrate 7 can substantially block the electromagnetic wave having the normalized frequency of 1.
  • the dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than the half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1, and
  • the length 5c is more than half the thickness of the dielectric substrate 7. Therefore, the electromagnetic wave is hardly propagated in the TE10 mode in the space 3b except the post wall waveguide 6, but is propagated in the TE10 mode in the post wall waveguide 6.
  • FIG. 14 is an explanatory diagram showing an electromagnetic field analysis result of a reflection amplitude of an electromagnetic wave in the waveguide plane line converter shown in FIG.
  • the finite element method is used for electromagnetic field analysis.
  • the horizontal axis of FIG. 14 is the center frequency of the electromagnetic wave propagated by the rectangular waveguide 1, and the center frequency of the electromagnetic wave is standardized by the X band.
  • the vertical axis of FIG. 14 is the reflection amplitude [dB] of the electromagnetic wave.
  • the length 5c is 0.5 [mm].
  • the specific bandwidth of the reflection amplitude of -20 [dB] is in the range of the normalized frequency of about 0.95 to 1.05, and the reflection amplitude is in the range of the normalized frequency of about 0.95 to 1.05. It is in the range of about ⁇ 20 to ⁇ 40 [dB]. Therefore, it is understood that the reflection of the electromagnetic wave propagated by the rectangular waveguide 1 is sufficiently small when the normalized frequency is in the range of about 0.95 to 1.05.
  • the first cross-sectional shape that is the cross-sectional shape of the pipeline on the first opening 2a side and the second cross-sectional shape that is the cross-sectional shape of the pipeline on the second opening 2b side are Differently, the longitudinal direction 4a of the first sectional shape and the lateral direction 5b of the second sectional shape are arranged in parallel, and the lateral direction 4b of the first sectional shape and the longitudinal direction 5a of the second sectional shape are arranged.
  • the waveguide plane line converter was configured so as to include the rectangular waveguides 1 arranged in parallel with each other. Therefore, the waveguide plane line converter can prevent electromagnetic waves from leaking to the outside without using a closed conductor.
  • FIG. 15 is a sectional view showing a waveguide plane line converter according to the second embodiment.
  • Y 1 -y 1 in waveguide planar line converter shown in FIG. 15 'cross section, y 1 -y 1 in waveguide planar line converter shown in FIG. 3' corresponds to the cross-section.
  • the same reference numerals as those in FIGS. 1 to 12 indicate the same or corresponding portions, and thus the description thereof will be omitted.
  • the conductive member 40 is realized by a conductive sponge, a conductive bond, or the like.
  • the conductive member 40 is provided in a part of the space 3b, and electrically connects the first metal block 1a and the first ground conductor 8 to each other.
  • the conductive member 40 is arranged such that the position in the y-axis direction is, for example, the position in the y-axis direction on the plane line 14.
  • the number of the conducting members 40 provided in a part of the space 3b may be one or plural.
  • the conducting member 40 is not a closed conductor that shields the entire space 3b. However, since the conductive member 40 acts as a shielding member that reflects electromagnetic waves, it can shield electromagnetic waves. Therefore, the waveguide plane line converter of the second embodiment can further suppress electromagnetic waves leaking to the outside than the waveguide plane line converter of the first embodiment.
  • FIG. 16 is a cross-sectional view showing the high frequency module according to the third embodiment.
  • the high-frequency module shown in FIG. 16 includes a waveguide plane line converter, and the y 1 -y 1 ′ cross section of the waveguide plane line converter is the same as that of the waveguide plane line converter shown in FIG. corresponds to y 1 -y 1 'section.
  • the same reference numerals as those in FIGS. 1 to 12 indicate the same or corresponding portions, and thus the description thereof is omitted.
  • the space 51 is formed by the first metal block 1a and the second metal block 1b in order to provide the high frequency amplifier 55 and the isolator 56.
  • the dielectric substrate 52 has a ground conductor 53 on one plane and a ground conductor 54 on the other plane.
  • the dielectric substrate 52 is arranged in the space 51 so that the ground conductor 54 contacts the second metal block 1b.
  • the high frequency amplifier 55 is provided on the ground conductor 53 of the dielectric substrate 52.
  • the high frequency amplifier 55 amplifies the electromagnetic wave propagated through the plane line 14 when the electromagnetic wave passes through the isolator 56.
  • the isolator 56 is provided on the second metal block 1b so as to be located between the dielectric substrate 7 and the high frequency amplifier 55.
  • the isolator 56 is a high frequency component that allows electromagnetic waves to pass in the forward direction but does not allow electromagnetic waves to pass in the reverse direction.
  • the isolator 56 allows the electromagnetic wave propagated through the plane line 14 in the quasi-TEM mode to pass therethrough, and blocks the electromagnetic wave output from the high frequency amplifier 55 from passing therethrough. In the high frequency module shown in FIG.
  • the isolator 56 allows the electromagnetic waves propagated through the plane line 14 to pass therethrough and blocks the electromagnetic waves output from the high frequency amplifier 55 from passing therethrough.
  • the heat dissipation fin 57 is a second metal facing the inner wall surface 101 of the second metal block 1b forming the space 51 in order to dissipate the heat generated from the high frequency amplifier 55 and the like to the outside of the high frequency module. It is provided on the outer wall surface 102 of the block 1b.
  • the high frequency module shown in FIG. 16 includes an isolator 56 between the dielectric substrate 7 and the dielectric substrate 52. Since the high-frequency module shown in FIG. 16 includes the isolator 56, even if the high-frequency amplifier 55 is provided, interference between the electromagnetic wave propagating through the plane line 14 in the quasi-TEM mode and the high-frequency amplified by the high-frequency amplifier 55 is prevented. Can be prevented. Since the second metal block 1b is provided on the outer wall surface 102 of the second metal block 1b, the heat generated from the high frequency amplifier 55 and the like is radiated to the outside of the high frequency module. In the high frequency module shown in FIG. 16, a high frequency amplifier 55 and an isolator 56 are provided in the space 51. Therefore, the high-frequency module shown in FIG. 16 can prevent each of the electromagnetic wave propagating through the plane line 14 and the high-frequency amplified by the high-frequency amplifier 55 from being radiated to the outside of the high-frequency module.
  • the space 51 for providing the high frequency amplifier 55 and the isolator 56 is formed by the first metal block 1a and the second metal block 1b.
  • a space 51 for providing the high frequency amplifier 55 and the isolator 56 may be a high frequency module formed by a shield member 58.
  • FIG. 17 is a sectional view showing another high-frequency module according to the third embodiment.
  • the shield member 58 has one end connected to the first ground conductor 8 and the other end connected to the ground conductor 53, and covers the high frequency amplifier 55 and the isolator 56. Since the high frequency module shown in FIG. 17 includes the shield member 58, it is possible to prevent the electromagnetic wave propagating through the plane line 14 and the high frequency amplified by the high frequency amplifier 55 from being radiated to the outside of the high frequency module. You can
  • FIG. 18 is a sectional view showing the high frequency module according to the fourth embodiment.
  • the high-frequency module shown in FIG. 18 includes a waveguide plane line converter, and the section taken along line y 1 -y 1 ′ of the waveguide plane line converter is the same as that of the waveguide plane line converter shown in FIG. corresponds to y 1 -y 1 'section.
  • the same reference numerals as those in FIGS. 1 to 12, 16 and 17 indicate the same or corresponding parts, and thus the description thereof will be omitted.
  • the choke structure 60 is formed on the inner wall surface 1 a ′ of the first metal block 1 a facing the post wall waveguide 6 among the inner wall surfaces of the first metal block 1 a.
  • the length 60a of the choke structure 60 is the length in the z-axis direction from the opening position of the choke structure 60 to the bottom portion 60b of the choke structure 60, and the length 60a is the wavelength of the electromagnetic wave whose propagation in the space 3b is to be suppressed.
  • the length is an odd multiple of 1/4.
  • the waveguide plane line converter included in the high-frequency module shown in FIG. 18 has a rectangular cross-section in the longitudinal direction 5a of the second cross-sectional shape, as in the waveguide plane line converter of the first embodiment.
  • the length is equal to or less than a half wavelength of the electromagnetic wave propagated by the waveguide 1. Therefore, the space 3b has a blocking structure at the frequency of the electromagnetic wave.
  • the choke structure 60 having a length 60a that is an odd multiple of a quarter of the wavelength of the electromagnetic wave acts to suppress the electromagnetic wave. Therefore, the waveguide plane line converter included in the high frequency module shown in FIG. 18 can further suppress the propagation of the electromagnetic wave in the space 3b as compared with the waveguide plane line converter of the first embodiment. ..
  • FIG. 19 is a perspective transparent view showing a waveguide plane line converter according to the fifth embodiment. 19, the same reference numerals as those in FIG. 1 indicate the same or corresponding portions, and thus the description thereof will be omitted.
  • the first waveguide plane line converter which is one of the waveguide plane line converters, is a conductor shown in the upper left of the distributor/combiner 70 in the figure. It is a waveguide flat line converter.
  • the second waveguide plane line converter which is the other waveguide plane line converter, is the waveguide plane line converter shown at the lower right of the distributor/combiner 70 in the figure.
  • the distributor/combiner 70 is an E-plane branch T-shaped waveguide having input/output ports 70a, 70b, and 70c.
  • the input/output port 70a is connected to the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter
  • the input/output port 70b is the second waveguide plane line. It is connected to the first opening 2a of the rectangular waveguide 1 in the converter.
  • the distributor/combiner 70 branches the electromagnetic wave into two when the electromagnetic wave is input to the input/output port 70a from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter, One electromagnetic wave is output to the input/output port 70b, and the other electromagnetic wave is output to the input/output port 70c.
  • the phase of the electromagnetic wave input to the input/output port 70a and the phase of the electromagnetic wave output to the input/output ports 70b and 70c are opposite phases.
  • the distributor/combiner 70 branches the electromagnetic wave into two when the electromagnetic wave is input to the input/output port 70b from the first opening 2a of the rectangular waveguide 1 in the second waveguide plane line converter. One electromagnetic wave is output to the input/output port 70a, and the other electromagnetic wave is output to the input/output port 70c.
  • the phase of the electromagnetic wave input to the input/output port 70b and the phase of the electromagnetic wave output to the input/output ports 70a and 70c are opposite phases.
  • the distributor/combiner 70 branches the electromagnetic wave into two, outputs one electromagnetic wave to the input/output port 70a, and outputs the other electromagnetic wave to the input/output port 70b. Output.
  • the phase of the electromagnetic wave output to the input/output port 70a and the phase of the electromagnetic wave output to the input/output port 70b are opposite phases.
  • the first probe 13a in the first waveguide plane line converter and the second probe 13b in the second waveguide plane line converter are It is arranged so as to face each other. Further, the second probe 13b in the first waveguide plane line converter and the first probe 13a in the second waveguide plane line converter are arranged so as to face each other.
  • FIG. 20 is a perspective transparent view showing a waveguide plane line converter to be compared with the waveguide plane line converter shown in FIG.
  • the first probe 13a in the first waveguide plane line converter and the first probe 13a in the second waveguide plane line converter are It is arranged so as to face each other.
  • the second probe 13b in the first waveguide plane line converter and the second probe 13b in the second waveguide plane line converter are arranged so as to face each other.
  • the phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 20 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase.
  • phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter and the second waveguide has a reverse phase.
  • FIG. 21 is an explanatory diagram showing an electromagnetic field analysis of a passing phase of an electromagnetic wave in the waveguide plane line converter shown in FIG.
  • the finite element method is used for electromagnetic field analysis.
  • the horizontal axis of FIG. 21 is the center frequency of each electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the two waveguide plane line converters, and the center frequency of the electromagnetic wave depends on the X band. It is standardized.
  • the vertical axis of FIG. 21 represents the electromagnetic wave passage phase [deg].
  • 81 is the electromagnetic wave passing phase in the first waveguide plane line converter
  • 82 is the electromagnetic wave passing phase in the second waveguide plane line converter.
  • the phases of the passing phase 81 and the passing phase 82 are inverted by 180 degrees.
  • FIG. 22 is an explanatory diagram showing an electromagnetic field analysis of the reflection amplitude of an electromagnetic wave in the waveguide plane line converter shown in FIG.
  • the finite element method is used for electromagnetic field analysis.
  • the horizontal axis of FIG. 22 is the center frequency of each electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the two waveguide plane line converters, and the center frequency of the electromagnetic wave depends on the X band. It is standardized.
  • the vertical axis of FIG. 22 represents the reflection amplitude [dB].
  • 91 is the reflection amplitude of the electromagnetic wave in the first waveguide plane line converter
  • 92 is the reflection amplitude of the electromagnetic wave in the second waveguide plane line converter.
  • the reflection amplitude 91 and the reflection amplitude 92 are substantially the same.
  • the waveguide plane shown in FIG. 20 becomes a line converter.
  • the phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 20 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase.
  • the waveguide plane line converter shown in FIG. 19 includes a first probe 13a in the first waveguide plane line converter shown in FIG. 20 and a second probe in the first waveguide plane line converter. 13b is the same as the waveguide plane line converter when it is replaced.
  • the phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 19 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase. Shall be Therefore, in the waveguide plane line converter shown in FIG. 19, the phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter and the second guide wave.
  • the phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the waveguide flat line converter has the same phase. Further, the reflection amplitudes of the respective electromagnetic waves are approximately the same.
  • the distributor/combiner 70 of the waveguide plane line converter shown in FIG. 19 combines two electromagnetic waves having the same passing phase and substantially the same reflection amplitude, and combines the electromagnetic waves combined from the input/output port 70a. Output to the outside.
  • the waveguide plane line converter shown in FIG. 19 has the same passing phase without providing a delay line for making the phases of the respective electromagnetic waves output from the two waveguide plane line converters the same. Two electromagnetic waves can be combined.
  • the invention of the present application is capable of freely combining the embodiments, modifying any constituent element of each embodiment, or omitting any constituent element in each embodiment. .
  • the present invention is suitable for a waveguide plane line converter including a rectangular waveguide and a plane line and a high frequency module.

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  • Waveguide Connection Structure (AREA)

Abstract

A waveguide planar line converter is configured to include a rectangular waveguide (1) in which a first cross-sectional shape, which is a cross-sectional shape in a conduit on a first opening (2a) side, is different from a second cross-sectional shape, which is a cross-sectional shape in a conduit on a second opening (2b) side, a longitudinal direction (4a) of the first cross-sectional shape and a lateral direction (5b) of the second cross-sectional shape are arranged in parallel, and a lateral direction (4b) of the first cross-sectional shape and a longitudinal direction (5a) of the second cross-sectional shape are arranged in parallel.

Description

導波管平面線路変換器及び高周波モジュールWaveguide plane line converter and high frequency module
　この発明は、方形導波管と平面線路とを備える導波管平面線路変換器及び高周波モジュールに関するものである。 The present invention relates to a waveguide plane line converter including a rectangular waveguide and a plane line and a high frequency module.
　以下の特許文献１には、平面線路と導波管との接続構造が開示されている。
　特許文献１に開示されている接続構造は、誘電体基板に形成されているポスト壁導波路を備えており、ポスト壁導波路の端部が導波管の中空部に挿入されている。
　また、特許文献１に開示されている接続構造は、ポスト壁導波路における上部側の接地導体層と、導波管の上部広壁との隙間から外部への高周波信号の漏れを防止するために、当該隙間に金属等の導体（以下、「閉鎖導体」と称する）を配置している。 The following Patent Document 1 discloses a connection structure between a plane line and a waveguide.
The connection structure disclosed in Patent Document 1 includes a post wall waveguide formed on a dielectric substrate, and an end portion of the post wall waveguide is inserted into a hollow portion of the waveguide.
In addition, the connection structure disclosed in Patent Document 1 prevents leakage of a high-frequency signal to the outside through a gap between the ground conductor layer on the upper side of the post wall waveguide and the upper wide wall of the waveguide. A conductor such as a metal (hereinafter referred to as “closed conductor”) is arranged in the gap.
特開２０１５－８０１０１号公報JP, 2005-80101, A
　特許文献１に開示されている接続構造では、ポスト壁導波路の製造誤差、導波管の製造誤差、又は、閉鎖導体の製造誤差に伴って、閉鎖導体とポスト壁導波路との間に隙間が生じることがある。閉鎖導体とポスト壁導波路との間に隙間が生じている場合、隙間の幅が、導波管の幅広寸法であって、高周波信号の実効波長の半波長以上であるため、当該接続構造は、高周波信号の遮断構造にならず、高周波信号が外部へ漏れてしまうことがあるという課題があった。 In the connection structure disclosed in Patent Document 1, due to a manufacturing error of the post wall waveguide, a manufacturing error of the waveguide, or a manufacturing error of the closed conductor, a gap is formed between the closed conductor and the post wall waveguide. May occur. When there is a gap between the closed conductor and the post wall waveguide, the width of the gap is the wide dimension of the waveguide and is not less than half the effective wavelength of the high frequency signal. However, there is a problem in that the high-frequency signal may leak to the outside because the high-frequency signal is not blocked.
　この発明は上記のような課題を解決するためになされたもので、閉鎖導体を用いることなく、外部への電磁波の漏れを防止することができる導波管平面線路変換器及び高周波モジュールを得ることを目的とする。 The present invention has been made to solve the above problems, and to obtain a waveguide plane line converter and a high-frequency module capable of preventing leakage of electromagnetic waves to the outside without using a closed conductor. With the goal.
　この発明に係る導波管平面線路変換器は、第１の開口側の管路における断面形状である第１の断面形状と、第２の開口側の管路における断面形状である第２の断面形状とが異なり、第１の断面形状の長手方向と第２の断面形状の短手方向とが平行に配置され、第１の断面形状の短手方向と第２の断面形状の長手方向とが平行に配置されている方形導波管と、一部が第２の開口側の管路内に配置されているポスト壁導波路と、先端が第１の開口側の管路内に配置され、基端がポスト壁導波路における第１の開口側の端部と接続されている平衡プローブと、方形導波管における第２の開口の外側に配置され、一端がポスト壁導波路における第２の開口側の端部と接続されている平面線路とを備えるものである。 A waveguide plane line converter according to the present invention has a first cross-sectional shape that is a cross-sectional shape of a conduit on the first opening side and a second cross-sectional shape that is a cross-sectional shape of a conduit on the second opening side. Different from the shape, the longitudinal direction of the first cross-sectional shape and the lateral direction of the second cross-sectional shape are arranged in parallel, and the lateral direction of the first cross-sectional shape and the longitudinal direction of the second cross-sectional shape are Rectangular waveguides arranged in parallel, a post wall waveguide part of which is arranged in the second opening side conduit, and a tip thereof arranged in the first opening side conduit, A balanced probe whose proximal end is connected to the end of the post wall waveguide on the side of the first opening, and a second end of the balanced probe which is disposed outside the second opening in the rectangular waveguide. The flat line is connected to the end on the opening side.
　この発明によれば、第１の開口側の管路における断面形状である第１の断面形状と、第２の開口側の管路における断面形状である第２の断面形状とが異なり、第１の断面形状の長手方向と第２の断面形状の短手方向とが平行に配置され、第１の断面形状の短手方向と第２の断面形状の長手方向とが平行に配置されている方形導波管を備えるように、導波管平面線路変換器を構成した。したがって、この発明に係る導波管平面線路変換器は、閉鎖導体を用いることなく、外部への電磁波の漏れを防止することができる。 According to the present invention, the first cross-sectional shape which is the cross-sectional shape of the first opening-side conduit and the second cross-sectional shape which is the cross-sectional shape of the second opening-side conduit are different from each other. A rectangular shape in which the longitudinal direction of the cross-sectional shape and the lateral direction of the second cross-sectional shape are arranged in parallel, and the lateral direction of the first cross-sectional shape and the longitudinal direction of the second cross-sectional shape are arranged in parallel. A waveguide planar line converter was constructed to include a waveguide. Therefore, the waveguide plane line converter according to the present invention can prevent leakage of electromagnetic waves to the outside without using a closed conductor.
実施の形態１に係る導波管平面線路変換器を示す斜視透過図である。FIG. 3 is a perspective transparent view showing the waveguide plane line converter according to the first embodiment. 図１に示す導波管平面線路変換器の分解斜視透過図である。FIG. 2 is an exploded perspective transparent view of the waveguide plane line converter shown in FIG. 1. 図１に示す導波管平面線路変換器の上面透過図である。FIG. 2 is a top transparent view of the waveguide plane line converter shown in FIG. 1. 図３に示す導波管平面線路変換器におけるｘ１－ｘ１’断面を示す断面図である。4 is a cross-sectional view showing an x 1 -x 1 ′ cross section in the waveguide plane line converter shown in FIG. 3. FIG. 図３に示す導波管平面線路変換器におけるｘ２－ｘ２’断面を示す断面図である。4 is a cross-sectional view showing an x 2 -x 2 ′ cross section in the waveguide plane line converter shown in FIG. 図３に示す導波管平面線路変換器におけるｘ３－ｘ３’断面を示す断面図である。FIG. 4 is a cross-sectional view showing an x 3 -x 3 ′ cross section in the waveguide plane line converter shown in FIG. 3. 図３に示す導波管平面線路変換器におけるｘ４－ｘ４’断面を示す断面図である。FIG. 4 is a cross-sectional view showing an x 4 -x 4 ′ cross section in the waveguide plane line converter shown in FIG. 3. 図３に示す導波管平面線路変換器におけるｘ５－ｘ５’断面を示す断面図である。FIG. 4 is a cross-sectional view showing an x 5 -x 5 ′ cross section in the waveguide plane line converter shown in FIG. 3. 図３に示す導波管平面線路変換器におけるｘ６－ｘ６’断面を示す断面図である。4 is a cross-sectional view showing an x 6 -x 6 ′ cross section in the waveguide plane line converter shown in FIG. 3. FIG. 図３に示す導波管平面線路変換器におけるｘ７－ｘ７’断面を示す断面図である。FIG. 4 is a sectional view showing a section taken along line x 7 -x 7 ′ in the waveguide plane line converter shown in FIG. 3. 図３に示す導波管平面線路変換器におけるｘ８－ｘ８’断面を示す断面図である。FIG. 4 is a cross-sectional view showing an x 8 -x 8 ′ cross section in the waveguide plane line converter shown in FIG. 3. 図３に示す導波管平面線路変換器におけるｘ９－ｘ９’断面を示す断面図である。FIG. 4 is a cross-sectional view showing an x 9 -x 9 ′ cross section in the waveguide plane line converter shown in FIG. 3. 空間３ｂをＴＥ１０モードで伝搬される電磁波の減衰定数の電磁界解析結果を示す説明図である。It is explanatory drawing which shows the electromagnetic field analysis result of the attenuation constant of the electromagnetic wave which propagates the space 3b by TE10 mode. 図１に示す導波管平面線路変換器における電磁波の反射振幅の電磁界解析結果を示す説明図である。It is explanatory drawing which shows the electromagnetic field analysis result of the reflection amplitude of the electromagnetic wave in the waveguide plane line converter shown in FIG. 実施の形態２に係る導波管平面線路変換器を示す断面図である。FIG. 6 is a cross-sectional view showing a waveguide plane line converter according to a second embodiment. 実施の形態３に係る高周波モジュールを示す断面図である。FIG. 6 is a cross-sectional view showing a high frequency module according to a third embodiment. 実施の形態３に係る他の高周波モジュールを示す断面図である。It is sectional drawing which shows the other high frequency module which concerns on Embodiment 3. 実施の形態４に係る高周波モジュールを示す断面図である。It is sectional drawing which shows the high frequency module which concerns on Embodiment 4. 実施の形態５に係る導波管平面線路変換器を示す斜視透過図である。FIG. 9 is a perspective transparent view showing a waveguide plane line converter according to a fifth embodiment. 図１９に示す導波管平面線路変換器と比較対象となる導波管平面線路変換器を示す斜視透過図である。FIG. 20 is a perspective transparent view showing a waveguide plane line converter as a comparison target with the waveguide plane line converter shown in FIG. 19. 図２０に示す導波管平面線路変換器における電磁波の通過位相の電磁界解析を示す説明図である。It is explanatory drawing which shows the electromagnetic field analysis of the passage phase of the electromagnetic wave in the waveguide plane line converter shown in FIG. 図２０に示す導波管平面線路変換器における電磁波の反射振幅の電磁界解析を示す説明図である。It is explanatory drawing which shows the electromagnetic field analysis of the reflection amplitude of the electromagnetic wave in the waveguide plane line converter shown in FIG.
　以下、この発明をより詳細に説明するために、この発明を実施するための形態について、添付の図面に従って説明する。 Hereinafter, in order to explain the present invention in more detail, modes for carrying out the present invention will be described with reference to the accompanying drawings.
実施の形態１．
　図１は、実施の形態１に係る導波管平面線路変換器を示す斜視透過図である。図２は、図１に示す導波管平面線路変換器の分解斜視透過図である。
　図３は、図１に示す導波管平面線路変換器の上面透過図である。
　図４は、図３に示す導波管平面線路変換器におけるｘ１－ｘ１’断面を示す断面図であり、図５は、図３に示す導波管平面線路変換器におけるｘ２－ｘ２’断面を示す断面図である。 Embodiment 1.
FIG. 1 is a perspective transparent view showing a waveguide plane line converter according to the first embodiment. FIG. 2 is an exploded perspective transparent view of the waveguide plane line converter shown in FIG.
FIG. 3 is a top transparent view of the waveguide plane line converter shown in FIG.
Figure 4 is a sectional view showing the x 1 -x 1 'cross-section in the waveguide planar line converter shown in FIG. 3, FIG. 5 is x 2 -x in waveguide planar line converter shown in FIG. 3 it is a sectional view showing a 2 'section.
　図６は、図３に示す導波管平面線路変換器におけるｘ３－ｘ３’断面を示す断面図であり、図７は、図３に示す導波管平面線路変換器におけるｘ４－ｘ４’断面を示す断面図である。
　図８は、図３に示す導波管平面線路変換器におけるｘ５－ｘ５’断面を示す断面図であり、図９は、図３に示す導波管平面線路変換器におけるｘ６－ｘ６’断面を示す断面図である。
　図１０は、図３に示す導波管平面線路変換器におけるｘ７－ｘ７’断面を示す断面図であり、図１１は、図３に示す導波管平面線路変換器におけるｘ８－ｘ８’断面を示す断面図である。
　図１２は、図３に示す導波管平面線路変換器におけるｘ９－ｘ９’断面を示す断面図である。 Figure 6 is a sectional view showing the x 3 -x 3 'section of waveguide planar line converter shown in FIG. 3, FIG. 7, x 4 -x in waveguide planar line converter shown in FIG. 3 4 'is a cross-sectional view showing a cross section.
8 is a sectional view showing a section taken along line x 5 -x 5 ′ in the waveguide plane line converter shown in FIG. 3, and FIG. 9 is a sectional view taken along line x 6 -x in the waveguide plane line converter shown in FIG. 6 'is a cross-sectional view showing a cross section.
10 is a sectional view showing a section taken along line x 7 -x 7 ′ in the waveguide plane line converter shown in FIG. 3, and FIG. 11 is a sectional view taken along line x 8 -x in the waveguide plane line converter shown in FIG. 8 'is a cross-sectional view showing a cross section.
FIG. 12 is a sectional view showing an x 9 -x 9 ′ section in the waveguide plane line converter shown in FIG.
　図１から図１２において、方形導波管１は、第１の金属ブロック１ａと、第２の金属ブロック１ｂとを備えている。
　第１の金属ブロック１ａと第２の金属ブロック１ｂとの間には、空間３ａ及び空間３ｂのそれぞれが形成されるように、第１の金属ブロック１ａと第２の金属ブロック１ｂとが接続されている。
　空間３ａは、方形導波管１における第１の開口２ａ側の管路である。
　空間３ｂは、方形導波管１における第２の開口２ｂ側の管路である。
　空間３ｂは、空間３ｃを含んでおり、空間３ｃは、図８に示すように、第２の開口２ｂ側の管路の内壁面１ａ’とポスト壁導波路６との間の空間である。
　第１の開口２ａ側の管路におけるｙ－ｚ面と平行な方向の断面形状と、第２の開口２ｂ側の管路におけるｙ－ｚ面と平行な方向の断面形状である第２の断面形状とが、異なっている。
　例えば、ｘ１－ｘ１’断面、ｘ２－ｘ２’断面及びｘ３－ｘ３’断面（図３を参照）におけるそれぞれの空間３ａの形状は、第１の断面形状である。
　例えば、ｘ４－ｘ４’断面及びｘ５－ｘ５’断面（図３を参照）におけるそれぞれの空間３ｂの形状は、第２の断面形状である。第２の断面形状は、長手方向が５ａで、短手方向が５ｂの矩形である。 1 to 12, the rectangular waveguide 1 includes a first metal block 1a and a second metal block 1b.
The first metal block 1a and the second metal block 1b are connected between the first metal block 1a and the second metal block 1b so that the space 3a and the space 3b are formed. ing.
The space 3a is a conduit on the side of the first opening 2a in the rectangular waveguide 1.
The space 3b is a conduit on the side of the second opening 2b in the rectangular waveguide 1.
The space 3b includes a space 3c, and the space 3c is a space between the inner wall surface 1a′ of the conduit on the second opening 2b side and the post wall waveguide 6, as shown in FIG.
A second cross section that is a cross-sectional shape in the direction parallel to the yz plane in the first opening 2a side and a cross-sectional shape in the direction parallel to the yz plane in the second opening 2b side conduit. The shape is different.
For example, the shape of each space 3a in the x 1 -x 1 ′ cross section, the x 2 −x 2 ′ cross section, and the x 3 −x 3 ′ cross section (see FIG. 3) is the first cross sectional shape.
For example, the shape of the respective spaces 3b in x 4 -x 4 'cross-section and x 5 -x 5' section (see Figure 3) is a second cross-sectional shape. The second cross-sectional shape is a rectangle having a longitudinal direction of 5a and a lateral direction of 5b.
　第１の断面形状における長手方向４ａと短手方向４ｂとは、図４から図６に示すように、互いに直交している。
　第２の断面形状における長手方向５ａと短手方向５ｂとは、図７及び図８に示すように、互いに直交している。
　第１の断面形状の長手方向４ａと、第２の断面形状の短手方向５ｂとは、図４から図８に示すように、互いに平行に配置されている。
　第１の断面形状の短手方向４ｂと、第２の断面形状の長手方向５ａとは、図４から図８に示すように、互いに平行に配置されている。 The longitudinal direction 4a and the lateral direction 4b in the first cross-sectional shape are orthogonal to each other, as shown in FIGS. 4 to 6.
The longitudinal direction 5a and the lateral direction 5b in the second cross-sectional shape are orthogonal to each other, as shown in FIGS.
The longitudinal direction 4a of the first cross-sectional shape and the lateral direction 5b of the second cross-sectional shape are arranged parallel to each other, as shown in FIGS. 4 to 8.
The short-side direction 4b of the first cross-sectional shape and the longitudinal direction 5a of the second cross-sectional shape are arranged in parallel with each other, as shown in FIGS. 4 to 8.
　ポスト壁導波路６の一部は、図７及び図８に示すように、ｙ－ｚ面における長手方向が、第２の断面形状の長手方向５ａと平行になるように、空間３ｂに配置されている。ポスト壁導波路６は、図９に示すように、方形導波管１における第２の開口２ｂの外側まで延びていてもよい。
　ポスト壁導波路６は、誘電体基板７と、第１の接地導体８と、第２の接地導体９と、第１の柱状導体１０と、第２の柱状導体１１とを備えている。
　誘電体基板７は、空間３ｂでは、ｙ－ｚ面における長手方向が、長手方向５ａと平行になるように配置され、空間３ａの一部では、ｙ－ｚ面における長手方向が、第１の断面形状の短手方向４ｂと平行になるように配置されている。また、誘電体基板７は、方形導波管１における第２の開口２ｂの外側では、ｙ－ｚ面における長手方向が、ｙ軸方向と平行になるように配置されている。
　第１の平面７ａは、誘電体基板７における２つのｘ－ｙ面のうち、－ｚ軸方向側のｘ－ｙ面である。
　第２の平面７ｂは、誘電体基板７における２つのｘ－ｙ面のうち、＋ｚ軸方向側のｘ－ｙ面である。
　第１の接地導体８は、誘電体基板７の第１の平面７ａに形成されている。
　第２の接地導体９は、誘電体基板７の第２の平面７ｂに形成されている。誘電体基板７は、第２の接地導体９が第２の金属ブロック１ｂと接するように配置されている。 As shown in FIGS. 7 and 8, a part of the post wall waveguide 6 is arranged in the space 3b such that the longitudinal direction in the yz plane is parallel to the longitudinal direction 5a of the second cross-sectional shape. ing. The post wall waveguide 6 may extend to the outside of the second opening 2b in the rectangular waveguide 1, as shown in FIG.
The post wall waveguide 6 includes a dielectric substrate 7, a first ground conductor 8, a second ground conductor 9, a first columnar conductor 10, and a second columnar conductor 11.
In the space 3b, the dielectric substrate 7 is arranged such that the longitudinal direction in the yz plane is parallel to the longitudinal direction 5a, and in a part of the space 3a, the longitudinal direction in the yz plane is the first. It is arranged so as to be parallel to the lateral direction 4b of the cross-sectional shape. Further, the dielectric substrate 7 is arranged outside the second opening 2b in the rectangular waveguide 1 so that the longitudinal direction in the yz plane is parallel to the y-axis direction.
The first plane 7a is the xy plane on the −z axis direction side of the two xy planes on the dielectric substrate 7.
The second plane 7b is the xy plane on the +z axis direction side of the two xy planes on the dielectric substrate 7.
The first ground conductor 8 is formed on the first plane 7 a of the dielectric substrate 7.
The second ground conductor 9 is formed on the second plane 7b of the dielectric substrate 7. The dielectric substrate 7 is arranged so that the second ground conductor 9 is in contact with the second metal block 1b.
　第１の柱状導体１０は、第１の接地導体８と第２の接地導体９との間を導通させている。
　第１の柱状導体１０は、複数存在しており、複数の第１の柱状導体１０は、ほぼｘ軸方向に沿って並べて配置されている。
　第２の柱状導体１１は、第１の柱状導体１０よりも＋ｙ軸方向側に配置されており、第１の接地導体８と第２の接地導体９との間を導通させている。
　第２の柱状導体１１は、複数存在しており、複数の第２の柱状導体１１は、ほぼｘ軸方向に沿って並べて配置されている。
　ポスト壁導波路６の導波路幅６ａは、第１の柱状導体１０と第２の柱状導体１１との間の長さである。
　ネジ１２ａ，１２ｂは、誘電体基板７を第２の金属ブロック１ｂに固定するための部材である。 The first columnar conductor 10 electrically connects between the first ground conductor 8 and the second ground conductor 9.
There are a plurality of first columnar conductors 10, and the plurality of first columnar conductors 10 are arranged side by side substantially along the x-axis direction.
The second columnar conductor 11 is arranged on the +y-axis direction side of the first columnar conductor 10, and electrically connects the first ground conductor 8 and the second ground conductor 9.
There are a plurality of second columnar conductors 11, and the plurality of second columnar conductors 11 are arranged side by side substantially along the x-axis direction.
The waveguide width 6 a of the post wall waveguide 6 is the length between the first columnar conductor 10 and the second columnar conductor 11.
The screws 12a and 12b are members for fixing the dielectric substrate 7 to the second metal block 1b.
　平衡プローブ１３は、第１のプローブ１３ａと、第２のプローブ１３ｂとを備えている。
　平衡プローブ１３は、先端が空間３ａに配置され、基端がポスト壁導波路６における第１の開口２ａ側の端部と接続されている。
　第１のプローブ１３ａは、先端が空間３ａに配置され、基端が第１の接地導体８における第１の開口２ａ側の端部８ａと接続されるように、誘電体基板７のうち、空間３ａに配置されている部分の誘電体基板７の第１の平面７ａに形成されている。
　第１のプローブ１３ａの先端は、－ｘ軸側の端部であり、第１のプローブ１３ａの基端は、＋ｘ軸側の端部である。
　第２のプローブ１３ｂは、先端が空間３ａに配置され、基端が第２の接地導体９における第１の開口２ａ側の端部９ａと接続されるように、誘電体基板７のうち、空間３ａに配置されている部分の誘電体基板７の第２の平面７ｂに形成されている。
　第２のプローブ１３ｂの先端は、－ｘ軸側の端部であり、第２のプローブ１３ｂの基端は、＋ｘ軸側の端部である。
　第１のプローブ１３ａの基端のｙ軸方向の位置と、第２のプローブ１３ｂの基端のｙ軸方向の位置とは、ほぼ同じ位置である。
　第１のプローブ１３ａにおける先端のｙ軸方向の位置と、第２のプローブ１３ｂにおける先端のｙ軸方向の位置とは、異なる位置であり、第１のプローブ１３ａと第２のプローブ１３ｂとは、基端から先端の方向に向かうほど、互いの間の距離が広がっている。 The balanced probe 13 includes a first probe 13a and a second probe 13b.
The balance probe 13 has a tip arranged in the space 3a and a base end connected to the end of the post wall waveguide 6 on the first opening 2a side.
Of the dielectric substrate 7, the space of the dielectric substrate 7 is arranged so that the tip of the first probe 13a is arranged in the space 3a and the base of the first probe 13a is connected to the end 8a of the first ground conductor 8 on the side of the first opening 2a. It is formed on the first flat surface 7a of the dielectric substrate 7 in the portion arranged on 3a.
The tip of the first probe 13a is an end on the −x axis side, and the base end of the first probe 13a is an end on the +x axis side.
The second probe 13b has a distal end arranged in the space 3a and a proximal end connected to the end portion 9a of the second ground conductor 9 on the first opening 2a side. It is formed on the second plane 7b of the dielectric substrate 7 in the portion arranged on 3a.
The tip of the second probe 13b is an end on the −x axis side, and the base end of the second probe 13b is an end on the +x axis side.
The position of the base end of the first probe 13a in the y-axis direction is substantially the same as the position of the base end of the second probe 13b in the y-axis direction.
The position of the tip of the first probe 13a in the y-axis direction is different from the position of the tip of the second probe 13b in the y-axis direction, and the first probe 13a and the second probe 13b are The distance from each other increases in the direction from the proximal end to the distal end.
　平面線路１４は、信号線導体１４ａと、接地導体１４ｂとを備えている。平面線路１４は、方形導波管１における第２の開口２ｂの外側に配置され、一端がポスト壁導波路６における第２の開口２ｂ側の端部と接続されている。
　信号線導体１４ａは、例えば、マイクロストリップ線路によって実現されている。
　信号線導体１４ａは、誘電体基板７のうち、第２の開口２ｂの外側に配置されている部分の誘電体基板７の第１の平面７ａに形成されている。
　接地導体１４ｂは、誘電体基板７のうち、第２の開口２ｂの外側に配置されている部分の誘電体基板７の第２の平面７ｂに形成されている。
　ネジ１５ａ，１５ｂは、誘電体基板７のうち、第２の開口２ｂの外側に配置されている部分の誘電体基板７を第２の金属ブロック１ｂに固定するための部材である。 The plane line 14 includes a signal line conductor 14a and a ground conductor 14b. The plane line 14 is arranged outside the second opening 2b in the rectangular waveguide 1, and one end thereof is connected to the end of the post wall waveguide 6 on the side of the second opening 2b.
The signal line conductor 14a is realized by, for example, a microstrip line.
The signal line conductor 14a is formed on the first plane 7a of the dielectric substrate 7 in a portion of the dielectric substrate 7 that is arranged outside the second opening 2b.
The ground conductor 14b is formed on the second plane 7b of the dielectric substrate 7 in a portion of the dielectric substrate 7 that is arranged outside the second opening 2b.
The screws 15a and 15b are members for fixing the portion of the dielectric substrate 7, which is arranged outside the second opening 2b, of the dielectric substrate 7 to the second metal block 1b.
　空間１６ａは、ネジ１２ａが第１の金属ブロック１ａと接触しないように形成された空洞である。
　空間１６ｂは、ネジ１２ｂが第１の金属ブロック１ａと接触しないように形成された空洞である。 The space 16a is a cavity formed so that the screw 12a does not come into contact with the first metal block 1a.
The space 16b is a cavity formed so that the screw 12b does not come into contact with the first metal block 1a.
　第１の断面形状の長手方向４ａの寸法は、方形導波管１により伝搬される電磁波の半波長以上の長さである。
　第２の断面形状の長手方向５ａの寸法は、方形導波管１により伝搬される電磁波の半波長以下の長さである。
　ポスト壁導波路６の導波路幅６ａは、方形導波管１により伝搬される電磁波の実効波長の半波長以上の長さである。
　なお、ポスト壁導波路６は、誘電体基板７を有しており、電磁波が誘電体基板７を通るので、実効波長は、空間３ａ等の空間を通る電磁波の波長よりも短くなる。
　空間３ｂを形成している第１の金属ブロック１ａの内壁面のうち、ポスト壁導波路６と対向している内壁面１ａ’と、ポスト壁導波路６における第１の接地導体８との間の長さ５ｃは、誘電体基板７の基板厚の半分以上の長さである。
　誘電体基板７の基板厚は、誘電体基板７の厚さのほかに、第１の接地導体８の導体厚及び第２の接地導体９の導体厚のそれぞれを含んでいるものとする。 The dimension of the first cross-sectional shape in the longitudinal direction 4a is equal to or longer than a half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1.
The dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than a half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1.
The waveguide width 6a of the post wall waveguide 6 is a length equal to or longer than half the effective wavelength of the electromagnetic wave propagated by the rectangular waveguide 1.
Since the post wall waveguide 6 has the dielectric substrate 7 and the electromagnetic wave passes through the dielectric substrate 7, the effective wavelength is shorter than the wavelength of the electromagnetic wave passing through the space such as the space 3a.
Among the inner wall surfaces of the first metal block 1a forming the space 3b, between the inner wall surface 1a′ facing the post wall waveguide 6 and the first ground conductor 8 in the post wall waveguide 6. 5c is more than half the thickness of the dielectric substrate 7.
The substrate thickness of the dielectric substrate 7 is assumed to include the conductor thickness of the first ground conductor 8 and the conductor thickness of the second ground conductor 9 in addition to the thickness of the dielectric substrate 7.
　次に、図１に示す導波管平面線路変換器の動作について説明する。
　第１の断面形状の長手方向４ａと、第２の断面形状の短手方向５ｂとは、図４から図８に示すように、互いに平行に配置されている。
　また、第１の断面形状の短手方向４ｂと、第２の断面形状の長手方向５ａとは、図４から図８に示すように、互いに平行に配置されている。
　したがって、空間３ａにおける広壁面と、空間３ｂにおける広壁面とが直交しており、空間３ａにおける狭壁面と、空間３ｂにおける狭壁面とが直交している。また、空間３ｂには、ポスト壁導波路６が配置されている。
　よって、空間３ａにおける基本モードは、ＴＥ０１モードであり、空間３ｂにおける基本モードは、ＴＥ１０モードである。ＴＥ０１モードとＴＥ１０モードとは、互いに直交しているモードであるため、ＴＥ０１モードとＴＥ１０モードとの結合は、小さい。
　ＴＥ０１モードとＴＥ１０モードとの結合が小さいため、方形導波管１における第２の開口２ｂから外部への電磁波の漏れを防止することができる。 Next, the operation of the waveguide plane line converter shown in FIG. 1 will be described.
The longitudinal direction 4a of the first cross-sectional shape and the lateral direction 5b of the second cross-sectional shape are arranged parallel to each other, as shown in FIGS. 4 to 8.
Further, the lateral direction 4b of the first cross-sectional shape and the longitudinal direction 5a of the second cross-sectional shape are arranged in parallel with each other, as shown in FIGS. 4 to 8.
Therefore, the wide wall surface in the space 3a and the wide wall surface in the space 3b are orthogonal to each other, and the narrow wall surface in the space 3a and the narrow wall surface in the space 3b are orthogonal to each other. The post wall waveguide 6 is arranged in the space 3b.
Therefore, the basic mode in the space 3a is the TE01 mode, and the basic mode in the space 3b is the TE10 mode. Since the TE01 mode and the TE10 mode are modes orthogonal to each other, the coupling between the TE01 mode and the TE10 mode is small.
Since the coupling between the TE01 mode and the TE10 mode is small, it is possible to prevent the electromagnetic wave from leaking from the second opening 2b in the rectangular waveguide 1 to the outside.
　そして、第１の断面形状の長手方向４ａの寸法が、方形導波管１により伝搬される電磁波の半波長以上の長さであるため、外部から第１の開口２ａに入力された電磁波は、ＴＥ０１モードで空間３ａを伝搬される。
　空間３ａでのＴＥ０１モードは、空間３ａに配置されている平衡プローブ１３である第１のプローブ１３ａ及び第２のプローブ１３ｂによって、平衡線路として、第１の接地導体８及び第２の接地導体９を有している、ポスト壁導波路６の伝搬が可能なモードに変換される。
　ポスト壁導波路６の導波路幅６ａは、当該電磁波の実効波長の半波長以上の長さであるため、当該電磁波は、ＴＥ１０モードでポスト壁導波路６を伝搬される。 Since the dimension of the first cross-sectional shape in the longitudinal direction 4a is equal to or longer than the half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1, the electromagnetic wave input from the outside into the first opening 2a is It is propagated in the space 3a in the TE01 mode.
In the TE01 mode in the space 3a, the first probe 13a and the second probe 13b, which are the balanced probes 13 arranged in the space 3a, cause the first ground conductor 8 and the second ground conductor 9 as a balanced line. Is converted into a mode capable of propagating in the post wall waveguide 6.
Since the waveguide width 6a of the post wall waveguide 6 is a length equal to or longer than a half wavelength of the effective wavelength of the electromagnetic wave, the electromagnetic wave propagates through the post wall waveguide 6 in the TE10 mode.
　一方、第２の断面形状の長手方向５ａの寸法は、方形導波管１により伝搬される電磁波の半波長以下の長さであるため、空間３ｂは、当該電磁波の周波数において、遮断構造である。したがって、当該電磁波は、空間３ｂ内では実質的に伝搬されない。
　方形導波管１における第２の開口２ｂの外側に配置されている平面線路１４の一端が、ポスト壁導波路６のｙ軸方向の中央部と接続されているため、ポスト壁導波路６を伝搬された電磁波は、準ＴＥＭモードで平面線路１４を伝搬される。 On the other hand, the dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than the half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1, so the space 3b has a blocking structure at the frequency of the electromagnetic wave. .. Therefore, the electromagnetic wave is not substantially propagated in the space 3b.
Since one end of the planar line 14 arranged outside the second opening 2b in the rectangular waveguide 1 is connected to the central portion of the post wall waveguide 6 in the y-axis direction, the post wall waveguide 6 is The propagated electromagnetic wave propagates through the plane line 14 in the quasi-TEM mode.
　図１３は、空間３ｂをＴＥ１０モードで伝搬される電磁波の減衰定数の電磁界解析結果を示す説明図である。
　電磁界解析には、有限要素法が用いられている。図１３の横軸は、方形導波管１により伝搬される電磁波の中心周波数であり、電磁波の中心周波数は、９．７ＧＨｚ帯であるＸ帯によって規格化されている。図１３の縦軸は、ＴＥ１０モードで伝搬される電磁波の減衰定数［Ｎ・ｓ／ｍ］である。
　電磁界解析においては、第１の接地導体８の導体厚と、第２の接地導体９の導体厚とを含む誘電体基板７の基板厚を０．５４［ｍｍ］で固定している。
　また、電磁界解析においては、図８に示す長さ５ｃを、０．２［ｍｍ］～０．８［ｍｍ］の範囲としている。
　図１３において、３０は長さ５ｃが０．２［ｍｍ］の場合の解析結果を示し、３１は長さ５ｃが０．２７［ｍｍ］の場合の解析結果を示し、３２は長さ５ｃが０．３［ｍｍ］の場合の解析結果を示し、３３は長さ５ｃが０．４［ｍｍ］の場合の解析結果を示し、３４は長さ５ｃが０．５［ｍｍ］の場合の解析結果を示し、３５は長さ５ｃが０．６［ｍｍ］の場合の解析結果を示し、３６は長さ５ｃが０．７［ｍｍ］の場合の解析結果を示し、３７は長さ５ｃが０．８［ｍｍ］の場合の解析結果を示している。
　解析結果３１に係る０．２７［ｍｍ］の長さ５ｃは、誘電体基板７の基板厚である０．５４［ｍｍ］の半分の長さである。 FIG. 13 is an explanatory diagram showing an electromagnetic field analysis result of an attenuation constant of an electromagnetic wave propagating in the space 3b in the TE10 mode.
The finite element method is used for electromagnetic field analysis. The horizontal axis of FIG. 13 is the center frequency of the electromagnetic wave propagated by the rectangular waveguide 1, and the center frequency of the electromagnetic wave is standardized by the X band which is the 9.7 GHz band. The vertical axis of FIG. 13 is the attenuation constant [N·s/m] of the electromagnetic wave propagated in the TE10 mode.
In the electromagnetic field analysis, the substrate thickness of the dielectric substrate 7 including the conductor thickness of the first ground conductor 8 and the conductor thickness of the second ground conductor 9 is fixed at 0.54 [mm].
Further, in the electromagnetic field analysis, the length 5c shown in FIG. 8 is set in the range of 0.2 [mm] to 0.8 [mm].
In FIG. 13, 30 indicates the analysis result when the length 5c is 0.2 [mm], 31 indicates the analysis result when the length 5c is 0.27 [mm], and 32 indicates the length 5c. The analysis result when 0.3 [mm] is shown, 33 shows the analysis result when the length 5c is 0.4 [mm], and 34 shows the analysis when the length 5c is 0.5 [mm]. The result is shown, 35 shows the analysis result when the length 5c is 0.6 [mm], 36 shows the analysis result when the length 5c is 0.7 [mm], and 37 shows the length 5c. The analysis result in the case of 0.8 [mm] is shown.
The length 5c of 0.27 [mm] according to the analysis result 31 is half the length of 0.54 [mm] that is the substrate thickness of the dielectric substrate 7.
　長さ５ｃが誘電体基板７の基板厚の半分の長さよりも短い０．２［ｍｍ］の場合は、解析結果３０が示すように、規格化周波数が１の減衰定数は、約０［Ｎ・ｓ／ｍ］である。したがって、誘電体基板７を含む空間３ｂは、規格化周波数が１の電磁波を遮断することができない。
　長さ５ｃが誘電体基板７の基板厚の半分以上の長さの場合は、解析結果３１～３７が示すように、規格化周波数が１の減衰定数は、約５０以上［Ｎ・ｓ／ｍ］である。したがって、誘電体基板７を含む空間３ｂは、規格化周波数が１の電磁波を実質的に遮断することができる。 When the length 5c is 0.2 [mm], which is shorter than the half of the substrate thickness of the dielectric substrate 7, as shown by the analysis result 30, the attenuation constant at the normalized frequency 1 is about 0 [N]. -S/m]. Therefore, the space 3b including the dielectric substrate 7 cannot block the electromagnetic wave having the normalized frequency of 1.
When the length 5c is more than half of the substrate thickness of the dielectric substrate 7, as shown by the analysis results 31 to 37, the attenuation constant at the normalized frequency 1 is about 50 or more [N·s/m]. ]. Therefore, the space 3b including the dielectric substrate 7 can substantially block the electromagnetic wave having the normalized frequency of 1.
　実施の形態１の導波管平面線路変換器は、第２の断面形状の長手方向５ａの寸法が、方形導波管１により伝搬される電磁波の半波長以下の長さであり、かつ、長さ５ｃが誘電体基板７の基板厚の半分以上の長さである。
　したがって、当該電磁波は、ポスト壁導波路６を除く空間３ｂをＴＥ１０モードでほとんど伝搬されないが、ポスト壁導波路６をＴＥ１０モードで伝搬される。 In the waveguide plane line converter according to the first embodiment, the dimension of the second cross-sectional shape in the longitudinal direction 5a is equal to or less than the half wavelength of the electromagnetic wave propagated by the rectangular waveguide 1, and The length 5c is more than half the thickness of the dielectric substrate 7.
Therefore, the electromagnetic wave is hardly propagated in the TE10 mode in the space 3b except the post wall waveguide 6, but is propagated in the TE10 mode in the post wall waveguide 6.
　図１４は、図１に示す導波管平面線路変換器における電磁波の反射振幅の電磁界解析結果を示す説明図である。
　電磁界解析には、有限要素法が用いられている。図１４の横軸は、方形導波管１により伝搬される電磁波の中心周波数であり、電磁波の中心周波数は、Ｘ帯によって規格化されている。図１４の縦軸は、当該電磁波の反射振幅［ｄＢ］である。
　電磁界解析において、長さ５ｃは、０．５［ｍｍ］であるとしている。
　反射振幅が－２０［ｄＢ］の比帯域幅は、規格化周波数が約０．９５～１．０５の範囲であり、規格化周波数が約０．９５～１．０５の範囲では、反射振幅が約－２０～－４０［ｄＢ］の範囲である。したがって、規格化周波数が約０．９５～１．０５の範囲では、方形導波管１により伝搬される電磁波の反射が十分に小さいことが分かる。 FIG. 14 is an explanatory diagram showing an electromagnetic field analysis result of a reflection amplitude of an electromagnetic wave in the waveguide plane line converter shown in FIG.
The finite element method is used for electromagnetic field analysis. The horizontal axis of FIG. 14 is the center frequency of the electromagnetic wave propagated by the rectangular waveguide 1, and the center frequency of the electromagnetic wave is standardized by the X band. The vertical axis of FIG. 14 is the reflection amplitude [dB] of the electromagnetic wave.
In the electromagnetic field analysis, the length 5c is 0.5 [mm].
The specific bandwidth of the reflection amplitude of -20 [dB] is in the range of the normalized frequency of about 0.95 to 1.05, and the reflection amplitude is in the range of the normalized frequency of about 0.95 to 1.05. It is in the range of about −20 to −40 [dB]. Therefore, it is understood that the reflection of the electromagnetic wave propagated by the rectangular waveguide 1 is sufficiently small when the normalized frequency is in the range of about 0.95 to 1.05.
　以上の実施の形態１は、第１の開口２ａ側の管路における断面形状である第１の断面形状と、第２の開口２ｂ側の管路における断面形状である第２の断面形状とが異なり、第１の断面形状の長手方向４ａと第２の断面形状の短手方向５ｂとが平行に配置され、第１の断面形状の短手方向４ｂと第２の断面形状の長手方向５ａとが平行に配置されている方形導波管１を備えるように、導波管平面線路変換器を構成した。したがって、導波管平面線路変換器は、閉鎖導体を用いることなく、外部への電磁波の漏れを防止することができる。 In the first embodiment described above, the first cross-sectional shape that is the cross-sectional shape of the pipeline on the first opening 2a side and the second cross-sectional shape that is the cross-sectional shape of the pipeline on the second opening 2b side are Differently, the longitudinal direction 4a of the first sectional shape and the lateral direction 5b of the second sectional shape are arranged in parallel, and the lateral direction 4b of the first sectional shape and the longitudinal direction 5a of the second sectional shape are arranged. The waveguide plane line converter was configured so as to include the rectangular waveguides 1 arranged in parallel with each other. Therefore, the waveguide plane line converter can prevent electromagnetic waves from leaking to the outside without using a closed conductor.
実施の形態２．
　実施の形態２では、第１の金属ブロック１ａと第１の接地導体８との間を導通させる導通部材４０を備える導波管平面線路変換器について説明する。
　図１５は、実施の形態２に係る導波管平面線路変換器を示す断面図である。
　図１５に示す導波管平面線路変換器におけるｙ１－ｙ１’断面は、図３に示す導波管平面線路変換器におけるｙ１－ｙ１’断面に対応している。
　図１５において、図１から図１２と同一符号は同一又は相当部分を示すので説明を省略する。
　導通部材４０は、導電性のスポンジ又は導電性のボンド等によって実現される。
　導通部材４０は、空間３ｂの一部に設けられており、第１の金属ブロック１ａと第１の接地導体８との間を導通させている。
　導通部材４０は、ｙ軸方向の位置が、例えば、平面線路１４のｙ軸方向の位置に配置される。
　空間３ｂの一部に設けられる導通部材４０の数は、１つでもよいし、複数でもよい。 Embodiment 2.
In the second embodiment, a waveguide plane line converter including a conducting member 40 that conducts conduction between the first metal block 1a and the first ground conductor 8 will be described.
FIG. 15 is a sectional view showing a waveguide plane line converter according to the second embodiment.
Y 1 -y 1 in waveguide planar line converter shown in FIG. 15 'cross section, y 1 -y 1 in waveguide planar line converter shown in FIG. 3' corresponds to the cross-section.
In FIG. 15, the same reference numerals as those in FIGS. 1 to 12 indicate the same or corresponding portions, and thus the description thereof will be omitted.
The conductive member 40 is realized by a conductive sponge, a conductive bond, or the like.
The conductive member 40 is provided in a part of the space 3b, and electrically connects the first metal block 1a and the first ground conductor 8 to each other.
The conductive member 40 is arranged such that the position in the y-axis direction is, for example, the position in the y-axis direction on the plane line 14.
The number of the conducting members 40 provided in a part of the space 3b may be one or plural.
　導通部材４０は、空間３ｂの全体を遮蔽する閉鎖導体ではない。しかし、導通部材４０は、例えば、電磁波を反射させる遮蔽部材として作用するため、電磁波を遮蔽することができる。
　したがって、実施の形態２の導波管平面線路変換器は、実施の形態１の導波管平面線路変換器よりも更に、外部へ漏洩する電磁波を抑圧することができる。 The conducting member 40 is not a closed conductor that shields the entire space 3b. However, since the conductive member 40 acts as a shielding member that reflects electromagnetic waves, it can shield electromagnetic waves.
Therefore, the waveguide plane line converter of the second embodiment can further suppress electromagnetic waves leaking to the outside than the waveguide plane line converter of the first embodiment.
実施の形態３．
　実施の形態３では、導波管平面線路変換器を備える送信系の高周波モジュールについて説明する。
　図１６は、実施の形態３に係る高周波モジュールを示す断面図である。
　図１６に示す高周波モジュールは、導波管平面線路変換器を含んでおり、当該導波管平面線路変換器におけるｙ１－ｙ１’断面は、図３に示す導波管平面線路変換器におけるｙ１－ｙ１’断面に対応している。
　図１６において、図１から図１２と同一符号は同一又は相当部分を示すので説明を省略する。
　空間５１は、高周波増幅器５５及びアイソレータ５６を設けるために、第１の金属ブロック１ａと第２の金属ブロック１ｂとによって形成されている。
　誘電体基板５２は、一方の平面に接地導体５３が施され、他方の平面に接地導体５４が施されている。誘電体基板５２は、接地導体５４が第２の金属ブロック１ｂと接するように、空間５１に配置されている。 Embodiment 3.
In the third embodiment, a high frequency module of a transmission system including a waveguide plane line converter will be described.
FIG. 16 is a cross-sectional view showing the high frequency module according to the third embodiment.
The high-frequency module shown in FIG. 16 includes a waveguide plane line converter, and the y 1 -y 1 ′ cross section of the waveguide plane line converter is the same as that of the waveguide plane line converter shown in FIG. corresponds to y 1 -y 1 'section.
16, the same reference numerals as those in FIGS. 1 to 12 indicate the same or corresponding portions, and thus the description thereof is omitted.
The space 51 is formed by the first metal block 1a and the second metal block 1b in order to provide the high frequency amplifier 55 and the isolator 56.
The dielectric substrate 52 has a ground conductor 53 on one plane and a ground conductor 54 on the other plane. The dielectric substrate 52 is arranged in the space 51 so that the ground conductor 54 contacts the second metal block 1b.
　高周波増幅器５５は、誘電体基板５２の接地導体５３に設けられている。
　高周波増幅器５５は、平面線路１４を伝搬された電磁波がアイソレータ５６を通過してくると、当該電磁波を増幅する。
　アイソレータ５６は、誘電体基板７と高周波増幅器５５との間に位置するように、第２の金属ブロック１ｂに設けられている。
　アイソレータ５６は、順方向には電磁波を通過させるが、逆方向には電磁波を通過させない高周波部品である。
　アイソレータ５６は、準ＴＥＭモードで平面線路１４を伝搬された電磁波を通過させて、高周波増幅器５５から出力された電磁波の通過を阻止する。
　図１６に示す高周波モジュールでは、アイソレータ５６が、平面線路１４を伝搬された電磁波を通過させて、高周波増幅器５５から出力された電磁波の通過を阻止している。しかし、これは一例に過ぎず、高周波増幅器５５から出力された電磁波を通過させて、平面線路１４を伝搬された電磁波の通過を阻止するアイソレータ５６であってもよい。
　放熱フィン５７は、高周波増幅器５５等から発生した熱を高周波モジュールの外部に放熱するために、空間５１を形成している第２の金属ブロック１ｂの内壁面１０１と対向している第２の金属ブロック１ｂの外壁面１０２に設けられている。 The high frequency amplifier 55 is provided on the ground conductor 53 of the dielectric substrate 52.
The high frequency amplifier 55 amplifies the electromagnetic wave propagated through the plane line 14 when the electromagnetic wave passes through the isolator 56.
The isolator 56 is provided on the second metal block 1b so as to be located between the dielectric substrate 7 and the high frequency amplifier 55.
The isolator 56 is a high frequency component that allows electromagnetic waves to pass in the forward direction but does not allow electromagnetic waves to pass in the reverse direction.
The isolator 56 allows the electromagnetic wave propagated through the plane line 14 in the quasi-TEM mode to pass therethrough, and blocks the electromagnetic wave output from the high frequency amplifier 55 from passing therethrough.
In the high frequency module shown in FIG. 16, the isolator 56 allows the electromagnetic waves propagated through the plane line 14 to pass therethrough and blocks the electromagnetic waves output from the high frequency amplifier 55 from passing therethrough. However, this is merely an example, and the isolator 56 that allows the electromagnetic wave output from the high-frequency amplifier 55 to pass therethrough and blocks the electromagnetic wave propagated through the planar line 14 may be used.
The heat dissipation fin 57 is a second metal facing the inner wall surface 101 of the second metal block 1b forming the space 51 in order to dissipate the heat generated from the high frequency amplifier 55 and the like to the outside of the high frequency module. It is provided on the outer wall surface 102 of the block 1b.
　図１６に示す高周波モジュールは、誘電体基板７と誘電体基板５２との間にアイソレータ５６を備えている。図１６に示す高周波モジュールは、アイソレータ５６を備えているため、高周波増幅器５５を備えても、準ＴＥＭモードで平面線路１４を伝搬される電磁波と、高周波増幅器５５により増幅される高周波との干渉を防ぐことができる。
　第２の金属ブロック１ｂの外壁面１０２には、第２の金属ブロック１ｂが設けられているため、高周波増幅器５５等から発生した熱は、高周波モジュールの外部に放熱される。
　図１６に示す高周波モジュールは、高周波増幅器５５及びアイソレータ５６を空間５１に設けている。したがって、図１６に示す高周波モジュールは、平面線路１４を伝搬される電磁波及び高周波増幅器５５により増幅される高周波のそれぞれが、高周波モジュールの外部に放射されることを防ぐことができる。 The high frequency module shown in FIG. 16 includes an isolator 56 between the dielectric substrate 7 and the dielectric substrate 52. Since the high-frequency module shown in FIG. 16 includes the isolator 56, even if the high-frequency amplifier 55 is provided, interference between the electromagnetic wave propagating through the plane line 14 in the quasi-TEM mode and the high-frequency amplified by the high-frequency amplifier 55 is prevented. Can be prevented.
Since the second metal block 1b is provided on the outer wall surface 102 of the second metal block 1b, the heat generated from the high frequency amplifier 55 and the like is radiated to the outside of the high frequency module.
In the high frequency module shown in FIG. 16, a high frequency amplifier 55 and an isolator 56 are provided in the space 51. Therefore, the high-frequency module shown in FIG. 16 can prevent each of the electromagnetic wave propagating through the plane line 14 and the high-frequency amplified by the high-frequency amplifier 55 from being radiated to the outside of the high-frequency module.
　図１６に示す高周波モジュールでは、高周波増幅器５５及びアイソレータ５６を設けるための空間５１が、第１の金属ブロック１ａと第２の金属ブロック１ｂとによって形成されている。
　しかし、これは一例に過ぎず、例えば、図１７に示すように、高周波増幅器５５及びアイソレータ５６を設けるための空間５１が、シールド部材５８によって形成されている高周波モジュールであってもよい。
　図１７は、実施の形態３に係る他の高周波モジュールを示す断面図である。
　シールド部材５８は、一端が第１の接地導体８と接続され、他端が接地導体５３と接続されており、高周波増幅器５５及びアイソレータ５６を覆っている。
　図１７に示す高周波モジュールは、シールド部材５８を備えているため、平面線路１４を伝搬される電磁波及び高周波増幅器５５により増幅される高周波のそれぞれが、高周波モジュールの外部に放射されることを防ぐことができる。 In the high frequency module shown in FIG. 16, the space 51 for providing the high frequency amplifier 55 and the isolator 56 is formed by the first metal block 1a and the second metal block 1b.
However, this is only an example, and for example, as shown in FIG. 17, a space 51 for providing the high frequency amplifier 55 and the isolator 56 may be a high frequency module formed by a shield member 58.
FIG. 17 is a sectional view showing another high-frequency module according to the third embodiment.
The shield member 58 has one end connected to the first ground conductor 8 and the other end connected to the ground conductor 53, and covers the high frequency amplifier 55 and the isolator 56.
Since the high frequency module shown in FIG. 17 includes the shield member 58, it is possible to prevent the electromagnetic wave propagating through the plane line 14 and the high frequency amplified by the high frequency amplifier 55 from being radiated to the outside of the high frequency module. You can
実施の形態４．
　実施の形態４では、第１の金属ブロック１ａの内壁面のうち、ポスト壁導波路６と対向している内壁面１ａ’に、チョーク構造６０が形成されている高周波モジュールについて説明する。
　図１８は、実施の形態４に係る高周波モジュールを示す断面図である。
　図１８に示す高周波モジュールは、導波管平面線路変換器を含んでおり、当該導波管平面線路変換器におけるｙ１－ｙ１’断面は、図３に示す導波管平面線路変換器におけるｙ１－ｙ１’断面に対応している。
　図１８において、図１から図１２、図１６及び図１７と同一符号は同一又は相当部分を示すので説明を省略する。
　チョーク構造６０は、第１の金属ブロック１ａの内壁面のうち、ポスト壁導波路６と対向している内壁面１ａ’に形成されている。
　チョーク構造６０の長さ６０ａは、チョーク構造６０の開口位置から、チョーク構造６０の底部６０ｂまでのｚ軸方向の長さであり、長さ６０ａは、空間３ｂの伝搬を抑圧したい電磁波の波長の４分の１の奇数倍の長さである。 Fourth Embodiment
In the fourth embodiment, a high frequency module in which a choke structure 60 is formed on an inner wall surface 1a′ of the first metal block 1a facing the post wall waveguide 6 will be described.
FIG. 18 is a sectional view showing the high frequency module according to the fourth embodiment.
The high-frequency module shown in FIG. 18 includes a waveguide plane line converter, and the section taken along line y 1 -y 1 ′ of the waveguide plane line converter is the same as that of the waveguide plane line converter shown in FIG. corresponds to y 1 -y 1 'section.
In FIG. 18, the same reference numerals as those in FIGS. 1 to 12, 16 and 17 indicate the same or corresponding parts, and thus the description thereof will be omitted.
The choke structure 60 is formed on the inner wall surface 1 a ′ of the first metal block 1 a facing the post wall waveguide 6 among the inner wall surfaces of the first metal block 1 a.
The length 60a of the choke structure 60 is the length in the z-axis direction from the opening position of the choke structure 60 to the bottom portion 60b of the choke structure 60, and the length 60a is the wavelength of the electromagnetic wave whose propagation in the space 3b is to be suppressed. The length is an odd multiple of 1/4.
　図１８に示す高周波モジュールに含まれている導波管平面線路変換器は、実施の形態１の導波管平面線路変換器と同様に、第２の断面形状の長手方向５ａの寸法が、方形導波管１により伝搬される電磁波の半波長以下の長さである。したがって、空間３ｂは、当該電磁波の周波数において、遮断構造である。
　当該電磁波の波長の４分の１の奇数倍の長さ６０ａを有するチョーク構造６０は、当該電磁波を抑圧するように作用する。
　したがって、図１８に示す高周波モジュールに含まれている導波管平面線路変換器は、実施の形態１の導波管平面線路変換器よりも更に、空間３ｂにおける当該電磁波の伝搬を抑えることができる。 The waveguide plane line converter included in the high-frequency module shown in FIG. 18 has a rectangular cross-section in the longitudinal direction 5a of the second cross-sectional shape, as in the waveguide plane line converter of the first embodiment. The length is equal to or less than a half wavelength of the electromagnetic wave propagated by the waveguide 1. Therefore, the space 3b has a blocking structure at the frequency of the electromagnetic wave.
The choke structure 60 having a length 60a that is an odd multiple of a quarter of the wavelength of the electromagnetic wave acts to suppress the electromagnetic wave.
Therefore, the waveguide plane line converter included in the high frequency module shown in FIG. 18 can further suppress the propagation of the electromagnetic wave in the space 3b as compared with the waveguide plane line converter of the first embodiment. ..
実施の形態５．
　実施の形態５では、実施の形態１～４の導波管平面線路変換器のうち、いずれかの実施の形態の導波管平面線路変換器を２つ備えている導波管平面線路変換器について説明する。
　図１９は、実施の形態５に係る導波管平面線路変換器を示す斜視透過図である。図１９において、図１と同一符号は同一又は相当部分を示すので説明を省略する。
　２つの導波管平面線路変換器のうち、一方の導波管平面線路変換器である第１の導波管平面線路変換器は、図中、分配合成器７０の左上に表記されている導波管平面線路変換器である。
　他方の導波管平面線路変換器である第２の導波管平面線路変換器は、図中、分配合成器７０の右下に表記されている導波管平面線路変換器である。 Embodiment 5.
In the fifth embodiment, among the waveguide plane line converters of the first to fourth embodiments, a waveguide plane line converter including two waveguide plane line converters according to any one of the embodiments. Will be described.
FIG. 19 is a perspective transparent view showing a waveguide plane line converter according to the fifth embodiment. 19, the same reference numerals as those in FIG. 1 indicate the same or corresponding portions, and thus the description thereof will be omitted.
Of the two waveguide plane line converters, the first waveguide plane line converter, which is one of the waveguide plane line converters, is a conductor shown in the upper left of the distributor/combiner 70 in the figure. It is a waveguide flat line converter.
The second waveguide plane line converter, which is the other waveguide plane line converter, is the waveguide plane line converter shown at the lower right of the distributor/combiner 70 in the figure.
　分配合成器７０は、入出力ポート７０ａ，７０ｂ，７０ｃを有するＥ面分岐のＴ型導波管である。
　分配合成器７０は、入出力ポート７０ａが第１の導波管平面線路変換器における方形導波管１の第１の開口２ａと接続され、入出力ポート７０ｂが第２の導波管平面線路変換器における方形導波管１の第１の開口２ａと接続されている。
　分配合成器７０は、第１の導波管平面線路変換器における方形導波管１の第１の開口２ａから入出力ポート７０ａに電磁波が入力されると、電磁波を２つに分岐して、一方の電磁波を入出力ポート７０ｂに出力し、他方の電磁波を入出力ポート７０ｃに出力する。入出力ポート７０ａに入力された電磁波の位相と、入出力ポート７０ｂ，７０ｃに出力された電磁波の位相とは、逆位相である。 The distributor/combiner 70 is an E-plane branch T-shaped waveguide having input/ output ports 70a, 70b, and 70c.
In the distributor/combiner 70, the input/output port 70a is connected to the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter, and the input/output port 70b is the second waveguide plane line. It is connected to the first opening 2a of the rectangular waveguide 1 in the converter.
The distributor/combiner 70 branches the electromagnetic wave into two when the electromagnetic wave is input to the input/output port 70a from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter, One electromagnetic wave is output to the input/output port 70b, and the other electromagnetic wave is output to the input/output port 70c. The phase of the electromagnetic wave input to the input/output port 70a and the phase of the electromagnetic wave output to the input/ output ports 70b and 70c are opposite phases.
　また、分配合成器７０は、第２の導波管平面線路変換器における方形導波管１の第１の開口２ａから入出力ポート７０ｂに電磁波が入力されると、電磁波を２つに分岐して、一方の電磁波を入出力ポート７０ａに出力し、他方の電磁波を入出力ポート７０ｃに出力する。入出力ポート７０ｂに入力された電磁波の位相と、入出力ポート７０ａ，７０ｃに出力された電磁波の位相とは、逆位相である。
　また、分配合成器７０は、入出力ポート７０ｃに電磁波が入力されると、電磁波を２つに分岐して、一方の電磁波を入出力ポート７０ａに出力し、他方の電磁波を入出力ポート７０ｂに出力する。入出力ポート７０ａに出力された電磁波の位相と、入出力ポート７０ｂに出力された電磁波の位相とは、逆位相である。 The distributor/combiner 70 branches the electromagnetic wave into two when the electromagnetic wave is input to the input/output port 70b from the first opening 2a of the rectangular waveguide 1 in the second waveguide plane line converter. One electromagnetic wave is output to the input/output port 70a, and the other electromagnetic wave is output to the input/output port 70c. The phase of the electromagnetic wave input to the input/output port 70b and the phase of the electromagnetic wave output to the input/ output ports 70a and 70c are opposite phases.
When an electromagnetic wave is input to the input/output port 70c, the distributor/combiner 70 branches the electromagnetic wave into two, outputs one electromagnetic wave to the input/output port 70a, and outputs the other electromagnetic wave to the input/output port 70b. Output. The phase of the electromagnetic wave output to the input/output port 70a and the phase of the electromagnetic wave output to the input/output port 70b are opposite phases.
　図１９に示す導波管平面線路変換器では、第１の導波管平面線路変換器における第１のプローブ１３ａと、第２の導波管平面線路変換器における第２のプローブ１３ｂとが、対向するように配置されている。
　また、第１の導波管平面線路変換器における第２のプローブ１３ｂと、第２の導波管平面線路変換器における第１のプローブ１３ａとが、対向するように配置されている。 In the waveguide plane line converter shown in FIG. 19, the first probe 13a in the first waveguide plane line converter and the second probe 13b in the second waveguide plane line converter are It is arranged so as to face each other.
Further, the second probe 13b in the first waveguide plane line converter and the first probe 13a in the second waveguide plane line converter are arranged so as to face each other.
　次に、図１９に示す導波管平面線路変換器の動作について説明する。
　図２０は、図１９に示す導波管平面線路変換器と比較対象となる導波管平面線路変換器を示す斜視透過図である。
　図２０に示す導波管平面線路変換器は、第１の導波管平面線路変換器における第１のプローブ１３ａと、第２の導波管平面線路変換器における第１のプローブ１３ａとが、対向するように配置されている。
　また、第１の導波管平面線路変換器における第２のプローブ１３ｂと、第２の導波管平面線路変換器における第２のプローブ１３ｂとが、対向するように配置されている。
　図２０に示す第１の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相と、第２の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相とが、同相であるものとする。
　図２０に示す導波管平面線路変換器では、第１の導波管平面線路変換器における方形導波管１の第１の開口２ａから出力された電磁波の位相と、第２の導波管平面線路変換器における方形導波管１の第１の開口２ａから出力された電磁波の位相とは、逆相になる。 Next, the operation of the waveguide plane line converter shown in FIG. 19 will be described.
20 is a perspective transparent view showing a waveguide plane line converter to be compared with the waveguide plane line converter shown in FIG.
In the waveguide plane line converter shown in FIG. 20, the first probe 13a in the first waveguide plane line converter and the first probe 13a in the second waveguide plane line converter are It is arranged so as to face each other.
Further, the second probe 13b in the first waveguide plane line converter and the second probe 13b in the second waveguide plane line converter are arranged so as to face each other.
The phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 20 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase. Shall be
In the waveguide plane line converter shown in FIG. 20, the phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter and the second waveguide The phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the plane line converter has a reverse phase.
　図２１は、図２０に示す導波管平面線路変換器における電磁波の通過位相の電磁界解析を示す説明図である。
　電磁界解析には、有限要素法が用いられている。図２１の横軸は、２つの導波管平面線路変換器における方形導波管１の第１の開口２ａから出力されたそれぞれの電磁波の中心周波数であり、電磁波の中心周波数は、Ｘ帯によって規格化されている。図２１の縦軸は、電磁波の通過位相［ｄｅｇ］である。
　図２１において、８１は、第１の導波管平面線路変換器における電磁波の通過位相、８２は、第２の導波管平面線路変換器における電磁波の通過位相である。
　通過位相８１と通過位相８２とは、位相が１８０度反転している。 FIG. 21 is an explanatory diagram showing an electromagnetic field analysis of a passing phase of an electromagnetic wave in the waveguide plane line converter shown in FIG.
The finite element method is used for electromagnetic field analysis. The horizontal axis of FIG. 21 is the center frequency of each electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the two waveguide plane line converters, and the center frequency of the electromagnetic wave depends on the X band. It is standardized. The vertical axis of FIG. 21 represents the electromagnetic wave passage phase [deg].
In FIG. 21, 81 is the electromagnetic wave passing phase in the first waveguide plane line converter, and 82 is the electromagnetic wave passing phase in the second waveguide plane line converter.
The phases of the passing phase 81 and the passing phase 82 are inverted by 180 degrees.
　図２２は、図２０に示す導波管平面線路変換器における電磁波の反射振幅の電磁界解析を示す説明図である。
　電磁界解析には、有限要素法が用いられている。図２２の横軸は、２つの導波管平面線路変換器における方形導波管１の第１の開口２ａから出力されたそれぞれの電磁波の中心周波数であり、電磁波の中心周波数は、Ｘ帯によって規格化されている。図２２の縦軸は、反射振幅［ｄＢ］である。
　図２２において、９１は、第１の導波管平面線路変換器における電磁波の反射振幅、９２は、第２の導波管平面線路変換器における電磁波の反射振幅である。
　反射振幅９１と反射振幅９２とは、概ね同じである。 22 is an explanatory diagram showing an electromagnetic field analysis of the reflection amplitude of an electromagnetic wave in the waveguide plane line converter shown in FIG.
The finite element method is used for electromagnetic field analysis. The horizontal axis of FIG. 22 is the center frequency of each electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the two waveguide plane line converters, and the center frequency of the electromagnetic wave depends on the X band. It is standardized. The vertical axis of FIG. 22 represents the reflection amplitude [dB].
In FIG. 22, 91 is the reflection amplitude of the electromagnetic wave in the first waveguide plane line converter, and 92 is the reflection amplitude of the electromagnetic wave in the second waveguide plane line converter.
The reflection amplitude 91 and the reflection amplitude 92 are substantially the same.
　図２０に示す導波管平面線路変換器において、第１の導波管平面線路変換器における第１のプローブ１３ａと、第２のプローブ１３ｂとを入れ替えた場合、図１９に示す導波管平面線路変換器となる。
　図２０に示す第１の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相と、第２の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相とが、同相であるものとする。
　図２０に示す第１の導波管平面線路変換器における第１のプローブ１３ａと、第２のプローブ１３ｂとを入れ替えた場合、図２１に示す電磁界解析結果により、２つの導波管平面線路変換器におけるそれぞれの電磁波の通過位相は、同相になることが分かる。
　図２０に示す第１の導波管平面線路変換器における第１のプローブ１３ａと、第２のプローブ１３ｂとを入れ替えても、図２２に示す電磁界解析結果により、２つの導波管平面線路変換器におけるそれぞれの電磁波の反射振幅は、概ね同じになることが分かる。 In the waveguide plane line converter shown in FIG. 20, when the first probe 13a and the second probe 13b in the first waveguide plane line converter are replaced with each other, the waveguide plane shown in FIG. It becomes a line converter.
The phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 20 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase. Shall be
When the first probe 13a and the second probe 13b in the first waveguide plane line converter shown in FIG. 20 are replaced with each other, two waveguide plane lines are obtained according to the electromagnetic field analysis result shown in FIG. It can be seen that the passing phases of the respective electromagnetic waves in the converter are in phase.
Even if the first probe 13a and the second probe 13b in the first waveguide plane line converter shown in FIG. 20 are exchanged, two waveguide plane lines are obtained according to the electromagnetic field analysis result shown in FIG. It can be seen that the reflected amplitudes of the respective electromagnetic waves in the converter are approximately the same.
　図１９に示す導波管平面線路変換器は、図２０に示す第１の導波管平面線路変換器における第１のプローブ１３ａと、第１の導波管平面線路変換器における第２のプローブ１３ｂとが入れ替えた場合の導波管平面線路変換器と同じである。
　図１９に示す第１の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相と、第２の導波管平面線路変換器の平面線路１４に与えられる電磁波の位相とが、同相であるものとする。
　したがって、図１９に示す導波管平面線路変換器では、第１の導波管平面線路変換器における方形導波管１の第１の開口２ａから出力された電磁波の位相と、第２の導波管平面線路変換器における方形導波管１の第１の開口２ａから出力された電磁波の位相とは、同位相になる。また、それぞれの電磁波の反射振幅は、概ね同じになる。
　図１９に示す導波管平面線路変換器の分配合成器７０は、通過位相が同相であり、かつ、反射振幅が概ね同じである２つの電磁波を合成し、入出力ポート７０ａから合成した電磁波を外部に出力する。 The waveguide plane line converter shown in FIG. 19 includes a first probe 13a in the first waveguide plane line converter shown in FIG. 20 and a second probe in the first waveguide plane line converter. 13b is the same as the waveguide plane line converter when it is replaced.
The phase of the electromagnetic wave given to the plane line 14 of the first waveguide plane line converter shown in FIG. 19 and the phase of the electromagnetic wave given to the plane line 14 of the second waveguide plane line converter are in phase. Shall be
Therefore, in the waveguide plane line converter shown in FIG. 19, the phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the first waveguide plane line converter and the second guide wave. The phase of the electromagnetic wave output from the first opening 2a of the rectangular waveguide 1 in the waveguide flat line converter has the same phase. Further, the reflection amplitudes of the respective electromagnetic waves are approximately the same.
The distributor/combiner 70 of the waveguide plane line converter shown in FIG. 19 combines two electromagnetic waves having the same passing phase and substantially the same reflection amplitude, and combines the electromagnetic waves combined from the input/output port 70a. Output to the outside.
　図１９に示す導波管平面線路変換器は、２つの導波管平面線路変換器から出力されるそれぞれの電磁波の位相を同位相にするための遅延線路を設けることなく、通過位相が同相の２つの電磁波を合成することができる。 The waveguide plane line converter shown in FIG. 19 has the same passing phase without providing a delay line for making the phases of the respective electromagnetic waves output from the two waveguide plane line converters the same. Two electromagnetic waves can be combined.
　なお、本願発明はその発明の範囲内において、各実施の形態の自由な組み合わせ、あるいは各実施の形態の任意の構成要素の変形、もしくは各実施の形態において任意の構成要素の省略が可能である。 It should be noted that, within the scope of the invention, the invention of the present application is capable of freely combining the embodiments, modifying any constituent element of each embodiment, or omitting any constituent element in each embodiment. .
　この発明は、方形導波管と平面線路とを備える導波管平面線路変換器及び高周波モジュールに適している。 The present invention is suitable for a waveguide plane line converter including a rectangular waveguide and a plane line and a high frequency module.
　１　方形導波管、１ａ　第１の金属ブロック、１ａ’　内壁面、１ｂ　第２の金属ブロック、２ａ　第１の開口、２ｂ　第２の開口、３ａ　空間、３ｂ　空間、３ｃ　空間、４ａ　第１の断面形状の長手方向、４ｂ　第１の断面形状の短手方向、５ａ　第２の断面形状の長手方向、５ｂ　第２の断面形状の短手方向、５ｃ　内壁面１と第１の接地導体との間の長さ、６　ポスト壁導波路、６ａ　導波路幅、７　誘電体基板、７ａ　第１の平面、７ｂ　第２の平面、８　第１の接地導体、８ａ　第１の接地導体における第１の開口側の端部、９　第２の接地導体、９ａ　第２の接地導体における第１の開口側の端部、１０　第１の柱状導体、１１　第２の柱状導体、１２ａ，１２ｂ　ネジ、１３　平衡プローブ、１３ａ　第１のプローブ、１３ｂ　第２のプローブ、１４　平面線路、１４ａ　信号線導体、１４ｂ　接地導体、１５ａ，１５ｂ　ネジ、１６ａ，１６ｂ　空間、３０　０．２［ｍｍ］の場合の解析結果、３１　０．２７［ｍｍ］の場合の解析結果、３２　０．３［ｍｍ］の場合の解析結果、３３　０．４［ｍｍ］の場合の解析結果、３４　０．５［ｍｍ］の場合の解析結果、３５　０．６［ｍｍ］の場合の解析結果、３６　０．７［ｍｍ］の場合の解析結果、３７　０．８［ｍｍ］の場合の解析結果、４０　導通部材、５１　空間、５２　誘電体基板、５３，５４　接地導体、５５　高周波増幅器、５６　アイソレータ、５７　放熱フィン、５８　シールド部材、６０　チョーク構造、６０ａ　チョーク構造の長さ、６０ｂ　チョーク構造の底部、７０　分配合成器、７０ａ，７０ｂ，７０ｃ　入出力ポート、８１，８２　通過位相、９１，９２　反射振幅、１０１　内壁面、１０２　外壁面。 1 rectangular waveguide, 1a 1st metal block, 1a' inner wall surface, 1b 2nd metal block, 2a 1st opening, 2b 2nd opening, 3a space, 3b space, 3c space, 4a 1st Longitudinal direction of cross section, 4b Short direction of first cross section, 5a Long direction of second cross section, 5b Short direction of second cross section, 5c Inner wall surface 1 and first ground conductor Length between, 6 post wall waveguide, 6a waveguide width, 7 dielectric substrate, 7a first plane, 7b second plane, 8 first ground conductor, 8a first in ground conductor Opening-side end, 9 second ground conductor, 9a First opening-side end of second ground conductor, 10 first columnar conductor, 11 second columnar conductor, 12a, 12b screw, 13 balanced Probe, 13a first probe, 13b second probe, 14 plane line, 14a signal line conductor, 14b ground conductor, 15a, 15b screw, 16a, 16b space, 30 0.2 [mm] analysis result, 31 analysis result for 0.27 [mm], 32 analysis result for 0.3 [mm], 33 analysis result for 0.4 [mm], 34 analysis for 0.5 [mm] As a result, the analysis result in the case of 35 0.6 [mm], the analysis result in the case of 36 0.7 [mm], the analysis result in the case of 37 0.8 [mm], 40 conducting member, 51 space, 52 dielectric Body board, 53, 54 ground conductor, 55 high frequency amplifier, 56 isolator, 57 radiating fin, 58 shield member, 60 choke structure, 60a choke structure length, 60b choke structure bottom, 70 distribution combiner, 70a, 70b, 70c input/output port, 81, 82 passing phase, 91, 92 reflection amplitude, 101 inner wall surface, 102 outer wall surface.

Claims (11)

  1. 　第１の開口側の管路における断面形状である第１の断面形状と、第２の開口側の管路における断面形状である第２の断面形状とが異なり、前記第１の断面形状の長手方向と前記第２の断面形状の短手方向とが平行に配置され、前記第１の断面形状の短手方向と前記第２の断面形状の長手方向とが平行に配置されている方形導波管と、
    　一部が前記第２の開口側の管路内に配置されているポスト壁導波路と、
    　先端が前記第１の開口側の管路内に配置され、基端が前記ポスト壁導波路における前記第１の開口側の端部と接続されている平衡プローブと、
    　前記方形導波管における前記第２の開口の外側に配置され、一端が前記ポスト壁導波路における前記第２の開口側の端部と接続されている平面線路と
    　を備えた導波管平面線路変換器。     The first cross-sectional shape, which is the cross-sectional shape in the first opening-side conduit, and the second cross-sectional shape, which is the cross-sectional shape in the second opening-side conduit, are different, and the length of the first cross-sectional shape is different. Direction and the short-side direction of the second cross-sectional shape are arranged in parallel, and the short-side direction of the first cross-sectional shape and the longitudinal direction of the second cross-sectional shape are arranged in parallel. With a tube,
    A post wall waveguide, a part of which is disposed in the conduit on the second opening side;
    A balanced probe having a distal end disposed in the first opening-side conduit and a proximal end connected to the first opening-side end of the post wall waveguide;
    A planar waveguide line which is arranged outside the second opening in the rectangular waveguide and has a planar line whose one end is connected to an end portion of the post wall waveguide on the side of the second opening. converter.
  2. 　前記第２の開口側の管路の内壁面と前記ポスト壁導波路との間に空間が設けられており、
    　前記第１の断面形状の長手方向の寸法が、前記方形導波管により伝搬される電磁波の半波長以上の長さであり、前記第２の断面形状の長手方向の寸法が、前記電磁波の半波長以下の長さであり、
    　前記ポスト壁導波路の導波路幅が、前記電磁波の実効波長の半波長以上の長さであることを特徴とする請求項１記載の導波管平面線路変換器。     A space is provided between the inner wall surface of the conduit on the second opening side and the post wall waveguide,
    The longitudinal dimension of the first cross-sectional shape is equal to or longer than a half wavelength of an electromagnetic wave propagated by the rectangular waveguide, and the longitudinal dimension of the second cross-sectional shape is a half wavelength of the electromagnetic wave. Is less than the wavelength,
    2. The waveguide plane line converter according to claim 1, wherein a waveguide width of the post wall waveguide is a length equal to or longer than a half wavelength of an effective wavelength of the electromagnetic wave.
  3. 　前記ポスト壁導波路は、
    　誘電体基板と、
    　前記誘電体基板の第１の平面に形成されている第１の接地導体と、
    　前記誘電体基板の第２の平面に形成されている第２の接地導体と、
    　前記第１の接地導体と前記第２の接地導体とを接続している第１の柱状導体と、
    　前記第１の接地導体と前記第２の接地導体とを接続している第２の柱状導体とを備えており、
    　前記ポスト壁導波路の導波路幅が、前記第１の柱状導体と前記第２の柱状導体との間の長さであることを特徴とする請求項１記載の導波管平面線路変換器。     The post wall waveguide is
    A dielectric substrate,
    A first ground conductor formed on a first plane of the dielectric substrate;
    A second ground conductor formed on a second plane of the dielectric substrate;
    A first columnar conductor connecting the first ground conductor and the second ground conductor;
    A second columnar conductor connecting the first ground conductor and the second ground conductor,
    2. The waveguide planar line converter according to claim 1, wherein a waveguide width of the post wall waveguide is a length between the first columnar conductor and the second columnar conductor.
  4. 　前記平衡プローブは、
    　先端が前記第１の開口側の管路内に配置され、基端が前記第１の接地導体における前記第１の開口側の端部と接続されている第１のプローブと、
    　先端が前記第１の開口側の管路内に配置され、基端が前記第２の接地導体における前記第１の開口側の端部と接続されている第２のプローブとを備えており、
    　前記第１のプローブと前記第２のプローブとは、基端から先端の方向に向かうほど、互いの間の距離が広がっていることを特徴とする請求項３記載の導波管平面線路変換器。     The balance probe is
    A first probe whose tip is arranged in the conduit on the side of the first opening and whose base end is connected to the end of the first ground conductor on the side of the first opening;
    A second probe having a tip arranged in the conduit on the first opening side and a base end connected to an end of the second ground conductor on the first opening side,
    4. The waveguide planar line converter according to claim 3, wherein the first probe and the second probe have a distance between them that increases in the direction from the base end to the tip. ..
  5. 　前記第２の開口側の管路の内壁面のうち、前記ポスト壁導波路と対向している内壁面と、前記ポスト壁導波路との間の長さが、前記誘電体基板の基板厚の半分以上の長さであることを特徴とする請求項３記載の導波管平面線路変換器。 Of the inner wall surface of the conduit on the second opening side, the length between the inner wall surface facing the post wall waveguide and the post wall waveguide is equal to the substrate thickness of the dielectric substrate. The waveguide plane line converter according to claim 3, wherein the waveguide plane line converter has a length of half or more.
  6. 　前記方形導波管は、第１の金属ブロックと、第２の金属ブロックとを備え、前記第１の金属ブロックと前記第２の金属ブロックとの間に、前記管路としての空間が形成されるように、前記第１の金属ブロックと前記第２の金属ブロックとが接続されており、
    　前記誘電体基板は、前記空間内に配置され、ネジによって、前記第２の金属ブロックに固定されていることを特徴とする請求項３記載の導波管平面線路変換器。     The rectangular waveguide includes a first metal block and a second metal block, and a space as the conduit is formed between the first metal block and the second metal block. So that the first metal block and the second metal block are connected,
    4. The waveguide planar line converter according to claim 3, wherein the dielectric substrate is arranged in the space and is fixed to the second metal block with a screw.
  7. 　前記方形導波管は、第１の金属ブロックと、第２の金属ブロックとを備え、前記第１の金属ブロックと前記第２の金属ブロックとの間に、前記管路としての空間が形成されるように、前記第１の金属ブロックと前記第２の金属ブロックとが接続されており、
    　前記誘電体基板は、前記第２の接地導体が前記第２の金属ブロックと接するように、前記空間に配置され、
    　前記第１の金属ブロックと前記第１の接地導体との間を導通させる導通部材を備えたことを特徴とする請求項３記載の導波管平面線路変換器。     The rectangular waveguide includes a first metal block and a second metal block, and a space as the conduit is formed between the first metal block and the second metal block. So that the first metal block and the second metal block are connected,
    The dielectric substrate is disposed in the space such that the second ground conductor is in contact with the second metal block,
    The waveguide flat line converter according to claim 3, further comprising a conductive member that electrically connects between the first metal block and the first ground conductor.
  8. 　前記方形導波管は、第１の金属ブロックと、第２の金属ブロックとを備え、前記第１の金属ブロックと前記第２の金属ブロックとの間に、前記管路としての空間が形成されるように、前記第１の金属ブロックと前記第２の金属ブロックとが接続されており、
    　前記空間を形成している前記第２の金属ブロックの内壁面と対向している前記第２の金属ブロックの外壁面に、放熱フィンが形成されていることを特徴とする請求項１記載の導波管平面線路変換器。     The rectangular waveguide includes a first metal block and a second metal block, and a space as the conduit is formed between the first metal block and the second metal block. So that the first metal block and the second metal block are connected,
    The heat dissipation fin is formed on an outer wall surface of the second metal block that faces an inner wall surface of the second metal block that forms the space. Wave tube plane line converter.
  9. 　前記方形導波管は、第１の金属ブロックと、第２の金属ブロックとを備え、前記第１の金属ブロックと前記第２の金属ブロックとの間に、前記管路としての空間が形成されるように、前記第１の金属ブロックと前記第２の金属ブロックとが接続されており、
    　前記第１の金属ブロックの内壁面のうち、前記ポスト壁導波路と対向している内壁面に、チョーク構造が形成されていることを特徴とする請求項１記載の導波管平面線路変換器。     The rectangular waveguide includes a first metal block and a second metal block, and a space as the conduit is formed between the first metal block and the second metal block. So that the first metal block and the second metal block are connected,
    The waveguide planar line converter according to claim 1, wherein a choke structure is formed on an inner wall surface of the first metal block facing the post wall waveguide. ..
  10. 　請求項４記載の導波管平面線路変換器を２つ備えており、
    　２つの導波管平面線路変換器のうちの一方の導波管平面線路変換器が、第１の導波管平面線路変換器であり、他方の導波管平面線路変換器が、第２の導波管平面線路変換器であり、
    　前記第１の導波管平面線路変換器における前記方形導波管の第１の開口と、前記第２の導波管平面線路変換器における前記方形導波管の第１の開口とが分配合成器を介して接続されており、
    　前記第１の導波管平面線路変換器における第１のプローブと、前記第２の導波管平面線路変換器における第２のプローブとが対向するように配置され、
    　前記第１の導波管平面線路変換器における第２のプローブと、前記第２の導波管平面線路変換器における第１のプローブとが対向するように配置されていることを特徴とする導波管平面線路変換器。     Two waveguide plane line converters according to claim 4 are provided,
    One of the two waveguide plane line converters is the first waveguide plane line converter, and the other waveguide plane line converter is the second waveguide plane line converter. It is a waveguide plane line converter,
    The first opening of the rectangular waveguide in the first waveguide plane line converter and the first opening of the rectangular waveguide in the second waveguide plane line converter are distributed and combined. Connected via
    The first probe in the first waveguide plane line converter and the second probe in the second waveguide plane line converter are arranged to face each other,
    A second probe in the first waveguide plane line converter and a first probe in the second waveguide plane line converter are arranged so as to face each other. Wave tube plane line converter.
  11. 　導波管平面線路変換器と、
    　送信用の高周波を増幅する高周波増幅器と、
    　前記導波管平面線路変換器に含まれる平面線路により伝搬される電磁波と、前記高周波増幅器により増幅される高周波との干渉を防ぐアイソレータとを備え、
    　前記導波管平面線路変換器は、
    　第１の開口側の管路における断面形状である第１の断面形状と、第２の開口側の管路における断面形状である第２の断面形状とが異なり、前記第１の断面形状の長手方向と前記第２の断面形状の短手方向とが平行に配置され、前記第１の断面形状の短手方向と前記第２の断面形状の長手方向とが平行に配置されている方形導波管と、
    　一部が前記第２の開口側の管路内に配置されているポスト壁導波路と、
    　先端が前記第１の開口側の管路内に配置され、基端が前記ポスト壁導波路における前記第１の開口側の端部と接続されている平衡プローブと、
    　前記方形導波管における前記第２の開口の外側に配置され、一端が前記ポスト壁導波路における前記第２の開口側の端部と接続されている平面線路とを備えていることを特徴とする高周波モジュール。     A waveguide plane line converter,
    A high frequency amplifier that amplifies high frequencies for transmission,
    An electromagnetic wave propagated by a plane line included in the waveguide plane line converter, and an isolator for preventing interference with a high frequency amplified by the high frequency amplifier,
    The waveguide plane line converter,
    The first cross-sectional shape, which is the cross-sectional shape in the first opening-side conduit, and the second cross-sectional shape, which is the cross-sectional shape in the second opening-side conduit, are different, and the length of the first cross-sectional shape is different. Direction and the short-side direction of the second cross-sectional shape are arranged in parallel, and the short-side direction of the first cross-sectional shape and the longitudinal direction of the second cross-sectional shape are arranged in parallel. With a tube,
    A post wall waveguide, a part of which is disposed in the conduit on the second opening side;
    A balanced probe having a distal end disposed in the first opening-side conduit and a proximal end connected to the first opening-side end of the post wall waveguide;
    A flat line disposed outside the second opening in the rectangular waveguide, one end of which is connected to an end of the post wall waveguide on the side of the second opening. High frequency module to do.
PCT/JP2018/044591 2018-12-04 2018-12-04 Waveguide planar line converter and high-frequency module WO2020115820A1 (en)

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