WO2019205144A1

WO2019205144A1 - Signal processing method and signal processing device

Info

Publication number: WO2019205144A1
Application number: PCT/CN2018/085104
Authority: WO
Inventors: 马英东; 何昭君; 郭勇; 李海; 张勇; 杨军; 王丽萍
Original assignee: 华为技术有限公司
Priority date: 2018-04-28
Filing date: 2018-04-28
Publication date: 2019-10-31

Abstract

A signal processing method and a signal processing device, capable of performing mapping and weighing using a plurality of reference factors reflecting the quality of receive signals to obtain a composite index for antenna alignment between communication devices, thereby improving the accuracy of antenna alignment. The signal processing device obtains reference factors of receive signals, the reference factors being used for reflecting the quality of the receive signals, the reference factors comprising at least one first type reference factor and at least one second type reference factor, the first type reference factor comprising a receive signal level (RSL); the signal processing device determines mapping values corresponding to the reference factors according to a preset mapping method; the signal processing device performs weighing on the mapping values respectively according to weighted coefficients corresponding to the reference factors to obtain weighted values of the mapping values; the signal processing device adds the weighted values together to obtain a composite index, the composite index being used for performing antenna alignment.

Description

Signal processing method and signal processing device

Technical field

The present application relates to the field of communications technologies, and in particular, to a signal processing method and a signal processing device.

Background technique

In recent years, in order to meet the needs of SME customers, many communication vendors have adopted commercial wireless local area networks (WLAN) commercial chips, combined with traditional microwave structures, to achieve high-capacity, low-cost, long-distance transmission. In order to improve the transmission distance, the basic idea of a technical solution is to increase the antenna gain. Referring to FIG. 1, FIG. 1 is a schematic diagram of a long-distance transmission scheme combining a commercial chip and a high-gain antenna. The high-gain antenna requires both sides of the communication to point the beam to each other while increasing the transmission distance. This operation is called "antenna alignment."

At present, the long-range microwave antenna alignment process is shown in Figure 2. After starting the antenna alignment, first adjust the antenna's pointing, and then check whether the received signal level (RSL) or signal-to-noise ratio (SNR) is up to standard. If the target is not met, the loop performs the step of adjusting the antenna pointing to see if the RSL or SNR is up to standard. If the target is reached, the antenna is reversed.

However, when performing "antenna alignment", the SNR and RSL measurements must be accurate enough. When using a low-cost commercial chip, in order to achieve low cost, the measurement part will be simplified as much as possible, resulting in unstable link when the antenna is misaligned, and large jitter of SNR and RSL values, resulting in difficulty in antenna alignment. .

Summary of the invention

The embodiment of the present application provides a signal processing method and a signal processing apparatus, which can perform mapping and weighting by using a plurality of reference factors reflecting the quality of the received signal, and obtain a comprehensive index for performing antenna alignment between communication devices, thereby solving the low-cost business. The problem of antenna alignment caused by the chip is difficult.

A first aspect of the embodiments of the present invention provides a signal processing method, including:

After the signal processing device acquires the reference factor of the received signal, the mapping value corresponding to each reference factor may be determined according to a preset mapping method, and each mapping value belongs to the same calculation range that can be used for adding and summing with each other, and The factor is used to reflect the quality of the received signal, and the reference factor includes at least one first type of reference factor and at least one second type of reference factor, the first type of reference factor including a received signal level (RSL), Then, the signal processing device may separately weight each mapping value according to each weighting coefficient corresponding to each reference factor, thereby obtaining weighting values of the respective mapping values. Finally, the signal processing device adds the respective weighting values to obtain a comprehensive index. The composite index can be used to achieve antenna alignment. When the composite index reaches the standard value, the antenna is already aligned. If the composite index does not reach the standard value, the antenna is not aligned, and the mapping value of each reference factor is Weighting is done to influence the alignment antenna according to each reference factor. Small to determine the weighting value of each reference factor, the greater the influence on the antenna alignment, the greater the weighting value, the smaller the reference factor that has less influence on the antenna alignment, the smaller the weighting value, by such a method Setting the weight value makes it easier to achieve antenna alignment.

As can be seen from the above technical solution, the embodiment of the present application has the following advantages: the signal processing device can map the plurality of reference factors of the received received signal according to a preset mapping method into the same calculation range that can be added and summed. And then the signal processing device weights each mapping value according to each weighting coefficient corresponding to each reference factor to obtain a weighting value of each mapping value, and finally adds a weighted value to obtain a comprehensive index reflecting the quality of the received signal. Used for antenna alignment. When the antenna alignment is performed, not only the reference factors reflecting the received signal quality of multiple different units are first mapped into the same calculation reference range, so that the addition between the mapping values can be realized, and the mapped mapping values are performed. Weighted to make it easier to align the antenna.

Based on the first aspect of the embodiments of the present application, in a first implementation manner of the first aspect of the embodiments of the present application, the second reference factor includes a group A reference factor or a group B reference factor, where the The group A reference factor includes a modulation coding scheme (MCS), a mean square error (MSE) of the received signal constellation point, a packet error ratio (PER), or a number of received packet bytes (number The received group B includes a signal to noise ratio (SNR) or a mean squared error MSE of the received signal constellation point.

In this embodiment, the signal processing apparatus can perform antenna alignment by using at least two reference factors reflecting the quality of the received signal, so that the signal alignment method can be used for antenna alignment in different application scenarios, and the expansion can be performed. The application scenario of antenna alignment improves the achievability of the solution.

In the second embodiment of the first aspect of the present application, the signal processing apparatus adds the weighting values according to the first aspect of the first embodiment of the present application. The composite index includes:

The signal processing device can calculate the composite index c by:

Where N is the number of reference factors; w _k is the weighting coefficient corresponding to the Kth reference factor; s _k is the Kth reference factor, and f _k (s _k ) is the Kth reference factor Corresponding mapping values, N and K are positive integers.

In the embodiment of the present application, the signal processing apparatus can obtain a comprehensive index for judging whether the antenna is aligned by weighting each reference factor, so that the antenna can be aligned more accurately with multiple reference factors at the same time.

Based on the first aspect of the first embodiment of the present application or the first implementation manner of the first aspect of the application, in the third implementation manner of the first aspect of the application, the signal processing apparatus is determined according to a preset mapping method. The mapping values corresponding to each of the reference factors include:

The signal processing apparatus may determine the mapping value corresponding to each of the reference factors according to a linear mapping method or a nonlinear mapping method.

In the embodiment of the present application, the signal processing apparatus may determine the mapping value corresponding to each reference factor by using a linear method or a nonlinear method, which improves the achievability of the technical solution of the present application.

Based on the third implementation manner of the first aspect of the embodiment of the present application, in the fourth implementation manner of the first aspect of the embodiment, the non-linear mapping method includes:

The difference between the mapping value of the first type of reference factor and the received power is negatively correlated, that is, the greater the difference of the received power, the smaller the mapping value of the RSL, and vice versa, if the received power is The smaller the difference, the larger the mapping value of the RSL, wherein the difference in received power is the difference between the received power and the target received power. Moreover, in a case where the change in the difference in received power is the same in the first interval and the second interval, the amount of change in the mapping value of the first type of reference factor in the first interval is greater than The amount of change in the second interval, wherein the first interval is an area in which the difference in received power is less than a first threshold, and the second interval is an area in which the difference in received power is not less than the first threshold. That is, in the range where the difference in received power is small (within the first interval), that is, when the received power of the first type of reference factor is close to the target received power, as long as the difference in received power With a slight change, the mapping value will change drastically; and in the range where the difference in received power is large (within the second interval), that is, when the received power is far away from the target received power, Even if the difference in received power is large, the change in the mapped value will be gentle, and will not change drastically with a large change in the received power.

In the embodiment of the present application, the signal processing apparatus may perform nonlinear mapping on the first type of reference factors according to the above formula, thereby determining a mapping value of the first type of reference factors, and providing a specific nonlinear mapping method, so in practice In the application, the achievability of the solution is improved.

In the fifth implementation manner of the first aspect of the embodiment of the present application, the nonlinear mapping method includes:

In the case that the amount of change of the parameter to be mapped in the first interval is the same as the amount of change in the parameter to be mapped in the second interval, the mapping value of the group A reference factor is in the first The amount of change in an interval is greater than the variable in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is that the parameter to be mapped is not For the area smaller than the second threshold, the parameter to be mapped corresponding to the A group reference factor includes a ratio of the weighted capacity to the maximum capacity of the MCS, a logarithm of the PER, or a ratio of the received data rate to the actual data rate.

In the embodiment of the present application, since the signal processing device can calculate the mapping value of the non-linearly varying reference factor by the interpolation method, another specific signal processing device is provided for performing nonlinear mapping, so that the calculation is performed. The mapping value result is more accurate, which is more conducive to achieving antenna alignment and improving the achievability of the solution.

Based on the third implementation manner of the first aspect of the embodiment of the present application, in the sixth implementation manner of the first aspect of the embodiment, the non-linear mapping method includes:

If the amount of change of the parameter to be mapped in the first interval of the group B reference factor is the same as the amount of change in the parameter to be mapped in the second interval, the mapping value of the group B reference factor is The amount of change in the first interval is smaller than the amount of change in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is the The mapping parameter is not smaller than the area of the second threshold, and the parameter to be mapped corresponding to the group B reference factor includes a difference value of the MSE and the target MSE, or a difference value between the SNR and the target SNR.

Based on the first aspect of the embodiments of the present application, the first embodiment of the first aspect of the present application, the first embodiment of the first aspect of the first embodiment of the present application, the first embodiment of the present application In a seventh implementation manner, before the signal processing apparatus weights each of the mapping values according to each weighting coefficient corresponding to each of the reference factors to obtain a weighting value of each of the mapping values, the method Also includes:

The signal processing device calculates each of the weighting coefficients corresponding to each of the mapping values according to the θ, wherein the θ is an angle between a preset reference direction and a target direction to be aligned. During the antenna alignment process of the signal processing device, the weighting coefficient of the reference factor changes continuously with the change of θ.

In the embodiment of the present application, since θ is a variable, the weighting coefficient is correspondingly changed continuously, thereby changing the comprehensive index of whether the measuring antenna is aligned, and the flexibility of applying the technical solution of the present application is increased.

According to the seventh embodiment of the first aspect of the embodiment of the present application, in the eighth implementation manner of the first aspect of the embodiment of the present application,

The formula for calculating, by the signal processing device, each of the weighting coefficients corresponding to each of the mapping values according to the θ is as follows:

w _k =F*▽E(s _k ,θ)/σ(s _k ,θ);

Where s _k is the Kth reference factor, ▽E(s _k , θ) is the mean value of the mapping value of the Kth reference factor following the rate of change of the normal deviation angle θ, σ(s _k , θ) is the variance of the mapped values of the Kth reference factor, and F is the correction factor, and the correction factor is calculated as follows:

Since the weighting coefficient w _{k of} the Kth reference factor is proportional to the correction factor F, and the mean value of F is proportional to the rate of change θE(s _k , θ), and the variance σ(s _k , θ ) is inversely proportional, so w _{k is} proportional to the rate of change ▽E(s _k , θ) and inversely proportional to the variance σ(s _k , θ), that is, the greater the rate of change of the mean with θ, then the weighting factor w _The larger _k , the larger the jitter (ie, the larger the variance), the smaller the weighting coefficient w _k .

In the embodiment of the present application, since the weighting coefficient of the dynamic weighting of the signal processing device can be calculated by using a specific formula, the achievability of the solution is improved.

Based on the first aspect of the embodiments of the present application, any one of the first to sixth embodiments of the first aspect of the present application, in the ninth implementation manner of the first aspect of the embodiment of the present application, And before the signal processing device weights each mapping value according to each weighting coefficient corresponding to each of the reference factors to obtain a weighting value of each of the mapping values, the method further includes:

The signal processing device may preset each of the weighting coefficients corresponding to each of the mapping values, and the calculation formula of the weighting coefficients is as follows:

w _k =F*Δ(s _k );

Wherein, the weighting coefficient of the preset is a constant value, and does not change according to the normal deviation angle θ, and Δ(s _k ) represents the Kth reference factor when the deviation angle is Δθ The amount of change in the mapped value;

F is the correction factor and is a constant. The formula is as follows:

The correction factor is used to ensure that the sum of the weighting coefficients is 1, and the calculation formula is as follows:

In the embodiment of the present application, since the signal processing apparatus can calculate the weighting coefficient of each mapping value when the weight is fixed by a specific formula, the achievability of the scheme is improved.

According to the ninth embodiment of the first aspect of the embodiment of the present application, in the tenth implementation manner of the first aspect of the embodiment of the present application,

The formula for calculating Δ(s _k ) is as follows:

Δ(s _k )=|f _k (s _k ,0)-f _k (s _k ,Δθ)|;

Where f _k (s _k , 0) is a mapping value of the Kth reference factor when the θ is 0 degrees, and f _k (s _k , Δθ) is the change rate of the θ when the Δθ is the K map values of the reference factors.

In the embodiment of the present application, further, since the signal processing apparatus gives a more specific formula for Δ(s _k ) in the formula for calculating the weighting coefficient at the time of fixed weighting, the achievability of the scheme is further improved.

According to the ninth embodiment of the first aspect of the embodiments of the present application, in the eleventh implementation manner of the first aspect of the embodiments of the present application, after the signal processing device acquires the reference factor of the received signal, the method further includes:

The signal processing apparatus may perform smoothing filtering on the reference factor, the smoothing filtering being used to cancel jitter of the reference factor. The step of smoothing filtering may be performed after the signal processing device acquires the reference factor of the received signal, before the signal processing device determines the mapping value corresponding to each reference factor according to a preset mapping method, or may perform After the signal processing device weights each mapping value according to each weighting coefficient corresponding to each of the reference factors to obtain a weighting value of each of the mapping values, the signal processing device adds each of the weighting values. Execute before the comprehensive index is obtained, which is not limited here. In addition, when the input signal jitter of the reference factor is large, the smoothing filter debounce may be adopted, and when the input signal of the reference factor is small, the step of performing the smoothing filtering may be omitted, specifically No restrictions are imposed.

In the embodiment of the present application, since the reference factor is filtered to increase the jitter of the reference factor when the reference factor jitter is severe, the reference factor reflecting the signal quality can be ensured for antenna alignment, and the solution is improved. The achievability.

According to the eleventh embodiment of the first aspect of the embodiments of the present application, in the twelfth implementation manner of the first aspect of the embodiments of the present application, the calculation formula of the smoothing filter is as follows:

Where N is the smoothing filter order, n is the sequence number of each step of the smoothing filter, X is an input signal of a reference factor, Y is an output signal of a reference factor, and an, bn are coefficients of the smoothing filter m is the time at which the input signal X is smooth filtered to obtain the output signal Y.

In the embodiment of the present application, since the output signal of the reference factor can be calculated by using a specific filtering calculation formula, and then the subsequent steps are performed by using the output signal, the achievability of the solution is improved.

A second aspect of the embodiments of the present application provides a signal processing apparatus having a function of realizing the entity behavior of the signal processing apparatus in the above first aspect. This function can be implemented in hardware or in hardware by executing the corresponding software. The hardware or software includes one or more modules corresponding to the functions described above.

A third aspect of the embodiments of the present application provides a computer storage medium for storing computer software instructions for use in the signal processing apparatus of the above third aspect, comprising: a program for executing a signal processing apparatus .

A fourth aspect of the embodiments of the present application provides a computer program product, which includes computer software instructions, which can be recorded by a processor to implement the method flow in the first to fourth aspects.

DRAWINGS

1 is a schematic diagram of a long-distance transmission scheme of a commercial chip and a high-gain antenna;

2 is a schematic diagram of a long-distance antenna alignment process;

3 is a schematic diagram of an outdoor parabolic high gain antenna;

4 is a schematic diagram of a direction of a high gain antenna;

Figure 5 is a schematic diagram of a typical antenna envelope;

FIG. 6 is a schematic diagram of an embodiment of a signal processing method according to an embodiment of the present application; FIG.

FIG. 7 is a schematic flowchart diagram of an embodiment of a signal processing method according to an embodiment of the present application;

FIG. 8 is a schematic diagram of filtering a reference factor by using a smoothing filter according to an embodiment of the present application; FIG.

FIG. 9 is another schematic diagram of filtering a reference factor by using a smoothing filter according to an embodiment of the present application; FIG.

10 is a schematic diagram of a nonlinear mapping of an RSL according to an embodiment of the present application;

11 is a schematic diagram of comparison of theoretical power and real measured power at different angles in an embodiment of the present application;

FIG. 12 is a schematic diagram of relationship between filtered target power and angle in the embodiment of the present application; FIG.

FIG. 13 is a schematic diagram of mapping characteristics of MCS/SNR/receive packet byte number in the embodiment of the present application; FIG.

14 is a schematic diagram of mapping characteristics of a PER/MSE in an embodiment of the present application;

15 is a schematic diagram of nonlinear mapping of MCS in an embodiment of the present application;

16 is a schematic diagram of a nonlinear mapping of a PER in an embodiment of the present application;

17 is a schematic diagram of a nonlinear mapping of the number of bytes of a received packet in the embodiment of the present application;

FIG. 18 is a schematic diagram of nonlinear mapping of MSE/SNR in an embodiment of the present application; FIG.

FIG. 19 is a schematic diagram of linear interpolation in an embodiment of the present application; FIG.

20 is a schematic flowchart of another embodiment of a signal processing method according to an embodiment of the present application;

FIG. 21 is a schematic diagram of another embodiment of a signal processing method according to an embodiment of the present application; FIG.

FIG. 22 is a schematic diagram of an embodiment of a signal processing apparatus according to an embodiment of the present application.

detailed description

The technical solutions in the embodiments of the present invention will be clearly and completely described in the following with reference to the accompanying drawings.

The embodiment of the present application provides a calculation method based on the received signal synthesis index, which is used to solve the problem that the RSL or SNR measurement of the low-cost commercial chip is inaccurate, and the antenna side lobes are high, resulting in the antenna being unable to be correctly aligned.

Please refer to FIG. 3. FIG. 3 is a typical parabolic directional antenna, commonly known as a "pot". In order to improve the transmission distance, the basic idea of a technical solution is to increase the antenna gain. The "pot" of Fig. 3 can converge the electromagnetic wave energy to achieve directional transmission, so that the same transmission power can achieve a longer transmission distance. For example, the transmission distance of the communication carrier in the frequency band of about 60 GHz can only cover about 20 meters indoors, and the high-gain antenna can be transmitted outdoors, and the transmission distance can reach 1 kilometer.

Please refer to FIG. 4 and FIG. 5. FIG. 4 is a schematic diagram of the direction of the high gain antenna. 4 is a schematic diagram for measuring the radiation capability of a directional antenna. The most concentrated energy is called the main lobe (also called the main beam), and the other is called the side lobe (also called the sub-beam). The directional antenna can be compared to a "flashlight". The brightest part of the center of the illumination area is the main lobe (ie, the main beam), and the edge is the darkest, but there are also some bright side lobes (ie, the secondary beam) near the edge. The higher the gain, the finer the beam and the farther the transmission distance of the equivalent transmit power.

While the high-gain antenna increases the transmission distance, both parties need to point the beam to the other side, that is, "antenna alignment" (also called "antenna alignment"). However, antenna alignment brings the following alignment problems: (1) Low-cost antennas often have higher side lobes, for example, about 10 dB from the main lobe, which may cause alignment to the antenna side lobes when aligned; 2) Commercial chips In order to achieve low cost, the indications of RSL and SNR are rough, too simplistic, and the jitter is large, for example, about 10 dB.

As an example, see the schematic diagram of a typical antenna direction envelope of FIG. As can be seen from FIG. 5, the main lobe and the side lobe of the antenna are 13-20 dB apart. If the RSL shown in Figure 5 is not accurate enough and the jitter is severe, it is easy to align to the side lobes of the antenna, thereby reducing the gain margin of the link, so that the link cannot be used under harsh conditions.

The present invention mainly solves the alignment problems of the above (1) and (2), that is, the RSL or SNR measurement of the low-cost commercial chip is inaccurate, and the antenna side lobes are high, resulting in the problem that the antenna cannot be properly aligned. In response to this technical problem, the present invention proposes the following technical solutions.

Based on the technical content of the antenna alignment described above, the technical solutions in the present application are described below. Please refer to Figure 6 and Figure 7. In an antenna alignment process, an embodiment of the signal processing method in the embodiment of the present application includes:

601. The signal processing device acquires a reference factor of the received signal.

The signal processing device obtains a reference factor capable of reflecting the quality of the received signal, the reference factor comprising at least one first type of reference factor and at least one reference factor other than the second type of reference factor, the first type of reference factor comprising RSL, the second type of reference The factor includes a Group A reference factor or a Group B reference factor, the Group A reference factor may be MCS, PER or the number of received packet bytes, and the Group B reference factor may be SNR or MSE. The units of each reference factor are different. The unit of SNR and RSL is dB. The MCS is a sequence number. Each sequence number corresponds to a modulation and coding mode. Each sequence number also corresponds to a physical layer rate. The unit of MSE is dB. The packet rate can be expressed as a percentage. The unit of the number of bytes received is one. For the reference factor obtained, it is not limited here.

602. The signal processing device performs preprocessing on a reference factor of the received signal.

After obtaining the reference factor of the received signal, the signal processing device can more easily determine the mapping value corresponding to each reference factor, and in order to eliminate the numerical range of each reference factor that affects the abnormality of the mapping result, for example, the value range with less sensitivity is eliminated. Or, in order to eliminate the numerical range of data anomalies, the signal processing device may preprocess the reference factor of the received signal, and the preprocessing may be implemented as follows:

For the reference factors RSL, PER, MSE, SNR, and the number of received packet bytes, the signal processing device can perform the pre-processing of the clipping by the following formula:

Where A _u , A _d are the upper and lower limit thresholds of the Kth factor of f _k (s _k ), respectively, and s _k is the Kth reference factor;

For the reference factor MCS, the signal processing device can perform pre-processing on the weighted capacity calculation of the MCS, and the preprocessing process is as follows:

In the statistical time period T, it is assumed that under different MCS conditions, the number of received bytes (or the number of packets) is Ai, the total number of bytes (or the total number of packets) is A; then the proportion of each MCS is:

Xi=Ai/A (Equation 2)

i=[1,...N], where N is a positive integer.

Let the physical layer (PHY) capacity (ie, PHY rate) corresponding to each MCS be a1, a2, ..., aN from low to high, respectively, then the weighted capacity (ie, weighted rate) can be expressed as

The relationship between the capacity of the MCS and the PHY can be referred to the following Table 1. The first column in Table 1 below is the MCS, and the last column is the capacity of the PHY. As can be seen from Table 1, the capacity value of the PHY is discrete. When the MCS is equal to 12, the PHY has the highest capacity, that is, the highest rate is 4620 Mbps. When the MCS is equal to 1, the PHY has the lowest capacity, that is, the rate is only 385 Mbps.

Table 1

For the reference factor to receive the number of packet bytes, the signal processing apparatus may perform pre-processing on the rate calculation of the number of bytes of the received packet according to Equation 4 below, thereby obtaining the rate of receiving the number of bytes of the packet, which is the received rate. The total number of bytes in all received packets is divided by the value of the statistical time period T, that is, the number of bytes received in a unit time. The unit time can be 5 milliseconds or 10 milliseconds. limited:

Rate = total number of bytes received A / statistical time period T (Equation 4).

603. The signal processing device uses filtering to eliminate jitter of the reference factor;

In this embodiment, step 603 may be performed between step 602 and step 604, and step 603 may be performed between step 606 and step 607, which is not limited herein.

The reference factor of the received signal is generally affected by noise, and there is generally jitter, and the filtering can be used to eliminate short-term random jitter of the reference factor input signal.

It should be noted that the filtering method used in this embodiment is a smooth filtering filtering method, and the smooth filtering method is used to achieve a smoothing effect on the output waveform of the reference factor, and other filtering methods such as limiting filtering may also be used. Since the waveform of the input signal of the reference factor may suddenly have a high glitch point (which may also be called an abnormal point), in this case, the input signal may be limited to filter out the abnormal value, and what filtering method is used. , specifically here is not limited.

Step 603 will be specifically described below.

If the mapping value of each reference factor is set between [0, 100], then it is usually required that the input signal of the observation reference factor should not exceed the fluctuation of the time window (ie, the preset time threshold) [0, T] ±2.5 (no unit after mapping), if it exceeds the range, it means that the input signal is directly output, and the update speed is faster. At this time, the reference factor input signal jitter will be larger, and the smoothing filtering method is needed to control the fluctuation of the input signal. In this range, smoothing is used to eliminate jitter; when the fluctuation of the input signal of the received signal does not exceed ±2.5, the input signal and the historical data are accumulated and output, and the update speed is slow. At this time, the reference factor input signal is jittered. If it is small, step 603 may not be performed. The signal processing device can eliminate jitter by filtering as follows:

Referring to FIG. 8, FIG. 8 is a schematic diagram of filtering a reference factor by using a smoothing filter in an embodiment of the present application. Z ^{-1 in} Fig. 8 represents a unit delay. This implementation is implemented by a smoothing filter method, and smoothing filtering is achieved by adjusting the smoothing filter coefficients a _n and b _n . For example, a smoothing filter of length N takes a _{n to} 0, b _n =1/N, N is the order of smoothing filtering, n is the sequence number of each step of the smoothing filter, and X is the input signal of the reference factor, Y is The output signal of the reference factor, a _n and b _n are the coefficients of the smoothing filter, and m is the time at which the input signal X is smoothed to obtain the output signal Y. The input-output relationship at the mth moment can be expressed by the following formula:

Further, the signal processing device may perform smoothing processing on the input signal of the reference factor by using an alpha filter structure. Referring to FIG. 9, FIG. 9 is a schematic diagram of implementing smoothing filtering on a reference factor by using an alpha filter in an embodiment of the present application. If the filter coefficient is c, at time m, the recursive relationship between the input signal X(m) of the reference factor and the output signal Y(m) of the reference factor is as follows:

Y(m)=c*X(m)+Y(m-1)-c*Y(m-1) (Equation 6)

The filter coefficient controls the smoothing effect. The value of the filter coefficient c is (0, 1). The larger the value, the worse the smoothing effect. When the value is 1, it indicates that there is no smoothing effect. The signal processing device can adjust the smoothing coefficient according to the value range (0, 1) of a (when the value is "1", it means that it is not smooth), thereby achieving different smoothing effects.

It should be noted that the implementation of Equation 6 (refer to FIG. 9) is a simplification of the implementation of Equation 5 (refer to FIG. 8), when b(1)=c, other b(n)=0; when a(2) =c-1, when other a(n)=0, Equation 5 is reduced to Equation 6. Therefore, it can be said that the implementation of Equation 6 is a special case of the implementation of Equation 5, and the implementation of Equation 5 is a generalization of the implementation of Equation 6.

604. The signal processing device determines, according to a preset mapping method, a mapping value corresponding to each reference factor.

The signal processing device may map the acquired multiple reference factors according to a preset mapping method, and determine each mapping value after mapping by each reference factor. Since the mapping values mapped by the reference factors are in the same dimension, the signal processing device may also be called It is within the same numerical range or the same range that can be mutually summed. Therefore, it can be said that the mapping is a unified standard, so that the signal processing device can process the mapping values mapped by the respective reference factors. For example, RSL, MCS, PER, received packet bytes, MSE, SNR can be mapped to values between 0-100; several reference factors can also be mapped to values between 0-100, in addition Several reference factors are mapped to values in the range between 0 and 50. It should be noted that when mapping values mapped between 0-50 and mapping values mapped to 0-100 are added, the mapping values between 0-50 need to be multiplied by 2 before, so that they can be 0- The mapped values between 100 are in the same standard before they can be summed with the mapped values between 0-100.

Further, the mapping method can be divided into a linear mapping and a nonlinear mapping. Which mapping method is used by the signal processing device needs to be determined according to specific engineering measurements, which can be determined in the following ways:

(1) If the mean value E(s _k , θ) follows the change from the absolute value of the normal deviation angle θ (for example, it may be a change of θ in the range of [-90, 0], or θ The change in the range of [90, 0] is approximately linearly increasing, and the signal processing apparatus may determine each mapping value corresponding to each reference factor according to a linear mapping method, wherein the normal deviation angle θ is a preset reference direction and needs to be The preset reference normal direction may also be referred to as "0 degree normal direction". The preset reference direction can be determined as follows:

Step1: Adjust each reference factor to the maximum value;

Step2: Fine-tune the fixed angle around the maximum value of each reference factor, and observe the amount of change caused by the fine adjustment of each reference factor;

Step3: Select the reference factor with the largest amount of change due to fine tuning (that is, the steepest part of the characteristic curve), and adjust the direction of the reference factor to the maximum value to be 0 degree normal.

It should be noted that the reference factor RSL is usually selected, and the direction in which the RSL is adjusted to the maximum value is determined to be 0 degree normal. The preset method for the reference direction is not limited here;

(2) If the mean E(s _k , θ) follows the change in the absolute value of θ from large to small (for example, it may be a change of θ in the range of [-90, 0], or θ at [90, The variation in the range of 0] is nonlinearly increasing. For example, there are a large number of inflection points to influence the direction in which the antenna is rotated, and the signal processing apparatus can determine the respective mapping values corresponding to the respective reference factors according to the nonlinear mapping method.

The following describes the linear mapping method and the nonlinear mapping method for each reference factor:

First, the linear mapping method of reference factors

1.1 RSL linear mapping

The reference factor RSL is taken as an example for linear mapping.

Let the RSL of the received signal range from -95 to -55 dBm (the pre-processing of step 802 is required before the range is exceeded, and the RSL needs to be subjected to clipping processing), and the corresponding mapping value is [0, 100]. Let RSL's input signal be X and the mapping value be Y, then the mapping method can be expressed by the following formula:

Y=(X+95)*2.5 (Equation 7)

According to Equation 7, the mapping value increases by 2.5 for every 1 dB increase in RSL.

It should be noted that the linear mapping method is simpler and easier to implement than the nonlinear mapping method, but sometimes it cannot be mapped in a simple linear manner. For example, RSL is also improved by 2dBm in different value segments, and it is easy to increase from -95dBm to -93dBm, but it is much more difficult to increase from -60dBm to -58dBm, and such a situation is usually not reflected by linear mapping.

1.2 Linear mapping of MCS

The description of the linear mapping is performed by taking the reference factor MCS as an example. Specifically, the mapping of the reference factor MCS may be a mapping of the reference factor MCS weighted capacity.

The signal processing apparatus can determine the mapping value Y corresponding to the weighted capacity X of the MCS by the following formula:

Y=X/R*100 (Equation 8)

Where R is the maximum capacity of the physical layer PHY.

In actual wireless transmission, different MCSs are used to adapt to different channel environment changes when packets are sent. When the channel conditions are good, the high-order MCS is used to increase the rate; when the channel conditions are poor, the low-order MCS is used to improve the reliability. The maximum MCS weighted capacity is equal to the maximum capacity R of the PHY.

1.3 PER linear mapping

The description of the linear mapping is performed by taking the reference factor PER as an example.

The linear mapping of PER can be expressed as follows. In the following relationship, the input PER is X and the output PER is Y:

(1) If X < 1E-10, then Y = 100;

(2) Otherwise, Y=-log10(x)*10.

According to the above relationship, when X is increased by one order (also called a multiplier layer), that is, the packet loss rate is decreased by 10 times, the map value is increased by 10; when X < 1E-10, the map value Y is Full score.

1.4 Linear mapping of the number of received packet bytes

The description of the linear mapping is performed by taking the reference packet receiving packet number as an example. Specifically, the mapping of the reference factor receiving packet byte number is a mapping of the rate at which the reference factor receives the packet byte number.

The mapped value of the rate at which the number of bytes of the packet is received can be expressed by the following formula:

The mapped value of the rate at which the number of bytes of the packet is received = the received data rate / the transmitted data rate * 100 (Equation 9);

The transmission data rate is a value that the signal processing device has acquired when receiving the data packet.

1.5 Linear mapping of MSE/SNR

The description of the linear mapping is made by taking the reference factor MSE or SNR as an example.

Let the MSE/SNR mapping value corresponding to the range [a, b] of MSE/SNR be [0, 100]. When the input signal of MSE/SNR is X, the mapped value Y is:

(1) If X <= a, output Y = 0;

(2) If X>=b, output Y=100;

(3) If X is between a and b, Y = 100 * (X - a) / (b - a) is output.

Second, the nonlinear mapping method of reference factors

In the embodiment of the present application, the interpolation factor may be used to perform nonlinear mapping on the reference factor. The signal processing device uses the interpolation method to nonlinearly map the reference factors and can be divided into the following 2.1 and 2.2 mapping modes.

2.1 Nonlinear mapping of the first type of reference factor

The first type of reference factor includes an RSL. In this embodiment, the first type of reference factor is described by using RSL as an example to describe a nonlinear mapping method of the first type of reference factor. Referring to FIG. 10, FIG. 10 is a schematic diagram of a nonlinear mapping relationship of RSL. The signal processing device can calculate the target received power by the following calculation formula:

Target received power = transmit power + transmit antenna gain - distance attenuation - other loss + receive antenna gain (Equation 10)

The unit of the target receiving power (power_target) and the transmitting power (power_tx) are both dBm, the unit of the transmitting antenna gain (gain_tx_antenna) and the receiving antenna gain (gain_rx_antenna) is dBi, and the unit of the distance attenuation (path_loss) is dB, and other losses are The unit of (other_loss) is dB. In FIG. 10, the horizontal axis represents the difference between the received power and the target received power, and the vertical axis represents the mapped value of the RSL. The difference between the received power and the target received power is negatively correlated with the mapped value of the RSL. That is, the greater the difference in received power, the smaller the mapping value of the RSL. Conversely, if the difference in received power is smaller, the mapping value of the RSL is larger. Large; the difference in received power is the difference between the received power and the target received power. Therefore, the signal processing device can determine the mapping value corresponding to the RSL with the negative correlation. Moreover, the non-linear mapping of the RSL has the advantage that, in the case where the variation of the difference in received power is the same in the first interval and the second interval, the amount of change of the RSL mapping value in the first interval is greater than in the second interval. The amount of change in the first interval is the area where the received power is close to the target received power, that is, the area where the received power difference is smaller than the first threshold, and the second area is the area where the received power is far from the target received power, that is, It is an area where the difference in received power is not less than the first threshold. That is to say, in the range where the difference of the received power is small (in the first interval), that is, when the received power is close to the target received power, the antenna is adjusted, and the antenna is slightly adjusted (that is, the difference in the received power is only slightly changed). It can also be seen that the output changes greatly (that is, the mapped value will change drastically), which is beneficial to the alignment of the antenna to the optimal point; and in the range where the difference in received power is large (in the second interval), that is, When the received power is far away from the target received power, even if the antenna is greatly adjusted (that is, even if the difference in received power is large), the output does not change significantly (that is, the change in the mapped value is gentle, and does not follow the reception. A dramatic change in the difference in power).

In addition, the line near the first threshold in the second interval becomes thicker, but the slope does not change, which means that the signal processing device can collect the input of the RSL in a large amount when the difference between the received power and the target received power is close to the first threshold. The signal, such that when the difference value is reduced to be close to the first threshold, a large number of mapped values of the difference value can be obtained, and therefore, the mapped value of the RSL is more accurate. When the line in the first interval becomes thicker and the slope becomes larger, it indicates that the difference value is close to zero, that is, the received power is close to the target received power, and the signal processing device can also collect a large number of input signals of the difference value. Thus, when the difference value is reduced to near zero, a large number of mapping values of the difference value can be obtained, and therefore, the mapping value of the RSL of the first interval is more accurate.

It should be noted that the first threshold (the difference between the received power and the target received power) may be 10 or 5, which is not limited herein.

Referring to FIG. 11 and FIG. 12, the nonlinear power mapping of the RSL is described in more detail below by comparing the theoretical power and the true measured power difference before and after the non-linear mapping of the RSL by the signal processing device. Figure 11 is a comparison of theoretical power and true measured power at different angles. The horizontal axis in Figure 11 is the normal deviation angle (0 degree represents 0 degree normal) and the vertical axis is received power. It can be seen from Figure 11:

(1) The difference between the sidelobe power and the main lobe power is about 12 dB;

(2) The measurement result of power has large jitter and is easy to be aligned to the side lobes;

FIG. 12 is a schematic diagram showing the relationship between the target received power and the angle obtained by mapping the transmission power by the nonlinear mapping method shown in FIG. 10 and then performing the filtering (the smoothing filter in the present embodiment).

As can be seen from Fig. 12, the RSL increases the mapping score near the center point by nonlinear mapping, so that the target is near the normal of 0 degree (that is, the preset reference direction, that is, the normal deviation angle θ is 0 degree). The received power is steeper than the side lobes. The smaller the normal deviation angle θ is, the larger the power value indicates the difference, even the fine angle adjustment causes a large change in power, that is, the more sensitive the indication. For engineering installers, the less likely it is to align to the side lobes, the easier it is to align to the center position for antenna alignment. It should be noted that the mapping value corresponding to the RSL and the mapping score can be found through the comparison table of the RSL mapping value and the mapping score.

Second, the nonlinear mapping of the second type of reference factor

Nonlinear mapping of Group A reference factors:

The Group A reference factor includes the MCS, PER, or the number of received packet bytes. The following describes the second non-linear mapping method by taking these reference factors as examples. According to the results obtained by the signal processing device for nonlinear mapping of these several reference factors, the curves are connected, and the mapping characteristics of the parameters of the second type of reference factors to be tracked by the normal deviation angle θ are roughly divided into two. In this case, the two cases are the mapping characteristics of FIG. 13 and FIG. 14, respectively. The parameters to be mapped of the second type of reference factor vary with the change of the normal deviation angle θ, wherein the parameters to be mapped of the second type of reference factor (including the Group A reference factor or the Group B reference factor) include: weighting of the MCS The ratio of the capacity to the maximum capacity, the logarithm of the PER, the ratio of the received data rate of the received packet bytes to the actual transmitted data rate, the difference between the MSE and the target MSE, or the difference between the SNR and the target SNR.

Figure 13 shows the mapping characteristics of the MCS, SNR, and the number of bytes of the packet to be mapped that follow the θ change. The parameters to be mapped of the MCS are the ratio of the weighted capacity to the maximum capacity, and the parameters to be mapped of the SNR are the SNR and the target. The difference value of the SNR and the parameter to be mapped of the number of received packet bytes are the ratio of the received data rate to the actual transmitted data rate. The mapping characteristics of the MCS, SNR, and the number of bytes of the received packet to be mapped follow the θ change are:

In the first interval, the MCS, SNR, and the number of bytes of the received packet to be mapped increase rapidly as θ decreases, while in the second interval, even if θ continues to decrease, MCS, SNR, and received packet words The parameter to be mapped of the number of sections does not increase rapidly, that is, in the case where the closer to the 0 degree normal direction (in the present embodiment, the mapping value at the 0 degree normal direction is the maximum value of the antenna alignment), the MCS The curve of the SNR, the number of bytes to be received, and the parameters to be mapped change will become more and more gradual. At this time, the first type of reference factor (for example, RSL) can be used to adjust the pre-mapping value of the RSL (ie, the difference between the received power and the target received power), so as to achieve the purpose of accurately aligning the antenna in the embodiment of the present application.

FIG. 14 is a schematic diagram showing the mapping characteristics of the PER and the MSE to be mapped parameters following the θ change. The parameter to be mapped of the PER is the logarithm of the PER, and the parameter to be mapped of the MSE is the difference between the MSE and the target MSE. The mapping characteristics of the PER and MSE parameters to be mapped follow the θ change are:

In the first interval, the mapping characteristics of PER and MSE and the mapping characteristics of MCS and SNR are just the opposite. Similar to an inverted trapezoid, the values of the parameters to be mapped of PER and MSE decrease rapidly as θ decreases. In the second interval, even if θ continues to decrease, the parameters to be mapped of PER and MSE will not decrease rapidly, that is, the closer to 0 degree normal, the parameters to be mapped of PER and MSE occur. The curve of change will become more and more gradual. At this time, the value of the pre-mapping of the RSL (ie, the difference value between the received power and the target received power) may be adjusted by using the first type of reference factor (for example, RSL), so as to achieve the purpose of precisely aligning the antenna in the embodiment of the present application.

The above describes the variation characteristics between the parameters to be mapped and the θ of the second type of reference factors in the two cases, and the nonlinear mapping method for the second type of reference factors is summarized as follows:

In the case where the second type of reference factor has the same amount of change of the parameter to be mapped in the first interval and the amount of change of the parameter to be mapped in the second interval, the amount of change of the mapped value of the second type of reference factor in the first interval is greater than The amount of change in the second interval, where the first interval is an area where the parameter to be mapped is greater than the second threshold, the second interval is an area where the parameter to be mapped is not greater than the second threshold, and the second type of reference factor may include SNR, MCS, MSE, PER or the number of bytes received.

The nonlinear mapping of each of the second type of reference factors is described in detail below.

2.2.1 Nonlinear mapping of MCS

The mapping of the reference factor MCS is a mapping of the reference factor MCS weighted capacity.

Referring to the graph of the relationship of the weighted capacity of the MCS shown in FIG. 13 as a function of the normal deviation angle θ. As can be seen from Fig. 13, the closer the weighted capacity of the MCS is to the normal of 0 degrees, the more the amount of change in the weighted capacity of the MCS becomes smoother. At this time, the map value can be obtained by adjusting the difference between the received power of the first type of reference factor (for example, RSL) and the target received power in the interval close to the normal of 0 degrees, because the difference of RSL in the interval close to the 0 degree normal direction The value changes abruptly as θ changes.

Referring to Table 2 below and FIG. 15, the nonlinear mapping method of the MCS weighted capacity is that the mapping result can be solved by the interpolation method according to the mapping relationship.

Table 2 is a mapping result corresponding to the ratio between the weighted capacity and the maximum capacity of the MCS, and Fig. 15 is a graphical result obtained according to the following Table 2, and the horizontal axis in Fig. 15 indicates the weighted capacity and the maximum capacity of the MCS. The ratio, the vertical axis represents the mapped value corresponding to the ratio. As can be seen from FIG. 15, in the second interval not less than the second threshold, the mapping result of the MCS changes gently as the ratio of the weighted capacity of the MCS to the maximum capacity changes; in the first interval smaller than the second threshold, The mapping result of the MCS changes drastically as the ratio between the weighted capacity and the maximum capacity changes. The larger the ratio between the weighted capacity and the maximum capacity of the MCS, the closer the weighted capacity is to the maximum capacity, and the closer to the maximum value of the antenna alignment (in this embodiment, the mapping value of the 0 degree normal is the maximum antenna alignment). value). It should be noted that, in the case where the amount of change in the ratio of the weighted capacity and the maximum capacity in the first interval is the same as the amount of change in the ratio in the second interval, the amount of change in the mapping value of the MCS in the first interval is greater than The amount of change in the second interval. That is, in the case where θ is close to the normal of 0 degrees, since the weighted capacity is close to the maximum capacity, even if the ratio between the weighted capacity and the maximum capacity continues to change (that is, even if the angle of θ continues to decrease), MCS The mapped values also do not change significantly.

It should be noted that the second threshold (the ratio of the weighted capacity to the maximum capacity) may be 0.8 or 0.9, which is not limited herein.

Table 2

加权容量/最大容量Weighted capacity / maximum capacity		映射结果Mapping result
00	00
0.20.2	3030
0.40.4	6060
0.50.5	7575
0.60.6	8585
0.80.8	9595
0.90.9	9898
11	100100

2.2.2 Nonlinear mapping of PER

Referring to the graph of the relationship of the PER as a function of the normal deviation angle θ shown in FIG. As can be seen from Fig. 14, the closer the PER is to the 0 degree normal, the more gradual the change in PER becomes. At this time, the map value can be obtained by adjusting the difference between the received power of the first type of reference factor (for example, RSL) and the target received power in the interval close to the normal of 0 degrees, because the difference of RSL in the interval close to the 0 degree normal direction The value changes abruptly as θ changes.

Refer to Table 3 below. Table 3 shows the mapping results corresponding to PER. Let the PER threshold be a=[1E-8 1E-7 1E-6 1E-5 1E-4 1E-3 1E-2 1E-1 2E-1 3E-1 4E-1], and the corresponding mapping value is b=[ 100 90 80 70 60 50 40 30 20 10 0].

table 3

PERPER	-10LOG10(PER)’-10LOG10(PER)’	映射结果Mapping result
1.00E-081.00E-08	80.080.0	100100
1.00E-071.00E-07	70.070.0	100100
1.00E-061.00E-06	60.060.0	9595
1.00E-051.00E-05	50.050.0	9090
1.00E-041.00E-04	40.040.0	8080
1.00E-031.00E-03	30.030.0	6060
1.00E-021.00E-02	20.020.0	3030
2.00E-012.00E-01	7.07.0	55
3.00E-013.00E-01	5.25.2	22
4.00E-014.00E-01	4.04.0	00

Let PER be X, then the mapping value Y is:

(1) If the PER threshold X is equal to a(k), then the mapped value Y=b(k);

(2) If the PER threshold X is less than a (1), then the mapping value is Y = 100;

(3) If the PER threshold X is greater than a (11), then the mapping value is Y (k) = 0;

(4) If the PER threshold X is between a(k) and a(k+1), the signal processing device may employ linear interpolation:

Y(k)=b(k)+[10*log10(X)-10*log10(a(k))]*[b(k+1)-b(k)]/[10*log10(a( k+1))-10*log10(a(k))] (Equation 11)

Please refer to FIG. 16. FIG. 16 is a graph result obtained according to Table 3. The horizontal axis of FIG. 16 represents the value "-10LOG(10PER)" after the packet loss rate conversion, and the vertical axis represents the value converted by the packet loss rate "- The mapped value of 10LOG(10PER)". As can be seen from FIG. 16, in the second interval not less than the second threshold, the mapping result of the PER changes gently with the change of the packet loss rate; in the first interval smaller than the second threshold, the mapping result of the PER will follow The change in the packet loss rate changes drastically. The smaller the ratio between the packet loss rate and the maximum packet loss rate, that is, the smaller the packet loss rate, the closer to the maximum value of the antenna alignment (in this embodiment, the mapping at 0 degree normal direction) The value is the maximum value of the antenna alignment). It should be noted that, in the case where the amount of change in the first interval (the packet loss rate) and the amount of change in the second interval are the same, the amount of change of the mapped value of the PER in the first interval is greater than that in the second interval. The amount of change. That is to say, in the case where θ is close to the normal of 0 degrees, since the packet loss rate is close to the minimum value, even if the packet loss rate continues to change, the mapped value of the PER does not change significantly.

It should be noted that the second threshold (the value of the packet loss rate "-10LOG (10 PER)") may be 60 or 65, which is not limited herein.

2.2.3 Non-linear mapping of the number of received packet bytes

The mapping of the number of reference packet received packet bytes is a mapping of the rate at which the reference factor receives the number of packet bytes.

Referring to the graph of the relationship of the rate of the number of received packet bytes shown in Fig. 13 as a function of the normal deviation angle θ. As can be seen from Fig. 13, the closer to the 0 degree normal, the more the amount of change in the rate of receiving the packet bytes becomes smoother. At this time, the map value can be obtained by adjusting the difference between the received power of the first type of reference factor (for example, RSL) and the target received power in the interval close to the normal of 0 degrees, because the difference of RSL in the interval close to the 0 degree normal direction The value changes abruptly as θ changes.

Referring to Table 4 below and FIG. 17, the method of receiving the nonlinear mapping of the rate of the number of bytes of the packet is that the mapping result can be solved by the interpolation method according to the mapping relationship. Refer to the related description in this step 604 for the interpolation method.

Table 4

Table 4 is a mapping result corresponding to the ratio between the received data rate and the actual transmitted data rate, and Fig. 17 is a graphical result obtained according to Table 4, and the horizontal axis of Fig. 17 indicates the received data rate and actual number of received packet bytes. The ratio of the transmitted data rate, and the vertical axis represents the mapping result corresponding to the ratio. As can be seen from FIG. 17, in the second interval not less than the second threshold, the mapping result of the rate of receiving the number of packet bytes changes gently as the ratio between the received data rate and the actual transmitted data rate changes; In the first interval of the second threshold, the mapping result of the rate of receiving the number of packet bytes varies drastically as the ratio between the received data rate and the actual transmitted data rate changes. The larger the ratio between the received data rate and the actual transmitted data rate, that is, the larger the received data rate, the closer to the maximum value of the antenna alignment (in this embodiment, the mapping value of 0 degree normal) Is the maximum value of the antenna alignment). It should be noted that, in the case where the amount of change in the ratio in the first interval (between the received data rate and the actual transmitted data rate) and the amount of change in the ratio in the second interval are the same, the rate of receiving the number of bytes of the packet is The amount of change in the map value in the first interval is greater than the amount of change in the second interval. That is, in the case where θ is close to the normal of 0 degrees, since the received data rate is close to the actual transmitted data rate, even if the ratio between the received data rate and the actual transmitted data rate continues to change (ie, even if it continues to decrease) The angle of θ), the mapped value of the rate of receiving the number of packets does not change significantly.

It should be noted that the second threshold (the ratio of the received data rate of the number of received packets to the actual transmitted data rate) may be 0.8 or 0.9, which is not limited herein.

Group B reference factor:

The Group B reference factor includes MSE or SNR. The following describes the manner of the third nonlinear mapping by taking the two reference factors as an example.

Referring to the graph of the relationship between the SNR and the normal deviation angle θ shown in FIG. 13, and the relationship of the MSE with the normal deviation angle θ shown in FIG. As can be seen from Figures 13 and 14, the closer the MSE/SNR (meaning the two reference factors of MSE or SNR) to the 0 degree normal, the more gradual the MSE/SNR variation will become. At this time, the map value can be obtained by adjusting the difference between the received power of the first type of reference factor (for example, RSL) and the target received power in the interval close to the normal of 0 degrees, because the difference of RSL in the interval close to the 0 degree normal direction The value changes abruptly as θ changes.

Referring to Table 5 below and FIG. 18, the method of nonlinear mapping of MSE/SNR is that the mapping result can be solved by interpolation method according to the mapping relationship. Refer to the related description in this step 604 for the interpolation method.

table 5

与目标MSE/SNR的差异值(dB)Difference value from target MSE/SNR (dB)	映射结果 Mapping result
00	100100
22	9898
44	9595
66	9090
88	8585
1212	7070
1616	5050
2020	3030
2525	00

Table 5 is the mapping result corresponding to the difference value between the MSE/SNR and the target MSE/SNR, and FIG. 18 is a graphical result obtained according to Table 5, and the horizontal axis represents the difference value between the MSE/SNR and the target MSE/SNR. The vertical axis represents the mapped value of MSE/SNR. As can be seen from FIG. 18, in the first interval smaller than the second threshold, the mapping result of the MSE/SNR changes gently as the difference value between the MSE/SNR and the target MSE/SNR changes; not less than the second threshold. In the second interval, the MSE/SNR mapping result will change drastically as the difference between the MSE/SNR and the target MSE/SNR changes. The smaller the difference between the MSE/SNR and the target MSE/SNR is, that is, the larger the MSE/SNR is, the closer to the maximum value of the antenna alignment (in this embodiment, the mapping of the 0 degree normal) The value is the maximum value of the antenna alignment). It should be noted that, in the case where the amount of change in the difference value in the first interval (between MSE/SNR and target MSE/SNR) and the amount of change in the difference value in the second interval are the same, the mapped value of MSE/SNR The amount of change in the first interval is smaller than the amount of change in the second interval. That is, in the case where θ is close to 0 degree normal, since the MSE/SNR is close to the target MSE/SNR, even if the difference value between the MSE/SNR and the target MSE/SNR continues to change, the MSE/SNR mapping The value will not change significantly.

It should be noted that the second threshold (the difference between the MSE/SNR and the target MSE/SNR) may be 5 or 8, which is not limited herein.

Third, using interpolation method to nonlinearly map reference factors

The following is a detailed description of the non-linear mapping of reference factors by the interpolation method for the above signal processing apparatus. Referring to FIG. 19, FIG. 19 is a schematic diagram of linear interpolation in the embodiment of the present application, and the curve shown in FIG. 18 can be approximated by a plurality of broken lines. As long as the number of fold points is sufficient, the curve can be approximated infinitely. A few fold lines are usually used in the project to approximate the entire curve. The implementation method is as follows:

(1) pre-stored x-axis vectors [x ₁ , x ₂ , ..., x _n ] of length n and y-axis vectors [y ₁ , y ₂ , ..., y _n ], ie preset x-axis vectors and y-axis vectors Corresponding tables for searching the x-axis vector and the y-axis vector;

(2) When the output is X, determine the method by which the polyline approximates the output Y:

a) If X is just at the polyline point, X = x _k , then output Y = y _k ;

b) If X is not at the polyline point, then determine the interval k where X is located, guarantee x _k-1 <X<x _k , and output Y by linear interpolation.

Y=y _k-1 +(XX _k-1 )*(y _k -y _k-1 )/(X _k -X _k-1 ) (Equation 12).

For each of the reference factors, the signal processing apparatus may use a linear mapping method or a non-linear mapping method according to the situation, which is not limited herein.

605. The signal processing device calculates each weighting coefficient corresponding to each reference factor.

After determining the respective mapping values corresponding to the respective reference factors according to the preset mapping method, the signal processing apparatus may calculate each weighting coefficient corresponding to each reference factor. Further, the signal processing device may dynamically weight the reference factor, and may also perform fixed weighting on the reference factor, which is not limited herein. The following describes the fixed weighting method and the dynamic weighting method separately:

First, dynamic weighting

In the case that the signal processing device dynamically weights the reference factor, the signal processing device may calculate each weighting coefficient (also referred to as a weight) corresponding to each reference factor according to the normal deviation angle. It should be noted that the normal deviation angle may be It is the angle between the maximum radiation direction of the antenna beam and the antenna normal, and the antenna normal is perpendicular to the antenna. Further, the signal processing device calculates each weighting coefficient corresponding to each reference factor according to the normal deviation angle, and can perform calculation according to the following method, thereby automatically determining the weighting coefficient:

(1) Let s _k be the Kth reference factor and f(s _k ) be the mapping result of s _k ;

(2) When the normal deviation angle is θ, ▽E(S _k , θ) is the mapping result of the Kth reference factor. The mean value of the output f(s _k , θ) follows the rate of change of θ, σ(s _k , θ) is the variance of the mapped values of the Kth reference factor;

(3) The weighting coefficient of the kth reference factor is calculated as Equation 13 below:

w _k =F*▽E(s _k ,θ)/σ(s _k ,θ) (Equation 13)

among them,

The meaning of Formula 14 is that the larger the ▽E(s _k , θ) indicating the rate of change of the mean with θ, the larger the weight; the larger the variance σ(s _k , θ) representing the jitter, the smaller the weight.

Correction factor F guarantees the sum of ownership values

When the signal processing device dynamically weights the reference factor, the weighting coefficient w _k changes as the reference factor f(s _k , θ) changes.

Specifically, the method of dynamically weighting is described below by taking reference factor flow and RSL as an example.

When the normal deviation angle is large, the RSL is relatively stable due to the irregular jitter of the RSL, and the antenna is basically aligned (typically 2 degrees). The difficulty lies in the fact that the relatively stable area of the RSL is too small. When the off angle is large, the adjustment direction of the antenna is judged according to the change of the RSL, and it is also difficult to slow the irregular beat of the RSL by adjusting the antenna. In engineering measurements, it is found that the jitter (ie, jitter) of a small traffic data (for example, the rate of 100 Kbps) transmitted from a certain site A is relatively more stable because the small traffic data uses a lower-order MCS due to the lower-order MCS. With better sensitivity (see Table 5 below), the same power can transmit longer distances, so the transmission can be maintained when the link quality is not good enough. Adjusting the antenna can see the change of the flow, so the traffic is used as the antenna. The basis for the adjustment. With the adjustment of the antenna, the flow tends to be stable, but at this time the antenna has not been adjusted to the optimal state. Since the microwave link is affected by wind and rain, to ensure the link availability (that is, to ensure the reliability of the link), the link margin must be left so that the signal level is higher than the sensitivity. Already coarse alignment, data traffic cannot be increased (for example, the Internet access rate is 1M, the antenna is 1M after the antenna is aligned, and the Internet access rate will not increase). However, after coarse alignment, the RSL will become relatively stable, so RSL is adopted. The change is used as a reference for antenna adjustment.

Table 6 below is an example of MCS and receiver sensitivity. The left column is the MCS order number and the right column is the sensitivity. As can be seen from Table 6, the sensitivity of the order of 0 is -78, and the sensitivity of the order of 12 is -53. From this, it can be seen that the sensitivity of -78 is felt when the order of MCS is 0, and the order is 12 Only the sensitivity of -53 can be felt, so the sensitivity of higher order MCS is lower. It should be noted that the order of the order in Table 6 is from the lowest order "0" to the highest "12".

Table 6

In this embodiment, according to the above adjustment idea that the change of the RSL is used as the reference basis for the antenna adjustment, the specific dynamic weighting method is as follows: f ₁ (s ₁ ), f ₂ (s ₂ ) respectively represent the data flow rate and the receiving level. The mapped value of RSL; w ₁ , w ₂ represent the weighting coefficients of the data traffic and the reception level RSL, respectively. When the data traffic is low, the weighting coefficient w _{1 of the} data traffic takes a large value, and is used as a coarse alignment of the antenna; when the data traffic increases beyond a certain threshold, the weight of the weighting coefficient w ₂ of the RSL increases. Used as a fine alignment of the antenna.

The advantage of aligning the antenna in the above manner is that the flow can be quickly adjusted to a substantially aligned range, which speeds up the search time, but when the flow rate is adjusted to the maximum, it is not equal to the complete alignment of the antenna; By aligning the antenna through the RSL, it is determined whether the antenna alignment reaches the target value according to whether the RSL of the observed link reaches the target value.

It should be noted that the dynamic weighted weighting coefficient will dynamically change according to the variable of Equation 13.

Second, fixed weighting

2.1 In the case where the signal processing device fixedly weights the reference factor, the weighting coefficient w _k of each factor is a fixed value, and the selection principle of the weighting coefficient w _k is as follows: the variation of the reference factor near the normal deviation angle θ=0 The larger the weight, the larger the configuration of the weight (ie, the weighting coefficient), for example,

Δ(s _k )=|f _k (s _k ,0)-f _k (s _k ,Δθ)| (Equation 16)

The change value of the Kth factor mapping result when the rate of change of the normal deviation angle is Δθ, where f _k (s _k , 0) is the mapping of the Kth reference factor when the θ is 0 degrees a value, f _k (s _k , Δθ) is a mapping value of the Kth reference factor when the rate of change of θ is Δθ; w _k =F*Δ(s _k ); the correction factor F is a constant

The sum of the guaranteed weights is 1,

It should be noted that the weighting coefficient of the fixed weight is calculated according to the formula 13 in the engineering measurement stage. After the weighting coefficient is configured for each reference factor, the weighting coefficient of each reference factor in the subsequent antenna alignment process will not be Change again.

The method for calculating the weighting coefficient used in the present embodiment is not specifically limited.

606. The signal processing device weights each mapping value according to each weighting coefficient corresponding to each reference factor to obtain a weighting value of each mapping value.

After the signal processing device calculates the weighting coefficient corresponding to each reference factor, the weighting value of each mapping value may be separately calculated according to the weighting coefficient corresponding to each reference factor, and the calculation formula may refer to Equation 17 below.

607. The signal processing device adds the respective weighting values to obtain a comprehensive index.

After the signal processing device calculates the weighting coefficients corresponding to each reference factor, the weighting values can be added to obtain a composite index, which is used for antenna alignment. Calculate the composite index c by:

Where N is the number of reference factors, w _k is the weighting coefficient corresponding to the Kth reference factor, s _k is the Kth reference factor, and f _k (s _k ) is the mapping value corresponding to the Kth reference factor, N And K are both positive integers.

608. Adjust the pointing of the antenna;

After calculating the composite index for aligning the various reference factors of the antenna, the signal processing device begins to adjust the orientation of the antenna so that the antennas between the devices of both communicating parties can be aligned. Adjusting the pointing of the antenna can be manually adjusted, and the command can be sent to the communication device, so that the communication device automatically adjusts the antenna pointing according to the command, and the specific manner of adjusting the antenna pointing is not specifically limited herein.

609. The signal processing device determines whether the comprehensive index reaches a target threshold.

After adjusting the antenna pointing, the signal processing device can compare the comprehensive index of each reference factor and the preset value range to determine whether the comprehensive index reaches the target value range; if yes, execute step 610; if not, execute step 611.

In this embodiment, a preset threshold of five thresholds (ie, five gears) may be preset, for example, five thresholds may be preset to [10, 40, 60, 80, 90], and the target threshold may be set in the first 5 thresholds "90", if the composite index reaches the 5th threshold "90", the signal processing device determines the comprehensive index of the reference factor to reach the standard, and if the composite index does not reach the 5th threshold, the signal processing The device determines that the composite index of the reference factor is not up to standard. Since there are 5 thresholds instead of just one threshold, when adjusting the antenna pointing, it can confirm the state of the comprehensive index distance according to the lighting condition. If only one or two lights are on, it means that the comprehensive index distance is up to standard. A big gap, if the 4 lights are on, the composite index is close to the standard.

610. The signal processing device determines the comprehensive index to reach the standard;

In this embodiment, if the signal processing device determines that the composite index reaches the target threshold, it is determined that the composite index has reached the standard, indicating that the antenna is aligned. Specifically, the signal processing apparatus may regard the comprehensive index of the reference factor reaching the fifth threshold “90” as “achieving the standard”, and the composite index of the reference factor reaching at least one or zero of the first to fourth thresholds is regarded as "did not make it". In the actual application scenario, five thresholds can be used to represent five thresholds. When the composite index reaches the first threshold "10", only one light is illuminated, and the illuminated light is displayed in green; When the composite index reaches the second threshold "40", two lights are lit; and so on, when the composite index reaches the fifth threshold "90", the 5 lights are fully illuminated, ie The composite index "reaches the standard", indicating that the antenna is aligned.

611. The signal processing device cyclically executes the steps from step 608 to step 609.

In this embodiment, if the signal processing device determines that the composite index has not reached the target threshold, it is determined that the composite index has not reached the target, indicating that the antenna is not aligned. Still taking the example of step 609 and step 610 as an example, if only 4 盏 or less lights are displayed, it means that the comprehensive index of the reference factor has not reached the target threshold, that is, the threshold value is “90”, and the signal processing device at this time Steps 608 and 609 can be performed cyclically.

The beneficial effect of this embodiment is that, when performing antenna alignment, first, a reference factor of quality of a plurality of different units of response received signals is mapped to the same reference range that can be summed, and then the mapped maps are mapped. The values are weighted to enable the signal processing device to more easily align the antenna, so in different application scenarios, ie, where the signal processing device can perform antenna alignment with a plurality of different reference factors, it can be according to the present embodiment. The signal processing method determines the type of mapping and weighting strategy to help more accurately align the antenna.

The above describes how to adjust the antenna with multiple reference factors by signal processing method to make the antenna alignment. The following embodiment takes the actual scene as an example, and how to use the two reference factors RSL and MCS to align the antenna. A description of the signal processing method is performed. 20 is a schematic flowchart of another embodiment of a signal processing method in an embodiment of the present application, and FIG. 21 is a schematic diagram of another embodiment of a signal processing method in an embodiment of the present application, which is used to calculate a reference. Factor synthesis index. 21 is another embodiment of a signal processing method in an embodiment of the present application, including:

2101: The signal processing device acquires the RSL and the MCS of the received signal;

In this embodiment, the signal processing device acquires RSL and MCS capable of reflecting the quality of the received signal. Step 2101 is similar to step 601, and details are not described herein again.

It should be noted that, in addition to the received signals RSL and MCS in this embodiment, the signal processing apparatus may acquire other reference factors of the received signal, such as SNR, PER, number of received packet bytes, and the like, and the signal The processing device arbitrarily combines the acquired reference factors for processing in subsequent steps.

2102. The signal processing device performs preprocessing on the RSL and the MCS.

After acquiring the RSL and the MCS, the signal processing device performs pre-processing on the RSL and performs pre-processing on the weighted capacity calculation of the MCS. Step 2102 is similar to step 602, and details are not described herein again.

2103. The signal processing device determines, according to a preset mapping method, a mapping value corresponding to the RSL and the MCS respectively.

After the signal processing device completes the pre-processing operation on the RSL and the MCS, it first determines whether the RSL and the MCS should use a linear mapping or a nonlinear mapping method. In this embodiment, the mean value E(s _k , θ) of the RSL and the MCS is described as an example in which the variation of θ in the range of [-90, 0] is nonlinearly increased. In this case, the signal processing device The mapping value corresponding to each of the RSL and the MCS may be determined by a non-linear mapping method. The non-linear mapping method of RSL and MCS has been described in detail in 2.1 and 2.2 of step 603 of the above embodiment, and details are not described herein again.

2104. The signal processing device calculates a weighting coefficient corresponding to each of the RSL and the MCS.

In this embodiment, the signal processing apparatus uses a fixed weighting as an example to describe how to calculate the weighting coefficients corresponding to each of the RSL and the MCS. The signal processing device obtains the weighting coefficient of each of the RSL and the MCS according to the fixed weighting formula of the step 605 in the above embodiment, according to the engineering measurement that the normal deviation angle θ is near 0 and the RSL variation is greater than the MCS variation. . The method of fixed weighting has been described in detail in step 605 and will not be described again here.

2105. The signal processing device weights the mapping values according to respective weighting coefficients of the RSL and the MCS, to obtain weighting values of the mapping values.

After calculating the weighting coefficients corresponding to each of the RSL and the MCS, the signal processing device may separately weight the mapped values according to the respective weighting coefficients to obtain weighting values of the mapped values. For the calculation of the weighting value of each mapping value, the formula 17 of the step 607 in the above embodiment may be used, and details are not described herein again.

2106. The signal processing device uses smoothing filtering to eliminate jitter of the RSL and the MCS;

In this embodiment, after obtaining the weighting value of each mapping value, the RSL and the MCS are greatly affected by the noise, and the RSL and MCS mapping values are preset in [0, T]. The fluctuations in the time exceeds ±2.5, so the smoothed filtering method is needed to control the RSL and MCS mapping values (here as input signals) within ±2.5, thus eliminating RSL and MCS jitter.

Further, the signal processing apparatus employs a process of smoothing the mapped values (ie, input signals) of the RSL and the MCS by the alpha filter structure. For the processing manner, reference may be made to FIG. 9 and Equation 6 of Step 603 in the foregoing embodiment, and a detailed description of Equation 6, and details are not described herein again.

The following steps from step 2107 to step 2111 are similar to the steps 607 to 611 in the foregoing embodiment, and details are not described herein again.

2107. The signal processing device adds the weighted values of the RSL and the MCS to obtain a comprehensive index.

2108. Adjust the pointing of the antenna;

2109. The signal processing device determines whether the comprehensive index reaches a target threshold;

2110. The signal processing device determines that the comprehensive index meets the standard;

2111. The signal processing device cyclically performs steps 2108 to 2109.

In this embodiment, when performing antenna alignment, since the signal processing apparatus can simultaneously use the two reference factors RSL and MCS for antenna alignment, after mapping the RSL and the MCS, the mapping values of the two reference factors can be The summation is added within the same calculation standard, and the signal processing device can separately weight the RSL and the MCS according to the influence magnitude of the reference factor, thereby calculating a comprehensive index of the reference factor for achieving more accurate antenna alignment.

The signal processing method in the embodiment of the present application is described above. The signal processing device in the embodiment of the present application is described below. Referring to FIG. 22, an embodiment of the signal processing device in the embodiment of the present application includes:

The signal processing device 2200 can vary considerably depending on configuration or performance and can include one or more central processing units (CPUs) 2201 (eg, one or more processors).

Signal processing device 2200 may also include one or more power sources 2202, one or more acquisition interfaces 2203, and/or one or more operating systems, such as Windows ServerTM, Mac OS XTM, UnixTM, LinuxTM, FreeBSDTM, and the like. After the acquisition interface 2203 acquires the reference factor of the received signal, the acquisition interface 2203 transmits the acquired reference factors of the plurality of received signals to the central processing unit 2201, and the central processing unit 2201 maps and weights the reference factors of the received signals. A comprehensive index for antenna alignment is obtained.

The flow executed by the central processing unit 2201 in the signal processing apparatus 2200 in this embodiment is similar to the method flow described in the foregoing embodiments shown in FIG. 6 to FIG. 21, and details are not described herein again.

The beneficial effect of the embodiment of the present application is that the central processor 2201 can map the reference factors of the plurality of received signals acquired by the collection interface 2203 to values in the same calculation range that can be added and summed according to a preset mapping method. Then, the central processing unit 2201 weights each mapping value according to each weighting coefficient corresponding to each reference factor to obtain a weighting value of each mapping value, and finally adds a weighted value to obtain a comprehensive index reflecting the quality of the received signal, and utilizes The comprehensive index can adjust the mapping mode and the weighting strategy in different application scenarios, so that the signal indication is more accurate and more accurate to assist antenna alignment.

Embodiments of the present application also provide a computer storage medium for storing computer software instructions for use in the foregoing signal processing apparatus, including a program for executing a signal processing apparatus. The embodiment of the present application further provides a computer program product, which includes computer software instructions, which can be loaded by a processor to implement the method flow in the foregoing embodiments shown in FIG. 6 to FIG.

A person skilled in the art can clearly understand that for the convenience and brevity of the description, the specific working process of the system, the device and the unit described above can refer to the corresponding process in the foregoing method embodiment, and details are not described herein again.

In the several embodiments provided by the present application, it should be understood that the disclosed system, apparatus, and method may be implemented in other manners. For example, the device embodiments described above are merely illustrative. For example, the division of the unit is only a logical function division. In actual implementation, there may be another division manner, for example, multiple units or components may be combined or Can be integrated into another system, or some features can be ignored or not executed. In addition, the mutual coupling or direct coupling or communication connection shown or discussed may be an indirect coupling or communication connection through some interface, device or unit, and may be in an electrical, mechanical or other form.

The units described as separate components may or may not be physically separated, and the components displayed as units may or may not be physical units, that is, may be located in one place, or may be distributed to multiple network units. Some or all of the units may be selected according to actual needs to achieve the purpose of the solution of the embodiment.

In addition, each functional unit in each embodiment of the present application may be integrated into one processing unit, or each unit may exist physically separately, or two or more units may be integrated into one unit. The above integrated unit can be implemented in the form of hardware or in the form of a software functional unit.

The integrated unit, if implemented in the form of a software functional unit and sold or used as a standalone product, may be stored in a computer readable storage medium. Based on such understanding, the technical solution of the present application, in essence or the contribution to the prior art, or all or part of the technical solution may be embodied in the form of a software product stored in a storage medium. A number of instructions are included to cause a computer device (which may be a personal computer, server, or network device, etc.) to perform all or part of the steps of the methods described in various embodiments of the present application. The foregoing storage medium includes: a U disk, a mobile hard disk, a read-only memory (ROM), a random access memory (RAM), a magnetic disk, or an optical disk, and the like. .

The above embodiments are only used to explain the technical solutions of the present application, and are not limited thereto; although the present application has been described in detail with reference to the foregoing embodiments, those skilled in the art should understand that they can still The technical solutions described in the embodiments are modified, or the equivalents of the technical features are replaced by the equivalents. The modifications and substitutions of the embodiments do not depart from the spirit and scope of the technical solutions of the embodiments of the present application.

Claims

A signal processing method, comprising:

The signal processing device acquires a reference factor of the received signal, the reference factor is used to reflect the quality of the received signal, and the reference factor includes at least one first type reference factor and at least one second type reference factor, the first class The reference factor includes a received signal level RSL;

The signal processing device determines, according to a preset mapping method, a mapping value corresponding to each of the reference factors;

And the signal processing device weights each mapping value according to each weighting coefficient corresponding to each of the reference factors to obtain a weighting value of each of the mapping values;

The signal processing device adds each of the weighting values to obtain a composite index for antenna alignment.
The method according to claim 1, wherein said second type of reference factor comprises a Group A reference factor or a Group B reference factor, said Group A reference factor comprising a modulation coding mechanism MCS, a packet loss rate PER Or receive the number of packet bytes, the Group B reference factor including the signal to noise ratio SNR or the mean square error MSE of the received signal constellation point.
The method according to claim 1 or 2, wherein said signal processing means adds said weighting values to obtain a composite index comprising:

The composite index c is calculated by:

Where N is the number of reference factors, w k is the weighting coefficient corresponding to the Kth reference factor, s k is the Kth reference factor, and f k (s k ) is the Kth reference factor Corresponding mapping values, N and K are positive integers.
The method according to claim 1 or 2, wherein the signal processing device determines, according to a preset mapping method, a mapping value corresponding to each of the reference factors, including:

The signal processing device determines the mapping value corresponding to each of the reference factors according to a linear mapping method or a nonlinear mapping method.
The method according to claim 4, wherein the nonlinear mapping method comprises:

The difference between the mapping value of the first type of reference factor and the received power is a negative correlation, wherein the difference of the received power is a difference between the received power and the target received power;

In a case where the change in the difference of the received power is the same in the first interval and the second interval, the amount of change of the mapping value of the first type of reference factor in the first interval is greater than in the second interval The amount of change within the first interval is an area in which the difference in received power is less than a first threshold, and the second interval is an area in which the difference in received power is not less than the first threshold.
The method according to claim 4, wherein the nonlinear mapping method comprises:

The mapping value of the Group A reference factor is in the case where the amount of change of the parameter to be mapped in the first interval is the same as the amount of change in the parameter to be mapped in the second interval. The amount of change in the first interval is greater than the amount of change in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is the to-be-mapped The parameter whose parameter is not smaller than the second threshold, the parameter to be mapped corresponding to the A group reference factor includes a ratio of the weighted capacity to the maximum capacity of the MCS, a logarithm of the PER, or a received data rate and an actual transmit data rate. The ratio.
The method according to claim 4, wherein the nonlinear mapping method comprises:

If the amount of change of the parameter to be mapped in the first interval of the group B reference factor is the same as the amount of change in the parameter to be mapped in the second interval, the mapping value of the group B reference factor is The amount of change in the first interval is smaller than the amount of change in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is the The mapping parameter is not smaller than the area of the second threshold, and the parameter to be mapped corresponding to the group B reference factor includes a difference value of the MSE and the target MSE, or a difference value between the SNR and the target SNR.
The method according to any one of claims 1 to 7, wherein the signal processing device weights each of the mapping values according to respective weighting coefficients corresponding to each of the reference factors to obtain each of the Before mapping the weighted values of the values, the method further includes:

The signal processing device calculates each of the weighting coefficients corresponding to each of the mapping values according to a normal deviation angle θ, wherein the θ is an angle between a preset reference direction and a target direction to be aligned.
The method according to claim 8, wherein the signal processing means calculates a formula of each of the weighting coefficients corresponding to each of the mapping values according to the θ as follows:

Where sk is the Kth reference factor,
The mean value of the mapped value of the Kth reference factor follows the rate of change of the normal deviation angle θ, σ(s k , θ) is the variance of the mapped value of the Kth reference factor, and F is a correction factor. The formula for calculating the correction factor is as follows:
The method according to any one of claims 1 to 7, wherein the signal processing device weights each mapping value according to each weighting coefficient corresponding to each of the reference factors to obtain each of the mapping values. Before the weighting value, the method further includes:

The signal processing device presets each of the weighting coefficients corresponding to each of the mapping values, and the calculation formula of the weighting coefficients is as follows:

w k =F*Δ(s k );

Where Δ(s k ) represents the amount of change of the mapping value of the Kth reference factor;

F is the correction factor and is a constant. The formula is as follows:

The correction factor is used to ensure that the sum of the weighting coefficients is one.
The method according to claim 10, wherein said Δ(s k ) is calculated as follows:

Δ(s k )=|f k (s k ,0)-f k (s k ,Δθ)|;

Where f k (s k , 0) is a mapping value of the Kth reference factor when the normal deviation angle θ is 0 degrees, and f k (s k , Δθ) is the rate of change of the θ by the Δθ The mapped value of the Kth reference factor.
The method according to claim 10, wherein after the signal processing device acquires the reference factor of the received signal, the method further comprises:

The signal processing device smooth filters the reference factor, and the smoothing filter is used to cancel jitter of the reference factor.
The method according to claim 12, wherein the smoothing filter is calculated as follows:

Where N is the order of the smoothing filter, n is the sequence number of each step of the smoothing filter, X is the input signal of the reference factor, Y is the output signal of the reference factor, and an, bn are smoothed The filtered coefficient, m is the time at which the input signal X is smooth filtered to obtain the output signal Y.
A signal processing device, comprising: a processor, an acquisition interface, and a bus;

The processor and the collection interface are respectively connected to the bus;

The acquisition interface is configured to acquire a reference factor of the received signal, the reference factor is used to reflect a quality of the received signal, and the reference factor includes at least one first type reference factor and at least one second type reference factor, The first type of reference factor includes a received signal level RSL;

The processor is configured to determine mapping values corresponding to the reference factors according to a preset mapping method, and weight each mapping value according to each weighting coefficient corresponding to each reference factor to obtain a weighting value of each of the mapping values. And adding each of the weighting values to obtain a composite index for performing antenna alignment.
The signal processing apparatus according to claim 14, wherein said second type of reference factor comprises a Group A reference factor or a Group B reference factor, said Group A reference factor comprising a modulation coding mechanism MCS, packet loss Rate PER or number of received packet bytes, the Group B reference factor including signal to noise ratio SNR, mean square error MSE of the received signal constellation point.
The signal processing apparatus according to claim 14 or 15, wherein the processor is specifically configured to calculate the composite index c by:

Where N is the number of reference factors, w k is the weighting coefficient corresponding to the Kth reference factor, s k is the Kth reference factor, and f k (s k ) is the Kth reference factor Corresponding mapping values, N and K are positive integers.
The signal processing apparatus according to claim 14 or 15, wherein the processor is specifically configured to determine the mapping value corresponding to each of the reference factors according to a linear mapping method or a nonlinear mapping method.
The signal processing apparatus according to claim 17, wherein said nonlinear mapping method comprises:

The difference between the mapping value of the first type of reference factor and the received power is a negative correlation, wherein the difference between the received power is a difference between the received power and the target received power; and within the first interval and the second interval In the case where the change in the difference in received power is the same, the amount of change of the map value of the first type of reference factor in the first interval is greater than the amount of change in the second interval, wherein the first The interval is an area in which the difference in received power is smaller than a first threshold, and the second interval is an area in which the difference in received power is not less than the first threshold.
The signal processing apparatus according to claim 17, wherein said nonlinear mapping method comprises:

In the case that the amount of change of the parameter to be mapped in the first interval is the same as the amount of change in the parameter to be mapped in the second interval, the mapping value of the group A reference factor is in the first The amount of change in an interval is greater than the amount of change in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is that the parameter to be mapped is not An area smaller than the second threshold, the parameter to be mapped corresponding to the A group reference factor includes a ratio of a weighted capacity to a maximum capacity of the MCS, a logarithm of a PER, or a ratio of a received data rate to an actual transmitted data rate. .
The signal processing apparatus according to claim 17, wherein said nonlinear mapping method comprises:

If the amount of change of the parameter to be mapped in the first interval of the group B reference factor is the same as the amount of change in the parameter to be mapped in the second interval, the mapping value of the group B reference factor is The amount of change in the first interval is smaller than the amount of change in the second interval, wherein the first interval is an area in which the parameter to be mapped is smaller than a second threshold, and the second interval is the The mapping parameter is not smaller than the area of the second threshold, and the parameter to be mapped corresponding to the group B reference factor includes a difference value of the MSE and the target MSE, or a difference value between the SNR and the target SNR.
The signal processing apparatus according to any one of claims 14 to 20, wherein the processor is further configured to calculate each of the weighting coefficients corresponding to each of the mapping values according to a normal deviation angle θ, wherein The θ is an angle between a preset reference direction and a target direction to be aligned.
The signal processing apparatus according to claim 21, wherein the processor is specifically configured to calculate, according to the θ, a formula of each of the weighting coefficients corresponding to each of the mapping values as follows:

Where s k is the Kth reference factor,
The mean value of the mapped value of the Kth reference factor follows the rate of change of the normal deviation angle θ, σ(s k , θ) is the variance of the mapped value of the Kth reference factor, and F is a correction factor. The formula for calculating the correction factor is as follows:
The signal processing apparatus according to any one of claims 14 to 20, wherein the processor is further configured to preset each of the weighting coefficients corresponding to each of the mapping values, and a calculation formula of the weighting coefficients as follows:

w k =F*Δ(s k );

Where Δ(s k ) represents the amount of change of the mapping value of the Kth reference factor;

F is the correction factor and is a constant. The formula is as follows:

The correction factor is used to ensure that the sum of the weighting coefficients is one.
A signal processing device according to claim 23, wherein

The formula for calculating Δ(s k ) is as follows:

Δ(s k )=|f k (s k ,0)-f k (s k ,Δθ)|;

Where f k (s k , 0) is a mapping value of the Kth reference factor when the normal deviation angle θ is 0 degrees, and f k (s k , Δθ) is the rate of change of the θ by the Δθ And a mapping value of the Kth reference factor, wherein the θ is an angle between a preset reference direction and a target direction to be aligned.
The signal processing apparatus according to claim 23, wherein the processor is further configured to perform smoothing filtering on the reference factor, the smoothing filtering to cancel jitter of the reference factor.
The signal processing apparatus according to claim 25, wherein said smoothing filter is calculated as follows:

Where N is the smoothing filter order, n is the sequence number of each step of the smoothing filter, X is the input signal of the reference factor, Y is the output signal of the reference factor, and an and bn are smoothing filters The coefficient, m is the time at which the input signal X is smoothed to obtain the output signal Y.
A computer program product comprising instructions, characterized in that, when run on a computer, the computer is caused to perform the method of any one of claims 1 to 13.
A computer readable storage medium comprising instructions for causing a computer to perform the method of any one of claims 1 to 13 when the instructions are run on a computer.