WO2019169904A1 - 一种低成本输入抗过压保护电路 - Google Patents

一种低成本输入抗过压保护电路 Download PDF

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Publication number
WO2019169904A1
WO2019169904A1 PCT/CN2018/116951 CN2018116951W WO2019169904A1 WO 2019169904 A1 WO2019169904 A1 WO 2019169904A1 CN 2018116951 W CN2018116951 W CN 2018116951W WO 2019169904 A1 WO2019169904 A1 WO 2019169904A1
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Prior art keywords
circuit
input
control
capacitor
resistor
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PCT/CN2018/116951
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English (en)
French (fr)
Inventor
罗皓
宋建峰
程志勇
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广州金升阳科技有限公司
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Publication of WO2019169904A1 publication Critical patent/WO2019169904A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
    • H02H9/04—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection responsive to excess voltage
    • H02H9/045—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection responsive to excess voltage adapted to a particular application and not provided for elsewhere
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H1/00—Details of emergency protective circuit arrangements
    • H02H1/0007—Details of emergency protective circuit arrangements concerning the detecting means
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
    • H02H9/04—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection responsive to excess voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/325—Means for protecting converters other than automatic disconnection with means for allowing continuous operation despite a fault, i.e. fault tolerant converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

Definitions

  • the invention relates to the field of circuits, and in particular to an input anti-overvoltage protection circuit for use in a three-phase four-wire and feeder power supply system.
  • Another method is to increase the input overvoltage protection circuit when detecting When the grid voltage is too high, the control chip is stopped. This method can only be used when the overvoltage is small. When the grid voltage is higher than 1.5 times, the rectified voltage has exceeded the large capacitor withstand voltage. Even the switch tube withstand voltage, which essentially stops working when overvoltage, does not protect the rear stage circuit.
  • Electrolytic capacitors and switch tubes are often over-sized and hard-resistant when over-voltage, and there is great safety. Hidden dangers. Therefore, it is necessary to improve the existing technology and design a low-cost anti-overvoltage protection circuit that can safely and reliably protect the subsequent circuits from normal operation when the grid voltage is abnormally high to twice the original.
  • the present invention provides a novel input overvoltage protection circuit realized by a chopper method.
  • the input voltage is generally an AC sinusoidal signal.
  • the absolute value of the voltage will change from the minimum value to the maximum value in one cycle.
  • the chopper circuit can disconnect the rear stage circuit and the large storage capacitor when the absolute value of the input AC voltage is high.
  • the latter circuit is maintained below a certain voltage, and the post-stage circuit can work normally under overvoltage. This circuit can effectively protect the switching power supply when the voltage drifts due to factors such as ground fault, and the cost is very low.
  • a low-cost input anti-overvoltage protection circuit including an input chopper circuit and a control circuit
  • the input end of the input chopper circuit is connected to the output end of the external EMC filter circuit, and the output end of the input chopper circuit supplies power to the subsequent stage circuit;
  • the control circuit collects the AC voltage outputted by the external EMC filter circuit in real time.
  • the output control signal Vg controls the input chopper circuit to be disconnected.
  • the storage capacitor in the chopper circuit is input. The voltage will not continue to rise, and the storage capacitor will supply power to the subsequent stage circuit;
  • the output control signal Vg controls the input chopper circuit to conduct, charges the storage capacitor, maintains the voltage of the storage capacitor, and the storage capacitor supplies power to the subsequent circuit.
  • the input chopper circuit comprises a capacitor C801, a rectifier bridge DB801, a capacitor C802, a switching device and a storage capacitor; the capacitor C801 is used as an input end of the input chopper circuit, and the capacitor C802 is connected in parallel to the energy storage. Both ends of the capacitor; both ends of the storage capacitor supply power to the rear stage circuit;
  • connection relationship between the switching device and the rectifier bridge DB801 is one of the following four ways:
  • the first input end and the second input end of the rectifier bridge DB801 are respectively connected to two ends of the capacitor C801, and the anode of the rectifier bridge DB801 is connected to the anode of the storage capacitor; the switching device is connected to the cathode and the storage capacitor of the rectifier bridge DB801. Between the negative poles, the control end of the switching device is connected to the control signal Vg;
  • the first input end and the second input end of the rectifier bridge DB801 are respectively connected to two ends of the capacitor C801, and the negative pole of the rectifier bridge DB801 is connected to the negative pole of the storage capacitor; the switching device is connected to the positive pole and the storage capacitor of the rectifier bridge DB801 Between the positive poles, the control terminal of the switching device is connected to the control signal Vg;
  • the switching device is connected between one end of the capacitor C801 and the first input end of the rectifier bridge DB801, the second input end of the rectifier bridge DB801 is connected to the other end of the capacitor C801, and the positive pole and the negative pole of the rectifier bridge DB801 are respectively connected to the positive pole of the storage capacitor and a negative electrode; the control terminal of the switching device is connected to the control signal Vg;
  • the switching device is connected between the other end of the capacitor C801 and the second input end of the rectifier bridge DB801.
  • the first input end of the rectifier bridge DB801 is connected to one end of the capacitor C801, and the positive pole and the negative pole of the rectifier bridge DB801 are respectively connected to the positive pole of the storage capacitor and a negative electrode;
  • the control terminal of the switching device is connected to the control signal Vg;
  • the AC signals at both ends of the capacitor C801 are Vac_L and Vac_N, respectively, and Vac_L and Vac_N are transmitted to the control circuit for processing; the negative pole of the rectifier bridge DB801 outputs the Vs signal, as the signal ground of the control circuit, and the positive output Vc signal of the storage capacitor
  • the control circuit outputs a control signal Vg connected to the control terminal of the switching device to control the opening and closing of the switching device.
  • the switching device comprises an N-channel MOS transistor TR808 and a varistor RV803, and the varistor RV803 is connected in parallel between the source and the drain of the N-channel MOS transistor TR808, and the N-channel
  • the source of the MOS transistor TR808 is connected to the cathode of the rectifier bridge DB801
  • the drain of the N-channel MOS transistor TR808 is connected to the cathode of the storage capacitor
  • the gate of the N-channel MOS transistor TR808 is used as the control terminal of the switching device.
  • the switching device comprises a P-channel MOS transistor TR809 and a varistor RV803, and both ends of the varistor RV803 are connected in parallel between the source and the drain of the P-channel MOS transistor TR809, and the P-type trench
  • the source of the MOS transistor TR809 is connected to the anode of the rectifier bridge DB801
  • the drain of the P-channel MOS transistor TR809 is connected to the anode of the storage capacitor
  • the gate of the P-channel MOS transistor TR809 is used as the control terminal of the switching device.
  • the switching device comprises a relay TR810 and a varistor RV803.
  • the first control end of the relay TR810 serves as a control end of the switching device, and the second control end of the relay TR810 and the first switching end are connected to the rectifier bridge.
  • the second switch end of the relay TR810 is connected to the negative pole of the storage capacitor; the two ends of the varistor RV803 are respectively connected to the first switch end and the second switch end of the relay TR810.
  • the switching device comprises a relay TR810 and a varistor RV803, the first control end of the relay TR810 is used as a control end of the switching device, and the second control end of the relay TR810 is connected to the negative pole of the rectifier bridge DB801.
  • the first switch end of the relay TR810 is connected to the positive pole of the rectifier bridge DB801
  • the second switch end of the relay TR810 is connected to the positive pole of the storage capacitor
  • the two ends of the varistor RV803 are respectively connected to the first switch end and the second of the relay TR810 Switch end.
  • the switching device comprises a relay TR810, the first control end of the relay TR810 is used as a control end of the switching device, the second control end of the relay TR810 is connected to the negative pole of the rectifier bridge DB801, and the relay TR810 is A switch terminal is connected to the AC signal Vac_L, and a second switch terminal of the relay TR810 is connected to the first input terminal of the rectifier bridge DB801.
  • the switching device comprises a relay TR810, the first control end of the relay TR810 is used as a control end of the switching device, the second control end of the relay TR810 is connected to the negative pole of the rectifier bridge DB801, and the relay TR810 is A switch terminal is connected to the AC signal Vac_N, and a second switch terminal of the relay TR810 is connected to the second input terminal of the rectifier bridge DB801.
  • the control circuit comprises an input voltage detection and return circuit, a stable power supply circuit, a control chip U801, a Zener diode D806, a Zener diode D807, a capacitor C811 and a resistor R807;
  • the input voltage detection and The return circuit includes a resistor R808, a resistor R809, a resistor R812, a resistor R813, a resistor R814, a transistor Q801, a Zener diode D808, and a capacitor C812.
  • the stable power supply circuit includes a resistor R802, a resistor R803, a resistor R806, a diode D805, and a capacitor. C810;
  • the Vc signal is connected to the anode of the diode D805, and the negative pole of the diode D805 is connected in series with the resistor R802 and the capacitor C810, and then connected to the signal ground of the control circuit; one end of the resistor R803 is connected to the series node of the resistor R802 and the capacitor C810, and the other end of the resistor R803 is connected.
  • the positive pole of the Zener diode D806 is connected to the signal ground of the control circuit.
  • the resistor R806 is connected between the cathode and the anode of the Zener diode D806.
  • the sampling terminal of the control chip U801 is connected.
  • One end of the capacitor C811 and the cathode of the Zener diode D807, the ground terminal of the control chip U801, the other end of the capacitor C811 and the anode of the Zener diode D807 are connected to the signal ground of the control circuit; one end of the resistor R807 is connected to the output end of the control chip U801.
  • the other end of the resistor R807 is connected to the cathode of the Zener diode D808; one end of the resistor R808 and one end of the resistor R809 are respectively connected to the AC signals Vzc_N and Vac_L of the two input ends of the rectifier bridge DB801; the other end of the resistor R808 and the other end of the resistor R809 One end of the resistor R813 and one end of the resistor R812 are simultaneously connected to the cathode of the Zener diode D807.
  • the other end of the resistor R812 is connected to the signal ground of the control circuit, the other end of the resistor R813 is connected to the collector of the transistor Q801; the emitter of the transistor Q801 is connected to the signal ground of the control circuit, and the base of the transistor Q801 is connected to one end of the resistor R814 and the capacitor C812 respectively.
  • One end and the anode of the Zener diode D808; the other end of the resistor R814 and the other end of the capacitor C812 are connected to the signal ground of the control circuit.
  • control chip U801 is replaced by a sampling comparison circuit comprising an operational amplifier U1, a transistor Q1, a diode D1 and a constant voltage source VREF; the non-inverting input terminal of the operational amplifier U1 is connected to one end of the capacitor C811
  • the inverting input terminal of the operational amplifier U1 is connected to the positive terminal of the constant voltage source VREF, the negative power terminal of the operational amplifier U1 and the negative terminal of the constant voltage source VREF are connected to the signal ground of the control circuit, and the positive power terminal of the operational amplifier U1 outputs the control signal.
  • the output terminal of the operational amplifier U1 is connected to the base of the transistor Q1
  • the emitter of the transistor Q1 is connected to the negative power terminal of the operational amplifier U1 and the anode of the diode D1
  • the collector of the transistor Q1 is connected to the cathode of the diode D1 and the positive of the operational amplifier U1. Power terminal.
  • the present invention has the following beneficial effects:
  • the present invention solves the problem that the existing ground fault causes damage to the switching power supply
  • the control circuit of the invention has a stable power supply circuit and does not require an additional power supply
  • the circuit of the invention is simple and reliable, and the cost is low;
  • the invention has a unique EMC optimized circuit and superior EMC performance.
  • FIG. 1 is a block diagram of an application of an input anti-overvoltage protection circuit of the present invention
  • FIG. 2 is a schematic diagram of an input anti-overvoltage protection circuit according to a first embodiment of the present invention (input chopping portion);
  • FIG. 3 is a schematic diagram (control circuit portion) of an input anti-overvoltage protection circuit according to a first embodiment of the present invention
  • FIG. 4 is a schematic diagram of an input chopper circuit according to a second embodiment of the present invention.
  • FIG. 5 is a schematic diagram 1 of an input chopper circuit according to a third embodiment of the present invention.
  • FIG. 6 is a schematic diagram 2 of an input chopper circuit according to a third embodiment of the present invention.
  • FIG. 7 is a schematic diagram 3 of an input chopper circuit according to a third embodiment of the present invention.
  • FIG. 8 is a schematic diagram 4 of an input chopper circuit according to a third embodiment of the present invention.
  • Figure 9 is a schematic diagram of a comparison circuit employed in a fourth embodiment of the present invention.
  • a low-cost input anti-overvoltage protection circuit includes an input chopper circuit and a control circuit.
  • the block diagram of the connection between these two parts of the circuit and the external circuit in the application is shown in Figure 1.
  • FIG. 2 is a schematic diagram of an input chopper circuit according to a first embodiment of the present invention, including: a capacitor C801, a rectifier bridge DB801, a capacitor C802, a varistor RV803, an N-channel MOS transistor TR808, and a storage capacitor C805.
  • the capacitors C801 and C802 select the safety capacitor, and the Vds of the N-channel MOS transistor TR808 is recommended to be 650V or more.
  • the safety capacitor C801 is connected at both ends to the front end of the EMC filter circuit L and N terminals, and is respectively connected to the two AC input terminals of the rectifier bridge DB801: the first input terminal and the second input terminal, the MOS transistor TR808 source (S Connected to the negative pole of rectifier bridge DB801, the drain (D) of TR808 is connected to the negative pole of storage capacitor C805, and is connected to one end of RV803 and C802. The other end of varistor RV803 is connected to the source (S) of MOS transistor TR808.
  • the other end of the gauge capacitor C802 is connected to the positive terminal of the storage capacitor C805 and the positive terminal of the rectifier DB801, and the gate of the TR808 is connected to the control signal Vg at the output of the control circuit. Both ends of the storage capacitor C805 supply power to the rear stage circuit.
  • Safety capacitor C801 and varistor RV803 can improve the reliability and EMC performance of the input chopper circuit.
  • the safety capacitor C801 generally selects 0.1uF X capacitor. The function is: when the TR808 is quickly turned off, the EMC filter is filtered. The inductive inrush current of the circuit and the front-end grid prevents the rectifier bridge DB801 and the MOS transistor TR808 from being damaged.
  • the varistor RV803 can choose 470V varistor, its function is: when the surge or high voltage interference, MOS tube TR808 will be turned off, then the TR808 source ( The voltage between S) and drain (D) is too high, and the voltage-sensitive RV803 can prevent the MOS transistor TR808 from being damaged by the surge shock and improve the lightning surge resistance of the circuit.
  • FIG. 3 is a schematic diagram of a control circuit according to a first embodiment of the present invention, wherein a broken line frame A is an input voltage detecting and returning part circuit, and a broken line frame B is a stable power supply circuit, and the control circuit includes: an input voltage detecting and returning circuit, and a stable Power supply circuit, control chip U801, voltage regulator diodes D806 and D807, capacitor C811 and resistor R807.
  • the input voltage detection and hysteresis circuit includes resistors R808, R809, R812, R813, R814, transistor Q801, Zener diode D808 and capacitor C812;
  • the stable power supply circuit includes resistors R802, R803, R806, diode D805, and capacitor C810.
  • the input chopping part circuit has five places connected to the control circuit, as shown in Fig. 2 and Fig. 3, wherein Vac_L and Vac_N are AC signals of the two input ends of the collecting rectifier bridge DB801, and are transmitted to the control circuit for processing.
  • the negative pole of the rectifier bridge DB801 outputs a Vs signal, and as a signal ground of the control circuit, the positive pole of the rectifier bridge DB801 outputs a Vc signal to supply power to the control circuit.
  • the control chip U810 in the control circuit outputs a control signal Vg to the gate of the TR808 to control the turn-on and turn-off of the TR808.
  • the Vc signal is connected to the anode of the diode D805, and the negative pole of the D805 is sequentially connected in series with the resistor R802 and the capacitor C810 to the signal ground of the control circuit; one end of the R803 is connected to the series node of the R802 and the C810, and the other end of the R803 is connected to the control chip U801.
  • the output terminal and the negative pole of D806, the positive pole of D806 is connected to the signal ground of the control circuit; the resistor R806 is connected between the cathode and the anode of D806; the sampling end of U801 is connected with one end of capacitor C811 and the cathode of D807, the grounding end of U801, C811 The other end and the anode of D807 are connected to the signal ground of the control circuit; one end of the resistor R807 is connected to the output end of the U801, the other end of the R807 is connected to the cathode of the D808; one end of the R808 and one end of the R809 are respectively connected to the two input ends of the rectifier bridge DB801.
  • the other end of the AC signal Vzc_N and Vac_L, R808 is connected to the other end of R809 and then connected to the cathode of D807; one end of R813 is connected to one end of R812 and then connected to the cathode of D807, the other end of R812 is connected to the signal ground of the control circuit, and the other end of R813 One end is connected to the collector of Q801; the emitter of Q801 is connected to the signal ground of the control circuit, and the base of Q801 is connected to one end of the resistor R814 and the capacitor C81 One end of 2 and the anode of D808; the other end of R814 and the other end of capacitor C812 are connected to the signal ground of the control circuit.
  • the working principle of the control circuit the input voltage detection and hysteresis circuit steps down the input AC signal and sends it to the U801 sampling end.
  • the U801 is a 2.5V TL431.
  • the U801 sampling terminal voltage is higher than 2.5V, Vg.
  • the Q801 changes from on to off, which further causes the voltage of the U801 sampling terminal to rise, which causes Vg to rapidly drop and increase the turn-off speed of the MOS transistor TR808.
  • the hysteresis circuit can also reduce the damage of the MOS transistor.
  • the input voltage detection and hysteresis circuit is shown in broken line A in Figure 3.
  • R808, R809, R812, R13 form a voltage dividing circuit, which can adjust the threshold voltage of the overvoltage protection by setting its resistance value. Among them, changing R813 and R812 can also adjust the hysteresis voltage.
  • the voltage regulator D808 can increase the turn-off speed of the MOS transistor, generally taking 9.1V.
  • the NPN transistor Q801 and the resistor R813R812 form a hysteresis circuit.
  • R814 and C812 are used to filter Q801, and C811 is used to filter the U801 sampling end to prevent interference.
  • the Zener diode D807 is generally taken at 5.1V to prevent surges or interference pulses from damaging the U801.
  • the stable power supply circuit is shown in the broken line frame B in FIG. Diode D805, resistor R802 and high-voltage film capacitor C810, rectify and filter the high-voltage oscillation after the rectifier bridge, and store the energy in the capacitor C810, and then obtain a stable supply voltage through the current limiting resistor R803 and the voltage regulator D806.
  • the voltage regulator D806 takes about 15V, and the R803 is about 500K ⁇ . Reducing the R803 resistance value can increase the MOS tube switching speed and reduce the MOS tube loss heat, but it will increase the loss of the control circuit.
  • R806 is a bleeder resistor. When standby, the control circuit energy is discharged, preventing the MOS tube from being turned on before power-on. The R806 can be adjusted according to environmental interference.
  • the added devices are MOS transistor TR808, X capacitor C801, varistor RV803 and the whole control circuit. Except for MOS tube TR808, the cost of other devices is not high, the total does not exceed 2 yuan, MOS tube TR808 selection needs to be based on the specific situation, generally less than 100W switching power supply can be selected within 2.5 yuan MOS tube, so the cost is lower. Therefore, the circuit of the present invention has extremely high product practical and commercial value.
  • the MOS transistor TR808 When the grid voltage is normal, the MOS transistor TR808 is always in the on state, the on-resistance is small, the heat generation is small, and the control circuit loss is also small (can be less than 0.1W), and the efficiency of the switching power supply is hardly affected.
  • the grid voltage abnormally rises to 2 times, the MOS transistor TR808 is in the switching state, and the heat generation is increased. It is necessary to select a suitable MOS tube according to the power consumption.
  • FIG. 4 is a schematic diagram of an input chopper circuit according to a second embodiment of the present invention.
  • the N-channel MOS transistor TR808 is changed to a P-channel MOS transistor TR809, and the connection relationship is adjusted.
  • the gate of the TR809 is connected to the control signal Vg output from the control circuit
  • the source of the TR809 is connected to the anode of the rectifier bridge DB801
  • the drain of the TR809 is connected to the anode of the storage capacitor C805.
  • Both ends of the RV803 are connected in parallel between the source and the drain of the TR809.
  • the connection relationship of other components remains unchanged.
  • the control circuit performs appropriate adjustment and isolation processing.
  • the operating principle of the adjusted circuit is the same as that of the first embodiment, and the same effect can be achieved.
  • FIG. 8 are schematic diagrams showing an input chopper circuit according to a third embodiment of the present invention. Unlike the first embodiment, the MOS transistor TR808 is changed to the relay TR810, and the connection manner of the relay is one of the following four types:
  • the first type the first control end of the relay is connected to the control signal Vg outputted by the control circuit, the second control end of the relay is connected to the signal ground of the control circuit, the first switch end of the relay is connected to the negative pole of the rectifier bridge DB801, and the second switch of the relay The end is connected to the negative pole of the storage capacitor C805; the two ends of the RV803 are respectively connected to the first switch end and the second switch end of the relay.
  • the second type the first control end of the relay is connected to the control signal Vg outputted by the control circuit, the second control end of the relay is connected to the signal ground of the control circuit, the first switch end of the relay is connected to the positive pole of the rectifier bridge DB801, and the second switch of the relay The end is connected to the positive pole of the storage capacitor C805; the two ends of the RV803 are respectively connected to the first switch end and the second switch end of the relay.
  • the third type the first control end of the relay is connected to the control signal Vg outputted by the control circuit, the second control end of the relay is connected to the signal ground of the control circuit, and the first switch end of the relay is connected to the N end of the EMC filter circuit of the front end, and the relay The second switch end is connected to the second input end of the rectifier bridge DB801.
  • the fourth type the first control end of the relay is connected to the control signal Vg outputted by the control circuit, the second control end of the relay is connected to the signal ground of the control circuit, and the first switch end of the relay is connected to the L end of the EMC filter circuit of the front end, and the relay The second switch end is connected to the first input end of the rectifier bridge DB801.
  • the working principle of the adjusted circuit is the same as that of the first embodiment.
  • the purpose is to disconnect the switching device in the input chopper circuit when the input AC voltage is greater than the set threshold, and stop charging the storage capacitor. Can achieve the same effect.
  • the chip U801 (TL431) is replaced by a sampling comparison circuit composed of an operational amplifier U1, a transistor Q1, a diode D1, and a constant voltage source VREF, as shown in FIG.
  • the non-inverting input terminal of U1 is connected to one end of capacitor C811, the inverting input terminal of U1 is connected to the positive terminal of constant voltage source VREF, the negative power terminal of U1 and the negative terminal of constant voltage source VREF are connected to the signal ground of control circuit, and the positive power source of U1
  • the output terminal of the terminal output control signal Vg, U1 is connected to the base of the transistor Q1, the emitter of the transistor Q1 is connected to the negative power terminal of the operational amplifier U1 and the anode of the diode D1, and the collector of the transistor Q1 is connected to the cathode of the diode D1 and the operational amplifier U1. Positive power supply.
  • the working principle of the adjusted circuit is the same as that of the above embodiment, and the same effect can be achieved.

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Abstract

一种低成本输入抗过压保护电路，能实时监控交流输入电压大小，并通过控制电路控制斩波电路中开关器件通断。当交流输入电压异常升高时，控制电路能迅速检测并控制斩波电路中开关器件处于开关状态，维持储能电容电压不过高，从而快速有效地保护后级电路，防止后级电路中储能电容和开关管因电压过高而损坏，且后级电路能持续正常工作。相对于现有技术，所述低成本输入抗过压保护电路，适用于可能出现接地故障等导致电网电压异常过压的情况和场合，反应速度快，电路简单可靠，成本低，EMC性能优越，设计灵活，可调节保护阈值。

Description

一种低成本输入抗过压保护电路 技术领域
本发明涉及电路领域，具体的，涉及一种用于三相四线和馈电网自动化电源系统中的输入抗过压保护电路。
背景技术
在三相四线电力电表和馈电网自动化行业开关电源中，常常会遇到接地故障和大功率设备干扰等问题，导致一段时间内电网电压异常偏高，此时电网电压会超过开关电源所能承受的电压上限，极易造成开关电源损坏甚至起火，存在巨大安全隐患。
现有开关电源解决电网电压偏高问题的方法归纳起来主要有两种，一种是增加输入过压保护电路，另一种是提高电源所能承受的工作电压范围上限。其中，增加输入电压上限，主要是采用高耐压器件或多级串并联方式，优点是过压时电路仍能正常工作，缺点是电路成本和体积增加，输入电压上限每提高一倍，储能电容成本约上升四倍，开关管成本约上升两倍以上，且过压工作时间很短，这种方法存在严重过设计，很浪费资源；另一种方法是增加输入过压保护电路，当检测到电网电压过高时，使控制芯片停止工作，这种方式只能用于过压较小的情况，而当电网电压偏高到原来的1.5倍以上时，整流后电压已超过大电容耐压甚至开关管耐压，其本质上只是过压时停止工作，并不能保护后级电路。
在三相四线电力电表和馈电网自动化行业，如今市面上只有少数开关电源具有抗接地故障和输入过压保护功能，过压时电解电容和开关管往往都是超规格硬抗，存在巨大安全隐患。因此，有必要对现有技术进行改进，设计一种在电网电压异常偏高到原来两倍时，也能安全可靠保护后级电路持续正常工作的低成本抗过压保护电路。
发明内容
有鉴于此，为了解决上述技术问题，本发明提供一种通过斩波方式实现的新型输入过压保护电路。输入电压一般都是交流正弦信号，电压绝对值在一个周期内会从最小值变化到最大值，斩波电路能在输入交流电压绝对值较高时，将后级电路和储能大电容断开，将后级电路维持在一定电压以下，过压时后级电路能正 常工作。此电路可以在接地故障等因素导致电压漂高时有效保护开关电源，且成本非常低。
本发明的目的是通过下述技术方案实现的，一种低成本输入抗过压保护电路，包括输入斩波电路和控制电路两部分电路；
输入斩波电路的输入端连接外部EMC滤波电路的输出端，输入斩波电路的输出端为后级电路供电；
控制电路实时采集外部的EMC滤波电路输出的交流电压，当交流电压绝对值大于设定阀值时，输出控制信号Vg控制输入斩波电路断开，此时输入斩波电路中的储能电容上的电压不会再继续上升，由储能电容为后级电路供电；
当交流电压绝对值低于设定阀值时，输出控制信号Vg控制输入斩波电路导通，为储能电容充电，维持储能电容的电压，同样由储能电容为后级电路供电。
优选的，所述的输入斩波电路，包括电容C801、整流桥DB801、电容C802、开关器件和储能电容；所述电容C801两端作为输入斩波电路的输入端，电容C802并联在储能电容的两端；储能电容的两端为后级电路供电；
所述的开关器件与整流桥DB801的连接关系为以下四种方式之一：
整流桥DB801的第一输入端和第二输入端分别连接到电容C801的两端，整流桥DB801的正极连接储能电容的正极；所述的开关器件连接在整流桥DB801的负极和储能电容的负极之间，所述开关器件的控制端连接控制信号Vg；
整流桥DB801的第一输入端和第二输入端分别连接到电容C801的两端，整流桥DB801的负极连接储能电容的负极；所述的开关器件连接在整流桥DB801的正极和储能电容的正极之间，所述开关器件的控制端连接控制信号Vg；
开关器件连接在电容C801的一端和整流桥DB801的第一输入端之间，整流桥DB801的第二输入端连接电容C801的另一端，整流桥DB801的正极和负极分别连接储能电容的正极和负极；所述开关器件的控制端连接控制信号Vg；
开关器件连接在电容C801的另一端和整流桥DB801的第二输入端之间，整流桥DB801的第一输入端连接电容C801的一端，整流桥DB801的正极和负极分别连接储能电容的正极和负极；所述开关器件的控制端连接控制信号Vg；
所述的电容C801两端的交流信号分别为Vac_L和Vac_N，将Vac_L和Vac_N传输给控制电路进行处理；整流桥DB801的负极输出Vs信号，作为控制电路的 信号地，储能电容的正极输出Vc信号，为控制电路供电；控制电路输出控制信号Vg连接到开关器件的控制端，控制开关器件的开通和关断。
优选的，所述的开关器件包括N型沟道MOS管TR808和压敏电阻RV803，所述压敏电阻RV803并联在N型沟道MOS管TR808的源极和漏极之间，N型沟道MOS管TR808的源极连接整流桥DB801的负极，N型沟道MOS管TR808的漏极连接储能电容的负极，N型沟道MOS管TR808的栅极作为开关器件的控制端。
优选的，所述的开关器件包括P型沟道MOS管TR809和压敏电阻RV803，压敏电阻RV803的两端并联在P型沟道MOS管TR809的源极和漏极之间，P型沟道MOS管TR809的源极连接整流桥DB801的正极，P型沟道MOS管TR809的漏极连接储能电容的正极；P型沟道MOS管TR809的栅极作为开关器件的控制端。
优选的，所述的开关器件包括继电器TR810和压敏电阻RV803，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端和第一开关端连接整流桥DB801的负极，所述继电器TR810的第二开关端连接储能电容的负极；压敏电阻RV803的两端分别连接继电器TR810的第一开关端和第二开关端。
优选的，所述的开关器件包括继电器TR810和压敏电阻RV803，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接整流桥DB801的正极，所述继电器TR810的第二开关端连接储能电容的正极；压敏电阻RV803的两端分别连接继电器TR810的第一开关端和第二开关端。
优选的，所述的开关器件包括继电器TR810，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接交流信号Vac_L，所述继电器TR810的第二开关端连接整流桥DB801的第一输入端。
优选的，所述的开关器件包括继电器TR810，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接交流信号Vac_N，所述继电器TR810的第二开关端连接整流桥DB801的第二输入端。
优选的，所述的控制电路，包括输入电压检测和回差电路、稳定供电电路、控制芯片U801、稳压管二极管D806、稳压二极管D807、电容C811和电阻R807；所述的输入电压检测和回差电路包括电阻R808、电阻R809、电阻R812、电阻R813、电阻R814、三极管Q801、稳压二极管D808和电容C812；所述的稳定供电电路包括电阻R802、电阻R803、电阻R806、二极管D805和电容C810；
所述的Vc信号连接二极管D805的阳极，二极管D805的负极依次与电阻R802、电容C810串联后接控制电路的信号地；电阻R803的一端连接电阻R802与电容C810的串联节点，电阻R803的另一端连接控制芯片U801的输出端和稳压二极管D806的负极，稳压二极管D806的正极连接控制电路的信号地；电阻R806连接在稳压二极管D806的阴极和阳极之间；控制芯片U801的采样端连接电容C811的一端和稳压二极管D807的阴极，控制芯片U801的接地端、电容C811的另一端和稳压二极管D807的阳极共同连接控制电路的信号地；电阻R807的一端连接控制芯片U801的输出端，电阻R807的另一端连接稳压二极管D808的阴极；电阻R808的一端和电阻R809的一端分别连接整流桥DB801的两个输入端的交流信号Vzc_N与Vac_L；电阻R808的另一端、电阻R809的另一端、电阻R813的一端、电阻R812的一端同时连接稳压二极管D807的阴极，电阻R812的另一端连接控制电路的信号地，电阻R813的另一端连接三极管Q801的集电极；三极管Q801的发射极接控制电路的信号地，三极管Q801的基极分别连接电阻R814的一端、电容C812的一端和稳压二极管D808的阳极；电阻R814的另一端和电容C812的另一端连接控制电路的信号地。
优选的，用一个采样比较电路替换控制芯片U801，所述的采样比较电路包括运算放大器U1、三极管Q1、二极管D1和恒压源VREF；所述的运算放大器U1的同相输入端连接电容C811的一端，运算放大器U1的反相输入端连接恒压源VREF的正端，运算放大器U1的负电源端和恒压源VREF的负端连接控制电路的信号地，运算放大器U1的正电源端输出控制信号Vg，运算放大器U1的输出端连接三极管Q1的基极，三极管Q1的发射极连接运算放大器U1的负电源端和二极管D1的阳极，三极管Q1的集电极连接二极管D1的阴极和运算放大器U1的正电源端。
与现有技术相比，本发明具有如下有益效果：
1)本发明解决现有接地故障导致开关电源损坏的问题；
2)本发明在输入过压时，后级电路仍能正常工作；
3)本发明控制电路自带稳定供电电路，无需额外电源供电；
4)本发明电路简单可靠，成本低；
5)本发明设计灵活，过压保护阀值可调；
6)本发明拥有独特的EMC优化电路，EMC性能优越。
附图说明
图1为本发明输入抗过压保护电路的应用框图；
图2为本发明第一实施例输入抗过压保护电路原理图(输入斩波部分)；
图3为本发明第一实施例输入抗过压保护电路原理图(控制电路部分)；
图4为本发明第二实施例的输入斩波电路的原理图；
图5为本发明第三实施例的输入斩波电路的原理图一；
图6为本发明第三实施例的输入斩波电路的原理图二；
图7为本发明第三实施例的输入斩波电路的原理图三；
图8为本发明第三实施例的输入斩波电路的原理图四；
图9为本发明第四实施例中采用比较电路的原理图。
具体实施例
第一实施例
一种低成本输入抗过压保护电路，包括输入斩波电路和控制电路两部分电路。这两部分电路在应用中与外部电路的连接关系框图如图1所示。
图2为本发明第一实施例输入斩波电路的原理图，包括：电容C801、整流桥DB801、电容C802、压敏电阻RV803、N型沟道MOS管TR808和储能电容C805。
电容C801和C802选择安规电容、N型沟道MOS管TR808的Vds建议650V以上。
所述安规电容C801两端连接前端的EMC滤波电路L和N端，并分别连接到整流桥DB801的两个交流输入端：第一输入端和第二输入端，MOS管TR808源极(S)连接到整流桥DB801负极，TR808漏极(D)连接到储能电容C805负极，并与RV803和C802的一端相连，压敏电阻RV803的另一端连接MOS管TR808的源极(S)，安规电容C802另一端与储能电容C805正极和整流DB801正极相连，TR808 的栅极连接控制电路的输出端的控制信号Vg。储能电容C805的两端为后级电路供电。
安规电容C801和压敏电阻RV803能提高输入斩波电路的可靠性和EMC性能，其中，安规电容C801一般选取0.1uF的X电容，作用为：当TR808快速关断时，滤除EMC滤波电路和前端电网的感性冲击电流，防止整流桥DB801和MOS管TR808损坏。若输入电压为220Vac交流电，两倍过压为440Vac，压敏电阻RV803可选取470V的压敏电阻，其作用为：浪涌或高压干扰时，MOS管TR808会关断，此时TR808源极(S)和漏极(D)间电压过高，压敏RV803能防止MOS管TR808因浪涌冲击而损坏，提高电路抗雷击浪涌能力。
图3为本发明第一实施例控制电路的原理图，其中虚线框A是输入电压检测和回差部分电路，虚线框B是稳定供电电路，控制电路包括：输入电压检测和回差电路、稳定供电电路、控制芯片U801、稳压管二极管D806和D807、电容C811和电阻R807。
其中输入电压检测和回差电路包括电阻R808、R809、R812、R813、R814、三极管Q801、稳压二极管D808和电容C812；
其中稳定供电电路包括电阻R802、R803、R806、二极管D805和电容C810。
输入斩波部分电路共有五处与控制电路相连，如图2和图3所示，其中Vac_L和Vac_N是采集整流桥DB801的两个输入端的交流信号，并传输给控制电路进行处理。整流桥DB801的负极输出Vs信号，作为控制电路的信号地，整流桥DB801的正极输出Vc信号，为控制电路供电。控制电路中的控制芯片U810输出控制信号Vg到TR808的栅极，控制TR808的开通和关断。
所述的Vc信号连接二极管D805的阳极，D805的负极依次与电阻R802、电容C810串联后接控制电路的信号地；R803的一端连接R802与C810的串联节点，R803的另一端连接控制芯片U801的输出端和D806的负极，D806的正极连接控制电路的信号地；电阻R806连接在D806的阴极和阳极之间；U801的采样端连接电容C811的一端和D807的阴极，U801的接地端、C811的另一端和D807的阳极共同连接控制电路的信号地；电阻R807的一端连接U801的输出端，R807的另一端连接D808的阴极；R808的一端和R809的一端分别连接整流桥DB801的两个输入端的交流信号Vzc_N与Vac_L，R808的另一端连接R809的另一端后再 连接D807的阴极；R813的一端连接R812的一端后再连接D807的阴极，R812的另一端连接控制电路的信号地，R813的另一端连接Q801的集电极；Q801的发射极接控制电路的信号地，Q801的基极分别连接电阻R814的一端、电容C812的一端和D808的阳极；R814的另一端和电容C812的另一端连接控制电路的信号地。
控制电路工作原理：输入电压检测和回差电路将输入交流信号降压后给到U801采样端，U801为2.5V的TL431，当输入交流电出现过压时，U801采样端电压高于2.5V，Vg端电压降低，导致Q801从导通变为截止，进一步促使U801采样端电压上升，使Vg快速下降，提高MOS管TR808的关断速度。由于存在回差，当输入电压下降到比过压点更低的电压时，U801采样端电压低于2.5V，Vg电压慢慢上升，MOS管TR808才重新开通，由于MOS管TR808开通时输入交流电压此时绝对值比储能电容电压更低，故开通时几乎没有电流流过MOS管，故回差电路除防抖动外，还能起到降低MOS管开通损坏的作用。
输入电压检测和回差电路如图3中虚线框A所示。R808、R809、R812、R13组成分压电路，可调节其阻值设定过压保护的阀值电压，其中，改变R813和R812还可调节回差电压大小。稳压管D808可提高MOS管关断速度，一般取9.1V。NPN三极管Q801和电阻R813R812组成回差电路。R814和C812用于对Q801滤波，C811用于对U801采样端滤波，防止干扰。稳压二极管D807一般取5.1V，能防止浪涌或干扰脉冲损伤U801。
稳定供电电路如图3中虚线框B所示。二极管D805、电阻R802和高压薄膜电容C810，对整流桥后的高压跃动进行整流滤波，并将能量储存在电容C810中，再通过限流电阻R803和稳压管D806得到稳定的供电电压，其中，稳压管D806取15V左右，R803为500KΩ左右，减小R803阻值可提高MOS管开关速度降低MOS管损耗发热，但会增加控制电路的损耗。R806是泄放电阻，待机时将控制电路能量泄放完，防止上电前MOS管处于导通状态，可根据环境干扰情况调节R806大小。
成本分析：增加抗过压保护电路后，增加的器件有，MOS管TR808、X电容C801、压敏电阻RV803以及整个控制电路。除MOS管TR808外，其它器件成本都不高，合计不超过2元，MOS管TR808选型需要根据具体情况，一般100W以下 开关电源选取2.5元以内MOS管即可，故成本较低。因此，本发明电路具有极高的产品实用和商业价值。
当电网电压正常时，MOS管TR808一直处于导通状态，导通阻抗很小，发热量小，且控制电路损耗也小(可做到0.1W以内)，几乎不影响开关电源整机效率。当电网电压异常升高到原来2倍时，MOS管TR808处于开关状态，发热量有所上升，需根据功耗选取合适的MOS管。
第二实施例
图4为本发明第二实施例中输入斩波电路的原理图，与第一实施例不同的是，将N型沟道MOS管TR808改为P型沟道MOS管TR809，并调整连接关系为：TR809的栅极连接控制电路输出的控制信号Vg，TR809的源极连接整流桥DB801的正极，TR809的漏极连接储能电容C805的正极。RV803的两端并联在TR809的源极和漏极之间。其他元器件的连接关系不变。同时，控制电路进行适当调整及隔离处理。
调整后电路的工作原理与第一实施例一样，可实现同等功效。
第三实施例
图5至图8为本发明第三实施例中输入斩波电路的原理图，与第一实施例不同的是，将MOS管TR808改为继电器TR810，继电器的连接方式为以下四种之一：
第一种：继电器的第一控制端连接控制电路输出的控制信号Vg，继电器的第二控制端连接控制电路的信号地，继电器的第一开关端连接整流桥DB801的负极，继电器的第二开关端连接储能电容C805的负极；RV803的两端分别连接继电器的第一开关端和第二开关端。
第二种：继电器的第一控制端连接控制电路输出的控制信号Vg，继电器的第二控制端连接控制电路的信号地，继电器的第一开关端连接整流桥DB801的正极，继电器的第二开关端连接储能电容C805的正极；RV803的两端分别连接继电器的第一开关端和第二开关端。
第三种：继电器的第一控制端连接控制电路输出的控制信号Vg，继电器的第二控制端连接控制电路的信号地，继电器的第一开关端连接前端的EMC滤波电路的N端，继电器的第二开关端连接整流桥DB801的第二输入端。
第四种：继电器的第一控制端连接控制电路输出的控制信号Vg，继电器的第二控制端连接控制电路的信号地，继电器的第一开关端连接前端的EMC滤波电路的L端，继电器的第二开关端连接整流桥DB801的第一输入端。
调整后电路的工作原理与第一实施例一样，目的都是为了实现在输入交流电压大于设定的阀值时，断开输入斩波电路中的开关器件，停止为储能电容充电。可实现同等功效。
第四实施例
与以上任何一种实施例不同的是，将芯片U801(TL431)替换为由运算放大器U1、三极管Q1、二极管D1和恒压源VREF组成的采样比较电路，见附图9。
U1的同相输入端连接电容C811的一端，U1的反相输入端连接恒压源VREF的正端，U1的负电源端和恒压源VREF的负端连接控制电路的信号地，U1的正电源端输出控制信号Vg，U1的输出端连接三极管Q1的基极，三极管Q1的发射极连接运算放大器U1的负电源端和二极管D1的阳极，三极管Q1的集电极连接二极管D1的阴极和运算放大器U1的正电源端。
调整后电路的工作原理与以上实施例一样，可实现同等功效。
以上公开的仅为本发明的优选实施例，但是本发明并非局限于此，任何本领域的技术人员在未脱离本发明的核心思想的前提下对本发明进行的若干修饰均应该落在本发明权利要求的保护范围之类。本发明的保护范围以权利要求书的内容为准。

Claims (10)

  1. 一种低成本输入抗过压保护电路，其特征在于：包括输入斩波电路和控制电路两部分电路；
    输入斩波电路的输入端连接外部EMC滤波电路的输出端，输入斩波电路的输出端为后级电路供电；
    控制电路实时采集外部的EMC滤波电路输出的交流电压，当交流电压绝对值大于设定阀值时，输出控制信号Vg控制输入斩波电路断开，此时输入斩波电路中的储能电容上的电压不会再继续上升，由储能电容为后级电路供电；
    当交流电压绝对值低于设定阀值时，输出控制信号Vg控制输入斩波电路导通，为储能电容充电，维持储能电容的电压，同样由储能电容为后级电路供电。
  2. 根据权利要求1所述的低成本输入抗过压保护电路，其特征在于：所述的输入斩波电路，包括电容C801、整流桥DB801、电容C802、开关器件和储能电容；所述电容C801两端作为输入斩波电路的输入端，电容C802并联在储能电容的两端；储能电容的两端为后级电路供电；
    所述的开关器件与整流桥DB801的连接关系为以下四种方式之一：
    整流桥DB801的第一输入端和第二输入端分别连接到电容C801的两端，整流桥DB801的正极连接储能电容的正极；所述的开关器件连接在整流桥DB801的负极和储能电容的负极之间，所述开关器件的控制端连接控制信号Vg；
    整流桥DB801的第一输入端和第二输入端分别连接到电容C801的两端，整流桥DB801的负极连接储能电容的负极；所述的开关器件连接在整流桥DB801的正极和储能电容的正极之间，所述开关器件的控制端连接控制信号Vg；
    开关器件连接在电容C801的一端和整流桥DB801的第一输入端之间，整流桥DB801的第二输入端连接电容C801的另一端，整流桥DB801的正极和负极分别连接储能电容的正极和负极；所述开关器件的控制端连接控制信号Vg；
    开关器件连接在电容C801的另一端和整流桥DB801的第二输入端之间，整流桥DB801的第一输入端连接电容C801的一端，整流桥DB801的正极和负极分别连接储能电容的正极和负极；所述开关器件的控制端连接控制信号Vg；
    所述的电容C801两端的交流信号分别为Vac_L和Vac_N，将Vac_L和Vac_N传输给控制电路进行处理；整流桥DB801的负极输出Vs信号，作为控制电路的 信号地，储能电容的正极输出Vc信号，为控制电路供电；控制电路输出控制信号Vg连接到开关器件的控制端，控制开关器件的开通和关断。
  3. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括N型沟道MOS管TR808和压敏电阻RV803，所述压敏电阻RV803并联在N型沟道MOS管TR808的源极和漏极之间，N型沟道MOS管TR808的源极连接整流桥DB801的负极，N型沟道MOS管TR808的漏极连接储能电容的负极，N型沟道MOS管TR808的栅极作为开关器件的控制端。
  4. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括P型沟道MOS管TR809和压敏电阻RV803，压敏电阻RV803的两端并联在P型沟道MOS管TR809的源极和漏极之间，P型沟道MOS管TR809的源极连接整流桥DB801的正极，P型沟道MOS管TR809的漏极连接储能电容的正极；P型沟道MOS管TR809的栅极作为开关器件的控制端。
  5. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括继电器TR810和压敏电阻RV803，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端和第一开关端连接整流桥DB801的负极，所述继电器TR810的第二开关端连接储能电容的负极；压敏电阻RV803的两端分别连接继电器TR810的第一开关端和第二开关端。
  6. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括继电器TR810和压敏电阻RV803，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接整流桥DB801的正极，所述继电器TR810的第二开关端连接储能电容的正极；压敏电阻RV803的两端分别连接继电器TR810的第一开关端和第二开关端。
  7. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括继电器TR810，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接交流信号Vac_L，所述继电器TR810的第二开关端连接整流桥DB801的第一输入端。
  8. 根据权利要求2所述的低成本输入抗过压保护电路，其特征在于：所述的开关器件包括继电器TR810，所述继电器TR810的第一控制端作为开关器件的控制端，所述继电器TR810的第二控制端连接整流桥DB801的负极，所述继电器TR810的第一开关端连接交流信号Vac_N，所述继电器TR810的第二开关端连接整流桥DB801的第二输入端。
  9. 根据权利要求3至8任意一项所述的低成本输入抗过压保护电路，其特征在于：所述的控制电路，包括输入电压检测和回差电路、稳定供电电路、控制芯片U801、稳压管二极管D806、稳压二极管D807、电容C811和电阻R807；所述的输入电压检测和回差电路包括电阻R808、电阻R809、电阻R812、电阻R813、电阻R814、三极管Q801、稳压二极管D808和电容C812；所述的稳定供电电路包括电阻R802、电阻R803、电阻R806、二极管D805和电容C810；
    所述的Vc信号连接二极管D805的阳极，二极管D805的负极依次与电阻R802、电容C810串联后接控制电路的信号地；电阻R803的一端连接电阻R802与电容C810的串联节点，电阻R803的另一端连接控制芯片U801的输出端和稳压二极管D806的负极，稳压二极管D806的正极连接控制电路的信号地；电阻R806连接在稳压二极管D806的阴极和阳极之间；控制芯片U801的采样端连接电容C811的一端和稳压二极管D807的阴极，控制芯片U801的接地端、电容C811的另一端和稳压二极管D807的阳极共同连接控制电路的信号地；电阻R807的一端连接控制芯片U801的输出端，电阻R807的另一端连接稳压二极管D808的阴极；电阻R808的一端和电阻R809的一端分别连接整流桥DB801的两个输入端的交流信号Vzc_N与Vac_L；电阻R808的另一端、电阻R809的另一端、电阻R813的一端、电阻R812的一端同时连接稳压二极管D807的阴极，电阻R812的另一端连接控制电路的信号地，电阻R813的另一端连接三极管Q801的集电极；三极管Q801的发射极接控制电路的信号地，三极管Q801的基极分别连接电阻R814的一端、电容C812的一端和稳压二极管D808的阳极；电阻R814的另一端和电容C812的另一端连接控制电路的信号地。
  10. 根据权利要求9所述的低成本输入抗过压保护电路，其特征在于：用一个采样比较电路替换控制芯片U801，所述的采样比较电路包括运算放大器U1、三极管Q1、二极管D1和恒压源V REF；所述的运算放大器U1的同相输入端连接电 容C811的一端，运算放大器U1的反相输入端连接恒压源V REF的正端，运算放大器U1的负电源端和恒压源V REF的负端连接控制电路的信号地，运算放大器U1的正电源端输出控制信号Vg，运算放大器U1的输出端连接三极管Q1的基极，三极管Q1的发射极连接运算放大器U1的负电源端和二极管D1的阳极，三极管Q1的集电极连接二极管D1的阴极和运算放大器U1的正电源端。
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