WO2018226864A1 - Système et procédé de réception d'énergie sans fil - Google Patents

Système et procédé de réception d'énergie sans fil Download PDF

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Publication number
WO2018226864A1
WO2018226864A1 PCT/US2018/036310 US2018036310W WO2018226864A1 WO 2018226864 A1 WO2018226864 A1 WO 2018226864A1 US 2018036310 W US2018036310 W US 2018036310W WO 2018226864 A1 WO2018226864 A1 WO 2018226864A1
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WO
WIPO (PCT)
Prior art keywords
power
impedance
network
input
control
Prior art date
Application number
PCT/US2018/036310
Other languages
English (en)
Inventor
Christopher Joseph DAVLANTES
Original Assignee
Supply, Inc.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Supply, Inc. filed Critical Supply, Inc.
Publication of WO2018226864A1 publication Critical patent/WO2018226864A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B5/00—Near-field transmission systems, e.g. inductive or capacitive transmission systems
    • H04B5/70—Near-field transmission systems, e.g. inductive or capacitive transmission systems specially adapted for specific purposes
    • H04B5/79—Near-field transmission systems, e.g. inductive or capacitive transmission systems specially adapted for specific purposes for data transfer in combination with power transfer
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F38/00—Adaptations of transformers or inductances for specific applications or functions
    • H01F38/14—Inductive couplings
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/20—Circuit arrangements or systems for wireless supply or distribution of electric power using microwaves or radio frequency waves
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H02J50/80—Circuit arrangements or systems for wireless supply or distribution of electric power involving the exchange of data, concerning supply or distribution of electric power, between transmitting devices and receiving devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
    • H02J7/00032—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries characterised by data exchange
    • H02J7/00034—Charger exchanging data with an electronic device, i.e. telephone, whose internal battery is under charge

Definitions

  • FIGURES 1A-1B are schematic representations of a first and second embodiment, respectively, of the system.
  • FIGURE 2 is a schematic view of a first example of an antenna.
  • FIGURE 3A is a perspective view of a second example of an antenna.
  • FIGURE 3B is a plan view of a cross resonator of the second example of the antenna.
  • FIGURES 5A-5B are schematic representations of an embodiment and a specific example, respectively, of the dynamic impedance match.
  • FIGURES 6A-6B are schematic representations of an embodiment and a specific example, respectively, of the RF-DC converter.
  • FIGURES 7A-7B are schematic representations of an embodiment and a specific example, respectively, of the DC impedance converter.
  • FIGURE 8 is a flowchart representation of an embodiment of the method.
  • FIGURES 9A-9D are schematic representations of various specific examples of the dynamic impedance match.
  • a system 100 for wireless power reception preferably includes one or more antennas 110, dynamic impedance matches 120, RF-DC converters 130, DC impedance converters 140, and/or DC power outputs 150 (e.g., as shown in FIGURE lA).
  • the system 100 e.g., wireless power receiver such as an RF power receiver
  • the system 100 can additionally or alternatively include any other suitable elements in any suitable arrangement.
  • the antenna 110 preferably functions to receive power (e.g., electromagnetic radiation transmitted toward the system 100, preferably propagating or "far-field” radiation but additionally or alternatively evanescent or “near-field” radiation) and to couple the received power into the system 100.
  • the antenna 110 preferably includes a tightly-coupled array of resonators 111 (e.g., as shown in FIGURE 3A), but can additionally or alternatively include a loosely-coupled array, a sparse array, a single resonator 111, and/or any other suitable antenna elements.
  • the resonators 111 preferably have a high quality factor, which can increase power reception for a given resonator size or footprint.
  • the resonators 111 preferably have a large conductor thickness and a low dielectric loss tangent.
  • Each resonator in preferably outputs power through a tap (e.g., conductive pin or via) at or near a current anti-node and/ or through a coupled circuit.
  • the resonators in can include resonant loops (e.g., as shown in FIGURE 2), cross-resonators (e.g., as shown in FIGURE 3B), split-ring resonators (e.g., as shown in FIGURE 3C), electro-inductive-capacitive resonators (e.g., as shown in FIGURES 4A-4D), other physically small resonators (e.g., small relative to their resonance wavelength), and/or any other suitable resonators.
  • the resonators can be otherwise configured.
  • the antenna 110 can optionally include multiple arrays (and/or other resonator arrangements) arranged with different orientations, which can function to efficiently couple to radiation of different polarizations (e.g., orthogonal polarizations).
  • the antenna 110 includes parallel resonator layers (e.g., parallel resonator arrays), each layer having a different in-plane resonator orientation (e.g., orthogonal orientations, oriented at oblique angles, etc.).
  • the antenna 110 includes resonators on non-parallel planes (e.g., orthogonal planes, planes oriented at oblique angles, etc.).
  • the antenna 110 can additionally or alternatively include any other suitable resonators 111 and/or other antenna elements, and can have any other suitable arrangement.
  • the antenna 110 can be a metamaterial or have any other suitable configuration.
  • the antennas of the transmitter (e.g., active antennas, passive antennas, etc.) and/or receiver can optionally include one or more supergaining antennas, supergaining arrays, arrays of supergaining antennas, and/or any other suitable structures capable or and/or configured to exhibit supergaining behavior.
  • the structures can exhibit an aperture efficiency, defined as A e /A, of 2-100 (e.g., 6.5-10, 10- 15, 15-22, 22-35, less than 6.5, greater than 25, etc.) and a quality factor of 100- 5,000,000 (e.g., 500-5000, 5000-50,000, 50,000-750,000, less than 500, greater than 750,000, etc.).
  • a e /A aperture efficiency
  • 2-100 e.g., 6.5-10, 10- 15, 15-22, 22-35, less than 6.5, greater than 25, etc.
  • a quality factor of 100- 5,000,000 e.g., 500-5000, 5000-50,000, 50,000-750,000, less than 500, greater than 750,000, etc.
  • the structures can exhibit an aperture efficiency of 1-10 (e.g., 1.5-1.6, 1.6-1.7, 1.7-1.8, 1.8-1.9, 1.9-2, 2-2.15, less than 1.5, greater than 2.15, etc.) and a quality factor of 10-5,000,000 (e.g., 50-500, 500-5000, 5000-50,000, 50,000-750,000, less than 500, greater than 750,000, etc.).
  • the structures can additionally or alternatively define any other suitable aperture efficiencies and/or quality factors.
  • such structures can include one or more resonators defining geometries that include sub-wavelength features (e.g., features defining characteristic dimensions smaller than the wavelengths of radiation that the resonator is configured to resonate with efficiently), such as cross-resonators (e.g., as shown in FIGURE 3B), split-ring resonators (e.g., as shown in FIGURE 3C), and/or electro- inductive-capacitive resonators (e.g., as shown in FIGURES 4A-4D).
  • sub-wavelength features e.g., features defining characteristic dimensions smaller than the wavelengths of radiation that the resonator is configured to resonate with efficiently
  • cross-resonators e.g., as shown in FIGURE 3B
  • split-ring resonators e.g., as shown in FIGURE 3C
  • electro- inductive-capacitive resonators e.g., as shown in FIGURES 4A-4D
  • such structures can include a discretized aperture (e.g., array of metamaterial unit cells, such as cross-resonators, split-ring resonators, and/or electro-inductive- capacitive resonators; example shown in FIGURE 3A), wherein the discrete elements of the aperture are controlled (e.g., independently, separately, etc.), such as to approximate a continuous distribution across the aperture.
  • a discretized aperture e.g., array of metamaterial unit cells, such as cross-resonators, split-ring resonators, and/or electro-inductive- capacitive resonators; example shown in FIGURE 3A
  • the discrete elements of the aperture are controlled (e.g., independently, separately, etc.), such as to approximate a continuous distribution across the aperture.
  • such structures can include an array of classical antenna elements (e.g., patch antennas, dipole antennas, etc.) arranged to enable and/or enhance supergaining behavior (e.g., as described in M. T. Ivrlac and J.
  • the dynamic impedance match 120 preferably functions to efficiently couple the antenna 110 to the downstream elements of the system (e.g., to the RF-DC converter 130).
  • the dynamic impedance match 120 can include an input 121, a tuning network 122, a power measurement module 123, a control network 124, an output 125, and/or any other suitable elements (e.g., as shown in FIGURES 5A-5B and/or 9A-9D).
  • the input 121 preferably functions to receive RF power from a power source (e.g., the antenna 110) that can exhibit arbitrary and/or changing output impedance and/or power magnitude.
  • the input 121 can be electrically coupled to (e.g., electrically connected to, resonantly coupled to, configured to be driven by, etc.) the antenna 110 and/or other power source.
  • the input 121 can be connected to the antenna 110 by a coaxial cable. However, the input can be otherwise coupled to the antenna.
  • the tuning network 122 preferably functions to tune the input impedance of the dynamic impedance match (e.g., the impedance experienced at the input 121 by the antenna 110).
  • the tuning network 122 can include a circuit including one or more inductors and capacitors.
  • the tuning network 122 includes one or more variable electrical components (e.g., variable capacitor), preferably wherein the control network 124 is operable to alter the electrical properties of the variable component(s) (e.g., as shown in FIGURES 5B, 9A, and/or 9D).
  • the power coupler preferably transmits most power from the tuning network 122 (e.g., received at the power coupler input port) to the transmitted port, and couples a small portion of the power (e.g., via the coupled port) into an RF power detector (e.g., RSSI detector), which preferably outputs a power measurement signal.
  • the power coupler can have a coupling factor (e.g., defined as 10 ⁇ og(P coupled /P in ), wherein P in is the input power at the input port and P CO upied is the output power at the coupled port) of negative 3, 6, 10, 20, 30, 3-6, 6-10, 10-20, or 20-30 dB, and/or any other suitable coupling factor.
  • the power coupler can include a transmission line coupler (e.g., coupled transmission lines, branch-line coupler, Lange coupler, T-junction power divider, Wilkinson power divider, hybrid ring coupler, etc.), a waveguide coupler (e.g., waveguide branch-line coupler, Bethe-hole coupler, Riblet short-slot coupler, Schwinger reversed-phase coupler, Moreno crossed-guide coupler, waveguide hybrid ring coupler, magic tee coupler, etc.), and/or any other suitable power coupler.
  • the RF power detector can, for example, include (e.g., be) a diode detector that outputs a rectified signal to the control network 124 (e.g., at the signal output).
  • control network 124 includes: an analog-to-digital converter that converts the rectified signal from the diode detector into a digital signal, an optimization circuit that implements the control algorithm based on the digital signal, a digital-to-analog converter that converts the output of the optimization circuit to an analog signal, and a buffer amplifier that outputs the analog signal to the tuning network 122, preferably via an inductive element (e.g., control network inductor) that electrically couples (e.g., connects) the buffer amplifier to the tuning network, but additionally or alternatively via any other suitable element(s) in any suitable arrangement.
  • inductive element e.g., control network inductor
  • the tuning network includes one or more inductors (e.g., inductors Li and/or L2) and/or capacitors (e.g., capacitors Ci and/or C2).
  • one or more of the inductors preferably electrically couples (e.g., connects) the antenna to the power measurement network and the power output
  • one or more of the capacitors preferably electrically couples (e.g., connects) one or more of the inductors (and/or any other suitable elements, such as the antenna, power measurement network, etc.) to ground.
  • the tuning network can define a T-match network (e.g., wherein an optional capacitor C2, which may be connected near the input 121, such as at a point between the antenna 110 and the inductor Li, is absent), a pi-match network (e.g., wherein the second inductance of inductor L2 is substantially zero, such as zero, negligible, and/or much less than the first inductance of inductor Li), an L-match network (e.g., wherein the optional capacitor C2 is absent and either the first or second inductance is substantially zero), and/or any other suitable tuning network.
  • T-match network e.g., wherein an optional capacitor C2, which may be connected near the input 121, such as at a point between the antenna 110 and the inductor Li, is absent
  • a pi-match network e.g., wherein the second inductance of inductor L2 is substantially zero, such as zero, negligible, and/or much less than the first inductance of inductor Li
  • control network inductor L3 which electrically couples the control network (e.g., buffer amplifier) to the tuning network, is preferably electrically coupled (e.g., connected) to the tuning network between at least one of the tuning network inductors and at least one of the tuning network capacitors.
  • control network 124 can additionally or alternatively include any other suitable elements in any other suitable arrangement
  • dynamic impedance match 120 can additionally or alternatively include any other suitable electrical couplings and/or connections.
  • the RF-DC converter 130 preferably functions to efficiently convert RF input power to DC output power.
  • the RF-DC converter 130 e.g., rectifier
  • the RF-DC converter 130 can include an input 131, diodes 132, DC blocking filters (e.g., series DC blocking filter 133, shunt DC blocking filter 134, etc.), low pass filters 135, DC pass filters 136, outputs 137, and/or any other suitable elements (e.g., as shown in FIGURES 6A-6B).
  • the input 131 e.g., rectifier input
  • the input 131 preferably functions to receive RF power.
  • the input 131 can be electrically coupled to the antenna 110, preferably via the dynamic impedance match 120.
  • the input 131 can be electrically connected to the output 125 of the dynamic impedance match (e.g., by a waveguide, such as a coaxial cable, microstrip, etc.).
  • the diodes 132 preferably function to provide passive waveshaping (e.g., of the input RF power).
  • the diodes 132 can (individually and/or cooperatively) generate common-mode and/or differential-mode RF signals (e.g., harmonics of the input RF power signal).
  • the diodes 132 preferably define an antisymmetric diode pair (e.g., two diodes 132a and 132b with opposing orientations, one between each transmission line and ground).
  • the antisymmetric diode pair preferably generates odd harmonics in the common-mode signal and even harmonics in the differential mode signal (e.g., such that the common-mode signal approximates a square wave).
  • the diodes 132 can be Zener diodes, Schottky diodes, and/or any other suitable diodes or other rectifying components (e.g., transistors, thyristors, any other suitable non-linear circuit elements and/or devices, etc.).
  • the RF-DC converter 130 can include series DC blocking filters 133 (e.g., capacitors C3 and/or C4), shunt DC blocking filters 134 (e.g., capacitor C5), and/or any other suitable filters.
  • the shunt DC blocking filter 134 preferably functions to short the differential-mode RF signal (e.g., containing substantially only even harmonics of the input RF power signal).
  • the DC blocking filters preferably include one or more capacitors, and can additionally or alternatively include any other suitable components.
  • the low pass filter 135 preferably functions as a harmonic terminator.
  • the low pass filter 135 preferably does not significantly attenuate the fundamental RF signal (the input RF power signal), and preferably strongly reflects harmonics (e.g., harmonics generated by and/or reflected off of the diodes 132 and sent back towards the input 131) of the fundamental (e.g., presents matched or near-matched impedance to the fundamental and high impedance to the harmonics).
  • the low pass filter 135 preferably provides a high impedance to these harmonics that are traveling from the diodes 132 towards the input 131, and the impedance presented to the harmonics traveling from the diodes 132 towards the filter 135 may be substantially different than or similar to (e.g., substantially equal to) the impedance that would be presented to the harmonics if they were travelling from the input 131 toward the filter 135.
  • the low pass filter 135 preferably includes one or more inductors (e.g., inductors L5 and/or L6), and can additionally or alternatively include any other suitable components. Although described herein as a low pass filter, the low pass filter 135 can additionally or alternatively include one or more band pass filters and/or any other suitable filters.
  • the DC pass filter 136 preferably functions to restrict the fundamental RF signal (e.g., while transmitting the DC power generated by the RF-DC converter 130).
  • the DC pass filter 136 preferably includes one or more inductors (e.g., inductors L3 and/or L4) and/or capacitors, and can additionally or alternatively include any other suitable components.
  • the DC pass filter 136 can be electrically coupled (e.g., directly electrically connected) to the output 137 (e.g., rectifier output), which preferably functions to output the DC power.
  • the DC impedance converter 140 preferably functions to present a substantially optimal load to the RF-DC converter output 137 (e.g., regardless of an arbitrary and/or changing load at the DC power output 150), such as by operating in a discontinuous conduction mode (e.g., feedforward discontinuous conduction mode), and/or to present a substantially consistent output to the load (e.g., standard output voltage, such as 3.3, 3.6, 4.5, 5, 6, 9, 12, 20, 24, 28, 36, 48, or 72 V).
  • the load can be a user device (e.g., smartphone, smartwatch, etc.), or be any other suitable powered system.
  • the DC impedance converter 140 can include an input 141, DC-DC converters (e.g., a first 142 and/or second switching DC-DC converter 144), DCM maintenance control 143, parameter measurement module 145, and feedback control 146 (e.g., as shown in FIGURES 7A-7B).
  • the DC impedance converter 140 can additionally or alternatively include an electrical energy store 147 and/or any other suitable elements.
  • the input 141 preferably functions to receive DC power.
  • the input 141 can be electrically coupled (preferably electrically connected) to the RF-DC converter output 137.
  • the input 141 preferably presents an input impedance substantially equal to the optimal load for the RF-DC converter 130, but can additionally or alternatively present any other suitable input impedance.
  • the DC-DC converters are preferably buck-boost converters, but can additionally or alternatively include single-ended primary-inductor converters (SEPIC), and/or any other suitable DC-DC converter (e.g., buck, boost, Cuk, etc.).
  • the DC-DC converters can include inductors (e.g., inductor L7 and/or L8), capacitors (e.g., capacitor C6 and/or C7), and/or any other suitable elements.
  • the first switching DC-DC converter 142 preferably operates in a discontinuous conduction mode (DCM) and/or is preferably designed to enable operation in the DCM (e.g., includes a low-value inductor, such as inductor L7), but can additionally or alternatively operate in a continuous conduction mode (e.g., to achieve an input impedance outside a range of input impedances achievable under DCM conditions, such as based on a feedforward and/or feedback control).
  • the first switching DC-DC converter 142 can be electrically coupled (preferably electrically connected) to the input 141.
  • the DC impedance converter 140 can optionally include a second switching
  • the DC-DC converter 144 which preferably operates in a continuous conduction mode.
  • the second converter 144 is preferably arranged downstream of the first converter 142 (e.g., wherein the first converter 142 is between the input 141 and the second converter 144).
  • the second switching DC-DC converter 144 could be omitted entirely and/or replaced with a different subsystem that is not necessarily a DC-DC converter.
  • the output voltage of 142 is substantially fixed to be the battery voltage.
  • 142 would serve as a constant voltage current source that dumps charge into the battery.
  • the first switching DC-DC converter 142 exhibits a converter efficiency ⁇
  • a battery with voltage V ou t is placed at the output of the first switching DC-DC converter 142, and an input impedance of 3 ⁇ 4 n is specified to be the input impedance of the first switching DC-DC converter 142
  • the current flowing into the battery is approximately equal to ( ⁇ * Vm 2 )/(V 0U t * 3 ⁇ 4 n ).
  • the output voltage will be regulated by the battery and only the current flowing into the battery will be altered to preserve the necessary converter input impedance.
  • the voltage is fixed in some manner other than by a battery, such as using a zener diode and/or a charged capacitor (e.g., an energy storage element that can accept trickle charging).
  • a linear regulator could be used; fixing a storage element directly to the output of the first switching DC-DC converter 142 could be used; a standard charge controller could be used; more advanced control such as an additional DC-DC converter (e.g., converter such as described above); and/or any other suitable system (e.g., system in which strong load regulation is not needed) could be used.
  • the DC impedance converter operation measurements can include: inductor current and/or capacitor voltage (e.g., for the inductors and/or capacitors of the first switching DC-DC converter 142, such as inductor L7 and/or capacitor C6); voltage, current, and/or power output from the DC impedance converter 140 and/or the first switching DC-DC converter 142 (e.g., wherein the control 143 is configured to optimize for the maximum power output from the converter); and/or any other suitable parameter measurements.
  • inductor current and/or capacitor voltage e.g., for the inductors and/or capacitors of the first switching DC-DC converter 142, such as inductor L7 and/or capacitor C6
  • voltage, current, and/or power output from the DC impedance converter 140 and/or the first switching DC-DC converter 142 e.g., wherein the control 143 is configured to optimize for the maximum power output from the converter
  • any other suitable parameter measurements e.g., any other suitable parameter measurements.
  • the parameter measurement module 145 preferably functions to measure one or more parameters (e.g., voltage, current, etc.) to be regulated at the DC power output 150.
  • the parameter measurement module 145 can be electrically coupled (preferably electrically connected) to the second switching DC-DC converter 144 (e.g., at the parameter measurement module input) and/or to the DC power output 150 (e.g., at the parameter measurement module output).
  • the DC impedance converter 140 can optionally include one or more electrical energy stores 147.
  • the electrical energy store 147 can function to buffer DC power delivery to the load and/or to power operation of the DC impedance converter 140 (and/or any other suitable elements of the system, such as the control network 124), such as during system startup (e.g., before wirelessly-received power is available to power the active elements of the system) and/or throughout system operation.
  • the DC impedance converter 140 can control DC power routing between the input 141, electrical energy store 147, and DC power output 150.
  • the electrical energy store 147 can include one or more batteries, capacitors (e.g., supercapacitors, capacitor C8, etc.), and/or any other suitable electrical energy storage components.
  • DC power routing for the DC impedance converter is achieved through a load switch that is controlled by an onboard logic unit that responds to one or more measurements, such as battery level and/or power, voltage, and/or current output to the energy storage element and/or load.
  • the DC impedance converter 140 (and/ or any other suitable elements of the system) can additionally or alternatively include one or more bootstrapping networks.
  • the bootstrapping network preferably functions to power operation of the DC impedance converter 140 (and/or any other suitable elements of the system, such as the control network 124), such as during system startup (e.g., before active elements of the system have started up and/or converged on acceptable configurations for efficient wireless power reception and/or delivery) and/or throughout system operation.
  • the bootstrapping network preferably receives (and distributes) power from the DC impedance converter output (e.g., analogous to an additional load), which can be beneficial as the bootstrapping network will not substantially alter the input impedance (e.g., by a possibly arbitrary and/or variable amount) at the RF-DC converter output 137.
  • the bootstrapping network can additionally or alternatively receive (and distribute) power from the RF-DC converter output 137 and/or from any other suitable location.
  • the DC impedance converter allows power flow from the RF-DC converter output 137 to the bootstrapping network (e.g., to the electrical energy store 147, such as an output capacitor of the DC impedance converter), and the bootstrapping network regulates (e.g., loosely regulates) delivery of this power to the active elements of the DC impedance converter (e.g., DCM maintenance control 143, parameter measurement module 145, and/or feedback control 146, etc.) and/or any other suitable elements of the system.
  • the active elements of the DC impedance converter e.g., DCM maintenance control 143, parameter measurement module 145, and/or feedback control 146, etc.
  • the active elements can achieve normal operation of the DC impedance converter, regulating power flow from the RF-DC converter output 137 to the load and to continue powering the active elements.
  • the DC impedance converter 140 can additionally or alternatively include any other suitable elements in any suitable arrangement, with any other suitable electrical couplings and/or connections.
  • the system 100 can optionally include a plurality of some or all of the system elements. Including duplicate elements can enable reception of greater amounts of RF power (e.g., due to favorable arrangements of multiple antennas 110).
  • the duplicate elements are preferably electrically connected in a parallel-series array (e.g., as shown in FIGURE lB), which can reduce the variance in current and/or voltage produced by the array (e.g., compared with the variance of an element of the array, variance between the elements, etc.).
  • the system 100 includes an array of input subsystems that all feed into a single output subsystem.
  • the input subsystems each include an antenna no, dynamic impedance match 120, and RF-DC converter 130
  • the output subsystem includes a single DC impedance converter 140 and DC power output 150.
  • the system 100 preferably includes only a small number (e.g., one) of DC impedance converters 140, which can typically be large and/or expensive. However, the system 100 can include any suitable number of elements in any suitable arrangement.
  • a method for wireless power reception preferably includes (e.g., as shown in FIGURE 8): receiving power (e.g., RF radiation, such as microwave radiation) wirelessly at an antenna, dynamically adjusting an input impedance of a dynamic impedance match coupled to the antenna, and/or delivering the power to a load.
  • the method can additionally or alternatively include rectifying the received power at a rectifier, adjusting an input impedance of a DC impedance converter coupled to the rectifier, communicating information associated with system operation to a wireless power transmitter, and/or controlling wireless power transmitter operation based on the information.
  • the method can additionally or alternatively include any other suitable elements performed in any suitable manner.
  • the method is preferably performed using (e.g., by) the system 100 (e.g., as described above, such as regarding functionality, behavior, and/or use of the system elements), optionally in coordination with one or more wireless power transmitters, but can additionally or alternatively be performed using any other wireless power receivers and/or other suitable systems.
  • the method is preferably performed in response to receiving wireless power at the receiver and/or receiving a request to receive wireless power, but can additionally or alternatively be performed at any other suitable time.
  • the power is preferably received wirelessly from propagating (e.g., "far- field") radiation, but can additionally or alternatively be received from evanescent (e.g., "near-field") radiation.
  • the received radiation is preferably one or more pure-tone (or substantially pure-tone, such as defining a bandwidth less than a threshold bandwidth) signals (e.g., which can be beneficial in embodiments that employ one or more supergaining structures and/or other narrow bandwidth antennas), but can additionally or alternatively include any suitable signal types (e.g., in embodiments that employ wider- bandwidth antennas, in embodiments in which communication signals are transmitted along with the power, etc.).
  • the radiation has a GHz-scale frequency (e.g., 5-10 GHz, such as 5.8 GHz and/or greater than 5.8 GHz).
  • the radiation has a hundreds of MHz-scale frequency (e.g., 100-500 MHz, such as 433 MHz and/or less than 433 MHz).
  • the power can additionally or alternatively be received in any other suitable form.
  • the antenna can be electrically coupled to (e.g., electrically connected to, resonantly coupled to, operable to drive, etc.) the impedance tuning network (e.g., via a lead, trace, wire, waveguide, resonant coupling, etc.), preferably to the input of the impedance tuning network, wherein RF input impedance (e.g., input impedance of the impedance tuning network, input impedance experienced by the antenna, etc.; impedance at an RF frequency, such as the frequency of RF power received by the antenna) is adjusted based on the control signal (e.g., adjusted directly by the control signal, such as by injection of a control signal current into the impedance tuning network and/or application of a control signal voltage to the impedance tuning network).
  • RF input impedance e.g., input impedance of the impedance tuning network, input impedance experienced by the antenna, etc.; impedance at an RF frequency, such as the frequency of RF power received
  • Determining the control signal preferably includes implementing a power optimization algorithm (e.g., as described above, such as regarding the control network 124), such as implemented over a series of iterations of a portion of the method elements.
  • a power optimization algorithm e.g., as described above, such as regarding the control network 124
  • the current control signal can modify the input impedance of the impedance tuning network, thereby modifying the coupling of power to the antenna, power measurement network, and/or output
  • the power measurement network can output an updated feedback signal based on the modified power coupling
  • the control network can determine (e.g., based on the algorithm) an updated control signal based on the current control signal, the associated updated feedback signal, and preferably one or more previous control signals and associated feedback signals.
  • control network can determine a desired feedback signal (and optionally, an associated feedback signal and/or other metric associated with the feedback signal), preferably an optimal feedback signal (e.g., associated with the best feedback signal achieved, such as the feedback signal indicative of the greatest power coupling).
  • a desired feedback signal and optionally, an associated feedback signal and/or other metric associated with the feedback signal
  • an optimal feedback signal e.g., associated with the best feedback signal achieved, such as the feedback signal indicative of the greatest power coupling.
  • the method can optionally include communicating information associated with system operation to a wireless power transmitter and/or controlling wireless power transmitter operation based on the information.
  • the method can include cooperation between the system and one or more power transmitters and/or other power receivers (e.g., using a wireless communication module, such as a Wi-Fi, Bluetooth, or BLE radio) to optimize power transmission (e.g., to the system, to the set of all power receivers, etc.).
  • the system can transmit an indication of the received power (e.g., power at the antenna 110, power measurement module 123, DC impedance converter 140, DC power output 150, etc.).
  • the system can transmit periodically, when requested, and/or with any other suitable timing.
  • the system continuously optimizes the dynamic impedance match(es) 120 (e.g., as a fast optimization inner loop, such as described above regarding implementing the power optimization algorithm), and transmits data representing the optimized power magnitude (e.g., measured by the power measurement module(s) 123).
  • the power transmitter can adjust power transmission parameters based on the data received from the system, preferably to optimize power transmission to the system (e.g., as a slower optimization outer loop).
  • all of the receiver parameters are initially set to predetermined values (e.g., pre-calculate to be a good baseline), such as by configuring the DC impedance converter duty cycle and/or the RF dynamic impedance match to predetermined values upon startup.
  • the transmitter optimization loop is performed (e.g., quickly, preferably as quickly as possible) to determine the transmission parameters, and then the receiver-side optimizations are performed (e.g., once, continuously, periodically, etc.) under fixed transmission parameters, which can reduce timing issues and/or complexity.
  • the method can additionally or alternatively include any other suitable elements performed in any suitable manner.
  • the preferred embodiments include every combination and permutation of the various system components and the various method processes.
  • various processes of the preferred method can be embodied and/or implemented at least in part as a machine configured to receive a computer- readable medium storing computer-readable instructions.
  • the instructions are preferably executed by computer-executable components preferably integrated with the system.
  • the computer-readable medium can be stored on any suitable computer readable media such as RAMs, ROMs, flash memory, EEPROMs, optical devices (CD or DVD), hard drives, floppy drives, or any suitable device.
  • the computer-executable component is preferably a general or application specific processing subsystem, but any suitable dedicated hardware device or hardware/firmware combination device can additionally or alternatively execute the instructions.

Landscapes

  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Signal Processing (AREA)
  • Charge And Discharge Circuits For Batteries Or The Like (AREA)

Abstract

L'invention concerne un système de réception d'énergie sans fil, comprenant de préférence une ou plusieurs : antennes, des aaptations d'impédance dynamique, des convertisseurs RF-CC, des convertisseurs d'impédance CC et/ou des sorties de puissance CC. L'invention concerne également un procédé de réception d'énergie sans fil, comprenant de préférence : la réception d'énergie sans fil au niveau d'une antenne, le réglage dynamique d'une impédance d'entrée d'une adaptation d'impédance dynamique couplée à l'antenne, et/ou la distribution de la puissance à une charge.
PCT/US2018/036310 2017-06-06 2018-06-06 Système et procédé de réception d'énergie sans fil WO2018226864A1 (fr)

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US62/515,962 2017-06-06

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CN111900943B (zh) * 2020-07-14 2023-05-05 电子科技大学 一种射频宽带高效率整流器

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