WO2018173364A1 - Bridgeless power factor correction circuit - Google Patents

Bridgeless power factor correction circuit Download PDF

Info

Publication number
WO2018173364A1
WO2018173364A1 PCT/JP2017/041704 JP2017041704W WO2018173364A1 WO 2018173364 A1 WO2018173364 A1 WO 2018173364A1 JP 2017041704 W JP2017041704 W JP 2017041704W WO 2018173364 A1 WO2018173364 A1 WO 2018173364A1
Authority
WO
WIPO (PCT)
Prior art keywords
current
inductor
detection circuit
factor correction
input
Prior art date
Application number
PCT/JP2017/041704
Other languages
French (fr)
Japanese (ja)
Inventor
小龍 江
大西　浩之
真吾 長岡
Original Assignee
オムロン株式会社
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by オムロン株式会社 filed Critical オムロン株式会社
Publication of WO2018173364A1 publication Critical patent/WO2018173364A1/en

Links

Images

Definitions

  • the present invention relates to a bridgeless power factor correction (PFC) circuit without a rectifying bridge, and more particularly to simplification of a voltage / current sensor in a totem pole bridgeless PFC circuit.
  • PFC power factor correction
  • a PFC circuit is used to improve the power factor of input power and suppress harmonic current.
  • many rectifier bridges are provided, but since the loss of the bridge itself hinders high efficiency and miniaturization, bridgeless PFC circuits that do not have such rectifier bridges have also been proposed. (For example, refer to FIG. 10 of Patent Document 1 or Patent Document 2).
  • a switching element that is subject to high-frequency switching in the positive half cycle of the AC input and a switching element that is subject to high-frequency switching in the negative half cycle are connected to the inductor provided on the AC input side, respectively.
  • a totem pole type bridgeless power factor converter has also been proposed (see, for example, Patent Document 3).
  • an object of the present invention is to provide a bridge that can simplify a circuit, reduce the overall size, reduce costs, and the like without using expensive circuit components for voltage / current detection. It is to provide a power factor correction circuit.
  • a bridgeless power factor correction circuit accumulates energy from an AC input power source and converts it from a low voltage high current to a high voltage low current, and the boost inductor intermittently.
  • a switching element that performs a switching operation for accumulating energy, a rectifying element that prevents a backflow of current from the switching element, a smoothing capacitor that smoothes energy output from the boost inductor, and the boost inductor
  • An inductor current detection circuit that detects the inductor current by a current detection element inserted in a path of the flowing inductor current, an input voltage detection circuit that detects an input voltage using one side of the input power supply as a reference potential, and an output to a load Output voltage detection for detecting voltage using the one side of the input power supply as a reference potential
  • a control unit that controls the switching operation based on a path, an inductor current detection result by the inductor current detection circuit, an input voltage detection result by the input voltage detection circuit, and an output voltage detection result
  • the output voltage detection circuit may be composed of, for example, a resistor and a differential amplifier, but is not limited thereto.
  • a current detection element although resistance is mentioned, for example, it is not restricted to this.
  • One end of the current detection element is connected to the reference potential, and the inductor current detection circuit measures the voltage across the current detection element by measuring one side of the input power supply as a reference potential. The inductor current may be detected.
  • bridgeless power factor correction circuit is a totem pole bridgeless power factor correction circuit, but is not limited thereto.
  • the bridgeless power factor correction circuit having such a configuration, it is not necessary to use expensive circuit parts for voltage / current detection, and the circuit can be simplified, the entire size can be reduced, and the cost can be reduced. .
  • the bridgeless power factor correction circuit of the present invention it is not necessary to use expensive circuit parts for voltage / current detection, and the circuit can be simplified, the entire size can be reduced, and the cost can be reduced.
  • FIG. 1 is a circuit diagram showing a schematic configuration of a totem pole / bridgeless PFC circuit 100 according to an embodiment of the present invention.
  • FIG. 3 is a circuit diagram illustrating a schematic configuration of an inductor current detection circuit 20.
  • FIG. 3 is a circuit diagram illustrating a schematic configuration of an output voltage detection circuit 30.
  • FIG. 1 is a circuit diagram showing a schematic configuration of a totem pole / bridgeless PFC circuit 100 according to an embodiment of the present invention.
  • FIG. 3 is a circuit diagram illustrating a schematic configuration of an inductor current detection circuit 20.
  • FIG. 3 is a circuit diagram illustrating a schematic configuration of an output voltage detection circuit 30.
  • FIG. 1 is a circuit diagram showing a schematic configuration of a totem pole bridgeless PFC circuit 100 according to an embodiment of the present invention.
  • a bridgeless PFC circuit 100 stores power energy from an AC input power source IP and converts it from a low voltage and high current to a high voltage and low current, and the boost inductor L is intermittently connected.
  • Switch Q1 and switch Q2 for performing a switching operation for accumulating power energy, rectifier element D1 and rectifier element D1 for preventing backflow of currents from these switches Q1 and Q2, and output from boost inductor L
  • Current smoothing capacitor C for smoothing the generated power energy
  • input voltage detection circuit 10 for detecting input voltage Vin using one side of input power supply IP as a reference potential
  • Inductor current that detects the inductor current by the voltage generated across the resistor 21 A detection circuit 20, and an output voltage detection circuit 30 for detecting the output voltage Vo to the output load OL one side of the input power IP as a reference potential.
  • the resistor 21 is an example of a current detection element, but such a current detection element is not limited to a resistance.
  • Examples of the switch Q1 and the switch Q2 include, but are not limited to, switching elements such as field effect transistors (FETs) and IGBTs.
  • FETs field effect transistors
  • IGBTs IGBTs
  • the switch Q1 and the switch Q2 have their respective switching operations (ON) so that the output voltage Vo becomes constant based on the detection results by the input voltage detection circuit 10, the inductor current detection circuit 20, and the output voltage detection circuit 30. / Off, timing, etc.) are controlled by a control unit (not shown).
  • the input voltage detection circuit 10 includes a resistor 11 and a resistor 12 connected in series. If a voltage obtained by dividing the input voltage Vin is detected, the input voltage Vin can be calculated based on the ratio of the resistor 11 and the resistor 12.
  • the output voltage detection circuit 30 includes resistors 31 to 34 and a differential amplifier 35, details of which will be described later.
  • the power supply of the differential amplifier 27 (details will be described later) and the differential amplifier 35 are common, and a voltage of ⁇ 15 V with a reference potential of 0 V is supplied.
  • FIG. 2 is a circuit diagram illustrating a schematic configuration of the inductor current detection circuit 20.
  • the configuration is not limited to this.
  • the inductor current detection circuit 20 includes resistors 22 to 25, a capacitor 26, and a differential amplifier 27 in addition to the resistor 21 for detecting the inductor current.
  • One end of the resistor 21 is connected to the inverting input of the differential amplifier 27 through the resistor 23 and is connected to the reference potential, and the other end of the resistor 21 is connected to the non-inverting input of the differential amplifier 27 through the resistor 24. It is connected.
  • the inverting input and output of the differential amplifier 27 are connected via a resistor 22, and a capacitor 26 is connected in parallel with the resistor 22.
  • the inductor current detection circuit 20 can detect the inductor current.
  • the bridgeless PFC circuit 100 is supplied with an input voltage Vin of 100 to 240 V from the input power source IP, and a current of several A to several tens of A flows through the inductor current detection circuit 20.
  • Vin 100 to 240 V
  • a current of several A to several tens of A flows through the inductor current detection circuit 20.
  • the voltage applied to both ends of the resistor 21 is about 75 mV at maximum.
  • the voltage of the inverting input of the differential amplifier 27 is the same as the reference potential, and the voltage of the non-inverting input is about 75 mV at the maximum, so that the input voltage of the differential amplifier 27 can be lowered.
  • the frequency of the current to be measured is related to the switching frequency of the circuit, but the frequency is high because the current shape is a triangular wave.
  • the switching frequency is 1 MHz, it is necessary to be able to measure up to about 5 MHz, assuming that the fifth harmonic is included.
  • FIG. 3 is a circuit diagram illustrating a schematic configuration of the output voltage detection circuit 30.
  • the resistor 31 and the resistor 32 are connected in series, and the connection point is connected to the non-inverting input of the differential amplifier 35.
  • One end of the resistor 31 (on the opposite side to the resistor 32) is connected to one side (see FIG. 1) of the output load OL, and one end of the resistor 32 (on the opposite side to the resistor 31) is the reference potential on the input power supply IP side. (See FIG. 1).
  • the resistor 33 and the resistor 34 are also connected in series, and the connection point is connected to the inverting input of the differential amplifier 35.
  • One end of the resistor 33 (on the side opposite to the resistor 34) is connected to the other side (see FIG. 1) of the output load OL, and one end of the resistor 34 (on the side opposite to the resistor 33) is the reference potential on the input power source IP side. (See FIG. 1).
  • the output voltage Vo can be detected by measuring the potential difference between both ends of the output load with the input power source IP side as the reference potential.
  • the resistance value ratio of the resistor 31 to the resistor 32 may be several tens of times, for example.
  • the resistance value ratio of the resistor 33 to the resistor 34 is the same.
  • the value of the resistor 31 and the resistor 33 is 493 k ⁇
  • the value of the resistor 32 and the resistor 34 is 10 k ⁇ .
  • the output voltage Vo to be measured by the output voltage detection circuit 30 is about 400V, but when viewed from the reference potential, the voltage on the switch Q1 side of the output load OL is about 500V, and the voltage on the switch Q2 side is about 100V. . Even in this case, the inverting input of the differential amplifier 35 is about 1V, and the non-inverting input is about 0.2V. Therefore, the input voltage of the differential amplifier 35 can be lowered.
  • the cut-off frequency only needs to correspond to about 20 Hz.
  • the present invention is suitable for, for example, an AC-DC converter and a power supply device.

Abstract

A bridgeless PFC circuit (100) is provided with: a boost inductor (L) for storing energy from an input power supply (IP) and converting low-voltage high-current to high-voltage low-current; switches (Q1, Q2) for performing a switching operation for intermittently storing energy into the boost inductor (L); rectifier elements (D1, D1) for preventing currents from reversely flowing from the respective switches (Q1, Q2); a current smoothing capacitor (C) for smoothing energy output from the boost inductor (L); an input voltage detection circuit (10) for detecting an input voltage (Vin) using one side of the input power supply (IP) as a reference potential; an inductor current detection circuit (20) for detecting inductor current by a resistor (21) inserted in a path of the inductor current; and an output voltage detection circuit (30) for detecting an output voltage (Vo) using the one side of the input power supply (IP) as the reference potential.

Description

ブリッジレス力率改善回路Bridgeless power factor correction circuit
　本発明は、整流用ブリッジを持たないブリッジレス力率改善（ＰＦＣ：Power Factor Correction）回路に関し、特に、トーテムポール・ブリッジレスＰＦＣ回路における電圧・電流センサの簡素化に関する。 The present invention relates to a bridgeless power factor correction (PFC) circuit without a rectifying bridge, and more particularly to simplification of a voltage / current sensor in a totem pole bridgeless PFC circuit.
　従来、交流入力に接続されるスイッチング電源では、入力電力の力率を改善するとともに高調波電流を抑制するため、ＰＦＣ回路が用いられている。一般的には整流用ブリッジを設けたものも多いが、ブリッジ自体の損失が高効率化や小型化の妨げにもなるため、このような整流用ブリッジを持たないブリッジレスＰＦＣ回路も提案されている（例えば、特許文献１または特許文献２の図１０を参照）。 Conventionally, in a switching power supply connected to an AC input, a PFC circuit is used to improve the power factor of input power and suppress harmonic current. In general, many rectifier bridges are provided, but since the loss of the bridge itself hinders high efficiency and miniaturization, bridgeless PFC circuits that do not have such rectifier bridges have also been proposed. (For example, refer to FIG. 10 of Patent Document 1 or Patent Document 2).
　さらに、交流入力側に設けられたインダクタに対して、交流入力の正の半サイクルで高周波スイッチングの対象となるスイッチング素子と、負の半サイクルで高周波スイッチングの対象となるスイッチング素子とをそれぞれ接続したトーテムポール方式のブリッジレス力率コンバータも提案されている（例えば、特許文献３参照）。 Furthermore, a switching element that is subject to high-frequency switching in the positive half cycle of the AC input and a switching element that is subject to high-frequency switching in the negative half cycle are connected to the inductor provided on the AC input side, respectively. A totem pole type bridgeless power factor converter has also been proposed (see, for example, Patent Document 3).
特開２００２－０１７０８７号公報JP 2002-017087 A 国際公開第２０１０／０６１６５４号International Publication No. 2010/061654 特開２０１２－０７０４９０号公報JP 2012-070490 A
　従来のブリッジレスＰＦＣ回路では、入力側の電圧、電流や出力側の電圧を測定する必要があるが、回路の入力側と出力側の間にはスイッチング動作するスイッチング素子が存在し、特に入力側の電圧測定点と出力側の電圧測定点の電位は大きく異なるため、特許文献１のようにトランスなどの絶縁型の検出素子または検出回路を使用していた。そのため回路の複雑化を招いたり、高価な回路部品を使う必要があった。 In the conventional bridgeless PFC circuit, it is necessary to measure the voltage and current on the input side and the voltage on the output side, but there is a switching element that performs switching operation between the input side and the output side of the circuit. Since the potentials at the voltage measurement point and the voltage measurement point on the output side are greatly different, an insulation type detection element or detection circuit such as a transformer is used as in Patent Document 1. For this reason, the circuit is complicated and expensive circuit parts must be used.
　従来技術のこのような課題に鑑み、本発明の目的は、電圧・電流検出のために高価な回路部品を使用することなく回路の簡素化や全体の小型化およびコストダウンなどを可能とするブリッジレス力率改善回路を提供することである。 In view of such problems of the prior art, an object of the present invention is to provide a bridge that can simplify a circuit, reduce the overall size, reduce costs, and the like without using expensive circuit components for voltage / current detection. It is to provide a power factor correction circuit.
　上記目的を達成するため、本発明のブリッジレス力率改善回路は、交流の入力電源からのエネルギーを蓄積して、低圧高電流から高圧低電流に変換する昇圧インダクタと、この昇圧インダクタに断続的にエネルギーを蓄積するためのスイッチング動作を行うスイッチング素子と、このスイッチング素子からの電流の逆流を防止する整流素子と、前記昇圧インダクタより出力されたエネルギーを平滑化する平滑コンデンサと、前記昇圧インダクタを流れるインダクタ電流の経路に挿入された電流検出素子によって前記インダクタ電流を検出するインダクタ電流検出回路と、前記入力電源の一方側を基準電位として入力電圧を検出する入力電圧検出回路と、負荷への出力電圧を前記入力電源の前記一方側を基準電位として検出する出力電圧検出回路と、前記インダクタ電流検出回路によるインダクタ電流検出結果と、前記入力電圧検出回路による入力電圧検出結果と、前記出力電圧検出回路による出力電圧検出結果とに基づいて前記スイッチング動作を制御する制御部とを備えることを特徴とする。 In order to achieve the above object, a bridgeless power factor correction circuit according to the present invention accumulates energy from an AC input power source and converts it from a low voltage high current to a high voltage low current, and the boost inductor intermittently. A switching element that performs a switching operation for accumulating energy, a rectifying element that prevents a backflow of current from the switching element, a smoothing capacitor that smoothes energy output from the boost inductor, and the boost inductor An inductor current detection circuit that detects the inductor current by a current detection element inserted in a path of the flowing inductor current, an input voltage detection circuit that detects an input voltage using one side of the input power supply as a reference potential, and an output to a load Output voltage detection for detecting voltage using the one side of the input power supply as a reference potential A control unit that controls the switching operation based on a path, an inductor current detection result by the inductor current detection circuit, an input voltage detection result by the input voltage detection circuit, and an output voltage detection result by the output voltage detection circuit; It is characterized by providing.
　ここで、出力電圧検出回路は、例えば、抵抗および差動増幅器で構成されてもよいが、これに限らない。また、電流検出素子としては、例えば抵抗が挙げられるが、これに限らない。この電流検出素子はいずれかの一端が前記基準電位に接続されており、前記インダクタ電流検出回路は、前記入力電源の一方側を基準電位として前記電流検出素子の両端の電圧を測定することにより前記インダクタ電流を検出するようにしてもよい。 Here, the output voltage detection circuit may be composed of, for example, a resistor and a differential amplifier, but is not limited thereto. Moreover, as a current detection element, although resistance is mentioned, for example, it is not restricted to this. One end of the current detection element is connected to the reference potential, and the inductor current detection circuit measures the voltage across the current detection element by measuring one side of the input power supply as a reference potential. The inductor current may be detected.
　また、ブリッジレス力率改善回路として、具体的にはトーテムポール・ブリッジレス力率改善回路が挙げられるが、これに限らない。 In addition, a specific example of the bridgeless power factor correction circuit is a totem pole bridgeless power factor correction circuit, but is not limited thereto.
　このような構成のブリッジレス力率改善回路によれば、電圧・電流検出のために高価な回路部品を使用する必要がなくなり、回路の簡素化や全体の小型化およびコストダウンなどが可能となる。 According to the bridgeless power factor correction circuit having such a configuration, it is not necessary to use expensive circuit parts for voltage / current detection, and the circuit can be simplified, the entire size can be reduced, and the cost can be reduced. .
　本発明のブリッジレス力率改善回路によれば、電圧・電流検出のために高価な回路部品を使用する必要がなくなり、回路の簡素化や全体の小型化およびコストダウンなどが可能となる。 According to the bridgeless power factor correction circuit of the present invention, it is not necessary to use expensive circuit parts for voltage / current detection, and the circuit can be simplified, the entire size can be reduced, and the cost can be reduced.
本発明の一実施形態に係るトーテムポール・ブリッジレスＰＦＣ回路１００の概略構成を示す回路図である。1 is a circuit diagram showing a schematic configuration of a totem pole / bridgeless PFC circuit 100 according to an embodiment of the present invention. FIG. インダクタ電流検出回路２０の概略構成を例示する回路図である。3 is a circuit diagram illustrating a schematic configuration of an inductor current detection circuit 20. FIG. 出力電圧検出回路３０の概略構成を例示する回路図である。3 is a circuit diagram illustrating a schematic configuration of an output voltage detection circuit 30. FIG.
　以下、本発明に係る実施形態を、図面を参照して説明する。 Embodiments according to the present invention will be described below with reference to the drawings.
　＜実施形態の全体構成＞
　図１は本発明の一実施形態に係るトーテムポール・ブリッジレスＰＦＣ回路１００の概略構成を示す回路図である。 <Overall Configuration of Embodiment>
FIG. 1 is a circuit diagram showing a schematic configuration of a totem pole bridgeless PFC circuit 100 according to an embodiment of the present invention.
　この図１に示すように、ブリッジレスＰＦＣ回路１００は、交流の入力電源ＩＰからの電力エネルギーを蓄積して、低圧高電流から高圧低電流に変換する昇圧インダクタＬと、この昇圧インダクタＬに断続的に電力エネルギーを蓄積するためのスイッチング動作を行うスイッチＱ１およびスイッチＱ２と、これらのスイッチＱ１およびスイッチＱ２からの各電流の逆流を防止する整流素子Ｄ１および整流素子Ｄ１と、昇圧インダクタＬより出力された電力エネルギーを平滑化する電流平滑コンデンサＣと、入力電源ＩＰの一方側を基準電位として入力電圧Ｖinを検出する入力電圧検出回路１０と、昇圧インダクタＬを流れるインダクタ電流の経路に挿入された抵抗２１の両端に発生する電圧によってインダクタ電流を検出するインダクタ電流検出回路２０と、出力負荷ＯＬへの出力電圧Ｖｏを入力電源ＩＰの一方側を基準電位として検出する出力電圧検出回路３０とを備えている。 As shown in FIG. 1, a bridgeless PFC circuit 100 stores power energy from an AC input power source IP and converts it from a low voltage and high current to a high voltage and low current, and the boost inductor L is intermittently connected. Switch Q1 and switch Q2 for performing a switching operation for accumulating power energy, rectifier element D1 and rectifier element D1 for preventing backflow of currents from these switches Q1 and Q2, and output from boost inductor L Current smoothing capacitor C for smoothing the generated power energy, input voltage detection circuit 10 for detecting input voltage Vin using one side of input power supply IP as a reference potential, and an inductor current path flowing through boost inductor L Inductor current that detects the inductor current by the voltage generated across the resistor 21 A detection circuit 20, and an output voltage detection circuit 30 for detecting the output voltage Vo to the output load OL one side of the input power IP as a reference potential.
　ここで、抵抗２１は電流検出素子の一例であるが、このような電流検出素子は抵抗に限らない。 Here, the resistor 21 is an example of a current detection element, but such a current detection element is not limited to a resistance.
　スイッチＱ１およびスイッチＱ２としては、例えば電界効果トランジスタ（ＦＥＴ）やＩＧＢＴなどのスイッチング素子が挙げられるが、これらに限らない。 Examples of the switch Q1 and the switch Q2 include, but are not limited to, switching elements such as field effect transistors (FETs) and IGBTs.
　また、スイッチＱ１およびスイッチＱ２は、入力電圧検出回路１０、インダクタ電流検出回路２０、および出力電圧検出回路３０による各検出結果に基づいて出力電圧Ｖｏが一定となるように、それぞれのスイッチング動作（オン／オフやタイミングなど）が制御部（不図示）によって制御される。 Further, the switch Q1 and the switch Q2 have their respective switching operations (ON) so that the output voltage Vo becomes constant based on the detection results by the input voltage detection circuit 10, the inductor current detection circuit 20, and the output voltage detection circuit 30. / Off, timing, etc.) are controlled by a control unit (not shown).
　入力電圧検出回路１０は、直列接続された抵抗１１および抵抗１２で構成されている。入力電圧Ｖinが分圧された電圧を検出すれば、抵抗１１と抵抗１２の比に基づいて入力電圧Ｖinを算出することができる。 The input voltage detection circuit 10 includes a resistor 11 and a resistor 12 connected in series. If a voltage obtained by dividing the input voltage Vin is detected, the input voltage Vin can be calculated based on the ratio of the resistor 11 and the resistor 12.
　出力電圧検出回路３０は、抵抗３１～３４および差動増幅器３５で構成されているが、詳細は後述する。 The output voltage detection circuit 30 includes resistors 31 to 34 and a differential amplifier 35, details of which will be described later.
　また、差動増幅器２７（詳細は後述）および差動増幅器３５の電源は共通であり、基準電位を０Ｖとした±１５Ｖの電圧が供給される。 Also, the power supply of the differential amplifier 27 (details will be described later) and the differential amplifier 35 are common, and a voltage of ± 15 V with a reference potential of 0 V is supplied.
　＜インダクタ電流検出回路２０の具体例＞
　図２はインダクタ電流検出回路２０の概略構成を例示する回路図である。ただし、このような構成に限るわけではない。 <Specific Example of Inductor Current Detection Circuit 20>
FIG. 2 is a circuit diagram illustrating a schematic configuration of the inductor current detection circuit 20. However, the configuration is not limited to this.
　この図２に示すように、インダクタ電流検出回路２０は、インダクタ電流を検出するための抵抗２１に加えて、抵抗２２～２５、コンデンサ２６、および差動増幅器２７を備えている。抵抗２１の一端が抵抗２３を介して差動増幅器２７の反転入力に接続されるとともに基準電位に接続されており、抵抗２１の他端は抵抗２４を介して差動増幅器２７の非反転入力に接続されている。また、差動増幅器２７の反転入力と出力とが抵抗２２を介して接続されるとともに、この抵抗２２と並列にコンデンサ２６が接続されている。 As shown in FIG. 2, the inductor current detection circuit 20 includes resistors 22 to 25, a capacitor 26, and a differential amplifier 27 in addition to the resistor 21 for detecting the inductor current. One end of the resistor 21 is connected to the inverting input of the differential amplifier 27 through the resistor 23 and is connected to the reference potential, and the other end of the resistor 21 is connected to the non-inverting input of the differential amplifier 27 through the resistor 24. It is connected. The inverting input and output of the differential amplifier 27 are connected via a resistor 22, and a capacitor 26 is connected in parallel with the resistor 22.
　このような構成を用いて抵抗２１の両端の電圧を測定する。この電圧と抵抗２１の抵抗値を用いて抵抗２１に流れる電流を計算することにより、インダクタ電流検出回路２０はインダクタ電流を検出することができる。 Measure the voltage across resistor 21 using this configuration. By calculating the current flowing through the resistor 21 using this voltage and the resistance value of the resistor 21, the inductor current detection circuit 20 can detect the inductor current.
　また、ブリッジレスＰＦＣ回路１００は、入力電源ＩＰから１００Ｖ～２４０Ｖの入力電圧Ｖinが供給され、このインダクタ電流検出回路２０には、数Ａ～数十Ａの電流が流れる。例えば、抵抗２１の値を５ｍΩとしたときに抵抗２１の両端にかかる電圧は最大７５ｍＶ程度である。 The bridgeless PFC circuit 100 is supplied with an input voltage Vin of 100 to 240 V from the input power source IP, and a current of several A to several tens of A flows through the inductor current detection circuit 20. For example, when the value of the resistor 21 is 5 mΩ, the voltage applied to both ends of the resistor 21 is about 75 mV at maximum.
　したがって、差動増幅器２７の反転入力の電圧は基準電位と同じとなり、また非反転入力の電圧は最大７５ｍＶ程度となるので、差動増幅器２７の入力電圧を低くすることができる。 Therefore, the voltage of the inverting input of the differential amplifier 27 is the same as the reference potential, and the voltage of the non-inverting input is about 75 mV at the maximum, so that the input voltage of the differential amplifier 27 can be lowered.
　このとき、測定すべき電流の周波数は回路のスイッチング周波数に関係するが、電流形状は三角波となるため周波数は高い。例えば、スイッチング周波数が１ＭＨｚのとき、５次高調波まで含むと仮定すれば、５ＭＨｚ程度まで測定可能でなければならない。 At this time, the frequency of the current to be measured is related to the switching frequency of the circuit, but the frequency is high because the current shape is a triangular wave. For example, when the switching frequency is 1 MHz, it is necessary to be able to measure up to about 5 MHz, assuming that the fifth harmonic is included.
　＜出力電圧検出回路３０の具体例＞
　図３は出力電圧検出回路３０の概略構成を例示する回路図である。 <Specific Example of Output Voltage Detection Circuit 30>
FIG. 3 is a circuit diagram illustrating a schematic configuration of the output voltage detection circuit 30.
　この図３に示すように、抵抗３１および抵抗３２は直列接続されており、その接続点が差動増幅器３５の非反転入力に接続されている。抵抗３１の一端（抵抗３２とは反対側）は出力負荷ＯＬの一方側（図１参照）に接続されるとともに、抵抗３２の一端（抵抗３１とは反対側）は入力電源ＩＰ側の基準電位（図１参照）に接続されている。また、抵抗３３および抵抗３４も直列接続されており、その接続点が差動増幅器３５の反転入力に接続されている。抵抗３３の一端（抵抗３４とは反対側）は出力負荷ＯＬの他方側（図１参照）に接続されるとともに、抵抗３４の一端（抵抗３３とは反対側）は入力電源ＩＰ側の基準電位（図１参照）に接続されている。 As shown in FIG. 3, the resistor 31 and the resistor 32 are connected in series, and the connection point is connected to the non-inverting input of the differential amplifier 35. One end of the resistor 31 (on the opposite side to the resistor 32) is connected to one side (see FIG. 1) of the output load OL, and one end of the resistor 32 (on the opposite side to the resistor 31) is the reference potential on the input power supply IP side. (See FIG. 1). The resistor 33 and the resistor 34 are also connected in series, and the connection point is connected to the inverting input of the differential amplifier 35. One end of the resistor 33 (on the side opposite to the resistor 34) is connected to the other side (see FIG. 1) of the output load OL, and one end of the resistor 34 (on the side opposite to the resistor 33) is the reference potential on the input power source IP side. (See FIG. 1).
　これにより、入力電源ＩＰ側を基準電位として出力負荷の両端の電位差を測定することにより出力電圧Ｖｏを検出することができる。なお、抵抗３２に対する抵抗３１の抵抗値比は、例えば数十倍とすればよい。抵抗３４に対する抵抗３３の抵抗値比も同様である。例えば、抵抗３１および抵抗３３の値をそれぞれ４９３ｋΩ、抵抗３２および抵抗３４の値をそれぞれ１０ｋΩとする。 Thus, the output voltage Vo can be detected by measuring the potential difference between both ends of the output load with the input power source IP side as the reference potential. Note that the resistance value ratio of the resistor 31 to the resistor 32 may be several tens of times, for example. The resistance value ratio of the resistor 33 to the resistor 34 is the same. For example, the value of the resistor 31 and the resistor 33 is 493 kΩ, and the value of the resistor 32 and the resistor 34 is 10 kΩ.
　出力電圧検出回路３０が測定すべき出力電圧Ｖｏは４００Ｖ程度であるが、基準電位から見たときの出力負荷ＯＬのスイッチＱ１側の電圧は５００Ｖ程度となり、スイッチＱ２側の電圧は１００Ｖ程度となる。この場合でも、差動増幅器３５の反転入力は１Ｖ程度、非反転入力は０．２Ｖ程度の電圧となるので、差動増幅器３５の入力電圧を低くすることができる。カットオフ周波数も２０Ｈｚ程度に対応できればよい。 The output voltage Vo to be measured by the output voltage detection circuit 30 is about 400V, but when viewed from the reference potential, the voltage on the switch Q1 side of the output load OL is about 500V, and the voltage on the switch Q2 side is about 100V. . Even in this case, the inverting input of the differential amplifier 35 is about 1V, and the non-inverting input is about 0.2V. Therefore, the input voltage of the differential amplifier 35 can be lowered. The cut-off frequency only needs to correspond to about 20 Hz.
　なお、本発明は、その主旨または主要な特徴から逸脱することなく、他のいろいろな形で実施することができる。そのため、上述の実施形態はあらゆる点で単なる例示にすぎず、限定的に解釈してはならない。本発明の範囲は特許請求の範囲によって示すものであって、明細書本文にはなんら拘束されない。さらに、特許請求の範囲の均等範囲に属する変形や変更は、全て本発明の範囲内のものである。 It should be noted that the present invention can be implemented in various other forms without departing from the spirit or main features thereof. Therefore, the above-mentioned embodiment is only a mere illustration in all points, and should not be interpreted limitedly. The scope of the present invention is indicated by the claims, and is not restricted by the text of the specification. Further, all modifications and changes belonging to the equivalent scope of the claims are within the scope of the present invention.
　この出願は、日本で２０１７年３月２１日に出願された特願２０１７－０５４６２６号に基づく優先権を請求する。その内容はこれに言及することにより、本出願に組み込まれるものである。また、本明細書に引用された文献は、これに言及することにより、その全部が具体的に組み込まれるものである。 This application claims priority based on Japanese Patent Application No. 2017-054626 filed on March 21, 2017 in Japan. The contents of which are hereby incorporated by reference into this application. In addition, the documents cited in the present specification are specifically incorporated in their entirety by referring to them.
　本発明は、例えば、ＡＣ－ＤＣコンバータや電源装置などに好適である。 The present invention is suitable for, for example, an AC-DC converter and a power supply device.
１００　　　ブリッジレスＰＦＣ回路
１０　　　　入力電圧検出回路
１１、１２　抵抗
２０　　　　インダクタ電流検出回路
２２～２５　抵抗
２６　　　　コンデンサ
２７　　　　差動増幅器
３０　　　　出力電圧検出回路
３１～３４　抵抗
３５　　　　差動増幅器
Ｃ　　　　　電流平滑コンデンサ
Ｄ１、Ｄ２　整流素子
ＩＰ　　　　入力電源
Ｌ　　　　　昇圧インダクタ
ＯＬ　　　　出力負荷
Ｑ１、Ｑ２　スイッチ
Ｖin　　　　入力電圧
Ｖｏ　　　　出力電圧 100 bridgeless PFC circuit 10 input voltage detection circuit 11, 12 resistor 20 inductor current detection circuit 22-25 resistor 26 capacitor 27 differential amplifier 30 output voltage detection circuit 31-34 resistor 35 differential amplifier C current smoothing capacitor D1, D2 rectification Element IP Input power supply L Boost inductor OL Output load Q1, Q2 Switch Vin Input voltage Vo Output voltage

Claims (4)

  1. 　交流の入力電源からのエネルギーを蓄積して、低圧高電流から高圧低電流に変換する昇圧インダクタと、
    　この昇圧インダクタに断続的にエネルギーを蓄積するためのスイッチング動作を行うスイッチング素子と、
    　このスイッチング素子からの電流の逆流を防止する整流素子と、
    　前記昇圧インダクタより出力されたエネルギーを平滑化する平滑コンデンサと、
    　前記昇圧インダクタを流れるインダクタ電流の経路に挿入された電流検出素子によって前記インダクタ電流を検出するインダクタ電流検出回路と、
    　前記入力電源の一方側を基準電位として入力電圧を検出する入力電圧検出回路と、
    　負荷への出力電圧を前記入力電源の前記一方側を基準電位として検出する出力電圧検出回路と、
    　前記インダクタ電流検出回路によるインダクタ電流検出結果と、前記入力電圧検出回路による入力電圧検出結果と、前記出力電圧検出回路による出力電圧検出結果とに基づいて前記スイッチング動作を制御する制御部とを備えることを特徴とするブリッジレス力率改善回路。     A boost inductor that accumulates energy from an AC input power source and converts low voltage high current to high voltage low current;
    A switching element that performs a switching operation for intermittently storing energy in the boost inductor;
    A rectifying element that prevents backflow of current from the switching element;
    A smoothing capacitor for smoothing the energy output from the boost inductor;
    An inductor current detection circuit for detecting the inductor current by a current detection element inserted in a path of an inductor current flowing through the boost inductor;
    An input voltage detection circuit for detecting an input voltage using one side of the input power supply as a reference potential;
    An output voltage detection circuit for detecting an output voltage to a load using the one side of the input power supply as a reference potential;
    A control unit that controls the switching operation based on an inductor current detection result by the inductor current detection circuit, an input voltage detection result by the input voltage detection circuit, and an output voltage detection result by the output voltage detection circuit; Bridgeless power factor correction circuit.
  2. 　請求項１に記載のブリッジレス力率改善回路において、
    　前記出力電圧検出回路は、抵抗および差動増幅器で構成されていることを特徴とするブリッジレス力率改善回路。     The bridgeless power factor correction circuit according to claim 1,
    The bridgeless power factor correction circuit, wherein the output voltage detection circuit is composed of a resistor and a differential amplifier.
  3. 　請求項１に記載のブリッジレス力率改善回路において、
    　前記電流検出素子はいずれかの一端が前記基準電位に接続されており、
    　前記インダクタ電流検出回路は、前記入力電源の一方側を基準電位として前記電流検出素子の両端の電圧を測定することにより前記インダクタ電流を検出することを特徴とするブリッジレス力率改善回路。     The bridgeless power factor correction circuit according to claim 1,
    One end of the current detection element is connected to the reference potential,
    The bridgeless power factor correction circuit, wherein the inductor current detection circuit detects the inductor current by measuring a voltage across the current detection element with one side of the input power supply as a reference potential.
  4. 　トーテムポール・ブリッジレス力率改善回路であることを特徴とする、請求項１～３のいずれか１項に記載のブリッジレス力率改善回路。 The bridgeless power factor correction circuit according to any one of claims 1 to 3, wherein the bridgeless power factor correction circuit is a totem pole / bridgeless power factor correction circuit.
PCT/JP2017/041704 2017-03-21 2017-11-20 Bridgeless power factor correction circuit WO2018173364A1 (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
JP2017-054626 2017-03-21
JP2017054626A JP2018157727A (en) 2017-03-21 2017-03-21 Bridgeless power factor correction circuit

Publications (1)

Publication Number Publication Date
WO2018173364A1 true WO2018173364A1 (en) 2018-09-27

Family

ID=63586338

Family Applications (1)

Application Number Title Priority Date Filing Date
PCT/JP2017/041704 WO2018173364A1 (en) 2017-03-21 2017-11-20 Bridgeless power factor correction circuit

Country Status (2)

Country Link
JP (1) JP2018157727A (en)
WO (1) WO2018173364A1 (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111856116A (en) * 2020-07-21 2020-10-30 广州金升阳科技有限公司 Bridgeless PFC current sampling circuit and application thereof

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110165883B (en) * 2019-06-21 2022-03-04 海信（广东）空调有限公司 Bridgeless PFC circuit and frequency conversion product
CN110212749B (en) * 2019-06-21 2022-03-04 海信（广东）空调有限公司 PFC module
JP7471948B2 (en) 2020-08-03 2024-04-22 東芝テック株式会社 Power Conversion Equipment

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2012019637A (en) * 2010-07-08 2012-01-26 Fujitsu Ltd Voltage dividing power factor improvement circuit, voltage dividing power factor improvement device, and voltage dividing power factor improvement method
JP2016152655A (en) * 2015-02-16 2016-08-22 東芝テック株式会社 Power conversion device
US9590494B1 (en) * 2014-07-17 2017-03-07 Transphorm Inc. Bridgeless power factor correction circuits

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2012019637A (en) * 2010-07-08 2012-01-26 Fujitsu Ltd Voltage dividing power factor improvement circuit, voltage dividing power factor improvement device, and voltage dividing power factor improvement method
US9590494B1 (en) * 2014-07-17 2017-03-07 Transphorm Inc. Bridgeless power factor correction circuits
JP2016152655A (en) * 2015-02-16 2016-08-22 東芝テック株式会社 Power conversion device

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN111856116A (en) * 2020-07-21 2020-10-30 广州金升阳科技有限公司 Bridgeless PFC current sampling circuit and application thereof

Also Published As

Publication number Publication date
JP2018157727A (en) 2018-10-04

Similar Documents

Publication Publication Date Title
JP5182375B2 (en) PFC converter
WO2018173364A1 (en) Bridgeless power factor correction circuit
US8953347B2 (en) Capacitor discharging circuit and power converter
US7630221B2 (en) Bridgeless PFC circuit for CRM and controlling method thereof
US9742264B2 (en) Boost inductor demagnetization detection for bridgeless boost PFC converter operating in boundary-conduction mode
TWI384736B (en) Bridgeless pfc circuit system having current sensing circuit and method thereof
KR100829121B1 (en) Single Stage Power Factor Correction Circuit by Boundary Conduction Mode
KR20170120592A (en) Semiconductor device for power control
TWI439021B (en) Switch control circuit and control method for bridgeless switching circuit, power converter and power control method
US9917503B2 (en) Overcurrent protection circuit and power factor correction circuit comprising the same
US9923455B2 (en) Current-sensing and gain-switching circuit and method for using wide range of current
TWI508423B (en) Power conversion device
WO2016086897A1 (en) Current zero-crossing detection circuit and method, and load voltage detection circuit and method
JP6607495B2 (en) Power converter
JP2014042433A (en) Bridgeless pfc converter with average current mode control
TWI408898B (en) Compensation device for synchronous rectifier control and method thereof
TW202007059A (en) Hybrid-mode boost power factor corrector
CN109088536B (en) Active power factor correction circuit and method for improving harmonic waves and driving system
JP2009033959A (en) Power supply changeover unit controlled by sampling coil voltage
JP6022883B2 (en) Power supply
KR20130084199A (en) Single power stage power factor correction circuit
JP2012175828A (en) Current detection circuit of step-up converter
JP5912726B2 (en) Synchronous rectifier bridge
JP2016189666A (en) Power supply circuit for driving surface discharge element
US9606565B2 (en) Power supply with a switch converter

Legal Events

Date Code Title Description
121 Ep: the epo has been informed by wipo that ep was designated in this application

Ref document number: 17902046

Country of ref document: EP

Kind code of ref document: A1

NENP Non-entry into the national phase

Ref country code: DE

122 Ep: pct application non-entry in european phase

Ref document number: 17902046

Country of ref document: EP

Kind code of ref document: A1