WO2018133605A1 - 一种升压型pfc变换器的软开关控制电路 - Google Patents

一种升压型pfc变换器的软开关控制电路 Download PDF

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Publication number
WO2018133605A1
WO2018133605A1 PCT/CN2017/116941 CN2017116941W WO2018133605A1 WO 2018133605 A1 WO2018133605 A1 WO 2018133605A1 CN 2017116941 W CN2017116941 W CN 2017116941W WO 2018133605 A1 WO2018133605 A1 WO 2018133605A1
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Prior art keywords
circuit
signal
control circuit
pfc converter
main switch
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PCT/CN2017/116941
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English (en)
French (fr)
Inventor
真齐辉
底青云
杨全民
Original Assignee
中国科学院地质与地球物理研究所
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Priority claimed from CN201710052071.XA external-priority patent/CN106787863B/zh
Priority claimed from CN201710048525.6A external-priority patent/CN106787676B/zh
Application filed by 中国科学院地质与地球物理研究所 filed Critical 中国科学院地质与地球物理研究所
Priority to US15/993,630 priority Critical patent/US10186957B2/en
Publication of WO2018133605A1 publication Critical patent/WO2018133605A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4233—Arrangements for improving power factor of AC input using a bridge converter comprising active switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H02M1/34—Snubber circuits
    • H02M1/342—Active non-dissipative snubbers
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention belongs to the technical field of converters, and in particular relates to a soft switch control circuit of a step-up PFC converter.
  • the three-phase six-switch Boost type PFC (Power Factor Correction) converter works in the current continuous mode, so the input inductor current and the switching current stress are relatively small, the voltage stress of the switching device is small, and the converter efficiency is high.
  • the six-tube Boost PFC converter has the advantages of good input current waveform quality and stable output voltage.
  • the main topology is shown in Figure 1. It includes three bridge arms, each of which includes an inductor, two switch tubes, and A diode in parallel with the switching transistor is provided with a capacitor and a resistor at the output.
  • the reverse recovery current of the hard switch and the diode of the switch tube in FIG. 1 brings many problems, which limits the increase of the switching frequency of the converter, and generates a large electromagnetic interference.
  • the composite active clamp ZVS three-phase Boost type PFC converter has certain advantages due to its simple structure. As shown in FIG. 2, it adds an auxiliary switch S7 and a capacitor, a diode and an inductor electrically connected thereto.
  • the converter shown in FIG. 2 is implemented by an improved space vector modulation method which divides a power frequency input period into 12 sectors, that is, divides the conventional space vector modulation method into Each of the six sectors is further divided into two, forming twelve. Two basic vectors and zero vectors are given in accordance with the method of space vector modulation, by controlling the time of three vectors. Modulation is now performed so that the three-phase input current vector is rotated in a circular trajectory.
  • the control algorithm of the three-phase Boost PFC converter is complicated by the improved SVM space vector modulation method.
  • the technical problem to be solved by the present invention is to provide a control circuit for a step-up type PFC converter, which can reduce cost, and has simple control, and the technology is easily popularized.
  • a technical solution adopted by the present invention is to provide a control circuit of a step-up PFC converter, which is a three-phase six-switch converter including six main switch tubes and one auxiliary switch tube.
  • the control circuit includes:
  • a main switch control circuit for outputting a driving signal of the main switch by a single cycle control algorithm to drive two of the main switch tubes;
  • a auxiliary switch control circuit configured to provide a reset signal to the main switch control circuit to control the main switch control circuit to control the main switch tube, and further, the auxiliary switch control circuit further outputs a auxiliary switch tube Driving a signal to control the auxiliary switch tube.
  • the auxiliary switch control circuit includes a first control unit and a second control unit, wherein: the first control unit includes a first branch and a second branch, wherein the first branch receives a clock signal, and outputs a driving signal of the auxiliary switch according to the clock signal, where The two branches receive the clock signal and output a reset initial signal according to the clock signal; the second control unit receives the reset initial signal, and outputs a reset signal according to the reset initial signal.
  • the clock signal and the drive signal are mutually inverted signals.
  • the first branch includes a NOT circuit, the input of the NOT circuit receives the clock signal, and the output terminal inverts the clock signal to obtain the drive signal.
  • the second branch includes a resistor, a capacitor, and an AND circuit, wherein: one end of the resistor receives the clock signal, and the other end electrically connects one end of the capacitor and one of the AND circuit An input terminal; the other end of the capacitor is grounded; the other input terminal of the AND circuit receives the clock signal, and an output of the AND circuit outputs a reset initial signal.
  • the timing of the drive signal and the reset signal is set according to a resonance time of a bridge arm voltage of the converter.
  • the second control unit after outputting the driving signal to drive the auxiliary switch to be turned off, the second control unit outputs the reset signal drive after the bridge voltage resonates to zero.
  • the main switch tube of the bridge arm after outputting the driving signal to drive the auxiliary switch to be turned off, the second control unit outputs the reset signal drive after the bridge voltage resonates to zero.
  • the frequency of the clock signal is the same as the frequency of the reset signal, and the reset signal has a time shift from the rising edge of the reset signal compared with the clock signal, and the falling edge has a time shift, changing The duty cycle.
  • the duty cycle of the clock signal is greater than 10% and the duty cycle of the reset signal is less than 5%.
  • the second control unit includes a first AND gate circuit and a second AND gate circuit, a NOT gate circuit, a resistor, and a capacitor, wherein: one end of the resistor receives the reset initial signal, and the other end of the resistor is electrically connected to one end of the capacitor and one input of the first AND gate circuit The other end of the first AND gate circuit receives the reset initial signal, and the output terminal is electrically connected to the input end of the NOT circuit; the second AND gate circuit An input receives the reset initial signal, another input is electrically coupled to an output of the NOT circuit, and an output of the second AND gate outputs the reset signal.
  • the present invention also provides a control circuit of a boost type PFC converter, which is a three-phase six-switch boost type PFC converter including six main switch tubes and one auxiliary
  • the switch tube and the control circuit include:
  • the interval selection circuit divides the input voltage signal into six intervals at intervals of 60° phase for selecting the required two current absolute value signals
  • Two comparison circuits are configured to compare the current comparison signal with the two current combined signals to obtain two pulse width modulated signals
  • the interval selection circuit selects two pulse width modulation signals as the drive signals of the main switch tube to drive two of the main switch tubes of the converter.
  • the invention has the beneficial effects that the soft switch control circuit of the boost type PFC converter is provided, and the boost type PFC converter is a three-phase six-switch boost type PFC converter, which is different from the prior art.
  • the utility model comprises six main switch tubes and one auxiliary switch tube, and the control circuit comprises a main switch control circuit for outputting a driving signal of the main switch tube by a single cycle control algorithm to drive two of the main switch tubes; a switch control circuit, configured to provide a reset signal to the main switch control circuit to control the main switch control circuit to control the main switch tube, and further, the auxiliary switch control circuit further outputs a drive of the auxiliary switch tube a signal to control the auxiliary switch tube.
  • the present invention provides a control circuit for a step-up PFC converter, the converter is a three-phase six-switch converter comprising six main switch tubes and one auxiliary switch tube, the control circuit comprising: an interval selection circuit, For selecting two required current absolute value signals; an integrating circuit for acquiring a current comparison signal; and two combining circuits for cross-merging the two current absolute value signals to obtain two current combined signals; a circuit comparison circuit for comparing the current comparison signal with the two current combined signals to obtain two pulse width modulated signals; the interval selecting circuit selecting two pulse width modulated signals as the main switch driving signals to drive the converter Two of the main switch tubes. Therefore, the present invention can reduce the cost, and the control is simple, and the technology is easily popularized.
  • FIG. 1 is a schematic structural view of a prior art converter
  • FIG. 2 is a schematic structural view of a three-phase six-switch boost type PFC converter having a soft switching function
  • FIG. 3 is a schematic structural diagram of a control circuit of a converter according to an embodiment of the present invention.
  • FIG. 4 is a schematic structural view of the auxiliary switch tube control circuit shown in FIG. 3;
  • Figure 5 is a waveform diagram of an input phase voltage and an input phase current
  • Fig. 6 is a waveform diagram of ZVS of the main switching tube and the auxiliary switching tube.
  • FIG. 2 is a schematic structural diagram of a three-phase six-switch converter
  • FIG. 3 is a schematic structural diagram of a control circuit of a boost type PFC converter according to an embodiment of the present invention.
  • the three-phase six-switch converter includes three parallel bridge arm circuits 21-23 and an auxiliary circuit 24.
  • the auxiliary circuit 24 is disposed between the bridge arm circuit and the output terminal.
  • Each bridge arm circuit includes an inductor, two switching tubes, two diodes, and two capacitors.
  • the bridge arm circuit 21 includes an inductor La, switching transistors S1 and S2, diodes V1 and V2, and capacitors C1 and C2.
  • the one end of the inductor La receives the voltage signal Va, and the other end is electrically connected to the emitter of the switch S1 and the collector of the switch S2, respectively.
  • the bases of the switches S1 and S2 receive the drive signals A1 and A2, respectively, and the collectors of the switch S1 are electrically connected to the bridge circuits 22 and 23 and the auxiliary circuit 24.
  • the emitter of the switching transistor S2 is electrically connected to the bridge arm circuits 22 and 23.
  • Diodes V1 and V2 are connected in parallel with switching transistors S1 and S2, respectively, and capacitors C1 and C2 are connected in parallel with switching transistors S1 and S2, respectively.
  • connection manners of the other bridge arm circuits 22 and 23 are the same as those of the bridge arm circuit 21, and will not be described herein.
  • An auxiliary circuit 24 is provided between the bridge arm circuit and the output terminal.
  • Auxiliary circuit 24 includes inductor Lr, electricity Capacitor Cr and C7, diode V7 and switch S7.
  • the one end of the inductor Lr is electrically connected to the bridge arm circuit, and the other end is electrically connected to the output end.
  • the emitter and the collector of the switch tube S7 are electrically connected to the bridge arm circuit and one end of the capacitor Cr, respectively, and the base receives the drive signal A7.
  • the other end of the capacitor Cr is electrically connected to the output terminal.
  • Capacitor C7 and diode V7 are connected in parallel with switch S7, respectively.
  • the switch tube S1-S6 is the main switch tube
  • the switch tube S7 is the auxiliary switch tube.
  • control circuit 30 includes a main switch control circuit 31 and a sub-switch control circuit 32.
  • the main switch control circuit 31 is configured to output a driving signal of the main switch by a single cycle control algorithm to drive two of the main switch tubes.
  • the auxiliary switch control circuit 32 is configured to provide a reset signal to the main switch control circuit 31 to control the main switch control circuit 31 to control the main switch tube. Further, the auxiliary switch control circuit 32 further outputs the drive signal A7 of the auxiliary switch tube to The auxiliary switch tube S7 is controlled.
  • the auxiliary switch control circuit 32 in this embodiment is a clock circuit.
  • the main switch control circuit 31 includes an interval selection circuit 311, an integration circuit 312, a merging circuit 313, and a comparison circuit 314.
  • the interval selection circuit 311 is used to select two required current absolute value signals.
  • the control circuit 30 further includes a sensor (not shown), a rectifier circuit (not shown), and a multi-channel analog switch 315.
  • the current of the converter is first acquired by the sensor, specifically, the three-phase currents ia, ib and ic of the converter are obtained.
  • the rectifier circuit then rectifies the three-phase current of the converter to obtain a current absolute value signal.
  • the sensor is preferably a Hall sensor.
  • the multiplexed analog switch 315 receives the current absolute value signals ia, -ia, ib, -ib, ic, and -ic, and receives the selection signal of the interval selection circuit 311 to select the desired two current absolute value signals.
  • the integration circuit 312 is used to acquire a current comparison signal.
  • the control circuit 30 further includes a voltage isolation collector (not shown), a comparator 316, and a regulator 317.
  • the voltage isolation collector is used to obtain the DC voltage V0.
  • the voltage isolation collector is preferably an isolated voltage isolation collector.
  • the comparator 316 is for comparing the DC voltage V0 with the reference voltage Vref to obtain an error signal.
  • Regulator 317 is used to adjust a control signal based on the error signal.
  • the integrating circuit 312 acquires a current comparison signal based on the control signal.
  • the current comparison signal is a sawtooth signal.
  • the integrating circuit 312 of this embodiment is a resettable integrating circuit.
  • the integration circuit 312 includes an integration resistor 3121, an integration capacitor 3122, a reset switch 3123, an integration comparator 3124, and an integrator 3125.
  • the one end of the integrating resistor 3121 is electrically connected to the output end of the regulator 317 and an input end of the integrator 3125.
  • the other end of the integrating resistor 3121 is electrically connected to the integrating capacitor 3122 and one end of the reset switch 3123 and an input end of the comparator 3124, respectively. .
  • the other input of the comparator 3124 is grounded, and the output of the comparator 3124 is electrically coupled to the other input of the integrator 3125 and to the other end of the reset switch 3123 and the integrating capacitor 3122.
  • the control terminal of the reset switch 3123 receives a reset signal.
  • the merging circuit 313 is two paths, respectively 3131 and 3132, for cross-merging the two current absolute value signals to obtain two current combining signals.
  • the comparison circuit 314 is two paths, respectively 3141 and 3142, for comparing the current comparison signal with the two current combined signals to obtain two pulse width modulated signals.
  • the interval selection circuit 311 selects two pulse width modulation signals as drive signals for the main switching transistor to drive two of the main switching transistors of the converter.
  • control circuit 30 further includes a filter 318, also two paths, 3181 and 3182, respectively, for filtering the two current absolute signals, respectively.
  • the filter 318 is a low pass filter.
  • control circuit 10 further includes a flip flop 319 and an output logic circuit 320.
  • the flip-flop 319 is two paths, respectively 3191 and 3192, for respectively outputting a pulse width modulation signal according to the reset signal.
  • the output logic circuit 320 is configured to receive the pulse width modulation signal and receive the selection signal of the interval selection circuit 311, and output any two of the drive signals A1-A6 to drive two of the main switch tubes of the converter. The remaining 4 main switches are kept off. Among them, the driving signals A1-A6 drive the switching tubes S1-S6, respectively.
  • the structure of the main switch control circuit 31 is described above, and the structure of the sub-switch control circuit 32 will be described below. Please refer to Figure 4 together.
  • the auxiliary switch control circuit 32 includes a first control unit 321 and a second control unit 322.
  • the first control unit 321 includes a first branch 3211 and a second branch 3212, wherein the first branch 3211 receives the clock signal, and outputs a driving signal A7 of the auxiliary switch according to the clock signal, and the second branch 3212 receives the clock.
  • the signal is output and the initial signal is reset according to the clock signal output.
  • the clock signal and the driving signal A7 are mutually inverted signals.
  • the first branch circuit 3211 includes a NOT gate circuit 3213.
  • the input terminal of the NOT gate circuit 3213 receives the clock signal, and the output terminal inverts the clock signal to obtain the drive signal A7.
  • the second branch 3212 includes a resistor 3214, a capacitor 3215, and an AND circuit 3216.
  • One end of the resistor 3214 receives a clock signal, and the other end is electrically connected to one end of the capacitor 3215 and an input terminal of the AND circuit 3216.
  • the other end of the capacitor 3215 is grounded.
  • the other input of the AND circuit 3216 receives the clock signal, and the output of the AND circuit 3216 outputs the reset initial signal.
  • the second control unit 322 receives the reset initial signal and outputs a reset signal according to the reset initial signal.
  • the second control unit 322 includes two AND gate circuits 3221 and 3222, and one NOT gate circuit 3223.
  • a resistor 3224 and a capacitor 3225 One end of the resistor 3224 receives a reset initial signal, and the other end of the resistor 3224 is electrically connected to one end of the capacitor 3225 and one of the input terminals of the AND circuit 3221.
  • the other end of the capacitor 3225 is grounded.
  • the other input of the AND circuit 3221 receives a reset initial signal, and the output is electrically coupled to the input of the NOT circuit 3223.
  • An input of the AND circuit 3222 receives a reset initial signal, the other input is electrically coupled to an output of the NOT circuit 3223, and an output of the AND circuit 3222 outputs a reset signal.
  • the timing of the drive signal and the reset signal is set according to the resonance time of the bridge arm voltage of the converter.
  • the second control unit 322 After outputting the driving signal to drive the auxiliary switch S7 to be turned off, the second control unit 322 outputs a reset signal to drive the main switch of the bridge arm when the bridge arm voltage resonates to zero.
  • the frequency of the clock signal is the same as the frequency of the reset signal.
  • the reset signal has a time shift from the rising edge of the reset signal, and the falling edge has a time shift, which changes the duty ratio.
  • the duty cycle of the clock signal is greater than 10% and the duty cycle of the reset signal is less than 5%.
  • the soft switching function of the boost type PFC converter can be realized by the above control circuit, and in order to verify the correctness of the present invention, please refer to FIG. Va, Vb, and Vc are three-phase input phase voltage amplitudes, set to 170V input, output voltage is set to 500V, clock frequency is 10KHz, boost inductor is set to 0.5mH, capacitors C1 to C7 are set to 10nF, and resonant inductor Lr is set to 50uH.
  • the clamp capacitor Cr is set to 480uF
  • the load R is set to 10 ⁇ (25KW output)
  • the support capacitor C is set to 1000uF.
  • the waveforms of the input phase voltages Va, Vb, and Vc and the input phase currents ia, ib, and ic are as shown in FIG.
  • the input power factor of the converter is close to 1, the phase current waveform is sinusoidal, and substantially follows the phase voltage waveform.
  • the ZVS (Zero Voltage Switch) of the main switch tube and the auxiliary switch tube of this embodiment is implemented as shown in FIG. 6.
  • the long dashed line moment shown in Figure 6 is the opening time of the main switch tube, which is turned on after the dc-link drops to zero, realizing zero voltage turn-on, and the short dashed line moment is the turn-on time of the auxiliary switch tube.
  • the voltage across the auxiliary light-emitting tube S7 drops to zero, it is turned on, and the purpose of zero-voltage turn-on is also realized.
  • the main switch tube and the auxiliary switch tube are connected in parallel with one capacitor, it can be considered that the switch tube is zero-voltage-off. (The capacitor voltage cannot be abruptly changed and charging time is required). Therefore, the system realizes the soft switching operation of all the switching tubes.
  • the present invention can realize the soft switching function of the converter through a simple circuit, the cost is low, and the control is simple, and the technology is easily popularized.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种升压型PFC变换器的软开关控制电路，升压型PFC变换器为三相六开关升压型PFC变换器，其包括六个主开关管（S1-S6）和一个辅开关管（S7），控制电路（30）包括主开关控制电路（31），用于通过单周期控制算法输出主开关管（S1-S6）的驱动信号，以驱动其中两个主开关管；辅开关控制电路（32），用于提供复位信号给主开关控制电路（31），以控制主开关控制电路（31）对主开关管（S1-S6）的控制，进一步的，辅开关控制电路（32）还输出辅开关管（S7）的驱动信号，以对辅开关管（S7）进行控制。其中，主开关控制电路（31）包括区间选择电路（311）、积分电路（312）、合并电路（313）以及比较电路（314）。因此能够降低成本，并且控制简单，技术极易推广。

Description

一种升压型PFC变换器的软开关控制电路 技术领域
本发明属于变换器技术领域，尤其涉及一种升压型PFC变换器的软开关控制电路。
背景技术
三相六开关Boost型PFC(Power Factor Correction，功率因数校正)变换器工作在电流连续模式下，因此输入电感电流和开关电流应力比较小，开关器件的电压应力小，变换器效率较高，三相六管Boost型PFC变换器具有输入电流波形质量好，输出电压稳定的优点，其主要拓扑如图1所示，其包括三个桥臂，每一桥臂包括一个电感、两个开关管以及与开关管并联的二极管，在输出端设置一电容和电阻。但是图1中的开关管的硬开关与二极管的反向恢复电流带来很多问题，限制了变换器开关频率的提高，产生很大的电磁干扰等。
现有技术中，为了解决上述问题，在图1的电路上加入一些辅助电路，实现开关管的软开关工作同时抑制二极管的反向恢复问题。如图2所示为基于复合有源箝位ZVS三相Boost型PFC变换器，其由于结构简单而具有一定的优势。如图2所示，其加入了辅助开关管S7及与之电连接的电容、二极管以及电感。
当前，对图2所示的变换器是通过改进的空间矢量调制方法来实现，该改进型空间矢量调制方法把一个工频输入周期分成12个扇区，也就是把传统的空间矢量调制方法分成6个扇区中的每一个扇区再分成两个，形成12个。在按照空间矢量调制的方法给出两个基本矢量和零矢量，通过控制三个矢量的时间来实 现调制，从而实现三相输入电流矢量按照一个圆轨迹进行旋转。
现有技术的控制方法存在以下缺点：
1、通过改进的SVM空间矢量调制方法来实现三相Boost型PFC变换器控制算法复杂。
2、通过智能芯片(DSP、MCU)来实现，需要各种外围资源配合程序的开发来实现，开发周期长。
3、控制器的成本高。
4、相关理论比较抽象，晦涩。
5、技术不易普及推广。
发明内容
本发明主要解决的技术问题是提供一种升压型PFC变换器的控制电路，能够降低成本，并且控制简单，技术极易推广。
为解决上述技术问题，本发明采用的一个技术方案是：提供一种升压型PFC变换器的控制电路，变换器为三相六开关变换器，其包括六个主开关管和一个辅开关管，该控制电路包括：
主开关控制电路，用于通过单周期控制算法输出主开关管的驱动信号，以驱动其中两个主开关管；
辅开关控制电路，用于提供复位信号给所述主开关控制电路，以控制所述主开关控制电路对所述主开关管的控制，进一步的，所述辅开关控制电路还输出辅开关管的驱动信号，以对所述辅开关管进行控制。
在其中一个实施例中，辅开关控制电路包括第一控制单元和第二控制单元， 其中：所述第一控制单元包括第一支路和第二支路，其中，所述第一支路接收时钟信号，并根据所述时钟信号输出所述辅开关管的驱动信号，所述第二支路接收时钟信号，并根据所述时钟信号输出复位初始信号；所述第二控制单元接收所述复位初始信号，并根据所述复位初始信号输出复位信号。
在其中一个实施例中，时钟信号和所述驱动信号互为反相信号。
在其中一个实施例中，第一支路包括一非门电路，所述非门电路的输入端接收所述时钟信号，输出端对所述时钟信号进行反相，得到所述驱动信号。
在其中一个实施例中，第二支路包括电阻、电容以及与门电路，其中：所述电阻的一端接收所述时钟信号，另一端电连接所述电容的一端以及所述与门电路的一输入端；所述电容的另一端接地；所述与门电路的另一输入端接收所述时钟信号，所述与门电路的输出端输出复位初始信号。
在其中一个实施例中，根据所述变换器的桥臂电压的谐振时间来设置所述驱动信号与所述复位信号的时间。
在其中一个实施例中，第一控制单元在输出所述驱动信号来驱动所述辅开关管关闭后，在所述桥臂电压谐振到零时，第二控制单元再输出所述复位信号驱动所述桥臂的主开关管。
在其中一个实施例中，时钟信号的频率与所述复位信号的频率相同，复位信号与时钟信号相比，复位信号的上升沿往后有一个时移，下降沿往前有一个时移，改变了占空比。
在其中一个实施例中，时钟信号的占空比大于10％，复位信号的占空比小于5％。
在其中一个实施例中，第二控制单元包括第一与门电路和第二与门电路、 一个非门电路、一个电阻以及一个电容，其中：所述电阻的一端接收所述复位初始信号，所述电阻的另一端电连接所述电容的一端以及所述第一与门电路的其中一输入端；所述电容的另一端接地；所述第一与门电路的另一输入端接收所述复位初始信号，输出端电连接所述非门电路的输入端；所述第二与门电路的一输入端接收所述复位初始信号，另一输入端与所述非门电路的输出端电连接，所述第二与门电路的输出端输出所述复位信号。
另一方面，本发明还提供一种升压型PFC变换器的控制电路，所述升压型PFC变换器为三相六开关升压型PFC变换器，其包括六个主开关管和一个辅开关管，控制电路包括：
区间选择电路，把输入电压信号以60°相位为间隔分成6个区间，用于选择所需的两个电流绝对值信号；
积分电路，用于获取一个电流比较信号；
两路合并电路，用于将两个电流绝对值信号进行交叉合并，得到两个电流合并信号；
两路比较电路，用于将电流比较信号分别与两个电流合并信号进行比较，以得到两个脉宽调制信号；
区间选择电路选择两个脉宽调制信号作为主开关管的驱动信号，以驱动变换器的其中两个主开关管。
本发明的有益效果在于：区别于现有技术的情况，本发明提供一种升压型PFC变换器的软开关控制电路，升压型PFC变换器为三相六开关升压型PFC变换器，其包括六个主开关管和一个辅开关管，控制电路包括主开关控制电路，用于通过单周期控制算法输出主开关管的驱动信号，以驱动其中两个主开关管；辅 开关控制电路，用于提供复位信号给所述主开关控制电路，以控制所述主开关控制电路对所述主开关管的控制，进一步的，所述辅开关控制电路还输出辅开关管的驱动信号，以对所述辅开关管进行控制。
进一步地，本发明提供一种升压型PFC变换器的控制电路，变换器为三相六开关变换器，其包括六个主开关管和一个辅开关管，该控制电路包括：区间选择电路，用于选择所需的两个电流绝对值信号；积分电路，用于获取一个电流比较信号；两路合并电路，用于将两个电流绝对值信号进行交叉合并，得到两个电流合并信号；两路比较电路，用于将电流比较信号分别与两个电流合并信号进行比较，以得到两个脉宽调制信号；区间选择电路选择两个脉宽调制信号作为主开关驱动信号，以驱动变换器的其中两个主开关管。因此，本发明能够降低成本，并且控制简单，技术极易推广。
附图说明
为了更清楚地说明本申请实施例或现有技术中的技术方案，下面将对实施例或现有技术描述中所需要使用的附图作简单地介绍，显而易见地，下面描述中的附图仅仅是本申请的一些实施例，对于本领域普通技术人员来讲，在不付出创造性劳动的前提下，还可以根据这些附图获得其他的附图。
图1是现有技术的变换器的结构示意图；
图2是具有软开关功能的三相六开关升压型PFC变换器的结构示意图；
图3是本发明实施例提供的一种变换器的控制电路的结构示意图；
图4是图3所示的辅开关管控制电路的结构示意图；
图5是输入相电压和输入相电流的波形图；
图6是主开关管与辅助开关管的ZVS的波形图。
具体实施方式
为使本发明实施例的目的、技术方案和优点更加清楚，下面将结合本发明实施例中的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有做出创造性劳动的前提下所获得的所有其他实施例，都属于本发明保护的范围。
请参阅图2和图3，图2是三相六开关变换器的结构示意图，图3是本发明实施例提供的一种升压型PFC变换器的控制电路的结构示意图。首先如图2所示，三相六开关变换器包括三个并联的桥臂电路21-23以及一个辅助电路24。其中，辅助电路24设置在桥臂电路与输出端之间。每一个桥臂电路包括一电感、两个开关管、两个二极管以及两个电容。如桥臂电路21包括电感La、开关管S1和S2、二极管V1和V2以及电容C1和C2。其中，电感La的一端接收电压信号Va、另一端分别电连接开关管S1的发射极以及开关管S2的集电极。开关管S1和S2的基极分别接收驱动信号A1和A2，开关管S1的集电极电连接桥臂电路22和23以及辅助电路24。开关管S2的发射极电连接桥臂电路22和23。二极管V1和V2分别与开关管S1和S2并联，电容C1和C2分别与开关管S1和S2并联。
同理，其他桥臂电路22和23的连接方式如桥臂电路21的相同，在此不再赘述。
在桥臂电路和输出端之间设置辅助电路24。辅助电路24包括电感Lr、电 容Cr和C7、二极管V7以及开关管S7。其中，电感Lr一端与桥臂电路电连接，另一端与输出端电连接，开关管S7的发射极和集电极分别与桥臂电路和电容Cr的一端电连接，基极接收驱动信号A7。电容Cr的另一端与输出端电连接。电容C7和二极管V7分别与开关管S7并联。
其中，开关管S1-S6为主开关管，开关管S7为辅开关管。
再如图3所示，控制电路30包括主开关控制电路31以及辅开关控制电路32。
其中，主开关控制电路31用于通过单周期控制算法输出主开关管的驱动信号，以驱动其中两个主开关管。
辅开关控制电路32用于提供复位信号给主开关控制电路31，以控制主开关控制电路31对主开关管的控制，进一步的，辅开关控制电路32进一步输出辅开关管的驱动信号A7，以对辅开关管S7进行控制。本实施例中的辅开关控制电路32是一个时钟电路。
本实施例中，主开关控制电路31包括区间选择电路311、积分电路312、合并电路313以及比较电路314。
其中，区间选择电路311用于选择所需的两个电流绝对值信号。具体的，控制电路30进一步包括传感器(图未示出)、整流电路(图未示出)以及多路模拟开关315。本实施例首先通过传感器获取变换器的电流，具体是获取变换器的三相电流ia、ib以及ic。然后整流电路将变换器的三相电流进行整流，以获得电流绝对值信号。这样，当电流为正的时候，电流波形不变，电流为负的时候，输出为电流信号极性取反，如图3中的正负相电流ia、-ia、ib、-ib、ic以及-ic的输入。其中，传感器优选为霍尔传感器。
多路模拟开关315接收电流绝对值信号ia、-ia、ib、-ib、ic以及-ic，并接收区间选择电路311的选择信号，以选择出所需的两个电流绝对值信号。
积分电路312用于获取一个电流比较信号。
具体的，控制电路30还包括电压隔离采集器(图未示)、比较器316以及调节器317。其中，电压隔离采集器用于获取直流电压V0。电压隔离采集器优选为隔离电压隔离采集器。比较器316用于将直流电压V0和参考电压Vref进行比较，以获取一个误差信号。调节器317用于根据误差信号调节出一个控制信号。积分电路312根据控制信号获取一个电流比较信号。该电流比较信号为锯齿波信号。
本实施例的积分电路312为可复位积分电路。具体而言，积分电路312包括积分电阻3121、积分电容3122、复位开关3123、积分比较器3124以及积分器3125。其中，积分电阻3121的一端电连接调节器317的输出端以及积分器3125的一输入端，积分电阻3121的另一端分别电连接积分电容3122以及复位开关3123的一端以及比较器3124的一输入端。比较器3124的另一输入端接地，比较器3124的输出端电连接积分器3125的另一输入端以及复位开关3123和积分电容3122的另一端。复位开关3123的控制端接收复位信号。
合并电路313为两路，分别为3131和3132，用于将两个电流绝对值信号进行交叉合并，得到两个电流合并信号。
比较电路314为两路，分别为3141和3142，用于将电流比较信号分别与两个电流合并信号进行比较，以得到两个脉宽调制信号。
区间选择电路311选择两个脉宽调制信号作为主开关管的驱动信号，以驱动变换器的其中两个主开关管。
进一步，控制电路30还包括滤波器318，同样为两路，分别为3181和3182，其用于分别对两个电流绝对信号进行滤波。其中，滤波器318为低通滤波器。
进一步，控制电路10还包括触发器319以及输出逻辑电路320。其中，触发器319为两路，分别为3191和3192，用于分别根据复位信号来输出脉宽调制信号。输出逻辑电路320用于接收脉宽调制信号，并接收区间选择电路311的选择信号，输出驱动信号A1-A6的任意两个，以驱动变换器的其中两个主开关管。其余的4个主开关管保存关闭状态。其中，驱动信号A1-A6分别驱动开关管S1-S6。
以上介绍的是主开关控制电路31的结构，以下将介绍辅开关控制电路32的结构。请一并参阅图4。
如图4所示，辅开关控制电路32包括第一控制单元321和第二控制单元322。其中，第一控制单元321包括第一支路3211和第二支路3212，其中第一支路3211接收时钟信号，并根据时钟信号输出辅开关管的驱动信号A7，第二支路3212接收时钟信号，并根据时钟信号输出复位初始信号。其中，时钟信号和驱动信号A7互为反相信号。
第一支路3211包括一非门电路3213，非门电路3213的输入端接收时钟信号，输出端对时钟信号进行反相，得到驱动信号A7。
第二支路3212包括电阻3214、电容3215以及与门电路3216，其中，电阻3214的一端接收时钟信号，另一端电连接电容3215的一端以及与门电路3216的一输入端。电容3215的另一端接地。与门电路3216的另一输入端接收时钟信号，与门电路3216的输出端输出复位初始信号。
第二控制单元322接收复位初始信号，并根据复位初始信号输出复位信号。具体的，第二控制单元322包括两个与门电路3221和3222、一个非门电路3223、 一个电阻3224以及一个电容3225。其中，电阻3224的一端接收复位初始信号，电阻3224的另一端电连接电容3225的一端以及与门电路3221的其中一输入端。电容3225的另一端接地。与门电路3221的另一输入端接收复位初始信号，输出端电连接非门电路3223的输入端。与门电路3222的一输入端接收复位初始信号，另一输入端与非门电路3223的输出端电连接，与门电路3222的输出端输出复位信号。
本实施例中，根据变换器的桥臂电压的谐振时间来设置驱动信号与复位信号的时间。第二控制单元322在输出驱动信号来驱动辅助开关管S7关闭后，在桥臂电压谐振到零时，再输出复位信号驱动桥臂的主开关管。
其中，时钟信号的频率与复位信号的频率相同。但复位信号与时钟信号相比，复位信号的上升沿往后有一个时移，下降沿往前有一个时移，改变了占空比。时钟信号的占空比大于10％，复位信号的占空比小于5％。
通过上述的控制电路，可以实现升压型PFC变换器的软开关功能，为了验证本发明的正确性，请再参阅图2所示。Va、Vb以及Vc为三相输入相电压幅度，设置成170V输入，输出电压设置500V，时钟频率为10KHz，升压电感设置为0.5mH，电容C1～C7设置为10nF，谐振电感Lr设置为50uH，钳位电容Cr设置为480uF，负载R设置为10Ω(25KW输出)，支撑电容C设置成1000uF。则输入相电压Va、Vb以及Vc和输入相电流ia、ib以及ic的波形如图5所示。变换器的输入功率因数接近1，相电流波形正弦化，并基本跟随相电压波形。
本实施例的主开关管与辅助开关管的ZVS(Zero Voltage Switch，零电压开关)实现如图6所示。图6所示的长虚线时刻是主开关管开通时刻，是在dc-link下降到零后才打开，实现了零电压开通，短虚线时刻是辅助开关管开通时刻，是 在辅助开光管S7两端电压下降到零的时候才打开，也实现了零电压开通的目的，由于主开关管和辅助开关管都并联了一个电容，所以可以认为开关管是零电压关断的(电容电压不能突变，需要有充电时间)，因此，该系统实现了所有开关管的软开关工作。
综上，本发明通过简单的电路就能实现变换器的软开关功能，成本低，并且控制简单，技术极易推广。
以上仅为本发明的实施例，并非因此限制本发明的专利范围，凡是利用本发明说明书及附图内容所作的等效结构或等效流程变换以及基于单周期控制的等效辅助开关驱动方法，或直接或间接运用在其他相关的技术领域，均同理包括在本发明的专利保护范围内。
最后应说明的是：以上各实施例仅用以说明本发明的技术方案，而非对其限制；尽管参照前述各实施例对本发明进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分或者全部技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本发明各实施例技术方案的范围。

Claims (11)

  1. 一种升压型PFC变换器的软开关控制电路，所述升压型PFC变换器为三相六开关升压型PFC变换器，其包括六个主开关管和一个辅开关管，其特征在于，所述控制电路包括：
    主开关控制电路，用于通过单周期控制算法输出主开关管的驱动信号，以驱动其中两个主开关管；
    时钟电路，用于提供复位信号给所述主开关控制电路，以控制所述主开关控制电路对所述主开关管的控制，进一步的，所述时钟电路还输出辅开关管的驱动信号，以对所述辅开关管进行控制。
  2. 根据权利要求1所述的升压型PFC变换器的软开关控制电路，其特征在于，所述时钟电路包括第一控制单元和第二控制单元，其中：
    所述第一控制单元包括第一支路和第二支路，其中，所述第一支路接收时钟信号，并根据所述时钟信号输出所述辅开关管的驱动信号，所述第二支路接收时钟信号，并根据所述时钟信号输出复位初始信号；
    所述第二控制单元接收所述复位初始信号，并根据所述复位初始信号输出复位信号。
  3. 根据权利要求2所述的升压型PFC变换器的软开关控制电路，其特征在于，所述时钟信号和所述驱动信号互为反相信号。
  4. 根据权利要求2或3所述的升压型PFC变换器的软开关控制电路，其特征在于，第一支路包括一非门电路，所述非门电路的输入端接收所述时钟信号，输出端对所述时钟信号进行反相，得到所述驱动信号。
  5. 根据权利要求2或3所述的升压型PFC变换器的软开关控制电路，其特征在于，所述第二支路包括电阻、电容以及与门电路，其中：
    所述电阻的一端接收所述时钟信号，另一端电连接所述电容的一端以及所述与门电路的一输入端；
    所述电容的另一端接地；
    所述与门电路的另一输入端接收所述时钟信号，所述与门电路的输出端输出复位初始信号。
  6. 根据权利要求1所述的升压型PFC变换器的软开关控制电路，其特征在于，根据所述变换器的桥臂电压的谐振时间来设置所述驱动信号与所述复位信号的时间。
  7. 根据权利要求2所述的升压型PFC变换器的软开关控制电路，其特征在于，第一控制单元在输出所述驱动信号来驱动所述辅开关管关闭后，在所述桥臂电压谐振到零时，第二控制单元再输出所述复位信号驱动所述桥臂的主开关管。
  8. 根据权利要求2所述的升压型PFC变换器的软开关控制电路，其特征在于，时钟信号的频率与所述复位信号的频率相同，但复位信号与时钟信号相比， 复位信号的上升沿往后有一个时移，下降沿往前有一个时移，改变了占空比。
  9. 根据权利要求2所述的升压型PFC变换器的软开关控制电路，其特征在于，时钟信号的占空比大于10％，复位信号的占空比小于5％以下。
  10. 根据权利要求2所述的升压型PFC变换器的软开关控制电路，其特征在于，所述第二控制单元包括第一与门电路和第二与门电路、一个非门电路、一个电阻以及一个电容，其中：
    所述电阻的一端接收所述复位初始信号，所述电阻的另一端电连接所述电容的一端以及所述第一与门电路的其中一输入端；
    所述电容的另一端接地；
    所述第一与门电路的另一输入端接收所述复位初始信号，输出端电连接所述非门电路的输入端；
    所述第二与门电路的一输入端接收所述复位初始信号，另一输入端与所述非门电路的输出端电连接，所述第二与门电路的输出端输出所述复位信号。
  11. 一种升压型PFC变换器的控制电路，所述升压型PFC变换器为三相六开关升压型PFC变换器，其包括六个主开关管和一个辅开关管，其特征在于，控制电路利用单周期控制方法来实现，包括：
    区间选择电路，把输入电压信号以60°相位为间隔分成6个区间，用于选择所需的两个电流绝对值信号；
    积分电路，用于获取一个电流比较信号；
    两路合并电路，用于将两个电流绝对值信号进行交叉合并，得到两个电流合并信号；
    两路比较电路，用于将电流比较信号分别与两个电流合并信号进行比较，以得到两个脉宽调制信号；
    区间选择电路选择两个脉宽调制信号作为主开关管的驱动信号，以驱动变换器的其中两个主开关管。
PCT/CN2017/116941 2017-01-20 2017-12-18 一种升压型pfc变换器的软开关控制电路 WO2018133605A1 (zh)

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Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1564447A (zh) * 2004-04-13 2005-01-12 浙江大学 复合有源箝位三相交流－直流功率因数校正变换器
US20090273330A1 (en) * 2008-04-30 2009-11-05 International Rectifier Corporation Merged ramp/oscillator for precise ramp control in one cycle pfc converter
CN202034915U (zh) * 2011-03-31 2011-11-09 武汉诚锐电器有限公司 一种输入宽范围连续可调的有源软开关无桥pfc变换器
CN203151389U (zh) * 2013-04-11 2013-08-21 安徽工业大学 一种三相高功率因数整流器的控制电路
CN106787863A (zh) * 2017-01-20 2017-05-31 中国科学院地质与地球物理研究所 一种升压型pfc变换器的控制电路
CN106787676A (zh) * 2017-01-20 2017-05-31 中国科学院地质与地球物理研究所 一种升压型pfc变换器的软开关控制电路

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4864483A (en) * 1986-09-25 1989-09-05 Wisconsin Alumni Research Foundation Static power conversion method and apparatus having essentially zero switching losses and clamped voltage levels
DE112009004353B4 (de) * 2009-01-13 2019-08-22 Mitsubishi Electric Corporation Stromumwandlungsvorrichtung
US8687388B2 (en) * 2012-01-31 2014-04-01 Delta Electronics, Inc. Three-phase soft-switched PFC rectifiers
US20160049892A1 (en) * 2014-08-18 2016-02-18 Baker Hughes Incorporated Systems and Methods for Variable Speed Drives
CN105471263B (zh) * 2015-12-23 2018-05-29 成都芯源系统有限公司 升降压变换器及其控制器和控制方法

Patent Citations (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN1564447A (zh) * 2004-04-13 2005-01-12 浙江大学 复合有源箝位三相交流－直流功率因数校正变换器
US20090273330A1 (en) * 2008-04-30 2009-11-05 International Rectifier Corporation Merged ramp/oscillator for precise ramp control in one cycle pfc converter
CN202034915U (zh) * 2011-03-31 2011-11-09 武汉诚锐电器有限公司 一种输入宽范围连续可调的有源软开关无桥pfc变换器
CN203151389U (zh) * 2013-04-11 2013-08-21 安徽工业大学 一种三相高功率因数整流器的控制电路
CN106787863A (zh) * 2017-01-20 2017-05-31 中国科学院地质与地球物理研究所 一种升压型pfc变换器的控制电路
CN106787676A (zh) * 2017-01-20 2017-05-31 中国科学院地质与地球物理研究所 一种升压型pfc变换器的软开关控制电路

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