WO2018077230A1 - 一种输出高压llc谐振变换器 - Google Patents

一种输出高压llc谐振变换器 Download PDF

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Publication number
WO2018077230A1
WO2018077230A1 PCT/CN2017/107984 CN2017107984W WO2018077230A1 WO 2018077230 A1 WO2018077230 A1 WO 2018077230A1 CN 2017107984 W CN2017107984 W CN 2017107984W WO 2018077230 A1 WO2018077230 A1 WO 2018077230A1
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Prior art keywords
diode
circuit
transformer
bridge
resonant converter
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PCT/CN2017/107984
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English (en)
French (fr)
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柏建国
邓礼宽
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深圳市优优绿能电气有限公司
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Publication of WO2018077230A1 publication Critical patent/WO2018077230A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • the present invention relates to the field of power electronics, and in particular to an output high voltage LLC resonant converter.
  • the working principle block diagram of the DC LLC resonant converter is shown in Figure 1, including: switching network, resonant cavity circuit, rectifier circuit, filter circuit and load Ro.
  • the switch network may be an asymmetric half bridge circuit, a symmetric half bridge circuit, a full bridge circuit, a three-level half bridge circuit, a three-level full bridge circuit, and the like.
  • the transformer T1 and the diodes D1, D2, D3, and D4 constitute a full-bridge rectifier circuit.
  • the DC output voltage is higher than 600V, only the diode above 600V can be used. Since the diode above 600V is not as good as the diode below 600V in price and performance, the cost performance of the product is reduced and it is not competitive.
  • the invention provides an output high-voltage LLC resonant converter, which comprises: a switch network, a resonant cavity circuit, a rectifier circuit and a filter circuit.
  • the switch network is connected to both ends of the input voltage, and the two ends of the filter circuit are connected to the load.
  • the resonant cavity circuit includes a resonant inductor, a magnetizing inductance, and a resonant capacitor connected in series;
  • the rectifier circuit includes a first full bridge rectifier circuit and a second full bridge rectifier circuit, and the first full bridge rectifier circuit includes a first transformer and a first diode a second diode, a third diode, and a fourth diode; wherein the first diode, the second diode, the third diode, and the fourth diode are connected in series;
  • One end of the primary side of the first transformer is connected between the resonant inductor and the magnetizing inductance, and the other end is connected between the exciting inductor and the resonant capacitor, and one end of the secondary side of the first transformer is connected to the first diode and the second diode
  • the other end of the first transformer secondary side is connected between the third diode and the fourth diode;
  • the second full bridge rectifier circuit includes a second transformer, a fifth diode, a sixth diode, a seventh diode, and an eighth diode; wherein the fifth diode, the sixth diode, and the seventh The diode and the eighth diode are connected in series with the positive and negative poles; one end of the primary side of the second transformer is connected between the resonant inductor and the magnetizing inductance, and the other end is connected between the exciting inductor and the resonant capacitor, and the second transformer secondary side One end is connected between the fifth diode and the sixth diode, and the other end of the second transformer secondary side is connected between the seventh diode and the eighth diode.
  • the first full bridge rectifier circuit further includes a third transformer, the third transformer is connected in series with the primary winding of the first transformer, and the secondary winding is connected in parallel;
  • the second full bridge rectifier circuit further includes a fourth transformer, a fourth transformer and a second The primary winding of the transformer is connected in series and the secondary windings are connected in parallel.
  • Figure 1 is a block diagram of the working principle of a DC LLC resonant converter.
  • FIG. 2 is a circuit diagram of an asymmetric half-bridge LLC resonant converter.
  • FIG. 3 is a circuit diagram of an output high voltage LLC resonant converter proposed by the present invention.
  • FIG. 4 is a circuit diagram of an asymmetric half-bridge LLC resonant converter proposed by the present invention.
  • FIG. 5 is a circuit diagram of a symmetric half-bridge LLC resonant converter proposed by the present invention.
  • FIG. 6 is a circuit diagram of a full-bridge LLC resonant converter proposed by the present invention.
  • FIG. 7 is a circuit diagram of a three-level symmetric half-bridge LLC resonant converter proposed by the present invention.
  • FIG. 8 is a circuit diagram of a three-level full-bridge LLC resonant converter proposed by the present invention.
  • FIG. 9 is a diagram of a full bridge interleaved LLC resonant circuit proposed based on the connection mode of FIG. 3.
  • FIG. 9 is a diagram of a full bridge interleaved LLC resonant circuit proposed based on the connection mode of FIG. 3.
  • FIG. 10 is a resonant circuit diagram of three full-bridge rectified series connected outputs based on the connection mode of FIG. 3.
  • FIG. 10 is a resonant circuit diagram of three full-bridge rectified series connected outputs based on the connection mode of FIG. 3.
  • Fig. 11 is a circuit diagram showing an output high voltage LLC resonance circuit of the transformer based on the connection mode of Fig. 3.
  • Figure 12 is a circuit diagram of a full-bridge LLC resonant converter based on the connection of Figure 11;
  • Figure 13 is a circuit diagram of a three-level symmetric half-bridge LLC resonant converter based on the connection of Figure 11;
  • Figure 14 is a circuit diagram of a three-level full-bridge LLC resonant converter based on the connection of Figure 11;
  • Figure 15 is a circuit diagram of a full bridge interleaved LLC resonant converter based on the connection of Figure 11;
  • Figure 16 is a circuit diagram showing another similar connection of Figure 11.
  • Figure 17 is a circuit diagram of a full-bridge LLC resonant converter based on the connection of Figure 16;
  • Figure 18 is a circuit diagram of a full bridge interleaved LLC resonant converter based on the connection of Figure 16;
  • Figure 19 is a circuit diagram of a hybrid application full-bridge LLC resonant converter.
  • Figure 20 is a schematic diagram of the operation of the full-bridge LLC resonant converter circuit.
  • FIG. 21 is a simulation waveform diagram of FIG. 20.
  • a new output high-voltage LLC resonant converter as shown in FIG. 3, comprises: a switch network, a resonant cavity circuit, a rectifier circuit and a filter circuit, wherein the switch network is connected to both ends of the input voltage, and the filter circuit is Connect the load to the end.
  • the invention is special in the connection mode of the resonant cavity circuit and the rectifying circuit, wherein: Lr1, Lm1 and Cr1 together constitute three key resonant components of the LLC resonant converter, Lr1 is a resonant inductor, and Lm1 is a magnetizing inductance (Lm1 can be separate Inductive components can also be magnetically integrated with T1 and T2.
  • Cr1 is a resonant capacitor; T1 and T2 are transformers; D1, D2, D3, D4, D5, D6, D7, and D8 are secondary rectifier diodes.
  • Transformer T1 and diodes D1, D2, D3, and D4 form a full-bridge rectification
  • transformer T2 and diodes D5, D6, D7, and D8 form a full-bridge rectification.
  • the full bridge composed of D1, D2, D3, and D4 is connected in series with the full bridge composed of D5, D6, D7, and D8.
  • the advantage of this scheme is that the full bridge composed of D1, D2, D3 and D4 and the full bridge composed of D5, D6, D7 and D8 solve the output high voltage problem in series, and the other two transformers are equally divided in power, and the heat dissipation is better.
  • the input Vin+ and Vin- of Figure 3 are switching networks.
  • the switching network can be composed of the following circuits: asymmetric half-bridge circuit, symmetric half-bridge circuit, full-bridge circuit, three-level symmetric half-bridge circuit, three-level full-bridge circuit, etc. .
  • the output Vo+ and Vo- of Figure 3 are connected to a filter circuit.
  • the filter circuit can be a capacitor or other circuit, and the back end of the filter circuit is connected to the load.
  • Figure 4 is an embodiment of an asymmetric half-bridge LLC resonant converter
  • Figure 5 is a schematic embodiment of a symmetric half-bridge LLC resonant converter
  • Figure 6 is a full bridge LLC resonant converter implementation
  • Figure 7 is a three-level symmetric half-bridge LLC resonant converter implementation
  • Figure 8 is a three-level full-bridge LLC resonant converter implementation
  • the outstanding advantage of the scheme of Figure 9 is that the two full-bridge inputs are respectively connected to two capacitors C1 and C2 connected in series to the input voltage source Uin such that the two full bridges are connected in series on the input side; on the output side D1, D2, D3,
  • the full-bridge rectification consisting of D4 is connected in series with the full-bridge rectification consisting of D5, D6, D7, and D8, and then full-bridge rectification consisting of D9, D10, D11, and D12 and full-bridge rectification consisting of D13, D14, D15, and D16 Parallel;
  • the drive waveforms of the switch tubes S1, S2, S3, S4 and S5, S6, S7, S8 are respectively staggered by 90 degrees; by staggered parallel connection, the ripple voltage and ripple current on the output capacitor Co can be greatly reduced, thereby reducing Small converter volume increases power density.
  • transformers T1 and T2 in Figure 3 can not meet the high power requirements, a new connection scheme can be introduced on the basis of Figure 3.
  • the newly added transformer T3 and the original T1 primary winding are connected in series.
  • the side windings are connected in parallel.
  • the newly added transformer T4 and the original T2 primary winding are connected in series, and the secondary windings are connected in parallel.
  • FIG. 10 is a resonant circuit diagram of three full-bridge rectified series connected outputs based on the connection mode of FIG. 3.
  • FIG. Lr1, Lm1, Cr1, T1, T2, T3 form a resonant cavity circuit, in which transformers T1, T2, T3 are connected in parallel with Lm1; full bridges composed of D1, D2, D3, and D4 and full bridges composed of D5, D6, D7, and D8
  • the series is connected in series with the full bridges composed of D9, D10, D11 and D12 to form a rectifier circuit. If a higher output voltage is required, the transformer can be extended to more than three or more in a manner similar to that of FIG. 3 and FIG. 10, and the output rectifier bridge is extended to more than three or more, which is also within the scope of this patent. .
  • FIG 11 is only to expand the transformers T1 and T4 into two transformers T1, T3 and T2, T4, respectively, of course, the expansion of the transformers T1 and T4 into three or more respectively is also within the scope of this patent protection Inside.
  • the inputs Vin+ and Vin- of FIG. 11 may be an asymmetric half bridge circuit, a symmetric half bridge circuit, a full bridge circuit, a three-level symmetric half bridge circuit, a three-level full bridge circuit, or the like.
  • the outputs Vo+ and Vo- of Figure 11 can be connected to capacitors and loads.
  • the specific embodiment based on Figure 11 is as follows:
  • Figure 12 is an embodiment of a full bridge LLC resonant converter based on the connection of Figure 11;
  • Figure 13 is a three-level symmetric half-bridge LLC resonant converter implementation based on the connection of Figure 11;
  • Figure 14 is a three-level full-bridge LLC resonant converter implementation based on the connection of Figure 11;
  • Figure 15 is an embodiment of a full bridge interleaved LLC resonant converter based on the connection of Figure 11; other embodiments than the embodiment of Figures 12-16 are also within the scope of this patent.
  • Figure 16 is another similar connection of Figure 11 and is also within the scope of this patent.
  • Figure 16 is the transformer T1 and T3 primary side series, T1 secondary side connected to the full bridge rectifier D1, D2, D3, D4, T3 secondary side connected full bridge rectifier D9, D10, D11, D12, full bridge rectifier D1, D2, D3, D4 is connected in parallel with full-bridge rectifiers D9, D10, D11, and D12, and T2 and T4 are connected in the same manner as diodes D5, D6, D7, D8, and D13, D14, D15, and D16.
  • the inputs Vin+ and Vin- of Figure 16 may be asymmetric half bridge circuits, symmetric half bridge circuits, full bridge circuits, three level symmetric half bridge circuits, three level full bridge circuits, and the like.
  • the outputs Vo+ and Vo- of Figure 16 can be connected to capacitors and loads.
  • the specific embodiment based on Figure 16 is as follows:
  • Figure 17 is a diagram of a full-bridge LLC resonant converter implementation based on the connection of Figure 16;
  • Figure 18 is an embodiment of a full bridge interleaved LLC resonant converter based on the connection of Figure 16; other embodiments than the embodiment of Figures 17 and 18 are also within the scope of this patent.
  • Figure 19 is an embodiment of a novel hybrid application full bridge LLC resonant converter.
  • S1, S2, S3, and S4 form a full-bridge switching network
  • Lr1, Lm1, Cr1, T1, and T2 form a resonant cavity circuit
  • D1, D2 The full bridge composed of D3 and D4 is connected in series with the full bridge composed of D5, D6, D7 and D8 to form a rectifier circuit
  • Co is a filter circuit
  • Ro is a load.
  • Figure 21 is the simulation waveform of Figure 20, the simulation parameters are designed as follows: input Uin is 400Vdc; capacitor C1 is 810uF; resonant inductor Lr1 is 16uH; magnetizing inductance Lm1 is 60uH; resonant capacitor Cr1 is 72nF; transformers T1 and T2 are the same, ratio Both are 32:38; the capacitance Co is 250uF; the load Ro is 75 ohms.
  • G1, G2, G3, and G4 are driving waveforms of the switching tubes S1, S2, S3, and S4, respectively;
  • ILr1 is a current waveform of the resonant inductor Lr1;
  • ILm1 is a current waveform of the exciting inductor Lm1;
  • Vo is the end of the load Ro.
  • VD1, VD4, VD5, and VD8 are voltage waveforms across rectifier diodes D1, D4, D5, and D8, respectively.
  • the diode D1 voltage waveform VD1
  • the diode D5 voltage waveform VD5
  • VD8 voltage waveform
  • VD8 also divides the output voltage Vo even during operation, so that the output diodes D1, D2, D3, D4, D5, D6, D7, and D8 can use ultra-fast recovery diodes of 600V or less.

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Abstract

一种输出高压LLC谐振变换器，包括开关网络、谐振腔电路、整流电路以及滤波电路四部分，其中，开关网络连接输入电压（Uin）的两端，滤波电路的两端连接负载。当该谐振变换器工作在较高工作频率，且输出工作电压高于600V时，通过谐振腔电路的多个变压器（T1，T2）原边并联，副边分别连接两个整流桥电路，并将两个整流桥电路串联，解决了输出二极管的电压应力问题，同时提高了产品的功率密度，降低了产品成本。

Description

一种输出高压LLC谐振变换器 技术领域
本发明涉及电力电子技术领域，特别是涉及一种输出高压LLC谐振变换器。
背景技术
电动化是汽车未来发展的必然趋势，而充电桩又是电动汽车普及的必要条件。电动汽车续航里程是限制其发展的关键因素，基于目前锂电池技术，提高续航里程的简单方法便是不断提高电动汽车锂电池的串联电压，根据国标：“GB/T 18487.1-2015电动汽车传导充电系统第1部分：通用要求”中的4.4要求直流充电电压最高950V。充电模块是充电桩核心部件，主要功能是将交流电转换成电动汽车锂电池需要的隔离直流电。经过多年发展，充电模块的高效率、高功率密度成为行业主流。由于LLC直流谐振变换器拓扑工作在较高的开关频率条件下仍然具备很高的转换效率，已成为充电模块直流变换器的首选拓扑。
直流LLC谐振变换器工作原理框图如图1所示，包括：开关网络、谐振腔电路、整流电路、滤波电路和负载Ro。其中：开关网络可以是不对称半桥电路、对称半桥电路、全桥电路、三电平半桥电路、三电平全桥电路等。
图2为不对称半桥LLC谐振变换器，变压器T1和二极管D1、D2、D3、D4构成全桥整流电路。该拓扑当直流输出电压高于600V时，只能使用600V以上的二极管，由于600V以上的二极管在价格和性能上都不如600V以下的二极管，使得产品性价比下降，没有竞争力。
发明内容
本发明提供了一种输出高压LLC谐振变换器，其包括：开关网络、谐振腔电路、整流电路以及滤波电路四部分，其中，开关网络连接输入电压的两端，滤波电路的两端连接负载。
其中，谐振腔电路包括串联连接的谐振电感、励磁电感以及谐振电容；整流电路包括第一全桥整流电路以及第二全桥整流电路，第一全桥整流电路包括第一变压器、第一二极管、第二二极管、第三二极管以及第四二极管；其中第一二极管、第二二极管、第三二极管以及第四二极管正负极依次串联；第一变压器的原边的一端连接在谐振电感与励磁电感之间、另一端连接在励磁电感与谐振电容之间，第一变压器副边的一端连接至第一二极管与第二二极管之间、第一变压器副边的另一端连接至第三二极管与第四二极管之间；
第二全桥整流电路包括第二变压器、第五二极管、第六二极管、第七二极管以及第八二极管；其中第五二极管、第六二极管、第七二极管以及第八二极管正负极依次串联；第二变压器的原边的一端连接在谐振电感与励磁电感之间、另一端连接在励磁电感与谐振电容之间，第二变压器副边的一端连接至第五二极管与第六二极管之间、第二变压器副边的另一端连接至第七二极管与第八二极管之间。
进一步地，第一全桥整流电路还包括第三变压器，第三变压器与第一变压器原边绕组串联、副边绕组并联；第二全桥整流电路还包括第四变压器，第四变压器与第二变压器原边绕组串联、副边绕组并联。
附图说明
图1为直流LLC谐振变换器工作原理框图。
图2为不对称半桥LLC谐振变换器的电路图。
图3为本发明提出的输出高压LLC谐振变换器电路图。
图4为本发明提出的不对称半桥LLC谐振变换器的电路图；
图5为本发明提出的对称半桥LLC谐振变换器的电路图；
图6为本发明提出的全桥LLC谐振变换器的电路图；
图7为本发明提出的三电平对称半桥LLC谐振变换器的电路图；
图8为本发明提出的三电平全桥LLC谐振变换器的电路图；
图9为基于图3连接方式提出的全桥交错并联LLC谐振电路图。
图10为基于图3连接方式扩展的输出三个全桥整流串联的谐振电路图。
图11为基于图3连接方式增加变压器的输出高压LLC谐振电路图。
图12为基于图11连接方式的全桥LLC谐振变换器的电路图；
图13为基于图11连接方式的三电平对称半桥LLC谐振变换器的电路图；
图14为基于图11连接方式的三电平全桥LLC谐振变换器的电路图；
图15为基于图11连接方式的全桥交错LLC谐振变换器的电路图；
图16为是图11的另外一种类似的连接方式的电路图。
图17为基于图16连接方式的全桥LLC谐振变换器的电路图；
图18为基于图16连接方式的全桥交错LLC谐振变换器的电路图；
图19为混合应用全桥LLC谐振变换器的电路图。
图20为全桥LLC谐振变换器电路工作示意图。
图21为图20的仿真波形图。
具体实施方式
下面结合附图和具体实施例对本发明作进一步的说明。本发明提出 一种新的输出高压LLC谐振变换器，如图3所示，其包括：开关网络、谐振腔电路、整流电路以及滤波电路四部分，其中，开关网络连接输入电压的两端，滤波电路的两端连接负载。本发明特别之处在于谐振腔电路与整流电路的连接方式，其中：Lr1、Lm1和Cr1共同组成LLC谐振变换器三个关键的谐振元件，Lr1为谐振电感，Lm1为励磁电感(Lm1可以是单独电感元件，也可以与T1和T2进行磁集成)，Cr1为谐振电容；T1和T2为变压器；D1、D2、D3、D4、D5、D6、D7、D8为副边整流二极管。变压器T1与二极管D1、D2、D3、D4组成全桥整流，变压器T2与二极管D5、D6、D7、D8组成全桥整流。D1、D2、D3、D4组成的全桥与D5、D6、D7、D8组成的全桥串联。这种方案的优点是：D1、D2、D3、D4组成的全桥与D5、D6、D7、D8组成的全桥串联解决输出高压问题，另外两个变压器功率均分，散热也会更好。
图3的输入Vin+和Vin-是开关网络，开关网络可以有如下电路组成：不对称半桥电路、对称半桥电路、全桥电路、三电平对称半桥电路、三电平全桥电路等。图3的输出Vo+和Vo-连接滤波电路，滤波电路可以是电容或其他电路，滤波电路后端连接负载。
基于图3的具体实施方案如下所示：
图4为不对称半桥LLC谐振变换器实施方案；
图5为对称半桥LLC谐振变换器实施方案；
图6为全桥LLC谐振变换器实施方案；
图7为三电平对称半桥LLC谐振变换器实施方案；
图8为三电平全桥LLC谐振变换器实施方案；
除图4-8实施方案外，其他使用图3连接方式的实施方案也在本专 利保护范围内。
这里特别提出的是基于图3连接方式推出全新的全桥交错并联LLC谐振电路,具体实施方案见图9所示。
图9方案突出优点是:两个全桥输入分别连接到串联在输入电压源Uin的两个电容C1和C2两侧，这样两个全桥在输入侧串联；在输出侧D1、D2、D3、D4组成的全桥整流与D5、D6、D7、D8组成的全桥整流串联后，再与D9、D10、D11、D12组成的全桥整流与D13、D14、D15、D16组成的全桥整流交错并联；开关管S1、S2、S3、S4与S5、S6、S7、S8的驱动波形分别交错90度；通过交错并联，可以大大减小输出电容Co上的纹波电压和纹波电流，进而减小变换器体积，提高功率密度。如果图3中变压器T1和T2不能满足大功率要求，可以在图3基础上推出新的连接方案图11，也在本专利保护范围内，新增加变压器T3和原有T1原边绕组串联，副边绕组并联。同样新增加变压器T4和原有T2原边绕组串联，副边绕组并联。
图10为基于图3连接方式扩展的输出三个全桥整流串联的谐振电路图。Lr1、Lm1、Cr1、T1、T2、T3组成谐振腔电路，其中变压器T1、T2、T3与Lm1并联；D1、D2、D3、D4组成的全桥与D5、D6、D7、D8组成的全桥串联，再与D9、D10、D11、D12组成的全桥串联后共同组成整流电路。如果需要更高的输出电压，可以用类似图3和图10的方式将变压器扩展到3个以上或更多，输出整流桥也相应扩展到3个以上或更多，也在本专利保护范围内。
图11是只是将变压器T1和T4分别扩展为两个变压器T1、T3和T2、T4,当然将变压器T1和T4分别扩展成3个或更多也在本专利保护范围 内。
图11的输入Vin+和Vin-可以是不对称半桥电路、对称半桥电路、全桥电路、三电平对称半桥电路、三电平全桥电路等。图11的输出Vo+和Vo-可以连接电容和负载。基于图11的具体实施方案如下所示：
图12为基于图11连接方式的全桥LLC谐振变换器实施方案；
图13为基于图11连接方式的三电平对称半桥LLC谐振变换器实施方案；
图14为基于图11连接方式的三电平全桥LLC谐振变换器实施方案；
图15为基于图11连接方式的全桥交错LLC谐振变换器实施方案；除图12-16的实施方案外，其他使用图11连接方式的实施方案也在本专利保护范围内。
图16是图11的另外一种类似的连接方式，也是本专利保护范围。图16是变压器T1和T3原边串联，T1副边连接全桥整流D1、D2、D3、D4，T3副边连接全桥整流D9、D10、D11、D12，全桥整流D1、D2、D3、D4和全桥整流D9、D10、D11、D12并联，T2和T4是与二极管D5、D6、D7、D8和D13、D14、D15、D16也是同样的连接方式。
图16的输入Vin+和Vin-可以是不对称半桥电路、对称半桥电路、全桥电路、三电平对称半桥电路、三电平全桥电路等。图16的输出Vo+和Vo-可以连接电容和负载。基于图16的具体实施方案如下所示：
图17为基于图16连接方式的全桥LLC谐振变换器实施方案；
图18为基于图16连接方式的全桥交错LLC谐振变换器实施方案；除图17和18实施方案外，其他使用图16连接方式的实施方案也在本专利保护范围内。
将图11和图16两种连接方式进行混合应用也在本专利保护范围内。图19为新型混合应用全桥LLC谐振变换器实施例。
这里以图20全桥LLC谐振变换器为例，介绍本发明工作原理：S1、S2、S3、S4组成全桥开关网络；Lr1、Lm1、Cr1、T1、T2组成谐振腔电路；D1、D2、D3、D4组成的全桥与D5、D6、D7、D8组成的全桥串联，共同组成整流电路；Co为滤波电路；Ro为负载。
图21为图20的仿真波形，仿真参数设计如下：输入Uin为400Vdc；电容C1为810uF；谐振电感Lr1为16uH；励磁电感Lm1为60uH；谐振电容Cr1为72nF；变压器T1和T2相同，变比都是32:38；电容Co为250uF；负载Ro为75欧姆。
图21中：G1、G2、G3、G4分别是开关管S1、S2、S3、S4的驱动波形；ILr1是谐振电感Lr1的电流波形；ILm1是励磁电感Lm1的电流波形；Vo是负载Ro两端的电压波形；VD1、VD4、VD5、VD8分别是整流二极管D1、D4、D5、D8两端的电压波形。由仿真结果看,当输出电压为942V左右是，二极管D1(电压波形VD1)和二极管D5(电压波形VD5)工作时可以均分输出电压Vo，二极管D4(电压波形VD4)和二极管D8(电压波形VD8)工作时也均分输出电压Vo，这样输出二极管D1、D2、D3、D4、D5、D6、D7、D8就可以使用600V以下的超快恢复二极管。
本发明的上述实施例仅仅是为清楚地说明本发明所作的举例，而并非是对本发明的限定。本领域技术人员在不脱离本发明精神的前提下，可对本发明做任何的修改，而本发明的保护范围由所附的权利要求来限定。

Claims (5)

  1. 一种输出高压LLC谐振变换器，所述谐振变压器包括开关网络、谐振腔电路、整流电路以及滤波电路四部分，其中，开关网络连接输入电压的两端，滤波电路的两端连接负载；其特征在于：
    其中，谐振腔电路包括串联连接的谐振电感、励磁电感以及谐振电容；整流电路包括第一全桥整流电路以及第二全桥整流电路，第一全桥整流电路包括第一变压器、第一二极管、第二二极管、第三二极管以及第四二极管；其中第一二极管、第二二极管、第三二极管以及第四二极管正负极依次串联；第一变压器的原边的一端连接在谐振电感与励磁电感之间、另一端连接在励磁电感与谐振电容之间，第一变压器副边的一端连接至第一二极管与第二二极管之间、第一变压器副边的另一端连接至第三二极管与第四二极管之间；
    第二全桥整流电路包括第二变压器、第五二极管、第六二极管、第七二极管以及第八二极管；其中第五二极管、第六二极管、第七二极管以及第八二极管正负极依次串联；第二变压器的原边的一端连接在谐振电感与励磁电感之间、另一端连接在励磁电感与谐振电容之间，第二变压器副边的一端连接至第五二极管与第六二极管之间、第二变压器副边的另一端连接至第七二极管与第八二极管之间。
  2. 根据权利要求1所述的输出高压LLC谐振变换器，其特征在于：
    进一步地，第一全桥整流电路还包括第三变压器，第三变压器与第一变压器原边绕组串联、副边绕组并联；第二全桥整流电路还包括第四变压器，第四变压器与第二变压器原边绕组串联、副边绕组并联。
  3. 根据权利要求1所述的输出高压LLC谐振变换器，其特征在于：其中开关网络包括第一晶体管、第二晶体管、第三晶体管、第四晶体管 以及第一电容；其中，第一电容、串联连接的第一晶体管和第二晶体管以及串联连接第三晶体管和第四晶体管并联连接在输入电压的两端。
  4. 根据权利要求1所述的输出高压LLC谐振变换器，其特征在于：
    进一步地，其中开关网络可以是不对称半桥电路、对称半桥电路、全桥电路、三电平对称半桥电路、三电平全桥电路等。
  5. 根据权利要求1所述的输出高压LLC谐振变换器，其特征在于：
    其中滤波电路为输出端电容，该输出端电容与输出负载并联。
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