WO2017107452A1 - 开关稳压电源 - Google Patents

开关稳压电源 Download PDF

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Publication number
WO2017107452A1
WO2017107452A1 PCT/CN2016/089019 CN2016089019W WO2017107452A1 WO 2017107452 A1 WO2017107452 A1 WO 2017107452A1 CN 2016089019 W CN2016089019 W CN 2016089019W WO 2017107452 A1 WO2017107452 A1 WO 2017107452A1
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Prior art keywords
circuit
voltage
rectifying
power supply
pulse
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PCT/CN2016/089019
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English (en)
French (fr)
Inventor
林艺霖
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Le Holdings Beijing Co Ltd
Leshi Zhixin Electronic Technology Tianjin Co Ltd
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Le Holdings Beijing Co Ltd
Leshi Zhixin Electronic Technology Tianjin Co Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only

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  • the embodiments of the present invention relate to the field of circuit technologies, and in particular, to a switching regulator power supply.
  • the 220 volt (V) AC voltage input from the grid is unstable, and the load connected to the circuit (such as TV sets, video recorders, etc.) is also constantly changing. Therefore, it is necessary to use a regulated power supply to stabilize the load connected to the circuit.
  • the DC voltage is such that the load can work normally and stably.
  • FIG. 1 is a schematic structural view of a conventional linear regulated power supply. As shown in FIG. 1 , the first rectifying and filtering circuit, the adjusting tube, the second rectifying and filtering circuit, the load circuit, the sampling circuit and the comparison and amplifying circuit are included, wherein the input 220V AC voltage is obtained by the first rectifying and filtering circuit to obtain a DC voltage U.
  • the emitter e of the adjustment tube is connected to the first end of the second rectification filter circuit, and the second end of the second rectification filter circuit is respectively connected with the first end of the sampling circuit and the load circuit
  • the first end is connected, the second end of the load circuit is grounded, the second end of the sampling circuit is connected to the first end of the comparison amplifier circuit, and the second end of the comparison amplifier circuit is connected to the base b of the adjustment tube.
  • the comparison amplifying circuit compares and amplifies the sampling voltage U 0 input by the sampling circuit and the reference voltage U ref provided by the reference voltage source, and outputs the voltage to the base b of the adjusting tube, and controls the adjustment by controlling the voltage U b of the base b of the adjusting tube.
  • the voltage U ce between the collector c and the emitter e of the tube stabilizes the voltage U ce between the collector c and the emitter e of the adjustment tube, thereby controlling the voltage U 0 output to the load to be stable and regulating effect.
  • the prior art has at least the following disadvantages: the adjustment tube in the linear regulated power supply is always working. In the zoom-in area, that is, in the linear state, the tube is expensive and the work efficiency is low.
  • the embodiment of the present application provides a switching regulator power supply.
  • the switch tube In the voltage regulation process, the switch tube is in a saturated region or a cut-off region, that is, in a non-linear state, alternately turned on and off to reduce tube consumption and improve work efficiency.
  • the embodiment of the present application provides a switching regulator power supply, including a first rectification filter circuit, a pulse transformer, a second rectification filter circuit, a load circuit, a switch tube, and an adjustment circuit, where: the first rectification filter circuit An output end is electrically connected to a first end of the primary coil of the pulse transformer, and a first end of the secondary coil of the pulse transformer is electrically connected to an input end of the second rectifying filter circuit, a secondary of the pulse transformer The second end of the coil is grounded, and the output end of the second rectifying and filtering circuit is electrically connected to the first end of the load circuit and the first end of the adjusting circuit, respectively, and the second end of the load circuit is grounded
  • the base of the switching tube is electrically connected to the second end of the adjusting circuit, the collector of the switching tube is electrically connected to the second end of the primary coil of the pulse transformer, and the emitter of the switching tube is grounded; a first rectifying and filtering circuit for rectifying and filtering an input AC voltage to obtain
  • the adjustment circuit includes a sampling circuit, a reference voltage source, a comparison amplification circuit, a pulse width modulation circuit, and a horizontal frequency pulse circuit; and the sampling circuit is configured to sample the DC output voltage input And the comparison amplification circuit; the reference voltage source is configured to generate a reference voltage input to the comparison amplification circuit; and the comparison amplification circuit is configured to compare and amplify the DC output voltage and the reference voltage to obtain a difference voltage is input to the pulse width modulation circuit; the horizontal frequency pulse circuit is configured to generate a horizontal frequency pulse signal input to the pulse width modulation circuit; And a circuit for generating the regulated voltage input to the base of the switch tube according to the difference voltage and the horizontal frequency pulse signal.
  • the switching transistor is a metal-oxide semiconductor field effect transistor MOSFET.
  • the first rectifying and filtering circuit includes a first rectifying diode and a first capacitor; a negative end of the first rectifying diode and a first end of the primary coil of the pulse transformer, respectively The first end of the first capacitor is electrically connected, and the second end of the first capacitor is grounded.
  • the second rectifying and filtering circuit includes a second rectifying diode and a second capacitor; a positive end of the second rectifying diode is electrically connected to a first end of the secondary coil of the pulse transformer Connected, a negative end of the second rectifier diode is electrically connected to a first end of the load circuit and a first end of the second capacitor, and a second end of the second capacitor is grounded.
  • the comparison amplifying circuit includes an error amplifier.
  • the pulse width modulation circuit includes a pulse width modulation comparator.
  • the horizontal frequency pulse circuit includes a sawtooth wave generator.
  • the switch tube in the voltage regulation process, is in a saturated region or a cut-off region, that is, in a non-linear state, alternately turned on and off, which reduces tube consumption and improves work efficiency.
  • FIG. 1 is a schematic structural view of a conventional linear regulated power supply
  • FIG. 2 is a schematic structural diagram of an embodiment of a switching regulator power supply according to an embodiment of the present disclosure
  • FIG. 3 is a schematic structural diagram of still another embodiment of a switching regulator power supply according to an embodiment of the present disclosure
  • FIG. 4 is a schematic structural diagram of still another embodiment of a switching regulator power supply according to an embodiment of the present disclosure
  • FIG. 5 is a waveform diagram of an adjustment voltage U b input to a base of a switching transistor in the switching regulator power supply shown in FIG. 4;
  • FIG. 6 is a waveform diagram of a pulse transformer primary coil induced voltage U L1 in the switching regulator power supply shown in FIG. 4;
  • FIG. 7 is a waveform diagram of a pulse transformer primary coil current I L1 in the switching regulator power supply shown in FIG. 4;
  • FIG. 8 is a waveform diagram of the induced voltage U L2 of the secondary winding of the pulse transformer in the switching regulator power supply shown in FIG. 4;
  • FIG. 9 is a waveform diagram of the pulse transformer secondary coil current I L2 in the switching regulator power supply shown in FIG. 4.
  • FIG. 2 is a schematic structural diagram of an embodiment of a switching regulator power supply according to an embodiment of the present application.
  • the switching regulator power supply of the embodiment of the present application may specifically include: a first rectification and filtering circuit 21, a pulse transformer 22, a second rectification and filtering circuit 23, a load circuit 24, a switching tube 25, and an adjustment circuit 26. among them:
  • the output end of the first rectifying and filtering circuit 21 is electrically connected to the first end of the primary coil of the pulse transformer 22, and the first end of the secondary coil of the pulse transformer 22 is electrically connected to the input end of the second rectifying and filtering circuit 23, and the pulse transformer 22
  • the second end of the secondary winding is grounded, and the output end of the second rectifying and filtering circuit 23 is electrically connected to the first end of the load circuit 24 and the first end of the adjusting circuit 26, respectively, and the second end of the load circuit 24 is grounded, the switch tube
  • the base b of the 25 is electrically connected to the second end of the regulating circuit 26, the collector c of the switching transistor 25 is electrically connected to the second end of the primary winding of the pulse transformer 22, and the emitter e of the switching transistor 25 is grounded.
  • the first rectifying and filtering circuit 21 is configured to rectify and filter the input AC voltage to obtain a DC voltage U i .
  • a pulse transformer 22 and a switching transistor 25 are used to convert the DC voltage U i into a pulsed DC voltage.
  • the second rectifying and filtering circuit 23 is configured to rectify and filter the pulsed DC voltage, and obtain the DC output voltage U 0 to be input to the load circuit 24.
  • the adjusting circuit 26 is configured to generate a regulating voltage U b according to the DC output voltage U 0 and input it to the base b of the switching transistor 25 to control the on-off time of the switching transistor 25 .
  • the switching regulator power supply of the embodiment of the present application is a pulse transformer coupled parallel type switching power supply.
  • the first rectification filter circuit 21 rectifies and filters the input AC voltage (for example, an AC voltage of 220 V) to obtain a DC voltage U i and outputs it to the primary coil of the pulse transformer 22.
  • the pulse transformer 22 and the switching transistor 25 convert the DC voltage U i output from the first rectifying and filtering circuit 21 into a high-frequency rectangular pulse DC voltage and output it to the second rectifying filter circuit 23.
  • the second rectifying and filtering circuit 23 rectifies and filters the high-frequency rectangular pulse DC voltage output from the secondary coil of the pulse transformer 22 to obtain a DC output voltage U 0 and outputs it to the load circuit 24.
  • the adjusting circuit 26 generates a pulse width adjustable adjusting voltage U b according to the DC output voltage U 0 outputted by the second rectifying and filtering circuit 23, and inputs it to the base b of the switching tube 25, and controls the switching time of the switching tube 25 (ie, the switching tube) the conduction time T on and cut-off time T off) so that the stable DC output voltage U 0 of the second rectifying and filtering circuit 23 output.
  • the adjustment circuit 26 can make the pulse width (i.e., the duty ratio D) of the generated adjustment voltage high after passing through the switch tube 25.
  • the average voltage of the frequency rectangular pulse DC voltage rises, thereby increasing the voltage value of the DC output voltage U 0 and vice versa.
  • the switch tube is in a saturated region or a cut-off region, that is, in a non-linear state, alternately turned on and off, which reduces tube consumption and improves work efficiency, and can reach 80. %-90%.
  • FIG. 3 is a schematic structural diagram of still another embodiment of a switching regulator power supply according to an embodiment of the present application.
  • the switching regulator power supply of the embodiment of the present application is a feasible implementation manner of the switching regulator power supply of the embodiment shown in FIG. 2.
  • the adjustment circuit 26 includes sampling.
  • the circuit 31, the reference voltage source 32, the comparison amplifying circuit 33, a pulse width modulation (PWM) circuit 34, and a horizontal frequency pulse circuit 35 are provided.
  • the sampling circuit 31 is configured to input the sampling DC output voltage U 0 to the comparison amplifying circuit 33.
  • the reference voltage source 32 is used to generate a reference voltage U ref for input to the comparison amplifying circuit 33.
  • the comparison amplifying circuit 33 is configured to compare and amplify the DC output voltage U 0 and the reference voltage U ref to obtain a difference voltage input to the pulse width modulation circuit 34.
  • the horizontal frequency pulse circuit 35 is configured to generate a horizontal frequency pulse signal input to the pulse width modulation circuit 34.
  • the pulse width modulation circuit 34 is configured to input the adjustment voltage U b to the base b of the switching transistor 25 according to the difference voltage and the horizontal frequency pulse signal.
  • the sampling circuit 31 inputs the actual value of the DC output voltage U 0 to the comparison amplifying circuit 33, and the reference voltage source 32 generates the reference voltage U ref to the comparison amplifying circuit 33.
  • the comparison amplifying circuit 33 compares and amplifies the DC output voltage U 0 and the reference voltage U ref to obtain a difference voltage input to the pulse width modulation circuit 34.
  • the horizontal frequency pulse circuit 35 generates a horizontal frequency pulse signal (i.e., a clock signal) and inputs it to the pulse width modulation circuit 34.
  • the pulse width modulation circuit 34 generates the adjustment voltage U b based on the difference voltage input from the comparison amplification circuit 33 and the horizontal frequency pulse signal input from the horizontal frequency pulse circuit 35 to the base b of the switching transistor 25, and controls the on and off of the switching transistor 25.
  • the time i.e., the on-time T on and the off-time T off of the switching transistor
  • the switch tube is in a saturated region or a cut-off region, that is, in a non-linear state, alternately turned on and off, which reduces tube consumption and improves work efficiency, and can reach 80. %-90%.
  • FIG. 4 is a schematic structural diagram of still another embodiment of a switching regulator power supply according to an embodiment of the present application.
  • the switching regulator power supply of the embodiment of the present application is a feasible implementation manner of the switching regulator power supply of the embodiment shown in FIG. 3.
  • the switch tube 25 can be specifically It is a Metal Oxide Semiconductor Field Effect Transistor (MOSFET).
  • MOSFET Metal Oxide Semiconductor Field Effect Transistor
  • the first rectifying and filtering circuit 21 may specifically include a first rectifying diode 41 and a first capacitor 42.
  • the negative ends of the first rectifier diode 41 are electrically connected to the first end of the primary coil of the pulse transformer 22 and the first end of the first capacitor 42, respectively, and the second end of the first capacitor 42 is grounded.
  • the second rectifying and filtering circuit 23 may specifically include a second rectifying diode 43 and a second capacitor 44.
  • the positive terminal of the second rectifier diode 43 is electrically connected to the first end of the secondary winding of the pulse transformer 22, and the negative terminal of the second rectifier diode 43 is electrically connected to the first terminal of the load circuit 24 and the first terminal of the second capacitor 44, respectively. Connected, the second end of the second capacitor 44 is grounded.
  • comparison amplifying circuit 33 may specifically include an error amplifier 45.
  • the pulse width modulation circuit 34 may specifically include a pulse width modulation PWM comparator 46.
  • the horizontal frequency pulse circuit 35 may specifically include a sawtooth wave generator 47.
  • the pulse transformer 22 also known as the energy storage transformer, can adopt the iron core of the ferrite material because of the high working frequency, and the same name end is marked by the dot in FIG. 4 .
  • Transformer 22 primary coil induced voltage U L1 changes (as shown in Figure 6)
  • pulse transformer 22 primary coil current I L1 changes (as shown in Figure 7)
  • pulse transformer 22 secondary coil induced voltage U L2 changes (such as Figure 8)
  • the change in the secondary winding current I L2 of the pulse transformer 22 shown in Figure 9) to illustrate the change in the circuit signal:
  • the positive pulse adjustment voltage U b output from the pulse width modulation circuit 34 is applied to the base of the switching transistor 25.
  • L 1 represents the inductance of the primary coil
  • I L1 represents the current of the primary coil
  • t represents time
  • U i represents the DC voltage output by the first rectifying and filtering circuit 21.
  • I L1 (0) is the initial current on the primary coil L 1 .
  • the negative pulse adjustment voltage U b output from the pulse width modulation circuit 34 acts on the base b of the switching transistor 25, and the switching transistor 22 is in the off state.
  • the pulse transformer 22 primary coil current I L1 0.
  • the direction of the induced voltage U L1 generated on the primary coil of the pulse transformer 22 is up-down and positive, and the connection of the same-named end of the pulse transformer 22 (the end indicated by a dot in FIG.
  • the secondary coil of the pulse transformer 22 is The direction of the induced voltage U L2 is positive and negative, so that the second rectifier diode 43 is turned on, the magnetic energy stored by the pulse transformer 22 can charge the second capacitor 44, and output the DC output voltage U 0 to the load circuit 24, the secondary The coil current I L1 decreases linearly from I 2m . If the loss of the pulse transformer 22 is ignored and all the energy stored in the primary coil is transferred to the secondary coil, the energy relationship between the primary coil and the secondary coil should satisfy:
  • L 1 and L 2 respectively represent inductance coefficients of the primary coil and the secondary coil of the pulse transformer 22
  • I 1m and I 2m respectively represent maximum current values of the primary coil and the secondary coil of the pulse transformer 22 at time t 1 .
  • I 1m and I 2m respectively represent the maximum current values of the primary coil and the secondary coil of the pulse transformer 22 at time t 1 .
  • the positive pulse adjustment voltage U b output from the pulse width modulation circuit 34 acts on the base b of the switching transistor 25 again, and the switching transistor 25 is again guided.
  • the primary winding current I L1 of the pulse transformer 22 starts to rise from I L1 (0).
  • the switching transistor 25 is turned on and the second rectifier diode 43 is turned off, the current required by the load circuit 24 is supplied by the second capacitor 44 by discharging.
  • L 1 and L 2 respectively represent the inductances of the primary coil and the secondary coil of the pulse transformer 22
  • ⁇ I L1 is the increase of the primary coil current I L1 of the pulse transformer 22
  • ⁇ I L2 is the decrease of the secondary coil current I L2 of the pulse transformer 22 the amount.
  • U i represents the DC voltage output by the first rectifying and filtering circuit
  • L 1 represents the inductance of the primary coil of the pulse transformer 22
  • Ton is the conduction time of the switching transistor 25 in one cycle.
  • the secondary winding current I L2 of the pulse transformer 22 is a linearly decreasing waveform
  • ⁇ I L2 is the reduction of the secondary coil current I L2 of the pulse transformer 22, wherein:
  • U i represents the DC voltage output by the first rectifying and filtering circuit
  • L 2 represents the inductance of the secondary coil of the pulse transformer 22
  • T off is the off time of the switching transistor 25 in one cycle.
  • the DC output voltage U 0 can be obtained as follows:
  • L 1 and L 2 represent the inductances of the primary and secondary coils of the pulse transformer 22, respectively
  • Ton is the on-time of the switching transistor 25 in one cycle
  • Toff is the cut-off time of the switching transistor 25 in one cycle
  • n 1 , n 2 are the turns of the primary and secondary coils of the pulse transformer 22, respectively.
  • the DC output voltage U 0 is proportional to the DC voltage U i outputted by the first rectifying and filtering circuit 21, and the turns ratio n 2 /n 1 of the primary and secondary coils of the pulse transformer 22 In proportion, it is proportional to the ratio T on /T off of the on- time and the off-time of the switch tube 15.
  • the sum of the on-time and the off-time, Ton + T off is synchronized with the period of the horizontal-frequency pulse signal output from the horizontal-frequency pulse circuit 35, and is fixed, for example, 64 microseconds (us).
  • the DC output voltage U 0 is adjusted by controlling the ratio T on /T off of the on- time and the off-time, that is, controlling the pulse width of the adjustment voltage U b (ie, the duty ratio D), so that the DC output voltage U 0 is stabilized.
  • the switch tube 25 and the second rectifier diode 43 are in a reverse polarity excitation relationship: when the switch tube 25 is turned on, the second rectifier diode 43 is turned off; and when the switch tube 25 is turned off, the second rectifier diode 43 is turned off. Turn on. That is, when the switch tube 25 is turned on, the input electric energy is stored on the primary coil of the pulse transformer 22. When the switch tube 25 is turned off, the electric energy stored on the primary coil of the pulse transformer 22 is output to the secondary coil and output to the load circuit. 14 in.
  • the switch tube is in a saturated region or a cut-off region, that is, in a non-linear state, alternately turned on and off, which reduces tube consumption and improves work efficiency, and can reach 80. %-90%.

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Abstract

一种开关稳压电源。该开关稳压电源包括第一整流滤波电路（21）、脉冲变压器（22）、第二整流滤波电路（23）、负载电路（24）、开关管（25）和调节电路（26），其中：第一整流滤波电路（21）对输入的交流电压进行整流和滤波得到直流电压；脉冲变压器（22）和开关管（25）将直流电压转变为脉冲直流电压；第二整流滤波电路（23）对脉冲直流电压进行整流和滤波得到直流输出电压输入至负载电路（24）；调节电路（26）根据直流输出电压生成调节电压输入至开关管（25）的基极，控制开关管（25）的通断时间。所述开关稳压电源，在稳压过程中，开关管（25）处于饱和区或截止区即非线性状态下，交替性导通和截止，降低了管耗，提高了工作效率。

Description

开关稳压电源
本专利申请要求申请日为2015年12月22日、申请号为2015210892630的中国专利申请的优先权，并将上述专利申请以引用的方式全文引入本文中。
技术领域
本申请实施例涉及电路技术领域，尤其涉及一种开关稳压电源。
背景技术
通常，从电网输入的220伏(V)的交流电压是不稳定的，电路连接的负载(比如电视机、录像机等)也是经常变化的，因此，需要采用稳压电源为电路连接的负载提供稳定的直流电压以使负载可以正常稳定的工作。
图1为现有的线性稳压电源的结构示意图。如图1所示，包括第一整流滤波电路、调整管、第二整流滤波电路、负载电路、取样电路和比较放大电路，其中，输入的220V交流电压经第一整流滤波电路后得到直流电压Ui，输入至调整管的集电极c，调整管的发射极e与第二整流滤波电路的第一端连接，第二整流滤波电路的第二端分别与取样电路的第一端和负载电路的第一端连接，负载电路的第二端接地，取样电路的第二端与比较放大电路的第一端连接，比较放大电路的第二端与调整管的基极b连接。比较放大电路将采样电路输入的采样电压U0和基准电压源提供的基准电压Uref进行比较放大后输出至调整管的基极b，通过控制调整管的基极b的电压Ub从而控制调整管的集电极c与发射极e之间的电压Uce，使得调整管的集电极c与发射极e之间的电压Uce稳定，从而控制输出至负载的电压U0稳定，起到稳压作用。
但现有技术至少存在如下缺点：线性稳压电源中的调整管始终工 作在放大区即线性状态下，因此管耗大，工作效率低。
发明内容
本申请实施例提供一种开关稳压电源，在稳压过程中，开关管处于饱和区或截止区即非线性状态下，交替性导通和截止，以降低管耗，提高工作效率。
为达到上述目的，本申请实施例采用如下技术方案：
一方面，本申请实施例提供一种开关稳压电源，包括第一整流滤波电路、脉冲变压器、第二整流滤波电路、负载电路、开关管和调节电路，其中：所述第一整流滤波电路的输出端与所述脉冲变压器的初级线圈的第一端电连接，所述脉冲变压器的次级线圈的第一端与所述第二整流滤波电路的输入端电连接，所述脉冲变压器的次级线圈的第二端接地，所述第二整流滤波电路的输出端分别与所述负载电路的第一端和所述调节电路的第一端电连接，所述负载电路的第二端接地，所述开关管的基极与所述调节电路的第二端电连接，所述开关管的集电极与所述脉冲变压器的初级线圈的第二端电连接，所述开关管的发射极接地；所述第一整流滤波电路，用于对输入的交流电压进行整流和滤波，得到直流电压；所述脉冲变压器和所述开关管，用于将所述直流电压转变为脉冲直流电压；所述第二整流滤波电路，用于对所述脉冲直流电压进行整流和滤波，得到直流输出电压输入至所述负载电路；所述调节电路，用于根据所述直流输出电压生成调节电压输入至所述开关管的基极，控制所述开关管的通断时间。
如上所述的开关稳压电源中，所述调节电路包括取样电路、基准电压源、比较放大电路、脉冲宽度调制电路和行频脉冲电路；所述取样电路，用于采样所述直流输出电压输入至所述比较放大电路；所述基准电压源，用于生成基准电压输入至所述比较放大电路；所述比较放大电路，用于对所述直流输出电压和所述基准电压进行比较放大，得到差值电压输入至所述脉冲宽度调制电路；所述行频脉冲电路，用于生成行频脉冲信号输入至所述脉冲宽度调制电路；所述脉冲宽度调 制电路，用于根据所述差值电压和所述行频脉冲信号生成所述调节电压输入至所述开关管的基极。
如上所述的开关稳压电源中，所述开关管为金属-氧化物半导体场效应晶体管MOSFET。
如上所述的开关稳压电源中，所述第一整流滤波电路包括第一整流二极管和第一电容；所述第一整流二极管的负端分别与所述脉冲变压器的初级线圈的第一端和所述第一电容的第一端电连接，所述第一电容的第二端接地。
如上所述的开关稳压电源中，所述第二整流滤波电路包括第二整流二极管和第二电容；所述第二整流二极管的正端与所述脉冲变压器的次级线圈的第一端电连接，所述第二整流二极管的负端分别与所述负载电路的第一端和所述第二电容的第一端电连接，所述第二电容的第二端接地。
如上所述的开关稳压电源中，所述比较放大电路包括误差放大器。
如上所述的开关稳压电源中，所述脉冲宽度调制电路包括脉冲宽度调制比较器。
如上所述的开关稳压电源中，所述行频脉冲电路包括锯齿波发生器。
本申请实施例提供的开关稳压电源，在稳压过程中，开关管处于饱和区或截止区即非线性状态下，交替性导通和截止，降低了管耗，提高了工作效率。
上述说明仅是本申请技术方案的概述，为了能够更清楚了解本申请的技术手段，而可依照说明书的内容予以实施，并且为了让本申请的上述和其它目的、特征和优点能够更明显易懂，以下特举本申请的具体实施方式。
附图说明
通过阅读下文优选实施方式的详细描述，各种其他的优点和益处对于本领域普通技术人员将变得清楚明了。附图仅用于示出优选实施 方式的目的，而并不认为是对本申请的限制。而且在整个附图中，用相同的参考符号表示相同的部件。在附图中：
图1为现有的线性稳压电源的结构示意图；
图2为本申请实施例提供的开关稳压电源一个实施例的结构示意图；
图3为本申请实施例提供的开关稳压电源又一个实施例的结构示意图；
图4为本申请实施例提供的开关稳压电源又一个实施例的结构示意图；
图5为图4所示的开关稳压电源中输入至开关管的基极的调节电压Ub的波形图；
图6为图4所示的开关稳压电源中脉冲变压器初级线圈感应电压UL1的波形图；
图7为图4所示的开关稳压电源中脉冲变压器初级线圈电流IL1的波形图；
图8为图4所示的开关稳压电源中脉冲变压器次级线圈感应电压UL2的波形图；
图9为图4所示的开关稳压电源中脉冲变压器次级线圈电流IL2的波形图。
具体实施方式
下面将参照附图更详细地描述本申请的示例性实施例。虽然附图中显示了本申请的示例性实施例，然而应当理解，可以以各种形式实现本申请而不应被这里阐述的实施例所限制。相反，提供这些实施例是为了能够更透彻地理解本申请，并且能够将本申请的范围完整的传达给本领域的技术人员。
下面结合附图对本申请实施例的开关稳压电源进行详细描述。
实施例一
图2为本申请实施例提供的开关稳压电源一个实施例的结构示意图。如图2所示，本申请实施例的开关稳压电源具体可包括：第一整流滤波电路21、脉冲变压器22、第二整流滤波电路23、负载电路24、开关管25和调节电路26。其中：
第一整流滤波电路21的输出端与脉冲变压器22的初级线圈的第一端电连接，脉冲变压器22的次级线圈的第一端与第二整流滤波电路23的输入端电连接，脉冲变压器22的次级线圈的第二端接地，第二整流滤波电路23的输出端分别与负载电路24的第一端和调节电路26的第一端电连接，负载电路24的第二端接地，开关管25的基极b与调节电路26的第二端电连接，开关管25的集电极c与脉冲变压器22的初级线圈的第二端电连接，开关管25的发射极e接地。
第一整流滤波电路21，用于对输入的交流电压进行整流和滤波，得到直流电压Ui。
脉冲变压器22和开关管25，用于将直流电压Ui转变为脉冲直流电压。
第二整流滤波电路23，用于对脉冲直流电压进行整流和滤波，得到直流输出电压U0输入至负载电路24。
调节电路26，用于根据直流输出电压U0生成调节电压Ub输入至开关管25的基极b，控制开关管25的通断时间。
具体的，本申请实施例的开关稳压电源为脉冲变压器耦合并联型开关稳压电源。第一整流滤波电路21对输入的交流电压(例如220V的交流电压)进行整流和滤波，得到直流电压Ui并输出至脉冲变压器22的初级线圈。脉冲变压器22和开关管25将第一整流滤波电路21输出的直流电压Ui转变为高频矩形脉冲直流电压并输出至第二整流滤波电路23。第二整流滤波电路23对脉冲变压器22的次级线圈输出的高频矩形脉冲直流电压进行整流和滤波，得到直流输出电压U0并输出至负载电路24。调节电路26根据第二整流滤波电路23输出的直流输出电压U0生成脉冲宽度可调节的调节电压Ub输入至开关管25的基极b，通过控制开关管25的通断时间(即开关管的导通时间Ton和截 止时间Toff)使得第二整流滤波电路23输出的直流输出电压U0稳定。当直流输出电压U0由于某种原因(比如负载的变化)降低时，则调节电路26可以通过改变所产生的调节电压的脉冲宽度(即占空比D)，使经过开关管25后的高频矩形脉冲直流电压的平均电压升高，进而提升直流输出电压U0的电压值，反之亦然。
本申请实施例的开关稳压电源，在稳压过程中，开关管处于饱和区或截止区即非线性状态下，交替性导通和截止，降低了管耗，提高了工作效率，可达到80％-90％。
实施例二
图3为本申请实施例提供的开关稳压电源又一个实施例的结构示意图。如图3所示，本申请实施例的开关稳压电源为图2所示实施例的开关稳压电源的一种可行实施方式，在图2所示实施例的基础上，调节电路26包括取样电路31、基准电压源32、比较放大电路33、脉冲宽度调制(Pulse Width Modulation，简称PWM)电路34和行频脉冲电路35。
取样电路31，用于采样直流输出电压U0输入至比较放大电路33。
基准电压源32，用于生成基准电压Uref输入至比较放大电路33。
比较放大电路33，用于对直流输出电压U0和基准电压Uref进行比较放大，得到差值电压输入至脉冲宽度调制电路34。
行频脉冲电路35，用于生成行频脉冲信号输入至脉冲宽度调制电路34。
脉冲宽度调制电路34，用于根据差值电压和行频脉冲信号生成调节电压Ub输入至开关管25的基极b。
具体的，取样电路31采样直流输出电压U0的实际值输入至比较放大电路33，基准电压源32生成基准电压Uref输入至比较放大电路33。比较放大电路33对直流输出电压U0和基准电压Uref进行比较放大，得到差值电压输入至脉冲宽度调制电路34。行频脉冲电路35生成行频脉冲信号(即时钟信号)输入至脉冲宽度调制电路34。脉冲宽 度调制电路34根据比较放大电路33输入的差值电压和行频脉冲电路35输入的行频脉冲信号生成调节电压Ub输入至开关管25的基极b，通过控制开关管25的通断时间(即开关管的导通时间Ton和截止时间Toff)使得第二整流滤波电路23输出的直流输出电压U0稳定在基准电压Uref附近。
本申请实施例的开关稳压电源，在稳压过程中，开关管处于饱和区或截止区即非线性状态下，交替性导通和截止，降低了管耗，提高了工作效率，可达到80％-90％。
实施例三
图4为本申请实施例提供的开关稳压电源又一个实施例的结构示意图。如图4所示，本申请实施例的开关稳压电源为图3所示实施例的开关稳压电源的一种可行实施方式，在图3所示实施例的基础上，开关管25具体可为金属-氧化物半导体场效应晶体管(Metal Oxide Semiconductor Field Effect Transistor，简称MOSFET)。
进一步的，第一整流滤波电路21具体可包括第一整流二极管41和第一电容42。第一整流二极管41的负端分别与脉冲变压器22的初级线圈的第一端和第一电容42的第一端电连接，第一电容42的第二端接地。
进一步的，第二整流滤波电路23具体可包括第二整流二极管43和第二电容44。第二整流二极管43的正端与脉冲变压器22的次级线圈的第一端电连接，第二整流二极管43的负端分别与负载电路24的第一端和第二电容44的第一端电连接，第二电容44的第二端接地。
进一步的，比较放大电路33具体可包括误差放大器45。
进一步的，脉冲宽度调制电路34具体可包括脉冲宽度调制PWM比较器46。
进一步的，行频脉冲电路35具体可包括锯齿波发生器47。
具体的，脉冲变压器22，又称储能变压器，由于工作频率较高，因此可采用铁氧体材料的铁心，同名端如图4中圆点所标。
为了更具体地说明本申请实施例的开关稳压电源的工作过程，下文以开关稳压电源中输入至开关管25的基极b的调节电压Ub的变化(如图5所示)、脉冲变压器22初级线圈感应电压UL1的变化(如图6所示)、脉冲变压器22初级线圈电流IL1的变化(如图7所示)、脉冲变压器22次级线圈感应电压UL2的变化(如图8所示)和脉冲变压器22次级线圈电流IL2的变化(如图9所示)来说明电路信号的变化：
如图5-图9所示，在t0～t1(t0、t1均表示某个时间点)期间，脉冲宽度调制电路34输出的正脉冲调节电压Ub作用到开关管25的基极b，开关管25饱和导通(Uce＝0)，脉冲变压器22初级线圈上产生的感应电压UL1的方向为上正下负，此时：
Figure PCTCN2016089019-appb-000001
其中，L1表示初级线圈的电感系数，IL1表示初级线圈的电流，t表示时间，Ui表示第一整流滤波电路21输出的直流电压。
对上述公式(1-1)进行逆变换，得到：
Figure PCTCN2016089019-appb-000002
其中，IL1(0)为初级线圈L1上的初始电流。
由式(1-2)可见，随着时间的增加，初级线圈电流IL1线性上升，由脉冲变压器22同名端(图4中以圆点标注的端)的连接可知，脉冲变压器22次级线圈上产生的感应电压UL2为上负下正，此时第二整流二极管43截止，脉冲变压器22次级线圈电流IL2＝0。在开关管25导通期间t0～t1，随着初级线圈电流IL1的上升，脉冲变压器22中的磁能增大，在t1时刻达到最大值
Figure PCTCN2016089019-appb-000003
其中，I1m表示在t1时刻初级线圈的最大电流值。
在t1～t2(t1、t2均表示某个时间点)期间，脉冲宽度调制电路34输出的负脉冲调节电压Ub作用到开关管25的基极b，开关管22处于截止状态，脉冲变压器22初级线圈电流IL1＝0。此时脉冲变压器22初级线圈上产生的感应电压UL1的方向为上负下正，由脉冲变压器22同 名端(图4中以圆点标注的端)的连接可知，脉冲变压器22次级线圈上产生的感应电压UL2的方向为上正下负，于是第二整流二极管43导通，脉冲变压器22储存的磁能使第二电容44充电，并输出直流输出电压U0至负载电路24，次级线圈电流IL1从I2m开始线性下降。如果忽略脉冲变压器22的损耗，初级线圈存储的所有能量全部转移到次级线圈，则初级线圈、次级线圈的能量关系应满足：
Figure PCTCN2016089019-appb-000004
其中，L1、L2分别表示脉冲变压器22初级线圈和次级线圈的电感系数，I1m、I2m分别表示在t1时刻脉冲变压器22初级线圈和次级线圈的最大电流值。
由此可得：
Figure PCTCN2016089019-appb-000005
其中，I1m、I2m分别表示在t1时刻脉冲变压器22初级线圈和次级线圈的最大电流值。
在t2～t3(t2、t3均表示某个时间点)期间，脉冲宽度调制电路34输出的正脉冲调节电压Ub又作用到开关管25的基极b，开关管25再次导通，第二整流二极管43截止，脉冲变压器22次级线圈电流IL2＝0，脉冲变压器22又开始储存能量，此时脉冲变压器22初级线圈电流IL1又从IL1(0)开始上升。在开关管25导通、第二整流二极管43截止期间，负载电路24所需电流由第二电容44通过放电来供给。
为讨论方便，我们仅考察电路工作在平衡状态后的稳态情况。当开关管25导通时，第二整流二极管43截止，脉冲变压器22储存能量，假设能量的增加量为ΔW1；当开关管25截止时，第二整流二极管43导通，脉冲变压器22储存的能量被负载电路24消耗，假设能量的减少量为ΔW2。平衡状态时，一个脉冲周期内增加的能量应与消耗的能量相等，即有ΔW1＝ΔW2，因为：
Figure PCTCN2016089019-appb-000006
Figure PCTCN2016089019-appb-000007
其中，L1、L2分别表示脉冲变压器22初级线圈和次级线圈的电感系数，ΔIL1为脉冲变压器22初级线圈电流IL1增加量，ΔIL2为脉冲变压器22次级线圈电流IL2减小量。
根据上述公式(1-2)可得：
Figure PCTCN2016089019-appb-000008
其中，Ui表示第一整流滤波电路21输出的直流电压，L1表示脉冲变压器22初级线圈的电感系数，Ton为开关管25在一个周期内的导通时间。
同理，脉冲变压器22次级线圈电流IL2为线性下降的波形，ΔIL2为脉冲变压器22次级线圈电流IL2减小量，其中：
Figure PCTCN2016089019-appb-000009
其中，Ui表示第一整流滤波电路21输出的直流电压，L2表示脉冲变压器22次级线圈的电感系数，Toff为开关管25在一个周期内的截止时间。
根据上述公式(1-5)～(1-8)可得直流输出电压U0为：
Figure PCTCN2016089019-appb-000010
其中，L1、L2分别表示脉冲变压器22初级线圈和次级线圈的电感系数，Ton为开关管25在一个周期内的导通时间，Toff为开关管25在一个周期内的截止时间，n1、n2分别为脉冲变压器22初级线圈和次级线圈的匝数。
根据上述公式(1-9)可知，直流输出电压U0与第一整流滤波电路21输出的直流电压Ui成正比，与脉冲变压器22初级线圈和次级线圈的匝数比n2/n1成正比，与开关管15导通时间和截止时间的比值Ton/Toff成正比。
本实施例中，导通时间和截止时间的和Ton+Toff与行频脉冲电路35输出的行频脉冲信号的周期同步，且是固定不变的，例如64微秒 (us)。通过控制导通时间和截止时间的比值Ton/Toff，即控制调节电压Ub的脉冲宽度(即占空比D)来调节直流输出电压U0，使得直流输出电压U0稳定。
从上述工作过程可以看出，开关管25和第二整流二极管43是反极性激励关系：开关管25导通时，第二整流二极管43截止；而开关管25截止时，第二整流二极管43导通。也即开关管25导通时，输入的电能存储在脉冲变压器22的初级线圈上，开关管25截止时，存储在脉冲变压器22初级线圈上的电能输出到次级线圈上，并输出至负载电路14中。
本申请实施例的开关稳压电源，在稳压过程中，开关管处于饱和区或截止区即非线性状态下，交替性导通和截止，降低了管耗，提高了工作效率，可达到80％-90％。
最后应说明的是：以上各实施例仅用以说明本申请的技术方案，而非对其限制；尽管参照前述各实施例对本申请进行了详细的说明，本领域的普通技术人员应当理解：其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分或者全部技术特征进行等同替换；而这些修改或者替换，并不使相应技术方案的本质脱离本申请各实施例技术方案的范围。

Claims (8)

  1. 一种开关稳压电源，其特征在于，包括第一整流滤波电路、脉冲变压器、第二整流滤波电路、负载电路、开关管和调节电路，其中：
    所述第一整流滤波电路的输出端与所述脉冲变压器的初级线圈的第一端电连接，所述脉冲变压器的次级线圈的第一端与所述第二整流滤波电路的输入端电连接，所述脉冲变压器的次级线圈的第二端接地，所述第二整流滤波电路的输出端分别与所述负载电路的第一端和所述调节电路的第一端电连接，所述负载电路的第二端接地，所述开关管的基极与所述调节电路的第二端电连接，所述开关管的集电极与所述脉冲变压器的初级线圈的第二端电连接，所述开关管的发射极接地；
    所述第一整流滤波电路，用于对输入的交流电压进行整流和滤波，得到直流电压；
    所述脉冲变压器和所述开关管，用于将所述直流电压转变为脉冲直流电压；
    所述第二整流滤波电路，用于对所述脉冲直流电压进行整流和滤波，得到直流输出电压输入至所述负载电路；
    所述调节电路，用于根据所述直流输出电压生成调节电压输入至所述开关管的基极，控制所述开关管的通断时间。
  2. 根据权利要求1所述的开关稳压电源，其特征在于，所述调节电路包括取样电路、基准电压源、比较放大电路、脉冲宽度调制电路和行频脉冲电路；
    所述取样电路，用于采样所述直流输出电压输入至所述比较放大电路；
    所述基准电压源，用于生成基准电压输入至所述比较放大电路；
    所述比较放大电路，用于对所述直流输出电压和所述基准电压进行比较放大，得到差值电压输入至所述脉冲宽度调制电路；
    所述行频脉冲电路，用于生成行频脉冲信号输入至所述脉冲宽度调制电路；
    所述脉冲宽度调制电路，用于根据所述差值电压和所述行频脉冲信号生成所述调节电压输入至所述开关管的基极。
  3. 根据权利要求1所述的开关稳压电源，其特征在于，所述开关管为金属-氧化物半导体场效应晶体管MOSFET。
  4. 根据权利要求1所述的开关稳压电源，其特征在于，所述第一整流滤波电路包括第一整流二极管和第一电容；
    所述第一整流二极管的负端分别与所述脉冲变压器的初级线圈的第一端和所述第一电容的第一端电连接，所述第一电容的第二端接地。
  5. 根据权利要求1所述的开关稳压电源，其特征在于，所述第二整流滤波电路包括第二整流二极管和第二电容；
    所述第二整流二极管的正端与所述脉冲变压器的次级线圈的第一端电连接，所述第二整流二极管的负端分别与所述负载电路的第一端和所述第二电容的第一端电连接，所述第二电容的第二端接地。
  6. 根据权利要求2所述的开关稳压电源，其特征在于，所述比较放大电路包括误差放大器。
  7. 根据权利要求2所述的开关稳压电源，其特征在于，所述脉冲宽度调制电路包括脉冲宽度调制比较器。
  8. 根据权利要求2所述的开关稳压电源，其特征在于，所述行频脉冲电路包括锯齿波发生器。
PCT/CN2016/089019 2015-12-22 2016-07-07 开关稳压电源 Ceased WO2017107452A1 (zh)

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