WO2017020968A1 - Noeud de réseau et procédé de formation de faisceau photonique - Google Patents

Noeud de réseau et procédé de formation de faisceau photonique Download PDF

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Publication number
WO2017020968A1
WO2017020968A1 PCT/EP2015/068189 EP2015068189W WO2017020968A1 WO 2017020968 A1 WO2017020968 A1 WO 2017020968A1 EP 2015068189 W EP2015068189 W EP 2015068189W WO 2017020968 A1 WO2017020968 A1 WO 2017020968A1
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WO
WIPO (PCT)
Prior art keywords
signal
network node
mll
optical modulator
coupled
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PCT/EP2015/068189
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English (en)
Inventor
Paolo Ghelfi
Antonella Bogoni
Antonio D'errico
Marzio Puleri
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Telefonaktiebolaget Lm Ericsson (Publ)
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Priority to PCT/EP2015/068189 priority Critical patent/WO2017020968A1/fr
Publication of WO2017020968A1 publication Critical patent/WO2017020968A1/fr

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Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04W—WIRELESS COMMUNICATION NETWORKS
    • H04W56/00—Synchronisation arrangements
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/25—Arrangements specific to fibre transmission
    • H04B10/2575—Radio-over-fibre, e.g. radio frequency signal modulated onto an optical carrier
    • H04B10/25752—Optical arrangements for wireless networks
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2676—Optically controlled phased array
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B2210/00—Indexing scheme relating to optical transmission systems
    • H04B2210/006—Devices for generating or processing an RF signal by optical means

Definitions

  • the present disclosure relates to a network node and method for photonic beamforming.
  • Gbps giga bytes per second
  • the cost of deploying, operating and maintaining a network, as well as the cost of the devices, should also be at a level that enables popular services to be provided at an attractive price for users, while maintaining attractive business cases for network operators. Energy efficiency should also be an important focus area, in order to achieve and retain a low network-operation cost even with the expected massive increase in traffic. Smart antennas including a very large number of steerable antenna elements, larger available spectrum and an increased coordination between base stations will help to provide such very high service levels.
  • the mobile-broadband technologies will also expand into new deployment scenarios, such as dense small-cell deployments, and new use cases, such as different kinds of machine-type communication.
  • ultra-dense networks will consist of low-power access nodes that will be deployed with much higher density than existing networks. In extreme cases, one can foresee indoor deployments with access nodes in every room and outdoor deployments with access nodes at lamppost distances apart. To reliably support multi-Gbps data rates, ultra-dense networks should support minimum transmission bandwidths of several hundreds of MHz with the possibility of an extension up to a few GHz of bandwidth.
  • Ultra-dense networks will primarily operate in the 10-100GHz range as higher frequency bands enable the very wide transmission bandwidth needed to reliably support multi-Gbps data rates. Although these ultra-dense networks will operate in different spectrum regions and will most likely be based on new radio-access technologies, they should be well integrated with the overlaid cellular networks, providing a seamless user experience as devices move in and out of ultra-dense network coverage.
  • arrayed antennas using beamforming techniques should be introduced, for example in order to steer the beam in both the vertical and horizontal planes.
  • the use of arrayed antennas could imply an increase of power consumption, complexity and cost, and given the huge number of base stations in micro- and pico-cells, reduction of costs and power consumption by system integration is a necessary step for making this solution feasible.
  • the power consumption should be kept at the current level in front of a traffic volume increase by a factor of 10 3 .
  • both LTE-A and 5G the aggressive scenario of a frequency reuse of one is going to be adopted, where all the cells use the same frequency.
  • a reuse of one provides the highest network efficiency and enables high data rates close to the base station.
  • the challenge with a reuse of one is the high inter-cell interference when the terminal (User Equipment, UE) is located between two cells.
  • UE User Equipment
  • Beamforming will be introduced in 5G to have the capability of pointing the radio beam to cover a precise area, tuning its orientation in order to reduce interference with closed radio sectors. In such a way, it is possible to cover several small crowded areas with radio beams working at microwave frequencies.
  • beamforming will introduce the capability of following users with the radio beams, for example having multiple-beams irradiated by the same antenna.
  • the latter has to work using different frequencies to avoid interference, so several licensed frequencies must be adopted.
  • a network node for use in photonic beamforming.
  • the network node comprises an input for receiving a mode locked laser (MLL) signal.
  • the network node comprises an optical modulator coupled to receive the MLL signal and a clock signal.
  • the network node comprises a clock derivation module for deriving the clock signal from the MLL signal.
  • the optical modulator may comprise a first transmitting optical modulator coupled to receive the MLL signal, the first transmitting optical modulator being configured to generate a comb signal of continuous waves.
  • the first transmitting optical modulator may be configured to be driven by the clock signal. It may also be configured to output a comb signal of continuous waves in the form of a single sideband modulation with carrier suppression.
  • transmitting optical modulator coupled to receive the MLL signal, wherein the second transmitting optical modulator is configured to be driven by an intermediate frequency signal.
  • the second transmitting optical modulator may be configured to output a data sideband signal for each respective laser line of the comb signal, at a frequency distance of the intermediate frequency from each respective laser line.
  • Each data sideband signal may be a single sideband modulation with carrier suppressions.
  • the network node further comprises a first selective phase shifter coupled to receive the output of the first transmitting optical modulator, and configured to selectively control the phase of each continuous wave.
  • the first selective phase shifter may be further coupled to receive the output of the second transmitting optical modulator.
  • the output of the first selective phase shifter may be coupled to a first demultiplexer.
  • the second transmitting optical modulator is coupled to the first demultiplexer.
  • the clock signal may be configured to be derived by dividing a frequency of a reference clock provided by the MLL signal by an integer number.
  • a frequency of the clock signal may be a frequency of a reference clock of the MLL signal.
  • the optical modulator may be coupled to receive the MLL signal via a de- interleaving module.
  • the optical modulator may comprise a receiving optical modulator coupled to receive the MLL signal, and which is configured to generate a comb signal of continuous waves.
  • the receiving optical modulator may be configured to be driven by the clock signal.
  • the receiving optical modulator may be configured to output a comb signal of continuous waves in the form of a single sideband modulation with carrier suppression.
  • the MLL signal may be further coupled to a second demultiplexer.
  • the second demultiplexer may be configured to separate the modes of the MLL signal and send each mode signal to one of a plurality of receiving antenna elements which modulate the mode signals with received signals to provide modulated signals comprising single-sideband modulation with carrier suppression.
  • the modulated signals from the plurality of receiving antenna elements may be coupled through a multiplexer to form a combined receiver signal.
  • the network node may further comprises a summing module configured to couple the combined receiver signal and the output of the receiving optical modulator.
  • a second selective phase shifter may be coupled between the input and the second demultiplexer, and configured to selectively control the phase of each mode of the MLL signal.
  • a second selective phase shifter may be coupled between the receiving optical modulator and the summing module, and configured to selectively control the phase of each continuous wave.
  • the method comprises receiving a mode locked laser (MLL) signal, and inputting the MLL signal into an optical modulator.
  • MLL mode locked laser
  • a clock signal is derived from the MLL signal, and the clock signal used to drive the optical modulator.
  • Figure 1 illustrates an example of a network node according to an
  • Figure 2 illustrates an example of a method carried out by a network node 100 according to an embodiment
  • Figure 3 illustrates an example of a network node according to another embodiment
  • Figure 4 illustrates an example of a network node according to another embodiment
  • Figure 5 illustrates an example of a network node according to another embodiment
  • Figure 6 shows a block diagram of a network node 600 according to an embodiment.
  • Figure 7 shows a block diagram of a network node 700 according to an embodiment.
  • Photonics-based wireless systems Although still at research level, are moving towards a new generation of multifunctional systems able to manage the wireless communications with several different frequencies and protocols, even simultaneously, while also realizing surveillance operations.
  • Photonics matches the new requirements of flexibility for software-defined architectures due to its ultra-wide bandwidths, and ease of tunability, guaranteeing low footprint and weight as a result of integrated photonic technologies.
  • photonics also allows increased resolution and sensitivity by means of the inherently low phase noise of lasers.
  • photonics has proved to have high precision and ultra-wide bandwidth, allowing the generation of extremely stable multiple radio-frequency (RF) signals with arbitrary waveforms up to the millimeter waves, while also allowing their detection and precise direct digitization (i.e., without noisy RF down-conversions).
  • RF radio-frequency
  • the photonics-based generation and detection of RF signals are usually studied only separately. Only recently a fully photonics- based RF transceiver has been developed and characterized, and is now being tested in a radar application.
  • the exploited architecture makes use of a single pulsed laser for both generating and detecting the tunable RF signals, avoiding RF up-/down-conversions and guaranteeing a software-defined approach, multiple functionalities, and high resolution, with performance exceeding the state-of-the-art electronics at carrier frequencies above 10GHz.
  • simple architectures for the photonic generation of RF signals have been envisioned based on the heterodyning of two independent lasers, but these implementations do not allow for a stable RF generation, making the obtained signals not useful for the requirements of future systems.
  • phase locking of the beating lasers is necessary, and this usually requires more complex and cumbersome set-ups.
  • phase locked laser lines One technique for generating phase locked laser lines is the mode locking of lasers: the intrinsic phase-locking condition of the mode-locked laser (MLL) ensures an extremely low phase noise of the generated RF signal. Moreover, the possibility of selecting laser modes with variable wavelength detuning allows the flexible production of RF carriers with tunable frequency, potentially generating any multiple frequency of the MLL repetition rate. Moreover, the phase noise of the obtained RF carriers have been measured and analyzed, demonstrating that they can be significantly less noisy than the signals generated by the state-of-the-art RF synthesizer.
  • MLL mode-locked laser
  • the photonics-generated carriers must be modulated into amplitude- and/or phase-coded signals via electronics methods, which would require frequency-specific RF components that become more expensive at increasing frequency.
  • An alternative modulation and coding approach based on photonics could instead allow broad RF bandwidth without restrictions on the carrier frequency selection.
  • the modulated RF signal is generated by heterodyning two modes from a MLL, one of which is modulated by the low-pass modulation signal.
  • the modulation signal can be generated by a digital synthesizer with narrow analog bandwidth, and directly up-converted by photonic techniques through the heterodyning.
  • Typical Wi-Fi OFDM (orthogonal frequency-division multiplexing) signals and compressed radar pulses have been generated with these techniques, with carrier frequencies up to 40GHz.
  • the schemes allow the photonic generation of arbitrary phase-modulated RF pulses with flexible carrier frequency, and phase stability suitable for coherent radar systems.
  • the receivers for Software Defined Radios would need high speed analog-digital convertors with a huge analog input bandwidth spanning over several tens of GHz, and with high spurious-free dynamic range (SFDR) as well as signal to noise ratio.
  • precise electronic analog-digital convertors show limited analog input bandwidth, since at high input frequency the aperture jitter of the sampling clock affects the accuracy of the digitized signal.
  • Existing electronic analog-digital convertors show an aperture jitter of hundreds of femtoseconds with only a few GHz of analog bandwidth.
  • Optical sampling can overcome the limitations faced by electronic analog-digital convertors, and in the last decade several photonics-assisted analog-digital convertors have been proposed, based on the electrical detection of modulated optical pulse trains with subsequent sample parallelization schemes. Most of these converters resort to the concept of under-sampling to acquire radio frequency signals with bandwidth up to a few GHz but a carrier frequency up to several tens of GHz. The use of narrow-pulse MLLs with very low temporal jitter guarantees a precise sampling time and a digitized signal with a low jitter-limited noise floor. The high electro-optical bandwidth of the optical modulators can broaden the analog input bandwidth of photonic-assisted ADCs up to tens of GHz.
  • Sample parallelization by time- or wavelength-interleaving schemes have been proposed to enlarge the instantaneous bandwidth (i.e., the maximum signal bandwidth) of the photonic ADCs, by exploiting a MLL with high repetition rate and a set of parallel low-speed high-precision electronic converters.
  • the data interleaving can also produce spurious peaks due to the inequalities of the data arrays in the parallel channels, and to the non-idealities of the parallelizing method as time skew and crosstalk.
  • time-interleaving suffers the inter-channels crosstalk due to the limited extinction ratio of the optical switching matrix.
  • Digital post-processing techniques are usually applied to minimize the effect of such spurious components and to maximize the precision of the photonic ADC.
  • the present Applicant has proposed the exploitation of the time-interleaving approach to avoid the time skew issues, and have presented a photonic ADC based on a 4-fold time- interleaving with an extremely low sampling jitter where the limited extinction ratio of the optical switching matrix is compensated for by a real-time digital post-processing, for reducing the spurious tones.
  • the realized ADC has shown a state-of-the-art precision above 7 effective bits up to 40GHz with an instantaneous bandwidth of 200MHz.
  • the scheme demonstrates to approach the theoretical limit imposed by the sampling jitter, and to be easily scalable to larger signal bandwidth with the current photonic technologies.
  • true-time delay Beamforming networks based on photonics have been proposed, either exploiting true-time delay or phase shift.
  • the solutions based on true-time delay have the advantage of avoiding the squint of the beam, even for broadband signals.
  • Photonics has been proposed for this application, thanks to the broad bandwidth it assures.
  • the true-time delay has been proposed by means of chirped fiber Bragg gratings and tunable laser sources. This solution requires one tunable laser per antenna element, therefore it becomes unpractical if the antenna array has several elements.
  • Another technical implementation of true-time delay consists in realizing a set of different delays which propagate the optical signal. This approach lacks the continuity of the delay that would be necessary for a precise beam control.
  • Optical beam-forming based on phase shift is realized by shifting the carrier with respect to the sidebands. This can be done, for example, by exploiting 2- D arrays of pixels based on liquid crystal on silicon and multi-wavelength optical sources. However, such a solution requires that the carrier and its sideband are separated more that the resolution of the pixels.
  • this approach allows the phase of the carriers to be easily controlled, without limitation on the frequency of the RF signal.
  • Embodiments described herein also consider the beamforming in both transmission and reception, and examples can compensate separately the phase fluctuations in the two directions.
  • Figure 1 illustrates a network node 100 according to an example of an embodiment.
  • the network node 100 which may be a basestation or other form of network node, is used for photonic beamforming.
  • the network node may be a basestation, a receiving or transmitting radio module or antenna, or a combination of a basestation and receiving and/or transmitting radio module (s) or antenna(s).
  • the network node 100 comprises an input 101 for receiving a mode locked laser (MLL) signal.
  • the MLL may be provided in the network node 100.
  • the MLL may be remote from the network node 100.
  • the network node 100 also comprises an optical modulator 103 which is coupled to receive the MLL signal and a clock signal 105.
  • a clock derivation module 106 is provided for deriving the clock signal 105 from the MLL signal.
  • Such an embodiment has an advantage in that, in addition to using an MLL signal by an optical modulator for photonic beamforming (for example whereby the MLL signal is used as a laser comb), the MLL signal is also used by a clock derivation module for providing a clock signal to the optical modulator. This has an advantage of providing a more stable and accurate optical modulator for photonic beamforming.
  • the MLL is at a frequency mF.
  • the signal from the MLL may be split to feed an optical modulator in the transmitting and/or the receiving parts.
  • the clock derivation module may comprise circuitry.
  • circuitry includes hardware only circuit implementations, such as implementations in only analogue and or digital circuitry.
  • circuitry also includes implementations including a combination of circuits, including for example a processor, and software.
  • the clock signal 105 can be derived by the clock derivation module 106 which in this example would comprise dividing circuitry for dividing a frequency of a reference clock of the MLL signal by an integer number.
  • the clock derivation module comprises circuitry for obtaining the frequency of the reference clock of the MLL signal and the reference clock frequency may be used for the clock signal .
  • the reference clock is a radio-frequency signal equal to the repetition rate of the optical pulses generated by the MLL, or, equivalently, equal to the frequency detuning between the laser lines constituting the comb generated by the MLL. It is usually provided by the MLL, or it can be derived by detecting the optical signal of the MLL with a photodiode.
  • Figure 2 illustrates a method carried out by a network node 100 according to example embodiments.
  • step 201 the network node 100 receives a mode locked laser (MLL) signal.
  • MLL mode locked laser
  • the MLL signal is input into an optical modulator in step 203.
  • step 205 a clock signal is derived from the MLL signal, and in step 207, the clock signal is used to drive the optical modulator.
  • Figure 3 illustrates an example of a network node according to another embodiment.
  • the optical modulator 103 comprises a first transmitting optical modulator 107, which is coupled to receive the MLL signal from the input 101 .
  • This first transmitting optical modulator 107 is configured to generate a comb signal of continuous waves as shown in the graph 109.
  • the first transmitting optical modulator 107 which configured to be driven by the clock signal 105, may in some examples produce a comb signal of continuous waves in the form of a single sideband modulation.
  • the network node 100 further comprises a second
  • transmitting optical modulator 1 1 1 which is also coupled to receive the MLL signal.
  • the second transmitting optical modulator is driven by an intermediate frequency signal 1 13.
  • the second transmitting optical modulator 1 1 1 may be configured to output a data sideband signal 1 15 for each respective laser line of the comb signal, at a frequency distance of the intermediate frequency from each respective laser line, as shown in the graph 1 15.
  • each data sideband signal may be a single sideband modulation with carrier suppressions (SSB-CS).
  • the example shown in Figure 3 also comprises a first selective phase shifter 1 17 which is coupled to receive the output of the first transmitting optical modulator 107.
  • This first selective phase shifter 1 17 may be configured to selectively control the phase of each continuous wave.
  • the output of the first selective phase shifter 1 17 is coupled to a first demultiplexer 1 19.
  • the first demultiplexer 1 19 may be situated within a transmitter, as shown in Figure 3, or within the network node 100 itself, for example within a basestation.
  • the output from the second transmitting optical modulator 1 1 1 is coupled with the output of the first selective phase shifter 1 17 and is also input into the first demultiplexer 1 19.
  • the coupled signal may first be amplified before being input into the first demultiplexer 1 19.
  • an Erbium Doped Fibre Amplifier (EDFA), as shown in Figure 3, may be provided for amplifying the outputs of the first selective phase shifter 1 17 and second transmitting optical modulator 1 1 1 .
  • the EDFA can be placed either at the network node 100 (e.g. basestation), or at the transmitter.
  • the first demultiplexer 1 19 then separates the pairs of optical signals: each signal pair, composed of the data sideband and the phase-controlled CW generated from the same MLL mode, is selected and sent to an output port of the first demultiplexer 1 19.
  • the signal pair is sent to a photodiode (PD) which generates the beating between the signals, producing the RF signal to be transmitted by the antenna element, with a controlled phase, at frequency F+IF.
  • PD photodiode
  • the clock signal is derived from the MLL reference clock frequency by dividing the frequency of reference clock by an integer number 'm'.
  • alternative methods could be used for deriving the clock signal from the MLL signal.
  • the optical modulator 103 also comprises a receiving optical modulator 121 which is coupled to receive the MLL signal. Again, this receiving optical modulator 121 generates a comb signal of continuous waves.
  • This receiving optical modulator 121 is also driven by the clock signal 105 which is derived from the MLL signal.
  • the output of the receiving optical modulator 121 may be in the form of a single sideband modulation with carrier
  • the MLL signal is also coupled to a second demultiplexer 123.
  • this second demultiplexer may be located within the network node 100 (e.g. the basestation) or in a receiver as shown in Figure 3.
  • the second demultiplexer 123 is configured to separate the modes of the MLL signal and send each mode signal to one of a plurality of receiving antenna elements 125.
  • These receiving antenna elements 125 for example optical modulators for providing single sideband modulation with carrier suppression, SSB-CS) modulate the mode signals with the signals which they receive. This provides modulated signals as shown in the graphs 127. As such, these modulated signals may comprise single sideband modulation with carrier suppression.
  • the modulated signals are then coupled, for example through a multiplexer 129.
  • This multiplexer 129 may be located within either the network node 100 (e.g. basestation) or the receiver.
  • the multiplexer 129 outputs a combined receiver signal. This combined receiver signal is input into a summing block 131 .
  • the summing block 131 may be configured to couple the combined receiver signal with the output of a second selective phase shifter 133.
  • the second selective phase shifter 133 may be coupled between the receiving optical modulator 121 and the summing block 131 (and which may be configured to selectively control the phase of each continuous wave).
  • the summing block 131 can control the reciprocal polarization and phase fluctuation of the two added signals.
  • This control can be implemented, for example, by means of a common PLL.
  • the embodiment of Figure 3 has an advantage in that an MLL signal is used not only as a laser comb, but also to derive a clock signal for controlling an optical modulator.
  • Figure 4 illustrates another example of a network node according to another embodiment.
  • Figure 4 differs from Figure 3 in that the clock signal is taken or derived directly from the frequency of the input MLL signal. Therefore the optical modulator 103 (comprising the first transmitting optical modulator 107 and receiving optical modulator 121 in this example) receives the MLL signal via a de-interleaving module 201 . The second transmitting optical modulator 1 1 1 and the second demultiplexer 123 are also coupled to receive the clock signal derived directly from the MLL signal via the de-interleaving module 201 .
  • Figure 5 illustrates another example of a network node according to another embodiment. Again, the elements of this figure which are similar to those of Figure 3 have been given the same reference numerals.
  • the first selective phase shifter 1 17 is not only coupled to the first transmitting optical modulator 107 to selectively control the phase of each continuous wave, but it is also coupled to receive the output of the second transmitting optical modulator 1 1 1 .
  • the first selective phase shifter 1 17 receives a signal which is the coupling of the signals output from the first and second transmitting optical modulators 107, 1 1 1 .
  • the first demultiplexer 1 19 does not receive the output of the second transmitting optical modulator 1 1 1 , but receives the output of the first selective phase shifter 1 17.
  • the first demultiplexer 1 19 is shown located within the network node 100 (e.g. basestation). It will be appreciated that the first demultiplexer 1 19 may be located within the
  • the second selective phase shifter 133 is instead coupled between the input 101 and the second demultiplexer 123.
  • the second demultiplexer 123 is shown as being located within the network node 100 (e.g. basestation), but it will be appreciated that the second demultiplexer 123 may be located within the receiver as shown in Figure 3. Therefore, in this example, the second selective phase shifter 133 is configured to selectively control the phase of each mode of the MLL signal. From the embodiments described above it can be seen that the MLL signal therefore acts as a very precise clock, and as laser comb. Each mode of the MLL feeds an antenna element and the association between the MLL mode and the antenna element may be determined by the wavelength of the mode, through the wavelength demultiplexers.
  • the LOs are very stable, since they are generated exploiting an electrical clock signal derived by the MLL.
  • each photodiode in the transmitter side receives only two optical signals.
  • the photodiode generates only the desired radio frequency signal to be transmitted. This has an advantage of not requiring radio frequency filtering after the PD, and this increases the efficiency of the scheme.
  • the demultiplexing and multiplexing based on signal wavelength minimize the insertion losses, compared for example with star couplers or splitters, especially for high numbers of antenna elements.
  • the phase control is separated for transmission and reception. This ensures the optimal setting of the beamforming in both directions.
  • optical modulators and/or the phase shifter may be located within the basestation or within the radio modules or antennas.
  • the MLL may also itself be located within the basestation or indeed within the radio modules or antennas. It is further noted that one MLL can be used to serve multiple radio modules or antennas, for example if the MLL is located within the basestation. Alternatively, an MLL could be used to serve a single radio module or antenna, and the MLL could then be located within that particular radio module or antenna.
  • Figure 6 shows a block diagram of a network node 600.
  • the network node 600 is configured for use in photonic beamforming and comprises, a processor 601 and memory 603, the memory 603 containing instructions executable by the processor 601 .
  • the network node 600 is operative to receive a mode locked laser (MLL) signal, input the MLL signal into an optical modulator, derive a clock signal from the MLL signal, and use the clock signal to drive the optical modulator.
  • Figure 7 illustrates a network node 700 according to another example, for use in photonic beamforming.
  • the network node 700 comprises a first module 701 configured to receive a mode locked laser (MLL) signal.
  • a second module 703 is configured to input the MLL signal into an optical modulator.
  • a third module 705 is configured to derive a clock signal from the MLL signal, wherein the clock signal is used to drive the optical modulator.

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Abstract

L'invention concerne un noeud de réseau et un procédé destiné à être utilisé pour la formation de faisceau photonique. Le noeud de réseau comprend une entrée destinée à recevoir un signal de laser verrouillé en mode (MLL). Un modulateur optique est couplé de manière à recevoir le signal MLL et un signal d'horloge. Le noeud de réseau comprend en outre un module de dérivation de signal d'horloge destiné à dériver le signal d'horloge à partir du signal MLL.
PCT/EP2015/068189 2015-08-06 2015-08-06 Noeud de réseau et procédé de formation de faisceau photonique WO2017020968A1 (fr)

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CN115086130A (zh) * 2022-07-08 2022-09-20 清华大学 基于光电振荡器的可调谐k/w波段ofdm雷达通信一体化系统
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JP6636229B1 (ja) * 2019-07-12 2020-01-29 三菱電機株式会社 光制御型フェーズドアレイアンテナ
WO2022024362A1 (fr) * 2020-07-31 2022-02-03 三菱電機株式会社 Dispositif d'antenne réseau à commande optique
JPWO2022024362A1 (fr) * 2020-07-31 2022-02-03
JP7179234B2 (ja) 2020-07-31 2022-11-28 三菱電機株式会社 光制御型アレイアンテナ装置
WO2023212837A1 (fr) * 2022-05-03 2023-11-09 Qualcomm Incorporated Techniques de formation de faisceau sur la base d'un emplacement de référence associé à une image correspondant à une zone cible qui est décalée par rapport à l'emplacement de référence
CN115086130A (zh) * 2022-07-08 2022-09-20 清华大学 基于光电振荡器的可调谐k/w波段ofdm雷达通信一体化系统

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