WO2017014207A1

WO2017014207A1 - Motor

Info

Publication number: WO2017014207A1
Application number: PCT/JP2016/071097
Authority: WO
Inventors: 洋次山田; 晃司三上; 晃尚服部; 横山　誠也
Original assignee: アスモ株式会社
Priority date: 2015-07-21
Filing date: 2016-07-19
Publication date: 2017-01-26

Abstract

A motor includes a stator having a winding, and a rotor. The rotor rotates by receiving a rotational magnetic field generated by drive current supplied to the winding. The winding includes a first winding and a second winding, the first and second windings both being excited at the same timing by the drive current. The first winding and the second winding are connected in series. The rotor includes a first magnetic pole section and a second magnetic pole section. The second magnetic pole section faces the second winding at the rotation position of the rotor at which the first magnetic pole section faces the first winding. The magnetic force exerted on the stator by the second magnetic pole section is weaker than that exerted by the first magnetic pole section.

Description

motor

The present invention relates to a motor.

Conventionally, a permanent magnet motor such as a brushless motor includes, for example, a stator in which a winding is wound around a stator core and a rotor having a permanent magnet facing the stator as a magnetic pole, as shown in Patent Document 1, for example. The rotor rotates by receiving a rotating magnetic field generated by supplying a drive current to the winding of the stator.

JP 2014-135852 A

In the permanent magnet motor as described above, the higher the rotor is driven, the greater the induced voltage generated in the stator winding due to the increase of the linkage flux by the permanent magnet of the rotor, and this induced voltage decreases the motor output. This hinders high motor rotation. Therefore, by reducing the magnetic force of the rotor magnetic poles, for example, by reducing the size of the permanent magnets of the rotor, it is possible to suppress the induced voltage when the rotor rotates at a high speed. Therefore, there is still room for improvement in this respect.

An object of the present invention is to provide a motor capable of increasing the rotation speed while suppressing a decrease in torque.

To achieve the above object, a motor according to one aspect of the present invention includes a stator having windings and a rotor. The rotor rotates in response to a rotating magnetic field generated by supplying a driving current to the winding. The winding includes a first winding and a second winding, and the first winding and the second winding are excited at the same timing by the drive current. The first winding and the second winding are connected in series. The rotor includes a first magnetic pole part and a second magnetic pole part. The second magnetic pole portion opposes the second winding at a rotational position of the rotor where the first magnetic pole portion opposes the first winding. The second magnetic pole part is weaker in magnetic force applied to the stator than the first magnetic pole part.

1 is a plan view of a motor according to a first embodiment of the present invention. It is an electric circuit diagram which shows the connection aspect of the coil | winding of FIG. (A) is a graph which shows the change of the induced voltage which arises in U phase winding at the time of rotor rotation in the motor of FIG. 1, (b) is the change of the induced voltage which arises in U phase winding at the time of rotor rotation in a conventional structure. It is a graph which shows. It is a top view of the rotor of another example of a 1st embodiment. It is a top view of the rotor of another example of a 1st embodiment. It is a top view of the rotor of another example of a 1st embodiment. It is an electric circuit diagram which shows the connection aspect of the coil | winding in the other example of 1st Embodiment. It is a top view of the motor of another example of a 1st embodiment. It is a top view of the rotor of another example. It is a top view of the motor concerning a 2nd embodiment of the present invention. It is a perspective view of the rotor of FIG. FIG. 11 is a sectional view taken along line 4-4 in FIG. (A) is a graph which shows the change of the induced voltage which arises in U phase winding at the time of rotor rotation in the motor of FIG. 10, (b) is the change of the induced voltage which arises in U phase winding at the time of rotor rotation in a conventional structure. It is a graph which shows. It is a perspective view of the rotor of another example of 2nd Embodiment. It is a disassembled perspective view of the rotor of another example of FIG. It is a disassembled perspective view of the rotor of another example of 2nd Embodiment. It is a top view of the rotor of another example. It is a disassembled perspective view of the rotor of another example of 2nd Embodiment. It is an electric circuit diagram which shows the connection mode of the coil | winding in another example of 2nd Embodiment. It is a top view of the motor of another example of a 2nd embodiment. (A) is a top view of the motor of 3rd Embodiment of this invention, (b) is a top view of the rotor of the same form. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is an electric circuit diagram which shows the connection aspect of the coil | winding in the other example of 3rd Embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the motor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. It is a top view of the rotor of another example of a 3rd embodiment. (A) is a top view of the motor which concerns on embodiment, (b) is a top view of a rotor. (A) (b) It is explanatory drawing for demonstrating the magnetic effect | action at the time of the field-weakening control in the motor of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment. It is a top view of the rotor of another example of 4th Embodiment.

Hereinafter, a first embodiment of the motor will be described.
As shown in FIG. 1, the motor 10 of the present embodiment is configured as a brushless motor, and a rotor 21 is arranged inside an annular stator 11.

[Structure of stator]
The stator 11 includes a stator core 12 and a winding 13 wound around the stator core 12. The stator core 12 is formed of a magnetic metal in a substantially annular shape, and has twelve teeth 12a extending radially inward at equal angular intervals in the circumferential direction.

Twelve windings 13 having the same number as the teeth 12a are provided, and each tooth 12a is wound in the same direction by concentrated winding. That is, twelve windings 13 are provided at equal intervals in the circumferential direction (30 ° intervals). The windings 13 are classified into three phases according to the three-phase driving currents (U phase, V phase, W phase) supplied, and U1, V1, W1, U2 in order counterclockwise in FIG. , V2, W2, U3, V3, W3, U4, V4, W4.

Referring to each phase, the U-phase windings U1 to U4 are arranged at equal intervals in the circumferential direction (90 ° intervals). Similarly, the V-phase windings V1 to V4 are arranged at equal circumferential intervals (90 ° intervals). Similarly, the W-phase windings W1 to W4 are arranged at equal intervals in the circumferential direction (90 ° intervals).

Further, as shown in FIG. 2, the windings 13 are connected in series for each phase. That is, the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4 each constitute a series circuit. In this embodiment, a series circuit of U-phase windings U1 to U4, a series circuit of V-phase windings V1 to V4, and a series circuit of W-phase windings W1 to W4 are star-connected.

[Configuration of rotor]
As shown in FIG. 1, the rotor 21 accommodated in the radially inner space of the stator 11 (the teeth 12 a) includes a rotor core 22 and eight permanent magnets 23 fixed to the outer peripheral surface of the rotor core 22. Yes. The permanent magnet 23 is, for example, an anisotropic sintered magnet, and is composed of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like.

The rotor core 22 is formed of a magnetic metal in a substantially cylindrical shape, and a rotating shaft 24 is fixed at the center. On the outer peripheral surface of the rotor core 22, a pair of first and second

magnet fixing surfaces

22 a and 22 b each having an arc shape centered on the axis L when viewed from the direction of the axis L of the rotating shaft 24 is formed. The first magnet fixing surface 22a and the second magnet fixing surface 22b are alternately formed in the circumferential direction, and their circumferential widths (open angles around the axis L) are all equal (that is, 90 °). Yes. Further, the outer diameters of the pair of first magnet fixing surfaces 22a are the same, and the outer diameters of the pair of second magnet fixing surfaces 22b are also the same. The outer diameter of the second magnet fixing surface 22b is smaller than the outer diameter of the first magnet fixing surface 22a.

Two permanent magnets 23 are fixed to each of the magnet fixing surfaces 22 a and 22 b, and a total of eight permanent magnets 23 are provided on the outer peripheral surface of the rotor core 22. Each permanent magnet 23 has the same material and the same shape, and the outer peripheral surface of each permanent magnet 23 has an arc shape centered on the axis L when viewed from the direction of the axis L of the rotating shaft 24. Further, the opening angle (circumferential width) around the axis L of each permanent magnet 23 is 45 °. Each permanent magnet 23 is formed such that the magnetic orientation is directed in the radial direction, and the magnetic poles appearing on the outer circumferential side are alternately arranged in the circumferential direction. Each of these permanent magnets 23 constitutes a magnetic pole of the rotor 21. That is, the rotor 21 is configured as an 8-pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (45 ° intervals).

In the rotor 21, four

N pole portions

25 a and 25 b each having an N pole permanent magnet 23 on the outer peripheral side are configured at equal circumferential intervals (90 ° intervals). The

N pole portions

25a and 25b include two first N pole portions 25a made up of N pole permanent magnets 23 (permanent magnet N1 in FIG. 1) provided on each first magnet fixing surface 22a and each second pole portion 25a. It is divided into two second N-pole portions 25b made of N-pole permanent magnets 23 (permanent magnet N2 in FIG. 1) provided on the magnet fixing surface 22b and positioned radially inward from the permanent magnet N1.

The outer peripheral surface of the second N pole portion 25b (the outer peripheral surface of the permanent magnet N2) is located radially inward from the outer peripheral surface of the first N pole portion 25a (the outer peripheral surface of the permanent magnet N1). In addition, the pair of first N pole portions 25a are provided at 180 ° facing positions in the circumferential direction, and similarly, the pair of second N pole portions 25b are also provided at 180 ° facing positions in the circumferential direction. That is, the first N-pole portions 25a and the second N-pole portions 25b are alternately provided at equal circumferential intervals (90 ° intervals) in the circumferential direction.

The configuration of the N pole of the rotor 21 is the same for the S pole. That is, the four

south pole portions

26a and 26b each formed by the permanent magnet 23 having the south pole on the outer circumferential side are configured at equal intervals in the circumferential direction (90 ° intervals). The

S pole portions

26a and 26b include two first S pole portions 26a made of S pole permanent magnets 23 (permanent magnet S1 in FIG. 1) provided on each first magnet fixing surface 22a, and each second. It is divided into two second S pole portions 26b formed of S pole permanent magnets 23 (permanent magnet S2 in FIG. 1) which are provided on the magnet fixing surface 22b and located radially inward of the permanent magnet S1.

The outer peripheral surface of the second S pole portion 26b (the outer peripheral surface of the permanent magnet S2) is positioned radially inward from the outer peripheral surface of the first S pole portion 26a (the outer peripheral surface of the permanent magnet S1). In addition, the pair of first S pole portions 26a is provided at a 180 ° facing position in the circumferential direction, and the pair of second S pole portions 26b is also provided at a 180 ° facing position in the circumferential direction. That is, the first S pole portion 26a and the second S pole portion 26b are alternately provided with the center positions in the circumferential direction at equal angular intervals (90 ° intervals).

The rotor 21 includes a first N pole portion 25a and a first S pole portion 26a as first magnetic pole portions, and a second N pole portion 25b and a second S pole portion 26b as second magnetic pole portions.
Next, the operation of this embodiment will be described.

A three-phase drive current (AC) having a phase difference of 120 ° is supplied from a drive circuit (not shown) to the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4, respectively. Then, the windings U1 to W4 are excited at the same timing for each phase to generate a rotating magnetic field in the stator 11, and the rotor 21 rotates based on the rotating magnetic field. At this time, the magnetic poles formed on the stator 11 by the supply of the three-phase drive current are the same for the windings U1 to W4 of each phase.

Here, the number of pole pairs of the rotor 21 (that is, the number of each of the

N pole portions

25a and 25b and the

S pole portions

26a and 26b) is the same as the number of the windings U1 to W4 of each phase (in this embodiment, “4 ]). Thus, when the rotor 21 rotates, for example, when one of the

N pole portions

25a and 25b is opposed to the U phase winding U1 in the radial direction, the other

N pole portions

25a and 25b are connected to the U phase windings U2 to U2. U4 is opposed to each in the radial direction (see FIG. 1).

At this time, since the outer peripheral surface of the second N pole portion 25b (the surface facing the stator 11) is located on the radially inner side with respect to the outer peripheral surface of the first N pole portion 25a, the radial direction between the second N pole portion 25b and the stator 11 is provided. The air gap is wider at the second N pole portion 25b than at the first N pole portion 25a. Thus, the magnetic force applied to the stator 11 (for example, the U-phase windings U1 to U4) by the

N pole portions

25a and 25b of the rotor 21 is weaker at the second N pole portion 25b than at the first N pole portion 25a. The same applies to the

S pole portions

26a and 26b of the rotor 21.

Thus, for example, as shown in FIG. 1, the U-phase windings U2 and U2 facing the second N-pole portions 25b at the rotational positions at which the N-

pole portions

25a and 25b of the rotor 21 respectively face the U-phase windings U1 to U4. The interlinkage magnetic flux interlinking U4 is smaller than the interlinkage magnetic flux interlinking U-phase windings U1, U3 facing the first N pole portion 25a. Accordingly, the induced voltage generated in the U-phase windings U2 and U4 facing the second N pole portion 25b is smaller than the induced voltage generated in the U-phase windings U1 and U3 facing the first N pole portion 25a.

Here, FIG. 3A shows the change in the induced voltage generated in the U-phase windings U1 to U4 during the rotation of the rotor in the present embodiment in a predetermined rotation range (90 °), and FIG. 4 shows changes in the induced voltage generated in the U-phase windings U1 to U4 during rotation of the rotor in the conventional configuration in a predetermined rotation range (90 °). The conventional configuration is a configuration in which the magnetic poles of the rotor are uniform, that is, a configuration in which the rotor core 22 is cylindrical and the radial positions of the permanent magnets N2 and S2 are the same as those of the permanent magnets N1 and S1.

In the conventional configuration, since the magnetic poles of the rotor are uniform, the change of the interlinkage magnetic flux in each of the U-phase windings U1 to U4 is also uniform. For this reason, as shown in FIG. 3B, when the rotor 21 rotates, the same induced voltage vx is generated in the U-phase windings U1 to U4. When the U-phase windings U1 to U4 are in series, the combined induced voltage vu ′ obtained by synthesizing the induced voltage vx generated in each U-phase winding U1 to U4 is the induced voltage vx of each U-phase winding U1 to U4. The sum (that is, four times the induced voltage vx).

On the other hand, as shown in FIG. 3 (a), in the present embodiment, the second N pole portion 25b and the second S pole portion 26b are more stable than the first N pole portion 25a and the first S pole portion 26a, respectively. The magnetic force to U1 to U4) is weak. As a result, the second N-pole portion 25b and the second N-pole portion 25b and the first S-pole portion 26a with respect to the induced voltage vx generated in the U-phase windings U1 to U4 (eg, U-phase windings U1 and U3) facing the first N-pole portion 25a and the first S-pole portion 26a The induced voltage vy generated in the U-phase windings U1 to U4 (for example, U-phase windings U2 and U4) facing the 2S pole portion 26b is reduced. Therefore, a combined induced voltage vu (vu = vx × 2 + vy × 2) obtained by synthesizing the induced voltages of the U-phase windings U1 to U4 is a pair of U-phases facing the second N-pole portion 25b and the second S-pole portion 26b. It decreases by the amount of decrease of the induced voltage vy in the winding, and becomes smaller than the combined induced voltage vu ′ in the conventional configuration shown in FIG. Here, the combined induced voltage vu of the U-phase windings U1 to U4 has been described as an example, but the second N-pole portion 25b and the second-phase windings V1 to V4 and the W-phase windings W1 to W4 are similarly described. A decrease in the synthesis induced voltage due to the 2S pole portion 26b occurs.

Next, characteristic advantages of this embodiment will be described.
(1) The windings 13 of the stator 11 are composed of four U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4, respectively, corresponding to the supplied three-phase driving current. Thus, the four windings of each phase are connected in series. That is, the winding 13 of the stator 11 includes at least two windings (first winding and second winding) connected in series in each phase.

Further, the N pole of the rotor 21 includes a first N pole portion 25a having a permanent magnet N1, and the first N pole portion 25a is a first winding (for example, U phase winding) in any of the U, V, and W phases. And a second N pole portion 25b facing the second winding (for example, U-phase windings U2 and U4) in phase at the rotational position of the rotor 21 facing the lines U1 and U3). The second N pole portion 25b is configured such that the magnetic force applied to the stator 11 is weaker than that of the first N pole portion 25a. Similarly, in the S pole of the rotor 21, the first S pole portion 26 a having the permanent magnet S 1 and the first S pole portion 26 a of the first winding (for example, U, V, or W phase) And a second S pole portion 26b facing the second winding of the same phase (for example, the U-phase windings U2 and U4) at the rotational position of the rotor 21 facing the U-phase windings U1 and U3). The second S pole portion 26b is configured such that the magnetic force applied to the stator 11 is weaker than that of the first S pole portion 26a.

As described above, in the present embodiment, the magnetic force (the magnetic force applied to the stator 11) of all the N pole portions (or S pole portions) facing the in-phase windings 13 in the rotor 21 is not weakened, but part of them. Are configured to weaken the magnetic force of the magnetic pole portions (second N pole portion 25b, second S pole portion 26b). As a result, it is possible to suppress the combined induction voltage (for example, the combined induction voltage vu of the U phase) generated in the in-phase winding 13 by the magnetic poles of the rotor 21 as much as possible while suppressing the torque reduction as much as possible. High rotation can be achieved.

Note that, in the winding mode in which the windings 13 are connected in series in each phase as in the present embodiment, the sum of the induced voltages generated in the respective windings for each phase becomes the combined induced voltage. The voltage tends to increase. For this reason, in the configuration in which the winding 13 is in series in each phase, the second N pole portion 25b and the second N pole portion 25b and the second S pole portion 26b are weakened by weakening the magnetic force of the second N pole portion 25b and the second S pole portion 26b as described above. The effect of suppressing the combined induction voltage by the second S pole portion 26b can be obtained more remarkably, and it is more preferable to increase the rotation of the motor 10.

(2) 2n pieces of U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4 (n is an integer of 2 or more, and in this embodiment, n = 2) The number of first and second

N pole portions

25a and 25b (first and second

S pole portions

26a and 26b) of the rotor 21 is n (that is, two). That is, according to this configuration, the number of windings in each phase (the number of U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4) is an even number of 4 or more. The first and second

N pole portions

25a and 25b (first and second

S pole portions

26a and 26b) of the rotor 21 are configured in the same number (half the number of windings in each phase).

Therefore, the first and second

N pole portions

25a and 25b (first and second

S pole portions

26a and 26b) of the rotor 21 can be alternately provided at equal intervals in the circumferential direction. As a result, the first and second

N pole portions

25a and 25b (first and second

S pole portions

26a and 26b) having different magnetic forces and masses are arranged in a balanced manner in the circumferential direction. A mechanically balanced structure can be obtained.

(3) The first and second

N pole portions

25a, 25b (first and second

S pole portions

26a, 26b) are configured to have permanent magnets N1, N2 (permanent magnets S1, S2), respectively. The outer peripheral surface of the portion 25b (second S pole portion 26b) is configured to be positioned radially inward from the outer peripheral surface of the first N pole portion 25a (second S pole portion 26b). According to this configuration, while the permanent magnets N1 and N2 (permanent magnets S1 and S2) are the same magnet (the same material and the same shape magnet), the magnetic force applied from the rotor 21 to the stator 11 is the first N pole portion 25a ( The second S pole part 25b (second S pole part 26b) can be weaker than the first S pole part 26a), which is advantageous in terms of component management.

In addition, you may change the said embodiment as follows.
Although not specifically mentioned in the above embodiment, field weakening control may be performed when the rotor 21 is rotating at a high speed. In the above embodiment, by providing the rotor 21 with the second N pole portion 25b (second S pole portion 26b), the field-weakening current supplied to the winding 13 can be kept small. Since the field weakening current can be reduced, the permanent magnets N1, N2, S1, and S2 are difficult to demagnetize during field weakening control, and the copper loss of the winding 13 can be suppressed. In other words, since the amount of flux linkage that can be reduced with the same amount of field-weakening current increases, higher rotation by field-weakening control can be obtained more effectively.

In the above embodiment, the permanent magnets N1 and N2 (permanent magnets S1 and S2) are the same magnet, and the permanent magnet N2 (permanent magnet S2) is disposed radially inward of the permanent magnet N1 (permanent magnet S1). Thus, the magnetic force applied to the stator 11 by the second N pole portion 25b (second S pole portion 26b) is made weaker than that of the first N pole portion 25a (first S pole portion 26a). However, the configuration for making the magnetic force applied to the stator 11 weaker at the second N pole portion 25b (second S pole portion 26b) than at the first N pole portion 25a (first S pole portion 26a) is limited to the above embodiment. is not.

For example, as shown in FIG. 4, the opening angle θ2 (opening angle about the axis L of the rotating shaft 24) of each permanent magnet N2, S2 of the second N pole portion 25b and the second S pole portion 26b is defined as the first N pole. The opening angle θ1 of each permanent magnet N1, S1 of the portion 25a and the first S pole portion 26a may be set narrower. According to such a configuration, the magnetic force applied from the rotor 21 to the stator 11 by the simple shape change of the permanent magnets N2 and S2 is greater than the first N pole portion 25a (first S pole portion 26a) than the second N pole portion 25b (first step). 2S pole portion 26b) can be weakened, and as a result, the induced voltage generated in winding 13 can be kept small. The rotor core 22 has a simple configuration in which the outer peripheral surface is circular in an axial view (that is, a configuration in which there is no step by providing the first and second

magnet fixing surfaces

22a and 22b on the outer peripheral surface of the rotor core 22). Is possible.

Further, as shown in FIG. 5, for example, the radial thickness T2 of the permanent magnet N2 (permanent magnet S2) is made thinner than the radial thickness T1 of the permanent magnet N1 (permanent magnet S1), so that the stator 21 can move to the stator. 11 may be weaker at the second N pole portion 25b (second S pole portion 26b) than at the first N pole portion 25a (first S pole portion 26a). Even with such a configuration, the magnetic force applied from the rotor 21 to the stator 11 by the simple shape change of the permanent magnets N1 and N2 is greater than the first N pole portion 25a (first S pole portion 26a) than the second N pole portion 25b (second S). The pole portion 26b) can be weakened, and as a result, the induced voltage generated in the winding 13 can be kept small.

In the example shown in FIGS. 4 and 5, the magnetic force applied from the rotor 21 to the stator 11 by changing the shape of the permanent magnets N1 and N2 is greater than the first N pole portion 25a (first S pole portion 26a). Although it is weakened by (2nd S pole part 26b), it is not restricted to this. For example, by setting the residual magnetic flux density of the permanent magnet N2 (permanent magnet S2) to be smaller than the residual magnetic flux density of the permanent magnet N1 (permanent magnet S1), the magnetic force applied from the rotor 21 to the stator 11 is the first N pole portion 25a ( It can be weaker than the first S pole part 26a) by the second N pole part 25b (second S pole part 26b). According to this configuration, the outer peripheral surface of the rotor core 22 can be made circular when viewed in the axial direction, and the shapes of the permanent magnets N1, N2, S1, and S2 can all be the same.

In the above embodiment, the first N pole portions 25a and the second N pole portions 25b in the rotor 21 are provided at positions opposed to each other by 180 ° in the circumferential direction. The second S pole portions 26b are provided at 180 ° facing positions in the circumferential direction. That is, the first N pole portion 25a and the second N pole portion 25b are alternately arranged in the circumferential direction, and the first S pole portion 26a and the second S pole portion 26b are also alternately arranged in the circumferential direction. It is not something.

For example, as shown in FIG. 6, the second N pole portion 25b may be provided at a position where the first N pole portion 25a is opposed to 180 °, and the second S pole portion 26b may be provided at a position where the first S pole portion 26a is opposed to 180 °. In the example of FIG. 6, the first magnet fixing surface 22a is formed on one half of the outer periphery of the rotor core 22, and the second magnet fixing surface 22b is formed on the other half. The first N pole portion 25a and the first S pole portion 26a are alternately provided on one half of the outer periphery of the rotor core 22 (first magnet fixing surface 22a), and the second N pole is provided on the other half (second magnet fixing surface 22b). The portions 25b and the second S pole portions 26b are alternately provided. Even with such a configuration, the induced voltage generated in the winding 13 can be kept small, and the motor 10 can be rotated at a high speed.

In the above embodiment, for example, in the N pole of the rotor 21, the first N pole portion 25a and the second N pole portion 25b are configured with the same number (half the number of windings 13 of each phase, which is two). The number is not necessarily the same. For example, the number of the first N pole portions 25a may be three (or one), and the number of the second N pole portions 25b may be one (or three). The same change may be made in the S pole of the rotor (first and second

S pole portions

26a, 26b).

In the above embodiment, the second N pole portion 25b and the second S pole portion 26b having a weak magnetic force are provided in the N pole and the S pole of the rotor 21, respectively, but the present invention is not particularly limited thereto. That is, a magnetic pole part (second N pole part 25b or second S pole part 26b) having a weak magnetic force is provided only on one pole of the rotor 21, and all the other poles are the same magnetic pole part (first N pole part 25a or first S pole). Part 26a).

In the above embodiment, the windings of each phase, that is, the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4 are connected in series. However, the winding mode may be changed as appropriate.

For example, in the example shown in FIG. 7, in the U phase, the windings U1 and U2 are connected in series, and the windings U3 and U4 are connected in series, and the series pair of the windings U1 and U2 and the windings U3 and U4. Are connected in parallel. Similarly, in the V phase, the windings V1 and V2 are connected in series, and the windings V3 and V4 are connected in series. The series pair of the windings V1 and V2 and the series pair of the windings V3 and V4 are parallel. It is connected. Similarly, in the W phase, the windings W1, W2 are connected in series, and the windings W3, W4 are connected in series. The series pair of the windings W1, W2 and the series pair of the windings W3, W4 Are connected in parallel.

When the winding mode of FIG. 7 is applied to the configuration of the rotor 21 of the above-described embodiment (see FIG. 1), for example, in the U phase, the windings U1 and U3 have induced voltages of the same magnitude (the induced voltage). vx) occurs, and induced voltages (the induced voltages vy) having the same magnitude are generated in the windings U2 and U4. For this reason, the combined induction voltage generated in the series pair of the windings U1 and U2 and the combined induction voltage generated in the series pair of the windings U3 and U4 are substantially equal (vx + vy). Thereby, the reduction of the induced voltage due to the provision of the second N pole part 25b (second S pole part 26b) having a weaker magnetic force than the first N pole part 25a (first S pole part 26a) is caused by the series connection of the windings U1 and U2. It will always occur in both the pair and the series pair of windings U3, U4. Since the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are parallel, the combined induction voltage vu in the entire U-phase winding is the combined induction voltage of the series pair of the windings U1 and U2. (And the combined induction voltage of the series pair of windings U3 and U4) (vx + vy), and the combined induction voltage vu can be effectively suppressed.

Here, when the winding U2 and the winding U3 are interchanged in the example shown in FIG. 7, that is, the windings U1, U3 having the same magnitude of the induced voltage are connected in series and the magnitude of the induced voltage is the same. Consider the case where the windings U2 and U4 are in series. In this case, the reduction of the induced voltage due to the provision of the second N pole portion 25b (second S pole portion 26b) having a lower magnetic force than the first N pole portion 25a (first S pole portion 26a) is caused by the series connection of the windings U2 and U4. It occurs only in one of the series and the pair of windings U1 and U3, and the induced voltage does not decrease on the other side. And since the series pair of winding U1, U3 and the series pair of winding U2, U4 are parallel, it is disadvantageous at the point which suppresses the synthetic | combination induced voltage in the whole U-phase winding effectively. Similarly, when the U-phase windings U1 to U4 are arranged in parallel, similarly, it is disadvantageous in that the combined induced voltage in the entire U-phase winding is effectively suppressed.

As described above, when the windings are connected in series in each phase, the first N pole portion 25a (or the first S pole portion 26a) and the second N pole portion 25b (or the second S pole) at a predetermined rotational position of the rotor 21. The windings (for example, the U-phase winding U1 and the U-phase winding U2) opposed to the portion 26b) are connected in series. As a result, the weak induced voltage generated in the windings of the same phase and the strong induced voltage can be added to obtain a combined induced voltage, and the combined induced voltage in each phase can be effectively suppressed.

In the example of FIG. 7, in the U phase, the windings U1, U2 are a series pair and the windings U3, U4 are a series pair, but the windings U1, U4 and the windings U2, U3 are respectively Similar effects can be obtained as a series pair. The same change can be made in the V phase and the W phase.

In the example of FIG. 7, in the U phase, the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are connected in parallel. However, the present invention is not particularly limited to this, and the winding U1 , U2 and the series pair of windings U3, U4 may be separated, and a pair of inverters may be provided to supply a U-phase drive current to each of the separated series pairs. The same effect can be obtained by this configuration. The same change can be made in the V phase and the W phase.

Moreover, in the example shown in the said embodiment (refer FIG. 2) and FIG. 7, although the connection aspect of the coil | winding was made into the star connection, it is good also as not only this but a delta connection, for example.
In the above embodiment, the rotor 21 has 8 poles and the number of windings 13 of the stator 11 is 12 (that is, the motor configuration has 8 poles and 12 slots). The number of can be appropriately changed according to the configuration. For example, the number of poles of the rotor 21 and the number of windings 13 are appropriately changed so that the relationship between the number of poles of the rotor 21 and the number of windings 13 is 2n: 3n (where n is an integer of 2 or more). May be.

In the case of a configuration of 6 poles 9 slots, 10 poles 15 slots, etc. (when the number of poles of the rotor 21 and the greatest common divisor n of the number of windings 13 is an odd number), the number of pole pairs of the rotor 21 is an odd number, That is, the number of N poles and S poles is an odd number. For this reason, the number of the 1st N pole part 25a (1st S pole part 26a) and the number of the 2nd N pole part 25b (2nd S pole part 26b) cannot be made the same number, but it becomes a magnetically unbalanced structure. . In that regard, as in the above embodiment, in the configuration in which the greatest common divisor n of the number of poles of the rotor 21 and the number of windings 13 is an even number, the number of first N pole portions 25a (first S pole portions 26a) and second N The number of pole portions 25b (second S pole portions 26b) can be made the same, and a magnetically balanced configuration can be achieved.

The relationship between the number of poles of the rotor 21 and the number of windings 13 is not necessarily 2n: 3n (where n is an integer equal to or greater than 2), for example, 10 poles 12 slots, 14 poles 12 slots, etc. It may be configured.

FIG. 8 shows an example of a motor 30 composed of 10 poles and 12 slots. In the example of FIG. 8, the same components as those in the above embodiment are denoted by the same reference numerals, detailed description thereof will be omitted, and different portions will be described in detail.

In the motor 30 shown in FIG. 8, the twelve windings 13 of the stator 11 are classified according to the three-phase driving current (U phase, V phase, W phase) supplied, and in FIG. In this order, U1, bar U2, bar V1, V2, W1, bar W2, bar U1, U2, V1, bar V2, bar W1, W2. In addition, U phase winding bar U1, bar U2, V phase winding bar V1 with respect to U phase windings U1, U2, V phase windings V1, V2 and W phase windings W1, W2 constituted by positive windings. , Bar V2, W-phase winding bar W1, bar W2 are constituted by reverse winding. Further, the U-phase winding U1 and the bar U1 are placed at positions facing each other by 180 °, and similarly, the U-phase winding U2 and the bar U2 are placed at positions facing each other by 180 °. The same applies to the other phases (V phase and W phase).

U-phase windings U1, U2, U1 and U2 are connected in series. Similarly, V-phase windings V1, V2, V1 and V2 are connected in series, and W-phase winding W1. , W2, bar W1, and bar W2 are connected in series. The U-phase windings U1, U2, U1 and U2 are supplied with U-phase drive current. As a result, the reverse winding U-phase winding bars U1 and U2 are always excited with the opposite polarity (reverse phase) with respect to the forward winding U-phase windings U1 and U2, but the excitation timing is the same. . The same applies to the other phases (V phase and W phase).

The rotor 21 of the motor 30 is a 10-pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (36 ° intervals), and is configured as the same type as the rotor 21 shown in FIG. Yes. That is, the rotor 21 includes a first N pole portion 25a made of a permanent magnet N1, a second N pole portion 25b made of a permanent magnet N2, a first S pole portion 26a made of a permanent magnet S1, and a second S pole made of a permanent magnet S2. The permanent magnets N2 and S2 are configured to be thinner in the radial direction than the permanent magnets N1 and S1.

Further, the first N pole portion 25a and the first S pole portion 26a (permanent magnets N1, S1) are alternately provided in the half circumference (right half circumference in FIG. 8) of the rotor 21, and the second N pole portion 25b and the second S pole portion 26b ( The permanent magnets N2 and S2) are alternately provided in the remaining half circumference (left half circumference in FIG. 8) of the rotor 21. Further, the second S pole portion 26b is located on the opposite side (180 ° facing position) of the first N pole portion 25a, and the second N pole portion 25b is located on the opposite side of the first S pole portion 26a (180 ° facing position). Is configured to be located.

In the example of the 10-pole rotor of FIG. 8, the first N pole portion 25a is composed of two, the first S pole portion 26a is three, the second N pole portion 25b is three, and the second S pole portion 26b is composed of two. However, the present invention is not limited to this, and the first N-pole portion 25a may be composed of three, the first S-pole portion 26a may be two, the second N-pole portion 25b may be two, and the second S-pole portion 26b may be three. . In the example shown in FIG. 8, the same type of rotor 21 as in the example of FIG. 5 is used, but the same type as the rotor 21 shown in the above embodiment and FIG. 4 may be used.

In the above configuration, when the rotor 21 rotates, for example, when the first S pole portion 26a faces the U phase winding U1 in the radial direction, the second N pole portion 25b is connected to the U phase winding bar U1 on the opposite side in the circumferential direction. Opposing in the radial direction (see FIG. 8). Here, since the permanent magnet N2 constituting the second N pole portion 25b is thinner in the radial direction than the permanent magnet S1 constituting the first S pole portion 26a, the second N pole portion 25b is smaller than the first S pole portion 26a. Thus, the magnetic force applied to the stator 11 is weakened.

In this way, the magnetic pole portions (for example, the first S pole portion 26a and the second N pole portion) of opposite polarity respectively opposed to the windings 13 (for example, the U-phase winding U1 and the bar U1) excited in opposite phases (same timing). 25b), the magnetic forces are different from each other (that is, the other magnetic force is weaker than the other). As a result, it is possible to suppress the combined induction voltage (for example, the combined induction voltage of the U-phase winding U1 and the bar U1) generated in the antiphase winding 13 by the magnetic poles of the rotor 21 while suppressing the torque reduction as much as possible. As a result, the rotation of the motor 30 can be increased.

In the example of the rotor 21 shown in FIG. 8, the first N pole portion 25 a and the first S pole portion 26 a are provided on the half circumference of the rotor 21, and the second N pole portion 25 b and the second S pole portion 26 b are provided on the other half circumference of the rotor 21. It was. However, the arrangement of the magnetic pole portions of the rotor 21 is not particularly limited to this, and the second S pole portion 26b is located on the opposite side of the first N pole portion 25a in the circumferential direction, and the first S pole portion 26a is opposite in the circumferential direction. If the 2nd N pole part 25b is located in the side, the arrangement | positioning of each magnetic pole part of the rotor 21 can be changed suitably.

Further, in the stator 11, it is not necessary that all the U-phase windings U1, U2, bar U1, and bar U2 are connected in series, and a pair of windings U1, U1 and a pair of windings U2, U2 are provided. It is good also as a structure which made each another separate serial pair. Moreover, it can change similarly also in V phase and W phase.

8 shows an example of 10 poles and 12 slots, but the present invention can also be applied to a 14 poles and 12 slots structure. Further, the present invention can also be applied to a configuration in which the number of rotor poles and the number of slots of 10 poles and 12 slots (or 14 poles and 12 slots) are equal.

FIG. 9 shows an example of the rotor 21 in the configuration of 20 poles and 24 slots. In the example of FIG. 9, the strong magnetic pole group Ma in which the first N pole portion 25a and the first S pole portion 26a are alternately arranged in the circumferential direction, and the second N pole portion 25b and the second S pole portion 26b are alternately arranged in the circumferential direction. The weak magnetic pole groups Mb thus arranged are alternately arranged at an occupation angle of 90 ° in the circumferential direction of the rotor 21. Thus, by arranging the strong magnetic pole group Ma and the weak magnetic pole group Mb in a balanced manner in the circumferential direction, the rotor 21 can be magnetically and mechanically balanced.

In the above embodiment, for example, the N pole of the rotor 21 is composed of only the first N pole portion 25a and the second N pole portion 25b. However, for example, the magnetic force applied to the stator 11 is weaker than that of the second N pole portion 25b. You may provide the 3rd N pole part.

In the above embodiment, the permanent magnet 23 is a sintered magnet, but other than this, for example, a bonded magnet may be used.
In the above embodiment, the present invention is embodied in the inner rotor type motor 10 in which the rotor 21 is disposed on the inner peripheral side of the stator 11, but the invention is not particularly limited thereto, and the rotor is disposed on the outer peripheral side of the stator. The outer rotor type motor may be embodied.

In the above embodiment, the present invention is embodied in the radial gap type motor 10 in which the stator 11 and the rotor 21 are opposed to each other in the radial direction. However, the present invention is not particularly limited thereto, and the stator and the rotor are in the axial direction. The present invention may be applied to an axial gap type motor that faces the motor.

-You may combine embodiment mentioned above and each modification suitably.
Hereinafter, a second embodiment of the motor will be described.
As shown in FIG. 10, the motor 110 of the present embodiment is configured as a brushless motor, and is configured by arranging a rotor 121 inside an annular stator 11. Since the configuration of the stator 11 is the same as that of the stator 11 of the first embodiment, detailed description thereof is omitted. The winding 13 of the stator 11 is configured similarly to the winding 13 of the first embodiment, and has the configuration shown in FIG.

[Configuration of rotor]
As shown in FIGS. 10, 11 and 12, the rotor 121 is disposed between the rotating shaft 122, a pair of

rotor cores

123n and 123s having the same shape, and the axial direction of the pair of

rotor cores

123n and 123s. And a permanent magnet 124. The

rotor cores

123n and 123s are both made of a magnetic metal. In the following description, the rotor core that contacts the N pole side end surface of the permanent magnet 124 magnetized in the axial direction is referred to as the N pole side rotor core 123n, and the rotor core that contacts the S pole side end surface of the permanent magnet 124 is the S pole side rotor core. 123s.

The N pole side rotor core 123n has a disk-shaped core base 125n, and a rotating shaft 122 is inserted through and fixed to the center of the core base 125n. A plurality (four in this embodiment) of N pole side claw-shaped

magnetic poles

126n and 127n are projected radially outward and extended in the axial direction on the outer peripheral portion of the core base 125n at equal intervals in the circumferential direction. Yes. These N pole side claw-shaped

magnetic poles

126n and 127n extend in the same direction in the axial direction.

Here, the four N pole side claw-shaped

magnetic poles

126n, 127n have a pair of first N pole side claw-shaped magnetic poles 126n (first magnetic pole portions) having an open angle θ1 (open angle with the axis L of the rotating shaft 122 as the center). ) And a pair of second N pole side claw-shaped magnetic poles 127n (second magnetic pole portions) having an opening angle θ2 narrower than the opening angle θ1. That is, the radially outer surface of the first N pole side claw-shaped magnetic pole 126n (the surface facing the stator 11) is wider in the circumferential direction than the radially outer surface of the second N pole side claw-shaped magnetic pole 127n. Note that the radially outer surfaces of the N-pole claw-shaped

magnetic poles

126n and 127n are arcuate surfaces located on the same circle centered on the axis L of the rotating shaft 122 when viewed in the axial direction. The thicknesses of the N-pole claw-shaped

magnetic poles

126n and 127n (the axial thickness of the portion extending in the radial direction and the radial thickness of the portion extending in the axial direction) are all the same.

The first N-pole claw-shaped magnetic pole 126n and the second N-pole claw-shaped magnetic pole 127n are alternately provided at their circumferential center positions at equal angular intervals (90 ° intervals). That is, the pair of first N pole side claw-shaped magnetic poles 126n are provided at positions facing each other by 180 ° in the circumferential direction. Similarly, the pair of second N pole side claw-shaped magnetic poles 127n are also provided at the positions facing each other by 180 °. ing.

The S pole side rotor core 123s has the same shape as the N pole side rotor core 123n, and corresponds to the core base 125n of the N pole side rotor core 123n, the first N pole side claw-shaped magnetic pole 126n, and the second N pole side claw-shaped magnetic pole 127n, respectively. It has a core base 125s, a first S pole side claw-shaped magnetic pole 126s (first magnetic pole part), and a second S pole side claw-shaped magnetic pole 127s (second magnetic pole part). That is, the opening angle θ2 of the second S pole side claw-shaped magnetic pole 127s is set to be narrower than the opening angle θ1 of the first S pole side claw-shaped magnetic pole 126s.

The S pole-side rotor core 123s is arranged between the N pole claw

magnetic poles

126n and 127n to which the S pole claw

magnetic poles

126s and 127s correspond respectively (the first N pole claw magnetic pole 126n and the second N pole claw magnetic pole 127n. Between the N pole rotor core 123n and the N pole rotor core 123n. More specifically, the claw-shaped

magnetic poles

126n, 127n, 126s, and 127s are configured such that their circumferential center positions are equiangular intervals (45 ° intervals). Further, the N pole side claw-shaped

magnetic poles

126n and 127n and the S pole side claw-shaped

magnetic poles

126s and 127s are alternately arranged in the circumferential direction.

The permanent magnet 124 is disposed between the axial direction of the core base 125n of the N-pole rotor core 123n and the core base 125s of the S-pole rotor core 123s. The permanent magnet 124 has an annular shape, and the rotating shaft 122 passes through the center of the permanent magnet 124. The axial end surface of the permanent magnet 124 has a planar shape perpendicular to the axis L of the rotating shaft 122, and is in close contact with the inner end surfaces of the core bases 125n and 125s. Moreover, in this embodiment, the outer diameter of the permanent magnet 124 corresponds with the outer diameter of each

core base

125n, 125s. The permanent magnet 124 is, for example, an anisotropic sintered magnet, and is composed of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like.

The N-pole claw-shaped

magnetic poles

126n and 127n are radially spaced from the outer peripheral surface of the core base 125s of the S-pole rotor core 123s and the outer peripheral surface of the permanent magnet 124. Further, the axial front end surfaces of the N pole side claw-shaped

magnetic poles

126n and 127n are configured at the same position in the axial direction as the outer end surface of the core base 125s.

Similarly, the S pole side claw-shaped

magnetic poles

126 s and 127 s are radially separated from the outer peripheral surface of the core base 125 n of the N pole side rotor core 123 n and the outer peripheral surface of the permanent magnet 124. Further, the axial front end surfaces of the S pole side claw-shaped

magnetic poles

126s and 127s are configured at the same position in the axial direction as the outer end surface of the core base 125n.

The permanent magnet 124 is magnetized in the axial direction so that the core base 125n side is an N pole and the core base 125s side is an S pole. Due to the magnetic field of the permanent magnet 124, the N pole side claw-shaped

magnetic poles

126n and 127n function as N poles, and the S pole side claw-shaped

magnetic poles

126s and 127s function as S poles.

Thus, the rotor 121 of the present embodiment is a so-called Landel type rotor having eight poles (four N pole side claw-shaped

magnetic poles

126n, 127n and four S pole side claw-shaped

magnetic poles

126s, 127s) using the permanent magnet 124. It is configured as.

That is, in the motor 110 of the present embodiment, the number of poles of the rotor 121 is set to 2n (n is an integer equal to or greater than 2), and the number of windings 13 of the stator 11 is set to 3n. The number of poles of the rotor 121 is set to “8”, and the number of windings 13 of the stator 11 is set to “12”.

Next, the operation of this embodiment will be described.
A three-phase drive current (AC) having a phase difference of 120 ° is supplied from a drive circuit (not shown) to the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4, respectively. Then, the windings U1 to W4 are excited at the same timing for each phase to generate a rotating magnetic field in the stator 11, and the rotor 121 rotates based on the rotating magnetic field. At this time, the magnetic poles formed on the side of the stator 11 by the supply of the three-phase drive current are the same for the windings U1 to W4 of each phase.

Here, the number of pole pairs of the rotor 121 (that is, the number of each of the N pole-side claw-shaped

magnetic poles

126n and 127n and the S pole-side claw-shaped

magnetic poles

126s and 127s) is the same as the number of windings U1 to W4 of each phase ( In this embodiment, “4”). Thereby, when the rotor 121 rotates, for example, when one of the S pole side claw-shaped

magnetic poles

126s and 127s is opposed to the U-phase winding U1 in the radial direction, the other S pole side claw-shaped

magnetic poles

126s and 127s are The U-phase windings U2 to U4 are opposed to each other in the radial direction (see FIG. 10).

At this time, the second S pole side claw-shaped magnetic pole 127s has a narrower opening angle than the first S pole side claw-shaped magnetic pole 126s (since the opening angle θ2 <open angle θ1 as described above), the S pole of the rotor 121 The magnetic force applied to the stator 11 (for example, the U-phase windings U1 to U4) is weaker at the second S pole side claw-shaped magnetic pole 127s than at the first S pole side claw-shaped magnetic pole 126s. The same applies to the N pole of the rotor 121 (N pole side claw-shaped

magnetic poles

126n, 127n).

Thus, for example, as shown in FIG. 10, the U-phase windings U2 and U4 facing the second N-pole claw-shaped magnetic pole 127n at the rotational positions where the N-pole of the rotor 121 faces the U-phase windings U1 to U4, respectively. Is less than the interlinkage flux interlinking the U-phase windings U1 and U3 facing the first N-pole claw-shaped magnetic pole 126n. Therefore, the induced voltage generated in the U-phase windings U2 and U4 facing the second N-pole claw-shaped magnetic pole 127n is more than the induced voltage generated in the U-phase windings U1 and U3 facing the first N-pole claw-shaped magnetic pole 126n. Get smaller.

Here, FIG. 13A shows a change in the induced voltage generated in the U-phase windings U1 to U4 during rotation of the rotor in the present embodiment in a predetermined rotation range (90 °), and FIG. 4 shows changes in the induced voltage generated in the U-phase windings U1 to U4 during rotation of the rotor in the conventional configuration in a predetermined rotation range (90 °). The conventional configuration is a configuration in which each magnetic pole of the rotor is uniform, that is, a configuration in which each claw-shaped

magnetic pole

126n, 127n, 126s, 127s of the rotor 121 has the same shape (the same opening angle).

In the conventional configuration, since the magnetic poles of the rotor are uniform, the change of the interlinkage magnetic flux in each of the U-phase windings U1 to U4 is also uniform. For this reason, as shown in FIG. 13B, when the rotor 121 rotates, the same induced voltage vx is generated in the U-phase windings U1 to U4. When the U-phase windings U1 to U4 are in series, the combined induced voltage vu ′ obtained by synthesizing the induced voltage vx generated in each U-phase winding U1 to U4 is the induced voltage vx of each U-phase winding U1 to U4. The sum (that is, four times the induced voltage vx).

On the other hand, as shown in FIG. 13A, in the present embodiment, the second S pole side claw-shaped magnetic pole 127s and the second N pole side claw-shaped magnetic pole 127n are replaced with the first S pole side claw-shaped magnetic pole 126s and the first N pole side claw, respectively. The magnetic force to the stator 11 (U-phase windings U1 to U4) is weaker than that of the magnetic pole 126n. Thus, with respect to the induced voltage vx generated in the U-phase windings U1 to U4 (for example, U-phase windings U2 and U4) facing the first S-pole claw-shaped magnetic pole 126s and the first N-pole claw-shaped magnetic pole 126n, the first The induced voltage vy generated in the U-phase windings U1 to U4 (for example, the U-phase windings U1 and U3) facing the 2S pole-side claw-shaped magnetic pole 127s and the second N-pole side claw-shaped magnetic pole 127n is reduced. Therefore, a combined induced voltage vu (vu = vx × 2 + vy × 2) obtained by synthesizing the induced voltages of the U-phase windings U1 to U4 is combined with the second S-pole claw-shaped magnetic pole 127s and the second N-pole claw-shaped magnetic pole 127n. It decreases by the amount of decrease of the induced voltage vy in the pair of opposing U-phase windings, and becomes smaller than the combined induced voltage vu ′ in the conventional configuration shown in FIG. Here, the combined induced voltage vu of the U-phase windings U1 to U4 has been described as an example, but the second S pole side claw-shaped magnetic pole is similarly applied to the V-phase windings V1 to V4 and the W-phase windings W1 to W4. The resultant interlinkage magnetic flux decreases due to the narrow opening angle of 127s and the second N-pole claw-shaped magnetic pole 127n.

Next, characteristic advantages of this embodiment will be described.
(4) The windings 13 of the stator 11 are composed of four U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4, respectively, corresponding to the supplied three-phase driving current. Thus, the four windings of each phase are connected in series. That is, the winding 13 of the stator 11 includes at least two windings (first winding and second winding) connected in series in each phase.

In addition, the N pole of the rotor 121 includes a first N pole side claw-shaped magnetic pole 126n, and the first N pole side claw-shaped magnetic pole 126n has a first winding (for example, a U phase) in any of the U, V, and W phases. A second N pole side claw-shaped magnetic pole 127n facing a second winding (for example, U phase windings U2, U4) in phase at the rotational position of the rotor 121 facing the windings U1, U3). The shape (open angle) of the second N-pole claw-shaped magnetic pole 127n is set so that the magnetic force applied to the stator 11 is weaker than that of the first N-pole claw-shaped magnetic pole 126n. Similarly, in the S pole of the rotor 121, the first S pole side claw-shaped magnetic pole 126 s and the first S pole side claw-shaped magnetic pole 126 s are in the first winding (U, V, or W phase). For example, a second S pole side claw-shaped magnetic pole 127s facing the second winding (for example, the U phase windings U2, U4) in phase at the rotational position of the rotor 121 facing the U phase windings U1, U3). The shape (open angle) of the second S pole side claw-shaped magnetic pole 127s is set so that the magnetic force applied to the stator 11 is weaker than that of the first S pole side claw-shaped magnetic pole 126s.

Thus, in the present embodiment, the magnetic force (magnetic force applied to the stator) of all the N poles (or all the S poles) in the rotor 121 is not weakened, but a part thereof (second N pole side claw-shaped magnetic pole 127n). And the second S-pole claw-shaped magnetic pole 127s) is configured to weaken the magnetic force. As a result, the combined induction voltage (for example, the combined induction voltage vu of the U phase) generated in the in-phase winding 13 by the magnetic poles of the rotor 121 can be suppressed to a low level while suppressing a decrease in torque as much as possible. High rotation can be achieved.

Note that, in the winding mode in which the windings 13 are connected in series in each phase as in the present embodiment, the sum of the induced voltages generated in the respective windings for each phase becomes the combined induced voltage. The voltage tends to increase. For this reason, in the configuration in which the windings 13 are connected in series in each phase, the combined induced voltage is suppressed by weakening the magnetic force of the second N pole side claw-shaped magnetic pole 127n and the second S pole side claw-shaped magnetic pole 127s as described above. The effect can be obtained more remarkably, and it is more suitable for increasing the rotation speed of the motor.

(5) 2n pieces of U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4 (n is an integer of 2 or more, and in this embodiment, n = 2) The number of first and second N pole side claw-shaped

magnetic poles

126n, 127n (first and second S pole side claw-shaped

magnetic poles

126s, 127s) of the rotor 121 is n (that is, two). The That is, according to this configuration, the number of windings in each phase (the number of U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4) is an even number of 4 or more. The first and second N pole side claw-shaped

magnetic poles

126n and 127n (first and second S pole side claw-shaped

magnetic poles

126s and 127s) of the rotor 121 are configured in the same number (half the number of windings of each phase). Is done.

Therefore, the first and second N pole side claw-shaped

magnetic poles

126n and 127n (first and second S pole side claw-shaped

magnetic poles

126s and 127s) of the rotor 121 can be alternately provided at equal intervals in the circumferential direction. As a result, the first and second N pole side claw-shaped

magnetic poles

126n and 127n (first and second S pole side claw-shaped

magnetic poles

126s and 127s) having different magnetic forces and masses are arranged in a balanced manner in the circumferential direction. Can be made magnetically and mechanically balanced.

In addition, you may change the said embodiment as follows.
Although not specifically mentioned in the above embodiment, field weakening control may be performed when the rotor 121 is rotating at a high speed. In the above embodiment, by providing the rotor 121 with the second N-pole claw-shaped magnetic pole 127n (second S-pole claw-shaped magnetic pole 127s), it becomes possible to suppress the field-weakening current supplied to the winding 13 to be small. Effects such as suppression of copper loss generated in the winding 13 can be obtained. In other words, since the amount of flux linkage that can be reduced with the same amount of field-weakening current increases, higher rotation by field-weakening control can be obtained more effectively.

In the above embodiment, for example, by setting the opening angle θ2 of the second N pole side claw-shaped magnetic pole 127n of the N pole side rotor core 123n to be narrower than the opening angle θ1 of the first N pole side claw-shaped magnetic pole 126n, The magnetic force to be applied is weaker at the second N-pole claw-shaped magnetic pole 127n than at the first N-pole claw-shaped magnetic pole 126n. However, this may be realized by changing the shape of the second N-pole claw-shaped magnetic pole 127n. For example, by making the thickness (the radial thickness of the portion extending in the axial direction and the axial thickness of the portion extending in the radial direction) of the second N-pole claw-shaped magnetic pole 127n thinner than that of the first N-pole claw-shaped magnetic pole 126n. The magnetic force applied to the stator 11 may be weaker at the second N pole side claw-shaped magnetic pole 127n than at the first N pole side claw-shaped magnetic pole 126n. The same change may also be made in the S pole side rotor core 123s.

In the above embodiment, for example, by changing the shape of a part of the four claw-shaped magnetic poles formed on the N-pole rotor core 123n (second N-pole claw-shaped magnetic pole 127n), the second N-pole claw-shaped magnetic pole The magnetic force 127n applies to the stator 11 is weaker than the first N-pole claw-shaped magnetic pole 126n. The same applies to the south pole side rotor core 123s. However, the configuration for relatively weakening the magnetic force of the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s is not limited to the above embodiment.

For example, as shown in FIGS. 14 and 15, the magnetic forces of the second N-pole claw-shaped magnetic pole 127n and the second S-pole-claw-shaped magnetic pole 127s are changed to the first N-pole claw-shaped magnetic pole 126n and the first S-pole claw-shaped magnetic pole 126s, respectively. A magnetic force adjusting magnet 130 may be provided in the rotor 121 for making it relatively weaker.

In the configuration shown in FIGS. 14 and 15, the first N-pole claw-shaped magnetic pole 126n and the second S-pole claw-shaped magnetic pole 127s are formed to have the same opening angle. Similarly, the first S pole side claw-shaped magnetic pole 126s and the second S pole side claw-shaped magnetic pole 127s are also formed to have the same opening angle.

The magnetism adjusting magnets 130 are provided in pairs, and each of the first back magnet portions 131 (FIG. 15) is disposed on the back side (radially inward) of the portion extending in the axial direction in the first N pole side claw-shaped magnetic pole 126n. Reference) and a second back magnet part 132 disposed on the back side (in the radial direction) of the portion extending in the axial direction of the first S-pole claw-shaped magnetic pole 126s.

Each of the magnetic force adjusting magnets 130 includes a first inter-pole magnet portion 133 disposed between the first N-pole claw-shaped magnetic pole 126n and the second S-pole claw-shaped magnetic pole 127s adjacent thereto. . Each of the magnetic force adjusting magnets 130 includes a second interpole magnet portion 134 disposed between the first N pole side claw-shaped magnetic pole 126n and the first S pole side claw-shaped magnetic pole 126s adjacent thereto. . Each of the magnetic force adjusting magnets 130 includes a third interpole magnet portion 135 disposed between the first S pole side claw-shaped magnetic pole 126s and the second N pole side claw-shaped magnetic pole 127n adjacent thereto. Yes.

In the same example, each of the pair of magnetism adjusting magnets 130 is configured as one component in which the magnet portions 131 to 135 are integrally formed. The magnetic force adjusting magnet 130 is preferably composed of a bonded magnet (plastic magnet, rubber magnet, etc.) made of a rare earth magnet such as a neodymium magnet.

The first back magnet portion 131 is in contact with the first N-pole claw-shaped magnetic pole 126n on the radially outer side, and is in contact with the outer peripheral surfaces of the permanent magnet 124 and the core base 125s on the radially inner side. The second back magnet part 132 is in contact with the first S pole side claw-shaped magnetic pole 126s on the radially outer side, and is in contact with the outer peripheral surfaces of the permanent magnet 124 and the core base 125n on the radially inner side.

14 and 15, solid arrows indicate the magnetization directions (from the S pole to the N pole) of the magnet portions 131 to 135 of the magnetic force adjusting magnet 130. The first back magnet part 131 is magnetized radially outward in order to suppress leakage magnetic flux from the first N pole side claw-shaped magnetic pole 126n to the back side (radially inside). That is, the first back magnet part 131 is magnetized in the radial direction so that the radially outer surface thereof becomes the N pole having the same polarity as the first N pole side claw-shaped magnetic pole 126n.

Similarly, the second back magnet part 132 is magnetized radially outward so as to suppress the leakage magnetic flux from the first S pole side claw-shaped magnetic pole 126s to the back side (inside in the radial direction). That is, the second back magnet part 132 is magnetized in the radial direction so that its radially outer surface is the S pole having the same polarity as the first S pole side claw-shaped magnetic pole 126s.

Further, the first inter-pole magnet portion 133 is magnetized in the circumferential direction so as to suppress the leakage magnetic flux in the circumferential direction of the first N-pole claw-shaped magnetic pole 126n. That is, the first inter-pole magnet section 133 is arranged in the circumferential direction so that the surface on the first N pole side claw-shaped magnetic pole 126n side in the circumferential direction is the N pole and the surface on the second S pole side claw magnetic pole 127s side is the S pole. Magnetized.

The second inter-pole magnet section 134 is magnetized in the circumferential direction in order to suppress leakage magnetic flux in the circumferential direction of the first N-pole claw-shaped magnetic pole 126n and the first S-pole claw-shaped magnetic pole 126s. That is, the second inter-pole magnet portion 134 is arranged in the circumferential direction so that the surface on the first N pole side claw-shaped magnetic pole 126n side in the circumferential direction is N pole and the surface on the first S pole side claw magnetic pole 126s side is S pole. Magnetized.

The third inter-pole magnet portion 135 is magnetized in the circumferential direction so as to suppress the leakage magnetic flux in the circumferential direction of the first S-pole claw-shaped magnetic pole 126s. That is, the third inter-pole magnet portion 135 is arranged in the circumferential direction so that the surface on the second N pole side claw-shaped magnetic pole 127n side in the circumferential direction is N pole and the surface on the first S pole side claw magnetic pole 126s side is S pole. Magnetized.

According to such a configuration, the leakage flux of the first N pole side claw-shaped magnetic pole 126n and the first S pole side claw-shaped magnetic pole 126s is suppressed by the magnet portions 131 to 135 of the magnetic force adjusting magnet 130. As a result, the magnetic forces applied to the stator 11 by the first N-pole claw-shaped magnetic pole 126n and the first S-pole claw-shaped magnetic pole 126s are stronger than those of the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s, respectively. That is, the magnetic forces of the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s are relatively weak). For this reason, as in the above embodiment, the combined flux linkage (for example, U-phase synthesized linkage flux φu) of the in-phase winding 13 by the magnetic poles of the rotor 121 can be suppressed to a minimum while suppressing a decrease in torque as much as possible. . Further, since the combined flux linkage in the in-phase winding 13 is suppressed to a low level, the induced voltage generated in the winding 13 can be suppressed to a low level, and as a result, the motor 110 can be rotated at a high speed.

Further, in the above configuration, the opening angle of the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s is not narrowed, but the addition of the magnetic force adjusting magnet 130 does not reduce the opening angle of the second N-pole claw-shaped magnetic pole 127n. The magnetic force of the 2S pole side claw-shaped magnetic pole 127s is relatively weakened. For this reason, it can be said that it is a more effective structure at the point which ensures a torque.

In the example shown in FIGS. 14 and 15, the magnet parts 131 to 135 are integrally formed. However, as shown in FIG. 16, for example, the magnet parts 131 to 135 may be configured separately. Further, in the magnetic force adjusting magnet 130 shown in FIGS. 14 and 15, any one or more of the magnet portions 131 to 135 may be omitted. Further, in the example shown in FIGS. 14 and 15, the magnetization mode of the magnetic force adjusting magnet 130 may be polar anisotropic orientation.

Further, in the example shown in FIGS. 14 and 15, for example, the magnetic force on the back side (radially inner side) of the portion extending in the axial direction in the second N-pole claw-shaped magnetic pole 127 n is larger than that of the first back magnet unit 131. It is also possible to provide a back magnet part having a small diameter and suppress the leakage magnetic flux flowing from the second N-pole claw-shaped magnetic pole 127n to the back side by the back magnet part. Similarly, an interpole magnet portion having a smaller magnetic force than the interpole magnet portions 133 to 135 is provided on the circumferential side of the second N pole side claw-shaped magnetic pole 127n, and the second N pole is provided by the interpole magnet portion. You may comprise so that the leakage magnetic flux which flows into the circumferential direction from the side nail | claw-shaped magnetic pole 127n may be suppressed. The same change may be made on the S pole side.

In the above embodiment, the single first N pole side claw-shaped magnetic pole 126n and the single first S pole side claw-shaped magnetic pole 126s each constitute the first magnetic pole portion, and the single second N pole side claw-shaped magnetic pole 127n. The single second S pole side claw-shaped magnetic pole 127s constitutes a second magnetic pole part having a magnetic force weaker than that of the first magnetic pole part, but is not particularly limited thereto.

For example, the rotor 140 shown in FIGS. 17 and 18 includes first and

second rotor cores

141 and 142 having the same shape, and a permanent magnet 124 disposed between the axial directions of the first and

second rotor cores

141 and 142. And a pair of outer peripheral magnets 150 (magnetic force adjusting magnets).

The first rotor core 141 includes a disk-shaped core base 143 and a pair of first claw-shaped magnetic poles 144 formed to extend from the outer peripheral surface of the core base 143. The pair of first claw-shaped magnetic poles 144 are formed at 180 ° facing positions in the circumferential direction. Each first claw-shaped magnetic pole 144 protrudes radially outward from the outer peripheral surface of the core base 143 and extends in the axial direction (the same direction as each other). A magnet fixing surface 145 to which the outer peripheral magnet 150 is fixed is formed on a half of the outer peripheral surface (radially outer surface) of the first claw-shaped magnetic pole 144, and the other half is from the magnet fixing surface 145. Also, a first salient pole portion 144a that protrudes radially outward is formed.

The second rotor core 142 has the same shape as the first rotor core 141, and corresponds to the core base 143 and the first claw-shaped magnetic pole 144 (first salient pole portion 144a) of the first rotor core 141, respectively. A two-claw magnetic pole 147 (second salient pole portion 147a) is provided.

The second rotor core 142 is assembled to the first rotor core 141 such that each second claw-shaped magnetic pole 147 is disposed between the corresponding first claw-shaped magnetic poles 144. More specifically, the claw-shaped

magnetic poles

144 and 147 are configured such that their circumferential center positions are at equal circumferential intervals (90 ° intervals). Further, the first claw-shaped magnetic poles 144 and the second claw-shaped magnetic poles 147 are alternately arranged in the circumferential direction.

The permanent magnet 124 is disposed between the axial directions of the core bases 143 and 146 of the first and

second rotor cores

141 and 142, and the surface of the permanent magnet 124 on the first rotor core 141 (core base 143) side is arranged. The north pole is magnetized in the axial direction so that the surface on the second rotor core 142 (core base 146) side becomes the south pole. Note that the permanent magnet 124 has substantially the same configuration as the permanent magnet 124 of the above embodiment, and thus detailed description thereof is omitted.

Each first claw-shaped magnetic pole 144 is radially spaced from the outer peripheral surface of the core base 146 of the second rotor core 142 and the outer peripheral surface of the permanent magnet 124. Similarly, the second claw-shaped magnetic pole 147 is radially spaced from the outer peripheral surface of the core base 143 of the first rotor core 141 and the outer peripheral surface of the permanent magnet 124.

The outer peripheral magnet 150 is provided across the magnet fixing surface 145 of the first claw-shaped magnetic pole 144 and the magnet fixing surface 145 of the second claw-shaped magnetic pole 147. Specifically, the outer peripheral magnet 150 includes an N pole portion 151 magnetized so that the N pole appears on the outer peripheral surface, and an S pole portion 152 magnetized so that the N pole appears on the outer peripheral surface. 152 is fixed to the magnet fixing surface 145 of the first claw-shaped magnetic pole 144, and the N pole portion 151 is fixed to the magnet fixing surface 145 of the second claw-shaped magnetic pole 147. That is, a magnet (S pole portion 152) having a polarity opposite to the magnetic pole (N pole) received by the first claw pole magnetic pole 144 by the magnetic field of the permanent magnet 124 is fixed to the magnet fixing surface 145 of the first claw pole magnetic pole 144. Then, a magnet (N pole portion 151) having a polarity opposite to that of the magnetic pole (S pole) received by the second claw pole magnetic pole 147 by the magnetic field of the permanent magnet 124 is fixed to the magnet fixing surface 145 of the second claw pole 147. Has been. In this example, the N pole portion 151 and the S pole portion 152 of each outer peripheral magnet 150 (second magnetic pole portion) and the first and second

salient pole portions

144a and 147a (first magnetic pole portion) in the axial direction view. Are configured such that their outer peripheral surfaces are located on the same circle centered on the axis L of the rotating shaft 122.

In the rotor 140 configured as described above, the first salient pole portion 144a of the first claw-shaped magnetic pole 144 functions as an N pole by the magnetic field of the permanent magnet 124 and the magnetic field of the S pole portion 152 of the outer peripheral magnet 150. Similarly, the second salient pole part 147a of the second claw-shaped magnetic pole 147 functions as the S pole by the magnetic field of the permanent magnet 124 and the magnetic field of the N pole part 151 of the outer peripheral magnet 150. Further, the N pole portion 151 of each outer peripheral magnet 150 constitutes a part of the N pole of the rotor 140, and the S pole portion 152 of each outer periphery magnet 150 constitutes a part of the S pole of the rotor 140. That is, in the rotor 140, the N pole is configured by the two first salient pole portions 144a and the two N pole portions 151, and the S pole is configured by the two second salient pole portions 147a and the two S pole portions 152. As a whole, it is composed of 8 poles.

Note that the arrangement relationship of the magnetic poles (first and second

salient pole portions

144a, 147a, N pole portion 151, and S pole portion 152) of the rotor 140 of this example is the same as that of the rotor 121 of the above embodiment. . That is, the first salient pole portion 144a is the first N pole side claw-shaped magnetic pole 126n of the above embodiment, the N pole portion 151 is the second N pole side claw-shaped magnetic pole 127n of the above embodiment, and the second salient pole portion 147a is the above mentioned. The first S pole side claw-shaped magnetic pole 126s of the embodiment and the S pole portion 152 correspond to the second S pole side claw-shaped magnetic pole 127s of the above embodiment, respectively.

According to such a configuration, the magnetic force applied to the stator 11 at the N pole of the rotor 140 can be made weaker at the N pole portion 151 than at the first salient pole portion 144a. Further, in the S pole of the rotor 140, the magnetic force applied to the stator 11 can be made weaker at the S pole portion 152 than at the second salient pole portion 147a. For this reason, as in the above embodiment, the combined flux linkage (for example, the U-phase combined flux linkage φu) of the in-phase winding 13 by the magnetic poles of the rotor 140 can be reduced while suppressing a reduction in torque as much as possible. . Further, since the combined flux linkage in the in-phase winding 13 is suppressed to a low level, the induced voltage generated in the winding 13 can be suppressed to a low level, and as a result, the motor 110 can be rotated at a high speed.

In the example shown in FIGS. 17 and 18, the magnetic force applied to the stator 11 is set to the N pole portion 151 (S pole) by setting the magnetic characteristics of the permanent magnet 124 and the outer peripheral magnet 150 (N pole portion 151 and S pole portion 152). It is also possible to weaken the first salient pole portion 144a (second salient pole portion 147a) than the portion 152).

In the example shown in FIGS. 17 and 18, the outer peripheral magnet 150 integrally including the N pole portion 151 and the S pole portion 152 is used. However, the configuration is not limited thereto, and the N pole portion 151 and the S pole portion 152 are divided. You may use the magnet made. In the same example, a back magnet part and an interpole magnet part as described in the examples of FIGS. 14 and 15 may be provided.

In the above embodiment, for example, in the N-pole rotor core 123n, the same number of first N-pole claw-shaped magnetic poles 126n and second N-pole claw-shaped magnetic poles 127n (half the number of the windings 13 of each phase, two ), But the number is not necessarily the same. For example, the first N pole side claw-shaped magnetic pole 126n may be configured as three (or one) and the second N pole side claw-shaped magnetic pole 127n may be configured as one (or three). The same change may also be made in the S pole side rotor core 123s.

In the above embodiment, the second N pole side claw-shaped magnetic pole 127n and the second S pole side claw-shaped magnetic pole 127s, which have relatively weak magnetic forces, are provided for the N pole side rotor core 123n and the S pole side rotor core 123s of the rotor 121, respectively. However, it is not particularly limited to this. For example, in the S pole side rotor core 123s, each second S pole side claw-shaped magnetic pole 127s is changed to the first S pole side claw-shaped magnetic pole 126s (that is, all claw-shaped magnetic poles provided in the S pole side rotor core 123s are the same). The configuration may be a shape).

For example, in the example shown in FIG. 19, in the U phase, the windings U1, U2 are connected in series, and the windings U3, U4 are connected in series, and the series pair of the windings U1, U2 and the windings U3, U4. Are connected in parallel. Similarly, in the V phase, the windings V1 and V2 are connected in series, and the windings V3 and V4 are connected in series. The series pair of the windings V1 and V2 and the series pair of the windings V3 and V4 are parallel. It is connected. Similarly, in the W phase, the windings W1, W2 are connected in series, and the windings W3, W4 are connected in series. The series pair of the windings W1, W2 and the series pair of the windings W3, W4 Are connected in parallel.

In the configuration of the rotor 121 of the above embodiment (see FIG. 10), when the winding mode of FIG. 19 is applied, for example, in the U phase, the induced voltage (the induced voltage) is equivalent to the winding U1 and the winding U3. vx) occurs, and induced voltages (the induced voltages vy) having the same magnitude are generated in the windings U2 and U4. For this reason, the combined induction voltage generated in the series pair of the windings U1 and U2 and the combined induction voltage generated in the series pair of the windings U3 and U4 are substantially equal (vx + vy). As a result, a decrease in the induced voltage due to the provision of the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s having a weak magnetic force causes the series pair of the windings U1 and U2 and the series of the windings U3 and U4 to be reduced. Will always occur in both pairs. Since the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are parallel, the combined induction voltage vu in the entire U-phase winding is the combined induction voltage of the series pair of the windings U1 and U2. (And the combined induction voltage of the series pair of windings U3 and U4) (vx + vy), and the combined induction voltage vu can be effectively suppressed.

Here, when the winding U2 and the winding U3 are interchanged in the example shown in FIG. 19, that is, the windings U1, U3 having the same magnitude of the induced voltage are connected in series, and the magnitude of the induced voltage is the same. Consider the case where the windings U2 and U4 are in series. In this case, the induced voltage is reduced by providing the second N-pole claw-shaped magnetic pole 127n and the second S-pole claw-shaped magnetic pole 127s having a weak magnetic force, and the series pair of the windings U2 and U4 and the series of the windings U1 and U3 are reduced. It occurs only in one of the pairs, and the induced voltage does not decrease on the other. And since the series pair of winding U1, U3 and the series pair of winding U2, U4 are parallel, it is disadvantageous at the point which suppresses the synthetic | combination induced voltage in the whole U-phase winding effectively. Similarly, when the U-phase windings U1 to U4 are arranged in parallel, similarly, it is disadvantageous in that the combined induced voltage in the entire U-phase winding is effectively suppressed.

As described above, when the windings are connected in series in each phase, the first N pole side claw-shaped magnetic pole 126n (or the first S pole side claw-shaped magnetic pole 126s) and the second N pole side at a predetermined rotational position of the rotor 121. The windings (for example, U-phase windings U1, U2) facing the claw-shaped magnetic pole 127n (or the second S-pole claw-shaped magnetic pole 127s) are connected in series. As a result, the weak induced voltage generated in the windings of the same phase and the strong induced voltage can be added to obtain a combined induced voltage, and the combined induced voltage in each phase can be effectively suppressed.

In the example of FIG. 19, in the U phase, the windings U1 and U2 are a series pair and the windings U3 and U4 are a series pair, but the windings U1 and U4 and the windings U2 and U3 are respectively Similar effects can be obtained as a series pair. The same change can be made in the V phase and the W phase.

In the example of FIG. 19, in the U phase, the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are connected in parallel. , U2 and the series pair of windings U3, U4 may be separated, and a pair of inverters may be provided to supply a U-phase drive current to each of the separated series pairs. The same effect can be obtained by this configuration. The same change can be made in the V phase and the W phase.

Moreover, in the example shown in the said embodiment (refer FIG. 2) and FIG. 19, although the connection aspect of the coil | winding was made into star connection, it is good also as not only this but delta connection, for example.
In the above embodiment, the rotor 121 has 8 poles and the number of windings 13 of the stator 11 is 12 (that is, the motor configuration has 8 poles and 12 slots). The number of can be appropriately changed according to the configuration. For example, the number of poles of the rotor 121 and the number of windings 13 are appropriately changed so that the relationship between the number of poles of the rotor 121 and the number of windings 13 is 2n: 3n (where n is an integer of 2 or more). May be.

In the case of a configuration of 6 poles 9 slots, 10 poles 15 slots, etc. (when the number of poles of the rotor 121 and the greatest common divisor n of the number of windings 13 is an odd number), the number of pole pairs of the rotor 121 is an odd number, That is, the number of N poles and S poles is an odd number. For this reason, for example, the first N pole side claw-shaped magnetic pole 126n and the second N pole side claw-shaped magnetic pole 127n cannot be the same number, resulting in a magnetically unbalanced configuration. In that regard, as in the above embodiment, in the configuration in which the greatest common divisor n of the number of poles of the rotor 121 and the number of windings 13 is an even number, the first N-pole claw-shaped magnetic pole 126n and the second N-pole claw-shaped magnetic pole 127n. And the same number, and a magnetically balanced configuration can be achieved.

In addition, the relationship between the number of poles of the rotor 121 and the number of windings 13 is not necessarily 2n: 3n (where n is an integer of 2 or more). For example, 10 poles 12 slots, 14 poles 12 slots, etc. It may be configured.

FIG. 20 shows an example of a motor 160 configured with 10 poles and 12 slots. In the example of FIG. 20, the same components as those in the above embodiment are denoted by the same reference numerals, detailed description thereof is omitted, and different portions will be described in detail.

In the motor 160 shown in FIG. 20, the twelve windings 13 of the stator 11 are classified according to the supplied three-phase drive currents (U phase, V phase, W phase), and are counterclockwise in FIG. In this order, U1, bar U2, bar V1, V2, W1, bar W2, bar U1, U2, V1, bar V2, bar W1, W2. In addition, U phase winding bar U1, bar U2, V phase winding bar V1 with respect to U phase windings U1, U2, V phase windings V1, V2 and W phase windings W1, W2 constituted by positive windings. , Bar V2, W-phase winding bar W1, bar W2 are constituted by reverse winding. Further, the U-phase winding U1 and the bar U1 are placed at positions facing each other by 180 °, and similarly, the U-phase winding U2 and the bar U2 are placed at positions facing each other by 180 °. The same applies to the other phases (V phase and W phase).

U-phase windings U1, U2, U1 and U2 are connected in series. Similarly, V-phase windings V1, V2, V1 and V2 are connected in series, and W-phase winding W1. , W2, bar W1, and bar W2 are connected in series. The U-phase windings U1, U2, U1 and U2 are supplied with U-phase drive current. As a result, the positive winding U-phase winding U1,
The U-phase winding bars U1 and U2 that are reversely wound with respect to U2 are always excited with the reverse polarity (reverse phase), but the excitation timing is the same. The same applies to the other phases (V phase and W phase).

The rotor 121 of the motor 160 is a 10 pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (36 ° intervals), and includes two first N pole side claw-shaped magnetic poles 126n and three first poles. A 1S pole-side claw-shaped magnetic pole 126s, three second N-pole-side claw-shaped magnetic poles 127n, and two second S-pole-side claw-shaped magnetic poles 127s are provided. The first N-pole claw-shaped magnetic pole 126 n and the first S-pole claw-shaped magnetic pole 126 s are alternately provided on the half circumference of the rotor 121, and the second N-pole claw-shaped magnetic pole 127 n and the second S-pole claw-shaped magnetic pole 127 s They are provided alternately in a half circle. Further, the second S pole-side claw-shaped magnetic pole 127s is located on the opposite side (180 ° opposite position) of the first N pole-side claw-shaped magnetic pole 126n, and the first S pole-side claw-shaped magnetic pole 126s is positioned on the opposite side (180 °). The second N-pole claw-shaped magnetic pole 127n is positioned at the (opposite position).

The numbers of the first and second N pole side claw-shaped

magnetic poles

126n, 127n and the first and second S pole side claw-shaped

magnetic poles

126s, 127s are not limited to the example of the 10-pole rotor of FIG. For example, three first N-pole claw-shaped magnetic poles 126n, two first S-pole claw-shaped magnetic poles 126s, two second N-pole claw-shaped magnetic poles 127n, and two second S-pole claw-shaped magnetic poles 127s. You may comprise.

In the above configuration, when the rotor 121 rotates, for example, when the first S-pole claw-shaped magnetic pole 126s faces the U-phase winding U1 in the radial direction, the second N-pole claw-shaped magnetic pole 127n is U on the opposite side in the circumferential direction. Opposite the phase winding bar U1 in the radial direction (see FIG. 20). That is, the magnetic pole portions having different polarities (for example, the first S pole side claw-shaped magnetic pole 126s and the second N pole) respectively opposed to the windings 13 (for example, the U phase winding U1 and the bar U1) excited in opposite phases (same timing). In the side claw-shaped magnetic pole 127n), the magnetic forces are different from each other (that is, the other magnetic force is weaker than the other). As a result, the combined induction voltage (for example, the combined induction voltage of the U-phase winding U1 and the bar U1) generated in the anti-phase winding 13 by the magnetic poles of the rotor 121 can be suppressed to a low level while suppressing the decrease in torque as much as possible. As a result, high rotation of the motor 160 can be achieved.

In the example of the rotor 121 shown in FIG. 20, the first N pole side claw-shaped magnetic pole 126n and the first S pole side claw-shaped magnetic pole 126s are provided on the half circumference of the rotor 121, and the second N pole side claw-shaped magnetic pole 127n and the second S pole side. A claw-shaped magnetic pole 127 s was provided on the other half of the rotor 121. However, the arrangement of the claw-shaped magnetic poles of the rotor 121 is not particularly limited to this, and the second S-pole claw-shaped magnetic pole 127s is located on the opposite side in the circumferential direction of the first N-pole claw-shaped magnetic pole 126n. If the second N-pole claw-shaped magnetic pole 127n is positioned on the opposite side of the pole-side claw-shaped magnetic pole 126s in the circumferential direction, the arrangement of the claw-shaped magnetic poles of the rotor 121 can be changed as appropriate.

FIG. 20 shows an example of 10 poles and 12 slots, but the present invention can also be applied to a 14 poles and 12 slots structure. Further, the present invention can also be applied to a configuration in which the number of rotor poles and the number of slots of 10 poles and 12 slots (or 14 poles and 12 slots) are equal. In the case of a configuration in which the number of rotor poles and the number of slots of 10 poles and 12 slots (or 14 poles and 12 slots) are respectively doubled, the first N pole side claw-shaped magnetic pole 126n and the first S pole side claw-shaped magnetic pole 126s are surrounded. The strong magnetic pole group alternately arranged in the direction and the weak magnetic pole group in which the second N-pole side claw-shaped magnetic pole 127n and the second S-pole side claw-like magnetic pole 127s are alternately arranged in the circumferential direction are alternately arranged in the circumferential direction. It is preferable to do. According to this configuration, the strong magnetic pole group and the weak magnetic pole group can be arranged with good balance in the circumferential direction, and the rotor 121 can be magnetically and mechanically balanced.

In the above embodiment, the claw-shaped magnetic poles formed on, for example, the N-pole rotor core 123n of the rotor 121 are the first N-pole claw-shaped magnetic poles 126n that constitute the first magnetic pole part and the second N that constitutes the second magnetic pole part. It consists only of the pole-side claw-shaped magnetic pole 127n. However, for example, the N pole rotor core 123n may be provided with a third N pole claw magnetic pole (third magnetic pole) whose magnetic force applied to the stator 11 is weaker than that of the second N pole claw magnetic pole 127n.

In the above embodiment, the rotor 121 is embodied as the inner rotor type motor 110 arranged on the inner peripheral side of the stator 11, but is not particularly limited to this, and the outer rotor type in which the rotor is arranged on the outer peripheral side of the stator It may be embodied in the motor.

In the above embodiment, the present invention is embodied in the radial gap type motor 110 in which the stator 11 and the rotor 121 are opposed to each other in the radial direction. However, the present invention is not particularly limited thereto, and the stator and the rotor are in the axial direction. The present invention may be applied to an axial gap type motor that faces the motor.

-You may combine embodiment mentioned above and each modification suitably.
Hereinafter, a third embodiment of the motor will be described.
As shown in FIG. 21A, the motor 210 of the present embodiment is configured as a brushless motor, and is configured with a rotor 221 disposed inside an annular stator 11. Since the configuration of the stator 11 is the same as that of the stator 11 of the first embodiment, detailed description thereof is omitted. The winding 13 of the stator 11 is configured similarly to the winding 13 of the first embodiment, and has the configuration shown in FIG.

[Configuration of rotor]
As illustrated in FIG. 21B, the rotor 221 includes a rotor core 222 and a permanent magnet 223. The rotor core 222 is formed of a magnetic metal in a substantially disk shape, and a rotating shaft 224 is fixed to the center portion. Two magnet fixing portions 225 and four protrusions 226 are formed on the outer peripheral portion of the rotor core 222.

Each magnet fixing portion 225 is provided at a 180 ° facing position in the circumferential direction. Two permanent magnets 223 are fixed to each of the magnet fixing portions 225, and a total of four permanent magnets 223 are provided on the outer peripheral portion of the rotor core 222.

The permanent magnets 223 have the same shape, and the outer peripheral surface of each permanent magnet 223 has an arc shape centered on the axis L when viewed from the direction of the axis L of the rotary shaft 224. Further, the opening angle (circumferential width) around the axis L of each permanent magnet 223 is 45 °. The permanent magnet 223 is, for example, an anisotropic sintered magnet, and includes, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like.

Each permanent magnet 223 is formed so that the magnetic orientation is directed in the radial direction, and the two permanent magnets 223 provided in each magnet fixing portion 225 are configured such that the magnetic poles appearing on the outer peripheral side are different from each other. Yes. Further, the permanent magnet 223 having the same polarity is disposed at a 180 ° facing position in the circumferential direction. These permanent magnets 223 constitute a part of the magnetic poles of the rotor 221. Specifically, the permanent magnet 223 in which the N pole appears on the outer peripheral side constitutes the N magnetic pole Mn, and the permanent magnet 223 in which the S pole appears on the outer peripheral side constitutes the S magnetic pole Ms.

The protrusions 226 of the rotor core 222 are provided so as to be adjacent to each other in the circumferential direction two by two in the circumferential direction of the magnet fixing portion 225. A gap K1 is formed between the circumferential directions of the pair of adjacent protrusions 226. In addition, one of the pair of adjacent protrusions 226 is adjacent to the N-pole magnet magnetic pole Mn (peripheral magnet 223 having an N pole on the outer peripheral side) in the circumferential direction, and the S pole is generated by the magnetic field of the N-pole permanent magnet 223. Function as a magnetic pole (a salient pole Ps as a core magnetic pole). Similarly, the other protrusion 226 is adjacent to the S-pole magnet magnetic pole Ms (the outer peripheral side is the S-pole permanent magnet 223), and the magnetic field of the S-pole permanent magnet 223 causes the N-pole magnetic pole (projection as a core magnetic pole). It functions as a pole Pn). The pair of N-pole salient poles Pn are arranged at 180 ° facing positions in the circumferential direction, and the pair of S-pole salient poles Ps are similarly arranged at 180 ° facing positions in the circumferential direction. The outer peripheral surface of each protrusion 226 is formed in an arc shape that is located on the same circle as the outer peripheral surface of each permanent magnet 223 as viewed from the axial direction (on the same circle with the axis L of the rotation shaft 224 as the center). ing. Further, the opening angle of each protrusion 226 is set smaller than the opening angle of each permanent magnet 223. Further, between the salient poles Pn and Ps (projections 226) and the magnet poles Mn and Ms (permanent magnet 223) having different polarities, that is, the N pole salient poles Pn and the S pole magnet poles Ms. And gaps K2 are formed between the S pole salient pole Ps and the N pole magnet magnetic pole Mn.

The rotor 221 having the above configuration is configured as an 8-pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (45 ° intervals) on the outer peripheral surface (that is, the surface facing the stator 11). . Specifically, the magnetic poles on the outer peripheral surface of the rotor 221 (that is, the surface facing the stator 11) are N pole magnet magnetic poles Mn, S pole salient poles Ps, and N pole salient pole poles in order in the clockwise direction. The Pn, S pole magnetic pole Ms, N pole magnetic pole Mn,... Are repeated. Further, the magnet magnetic pole Mn and salient pole magnetic pole Pn constituting the N pole of the rotor 221 are alternately arranged at equal angular intervals (90 ° intervals) in the circumferential direction. The magnet magnetic pole Ms and salient pole magnetic pole Ps which comprise are arrange | positioned alternately by the center position of the circumferential direction at equal angular intervals (90 degree space | interval).

The rotor core 222 is formed with four slit holes 227 extending along the radial direction of the rotating shaft 224. The slit holes 227 are arranged at intervals of 90 ° in the circumferential direction, and are respectively provided at a boundary portion between the salient poles Pn and Ps adjacent in the circumferential direction and a boundary portion between the magnet magnetic poles Mn and Mn adjacent in the circumferential direction. It has been. In addition, each slit hole 227 extends along the radial direction from a position near the fixed hole 222a where the rotation shaft 224 of the rotor core 222 is fixed to a position near the permanent magnet 223 and the protrusion 226. In this embodiment, each slit hole 227 penetrates the rotor core 222 in the axial direction. Since each of these slit holes 227 is a gap and has a larger magnetic resistance than the magnetic metal rotor core 222, the magnetic flux of each permanent magnet 223 passing through the rotor core 222 by each slit hole 227 is applied to the adjacent salient poles Pn and Ps. It is suitably guided (see the broken arrow in FIG. 21 (a)).

That is, the rotor 221 includes the magnet magnetic pole Mn and the magnet magnetic pole Ms as the first magnetic pole part, and the salient pole magnetic pole Pn and the salient pole magnetic pole Ps as the second magnetic pole part.
Next, the operation of this embodiment will be described.

A three-phase drive current (AC) having a phase difference of 120 ° is supplied from a drive circuit (not shown) to the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4, respectively. Then, the windings U1 to W4 are excited at the same timing for each phase to generate a rotating magnetic field in the stator 11, and the rotor 221 rotates based on the rotating magnetic field. At this time, the magnetic poles formed on the stator 11 by the supply of the three-phase drive current are the same for the windings U1 to W4 of each phase.

As described above, the number of pole pairs of the rotor 221 (that is, the number of N poles and S poles) is the same as the number of windings U1 to W4 of each phase (“4” in this embodiment). Yes. Thereby, when the rotor 221 rotates, for example, when one of the N poles (magnet magnetic pole Mn and salient pole Pn) of the rotor 221 is opposed to the U-phase winding U1 in the radial direction, the other N pole is U The phase windings U2 to U4 are opposed to each other in the radial direction (see FIG. 21A).

Here, half of the four N poles of the rotor 221 are constituted by salient pole magnetic poles Pn formed by the protrusions 226, and each salient pole magnetic pole Pn functions by the magnetic field of the permanent magnet 223 of the adjacent magnet magnetic pole Ms. Since the magnetic pole is a pseudo magnetic pole, the magnetic force applied to the stator 11 is weaker than the magnetic pole Mn by the permanent magnet 223. The same applies to the S pole of the rotor 221 (the salient pole magnetic pole Ps and the magnet magnetic pole Ms).

Accordingly, for example, each interlinkage magnetic flux φx interlinking the U-phase windings U1 to U4 (U-phase windings U1 and U3 in the example shown in FIG. 21A) facing each magnet magnetic pole Mn. Linkage magnetic flux φy interlinking U-phase windings U1 to U4 (U-phase windings U2 and U4 in the example shown in FIG. 21A) facing salient pole Pn is reduced. Therefore, an induced voltage generated in the U-phase winding (winding facing the salient pole magnetic pole Pn) in which the linkage flux φy is generated is applied to the U-phase winding (winding facing the magnet magnetic pole Mn) in which the linkage flux φx is generated. It becomes smaller than the induced voltage. Therefore, the combined induced voltage obtained by combining the induced voltages generated in the U-phase windings U1 to U4 is a pair of U-phase windings facing the salient pole Pn (in FIG. 21A, U-phase windings U2 and U4). ). Here, the reduction in the combined induced voltage when the U-phase windings U1 to U4 face the N pole (magnet magnetic pole Mn and salient pole Pn) of the rotor 221 has been described as an example, but the V-phase windings V1 to The same applies to the V4 and W-phase windings W1 to W4, and similarly, the resultant induced voltage due to the salient pole magnetic pole Ps also decreases at the S pole (magnet magnetic pole Ms and salient pole magnetic pole Ps) of the rotor 221.

Next, characteristic advantages of this embodiment will be described.
(6) The winding 13 of the stator 11 includes four U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4, respectively, corresponding to the supplied three-phase driving current. Thus, the four windings of each phase are connected in series. That is, the winding 13 of the stator 11 includes at least two windings (first winding and second winding) connected in series in each phase.

The N pole of the rotor 221 is composed of a magnet magnetic pole Mn using the permanent magnet 223 and a salient pole Pn using the protrusion 226 of the rotor core 222. The N pole of the rotor 221 is a salient pole at the rotational position of the rotor 221 where the magnet magnetic pole Mn faces the first winding (for example, the U phase windings U1 and U3) of any of the U, V, and W phases. The magnetic pole Pn is configured to face a second winding having the same phase (for example, U-phase windings U2 and U4). Similarly, the south pole of the rotor 221 includes a magnet magnetic pole Ms using the permanent magnet 223 and a salient pole magnetic pole Ps using the protrusion 226 of the rotor core 222. The S pole of the rotor 221 is a salient pole at the rotational position of the rotor 221 where the magnet magnetic pole Ms faces the first winding (for example, the U phase windings U1 and U3) in any of the U, V, and W phases. The magnetic pole Ps is configured to face a second winding having the same phase (for example, U-phase windings U2 and U4).

According to this configuration, the magnetic force of all the N poles (or S poles) facing the in-phase winding 13 in the rotor 221 is not weakened, but a part of them is used as the salient pole magnetic pole Pn (the salient pole magnetic pole Ps). The magnetic force is weakened. As a result, it is possible to suppress the combined induction voltage generated in the in-phase winding 13 by the magnetic poles of the rotor 221 as much as possible while suppressing a reduction in torque as much as possible. As a result, it is possible to increase the rotation of the motor 210. Further, since the magnetic poles having a weak magnetic force with respect to the magnet magnetic poles Mn and Ms are constituted by the salient pole magnetic poles Pn and Ps formed by the protrusions 226 of the rotor core 222 (that is, a so-called continuous pole type rotor structure), Torque reduction due to weakening the magnetic force of some of the magnetic poles of the rotor 221 can be suppressed as much as possible.

Note that, in the winding mode in which the windings 13 are connected in series in each phase as in the present embodiment, the sum of the induced voltages generated in the respective windings for each phase becomes the combined induced voltage. The voltage tends to increase. Therefore, by providing the salient poles Pn and Ps as described above in the configuration in which the winding 13 is in series in each phase, the effect of suppressing the combined induced voltage can be obtained more remarkably, and the motor high This is more suitable for rotation.

(7) 2n pieces of U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4 (n is an integer of 2 or more, and in this embodiment, n = 2) The number of magnet magnetic poles Mn, Ms and salient pole magnetic poles Pn, Ps of the rotor 221 is n (that is, two). That is, since the magnet magnetic poles Mn, Ms and salient pole magnetic poles Pn, Ps are composed of the same number (half the number of windings of each phase), the magnet magnetic pole Mn and salient pole magnetic pole Pn (magnet magnetic pole Ms and salient pole magnetic pole). Ps) can be alternately provided at equal intervals in the circumferential direction. As a result, the magnet magnetic pole Mn and salient pole magnetic pole Pn (magnet magnetic pole Ms and salient pole magnetic pole Ps) having different magnetic force and mass are arranged in a balanced manner in the circumferential direction, and the rotor 221 is magnetically and mechanically balanced. It can be set as the outstanding structure.

(8) The salient poles Pn and Ps are configured so as to be adjacent to the magnet poles Mn and Ms having different polarities using the permanent magnet 223 in the circumferential direction. The magnetic pole Pn can be made to function suitably as an N pole.

(9) Since the gap K2 is provided between the salient poles Pn, Ps and the magnet poles Mn, Ms having different polarities, the magnetic flux density at the boundary between the salient pole poles Pn, Ps and the magnet poles Mn, Ms. As a result, it is possible to reduce torque pulsation.

(10) The N-pole salient pole Pn and the S-pole salient pole Ps are configured to be adjacent to each other in the circumferential direction via the gap K1. That is, since the gap K1 is provided between the N salient pole Pn and the S salient pole Ps adjacent to each other, the magnetic flux amounts of the salient poles Pn and Ps of each pole are adjusted to a desired value. As a result, the output characteristics of the motor 210 can be easily adjusted.

(11) The rotor core 222 is formed with a slit hole 227 (magnetic adjustment unit) for guiding the magnetic flux flowing through the rotor core 222. According to this configuration, the amount of magnetic flux of the salient poles Pn and Ps magnetized by the permanent magnets 223 adjacent in the circumferential direction can be easily adjusted to a desired value, and as a result, the output characteristics of the motor 210 can be easily adjusted. Is possible. Specifically, the slit hole 227 formed at the boundary between the magnet magnetic poles Mn and Mn adjacent in the circumferential direction suppresses a short circuit of the magnetic flux between the magnet magnetic poles Mn and Ms. Therefore, it is possible to suppress a decrease in the amount of magnetic flux from each magnet magnetic pole Mn, Ms toward the adjacent salient pole magnetic poles Pn, Ps, and as a result, it is possible to contribute to higher torque.

(12) The magnet magnetic poles Mn and Ms are formed by fixing the permanent magnet 223 to the outer peripheral surface (magnet fixing portion 225) of the rotor core 222. That is, since the rotor 221 has a surface magnet type structure (SPM structure), it can contribute to an increase in torque of the motor 210.

In addition, you may change the said embodiment as follows.
Although not specifically mentioned in the above embodiment, field weakening control may be performed when the rotor 221 is rotating at a high speed. In the above embodiment, the rotor 221 is provided with salient poles Pn and Ps that do not spontaneously generate magnetic flux, so that the field-weakening current supplied to the winding 13 can be kept small. Since the field weakening current can be reduced, the permanent magnet 223 is difficult to demagnetize during field weakening control, and the copper loss of the winding 13 can be suppressed. In other words, since the amount of flux linkage that can be reduced with the same amount of field-weakening current increases, higher rotation by field-weakening control can be obtained more effectively.

In the above embodiment, two protrusions 226 of the rotor core 222 are provided in the circumferential direction of each magnet fixing portion 225. However, in addition to this, as shown in FIG. 22, for example, each magnet fixing portion 225 is provided. One may be provided between the circumferential directions. As shown in FIG. 22, the slit hole 227 provided along the boundary between the salient poles Pn and Ps adjacent in the circumferential direction extends to the protrusion 226, thereby generating the magnetic flux of the permanent magnet 223. It is more preferable in terms of flowing through the salient pole magnetic poles Pn and Ps.

The configuration of the arrangement and shape of the slit holes 227 formed in the rotor core 222 is not limited to the above embodiment and the example shown in FIG. 22, and may be configured as shown in FIGS. 23 to 26, for example. . 23 to FIG. 26 show the type of the above embodiment (a type in which the protrusion 226 is divided into two) as an example, but the protrusion 226 as in the example shown in FIG. 22 is divided. It can be applied to other types.

In the example shown in FIG. 23, the slit hole 227 is disposed at a position on the inner side in the radial direction of each permanent magnet 223 and corresponding to the circumferential center of each permanent magnet 223. Thus, by arranging the slit hole 227 on the radially inner side of the permanent magnet 223, the magnetic flux of the permanent magnet 223 passing through the rotor core 222 is branched to both sides in the circumferential direction of the slit hole 227 (in FIG. 23, a broken line). (See arrow for.) Thereby, according to the circumferential direction position of the slit hole 227 in the radial direction inner side of the permanent magnet 223, the amount of magnetic flux between the adjacent protrusions 226 (the salient pole magnetic poles Pn and Ps) in each permanent magnet 223 and the adjacent ones. The amount of magnetic flux between the permanent magnet 223 (magnet magnetic poles Mn, Ms) can be determined, and the output characteristics of the motor 210 can be adjusted more suitably.

In the example shown in FIG. 24, each slit hole 227 has a curved shape that is convex toward the inside in the radial direction. More specifically, each slit hole 227 extends radially inward of each permanent magnet 223 from the position corresponding to the circumferential center of each permanent magnet 223 to the inner peripheral side, and from there to the adjacent protrusion 226. It curves toward the vicinity of the boundary between the salient pole magnetic poles Pn and Ps. Even with such a configuration, it is possible to obtain substantially the same effect as in the example of FIG.

Further, for example, as shown in FIG. 25, an auxiliary magnet 228 may be fitted in the slit hole 227. In this configuration, the slit hole 227 and the auxiliary magnet 228 constitute a magnetic adjustment unit. The auxiliary magnet 228 is composed of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like, and may be any configuration of a sintered magnet and a bonded magnet.

In the example shown in FIG. 25, the auxiliary magnet 228 is provided in a slit hole (slit hole 227a in FIG. 25) provided at the boundary between the salient poles Pn and Ps adjacent in the circumferential direction. That is, the auxiliary magnet 228 is provided at the boundary between the N-pole salient pole Pn and the S-pole salient pole Ps. The auxiliary magnet 228 has a magnetic orientation substantially along the circumferential direction of the rotor 221, and a surface near the salient pole magnetic pole Pn in the circumferential direction is an N pole, and a surface near the salient pole magnetic pole Ps in the circumferential direction is an S pole. It is magnetized to become.

According to such a configuration, not only the magnetic flux of the permanent magnet 223 but also the magnetic flux of the auxiliary magnet 228 flows to the salient pole magnetic poles Pn and Ps, so that the magnetic flux flowing to the salient pole magnetic poles Pn and Ps increases. This can contribute to a higher torque of the motor 210. Even in this case, it is preferable that the magnetic force applied from the rotor 221 to the stator 11 is weaker at the salient pole magnetic poles Pn and Ps than at the magnet magnetic poles Mn and Ms.

In this example, the output characteristics of the motor 210 can be easily adjusted by making the magnetic characteristics (residual magnetic flux density and coercive force) of the auxiliary magnet 228 different from those of the permanent magnet 223. Since the auxiliary magnet 228 is embedded in the rotor core 222 and is not easily affected by an external magnetic field, the coercive force can be set small (or the residual magnetic flux density can be set high).

Further, in the configuration in which the auxiliary magnet 228 is provided, a configuration in which the slit hole 227 similar to that in the above FIG. 23 and FIG. 24 is applied may be adopted. FIG. 26 shows a configuration in which the same slit hole 227 as in FIG. 24 is applied to the configuration in which the auxiliary magnet 228 is provided.

In the rotor 221 of the above-described embodiment, the N pole magnet magnetic poles Mn and the salient pole magnetic poles Pn are provided at positions opposed to each other by 180 ° in the circumferential direction. The poles Ps are provided at 180 ° opposing positions in the circumferential direction. That is, although the magnet magnetic pole Mn and the salient pole magnetic pole Pn are alternately arranged in the circumferential direction, and the magnet magnetic pole Ms and the salient pole magnetic pole Ps are also alternately arranged in the circumferential direction, it is not particularly limited to this. For example, an N-pole salient pole Pn may be provided at a position 180 ° opposite to the N-pole magnet magnetic pole Mn. Similarly, an S-pole salient pole Ps may be provided at a position 180 ° opposite to the S-pole magnet magnetic pole Ms.

In the above embodiment, the number of magnet magnetic poles Mn and salient poles Pn is the same number (for example, half of the number of windings 13 in each phase, ie, two) in the N pole of the rotor 221, for example. There is no need. For example, the number of magnet magnetic poles Mn may be three (or one), and the number of salient pole magnetic poles Pn may be one (or three). The same change may be made for the S pole (magnet magnetic pole Ms and salient pole Ps) of the rotor.

In the above embodiment, the salient pole magnetic pole Pn and the salient pole magnetic pole Ps are provided in the N pole and the S pole of the rotor 221, respectively. However, the present invention is not limited to this. For example, only one pole of the rotor 221 is provided. A salient pole may be provided, and the other pole may be composed entirely of magnet poles.

For example, in the example shown in FIG. 27, in the U phase, the windings U1, U2 are connected in series, and the windings U3, U4 are connected in series, and the series pair of the windings U1, U2 and the windings U3, U4. Are connected in parallel. Similarly, in the V phase, the windings V1 and V2 are connected in series, and the windings V3 and V4 are connected in series. The series pair of the windings V1 and V2 and the series pair of the windings V3 and V4 are parallel. It is connected. Similarly, in the W phase, the windings W1, W2 are connected in series, and the windings W3, W4 are connected in series. The series pair of the windings W1, W2 and the series pair of the windings W3, W4 Are connected in parallel.

27 is applied to the configuration of the rotor 221 of the above embodiment (see FIG. 21), for example, induced voltages having the same magnitude are generated in the winding U1 and the winding U3 in the U phase, for example. In addition, induced voltages having the same magnitude are generated in the winding U2 and the winding U4. For this reason, the combined induced voltage generated in the series pair of the windings U1 and U2 is substantially equal to the combined induced voltage generated in the series pair of the windings U3 and U4. Thereby, the reduction of the induced voltage due to the provision of the salient poles Pn and Ps always occurs in both the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4. Since the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are parallel, the combined induced voltage in the entire U-phase winding is the combined induced voltage of the series pair of the windings U1 and U2 ( And the combined induction voltage of the series pair of windings U3 and U4), and the combined induction voltage in the entire U-phase winding can be effectively suppressed.

Here, when the winding U2 and the winding U3 are interchanged in the example shown in FIG. 27, that is, the windings U1 and U3 having the same magnitude of the induced voltage are connected in series and the magnitude of the induced voltage is the same. Consider the case where the windings U2 and U4 are in series. In this case, the reduction of the induced voltage due to the provision of the salient poles Pn and Ps occurs only in one of the series pair of the windings U2 and U4 and the series pair of the windings U1 and U3. Does not decrease. And since the series pair of winding U1, U3 and the series pair of winding U2, U4 are parallel, it is disadvantageous at the point which suppresses the synthetic | combination induced voltage in the whole U-phase winding effectively. Similarly, when the U-phase windings U1 to U4 are arranged in parallel, similarly, it is disadvantageous in that the combined induced voltage in the entire U-phase winding is effectively suppressed.

As described above, when the windings are arranged in series in each phase, the magnetic pole Mn (magnet magnetic pole Ms) and the salient pole magnetic pole Pn (saliency pole Ps) are opposed to each other at a predetermined rotational position of the rotor 221. By connecting the windings (for example, the U-phase winding U1 and the U-phase winding U2) in series, the weak induced voltage generated in the same-phase winding and the strong induced voltage are added to form a combined induced voltage. And the combined induction voltage in each phase can be effectively suppressed.

In the example of FIG. 27, in the U phase, the windings U1, U2 are a series pair and the windings U3, U4 are a series pair, but the windings U1, U4 and the windings U2, U3 are respectively connected. Similar effects can be obtained as a series pair. The same change can be made in the V phase and the W phase.

In the example of FIG. 27, in the U-phase, the series pair of the windings U1 and U2 and the series pair of the windings U3 and U4 are connected in parallel. , U2 and the series pair of windings U3, U4 may be separated, and a pair of inverters may be provided to supply a U-phase drive current to each of the separated series pairs. The same effect can be obtained by this configuration. The same change can be made in the V phase and the W phase.

Moreover, in the example shown in the said embodiment (refer FIG. 2) and FIG. 27, although the connection aspect of the coil | winding was made into the star connection, it is good not only as this but a delta connection, for example.
The rotor 221 of the above embodiment has a surface magnet type structure (SPM structure) in which the permanent magnets 223 constituting the magnet magnetic poles Mn and Ms are fixed to the outer peripheral surface (magnet fixing portion 225) of the rotor core 222. For example, as shown in FIG. 28, an embedded magnet type structure (IPM structure) may be employed in which a permanent magnet 223a is embedded in an inner portion of the outer peripheral surface 222b of the rotor core 222.

In the example shown in FIG. 28, the outer peripheral surface 222b of the rotor core 222 has a circular shape when viewed in the axial direction, and the radially outer side surface and the radially inner side surface of each permanent magnet 223a constituting the magnetic poles Mn and Ms are viewed in the axial direction. The arc shape is centered on the central axis of the rotor core 222 (the axis L of the rotating shaft 224).

The rotor 221 shown in FIG. 28 is configured as an 8-pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (45 ° intervals) on the outer peripheral surface 222b, as in the above embodiment. . Specifically, the magnetic pole adjacent to the N-pole magnet magnetic pole Mn in the circumferential direction (the magnetic pole on the opposite side of the magnet magnetic pole Mn from the magnet magnetic pole Ms) is configured as a core magnetic pole Cs formed of a part of the rotor core 222, The core magnetic pole Cs functions as an S magnetic pole by the magnetic field of the permanent magnet 223a of the magnet magnetic pole Mn. Similarly, the magnetic pole adjacent to the S magnetic pole Ms in the circumferential direction (the magnetic pole on the opposite side of the magnet magnetic pole Ms from the magnet magnetic pole Mn) is configured as a core magnetic pole Cn composed of a part of the rotor core 222. Cn functions as a magnetic pole of N pole by the magnetic field of the permanent magnet 223a of the magnetic pole Ms.

That is, the magnetic poles on the outer peripheral surface of the rotor 221 are, in order in the clockwise direction, N pole magnet poles Mn, S pole core poles Cs, N pole core poles Cn, S pole magnet poles Ms, and N pole magnet poles. Mn,... Are repeated. Further, the magnet magnetic pole Mn and the core magnetic pole Cn constituting the N pole of the rotor 221 are alternately arranged so that their circumferential center positions are equiangularly spaced (90 ° intervals). The magnetic pole Ms and the core magnetic pole Cs that constitute the S pole are alternately arranged so that their circumferential center positions are equiangularly spaced (90 ° intervals).

The rotor core 222 includes a pair of slit holes 231 extending in the radial direction at the boundary between the core magnetic poles Cn and Cs adjacent in the circumferential direction and the radial direction at the boundary between the magnetic magnetic poles Mn and Ms adjacent in the circumferential direction. A pair of slit holes 232 extending along the line are formed. These slit holes 231 and 232 are alternately formed at equal intervals in the circumferential direction (90 ° intervals).

Each of the slit holes 231 and 232 is an air gap and penetrates the rotor core 222 in the axial direction. Further, each of the slit holes 231 and 232 has a rectangular shape when viewed in the axial direction. Further, the slit hole 231 between the core magnetic poles Cn and Cs extends from the position near the fixed hole 222a to the position near the outer peripheral surface 222b of the rotor core 222 along the radial direction. Further, the slit hole 232 between the magnet magnetic poles Mn and Ms extends from the position near the fixed hole 222a to the position near the permanent magnet 223a along the radial direction.

Since the slit holes 231 and 232 are air gaps, the magnetic resistance is larger than that of the magnetic metal rotor core 222. Therefore, the magnetic fluxes of the permanent magnets 223a passing through the rotor core 222 by the slit holes 231 and 232 are adjacent to each other. It is suitably guided to Cn and Cs (see broken line arrows in FIG. 28).

In the rotor 221 having the SPM structure as in the above embodiment, the permanent magnet 223 fixed to the outer peripheral surface of the rotor core 222 is directly opposed to the stator 11, so that a high torque can be obtained. It becomes easy to demagnetize. In that regard, in the rotor 221 having the IPM structure, the permanent magnet 223a constituting the magnet magnetic poles Mn and Ms is embedded in the rotor core 222, so that demagnetization of the permanent magnet 223 during field-weakening control can be suppressed. .

Further, the rotor core 222 is formed with slit holes 231 and 232 (magnetic adjustment portions) for guiding the magnetic flux flowing in the rotor core 222. According to this configuration, it is easy to adjust the magnetic flux amount of the core magnetic poles Cn and Cs magnetized by the permanent magnets 223a adjacent in the circumferential direction to a desired value, and as a result, the output characteristics of the motor can be easily adjusted. It becomes. In the example shown in FIG. 28, the slit hole 231 between the core magnetic poles Cn and Cs may be omitted.

That is, the rotor 221 shown in FIG. 28 includes a magnet magnetic pole Mn and a magnet magnetic pole Ms as the first magnetic pole part, and a core magnetic pole Cn and a core magnetic pole Cs as the second magnetic pole part.
A rotor 221 shown in FIG. 29 is a further modification of the configuration shown in FIG. 28, and an auxiliary magnet 233 (magnetic adjustment unit) is provided in each slit hole 231 between the core magnetic poles Cn and Cs. Each auxiliary magnet 233 is magnetized so that the surface near the core magnetic pole Cn in the circumferential direction is an N pole and the surface near the core magnetic pole Cs is an S pole. The auxiliary magnet 233 is composed of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like, and may be any configuration of a sintered magnet and a bonded magnet.

According to such a configuration, not only the magnetic flux of the permanent magnet 223a but also the magnetic flux of the auxiliary magnet 233 flows through the core magnetic poles Cn and Cs, so that the magnetic flux flowing through the core magnetic poles Cn and Cs increases. Can contribute to higher torque. Even in this case, it is preferable that the magnetic force applied from the rotor 221 to the stator 11 is weaker at the core magnetic poles Cn and Cs than at the magnetic poles Mn and Ms.

The location of the auxiliary magnet 233 is not limited to the slit hole 231 between the core magnetic poles Cn and Cs. As shown in FIG. 30, the auxiliary magnet 233 is provided in the slit hole 232 between the magnetic poles Mn and Ms. May be. In this case, each auxiliary magnet 233 is preferably magnetized so that the surface near the magnet magnetic pole Ms in the circumferential direction is an N pole and the surface near the magnet magnetic pole Mn is an S pole. Even with the configuration as shown in FIG. 30, it is possible to increase the magnetic flux flowing through the core magnetic poles Cn and Cs, and as a result, it is possible to contribute to an increase in torque of the motor. In the configuration shown in FIG. 30, the auxiliary magnet 233 is provided at the radially inner end of the slit hole 232, but the arrangement position of the auxiliary magnet 233 in the slit hole 232 is limited to the configuration shown in FIG. Instead, it can be appropriately changed according to the configuration.

Further, the rotor 221 shown in FIG. 31 is obtained by changing the configuration shown in FIG. 28, and a communication portion 234 that connects the slit hole 231 and the slit hole 232 at their inner end portions is formed. In the example shown in FIG. 31, in the rotor core 222, the pair of support portions 222d that support the central portion 222c having the fixed hole 222a divide the slit hole 231 along the boundary portion between the core magnetic poles Cn and Cs. Is formed. The communication part 234 becomes a magnetic resistance between the adjacent core magnetic poles Cn and Cs and between the adjacent magnet magnetic poles Mn and Ms at the radially inner ends of the slit holes 231 and 232. According to such a configuration, the short-circuit magnetic flux that can be generated between the permanent magnets 223a constituting the magnet magnetic poles Mn and Ms by the communication portion 234 can be suppressed to a low level. For this reason, the magnetic flux which flows into core magnetic pole Cn, Cs increases, As a result, it can contribute to the high torque increase of a motor.

Further, the rotor 221 shown in FIG. 32 is a modification of the configuration shown in FIG. 31. In the rotor core 222, a pair of support portions 222e that support the center portion 222c are along the boundary between the magnetic poles Mn and Ms. The slit hole 232 is divided. According to this configuration, the central portion 222c of the rotor core 222 can be stably supported by the

support portions

222d and 222e. In addition, in the example shown in FIG. 32, it is good also as a structure which abbreviate | omitted support part 222d.

Further, the rotor 221 shown in FIG. 33 is a further modification of the configuration shown in FIG. 32, and an auxiliary magnet 235 (magnetic adjustment part) is provided in each communication part 234. The auxiliary magnet 235 provided in the communication portion 234 formed across the N-pole core magnetic pole Cn and the S-pole magnet magnetic pole Ms is magnetized so that the radially outer surface becomes the N pole. Further, the auxiliary magnet 235 provided in the communication portion 234 formed across the core magnetic pole Cs having the S pole and the magnet magnetic pole Mn having the N pole is magnetized so that the radially outer surface becomes the S pole. Yes. One end of each auxiliary magnet 235 (the end opposite to the slit hole 231) is set at a position corresponding to the boundary line between the core magnetic poles Cn and Cs and the magnet magnetic poles Mn and Ms. Even with the configuration as shown in FIG. 33, it is possible to increase the magnetic flux flowing through the core magnetic poles Cn and Cs. As a result, it is possible to contribute to an increase in torque of the motor. In the configuration shown in FIG. 33, the auxiliary magnet 235 is provided at a position near the core magnetic poles Cn and Cs in each communication portion 234. However, the arrangement position of the auxiliary magnet 235 in the communication portion 234 is limited to the configuration shown in FIG. However, it can be appropriately changed according to the configuration.

In the above embodiment, the rotor 221 has 8 poles and the number of windings 13 of the stator 11 is 12 (that is, the motor configuration has 8 poles and 12 slots). The number of can be appropriately changed according to the configuration. For example, the number of poles of the rotor 221 and the number of windings 13 are appropriately changed so that the relationship between the number of poles of the rotor 221 and the number of windings 13 is 2n: 3n (where n is an integer of 2 or more). May be.

In the case of a configuration of 6 poles 9 slots, 10 poles 15 slots, etc. (when the greatest common divisor n of the number of poles of the rotor 221 and the number of windings 13 is an odd number), the number of pole pairs of the rotor 221 is an odd number, That is, the number of N poles and S poles is an odd number. For this reason, for example, the number of magnet magnetic poles Mn and salient pole magnetic poles Pn cannot be the same, resulting in a magnetically unbalanced configuration. In that respect, in the configuration in which the greatest common divisor n of the number of rotors 221 and the number of windings 13 is an even number as in the above-described embodiment, the number of magnet magnetic poles Mn and salient poles Pn can be the same. A magnetically balanced configuration can be achieved.

Further, the relationship between the number of poles of the rotor 221 and the number of windings 13 is not necessarily 2n: 3n (where n is an integer of 2 or more). For example, 10 poles 12 slots, 14 poles 12 slots, etc. It may be configured.

FIG. 34 shows an example of a motor 230 configured with 10 poles and 12 slots. In the example of FIG. 34, the same components as those in the above embodiment are denoted by the same reference numerals, detailed description thereof will be omitted, and different portions will be described in detail.

In the motor 230 shown in FIG. 34, the twelve windings 13 of the stator 11 are classified according to the supplied three-phase drive currents (U phase, V phase, W phase), and are counterclockwise in FIG. In this order, U1, bar U2, bar V1, V2, W1, bar W2, bar U1, U2, V1, bar V2, bar W1, W2. In addition, U phase winding bar U1, bar U2, V phase winding bar V1 with respect to U phase windings U1, U2, V phase windings V1, V2 and W phase windings W1, W2 constituted by positive windings. , Bar V2, W-phase winding bar W1, bar W2 are constituted by reverse winding. Further, the U-phase winding U1 and the bar U1 are placed at positions facing each other by 180 °, and similarly, the U-phase winding U2 and the bar U2 are placed at positions facing each other by 180 °. The same applies to the other phases (V phase and W phase).

The rotor 221 of the motor 230 is a 10-pole rotor in which N poles and S poles are alternately set at equal intervals in the circumferential direction (36 ° intervals), and includes three magnet magnetic poles Mn, two magnet magnetic poles Ms, 2 Two salient poles Pn and three salient poles Ps are provided. Specifically, the magnetic poles of the rotor 221 are, in order in the clockwise direction, the S-pole magnet magnetic pole Ms, the N-pole magnet magnetic pole Mn, the S-pole salient pole Ps, the N-pole magnet magnetic pole Mn, and the S-pole magnet. The magnetic pole Ms, the N pole salient pole Pn, the S pole salient pole Ps, the N pole magnet magnetic pole Mn, the S pole salient pole Ps, and the N pole salient pole Pn. That is, the S-pole salient pole Ps is located on the opposite side of the N-pole magnet magnetic pole Mn in the circumferential direction (180 ° facing position), and the N-pole is located on the opposite side in the circumferential direction of the S-pole magnet magnetic pole Ms (180 ° facing position). The salient pole magnetic pole Pn of the pole is located. Further, the rotor core 222 is similar to the above embodiment at the positions corresponding to the boundary between the magnetic poles Mn and Ms adjacent in the circumferential direction and the boundary between the salient poles Pn and Ps adjacent in the circumferential direction. The slit hole 227 is formed.

The number of magnet magnetic poles Mn, Ms and salient pole magnetic poles Pn, Ps is not limited to the example of the 10-pole rotor of FIG. 34. For example, two magnet magnetic poles Mn, three magnet magnetic poles Ms, You may comprise three salient pole magnetic poles Pn and two salient pole magnetic poles Ps. Also, in the rotor 221 of the example shown in FIG. 34, a slit hole 227 as shown in FIG. 23 or FIG. 24 may be added, and an auxiliary magnet 228 is added to the slit hole 227a as shown in FIG. 25 or FIG. A fitted configuration may be added.

In the above configuration, when the rotor 221 rotates, for example, when the S-pole magnet magnetic pole Ms faces the U-phase winding U1 in the radial direction, the N-pole salient pole Pn is placed on the U-phase winding on the opposite side in the circumferential direction. It faces the bar U1 in the radial direction (see FIG. 34). In other words, one of the magnetic poles having different polarities facing the windings 13 (for example, the U-phase winding U1 and the bar U1) excited in opposite phases (same timing), one of which is composed of the magnet magnetic pole Ms (magnet magnetic pole Mn). The other is composed of salient pole magnetic poles Pn (saliency pole magnetic poles Ps). As a result, it is possible to suppress the combined induction voltage (for example, the combined induction voltage of the U-phase winding U1 and the bar U1) generated in the anti-phase winding 13 by the magnetic poles of the rotor 221 as much as possible while suppressing a decrease in torque. As a result, high rotation of the motor 230 can be achieved.

The arrangement of the magnetic poles of the rotor 221 is not limited to the example shown in FIG. 34. The salient pole Ps is located on the opposite side of the magnet magnetic pole Mn in the circumferential direction, and the opposite side of the magnet magnetic pole Ms in the circumferential direction. As long as the salient pole magnetic pole Pn is positioned, the arrangement of the magnetic poles of the rotor 221 can be changed as appropriate.

Further, in the stator 11, it is not necessary that all the U-phase windings U1, U2, bar U1, and bar U2 are connected in series, and the windings U1, bar U1, and windings U2, U2 are respectively connected in different series. A paired configuration may be used. Moreover, it can change similarly also in V phase and W phase.

FIG. 34 shows an example of 10 poles and 12 slots, but the present invention can also be applied to a 14 poles and 12 slots structure. Further, the present invention can also be applied to a configuration in which the number of rotor poles and the number of slots of 10 poles and 12 slots (or 14 poles and 12 slots) are equal. FIG. 34 shows an example of a type in which the protrusion 226 is divided into a plurality according to the magnetic pole, but the present invention can also be applied to a type in which the protrusion 226 is not divided as in the example shown in FIG. .

In the above embodiment, the magnetic flux guiding part (magnetic) for guiding the magnetic flux of the magnet magnetic poles Mn and Ms toward the circumferential center CL (the circumferential center of the projecting part 226) of the salient pole magnetic poles Pn and Ps (projecting part 226). An adjustment unit) may be provided in the rotor core 222.

For example, in the configuration shown in FIG. 35, a magnetic flux guiding recess 226a serving as the magnetic flux guiding portion is formed in the radially outer surface of each salient pole magnetic pole Pn, Ps. More specifically, on the radially outer side surface of each salient pole magnetic pole Pn (projection 226), the magnetic flux guiding recess 226a is formed at the end near the adjacent magnet magnetic pole Ms. Similarly, on the radially outer surface of each salient pole magnetic pole Ps (projection 226), the magnetic flux guiding recess 226a is formed at the end near the adjacent magnet magnetic pole Mn. In the example of FIG. 35, each magnetic flux guiding recess 226a is set to about ¼ of the circumferential width of the protrusion 226. Further, the circumferential center CL of the protrusion 226 and the circumferential center of the permanent magnet 223 are set at equal circumferential intervals (45 ° intervals).

According to such a configuration, for example, the magnetic flux φa directed from the magnet magnetic pole Ms (permanent magnet 223) to the adjacent salient pole magnetic pole Pn through the rotor core 222 is surrounded by the magnetic flux guiding recess 226a around the salient pole magnetic pole Pn (projection 226). It is guided toward the direction center CL. As a result, the circumferential magnetic pole centers (peak positions of the magnetic flux density) of the magnetic poles of the rotor 221 (that is, the magnetic magnetic poles Mn and Ms and the salient magnetic poles Pn and Ps) are equally spaced in the circumferential direction (in the example of FIG. 45 ° intervals), and as a result, it can contribute to higher torque.

In the example shown in FIG. 35, the magnetic flux guiding portion (magnetic flux guiding recess 226a) is provided on the radially outer surface of the salient pole magnetic poles Pn, Ps. However, the location where the magnetic flux guiding portion is provided is not limited thereto. For example, holes (gap portions) formed in the rotor core 222 in the salient pole magnetic poles Pn and Ps may function as the magnetic flux guiding portions.

In FIG. 35, the present invention is applied to the surface magnet type structure (SPM structure), but the present invention may be applied to an embedded magnet type structure (IPM structure).
An example of the rotor 221 applied to the IPM structure is shown in FIG. In the rotor 221 shown in the figure, the arrangement configuration of the magnetic poles (the circumferential positions of the magnetic poles Mn and Ms and the core magnetic poles Cn and Cs) is substantially the same as the IPM structure (for example, see the configuration of FIG. 28). . That is, the magnetic poles of the rotor 221 are arranged in order in the clockwise direction: N pole magnetic pole Mn, S pole core pole Cs, N pole core pole Cn, S pole magnet pole Ms, N pole magnet pole Mn,.・ It has a structure that repeats.

36, each magnet magnetic pole Mn, Ms includes a pair of permanent magnets 241 embedded in the rotor core 222. In the configuration shown in FIG. In each of the magnetic poles Mn and Ms, the pair of permanent magnets 241 is arranged in a substantially V shape that expands to the outer peripheral side when viewed in the axial direction, and on the magnetic pole center line in the circumferential direction (see the straight line L1 in FIG. 36). On the other hand, they are provided symmetrically. Each permanent magnet 241 has a rectangular parallelepiped shape. In addition, the pair of permanent magnets 241 in each of the magnetic poles Mn and Ms has an angular range (this example) when the rotor 221 is equally divided by the number of poles (the total number of the magnetic poles Mn and Ms and the core magnetic poles Cn and Cs) in the circumferential direction. In the range of 45 °.

In FIG. 36, the magnetization directions of the permanent magnets 241 of the N-pole magnet magnetic pole Mn and the S-pole magnet magnetic pole Ms are indicated by solid arrows, and the tip end side of the arrow represents the N pole and the base end side of the arrow represents the S pole. ing. As indicated by the arrows, the permanent magnets 241 in the N-pole magnet magnetic pole Mn face each other (the face on the magnetic pole center line side) so that the outer peripheral face of the magnet magnetic pole Mn is the N-pole. Is magnetized so that the N pole appears. In addition, each permanent magnet 241 in the S magnetic pole Ms has the S poles appearing on the surfaces facing each other (the surface on the magnetic pole center line side) so that the outer peripheral surface of the magnet magnetic pole Ms becomes the S pole. Magnetized.

The rotor core 222 is formed with a pair of slit holes 231 extending along the radial direction at the boundary between the core magnetic poles Cn and Cs adjacent in the circumferential direction. Each slit hole 231 extends from the position near the fixed hole 222a to the position near the outer peripheral surface 222b of the rotor core 222 along the radial direction.

Further, the rotor core 222 is formed with a magnetoresistive hole 242 (magnetic adjustment portion) at a position on the inner peripheral side with respect to the pair of permanent magnets 241 in each magnet magnetic pole Mn, Ms. Each magnetoresistive hole 242 is a rectangular hole that is long in the radial direction when viewed in the axial direction, and is provided at the circumferential center position of each magnet magnetic pole Mn, Ms. That is, in this example, the distance between the centers of the magnetic resistance holes 242 of the magnet magnetic poles Mn and Ms adjacent in the circumferential direction is set to 45 °.

Each slit hole 231 and each magnetoresistive hole 242 penetrate the rotor core 222 in the axial direction, and each slit hole 231 and each magnetoresistive hole 242 are voids. Thereby, each magnetoresistive hole 242 suppresses the short circuit of the magnetic flux between the magnet magnetic poles Mn and Ms adjacent in the circumferential direction, and each slit hole 231 causes the magnetic flux of the magnet magnetic poles Mn and Ms to pass through the core magnetic poles Cn and Cs. Suppresses short circuit. That is, the magnetic fluxes of the magnet magnetic poles Mn and Ms passing through the rotor core 222 are preferably guided to the adjacent core magnetic poles Cn and Cs by the slit holes 231 and the magnetic resistance holes 242.

Further, gaps K3 and K4 are provided on the inner peripheral side and the outer peripheral side of each permanent magnet 241 respectively. Each gap K3, K4 is a part of each magnet accommodation hole 244 formed in the rotor core 222 and accommodates each permanent magnet 241. The inner peripheral side surface of each permanent magnet 241 faces each gap K3, The inner peripheral side surface of each permanent magnet 241 is configured to face each gap K4. That is, a gap K3 is provided between the permanent magnet 241 and the radially inner end of the magnet accommodation hole 244, and a gap K4 is provided between the permanent magnet 241 and the radially outer end of the magnet accommodation hole 244. Yes.

The magnetic resistance of each of the gaps K3 and K4 can suppress the short circuit of the magnetic flux in each of the permanent magnets 241 (the magnetic flux of each permanent magnet 241 is shorted between its own N and S poles via the rotor core 222). It has become. That is, also by the gaps K3 and K4, the magnetic fluxes of the magnet magnetic poles Mn and Ms are preferably guided to the adjacent core magnetic poles Cn and Cs, which can contribute to higher torque.

Here, in the rotor core 222 of this example, a magnetic flux guiding hole 243 (magnetic flux guiding portion) for guiding the magnetic flux of the magnet magnetic poles Mn and Ms toward the circumferential center CL of the core magnetic poles Cn and Cs is formed. Each magnetic flux guide hole 243 is provided at a position near the magnet magnetic poles Mn and Ms adjacent to each other in the circumferential direction in each of the core magnetic poles Cn and Cs. More specifically, in each of the core magnetic poles Cn and Cs, the magnetic flux guide hole 243 communicates with the magnet accommodation hole 244 (magnet accommodation hole 244a in FIG. 36) in which the nearest permanent magnet 241 is accommodated, and the magnet accommodation hole. It is formed to extend from 244a into the core magnetic poles Cn and Cs along the circumferential direction. Each magnetic flux guide hole 243 is formed at a position corresponding to the radially outer end of the nearest permanent magnet 241. The radial width of each magnetic flux guide hole 243 is set to ¼ or less of the long side length of the permanent magnet 241 when viewed in the axial direction.

According to such a configuration, for example, the magnetic flux φa directed from the magnet magnetic pole Ms to the adjacent core magnetic pole Cn through the rotor core 222 is guided toward the circumferential center CL of the core magnetic pole Cn by the magnetic flux guide hole 243. As a result, the magnetic pole centers (the peak positions of the magnetic flux density) in the circumferential direction of the magnetic poles of the rotor 221 (namely, the magnetic magnetic poles Mn and Ms and the core magnetic poles Cn and Cs) are set at equal circumferential intervals (45 in the example of FIG. ° interval), and as a result, can contribute to higher torque.

In addition, according to the configuration of the magnet magnetic poles Mn and Ms of this example (arrangement configuration of the permanent magnet 241), it is possible to increase the rotor core volume (volume of the outer core portion 22g) on the outer peripheral side of the permanent magnet 241. Thus, the reluctance torque can be increased, which can contribute to further increase in torque.

Further, in this example, since a short circuit of the magnetic flux between the N-pole magnet magnetic pole Mn and the S-pole magnet magnetic pole Ms adjacent in the circumferential direction is suppressed by the magnetoresistive hole 242, it is adjacent to each magnet magnetic pole Mn, Ms. Decrease in the amount of magnetic flux toward the core magnetic poles Cn and Cs can be suppressed, and as a result, high torque can be contributed. Further, the magnetoresistive hole 242 is provided radially inward from the permanent magnet 241 in the magnet magnetic poles Mn and Ms in which the pair of permanent magnets 241 are arranged in a V shape, so that the magnetoresistive hole 242 is adjacent in the circumferential direction. Short-circuiting of the magnetic flux between the magnet poles Mn and Ms having different polarities can be suitably suppressed.

In this example, the core magnetic poles Cn and Cs adjacent in the circumferential direction are connected to each other at both ends in the radial direction of the slit hole 231. However, the present invention is not limited to this, and the core magnetic poles Cn and Cs are connected to the slit hole. You may comprise so that any one of the radial direction inner side edge part of 231 and a radial direction outer side edge part may be connected. In the example shown in FIG. 36, each magnetoresistive hole 242 may extend radially inward to the inner peripheral surface (fixed hole 222a) of the rotor core 222.

Also, the configuration shown in FIG. 36 may be changed as shown below. The rotor 221 shown in FIG. 37 has a configuration in which the auxiliary magnet 251 (magnetic adjustment unit) is arranged in each slit hole 231 having the configuration shown in FIG. 36 and the auxiliary magnet 252 (magnetic adjustment unit) is arranged in each magnetic flux guide hole 243. Each auxiliary magnet 251 is provided at a position closer to the inside in the radial direction in each slit hole 231. Note that the radial length of the auxiliary magnet 251 is set to be equal to or less than half the radial length of the slit hole 231.

Also in FIG. 37, the magnetization directions of the permanent magnets 241 and the

auxiliary magnets

251 and 252 are indicated by solid arrows, and the tip end side of the arrow represents the N pole and the base end side of the arrow represents the S pole. As indicated by the arrows, each auxiliary magnet 251 is magnetized so that the surface near the core magnetic pole Cn in the circumferential direction is an N pole and the surface near the core magnetic pole Cs is an S pole. The auxiliary magnet 252 provided in the magnetic flux guide hole 243 of the N-pole magnet magnetic pole Mn is magnetized so that the radially outer surface becomes the N-pole, and provided in the magnetic flux guide hole 243 of the S-pole magnet magnetic pole Ms. The auxiliary magnet 252 thus magnetized is magnetized so that the radially outer surface becomes the south pole. The

auxiliary magnets

251 and 252 are made of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN magnet, a ferrite magnet, an alnico magnet, or the like, and may be any of a sintered magnet and a bonded magnet.

According to such a configuration, since not only the magnetic fluxes of the adjacent magnet magnetic poles Mn and Ms but also the magnetic fluxes of the

auxiliary magnets

251 and 252 flow in the core magnetic poles Cn and Cs, the magnetic flux flowing through the core magnetic poles Cn and Cs increases. As a result, it is possible to contribute to higher torque of the motor. Even in this case, it is preferable that the magnetic force applied from the rotor 221 to the stator 11 is weaker at the core magnetic poles Cn and Cs than at the magnetic poles Mn and Ms.

In the example shown in FIG. 37, the auxiliary magnet 251 is disposed in the slit hole 231 and the auxiliary magnet 252 is disposed in the magnetic flux guide hole 243. However, any one of the

auxiliary magnets

251 and 252 may be omitted.

In the above embodiment, the permanent magnet 223 is a sintered magnet, but other than this, for example, a bonded magnet may be used.
In the above embodiment, the present invention is embodied in the inner rotor type motor 210 in which the rotor 221 is disposed on the inner peripheral side of the stator 11. However, the present invention is not particularly limited thereto, and the rotor is disposed on the outer peripheral side of the stator. The present invention may be embodied in an outer rotor type motor.

In the above embodiment, the present invention is embodied in the radial gap type motor 210 in which the stator 11 and the rotor 221 are opposed to each other in the radial direction. However, the present invention is not particularly limited thereto, and the stator and the rotor are in the axial direction. The present invention may be applied to an axial gap type motor that faces the motor.

-You may combine embodiment mentioned above and each modification suitably.
Hereinafter, a fourth embodiment of the motor will be described.
As shown in FIG. 38A, the motor 310 of the present embodiment is configured as a brushless motor, and is configured with a rotor 321 disposed inside an annular stator 11. Since the configuration of the stator 11 is the same as that of the stator 11 of the first embodiment, detailed description thereof is omitted. The winding 13 of the stator 11 is also configured similarly to the winding 13 of the first embodiment.

[Configuration of rotor]
As shown in FIG. 38B, the rotor 321 has an embedded magnet type structure (IPM structure) in which a permanent magnet 322 forming a magnetic pole is embedded in the rotor core 323. The rotor core 323 is formed in a cylindrical shape by laminating a plurality of core sheets made of a circular plate-shaped magnetic metal in the axial direction, and a rotating shaft 324 is inserted and fixed at the center of the rotor core 323. A fixing hole 323a is formed.

The rotor 321 is configured as an 8-pole rotor in which N poles and S poles are alternately set on the outer peripheral surface 323b of the rotor core 323. Specifically, the rotor 321 includes an N-pole magnet magnetic pole Mn, an S-pole magnet magnetic pole Ms, an N-pole core magnetic pole Cn, and an S-pole core magnetic pole Cs. Each of the magnetic poles Mn and Ms is a magnetic pole using the permanent magnet 322, and each of the core magnetic poles Cn and Cs is a magnetic pole using a part of the rotor core 323.

Each of the magnetic poles Mn and Ms of the N pole and the S pole includes a pair of permanent magnets 322 embedded in the rotor core 323. In each of the magnetic poles Mn and Ms, the pair of permanent magnets 322 are arranged in a substantially V shape that expands to the outer peripheral side when viewed in the axial direction, and a magnetic pole center line in the circumferential direction (straight line L1 in FIG. 38B). For reference). Each permanent magnet 322 forms a rectangular parallelepiped. The pair of permanent magnets 322 in each of the magnetic poles Mn and Ms is equally divided by the number of poles in the circumferential direction of the rotor 321 (the total number of the magnetic poles Mn and Ms and the core magnetic poles Cn and Cs, which is 8 in this embodiment). It is arranged so that it falls within the angle range (45 ° range in this embodiment). Each permanent magnet 322 is, for example, an anisotropic sintered magnet, and includes, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN magnet, a ferrite magnet, an alnico magnet, or the like.

In FIG. 38 (b), the magnetization directions of the permanent magnets 322 of the N-pole magnet magnetic pole Mn and the S-pole magnet magnetic pole Ms are indicated by solid arrows, and the tip end side of the arrow is the N pole and the base end side of the arrow is the S pole. Represents. As indicated by the arrows, the permanent magnets 322 in the N-pole magnet magnetic pole Mn are surfaces facing each other (the surface on the magnetic pole center line side) so that the outer peripheral surface of the magnet magnetic pole Mn is the N-pole. Is magnetized so that the N pole appears. In addition, each permanent magnet 322 in the magnetic pole Ms having the S pole has the S poles appearing on the surfaces facing each other (the surface on the magnetic pole center line side) so that the outer peripheral surface of the magnetic pole Ms becomes the S pole. Magnetized.

The N-pole magnet magnetic pole Mn and the S-pole magnet magnetic pole Ms are arranged adjacent to each other so that the distance between the circumferential center positions (magnetic pole centers) is 45 °. A pair of the magnetic pole Mn and the magnetic pole Ms of the S pole is referred to as a magnetic pole pair P. And in the rotor 321 of this embodiment, the two magnet magnetic pole pairs P are provided in the 180 degree opposing position of the circumferential direction. More specifically, the N-pole magnetic pole Mn of one magnet pole pair P and the N-pole magnet pole Mn of the other magnet pole pair P are disposed at positions opposite to each other by 180 °. The S-pole magnet magnetic pole Ms of the pair P and the S-pole magnet magnetic pole Ms of the other magnet magnetic pole pair P are arranged at 180 ° opposite positions. That is, the magnetic poles Mn and Ms (permanent magnets 322) are provided so as to be point-symmetric about the axis L of the rotor 321 (the axis of the rotating shaft 324).

Further, the opening angle θm (occupied angle) around the axis L of the magnet magnetic poles Mn and Ms is set to an angle (45 ° in this embodiment) obtained by equally dividing the rotor 321 by the number of poles in the circumferential direction. . That is, the opening angle of each magnetic pole pair P composed of the magnetic poles Mn and Ms adjacent in the circumferential direction is approximately 90 °.

Here, in the circumferential direction of the rotor core 323, the occupying angle of the pair of magnet magnetic pole pairs P is approximately 180 °, and the remaining range is a portion where the magnet is not disposed (non-magnet magnetic pole portion 325). That is, in the rotor core 323, a pair of magnet magnetic pole pairs P and a pair of non-magnet magnetic pole portions 325 are alternately configured at intervals of approximately 90 ° in the circumferential direction.

Each non-magnet magnetic pole portion 325 is provided with a pair of

slit portions

326a and 326b as magnetic resistance portions. In this embodiment, each slit

part

326a, 326b extends from the vicinity of the fixing hole 323a of the rotor core 323 to the vicinity of the outer peripheral surface 323b of the rotor core 323 along the radial direction. Each

slit

326a, 326b is a hole that penetrates the rotor core 323 in the axial direction.

In each non-magnet magnetic pole portion 325, the pair of

slit portions

326a and 326b are formed so as to be line symmetric with respect to the circumferential center line L2 of the non-magnet magnetic pole portion 325. Note that a portion near the N-pole magnetic pole Mn with respect to the circumferential center line L2 is a slit portion 326a, and a portion near the S-pole magnet magnetic pole Ms is a slit portion 326b. In the present embodiment, in the circumferential direction of the rotor 321, the angle formed by the circumferential center line L2 and the

slit portions

326a and 326b is set to approximately 25 °. That is, in each non-magnet magnetic pole portion 325, the circumferential angle formed by the pair of

slit portions

326a and 326b is set to about 50 °. Thus, the angle formed by the pair of

slit portions

326a and 326b of the non-magnet magnetic pole portion 325 is preferably set to be half or more of the open angle of the non-magnet magnetic pole portion 325 (approximately 90 ° in the present embodiment). The angle formed by the circumferential center line L2 of the non-magnet magnetic pole portion 325 and the circumferential center line L3 of the magnet magnetic pole pair P (boundary line between the adjacent magnet magnetic poles Mn and Ms) is 90 °.

The rotor core 323 is formed with a magnetoresistive hole 327 at a position on the inner peripheral side of the pair of permanent magnets 322 in each of the magnetic poles Mn and Ms. Each magnetoresistive hole 327 is a rectangular hole that is long in the radial direction when viewed in the axial direction, and is provided at the center position in the circumferential direction of each of the magnet magnetic poles Mn and Ms. In other words, in the present embodiment, the distance between the centers of the magnetoresistive holes 327 of the magnet magnetic poles Mn and Ms adjacent in the circumferential direction is set to 45 °. Each magnetoresistive hole 327 passes through the rotor core 323 in the axial direction.

Further, gaps K1 and K2 are provided on the inner peripheral side and the outer peripheral side of each permanent magnet 322, respectively. Each gap K1, K2 is a part of each magnet accommodation hole 323c formed in the rotor core 323 for accommodating each permanent magnet 322, and the inner peripheral side surface of each permanent magnet 322 faces each gap K1, The inner peripheral side surface of the permanent magnet 322 is configured to face each gap K2. That is, a gap K1 is provided between the permanent magnet 322 and the radially inner end of the magnet accommodation hole 323c, and a gap K2 is provided between the permanent magnet 322 and the radially outer end of the magnet accommodation hole 323c. Yes.

Each magnetic resistance hole 327 suppresses a short circuit of magnetic flux between the magnet magnetic poles Mn and Ms in each magnet magnetic pole pair P, and suppresses a magnetic flux short circuit in each permanent magnet 322 by the gaps K1 and K2. As a result, the magnetic flux (magnet magnetic flux) of the permanent magnet 322 of each magnet magnetic pole Mn, Ms is efficiently guided to the outer peripheral side of the magnet magnetic pole Mn, Ms and the non-magnetic magnetic pole portion 325 in the circumferential direction. ing.

Here, each non-magnet magnetic pole portion 325 of the rotor core 323 is divided into three regions by a pair of

slit portions

326a and 326b, and a region adjacent to the N-pole magnet magnetic pole Mn in the circumferential direction (the slit portion 326a and the magnet). A region between the magnetic pole Mn and the magnetic pole Mn is configured as an S-pole core magnetic pole Cs. A region adjacent to the S-pole magnet magnetic pole Ms in the circumferential direction (region between the slit 326b and the magnet magnetic pole Ms) is configured as an N-pole core magnetic pole Cn.

More specifically, magnet magnetic flux flowing from the N-pole magnet magnetic pole Mn toward the circumferential non-magnet magnetic pole portion 325 (portion not adjacent to the magnet magnetic pole Ms) is applied to the outer peripheral surface 323b of the rotor core 323 by the magnetic resistance of the slit portion 326a. Be directed towards. Thereby, the region adjacent to the N-pole magnet magnetic pole Mn in the non-magnet magnetic pole portion 325 functions as an S-pole core magnetic pole Cs (pseudo magnetic pole) by the magnet magnetic flux of the magnet magnetic pole Mn.

Similarly, the magnetic flux that flows from the magnetic pole Ms of the S pole toward the circumferential non-magnet magnetic pole part 325 (the part not adjacent to the magnetic pole Mn) is applied to the outer peripheral surface 323b of the rotor core 323 by the magnetic resistance of the slit part 326b. Be directed towards. As a result, a region adjacent to the S-pole magnet magnetic pole Ms in the non-magnet magnetic pole portion 325 functions as an N-pole core magnetic pole Cn (pseudo-magnetic pole) by the magnet magnetic flux of the magnet magnetic pole Ms.

In each non-magnet magnetic pole portion 325, the region between the pair of

slit portions

326a and 326b (that is, between the core magnetic poles Cn and Cs) (inter-slit core portion 328) is magnetized by the magnetic resistance of the

slit portions

326a and 326b. The magnetic poles Mn and Ms are configured not to be affected by the magnetic flux of the magnetic poles Ms and Ms. That is, the inter-slit core portion 328 of each non-magnet magnetic pole portion 325 is configured not to form a magnetic pole due to the magnet magnetic flux of the magnet magnetic poles Mn and Ms (permanent magnet 322).

In the rotor 321 having the above-described configuration, the N-pole magnet magnetic pole Mn, the S-pole core magnetic pole Cs, the inter-slit core portion 328, the N-pole core magnetic pole Cn, and the S-pole magnet magnetic pole in order in the clockwise direction in the circumferential direction. Ms, N magnetic poles Mn,... Are repeated.

Note that the opening angle θa (occupied angle) around the axis L of each inter-slit core portion 328 is substantially equal to the circumferential angle formed by the

slit portions

326a and 326b, and is approximately 50 ° in the present embodiment. It has become. Further, the opening angle θc (occupied angle) around the axis L of each of the core magnetic poles Cn and Cs is determined based on the relationship in which the inter-slit core portion 328 is formed in each non-magnet magnetic pole portion 325. It is configured to be smaller than the angle θm (45 ° in the present embodiment).

Next, the operation of this embodiment will be described.
A three-phase drive current (AC) having a phase difference of 120 ° is supplied from a drive circuit (not shown) to the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4, respectively. Then, the windings U1 to W4 are excited at the same timing for each phase, and a rotating magnetic field is generated in the stator 11. Then, the rotor 321 rotates by the interaction between the rotating magnetic field of the stator 11 and the magnetic flux of the magnetic poles of the rotor 321 (magnet magnetic poles Mn, Ms and core magnetic poles Cn, Cs).

When the rotor 321 rotates at high speed, field weakening control for supplying a field weakening current (d-axis current) to the winding 13 is executed. Here, the magnetic action by the field weakening control will be described with reference to FIGS. 39 (a) and 39 (b). 39 (a) and 39 (b), for convenience of explanation, only the U phase is shown as the configuration of the stator 11, and the other phases are not shown.

The rotational position of the rotor 321 as shown in FIG. 39A during the high-speed rotation of the rotor 321 (during field weakening control), that is, the N-pole magnet magnetic pole Mn faces the U-phase windings U1 and U3 in the radial direction. In addition, an explanation will be given by taking as an example the rotational position of the rotor 321 in which the core portion 328 between the slits faces the U-phase windings U2 and U4 in the radial direction. At this time, in the U-phase windings U1 and U3, the magnetic flux (magnetic flux outward in the radial direction) generated by the opposing N-pole magnet magnetic pole Mn is the flux linkage caused by the field weakening current (linkage magnetic flux in the radial inner direction). ), And the interlinkage magnetic flux φx that passes outward in the radial direction is generated in the U-phase windings U1 and U3.

On the other hand, in the U-phase windings U2 and U4, the portion of the opposing rotor 321 is not a magnetic pole but an inter-slit core portion 328 that is hardly affected by the magnet magnetic flux. For this reason, the d-axis magnetic flux generated by the supply of the field weakening current (d-axis current) passes through the inter-slit core portion 328 (rotor core 323) without being substantially affected by the magnetic flux of the rotor 321. As a result, the interlinkage magnetic flux φy passing inward in the radial direction based on the field weakening current is generated in the U-phase windings U2 and U4 without being canceled by the magnetic poles of the rotor 321. That is, in the U-phase windings U2 and U4, an interlinkage magnetic flux φy having a phase opposite to the interlinkage magnetic flux φx generated in the U-phase windings U1 and U3 by the magnetic pole Mn is generated.

At this time, induced voltages are generated in the U-phase windings U1 to U4 by the interlinkage magnetic fluxes φx and φy. Since the interlinkage magnetic fluxes φx and φy are in opposite phases as described above, an induced voltage generated in the U-phase windings U2 and U4 by the interlinkage magnetic flux φy and generated in the U-phase windings U1 and U3 by the interlinkage magnetic flux φx. The induced voltage has opposite polarity (reverse phase). For this reason, the combined induced voltage obtained by combining the induced voltages of the U-phase windings U1 to U4 is effectively reduced.

It should be noted that the above action also occurs when the S-pole magnet magnetic pole Ms faces the U-phase windings U1 and U3, for example. That is, when the S magnetic pole Ms faces the U-phase windings U1 and U3, the inter-slit core portion 328 faces the U-phase windings U2 and U4, respectively. The voltage and the induced voltage generated in the U-phase windings U2 and U4 are in opposite phases, and the combined induced voltage of the U-phase windings U1 to U4 is effectively reduced.

In the above description, the combined induced voltage of the U-phase windings U1 to U4 has been described as an example. Similarly, in the V-phase windings V1 to V4 and the W-phase windings W1 to W4, the inter-slit core portion 328 is added to the rotor core 323. The composite induced voltage is reduced due to the provision of.

Next, when the rotor 321 is in the rotational position as shown in FIG. 39B during the high-speed rotation of the rotor 321 (during field weakening control), that is, the N-pole magnet magnetic pole Mn is the U-phase winding U1, U3. And the magnetic action when the N-pole core magnetic pole Cn is opposed to the U-phase windings U2 and U4 in the radial direction.

Even at this time, in the U-phase windings U1 and U3, the magnet magnetic flux (magnetic flux outward in the radial direction) generated by the opposing N-pole magnet magnetic pole Mn is weakened. Is generated in the U-phase windings U1 and U3 and passes outward in the radial direction.

On the other hand, the core magnetic pole Cn facing the U-phase windings U2 and U4 is a pseudo magnetic pole having no magnet, and has a lower magnetic force applied to the stator 11 than the magnet magnetic pole Mn. Thereby, the interlinkage magnetic flux φy of the U-phase windings U2 and U4 facing the core magnetic pole Cn is smaller than the interlinkage magnetic flux φx of the U-phase windings U1 and U3 facing the magnet magnetic pole Mn. The induced voltage generated in windings U2 and U4 is smaller than the induced voltage generated in U-phase windings U1 and U3. Therefore, the combined induced voltage obtained by synthesizing the induced voltages generated in the U-phase windings U1 to U4 is reduced by the decrease in the induced voltage in the U-phase windings U2 and U4. Thus, when the N-pole magnet magnetic pole Mn is opposed to the U-phase windings U1 and U3 in the radial direction, the portion of the rotor 321 radially opposed to the U-phase windings U2 and U4 is the N-pole core magnetic pole Cn. Even in this case, the combined induction voltage of the U-phase windings U1 to U4 is reduced.

In the above description, the decrease in the combined induction voltage when the U-phase windings U1 to U4 face the N pole of the rotor 321 has been described as an example. However, in the V-phase windings V1 to V4 and the W-phase windings W1 to W4, The same is true for the S pole of the rotor 321, and similarly, the combined induced voltage decreases due to the core portion 328 between the slits or the core magnetic pole Cs.

Further, in the winding mode in which the windings 13 are connected in series in each phase as in the present embodiment, the sum of the induced voltages generated in the respective windings 13 for each phase becomes the combined induced voltage. The induced voltage tends to increase. Therefore, by providing the inter-slit core portion 328 and the core magnetic poles Cn and Cs as described above in a configuration in which the winding 13 is in series in each phase, the effect of suppressing the combined induced voltage can be obtained more significantly. Therefore, it is more preferable to increase the rotation of the motor 310.

Further, the field-weakening current supplied to the winding 13 can be kept small by the action of the core portion 328 between the slits or the core magnetic poles Cn and Cs. Since the field weakening current can be reduced, the permanent magnet 322 is difficult to demagnetize during field weakening control, and the copper loss of the winding 13 can be suppressed. In other words, the amount of interlinkage magnetic flux that can be reduced with the same amount of field-weakening current increases, so that higher rotation by field-weakening control can be obtained more effectively.

Next, characteristic advantages of this embodiment will be described.
(13) The windings 13 of the stator 11 are composed of four U-phase windings U1 to U4, V-phase windings V1 to V4, and W-phase windings W1 to W4, respectively, corresponding to the supplied three-phase driving current. Thus, the four windings of each phase are connected in series. That is, the winding 13 of the stator 11 includes at least two windings (first winding and second winding) connected in series in each phase.

The rotor 321 includes a U-phase winding U2 at a rotational position of the rotor 321 where the magnet magnetic pole Mn, Ms having the permanent magnet 322 and the magnet magnetic pole Mn (or the magnet magnetic pole Ms) face the U-phase windings U1, U3, for example. , U4 and the non-magnetic magnetic pole portion 325 of the rotor core 323 facing each other. The non-magnet magnetic pole portion 325 of the rotor core 323 is weakened by the core magnetic poles Cn and Cs functioning as magnetic poles opposite to the magnetic poles Mn and Ms by the magnetic fluxes of the magnetic magnetic poles Mn and Ms and the windings 13 facing each other. It consists of an inter-slit core portion 328 (flux allowing portion) that allows generation of field magnetic flux (linkage flux φy).

According to this configuration, the core magnetic poles Cn and Cs are pseudo magnetic poles having no magnet, and the magnetic force applied to the stator 11 is weaker than the magnet magnetic poles Mn and Ms. Can be suppressed. Further, the inter-slit core portion 328 allows the generation of field-weakening magnetic flux (interlinkage magnetic flux φy) in the opposing winding 13, so that the interlinkage magnetic flux φy is generated in the winding 13 facing the inter-slit core portion 328. The induced voltage generated by the above is opposite in polarity to the induced voltage generated in the winding 13 facing the magnetic poles Mn and Ms. Thereby, the synthetic | combination induced voltage in the coil | winding 13 of each phase can be suppressed further smaller. Due to the actions of the core magnetic poles Cn and Cs of the non-magnet magnetic pole part 325 and the core part 328 between slits, the motor 310 can be rotated at a high speed.

Here, considering the configuration in which all the non-magnet magnetic pole portions 325 of the rotor core 323 are the core magnetic poles Cn and Cs (configuration in which each non-magnet magnetic pole portion 325 has only one slit portion), although the torque can be increased, the core magnetic pole The magnetic force of Cn and Cs weakens and prevents the generation of field magnetic flux, which is disadvantageous for achieving high rotation. Therefore, as in the present embodiment, by forming the inter-slit core portion 328 and the core magnetic poles Cn and Cs in the non-magnet magnetic pole portion 325, it is possible to achieve high rotation while suppressing a decrease in torque as much as possible.

In the present embodiment, the output characteristics (torque and rotation speed) of the motor 310 can be adjusted by changing the configuration of the pair of

slit portions

326a and 326b formed in each non-magnet magnetic pole portion 325. Become.

For example, the larger the angle formed by the pair of

slit portions

326a and 326b in each non-magnet magnetic pole portion 325, the larger the opening angle θa of the inter-slit core portion 328 and the smaller the opening angle θc of the core magnetic poles Cn and Cs. As a result, the field weakening magnetic flux generated in the winding 13 at the time of field weakening control increases, which is advantageous for achieving high rotation. On the other hand, the smaller the angle formed by the pair of

slit portions

326a and 326b in each non-magnet magnetic pole portion 325, the smaller the opening angle θa of the inter-slit core portion 328, and the larger the opening angle θc of the core magnetic poles Cn and Cs. This is an advantageous configuration for achieving high torque. Therefore, desired motor characteristics can be obtained by setting the angle between the

slit portions

326a and 326b.

(14) The inter-slit core portion 328 is provided between the N-pole core magnetic pole Cn and the S-pole core magnetic pole Cs in the circumferential direction of the rotor 321, and the N-pole and S-pole core magnetic poles Cn, Cs are respectively It is configured to be adjacent to the magnet poles Mn and Ms having different polarities at a portion opposite to the core portion 328 between the slits in the circumferential direction. According to this configuration, since the core magnetic poles Cn and Cs are respectively interposed between the core portion 328 between the slits and the magnet magnetic poles Mn and Ms in the circumferential direction, the core portion 328 between the slits is the magnetic flux of the magnet magnetic poles Mn and Ms. The configuration can be made less susceptible to influence. Accordingly, the inter-slit core portion 328 is more preferable because it allows generation of field-weakening magnetic flux (linkage magnetic flux φy).

(15) The opening angle θm of the magnet magnetic poles Mn and Ms facing the stator 11 (the outer peripheral surface of the magnet magnetic poles Mn and Ms) is such that the core magnetic poles Cn and Cs face the stator 11 (the core magnetic poles Cn and Cs). It is set larger than the opening angle θc of the outer peripheral surface. As a result, the magnetic force of the magnet magnetic poles Mn and Ms and the magnetic force of the core magnetic poles Cn and Cs that function as pseudo magnetic poles can be secured by the magnetic flux of the magnet magnetic poles Mn and Ms, and the reduction in torque can be more suitably suppressed. .

(16) The opening angle θa of the surface facing the stator 11 in the core portion 328 between slits (the outer peripheral surface of the core portion 328 between slits) is set larger than the opening angle θc of the outer peripheral surfaces of the core magnetic poles Cn and Cs. Thus, a configuration suitable for higher rotation can be obtained.

(17) Since the rotor core 323 includes slit

portions

326a and 326b as magnetoresistive portions between the core portions 328 between the slits adjacent to each other and the core magnetic poles Cn and Cs, the magnet magnetic pole Mn passing through the core magnetic poles Cn and Cs. It is possible to suppress the magnetic flux of Ms from flowing into the core portion 328 between slits.

Further, the magnetoresistive portion between the core portion 328 between the slits and the core magnetic poles Cn and Cs is the

slit portions

326 a and 326 b formed in the rotor core 323, so that the magnetoresistive portion can be easily configured in the rotor core 323. .

In addition, you may change the said embodiment as follows.
The configuration of the

slit portions

326a and 326b in each non-magnet magnetic pole portion 325 is not limited to the above embodiment, and a magnetic flux allowing portion and a core magnetic pole Cn that allow each non-magnet magnetic pole portion 325 to generate a field weakening magnetic flux. , Cs can be appropriately changed to other configurations.

For example, as shown in FIG. 40, the

slit portions

326a and 326b of the above embodiment may be connected to each other at the inner peripheral side end portion. According to such a structure, it can suppress more suitably that the magnetic flux of the magnet magnetic poles Mn and Ms which pass through the core magnetic poles Cn and Cs flows into the core part 328 between slits.

Further, for example, as shown in FIG. 41, a plurality of bridge portions 331 may be formed at the radial intermediate portions of the

slit portions

326a and 326b. Each bridge portion 331 is formed on the rotor core 323, and is configured to connect a pair of side surfaces facing each other in the circumferential direction in each of the

slit portions

326a and 326b. In the configuration of FIG. 41, the

slit portions

326a and 326b are opened outward in the radial direction. According to such a configuration, the output characteristics (torque and rotation speed) of the motor 310 and the rigidity of the rotor core 323 can be easily adjusted by changing the configuration (number, axial direction, and radial dimension) of the bridge portion 331. It becomes possible.

For example, as shown in FIG. 42, an auxiliary magnet 332 may be provided in each of the

slit portions

326a and 326b. In FIG. 42, the magnetization directions of the permanent magnets 322 and the auxiliary magnets 332 are indicated by solid arrows, and the tip end side of the arrow represents the N pole and the arrow base end side represents the S pole. Each auxiliary magnet 332 is a permanent magnet having a rectangular parallelepiped shape, and has a magnetization direction corresponding to the core magnetic poles Cn and Cs adjacent in the circumferential direction. That is, the auxiliary magnet 332 provided in the slit portion 326a is magnetized so that the surface near the core magnetic pole Cs adjacent in the circumferential direction becomes the S pole. Further, the auxiliary magnet 332 provided in the slit portion 326b is magnetized so that the surface near the core magnetic pole Cn adjacent in the circumferential direction becomes an N pole. According to such a configuration, the amount of magnetic flux of the core magnetic poles Cn and Cs can be increased by the auxiliary magnets 332 in the

respective slit portions

326a and 326b, and a decrease in torque can be more suitably suppressed.

In the configuration shown in FIG. 42, the bridge portion 331 formed in each of the

slit portions

326a and 326b is used for positioning the auxiliary magnet 332 in the radial direction. Further, the bridge portion 331 prevents the auxiliary magnet 332 from falling off from the

slit portions

326a and 326b to the outside in the radial direction. Further, in the configuration shown in FIG. 42, since the auxiliary magnet 332 is provided at a position closer to the inner peripheral side of each

slit portion

326a, 326b, the magnetic flux of the auxiliary magnet 332 is changed to the outer peripheral side of the inter-slit core portion 328 (that is, It is difficult to flow in the field path of the field weakening magnetic flux. For this reason, it is possible to suppress the weak field magnetic flux from flowing through the core portion 328 between the slits by the magnetic flux of the auxiliary magnet 332 (that is, hindering high rotation).

Further, in the above embodiment, the

slit portions

326a and 326b of the non-magnet magnetic pole portion 325 are formed along the radial direction of the rotor 321, but the present invention is not limited to this. For example, as shown in FIG. It is good also as an aspect which 326b does not follow the radial direction of the rotor 321. FIG.

In the configuration shown in FIG. 43, each slit

portion

326a, 326b is formed at a position on the outer peripheral side from the approximate center in the radial direction of the non-magnet magnetic pole portion 325, and the inner peripheral side end of each

slit portion

326a, 326b is a non-magnet. The magnetic pole portions 325 are configured to approach each other at a substantially central position in the radial direction. And the core part 333 between slits of the outer peripheral side rather than each slit

part

326a, 326b in the non-magnet magnetic pole part 325 functions as a magnetic flux permission part.

Further, in the configuration shown in FIG. 43, the auxiliary magnet 334 is embedded in a portion on the radially inner side of the inter-slit core portion 333 (each

slit portion

326a, 326b) in the non-magnet magnetic pole portion 325. The auxiliary magnet 334 is disposed on the circumferential center line L2 of the non-magnet magnetic pole portion 325. Further, the auxiliary magnet 334 has a rectangular shape that is long in the radial direction when viewed in the axial direction, and a portion near the core magnetic pole Cn in the circumferential direction (a portion closer to the magnet magnetic pole Ms than the slit portion 326b in the non-magnet magnetic pole portion 325) is N poles. The portion near the core magnetic pole Cs (the portion closer to the magnet magnetic pole Mn than the slit portion 326a in the non-magnetic magnetic pole portion 325) is magnetized so as to be the south pole (see the solid line arrow in FIG. 43).

According to such a configuration, the amount of magnetic flux of the core magnetic poles Cn and Cs can be increased by the auxiliary magnet 334, and a reduction in torque can be more suitably suppressed. Further, in this configuration, the auxiliary magnet 334 is provided on the radially inner side with respect to the

slit portions

326a and 326b. For this reason, it can suppress that the magnetic flux of the auxiliary magnet 334 penetrate | invades into the core part 333 between slits by each slit

part

326a, 326b, and it can suppress that the magnetic flux of the auxiliary magnet 332 prevents high rotation.

In the configuration shown in FIG. 43, when aiming at further torque improvement, for example, as shown in FIG. 44, an auxiliary magnet 332 may be provided in each of the

slit portions

326a and 326b. Even in such a configuration, in order to suppress interference with the magnetic path of the field weakening magnetic flux, the auxiliary magnet 332 is preferably provided at a position closer to the inner peripheral side of each of the

slit portions

326a and 326b.

In addition, it is preferable that the

auxiliary magnets

332 and 334 in each of the above-described configurations are composed of, for example, a neodymium magnet, a samarium cobalt (SmCo) magnet, an SmFeN-based magnet, a ferrite magnet, an alnico magnet, or the like. Further, the

auxiliary magnets

332 and 334 may have any configuration of a sintered magnet and a bonded magnet.

In the above embodiment, the

slit portions

326a and 326b penetrate the rotor core 323 in the axial direction. However, the

slit portions

326a and 326b are not limited to this, and the

slits

326a and 326b are holes that do not penetrate the rotor core 323 in the axial direction. The output characteristics (torque and rotation speed) of the motor 310 may be adjusted by changing the axial lengths of the

portions

326a and 326b.

In the rotor core 323 of the above embodiment, the

slit portions

326a and 326b are formed as the magnetoresistive portions between the core portions 328 between the slits adjacent to each other and the core magnetic poles Cn and Cs. However, the present invention is not particularly limited thereto. . For example, the magnetoresistive portion between the core portion 328 between the slits and the core magnetic poles Cn and Cs may be configured by partially demagnetizing the rotor core 323 by laser irradiation.

As shown in FIG. 45, the outer diameter D1 of the non-magnet magnetic pole portion 325 (that is, the outer diameter of each core magnetic pole Cn, Cs and the outer diameter of the core portion 328 between slits) is changed to the outer diameter of each magnet magnetic pole Mn, Ms. You may comprise larger than D2.

According to such a configuration, the air gap (gap) between the stator teeth 12a and the inner peripheral surface of the stator becomes smaller at the non-magnet magnetic pole portion 325 than at the magnetic poles Mn and Ms. That is, since the core part 328 between slits of the non-magnet magnetic pole part 325 and the core magnetic poles Cn, Cs are closer to the inner peripheral surface of the tooth 12a, the field weakening magnetic flux is weakened to the core part 328 between slits and the core magnetic poles Cn, Cs. Becomes easier to pass. Thereby, the synthetic induction voltage in each phase can be suppressed to a smaller value, which can contribute to further higher rotation.

In the rotor 321 of the above-described embodiment, the magnetic flux allowing portion (inter-slit core portion 328) configured in the non-magnet magnetic pole portion 325 is integrally formed with the rotor core 323. That is, the rotor core 323 is configured as an integral part including the magnetic flux allowance portion (core portion 328 between slits). However, the present invention is not limited thereto, and at least a part of the portion constituting the magnetic flux allowance portion may be configured separately. .

For example, in the configuration shown in FIG. 46, the rotor core 323 includes a core main body 351 having the same magnetic pole pair P and core magnetic poles Cn and Cs as in the above embodiment, and a separate core member 352 connected to the core main body 351. I have.

The core body 351 is formed in a substantially cylindrical shape from, for example, a cold rolled steel plate (SPCC) iron or the like, and a rotating shaft 324 is fixed to the center. In addition, the core body 351 has an accommodation recess 353 that is recessed in the non-magnetic pole portion 325 of the rotor core 323 so as to be recessed radially inward from the outer peripheral surface of the core body 351. Both end surfaces in the circumferential direction of the housing recess 353 have a planar shape along the radial direction, and connecting projections 354 projecting in the circumferential direction are formed in the housing recess 353 on the both end surfaces. Each connecting convex portion 354 has a tapered shape in which the width along the radial direction of the rotor 321 extends from the protruding tip (circumferential tip).

In the core body 351, an N-pole core magnetic pole Cn is formed between the housing recess 353 and the S-pole magnet magnetic pole Ms, and an S-pole is placed between the housing recess 353 and the N-pole magnet magnetic pole Mn. A core magnetic pole Cs is configured. In addition, a magnetoresistive hole 355 that penetrates the core body 351 in the axis L direction is formed in a radially inner portion of the housing recess 353 in the core body 351. By this magnetoresistive hole 355, the short circuit of the magnetic flux between the magnetic poles Mn and Ms constituted by sandwiching the non-magnetic magnetic pole portion 325 in the circumferential direction is suppressed.

In the housing recess 353 of the core body 351, a separate core member 352 having a fan shape centered on the axis L of the rotating shaft 324 is housed. The separate core member 352 is made of a material (for example, amorphous metal or permalloy) having a higher magnetic permeability than the core body 351 (for example, iron material). The outer peripheral surface of the separate core member 352 has an arc shape centered on the axis L when viewed from the direction of the axis L of the rotation shaft 324. The outer peripheral surface of the separate core member 352 and the outer peripheral surface of the core body 351 are , And are located on the same circle centered on the axis L.

Both end surfaces in the circumferential direction of the separate core member 352 have a planar shape along the radial direction, and are opposed to both end surfaces in the circumferential direction of the housing recess 353, respectively. That is, the separate core member 352 is disposed between the N-pole core magnetic pole Cn and the S-pole core magnetic pole Cs in the circumferential direction. And the connection recessed part 361 by which the connection convex part 354 of the core main body 351 is fitted is formed in the circumferential direction both end surface of the separate core member 352, respectively. The separate core member 352 is fixed in the housing recess 353 by fitting the connection protrusions 354 to the connection recesses 361.

In the fixed state of the separate core member 352, between the circumferential direction both end faces of the separate core member 352 and the circumferential end faces of the receiving recess 353, and the radial inner side surface of the separate core member 352 and the diameter of the receiving recess 353 A gap K3 is provided between the inner side surface in the direction. In addition, a gap K4 is provided between the connection concave portions 361 and the connection convex portions 354 fitted in the connection concave portions 361 in the circumferential direction. That is, the separate core member 352 is in contact with the core main body 351 (the connecting convex portion 354) only on the both radial sides of the connecting concave portion 361.

The separate core member 352 is configured to be line symmetric with respect to the circumferential center line L2 of the non-magnet magnetic pole portion 325. Further, the opening angle (occupation angle) around the axis L of the separate core member 352 is set in the same manner as the opening angle θa of the inter-slit core portion 328 of the above embodiment. In the configuration shown in FIG. 46, the inner diameter of the separate core member 352 is about half of the outer diameter of the rotor core 323 (the outer diameter of the core main body 351). You may set to more than half or less than half of the outer diameter of the rotor core 323.

According to such a configuration, the separate core member 352 functions as a magnetic flux allowing portion that allows generation of field-weakening magnetic flux, similar to the inter-slit core portion 328 of the above embodiment. Rotation can be achieved. In the same configuration, the separate core member 352 is configured separately from the core body 351 having the magnet magnetic poles Mn and Ms and the core magnetic poles Cn and Cs. For this reason, interference between the magnetic path of the field weakening magnetic flux (d-axis magnetic path) in the separate core member 352 and the magnetic paths of the magnetic poles Mn and Ms in the core body 351 can be suppressed. As a result, the field weakening magnetic flux can easily pass through the separate core member 352, thereby contributing to further higher rotation.

Further, in the same configuration, the separate core member 352 is made of a material having a higher magnetic permeability than the core main body 351, so that the weakening field magnetic flux can be more easily passed through the separate core member 352. As a result, it can contribute to further higher rotation. Further, in the component parts of the rotor core 323, at least the separate core member 352 is made of a material having high magnetic permeability, and the core body 351 is made of an inexpensive iron material or the like, so that an increase in manufacturing cost can be suppressed while increasing the rotation speed. Can be achieved.

Furthermore, since the core magnetic poles Cn and Cs are respectively interposed between the separate core member 352 and the magnet magnetic poles Mn and Ms in the circumferential direction, the separate core member 352 is more affected by the magnetic flux of the magnet magnetic poles Mn and Ms. It can be configured to be difficult to receive. Further, since the gaps K3 are provided between the separate core member 352 and the core magnetic poles Cn and Cs in the circumferential direction, interference of the magnetic poles Mn and Ms with respect to the field weakening magnetic flux passing through the separate core member 352 is prevented. It can be further suppressed.

In the configuration shown in FIG. 46, the separate core member 352 is connected by the connecting protrusion 354 integrally formed with the core body 351. However, the present invention is not limited to this, and for example, as shown in FIG. The core body 351 and the separate core member 352 may be connected via a connecting member 362 that is separate from the 351 and the separate core member 352.

The connecting member 362 is provided across the separate core member 352 and the core body 351 on both sides of the separate core member 352 in the circumferential direction, and both end portions in the circumferential direction of each connecting member 362 are separate core members 352. Are fitted in connecting

recesses

363 and 364 respectively formed on both end surfaces in the circumferential direction and on both end surfaces in the circumferential direction of the housing recess 353. The radial installation position of the connecting member 362 is set to the radial center position of the separate core member 352. In addition, each connecting member 362 has a tapered shape in which the radial width increases from the center in the circumferential direction to both ends in the circumferential direction. By this connecting member 362, the core main body 351 (accommodating recess 353) and the separate core member 352 are connected so as not to contact each other. The connecting member 362 is made of a material (for example, resin, stainless steel, brass, etc.) having a larger magnetic resistance than the core main body 351 and the separate core member 352.

According to such a configuration, the core main body 351 and the separate core member 352 can be configured to be connected only by the connecting member 362. The magnetic material of the magnetic poles Mn and Ms of the core main body 351 is separated through the connecting member 362 by using a material having a larger magnetic resistance than the core main body 351 and the separate core member 352 as the constituent material of the connecting member 362. The flow toward the member 352 can be suppressed. As a result, the interference of the magnetic poles Mn and Ms with respect to the field weakening magnetic flux passing through the separate core member 352 can be further suppressed. In the configuration shown in FIG. 47, the gap K3 is provided between the housing recess 353 of the core body 351 and the separate core member 352. However, the present invention is not limited to this. For example, a filler such as a resin is provided in the gap K3. And the filler may function as a connecting member that connects the core body 351 and the separate core member 352.

46 and 47, it is preferable that the separate core member 352 is mainly made of a material having an easy magnetization axis (a crystal orientation easy to be magnetized) in the circumferential direction. According to this, the field-weakening magnetic flux easily passes through the d-axis magnetic path in the separate core member 352, and as a result, it can contribute to further higher rotation.

46 and 47, a cylindrical cover member that covers the outer peripheral surface of the rotor 321 may be provided. According to this, it is possible to suppress the separate core member 352 from dropping from the core body 351 by the cover member.

In the above embodiment, the windings of each phase, that is, the U-phase windings U1 to U4, the V-phase windings V1 to V4, and the W-phase windings W1 to W4 are connected in series. However, the winding mode may be changed as appropriate. For example, when the U phase is taken as an example of modification, U phase windings U1 and U2 are connected in series, U phase windings U3 and U4 are connected in series, and a series pair of these U phase windings U1 and U2 is connected. And a series pair of U-phase windings U3 and U4 may be connected in parallel.

In the above embodiment, the rotor 321 has 8 poles and the number of windings 13 of the stator 11 is 12 (that is, the motor configuration has 8 poles and 12 slots). The number of can be appropriately changed according to the configuration.

In the above embodiment, for example, in the N pole of the rotor 321, the magnetic pole Mn and the core magnetic pole Cn are configured in the same number (each two), but it is not always necessary to have the same number. For example, the number of magnet magnetic poles Mn may be three (or one) and the number of core magnetic poles Cn may be one (or three). The same change may be made for the S pole (magnet magnetic pole Ms and core magnetic pole Cs) of the rotor.

In the above embodiment, the core magnetic pole Cn and the core magnetic pole Cs are provided in the N pole and the S pole of the rotor 321, respectively. However, the present invention is not particularly limited thereto. May be provided, and the other pole may be composed entirely of magnet magnetic poles.

In each of the magnetic poles Mn and Ms of the above-described embodiment, the pair of permanent magnets 322 embedded in the rotor core 323 are arranged in a substantially V shape that expands to the outer peripheral side when viewed in the axial direction. However, the configuration of the permanent magnets in the magnet magnetic poles Mn and Ms can be changed as appropriate. For example, it is good also as a structure which has one permanent magnet per one magnetic pole Mn and Ms.

Further, the rotor 321 of the above embodiment has an embedded magnet type structure (IPM structure) in which the permanent magnets 322 constituting the magnetic poles Mn and Ms are embedded in the rotor core 323, but the magnetic poles Mn and Ms are constituted. The permanent magnet may be a surface magnet type structure (SPM structure) in which the outer peripheral surface of the rotor core 323 is fixed.

In the above embodiment, the permanent magnet 322 is a sintered magnet, but other than this, for example, a bonded magnet may be used.
In the above embodiment, the rotor core 323 has a laminated structure of the core sheets. However, other than this, for example, a green compact core or an integrated block formed by forging (cold forging), cutting, or the like may be used.

In the above embodiment, the present invention is embodied in the inner rotor type motor 310 in which the rotor 321 is disposed on the inner peripheral side of the stator 11. However, the present invention is not particularly limited thereto, and the rotor is disposed on the outer peripheral side of the stator. The present invention may be embodied in an outer rotor type motor.

In the above embodiment, the present invention is embodied in the radial gap type motor 310 in which the stator 11 and the rotor 321 face each other in the radial direction. However, the present invention is not particularly limited thereto, and the stator and the rotor are in the axial direction. The present invention may be applied to an axial gap type motor that faces the motor.

-The above-mentioned embodiment and each modification may be combined suitably.

Claims

A stator having windings;
A rotor that rotates in response to a rotating magnetic field generated by supplying a driving current to the winding; and
The winding includes a first winding and a second winding, and the first winding and the second winding are excited at the same timing by the drive current and are connected in series. Connected,
The rotor is
A first magnetic pole portion;
The first magnetic pole portion is opposed to the second winding at the rotational position of the rotor facing the first winding, and the second magnetic pole portion has a magnetic force applied to the stator that is weaker than that of the first magnetic pole portion. Including motor.
The motor according to claim 1,
Each of the windings includes 2n U-phase windings, V-phase windings, and W-phase windings according to the supplied three-phase driving current.
n is an integer greater than or equal to 2,
A motor in which each of the first and second magnetic pole portions is n.
The motor according to claim 2,
The motor in which the first magnetic pole part and the second magnetic pole part are provided alternately at equal intervals in the circumferential direction.
The motor according to any one of claims 1 to 3,
The first and second magnetic pole portions each have a permanent magnet;
A motor in which an outer peripheral surface of the second magnetic pole part is positioned radially inward from an outer peripheral surface of the first magnetic pole part.
The motor according to any one of claims 1 to 4,
The first and second magnetic pole portions each have a permanent magnet;
A motor in which an opening angle around the rotor axis of the permanent magnet of the second magnetic pole portion is narrower than an opening angle around the rotor axis of the permanent magnet of the first magnetic pole portion.
The motor according to any one of claims 1 to 5,
The first and second magnetic pole portions each have a permanent magnet;
The motor in which the radial thickness of the permanent magnet of the second magnetic pole portion is thinner than the radial thickness of the permanent magnet of the first magnetic pole portion.
The motor according to any one of claims 1 to 6,
The first and second magnetic pole portions each have a permanent magnet;
A motor having a residual magnetic flux density of the permanent magnet of the second magnetic pole portion smaller than a residual magnetic flux density of the permanent magnet of the first magnetic pole portion.
The motor according to any one of claims 1 to 7,
The motor is configured to be capable of performing field-weakening control.
The motor according to claim 1,
The rotor is
A pair of rotor cores each having a plurality of claw-shaped magnetic poles in the circumferential direction and assembled in a manner in which the claw-shaped magnetic poles alternate in the circumferential direction;
A permanent magnet disposed between the pair of rotor cores in the axial direction and magnetized in the axial direction to cause the claw-shaped magnetic pole to function as a magnetic pole,
The rotor magnetic pole includes the first magnetic pole part and the second magnetic pole part.
The motor according to claim 9, wherein
Each of the windings includes 2n U-phase windings, V-phase windings, and W-phase windings according to the supplied three-phase driving current.
n is an integer greater than or equal to 2,
A motor in which each of the first and second magnetic pole portions is n.
The motor according to claim 10, wherein
The motor in which the first magnetic pole part and the second magnetic pole part are provided alternately at equal intervals in the circumferential direction.
The motor according to any one of claims 9 to 11,
Each of the first and second magnetic pole portions is composed of a single claw-shaped magnetic pole,
The claw-shaped magnetic poles forming the first magnetic pole part and the claw-shaped magnetic poles forming the second magnetic pole part have different shapes from each other.
The motor according to claim 12, wherein
The claw-shaped magnetic pole forming the second magnetic pole part has a narrower opening angle than the claw-shaped magnetic pole forming the first magnetic pole part.
The motor according to any one of claims 9 to 13,
The rotor includes a magnetic force adjusting magnet for making the magnetic force of the second magnetic pole part weaker than that of the first magnetic pole part.
The motor according to claim 14, wherein
Each of the first and second magnetic pole portions is composed of a single claw-shaped magnetic pole,
The magnetic force adjusting magnet includes a back magnet portion that is arranged on the back side of the claw-shaped magnetic pole that forms the first magnetic pole portion and is magnetized to suppress leakage magnetic flux flowing from the claw-shaped magnetic pole to the back side.
The motor according to claim 14 or 15,
Each of the first and second magnetic pole portions is composed of a single claw-shaped magnetic pole,
The magnet for adjusting magnetic force includes an inter-pole magnet portion that is arranged on the side in the circumferential direction of the claw-shaped magnetic pole that forms the first magnetic pole and is magnetized so as to suppress leakage magnetic flux flowing in the circumferential direction from the claw-shaped magnetic pole. motor.
The motor according to claim 14, wherein
The magnetic force adjusting magnet is provided on the outer peripheral surface of the claw-shaped magnetic pole, and a portion of the claw-shaped magnetic pole where the magnetic force adjusting magnet is not provided is one of the first magnetic pole part and the second magnetic pole part. Configure
The motor in which the magnet for adjusting magnetic force constitutes the other of the first magnetic pole part and the second magnetic pole part.
The motor according to any one of claims 9 to 17,
The motor is configured to be capable of performing field-weakening control.
The motor according to claim 1,
The first magnetic pole portion is a magnetic pole using a permanent magnet,
The motor in which the second magnetic pole portion is a core magnetic pole using a part of a rotor core.
The motor according to claim 19,
Each of the windings includes 2n U-phase windings, V-phase windings, and W-phase windings according to the supplied three-phase driving current.
n is an integer greater than or equal to 2,
A motor in which the number of each of the magnet magnetic pole and the core magnetic pole is n.
The motor according to claim 20, wherein
The motor in which the magnet magnetic pole and the core magnetic pole are alternately provided at equal intervals in the circumferential direction.
The motor according to any one of claims 19 to 21,
The core magnetic pole is a motor adjacent to the magnet pole of a different polarity using the permanent magnet in the circumferential direction.
The motor according to claim 22,
A motor in which a gap is provided between the core magnetic pole and the magnet pole having a different polarity.
The motor according to any one of claims 19 to 23,
Each of the N pole and S pole of the rotor includes the magnet magnetic pole and the core magnetic pole,
A motor in which the core magnetic pole of N pole and the core magnetic pole of S pole are adjacent to each other through a gap in the circumferential direction.
The motor according to any one of claims 19 to 24,
The motor in which the magnetic adjustment part for adjusting the magnetic flux which flows through the inside of the rotor core is provided in the rotor core.
The motor according to claim 25,
The magnetic adjustment unit is a motor including an auxiliary magnet embedded in the rotor core and causing a magnetic flux to flow through the core magnetic pole.
The motor according to claim 25 or 26,
The core magnetic pole is adjacent to the magnet pole of a different polarity using the permanent magnet in the circumferential direction,
The said magnetic adjustment part is a motor containing the magnetic flux guidance | guide part which guides the magnetic flux of the said magnetic pole toward the circumferential direction center of the said adjacent core magnetic pole.
The motor according to any one of claims 25 to 27,
Each of the N pole and S pole of the rotor includes the magnet magnetic pole and the core magnetic pole,
The N magnetic pole and the S magnetic pole are adjacent in the circumferential direction,
The S magnetic pole is provided on the opposite side of the N magnetic pole to the S magnetic pole,
On the opposite side of the S magnetic pole from the N magnetic pole, the N magnetic core is provided.
The said magnetic adjustment part is a motor comprised so that the short circuit of the magnetic flux between the magnet pole of the N pole adjacent to the circumferential direction and the magnet pole of the S pole may be suppressed.
The motor according to any one of claims 19 to 28,
The magnet magnetic pole includes the rotor core and the permanent magnet fixed to the outer peripheral surface of the rotor core.
The motor according to any one of claims 19 to 28,
The magnet magnetic pole includes the rotor core and the permanent magnet embedded in the rotor core.
The motor according to claim 28,
The magnet magnetic pole includes the rotor core and the permanent magnet embedded in the rotor core,
Each of the magnetic poles of N and S poles includes a pair of permanent magnets,
The pair of permanent magnets are substantially V-shaped motors extending outward in the radial direction when viewed in the axial direction.
The motor according to claim 31, wherein
The said magnetic adjustment part is a motor provided in the radial inside rather than the said permanent magnet in each of the said magnetic pole of N pole and S pole.
The motor according to claim 31 or 32,
The rotor core has a plurality of magnet accommodation holes for accommodating the permanent magnets, respectively.
A motor in which a gap is provided between a radial end of the magnet housing hole and the permanent magnet housed in the magnet housing hole.
The motor according to any one of claims 19 to 33,
The motor is configured to be capable of performing field-weakening control.
The motor according to claim 19,
The rotor is
The magnetic core further comprises a magnetic flux allowing portion that is part of the rotor core and that faces the second winding at a rotational position of the rotor where the magnet magnetic pole faces the first winding,
The magnetic flux allowing portion is a motor configured to allow the generation of the interlinkage magnetic flux by the field weakening current in the second winding.
36. The motor of claim 35.
Each of the N pole and S pole of the rotor includes the magnet magnetic pole and the core magnetic pole,
The magnetic flux allowing portion is provided between the core magnetic pole of N pole and the core magnetic pole of S pole in the circumferential direction of the rotor,
The N and S core magnetic poles are respectively adjacent to the magnet poles having different polarities on the side opposite to the circumferential magnetic flux allowing portion.
The motor of claim 36.
A motor in which an opening angle of the magnet magnetic pole facing the stator is larger than an opening angle of the core magnetic pole facing the stator.
The motor according to claim 36 or 37,
The motor in which the opening angle of the surface facing the stator in the magnetic flux allowing portion is larger than the opening angle of the surface facing the stator in the core magnetic pole.
The motor according to any one of claims 36 to 38,
The rotor core further includes a magnetoresistive portion positioned between the magnetic flux allowing portion and the core magnetic pole adjacent to each other.
40. The motor of claim 39, wherein
The motor in which the magnetoresistive portion is a slit portion provided in the rotor core.
The motor according to claim 40,
A motor in which an auxiliary magnet is provided in the slit portion.
The motor according to any one of claims 36 to 41,
The rotor further includes an auxiliary magnet for flowing a magnetic flux to the core magnetic pole,
The auxiliary magnet is a motor embedded in a portion radially inward of the magnetic flux allowing portion in the rotor core.
The motor according to any one of claims 35 to 42,
The rotor core is
A core body having the magnet magnetic pole and the core magnetic pole;
A separate core member connected to the core body and constituting at least a part of the magnetic flux allowing portion; and
Including motor.
45. The motor of claim 43.
The separate core member is a motor made of a material having a higher magnetic permeability than the core body.
The motor according to claim 43 or 44,
Each of the N pole and S pole of the rotor includes the magnet magnetic pole and the core magnetic pole,
The separate core member constituting the magnetic flux allowing portion is provided between the core magnetic pole of N pole and the core magnetic pole of S pole in the circumferential direction of the rotor,
The north and south poles of the core magnetic poles are adjacent to the magnet poles of different polarities on the side opposite to the separate core member in the circumferential direction,
A motor in which a gap is provided between the separate core member in the circumferential direction and the core poles of N and S poles.
The motor according to any one of claims 43 to 45,
The core body and the separate core member are connected to each other via a connecting member,
The connecting member is a motor made of a material having a larger magnetic resistance than the core body and the separate core member.