WO2016066016A1 - 一种超宽带小型化交叉圆极化天线 - Google Patents

一种超宽带小型化交叉圆极化天线 Download PDF

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Publication number
WO2016066016A1
WO2016066016A1 PCT/CN2015/091941 CN2015091941W WO2016066016A1 WO 2016066016 A1 WO2016066016 A1 WO 2016066016A1 CN 2015091941 W CN2015091941 W CN 2015091941W WO 2016066016 A1 WO2016066016 A1 WO 2016066016A1
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Prior art keywords
substrate
cross
polarized antenna
transmission line
excitation slit
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PCT/CN2015/091941
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English (en)
French (fr)
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庄昆杰
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庄昆杰
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Application filed by 庄昆杰 filed Critical 庄昆杰
Priority to KR1020167031170A priority Critical patent/KR20170004991A/ko
Priority to JP2016575342A priority patent/JP6247407B2/ja
Priority to US15/316,061 priority patent/US10186777B2/en
Publication of WO2016066016A1 publication Critical patent/WO2016066016A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/0428—Substantially flat resonant element parallel to ground plane, e.g. patch antenna radiating a circular polarised wave
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H01Q1/38—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith formed by a conductive layer on an insulating support
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
    • H01Q15/14—Reflecting surfaces; Equivalent structures
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
    • H01Q9/04—Resonant antennas
    • H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
    • H01Q9/045—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means
    • H01Q9/0457—Substantially flat resonant element parallel to ground plane, e.g. patch antenna with particular feeding means electromagnetically coupled to the feed line

Definitions

  • the present invention relates to the field of antenna technologies in the field of mobile communications, and in particular to an ultra-wideband miniaturized cross-circularly polarized antenna.
  • radiocommunications are divided into more than 50 different services such as aeronautical communications, marine communications, terrestrial communications, satellite communications, broadcasting, television, radio navigation, positioning and telemetry, remote control, space exploration, etc.
  • Each service has a certain frequency band.
  • GSM 900 uses 890-960MHz
  • GSM1800 uses 1710-1550MHz
  • CDMA uses 825-880MHz
  • 3G's main working frequency band is 1880-2025MHz, which was previously approved by the Ministry of Industry and Information Technology.
  • the 4G band is the 2575-2635MHz contour band.
  • the current 2G, 3G, and 4G communication networks coexist. Whether it is a base station or an indoor distribution system, each communication system has its own antenna.
  • the bandwidth of the existing antenna is narrow, and it is necessary to adopt more bandwidth when meeting the bandwidth of 2G, 3G, and 4G antennas.
  • An antenna with different bandwidths has a high cost of establishing a station.
  • Linearly polarized antennas receive linearly polarized antennas with multipath fading, which can cause serious fading of wireless signals at a certain moment.
  • both the base station and the terminal antennas use polarization diversity reception, that is, dual channel dual Polarized antenna.
  • the present invention is to overcome the disadvantages of narrow bandwidth of dual-polarized antennas in the prior art. According to an aspect of the present invention, an ultra-wideband miniaturized cross-circularly polarized antenna is proposed.
  • An ultra-wideband miniaturized cross-circularly polarized antenna provided by an embodiment of the present invention includes: a plurality of radiating fins, a substrate, a reflecting plate, and a power splitter with a phase shift of 90 degrees;
  • the front surface of the substrate is opposite to the radiation sheet, and the front surface of the substrate is provided with an excitation slit;
  • the back surface of the substrate is opposite to the reflection plate, and the back surface of the substrate is provided with a first power divider and two first transmission lines and a second power a splitter and two second transmission lines;
  • the first transmission line and the second transmission line are transmission lines of two polarization orthogonal cross-line polarization antennas;
  • the two first transmission lines and the two output ends of the first power divider respectively Connected, two second transmission lines are respectively connected to two output ends of the second power splitter;
  • the input ends of the first power splitter and the second power splitter are respectively connected to two input ends of a power splitter with a phase shift of 90 degrees;
  • the two first transmission lines and the two second transmission lines respectively intersect the excitation slit orthogonally and are connected to the metal surface of the front surface of the substrate, and the four orthogonal points of the transmission line orthogonally intersecting the excitation slit are symmetrically distributed;
  • the plurality of radiating sheets are circular radiating sheets arranged in parallel with each other, and the farther the radiating sheet is from the substrate, the smaller the diameter of the radiating sheet.
  • the excitation slit is a symmetrical gradient shape, including: a positive cross-shaped gradient shape, a diamond-shaped cross-gradient shape, and a mes-shaped gradient shape;
  • the width of the excitation slit is the narrowest at the short-circuit feed point. The closer to the center of the excitation slit, the wider the width of the excitation slit.
  • the short-circuit feed point is the orthogonal point where the transmission line and the excitation slit intersect orthogonally.
  • a circular metal surface which is capacitively coupled to the excitation slit is further provided at a central position of the cross slit, and the circular metal surface is surrounded by the cross gap.
  • the back surface of the substrate is provided with a cross gap having the same shape as the excitation slit at a mapping position of the excitation slit on the front surface of the substrate, and the cross gap is connected to each transmission line branch;
  • a circular metal surface is formed at a central position of the cross slit to form a capacitive coupling with the excitation slit, and the circumference of the circular metal surface is surrounded by the cross gap.
  • the substrate is provided with a plurality of via holes, and the via holes are distributed along the edge of the transmission line and/or the edge of the excitation slit; the metal surface of the front surface of the substrate is connected to the metal surface of the back surface of the substrate through the via hole.
  • the ultra-wideband miniaturized cross-circularly polarized antenna provided by the embodiment of the present invention achieves the effect of expanding the frequency band by setting the multi-layer radiating strips of different sizes and corresponding to different frequency bands; the polarization difference is transmitted by the first transmission line and the second transmission line respectively
  • the 90-degree two-way transmission signal divides each signal into two tributary signals by an aliquoting two-power splitter.
  • the four transmission line branches simultaneously excite the cross-star excitation gap to form four feedings, and the generated electromagnetic waves are excited.
  • the output cross-polarization wave forms a cross-circular polarized wave in space, and the antenna distance is obtained by the spatial distance and polarization loss.
  • the cross-circularly polarized antenna replaces the cross-line polarized antenna, which not only has better receiving capability than the linearly polarized antenna, but also has anti-interference, anti-fading and more stability. At the same time, the antenna is changed from two joints to one joint, which improves the channel utilization. Reduced size and cost.
  • FIG. 1 is a structural diagram of an ultra-wideband miniaturized cross-circularly polarized antenna according to an embodiment of the present invention
  • FIG. 2 is a structural view of a back surface of a substrate in an embodiment of the present invention.
  • FIG. 3 is a structural view of a front surface of a substrate according to an embodiment of the present invention.
  • FIG. 4 is a perspective structural view of an ultra-wideband miniaturized cross-circularly polarized antenna according to an embodiment of the present invention
  • Figure 5 is a detailed structural view of a substrate short-circuit feed point in the embodiment of the present invention.
  • FIG. 1 is a structural diagram of an ultra-wideband miniaturized cross-circularly polarized antenna according to an embodiment of the present invention
  • FIG. 4 is a perspective structural view of the crossed circularly polarized antenna.
  • the ultra-wideband miniaturized cross-circularly polarized antenna is sequentially provided with a plurality of radiating sheets 20, a substrate 10, and a reflecting plate 30.
  • the radiation sheet 20 can be fixed on the substrate 10 by the radiation sheet holder. It can be understood by those skilled in the art that the radiation sheet 20 can also be used in other manners. Fixed, using a radiation sheet holder is only one specific implementation.
  • the front surface of the substrate 10 is opposite to the radiation sheet 20, and the front surface of the substrate 10 is provided with an excitation slit 101; the back surface of the substrate 10 is opposite to the reflection plate 30, and the back surface of the substrate 10 is provided with a first power divider 110.
  • the first transmission line 111 is respectively connected to the two output ends of the first power splitter 110, and the two second transmission lines 121 are respectively connected to the two output ends of the second power splitter 120.
  • the first power splitter 110 and the second power splitter 120 are equally divided into two power splitters.
  • the two first transmission lines 111 and the two second transmission lines 121 respectively intersect the excitation slit 101 orthogonally and are connected to the metal surface of the front surface of the substrate 10, and the four orthogonal points of the transmission line orthogonally intersect the excitation slit 101 are symmetrically distributed.
  • the plurality of radiating sheets 20 are circular radiating sheets disposed in parallel with each other, and the farther the radiating sheet is from the substrate, the smaller the diameter of the radiating sheet, as shown in FIG.
  • the ultra-wideband miniaturized cross-circularly polarized antenna further includes a power splitter 150 that is phase shifted by 90 degrees.
  • a phase shifted 90 degree isoelectric divider 150 can be placed on the back side of the substrate.
  • the input ends of the first power splitter 110 and the second power splitter 120 are respectively connected to two input ends of the power splitter 150 that are phase-shifted by 90 degrees.
  • the output end of the phase shift 90-degree power divider is the transmitting end or the receiving end of the cross-circularly polarized antenna, and the cross-circularly polarized antenna signal can be outputted outward.
  • the excitation slit 101 is a symmetrical gradient shape, including but not limited to: a positive cross-shaped gradient shape, a diamond-shaped cross-gradient shape, and an I-shaped gradient shape.
  • the width of the excitation slit is the narrowest at the short-circuit feeding point, and the width of the excitation slit is wider as the center of the excitation slit is closer, and the short-circuit feeding point is the intersection of the transmission line and the excitation slit orthogonally. Intersection. See Figure 5 for a detailed block diagram of the short-circuit feed point.
  • the back surface of the substrate is provided with a cross slit 102 having the same shape as that of the excitation slit 101 at the mapping position of the excitation slit 101 on the front surface of the substrate, and the cross slit 102 communicates with each transmission line branch.
  • a circular metal surface 130 that is capacitively coupled with the excitation slit is further disposed at a central position of the cross slit, and the circumference of the circular metal surface 130 is surrounded by the cross gap.
  • the circular metal surface 130 does not communicate with the back metal surface of the substrate 10.
  • the circular metal surface 130 can reduce the length of the excitation slit 102, which is advantageous for miniaturization of the antenna.
  • the substrate 10 is provided with a plurality of via holes 140, and the via holes 140 are distributed along the edge of the transmission line and/or the edge of the excitation slit.
  • the distribution shape of the via holes is shown in FIGS. 2 and 3.
  • the metal surface on the front side of the substrate is connected to the metal surface on the back side of the substrate through via holes.
  • the substrate there are more than one number of vias.
  • the front surface of the substrate as shown in FIG. 3, except for the excitation slit 101, other areas on the front side of the substrate are covered with copper over a large area, and the copper-clad area on the front side of the substrate is the metal surface on the front side of the substrate.
  • the metal is also the metal ground plane.
  • the power splitter including the first power splitter 110 and the second power splitter 120
  • the transmission line including the first transmission line 111 and the second transmission line 121
  • the other areas on the back side of the substrate are covered with copper over a large area, and the copper-clad area on the back side of the substrate is the metal surface on the back side of the substrate.
  • the metal surface on the front side of the substrate is connected to the metal surface on the back surface of the substrate through the via holes, so that the two surfaces become a common ground, thereby reducing the interference of the plane wave generated by the transmission line in the electromagnetic field and making the antenna performance more stable.
  • the two first transmission lines 111 and the two second transmission lines 121 are connected to the metal surface of the front surface of the substrate 10 through the via holes 140, that is, the end (output end) of the transmission line is grounded, that is, short-circuited, and the transmission line and the excitation slot 102 are reduced. Coupling between the four feed points.
  • Embodiments of the present invention provide an ultra-wideband miniaturized cross-circularly polarized antenna.
  • the output cross-line polarized wave forms a cross-circular polarized wave in space.
  • the near-field cross-circularly polarized wave emitted by the cross-polarized antenna passes through the spatial distance and the loss of polarization, so that the antenna obtains the corresponding antenna port isolation.
  • circularly polarized antennas Compared with linearly polarized antennas, circularly polarized antennas have the following advantages:
  • the circularly polarized antenna can receive any linearly polarized incoming wave, and the circularly polarized antenna radiated wave can be received by any linearly polarized antenna.
  • the circularly polarized antenna can suppress rain and fog interference and multipath reflection when applied to mobile communication.
  • the circularly polarized antenna is more advantageous in anti-fading, anti-interference and multi-path resistance than the linearly polarized antenna.
  • the cross-circularly polarized antenna When the cross-circularly polarized antenna receives the signal of the linearly polarized antenna, the cross-circular polarization can be decomposed into two orthogonal linear polarizations, that is, the direction is vertical, and the phase difference is 90 degrees. Therefore, it has the same effect as the dual-polarized dual-channel antenna. Moreover, the transmit power of the dual-polarized antenna is sent to the antenna in two ways. So, there will be 3dB loss in the downlink. The single-channel cross-polarized antenna receives a line-polarized antenna that also loses 3 dB of power, but saves one channel. Therefore, the cross-polarized antenna can completely replace the dual-polarized antenna.
  • Existing covered antennas generally use dual-polarized antennas. When dual-polarized antennas receive dual-polarized antennas, although polarization diversity is also used to reduce multipath fading, there is always no circularly polarized antenna in anti-interference and anti-destruction. Have an advantage
  • the cross-polarized antenna is replaced by a cross-polarized antenna. Since the base station and the terminal are cross-line polarized antennas, when two orthogonal linear-polarized antennas receive a crossed circularly polarized wave, the polarization matching factor is 1, that is, the most ideal polarization matching state is reached, and the received signal power is independent of the position of the transmitting and receiving antenna, and does not depend on the direction of the antenna, that is, when the circularly polarized antenna is always subjected to linear polarization after being interfered by the obstacle,
  • the antenna has good transceiving capability, and the energy of the circularly polarized waves received by the two crossed-line polarized antennas at the receiving end is always equal.
  • a cross-circularly polarized antenna receives a cross-line polarized wave.
  • the cross-circularly polarized antenna replaces the cross-line polarized antenna, which not only has better receiving capability than the linearly polarized antenna, but also has anti-interference, anti-fading and more stability.
  • the antenna is changed from two joints to one joint, which improves the channel utilization. Reduced size and cost.
  • two transmission signals with polarizations of 90 degrees are respectively transmitted by the first transmission line and the second transmission line, and each signal is divided into two by an equal-divide two-power splitter.
  • the road branch signal, the four transmission line branches simultaneously excite the cross star excitation gap to form four feedings, and the generated electromagnetic wave excites the multilayer radiation sheet to form a plurality of standing wave electromagnetic fields of different frequencies in the multilayer thin layer space.
  • the radiation sheets are secondarily excited by the reflection plate, so that the electromagnetic waves form multiple resonances in different frequency bands corresponding to the multilayer radiation sheets of different sizes, thereby achieving the effect of expanding the frequency band.
  • the output cross-polarization wave forms a cross-circular polarized wave in space, and the antenna distance is obtained by the spatial distance and polarization loss.
  • the cross-circularly polarized antenna replaces the cross-line polarized antenna, which not only has better receiving capability than the linearly polarized antenna, but also has anti-interference, anti-fading and more stability.
  • the antenna is changed from two joints to one joint, which improves the channel utilization. Reduced size and cost.
  • the present invention can be embodied in a variety of different forms, and the technical solutions of the present invention are exemplified in the following with reference to FIG. 1 to FIG. 5, which does not mean that the specific examples applied to the present invention can be limited to In a particular process or embodiment structure, one of ordinary skill in the art should It is to be understood that the specific embodiments provided above are only a few examples of various preferred uses, and any embodiments embodying the claims of the present invention are intended to be within the scope of the invention.

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Abstract

本发明公开了一种超宽带小型化交叉圆极化天线，包括：依次设置的多个辐射片、基片、反射板和相移90度等功率分配器；基片的正面与辐射片相对，且基片的正面设有激励缝隙；基片的背面与反射板相对，且基片的背面设有第一功分器及两路第一传输线、第二功分器及两路第二传输线；第一功分器和第二功分器的输入端分别与相移90度等功率分配器的两个输入端相连；两路第一传输线和两路第二传输线分别与激励缝隙正交相交、并与基片正面的金属面相连。该超宽带小型化交叉圆极化天线通过设置的大小不同、对应不同频段的多层辐射片，达到扩展频带的效果；且通过相移90度等功率分配器实现交叉圆极化与线极化之间的转换。

Description

一种超宽带小型化交叉圆极化天线 技术领域
本发明涉及移动通信领域中的天线技术领域，具体地，涉及一种超宽带小型化交叉圆极化天线。
背景技术
按照国际无线电规则规定，现有的无线电通信共分成航空通信、航海通信、陆地通信、卫星通信、广播、电视、无线电导航，定位以及遥测、遥控、空间探索等50多种不同的业务，并对每种业务都规定了一定的频段。
在移动通信业务中，所有手机的通讯频段各不相同，GSM 900使用890-960MHz，GSM1800使用1710-1850MHz，CDMA使用825-880MHz，3G的主要工作频段则在1880-2025MHz，而此前工信部批准的4G频段是2575-2635MHz等高频段。
目前的2G、3G、4G通信网络共存，无论是基站还是室内分布系统，每个通信系统都有各自的天线，现有天线的带宽较窄，在满足2G、3G、4G天线带宽时需要采用多种不同带宽的天线，建站成本高。线极化天线接收线极化天线普遍存在着多径衰落，使得无线信号在某一时刻可能严重衰落，为了解决这个问题，现在的基站与终端天线都采用极化分集接收，即采用双通道双极化天线。
发明内容
本发明是为了克服现有技术中双极化天线带宽较窄缺陷，根据本发明的一个方面，提出一种超宽带小型化交叉圆极化天线。
本发明实施例提供的一种超宽带小型化交叉圆极化天线，包括：依次设置的多个辐射片、基片、反射板和相移90度等功率分配器；
基片的正面与辐射片相对，且基片的正面设有激励缝隙；基片的背面与反射板相对，且基片的背面设有第一功分器及两路第一传输线、第二功 分器及两路第二传输线；第一传输线和第二传输线分别为两路极化正交的交叉线极化天线的传输线；两路第一传输线分别与第一功分器的两个输出端相连，两路第二传输线分别与第二功分器的两个输出端相连；
第一功分器和第二功分器的输入端分别与相移90度等功率分配器的两个输入端相连；
两路第一传输线和两路第二传输线分别与激励缝隙正交相交、并与基片正面的金属面相连，且传输线与激励缝隙正交相交的四个正交点对称分布；
多个辐射片为互相平行设置的圆形辐射片，且辐射片距离基片越远，辐射片的直径越小。
在上述技术方案中，激励缝隙为对称的渐变形状，包括：正十字形渐变形状、菱形十字渐变形状、工字渐变形状；
在短路馈点处激励缝隙的宽度最窄，越靠近激励缝隙中央位置激励缝隙的宽度越宽，短路馈点为传输线与激励缝隙正交相交的正交点。
在上述技术方案中，在十字缝隙的中央位置还设有与激励缝隙形成电容耦合的圆形金属面，圆形金属面被十字缝隙包围。
在上述技术方案中，基片背面在基片正面的激励缝隙的映射位置设置有与激励缝隙形状相同的十字缝隙，十字缝隙与各传输线支路相连通；
在十字缝隙的中央位置设有与激励缝隙形成电容耦合的圆形金属面，圆形金属面的四周都被十字缝隙所包围。
在上述技术方案中，基片上设有多个过孔，且过孔沿传输线边沿和/或激励缝隙边沿分布；基片正面的金属面与基片背面的金属面通过过孔相连。
本发明实施例提供的超宽带小型化交叉圆极化天线，通过设置的大小不同、对应不同频段的多层辐射片，达到扩展频带的效果；由第一传输线和第二传输线分别传输极化相差90度的两路传输信号，由等分二功分器将每路信号分成两路支路信号，该四条传输线支路同时激励十字星形激励缝隙，形成四次馈电，产生的电磁波激励多层辐射片，在多层薄层空间内形成多个不同频率的驻波型电磁场，并通过反射板二次激励这些辐射片，使得电磁波在大小不同的多层辐射片对应的不同频段中形成了多次谐振， 从而达到扩展频带的效果。通过加入相移90度等功率分配器，使得输出的交叉线极化波在空间中形成交叉圆极化波，通过空间距离和极化的损耗，使得天线获得相应的天线端口隔离度。交叉圆极化天线取代交叉线极化天线，不仅接收能力比线极化天线好，而且抗干扰、抗衰弱、更稳定；同时使得天线从两个接头变为一个接头，提高了通道利用率，缩小了体积，节省了成本。
本发明的其它特征和优点将在随后的说明书中阐述，并且，部分地从说明书中变得显而易见，或者通过实施本发明而了解。本发明的目的和其他优点可通过在所写的说明书、权利要求书、以及附图中所特别指出的结构来实现和获得。
下面通过附图和实施例，对本发明的技术方案做进一步的详细描述。
附图说明
附图用来提供对本发明的进一步理解，并且构成说明书的一部分，与本发明的实施例一起用于解释本发明，并不构成对本发明的限制。在附图中：
图1为本发明实施例中超宽带小型化交叉圆极化天线的结构图；
图2为本发明实施例中基片背面的结构图；
图3为本发明实施例中基片正面的结构图；
图4为本发明实施例中超宽带小型化交叉圆极化天线的立体结构图；
图5为本发明实施例中基片短路馈点处的详细结构图。
具体实施方式
下面结合附图，对本发明的具体实施方式进行详细描述，但应当理解本发明的保护范围并不受具体实施方式的限制。
根据本发明实施例，提供了一种超宽带小型化交叉圆极化天线，图1为本发明实施例提供的超宽带小型化交叉圆极化天线的结构图，图2和图3分别为基片的背面结构图和正面结构图，图4为该交叉圆极化天线的立体结构图。具体的，该超宽带小型化交叉圆极化天线依次设置有多个辐射片20、基片10和反射板30。其中，辐射片20可以通过辐射片支架固定在基片10上，本领域技术人员可以理解，辐射片20也可以通过其他方式 固定，采用辐射片支架仅为其中一种具体实施方式。
其中，基片10的正面与辐射片20相对，且基片10的正面设有激励缝隙101；基片10的背面与反射板30相对，且基片10的背面设有第一功分器110及两路第一传输线111、第二功分器120及两路第二传输线121；第一传输线111和第二传输线121分别为两路极化正交的交叉线极化天线的传输线；两路第一传输线111分别与第一功分器110的两个输出端相连，两路第二传输线121分别与第二功分器120的两个输出端相连。具体的，第一功分器110和第二功分器120均为等分二功分器。
两路第一传输线111和两路第二传输线121分别与激励缝隙101正交相交、并与基片10正面的金属面相连，且传输线与激励缝隙101正交相交的四个正交点对称分布。多个辐射片20为互相平行设置的圆形辐射片，且辐射片距离基片越远，辐射片的直径越小，具体如图1所示。
该超宽带小型化交叉圆极化天线还包括：相移90度等功率分配器150。如图1所示，相移90度等功率分配器150可以设置在基片的背面。其中，第一功分器110和第二功分器120的输入端分别与相移90度等功率分配器150的两个输入端相连。相移90度等功率分配器的输出端即为该交叉圆极化天线的发射端或接收端，可以向外输出交叉圆极化天线信号。
优选的，激励缝隙101为对称的渐变形状，包括但不限于：正十字形渐变形状、菱形十字渐变形状、工字渐变形状。具体的，如图2和图3所示，在短路馈点处激励缝隙的宽度最窄，越靠近激励缝隙中央位置激励缝隙的宽度越宽，短路馈点为传输线与激励缝隙正交相交的正交点。短路馈点处的详细结构图参见图5所示。
在图2中，基片背面在基片正面的激励缝隙101的映射位置设置有与激励缝隙101形状相同的十字缝隙102，十字缝隙102与各传输线支路相连通。在本发明实施例提供的交叉圆极化天线中，在十字缝隙的中央位置还设有与激励缝隙形成电容耦合的圆形金属面130，圆形金属面130的四周都被十字缝隙所包围。该圆形金属面130与上述基片10的背面金属面并不连通。圆形金属面130可以减少激励缝隙102的长度，有利于实现天线的小型化。
优选的，基片10上设有多个过孔140，且过孔140沿传输线边沿和/或激励缝隙边沿分布，过孔的分布形状参见图2和图3所示。基片正面的金属面与基片背面的金属面通过过孔相连。
具体的，过孔的数量不止一个。在基片正面中，如图3所示，除激励缝隙101之外，基片正面的其他区域大面积覆铜，该基片正面的覆铜区域即为基片正面的金属面，该正面的金属正也为金属接地面。同理，在基片背面中，除十字缝隙102、功分器(包括第一功分器110和第二功分器120)、传输线(包括第一传输线111和第二传输线121)之外，基片背面的其他区域大面积覆铜，该基片背面的覆铜区域即为基片背面的金属面。
基片正面的金属面与基片背面的金属面通过过孔相连，使二者成为共地面，从而减少了传输线产生的平面波在电磁场中的干扰，使天线性能更稳定。两路第一传输线111和两路第二传输线121通过过孔140与基片10正面的金属面相连，即将传输线的末端(输出端)接地，即短路，减少了传输线与激励缝隙102相馈电的四个馈点间的耦合。
本发明实施例提供了一种超宽带小型化交叉圆极化天线，通过加入相移90度等功率分配器，使得输出的交叉线极化波在空间中形成交叉圆极化波。该交叉圆极化天线发射的近区场交叉圆极化波，通过空间距离和极化的损耗，使得天线获得相应的天线端口隔离度。
相对于线极化天线，圆极化天线有以下几个方面的优势：
(1)、圆极化天线可以接收任意线极化来波，且圆极化天线辐射波可以由任意线极化天线收到。
(2)、由于圆极化天线的极化正交性，即天线若辐射左旋圆极化波，则只接收左旋圆极化波而不接收右旋圆极化波。
(3)、圆极化波入射到对称目标(如平面、球面等)时旋向逆转，因此圆极化天线应用于移动通信时等能抑制雨雾干扰和抗多径反射。
所以圆极化天线相对于线极化天线在抗衰落、抗干扰以及抗多径效应上更有优势。
当交叉圆极化天线接收线极化天线的信号时，因为交叉圆极化可以分解为两个正交的线极化，即方向垂直，相位差90度。所以与双极化双通道天线一样的作用效果。而且双极化天线的发射功率要分两路送到天线 里，所以下行链路会有3dB损耗。而单通道交叉圆极化天线接收线极化天线也是损耗3dB功率，却节省了一个通道。所以交叉圆极化天线可以完全取代双极化天线。现有的覆盖天线普遍采用双极化天线，当双极化天线接收双极化天线时，虽然也同样有极化分集来减少多径衰落，但是始终没有圆极化天线在抗干扰、抗衰弱上有优势
同时，采用交叉圆极化天线取代交叉线极化天线，由于基站和终端是交叉线极化天线，两根正交的线极化天线接收一个交叉圆极化波时，其极化匹配因子为1，即达到最理想的极化匹配状态，且接收信号功率与收发天线位置无关，不取决于天线的方向，也就是说当圆极化天线在受到障碍物干扰后始终保持着对线极化天线良好的收发能力，接收端的两根交叉线极化天线接收到的圆极化波的能量始终是相等的。同样的，当交叉圆极化天线接收交叉线极化波时也是如此。交叉圆极化天线取代交叉线极化天线，不仅接收能力比线极化天线好，而且抗干扰、抗衰弱、更稳定；同时使得天线从两个接头变为一个接头，提高了通道利用率，缩小了体积，节省了成本。
本发明实施例提供的超宽带小型化交叉圆极化天线，由第一传输线和第二传输线分别传输极化相差90度的两路传输信号，由等分二功分器将每路信号分成两路支路信号，该四条传输线支路同时激励十字星形激励缝隙，形成四次馈电，产生的电磁波激励多层辐射片，在多层薄层空间内形成多个不同频率的驻波型电磁场，并通过反射板二次激励这些辐射片，使得电磁波在大小不同的多层辐射片对应的不同频段中形成了多次谐振，从而达到扩展频带的效果。通过加入相移90度等功率分配器，使得输出的交叉线极化波在空间中形成交叉圆极化波，通过空间距离和极化的损耗，使得天线获得相应的天线端口隔离度。交叉圆极化天线取代交叉线极化天线，不仅接收能力比线极化天线好，而且抗干扰、抗衰弱、更稳定；同时使得天线从两个接头变为一个接头，提高了通道利用率，缩小了体积，节省了成本。
本发明能有多种不同形式的具体实施方式，上面以图1-图5为例结合附图对本发明的技术方案作举例说明，这并不意味着本发明所应用的具体实例只能局限在特定的流程或实施例结构中，本领域的普通技术人员应当 了解，上文所提供的具体实施方案只是多种优选用法中的一些示例，任何体现本发明权利要求的实施方式均应在本发明技术方案所要求保护的范围之内。
最后应说明的是：以上所述仅为本发明的优选实施例而已，并不用于限制本发明，尽管参照前述实施例对本发明进行了详细的说明，对于本领域的技术人员来说，其依然可以对前述各实施例所记载的技术方案进行修改，或者对其中部分技术特征进行等同替换。凡在本发明的精神和原则之内，所作的任何修改、等同替换、改进等，均应包含在本发明的保护范围之内。

Claims (5)

  1. 一种超宽带小型化交叉圆极化天线，其特征在于，包括：依次设置的多个辐射片、基片、反射板和相移90度等功率分配器；
    所述基片的正面与所述辐射片相对，且所述基片的正面设有激励缝隙；所述基片的背面与所述反射板相对，且所述基片的背面设有第一功分器及两路第一传输线、第二功分器及两路第二传输线；所述第一传输线和所述第二传输线分别为两路极化正交的交叉线极化天线的传输线；两路所述第一传输线分别与所述第一功分器的两个输出端相连，两路所述第二传输线分别与所述第二功分器的两个输出端相连；
    所述第一功分器和所述第二功分器的输入端分别与所述相移90度等功率分配器的两个输入端相连；
    两路所述第一传输线和两路所述第二传输线分别与所述激励缝隙正交相交、并与所述基片正面的金属面相连，且传输线与所述激励缝隙正交相交的四个正交点对称分布；
    多个辐射片为互相平行设置的圆形辐射片，且辐射片距离所述基片越远，辐射片的直径越小。
  2. 根据权利要求1所述的交叉圆极化天线，其特征在于，所述激励缝隙为对称的渐变形状，包括：正十字形渐变形状、菱形十字渐变形状、工字渐变形状；
    在短路馈点处所述激励缝隙的宽度最窄，越靠近所述激励缝隙中央位置所述激励缝隙的宽度越宽，所述短路馈点为传输线与所述激励缝隙正交相交的正交点。
  3. 根据权利要求1所述的交叉圆极化天线，其特征在于，在十字缝隙的中央位置还设有与激励缝隙形成电容耦合的圆形金属面，所述圆形金属面被十字缝隙包围。
  4. 根据权利要求1所述的交叉圆极化天线，其特征在于，
    所述基片背面在所述基片正面的激励缝隙的映射位置设置有与所述激励缝隙形状相同的十字缝隙，所述十字缝隙与各传输线支路相连通；
    在所述十字缝隙的中央位置设有与所述激励缝隙形成电容耦合的圆形金属面，所述圆形金属面的四周都被所述十字缝隙所包围。
  5. 根据权利要求1-4任一所述的交叉圆极化天线，其特征在于，所述基片上设有多个过孔，且所述过孔沿传输线边沿和/或所述激励缝隙边沿分布；所述基片正面的金属面与所述基片背面的金属面通过所述过孔相连。
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CN204130695U (zh) * 2014-10-30 2015-01-28 庄昆杰 一种超宽带小型化轻薄型双极化阵列天线
CN104701603A (zh) * 2014-10-30 2015-06-10 庄昆杰 一种超宽带小型化轻薄型双极化阵列天线

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WO2018121256A1 (zh) * 2016-12-30 2018-07-05 深圳超级数据链技术有限公司 低剖面天线
CN114284711A (zh) * 2021-12-27 2022-04-05 湖北三江航天险峰电子信息有限公司 一种圆极化天线元
CN114284711B (zh) * 2021-12-27 2023-07-04 湖北三江航天险峰电子信息有限公司 一种圆极化天线元

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