WO2015018002A1 - 一种变换器 - Google Patents

一种变换器 Download PDF

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Publication number
WO2015018002A1
WO2015018002A1 PCT/CN2013/080986 CN2013080986W WO2015018002A1 WO 2015018002 A1 WO2015018002 A1 WO 2015018002A1 CN 2013080986 W CN2013080986 W CN 2013080986W WO 2015018002 A1 WO2015018002 A1 WO 2015018002A1
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WIPO (PCT)
Prior art keywords
energy storage
switching
storage device
switching device
output terminal
Prior art date
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Ceased
Application number
PCT/CN2013/080986
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English (en)
French (fr)
Inventor
张芳坡
梅晓东
孙维
王鹏
郑群
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Sungrow Power Supply Co Ltd
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Sungrow Power Supply Co Ltd
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Priority to PCT/CN2013/080986 priority Critical patent/WO2015018002A1/zh
Publication of WO2015018002A1 publication Critical patent/WO2015018002A1/zh
Anticipated expiration legal-status Critical
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H02M3/1586—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel switched with a phase shift, i.e. interleaved

Definitions

  • the present invention relates to the field of power electronics, and in particular, to a converter. Background technique
  • Common converter circuits such as Boost circuits, Buck circuits, Buck-Boost circuits, and three- or five-level circuits.
  • the frequency of the ripple current on the energy storage device is the same as the frequency of the switching transistor. If you want to increase the frequency of the ripple current on the energy storage device, you need to increase the switching frequency of the switching device.
  • the switching frequency of a common switching device such as an IGBT is usually at 20 kHz, and the switching device with a higher switching frequency is expensive and the switching frequency is increased.
  • the present invention provides a converter capable of increasing the frequency of ripple current on an energy storage device without increasing the frequency of the switching device.
  • the present invention provides a converter comprising: an energy storage device, a switching device group for charging the energy storage device, and a switching device group discharging the energy storage device;
  • one of the switching devices includes Two less switching devices are connected in parallel; another group of switching devices includes at least one switching device in parallel;
  • the converter is a Boost circuit, a Buck circuit, a Buck-Boost circuit, a three-level topology or a five-level topology.
  • the converter is a Boost circuit
  • One end of the energy storage device is connected to a power source, and the other end of the energy storage device is connected to the positive output terminal through a switch device group that discharges the energy storage device;
  • the other end of the energy storage device is also connected to the negative output terminal by a switch device group for charging the energy storage device;
  • a capacitor is connected between the positive output terminal and the negative output terminal.
  • the converter is a Buck circuit
  • One end of the energy storage device is connected to a power source through a switch device group for charging an energy storage device, and the other end of the energy storage device is connected to a positive output terminal;
  • One end of the energy storage device is also connected to the negative output terminal through a switch device group that discharges the energy storage device; a capacitance is connected between the positive output terminal and the negative output terminal.
  • the converter is a Buck-Boost converter
  • One end of the energy storage device is connected to a power source through a switching device for charging an energy storage device, and the other end of the energy storage device is connected to a negative output terminal;
  • One end of the energy storage device is also connected to the positive output terminal through a switch device group that discharges the energy storage device; a capacitance is connected between the positive output terminal and the negative output terminal.
  • the converter is a three-level topology
  • the switching device group for charging the energy storage device comprises two groups, which are a first charging switch device group and a second charging switch device group respectively;
  • the switching device group for discharging the energy storage device comprises two groups, respectively being the first a discharge switch device group and a second discharge switch device group;
  • the first discharge switch device group and the second discharge switch device group are connected in series with one end connected to the first node; the other end is connected to the second node;
  • the first node is half of a power supply voltage
  • One end of the first charging switch device group is connected to the positive end of the power source, and the other end is connected to the second node; one end of the second charging switch device group is connected to the second node, and the other end is connected to the negative of the power source.
  • One end of the energy storage device is connected to the second node, and the other end is connected to the positive output end; a capacitance is connected between the positive output end and the negative output end;
  • the first node is connected to a negative output.
  • the switching device group for charging and discharging the energy storage device includes a switching device
  • the switching device is a controllable switch tube or an uncontrollable switch tube
  • the switching device group for charging and discharging the energy storage device includes at least two switching devices
  • the switching device is a controllable switching transistor.
  • the present invention has the following advantages:
  • the switching device 2 is turned on by 1/N switching cycles longer than the switching device 1, and the switching device 3 is turned on by 1/N switching cycles than the switching device 2.
  • the frequency of the ripple current on the energy storage device is N times that of the N switching devices when the same switching element is turned on and off, and the amplitude of the ripple current is 1/N when the N switching devices are on and off.
  • the present invention has a relatively low selection requirement for a switching device, and it is also possible to reduce the cost without selecting a switching device capable of withstanding a high switching frequency.
  • Figure 1 is a schematic view of a first embodiment of a converter provided
  • FIG. 2 is a schematic diagram of a first embodiment of a Boost circuit provided by the present invention.
  • FIG. 3 is a turn-on timing diagram of the switching device of FIG. 2;
  • FIG. 4 is a schematic diagram of a second embodiment of a Boost circuit provided by the present invention.
  • FIG. 5 is a turn-on timing diagram of the switching device of Figure 4.
  • FIG. 6 is a schematic diagram of an embodiment of a converter provided by the present invention as a Buck circuit
  • FIG. 7 is a schematic diagram of an embodiment of a converter provided with a Buck-Boost circuit according to the present invention
  • FIG. 8 is a schematic diagram of a T-type three-level topology embodiment of the converter provided by the present invention.
  • FIG. 1 a schematic diagram of a first embodiment of a converter provided by the present invention is shown.
  • a converter provided in this embodiment includes: an energy storage device 100, a switching device group 200 for charging the energy storage device, and a switching device group 300 for discharging the energy storage device;
  • one of the switching devices includes at least two switching devices connected in parallel; the other group of switching devices includes at least one switching device connected in parallel; the said energy storage device 100 Alternating between the switching devices of the charged switching device group 200; The switching devices in the switching device group 300 that discharge the energy storage device 100 are alternately turned on.
  • a switching device group 200 for charging the energy storage device 100 includes N switching devices in parallel, and a switching device group 300 for discharging the energy storage device 100 includes a switching device.
  • the tube may also be a plurality of switching tubes (the plurality of switching tubes are externally embodied as one switching device); when each switching device includes a plurality of switching tubes, the plurality of switching tubes may be connected in parallel or in series, or of course The way of series and parallel mixing.
  • the switch tube is divided into a controllable switch tube and an uncontrollable switch tube, wherein the diode is an uncontrollable switch tube, and the IGBT and the MOS tube are controllable switch tubes. As long as the N switching devices are alternately turned on, they are not turned on at the same time.
  • the duty ratios of the N switching devices are the same, both are D, and the switching periods of 1/N intervals are turned on. That is, the switching device 2 is turned on by 1/N switching cycles than the switching device 1, and the switching device 3 is delayed by 1/N switching cycles than the switching device 2.
  • the frequency of the ripple current on the energy storage device is N times that of the N switching devices.
  • the converter provided by the embodiment of the present invention is connected in parallel by a plurality of switching devices, and controls the switching devices to be alternately turned on, thereby increasing the frequency of the ripple current on the energy storage device, but it is not necessary to increase the switching of the switching device. frequency. In this way, the selection requirements for the switching device are relatively low, and it is not necessary to select a switching device capable of withstanding a high switching frequency, which also reduces the cost.
  • the energy storage device in the embodiment of the present invention may be an energy storage inductor or a variable. Pressure cooker, etc.
  • the energy storage inductor can be a single inductor, or multiple inductors in parallel, or multiple inductors in series, and multiple inductors in series and parallel hybrids.
  • the implementation of the transformer and the inductor is similar, and will not be described here.
  • an energy storage device is used as an energy storage inductor as an example.
  • FIG. 2 the figure is a schematic diagram of a first embodiment of a Boost circuit provided by the present invention.
  • a diode is included in the switching device group for discharging the energy storage inductor as an example.
  • the switching device in the switching device group for discharging the energy storage inductor can also be a switching tube, such as a MOS tube, an IGBT tube, etc.
  • the Boost circuit can be used as a bidirectional Boost circuit. Can be used as an input.
  • C1 is connected in parallel at both ends of the power supply, and C1 acts as a DC input filter capacitor.
  • C2 acts as an output filter capacitor.
  • L is the energy storage inductor
  • D11 is the switching device for the storage inductor discharge, which can be a diode or a switch tube;
  • Q1 and Q2 are switching devices for charging energy storage inductors, and Q1 and Q2 are connected in parallel.
  • Both Q1 and Q2 use the same switching frequency, but alternately turn on to ensure that Q1 and Q2 are not turned on at the same time.
  • the duty ratio of Q1 is Dl
  • the duty ratio of Q2 is D2
  • Dl+D2 l-Ul/Uo is satisfied.
  • FIG. 3 is the turn-on timing diagram of the switching device. As can be seen from the timing diagram, Q1 and Q2 are not turned on at the same time in one cycle.
  • the ripple current frequency is twice that of the prior art when Q1 and Q2 are on the same level, and the ripple current amplitude is 1/2 of that in the prior art.
  • the figure is a schematic diagram of a second embodiment of a Boost circuit provided by the present invention.
  • the switching device group for charging the energy storage inductor L includes a plurality of switching devices connected in parallel.
  • the switching device group for discharging the energy storage inductor L includes only one switching device D1 l.
  • Q1-QN is N switching devices, and it is possible to use a MOS tube or a switching tube such as an IGBT. It is also possible to use a mechanical switch or the like, a combination of a plurality of switching devices, and the like, and a diode can also be used. These N switching devices can use the same switching frequency.
  • N switching devices can also adopt different switching frequencies.
  • a switching device with twice the frequency can be used instead of two switching devices to achieve the same effect.
  • the switching frequency of the two switching devices is 20K (the period is T1), and the switching frequency of the other switching device is 40K (the period is T2), then the two switching frequencies
  • the phase shift of a switching device with a rate of 20K relative to a switching device with a switching frequency of 40K is 1/2 T2 period and 3/2 T2 periods, respectively; thus, three switching devices with different switching frequencies can be utilized to achieve utilization of four
  • the same switching frequency (20K) switching device has the same control effect.
  • the sum of the duty cycles of the N switching devices in each switching cycle can be equal to the duty cycle required for the N switching devices in the prior art to be on and off.
  • the N switching devices are alternately turned on to ensure that no two switching devices are turned on at the same time, that is, there is no intersection of the on-times.
  • FIG. 5 the figure is a turn-on timing diagram of the switching device of FIG.
  • the ripple current frequency at L is N switching devices in the prior art. N times the same as when the same switch is turned off, the ripple current amplitude is 1/N when the N switching devices are on the same level.
  • the above embodiment is described by taking a converter as a Boost circuit as an example.
  • the following describes the Buck circuit, the Buck-Boost circuit, and the T-type three-level circuit.
  • the method provided by the present invention is equally applicable to several circuit topologies.
  • FIG. 6 the figure is a schematic diagram of an embodiment of a converter provided with a Buck circuit.
  • the converter is a Buck circuit
  • One end of the energy storage device L is connected to the power source U1 through a switching device group for charging the energy storage device, and the other end of the energy storage device L is connected to the positive output terminal; that is, the positive output terminal of Uo.
  • One end of the energy storage device L is also connected to the negative output terminal by a group of switching devices that discharge the energy storage device; that is, the negative output terminal of Uo.
  • a capacitor C 2 is connected between the positive output terminal and the negative output terminal.
  • C1 is the DC input filter capacitor of the power supply.
  • the L-switched switching device group includes N parallel switching devices, respectively
  • the switching device group for L discharge includes M parallel switching devices, which are Q2-1 up to Q2-M. Both M and N are integers and may or may not be equal.
  • FIG. 7 the figure is a schematic diagram of an embodiment of a converter provided as a Buck-Boost circuit.
  • the converter in this embodiment is a Buck-Boost converter;
  • One end of the energy storage device L is connected to the power source U1 through a switching device for charging the energy storage device, and the other end of the energy storage device L is connected to the negative output terminal; that is, the negative output terminal of Uo.
  • One end of the energy storage device is also coupled to the positive output through a set of switching devices that discharge the energy storage device; that is, the positive output of Uo.
  • a capacitor C 2 is connected between the positive output terminal and the negative output terminal.
  • C 2 is the output filter capacitor.
  • the switching device group for L discharge includes M parallel switching devices, which are Q2-1 up to Q2-M. Both M and N are integers and may or may not be equal.
  • FIG 8 is a schematic diagram of a three-level embodiment of the converter provided by the present invention.
  • the converter is a three-level topology
  • the switching device group for charging the energy storage device comprises two groups, which are a first charging switch device group and a second charging switch device group respectively; the switching device group for discharging the energy storage device comprises two groups, respectively being the first a discharge switch device group and a second discharge switch device group; As shown in FIG. 8, the first charging switch device group includes N parallel switching devices, respectively Q1-1 to Q1-N; and the second charging switching device group includes M parallel switching devices, respectively Q2-1; Q2-M; The first discharge switching device group includes X parallel switching devices, respectively Q3-1 to Q3-X; and the second discharging switching device group includes Y parallel switching devices, respectively Q4-1 until Q4- Y.
  • the first discharge switch device group and the second discharge switch device group are connected in series with one end connected to the first node A; the other end is connected to the second node B;
  • the first node A is half of the power supply voltage
  • One end of the first charging switch device group is connected to the positive end of the power source, and the other end is connected to the second node B;
  • One end of the second charging switch device group is connected to the second node B, and the other end is connected to the negative end of the power source;
  • One end of the energy storage device is connected to the second node B, and the other end is connected to the positive output terminal; a capacitance C3 is connected between the positive output terminal and the negative output terminal; C3 is an output filter capacitor.
  • capacitors C1 and C2 are equal, and C1 and C2 divide the power supply voltage by 1/2, that is, the voltage at point A is 1/2 of U1.
  • the first node A is connected to a negative output.
  • the switching device group for charging the energy storage device is stored. It can be used to meet the working requirements.
  • the two sets of switching devices ensure the normal operation of the Boost circuit.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

一种变换器，包括：储能器件（L）、为储能器件充电的开关器件组（Q1，Q2）和为储能器件放电的开关器件组（D11）。为储能器件充电和放电的开关器件组中，其中有一组开关器件包括至少并联的两个开关器件；另外一组开关器件组包括一个开关器件或至少两个开关器件并联。为储能器件充电或放电的开关器件组中的开关器件之间交替导通，从而可以提高储能器件上的纹波电流的频率，但是不必提高开关器件的开关频率。

Description

一种变换器
技术领域
本发明涉及一种电力电子技术领域， 尤其涉及一种变换器。 背景技术
目前， 在应用开关器件的电路中， 为了承受更大的功率， 经常采用两个或 者多个开关器件并联，且并联的所有开关器件的控制信号完全相同， 即开关器 件的导通时序是完全相同的。
常见的变换器电路， 例如 Boost电路、 Buck电路、 Buck-Boost电路， 以 及三电平或五电平电路。在这些变换器电路中，储能器件上的纹波电流的频率 与开关管的频率相同，如果想提高储能器件上的纹波电流的频率， 就需要提高 开关器件的开关频率。
但是， 普通的开关器件， 例如 IGBT的开关频率通常都在 20kHz作用， 更 高开关频率的开关器件的价格很贵并且开关频率提升的空间较小。
因此， 如何提供一种变换器可以在提高储能器件上的纹波电流频率的同 时， 不提高开关器件的频率， 是本领域技术人员需要解决的技术问题。
发明内容
本发明提供一种变换器， 能够提高储能器件上的纹波电流频率， 并且不提 高开关器件的频率。
本发明提供一种变换器， 包括： 储能器件、 为所述储能器件充电的开关器 件组和为所述储能器件放电的开关器件组；
为所述储能器件充电和放电的开关器件组中，其中有一组开关器件包括至 少两个开关器件并联； 另外一组开关器件组包括至少一个开关器件并联；
优选地， 所述变换器为 Boost电路、 Buck电路、 Buck-Boost电路、 三电 平拓朴或者五电平拓朴。
优选地， 所述变换器为 Boost电路；
所述储能器件的一端连接电源，所述储能器件的另一端通过为储能器件放 电的开关器件组连接正输出端；
所述储能器件的另一端还通过为储能器件充电的开关器件组连接负输出 端；
所述正输出端和负输出端之间连接电容。
优选地， 所述变换器为 Buck电路；
所述储能器件的一端通过为储能器件充电的开关器件组连接电源，所述储 能器件的另一端连接正输出端；
所述储能器件的一端还通过为储能器件放电的开关器件组连接负输出端； 所述正输出端和负输出端之间连接电容。
优选地， 所述变换器为 Buck-Boost变换器；
所述储能器件的一端通过为储能器件充电的开关器件连接电源，所述储能 器件的另一端连接负输出端；
所述储能器件的一端还通过为储能器件放电的开关器件组连接正输出端； 所述正输出端和负输出端之间连接电容。
优选地， 所述变换器为三电平拓朴； 所述为储能器件充电的开关器件组包括两组，分别为第一充电开关器件组 和第二充电开关器件组； 所述为储能器件放电的开关器件组包括两组， 分别为 第一放电开关器件组和第二放电开关器件组；
所述第一放电开关器件组和第二放电开关器件组串联后一端连接第一节 点； 另一端连接第二节点；
所述第一节点为电源电压的一半；
所述第一充电开关器件组的一端连接电源的正端，另一端连接所述第二节 点； 所述第二充电开关器件组的一端连接所述第二节点，另一端连接所述电源 的负端；
所述储能器件的一端连接所述第二节点， 另一端连接正输出端； 所述正输出端和负输出端之间连接电容；
所述第一节点连接负输出端。
优选地， 所述为储能器件充电和放电的开关器件组中包括一个开关器件 时， 该开关器件为可控开关管或者不可控开关管；
所述为储能器件充电和放电的开关器件组中包括至少两个开关器件时，该 开关器件为可控开关管。
与现有技术相比， 本发明具有以下优点：
如果 N个开关器件的占空比均相同， 均为 D, 且依次间隔 1/N的开关周 期导通。 即开关器件 2比开关器件 1延时 1/N个开关周期导通， 开关器件 3 比开关器件 2延时 1/N个开关周期导通等。这样储能器件上的纹波电流的频率 是 N个开关器件同开同关时的 N倍， 纹波电流的幅值为 N个开关器件同开同 关时的 1/N。 由此可见，本发明实施例提供的变换器，通过多个开关器件并联， 并且控制这些开关器件交替导通， 从而可以提高储能器件上的纹波电流的频 率， 但是不必提高开关器件的开关频率。 因此， 本发明对于开关器件的选型要 求比较低， 不用选取能够承受高开关频率的开关器件， 也可以降低成本。 附图说明
图 1是提供的变换器实施例一示意图；
图 2是本发明提供的变换器为 Boost电路实施例一示意图；
图 3是图 2中开关器件的导通时序图；
图 4是本发明提供的变换器为 Boost电路实施例二示意图；
图 5是图 4中开关器件的导通时序图；
图 6是本发明提供的变换器为 Buck电路的实施例示意图；
图 7是本发明提供的变换器为 Buck-Boost电路的实施例示意图； 图 8是本发明提供的变换器为 T型三电平拓朴实施例示意图。
具体实施方式
为使本发明的上述目的、 特征和优点能够更加明显易懂， 下面结合附图对 本发明的具体实施方式做详细的说明。
参见图 1 , 该图为本发明提供的变换器实施例一示意图。
本实施例提供的一种变换器， 包括： 储能器件 100、 为所述储能器件充电 的开关器件组 200和为所述储能器件放电的开关器件组 300;
为所述储能器件 100充电和放电的开关器件组中，其中有一组开关器件包 括至少两个开关器件并联； 另外一组开关器件包括至少一个开关器件并联； 所述为所述储能器件 100充电的开关器件组 200的开关器件之间交替导 通； 所述为所述储能器件 100放电的开关器件组 300中的开关器件之间交替导 通。
例如，为所述储能器件 100充电的开关器件组 200中包括 N个开关器件并 联， 为所述储能器件 100放电的开关器件组 300中包括一个开关器件。 管， 也可以为多个开关管（多个开关管对外体现为一个开关器件）； 当每个开 关器件包括多个开关管时， 多个开关管可以为并联， 也可以串联， 当然也可以 为串并联混合的方式。
需要说明的是， 开关管分为可控开关管和不可控开关管， 其中二极管为不 可控开关管， IGBT和 MOS管为可控开关管。 只要保证 N个开关器件交替导 通即可， 即不同时导通。
为了叙述方便， 假设 N个开关器件的占空比均相同， 均为 D, 且依次间隔 1/N的开关周期导通。 即开关器件 2比开关器件 1延时 1/N个开关周期导通， 开关器件 3比开关器件 2延时 1/N个开关周期导通等。
这样， 储能器件上的纹波电流的频率是 N个开关器件同开同关时的 N倍
(现有技术中是 N个并联的开关器件同开同关， 即导通时序完全相同） ， 储 能器件上纹波电流的幅值为 N个开关器件同开同关时的 1/N。 由此可见， 本发 明实施例提供的变换器，通过多个开关器件并联， 并且控制这些开关器件交替 导通，从而可以提高储能器件上的纹波电流的频率，但是不必提高开关器件的 开关频率。这样对于开关器件的选型要求比较低， 不用选取能够承受高开关频 率的开关器件， 这样也降低成本。
需要说明的是， 本发明实施例中的储能器件可以为储能电感， 也可以为变 压器等。 其中， 储能电感可以为单个电感， 也可以为多个电感并联， 或者多个 电感串联， 以及多个电感串联和并联混联等。 变压器与电感的实现方式类似， 在此不再赘述。
下面实施例中以储能器件为储能电感为例进行介绍。
首先介绍所述变换器为 Boost电路时的实现方式。
参见图 2, 该图为本发明提供的变换器为 Boost电路实施例一示意图。 介绍， 为储能电感放电的开关器件组中包括一个二极管为例进行介绍。
可以理解的是， 为储能电感放电的开关器件组中的开关器件也可以为开关 管， 例如 MOS管、 IGBT管等， 当开关器件为开关管时， Boost电路可以作为 双向 Boost电路， 左右均可以作为输入端。
如图 2所示， C1并联在电源的两端， C1作为直流输入滤波电容。
C2作为输出滤波电容。
L为储能电感； D11为储能电感放电的开关器件， 可以为二极管， 也可以 为开关管；
Q1和 Q2为储能电感充电的开关器件， Q1和 Q2并联。
Q1和 Q2均采用相同的开关频率， 但是交替导通， 保证 Q1和 Q2不同时 导通。
Q1的占空比为 Dl , Q2的占空比为 D2; 且满足 Dl+D2=l-Ul/Uo。
Ql、 Q2和 D11的导通时序可以参见图 3, 为开关器件的导通时序图。 从 时序图中可以看出， 一个周期内， Q1和 Q2不同时导通。
如果 Q1和 Q2的占空比相同， 即 D1=D2, 且 Q2比 Q1延时 1/2开关周期 时间导通， 那么此时 L上的纹波电流的频率为两个开关管（Q1和 Q2 )同开同 关时提高了 1倍， 同时 L上的纹波电流幅值降低 1倍。
如果 Q1和 Q2的占空比不相同， 但是同样满足 Dl+D2=l-Ul/Uo, 且 Q1 和 Q2交错导通， 则此时 L上的纹波电流幅值同样有所下降。
例如： 在电源为直流输入 U1=30V时， 如果要得到一个直流 Uo=60V的输 出电压， Q1和 Q2的开关频率为 16K, 如果采用现有技术中的 Q1和 Q2同开 同关， 其占空比为 D0=0.5 , 那么采用本发明的提供的方案， Q1和 Q2的占空 比分别为 D1=D2=0.25 , Q2比 Q1延时 1/2个开关周期导通， 则此时 L上的纹 波电流频率为现有技术中 Q1和 Q2同开同关时的 2倍， 纹波电流幅值为现有 技术时的 1/2。
下面结合附图介绍 Boost电路中为储能电感充电的开关器件组中包括多个 开关器件并联的实现方式。
参见图 4 , 该图为本发明提供的变换器为 Boost电路实施例二示意图。 本实施例提供的 Boost电路中， 为储能电感 L充电的开关器件组中包括多 个开关器件并联。 为储能电感 L放电的开关器件组仅包括一个开关器件 Dl l。
如图 4所示， Q1-QN是 N个开关器件， 可以采用 MOS管或者 IGBT等开 关管。 也可以采用机械开关等， 也可以多个开关器件的组合等， 同时也可以采 用二极管。 这 N个开关器件可以采用相同的开关频率。
可以理解的是， N个开关器件也可以采用不同的开关频率， 例如可以用一 个两倍频率的开关器件， 代替两个开关器件达到同样的效果。
例如， 三个并联的开关器件中， 两个开关器件的开关频率是 20K (周期为 T1 ) , 而另外一个开关器件的开关频率为 40K (周期为 T2 ) , 则两个开关频 率是 20K的开关器件相对于 40K开关频率的开关器件的相移分别是 1/2个 T2 周期和 3/2个 T2周期； 这样， 可以利用三个不同开关频率的开关器件， 达到 利用四个相同开关频率（20K ) 的开关器件同样的控制效果。
每个开关周期内 N个开关器件的占空比之和可以等于现有技术中 N个开 关器件同开同关时所需要的占空比。
N个开关器件交替导通， 保证任意两个开关器件都不同时导通， 即导通时 间没有交集。 如图 5所示， 该图为图 4中开关器件的导通时序图。
如果 Ql、 Q2...QN的占空比相同均为 D ( D x N=l-Ul/Uo ) , 且依次间隔 1/N个开关周期时间导通（例如： Q2比 Q1延时 1/N个开关周期， Q3比 Q2 延时 1/N个开关周期… QN比 QN-1延时 1/N个周期） ， 那么此时 L上的纹波 电流频率是现有技术中 N个开关器件同开同关时的 N倍， 纹波电流幅值为 N 个开关器件同开同关时的 1/N。
如果 Ql、 Q2 -. QN 的占空比分别为 Dl、 D2 ... DN (满足 D1+D2+ ... +DN=l-Ul/Uo ) , 且任意两个开关器件不同时导通， 那么此时 L上的纹波电 流幅值也可以有所下降。
以上实施例是以变换器为 Boost电路为例进行介绍的。 下面介绍 Buck电 路、 Buck-Boost电路以及 T型三电平电路。 本发明提供的方法同样适用于以 上几种电路拓朴。
参见图 6, 该图为本发明提供的变换器为 Buck电路的实施例示意图。
本实施例中变换器为 Buck电路；
所述储能器件 L的一端通过为储能器件充电的开关器件组连接电源 U1 , 所述储能器件 L的另一端连接正输出端； 即， Uo的正输出端。 所述储能器件 L 的一端还通过为储能器件放电的开关器件组连接负输出 端； 即， Uo的负输出端。
所述正输出端和负输出端之间连接电容 C 2。
C1是电源的直流输入滤波电容。
如图 6中， 为 L充电的开关器件组中包括 N个并联的开关器件， 分别是
Q1-1直到 Q1-N; 为 L放电的开关器件组中包括 M个并联的开关器件， 分别 是 Q2-1直到 Q2-M。 M和 N均为整数， 可以相等也可以不相等。
参见图 7,该图为本发明提供的变换器为 Buck-Boost电路的实施例示意图。 本实施例中所述变换器为 Buck-Boost变换器；
所述储能器件 L的一端通过为储能器件充电的开关器件连接电源 U1 , 所 述储能器件 L的另一端连接负输出端； 即， Uo的负输出端。
所述储能器件的一端还通过为储能器件放电的开关器件组连接正输出端； 即， Uo的正输出端。
所述正输出端和负输出端之间连接电容 C 2。 C 2为输出滤波电容。
Q1-1直到 Q1-N; 为 L放电的开关器件组中包括 M个并联的开关器件， 分别 是 Q2-1直到 Q2-M。 M和 N均为整数， 可以相等也可以不相等。
参见图 8, 该图为本发明提供的变换器为三电平实施例示意图。
所述变换器为三电平拓朴；
所述为储能器件充电的开关器件组包括两组，分别为第一充电开关器件组 和第二充电开关器件组； 所述为储能器件放电的开关器件组包括两组， 分别为 第一放电开关器件组和第二放电开关器件组； 如图 8所示，第一充电开关器件组包括 N个并联的开关器件，分别为 Q1-1 直到 Q1-N; 第二充电开关器件组包括 M个并联的开关器件， 分别为 Q2-1直 到 Q2-M; 第一放电开关器件组包括 X个并联的开关器件， 分别为 Q3-1直到 Q3-X;第二放电开关器件组包括 Y个并联的开关器件，分别为 Q4-1直到 Q4-Y。
所述第一放电开关器件组和第二放电开关器件组串联后一端连接第一节 点 A; 另一端连接第二节点 B;
所述第一节点 A为电源电压的一半；
所述第一充电开关器件组的一端连接电源的正端，另一端连接所述第二节 点 B;
所述第二充电开关器件组的一端连接所述第二节点 B,另一端连接所述电 源的负端；
所述储能器件的一端连接所述第二节点 B, 另一端连接正输出端； 所述正输出端和负输出端之间连接电容 C3; C3为输出滤波电容。
其中， 电容 C1和 C2的容值相等， C1和 C2将电源电压进行 1/2的分压， 即 A点的电压为 U1的 1/2。
所述第一节点 A连接负输出端。
可以理解的是， 本发明提供的技术方案除了可以应用于三电平拓朴以外， 还适用于五电平拓朴。
需要说明的是，以上实施例仅是列举了几个为储能器件换能（充电和放电 ) 的例子，但是本发明提供的方案并不局限于此，任何为储能器件换能的拓朴均 可以应用本发明提供的方案。 在此不再对具体的拓朴进行一一的列举。
需要说明的是， 本发明以上实施例中为储能器件充电的开关器件组和为储 满足工作要求即可，例 如 Boost电路中， 这两组开关器件保证 Boost电路的正常工作即可。
以上所述， 仅是本发明的较佳实施例而已， 并非对本发明作任何形式上的 限制。 虽然本发明已以较佳实施例揭露如上， 然而并非用以限定本发明。 任何 熟悉本领域的技术人员，在不脱离本发明技术方案范围情况下，都可利用上述 揭示的方法和技术内容对本发明技术方案做出许多可能的变动和修饰，或修改 为等同变化的等效实施例。 因此， 凡是未脱离本发明技术方案的内容， 依据本 于本发明技术方案保护的范围内。

Claims

权 利 要 求
1、 一种变换器， 其特征在于， 包括： 储能器件、 为所述储能器件充电的 开关器件组和为所述储能器件放电的开关器件组；
为所述储能器件充电和放电的开关器件组中，其中有一组开关器件包括至 少两个开关器件并联； 另外一组开关器件组包括至少一个开关器件并联；
2、 根据权利要求 1所述的变换器， 其特征在于， 所述变换器为 Boost电 路、 Buck电路、 Buck-Boost电路、 三电平拓朴或者五电平拓朴。
3、 根据权利要求 2所述的变换器， 其特征在于， 所述变换器为 Boost电 路；
所述储能器件的一端连接电源，所述储能器件的另一端通过为储能器件放 电的开关器件组连接正输出端；
所述储能器件的另一端还通过为储能器件充电的开关器件组连接负输出 端；
所述正输出端和负输出端之间连接电容。
4、根据权利要求 2所述的变换器，其特征在于，所述变换器为 Buck电路； 所述储能器件的一端通过为储能器件充电的开关器件组连接电源，所述储 能器件的另一端连接正输出端；
所述储能器件的一端还通过为储能器件放电的开关器件组连接负输出端； 所述正输出端和负输出端之间连接电容。
5、根据权利要求 2所述的变换器，其特征在于，所述变换器为 Buck-Boost 变换器；
所述储能器件的一端通过为储能器件充电的开关器件连接电源，所述储能 器件的另一端连接负输出端；
所述储能器件的一端还通过为储能器件放电的开关器件组连接正输出端； 所述正输出端和负输出端之间连接电容。
6、 根据权利要求 2所述的变换器， 其特征在于， 所述变换器为三电平拓 朴；
所述为储能器件充电的开关器件组包括两组，分别为第一充电开关器件组 和第二充电开关器件组； 所述为储能器件放电的开关器件组包括两组， 分别为 第一放电开关器件组和第二放电开关器件组；
所述第一放电开关器件组和第二放电开关器件组串联后一端连接第一节 点； 另一端连接第二节点；
所述第一节点为电源电压的一半；
所述第一充电开关器件组的一端连接电源的正端，另一端连接所述第二节 点；
所述第二充电开关器件组的一端连接所述第二节点，另一端连接所述电源 的负端；
所述储能器件的一端连接所述第二节点， 另一端连接正输出端； 所述正输出端和负输出端之间连接电容；
所述第一节点连接负输出端。
7、 根据权利要求 1或 2所述的变换器， 其特征在于，
所述为储能器件充电和放电的开关器件组中包括一个开关器件时，该开关 器件为可控开关管或者不可控开关管；
所述为储能器件充电和放电的开关器件组中包括至少两个开关器件时，该 开关器件为可控开关管。
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CN101958653A (zh) * 2010-09-25 2011-01-26 天津理工大学 应用于风电并网的电流型多电平变流系统

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WO2017107193A1 (zh) * 2015-12-25 2017-06-29 华为技术有限公司 低压差稳压器及电压调节方法
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