用于超声波通信的信道估计和均衡方法及装置 技术领域 Channel estimation and equalization method and device for ultrasonic communication
本发明涉及信道估计和均衡技术, 具体地, 涉及用于超声波通信的信 道估计和均衡方法及装置„ 背景技术 The present invention relates to channel estimation and equalization techniques, and in particular to a channel estimation and equalization method and apparatus for ultrasonic communication.
在使用超声波信号进行通信的情况下, 由于超声波信号在空间中传输 时, 尤其在密闭空间中传输时, 存在较大的多径叠加或干扰, 信号变化较 大。 因此, 为了提高解码的准确性, 降低码间串扰、 多径效应等, 必须对 超声波信道进行估计和均衡。 In the case of communication using an ultrasonic signal, since the ultrasonic signal is transmitted in space, especially in a confined space, there is a large multipath superposition or interference, and the signal changes greatly. Therefore, in order to improve the accuracy of decoding, reduce inter-code crosstalk, multipath effects, etc., it is necessary to estimate and equalize the ultrasonic channel.
信道估计和均衡技术在无线通信中已经进行了广泛的研究, 提出了例 如基于最小均方(LMS )的信道估计技术、 基于最小二乘法(LS )的信道 估计技术、 基于递归最小二乘法(RLS ) 的信道估计技术、 基于最大似然 序列检测 ( MLSE )的信道估计技术、 基于最大后验概率 ( MAP )的均衡 技术等。 然而, 在无线通信中使用的信道估计和均衡技术的复杂度较高, 计算量很大。 Channel estimation and equalization techniques have been extensively studied in wireless communication, and proposed, for example, channel estimation techniques based on least mean square (LMS), channel estimation techniques based on least squares (LS), and recursive least squares (RLS). Channel estimation techniques, channel estimation techniques based on maximum likelihood sequence detection (MLSE), equalization techniques based on maximum a posteriori probability (MAP), etc. However, the channel estimation and equalization techniques used in wireless communications are highly complex and computationally intensive.
另外, 在现有的信号均衡技术中, 通常假设通过信道估计而获得的信 道响应在一帧中是不变的, 但实际上信道响应是随时间变化的, 因此, 现 有的信号均衡技术不能跟踪信道的变化。 发明内容 In addition, in the existing signal equalization techniques, it is generally assumed that the channel response obtained by channel estimation is constant in one frame, but in fact the channel response is time-varying, and therefore, the existing signal equalization technique cannot Track changes in the channel. Summary of the invention
本发明正是鉴于上述技术问题而提出的, 其目的在于提供一种用于超 声波通信的信道估计和均衡方法及装置, 其能够降低超声波信号在传输过 程中的多径效应和码间串扰, 显著减少计算量, 并跟踪信道的变化。 The present invention has been made in view of the above technical problems, and an object thereof is to provide a channel estimation and equalization method and apparatus for ultrasonic communication, which can reduce multipath effect and inter-code crosstalk of an ultrasonic signal during transmission, and is remarkable Reduce the amount of calculations and track changes in the channel.
根据本发明的一个方面, 提供一种用于超声波通信的信道估计和均衡 方法, 其包括: 响应于接收超声波信号, 估计信道响应; 基于所估计的信 道响应, 使用线性均衡器对所述超声波信号进行均衡; 以及根据所述信道
响应的变化, 调整所述线性均衡器的系数。 According to an aspect of the present invention, a channel estimation and equalization method for ultrasonic communication is provided, comprising: estimating a channel response in response to receiving an ultrasonic signal; and using the linear equalizer to the ultrasonic signal based on the estimated channel response Performing equalization; and according to the channel The coefficient of the linear equalizer is adjusted by the change in response.
根据本发明的另一个方面, 提供一种用于超声波通信的信道估计和均 衡装置, 其包括: 信道估计器, 其被配置为响应于接收超声波信号, 估计 信道响应; 线性均衡器, 其被配置为基于所估计的信道响应, 对所述超声 波信号进行均衡; 以及调整器, 其被配置为根据所述信道响应的变化, 调 整所述线性均衡器的系数。 附图说明 According to another aspect of the present invention, a channel estimation and equalization apparatus for ultrasonic communication is provided, comprising: a channel estimator configured to estimate a channel response in response to receiving an ultrasonic signal; a linear equalizer configured And equalizing the ultrasonic signal based on the estimated channel response; and an adjuster configured to adjust a coefficient of the linear equalizer according to the change in the channel response. DRAWINGS
图 1是根据本发明的一个实施例的用于超声波通信的信道估计和均衡 方法的示意性流程图; 1 is a schematic flow chart of a channel estimation and equalization method for ultrasonic communication according to an embodiment of the present invention;
图 2是说明图 1所示的实施例的方法中的调整线性均衡器的系数的一 个例子的示意性流程图; Figure 2 is a schematic flow chart showing an example of adjusting coefficients of a linear equalizer in the method of the embodiment shown in Figure 1;
图 3是说明图 1所示的实施例的方法中的调整线性均衡器的系数的另 一个例子的示意性流程图; Figure 3 is a schematic flow chart showing another example of adjusting the coefficients of the linear equalizer in the method of the embodiment shown in Figure 1;
图 4是根据本发明的一个实施例的用于超声波通信的信道估计和均衡 装置的示意性方框图。 具体实施方式 4 is a schematic block diagram of a channel estimation and equalization apparatus for ultrasonic communication, in accordance with one embodiment of the present invention. detailed description
相信通过以下结合附图对本发明的具体实施方式的详细描述, 本发明 的上述和其它目的、 特征和优点将更加明显。 The above and other objects, features and advantages of the present invention will become more apparent from
图 1示出了根据本发明的一个实施例的用于超声波通信的信道估计和 均衡方法的示意性流程图。 下面结合附图, 对本实施例进行详细说明。 1 shows a schematic flow chart of a channel estimation and equalization method for ultrasonic communication in accordance with one embodiment of the present invention. The present embodiment will be described in detail below with reference to the accompanying drawings.
如图 1所示, 在步驟 S110, 响应于接收超声波信号, 估计超声波信道 的信道响应。 在本实施例中, 超声波信号可使用 20KHz至 22KHz范围内 的频率,并可采用帧的形式。超声波信号的每一帧可包括报头和数据部分。 报头使用伪随机码 ( PN )序列, 例如, 使用码长度为 31的 PN码序列。 接着, 对超声波信号进行频率调制以进行发射。 例如, 频率调制所使用的 频率可以分别是 20.5KHZ和 21.5KHz。 在接收了超声波信号后, 可通过适
当的处理, 包括信道补偿、 提取频域信号、 信号滤波和归一化、 同步处理 等, 获得超声波信号的同步频域信号。 根据所获得的同步频域信号, 对超 声波信道进行信道估计。 As shown in FIG. 1, in step S110, the channel response of the ultrasonic channel is estimated in response to receiving the ultrasonic signal. In the present embodiment, the ultrasonic signal may use a frequency in the range of 20 kHz to 22 kHz, and may take the form of a frame. Each frame of the ultrasonic signal may include a header and a data portion. The header uses a pseudo-random code (PN) sequence, for example, a PN code sequence of code length 31 is used. Next, the ultrasonic signal is frequency modulated for transmission. For example, the frequencies used for frequency modulation can be 20.5 kHz and 21.5 kHz, respectively. After receiving the ultrasonic signal, it can be adapted The processing, including channel compensation, extracting frequency domain signals, signal filtering and normalization, synchronization processing, etc., obtains a synchronized frequency domain signal of the ultrasonic signal. Channel estimation is performed on the ultrasonic channel based on the obtained synchronized frequency domain signal.
首先, 可以使用超声波信号的同步频域信号(为了方便说明, 以下简 称为 "超声波信号" ) , 计算超声波信道的初始信道响应。 在一个例子中, 可以使用已有的信道估计方法计算初始信道响应。 例如, 超声波信道的初 始信道响应可被表示为 h={/¾, hh hc-i ^ 初始信道响应 h的长度为 C, 各系数被计算为 K = E{ynrn_k }l E{rnrn ) , 其中 k=0, 1, . . .,C-1, rn表示值为 {-1, 1 } 的 PN码序列, yn表示在时刻 n的所接收的超声波信号在两个发射频率上 进行快速傅立叶变换(FFT )后获得的幅值的差值, EW表示均值。 接着, 对所计算的初始信道响应进行基于最小均方(LMS )的自适应估计, 以获 得超声波信道的信道响应。 具体地, 在基于 LMS 的自适应估计中, 使用 超声波信号的每一帧的报头中的 PN码序列对初始信道响应 h在时域上进 行估计, 得到在该帧的数据部分的开始时刻 的信道响应 。 在上述的基 于 LMS的自适应估计中, 步长可以设置为 0.005。 First, the initial channel response of the ultrasonic channel can be calculated using the synchronous frequency domain signal of the ultrasonic signal (hereinafter referred to as "ultrasonic signal" for convenience of explanation). In one example, the initial channel response can be calculated using an existing channel estimation method. For example, the initial channel response of the ultrasound channel can be expressed as h={/3⁄4, h h hc-i ^ The length of the initial channel response h is C, and the coefficients are calculated as K = E{y n r n _ k }l E{r n r n ) , where k=0, 1, . . . , C-1, r n represents a sequence of PN codes with a value of {-1, 1 }, and y n represents the received ultrasound at time n The difference in amplitude obtained after the signal is subjected to Fast Fourier Transform (FFT) at two transmission frequencies, and EW represents the mean. Next, a minimum mean square (LMS) based adaptive estimation is performed on the calculated initial channel response to obtain a channel response of the ultrasonic channel. Specifically, in the LMS-based adaptive estimation, the initial channel response h is estimated in the time domain using the PN code sequence in the header of each frame of the ultrasonic signal, and the channel at the beginning of the data portion of the frame is obtained. response. In the above LMS-based adaptive estimation, the step size can be set to 0.005.
在获得了超声波信道的信道响应后, 在步骤 S120, 基于所估计的信道 响应, 使用线性均衡器对超声波信号进行均衡。 在本实施例中, 线性均衡 器可基于最小均方误差(MMSE )对信号进行自适应均衡。在一个例子中, 假设线性均衡器的长度为 / = /1 + /2 + 1, 其中, A、 /2分别表示前向滤波长度 和后向滤波长度, 则线性均衡器的输出为 „= (yn - + ), 其中 c„表示 在 n时刻的线性均衡器的系数向量, 表示信道响应矩阵, 由信道响应 / z 构成, 表示先验信息向量, s表示常系数向量。 After the channel response of the ultrasonic channel is obtained, the ultrasonic signal is equalized using a linear equalizer based on the estimated channel response in step S120. In this embodiment, the linear equalizer can adaptively equalize the signal based on the minimum mean square error (MMSE). In one example, assuming that the length of the linear equalizer is / = / 1 + / 2 + 1, where A, / 2 represent the forward filter length and the backward filter length, respectively, then the output of the linear equalizer is „= ( y n - + ), where c „ denotes the coefficient vector of the linear equalizer at time n, represents the channel response matrix, consists of the channel response / z, represents the a priori information vector, and s denotes the constant coefficient vector.
由于线性均衡器的系数向量^需要在每个采样时刻进行计算, 并且超 声波信道的信道响应随时间变化, 因此, 为了减少计算量, 可以根据信道 响应的变化来调整线性均衡器的系数向量。 下面结合图 2和图 3, 具体说 明线性均衡器的系数的调整方法。 Since the coefficient vector of the linear equalizer needs to be calculated at each sampling instant, and the channel response of the ultrasonic channel changes with time, in order to reduce the amount of calculation, the coefficient vector of the linear equalizer can be adjusted according to the change of the channel response. The adjustment method of the coefficient of the linear equalizer will be specifically described below with reference to Figs. 2 and 3.
图 2 示出了说明线性均衡器的系数的调整的一个例子的示意性流程 图。 如图 2所示, 在步驟 S210, 根据在当前采样时刻的信道响应, 计算线
性均衡器在当前采样时刻的系数。 在一个例子中, 当前采样时刻被设置为 超声波信号的帧的数据部分的开始时刻 n1 (> 这样, 通过上述的步骤 S110, 获得了当前采样时刻的信道响应/ ^。 然后, 利用上述的信号的自适应均衡 方法, 可以获得线性均衡器的在当前采样时刻的系数向量 c„。 接着, 在步 骤 S220,计算当前采样时刻的信道响应与随后的采样时刻的信道响应的变 化量。 信道响应的变化量可反映信道的变化。 在上面的例子中, 随后的采 样时刻是当前采样时刻 的下一个时刻( m+i )。同样,通过上述步骤 siio, 可以获得在时刻(I +1 )的信道响应/ 在一个例子中, 信道响应的变化 的绝对值。 当然, 对于本领域的普通技术人员来说, 能够容易想到信道响 应的变化量还可以采用其它定义。 然后, 在步驟 S230, 比较在步骤 S220 计算的变化量与预定的信道变化阈值。 如果比较结果表明变化量大于信道 变化阈值, 则在步骤 S240, 利用上述的信号的自适应均衡方法, 计算线性 均衡器在随后的采样时刻的系数, 并且将随后的采样时刻的信道响应设置 为当前采样时刻的信道响应。 在上面的例子中, 此时, 当前采样时刻变成Fig. 2 shows a schematic flow chart showing an example of the adjustment of the coefficients of the linear equalizer. As shown in FIG. 2, in step S210, the line is calculated according to the channel response at the current sampling time. The coefficient of the sex equalizer at the current sampling instant. In one example, the current sampling instant is set to the start time n 1 of the data portion of the frame of the ultrasonic signal (> such that, by the above-described step S110, the channel response of the current sampling instant is obtained / ^. Then, using the above signal The adaptive equalization method can obtain the coefficient vector c of the linear equalizer at the current sampling moment. Next, in step S220, the channel response of the current sampling moment and the amount of change of the channel response at the subsequent sampling moment are calculated. The amount of change can reflect the change of the channel. In the above example, the subsequent sampling instant is the next moment ( m+i ) of the current sampling instant. Similarly, the channel at time (I +1 ) can be obtained by the above step siio Response / In one example, the absolute value of the change in channel response. Of course, it will be readily apparent to one of ordinary skill in the art that other variations can be made in the amount of change in channel response. Then, in step S230, the comparison is in step S220 calculates the amount of change and the predetermined channel change threshold. If the comparison result indicates that the amount of change is large The channel change threshold is then, in step S240, the coefficient of the linear equalizer at the subsequent sampling instant is calculated using the adaptive equalization method of the signal described above, and the channel response of the subsequent sampling instant is set to the channel response of the current sampling instant. In the above example, at this point, the current sampling time becomes
( m+i ) , 而当前采样时刻的信道响应变为/ , 线性均衡器的系数向量变 为 c„+1。 如果步骤 S230的比较结果表明变化量小于信道变化阈值, 则在步 骤 S250, 维持线性均衡器在当前采样时刻的系数。 在上面的例子中, 线性 均衡器的系数向量 保持不变。 然后, 对于当前采样时刻 ( +1 )的下一 个采样时刻( +2 ), 重复上述的变化量计算步骤 S220和比较步骤 S230, 直到超声波信号的一个帧结束。 (m+i), and the channel response of the current sampling instant becomes /, and the coefficient vector of the linear equalizer becomes c „ +1 . If the comparison result of step S230 indicates that the amount of change is smaller than the channel change threshold, then in step S250, The coefficient of the linear equalizer at the current sampling instant. In the above example, the coefficient vector of the linear equalizer remains unchanged. Then, for the next sampling instant (+2) of the current sampling instant (+1), repeat the above change. The quantity calculation step S220 and the comparison step S230 are performed until one frame of the ultrasonic signal ends.
图 3示出了说明线性均衡器的系数的调整的另一个例子的示意性¾½ 图。 在本例子中, 步骤 S310至 S340与图 2中的步骤 S210至 S240相同, 不同之处在于当变化量小于信道变化阈值时的处理。 Fig. 3 shows a schematic 3⁄4⁄2 diagram illustrating another example of the adjustment of the coefficients of the linear equalizer. In the present example, steps S310 to S340 are the same as steps S210 to S240 in Fig. 2, except for the processing when the amount of change is smaller than the channel change threshold.
在本例子中, 如果变化量小于信道变化阈值, 则在步骤 S350, 使用基 于最小均方(LMS )的自适应估计来更新线性均衡器在当前采样时刻的系 数, 以便跟踪信道的细微变化。 在该 LMS 自适应估计中, 步长被设置为 0.005。接着, 在步骤 S360, 根据线性均衡器的更新的系数, 确定用于对系
数^的第一阈值。 由于线性均衡器的内在特定, 当在其系数向量中存在 较多接近于零的系数时, 会对输出带来较大的噪声, 因此, 需要对一些系 数进行迫零。 第一阈值可根据线性均衡器的系数的相对大小来确定。 在一 个实施例中, 第一阈值可被确定为线性均衡器的更新的系数中的最大值的 绝对值的 0.1。对于本领域的普通技术人员来说,可以容易想到还可以其它 方式定义第一阈值。 然后, 在步骤 S370, 比较线性均衡器的更新的各个系 数与第一阈值。 在一个例子中, 可以将各个系数的绝对值与第一阈值进行 比较。 然后, 在步骤 S380, 将例如绝对值小于第一阈值的线性均衡器的更 新的系数设置为零。 此外, 还可以根据置零系数的个数与所有系数的个数 的比值, 调整在更新线性均衡器的系数时使用的 LMS估计的步长。 当置 零系数越多时, 步长被调整得越大。 In the present example, if the amount of change is less than the channel change threshold, then the coefficient of the linear equalizer at the current sampling instant is updated using a minimum mean square (LMS) based adaptive estimate in step S350 to track subtle changes in the channel. In this LMS adaptive estimation, the step size is set to 0.005. Next, in step S360, determining, according to the updated coefficient of the linear equalizer, The first threshold of the number ^. Due to the inherent specificity of the linear equalizer, when there are more coefficients close to zero in its coefficient vector, it will bring more noise to the output. Therefore, some coefficients need to be forced to zero. The first threshold may be determined based on the relative magnitude of the coefficients of the linear equalizer. In one embodiment, the first threshold may be determined to be 0.1 of the absolute value of the maximum of the updated coefficients of the linear equalizer. It will be readily apparent to one of ordinary skill in the art that the first threshold can also be defined in other ways. Then, in step S370, the updated respective coefficients of the linear equalizer are compared with the first threshold. In one example, the absolute value of each coefficient can be compared to a first threshold. Then, in step S380, the updated coefficient of, for example, the linear equalizer whose absolute value is smaller than the first threshold is set to zero. In addition, the step size of the LMS estimation used in updating the coefficients of the linear equalizer may be adjusted according to the ratio of the number of zeroing coefficients to the number of all coefficients. When the zeroing coefficient is larger, the step size is adjusted larger.
通过以上描述可以看出, 本实施例的方法能够自适应地进行信道估计 和均衡, 降低超声波信号在空间中传输时引起的多径效应和码间串扰, 并 且能够根据信道的变化调整线性均衡器的系数, 从而快速地跟踪信道的变 化, 使得信道估计和均衡能够适应信道的变化。 此外, 本实施例的方法具 有计算量小的优点。 As can be seen from the above description, the method of the present embodiment can adaptively perform channel estimation and equalization, reduce multipath effects and inter-code crosstalk caused by transmission of ultrasonic signals in space, and can adjust linear equalizer according to channel changes. The coefficients are such that the channel changes are quickly tracked so that channel estimation and equalization can accommodate channel variations. Further, the method of this embodiment has the advantage of a small amount of calculation.
在同一个发明构思下, 图 4示出了根据本发明的一个实施例的用于超 声波通信的信道估计和均衡装置 400的示意性方框图。 下面结合附图, 对 本实施例进行详细描述, 其中, 对于与前面实施例相同的部分, 适当省略 其说明。 Under the same inventive concept, Fig. 4 shows a schematic block diagram of a channel estimation and equalization apparatus 400 for ultrasonic communication in accordance with one embodiment of the present invention. The present embodiment will be described in detail below with reference to the accompanying drawings, wherein the description of the same portions as those of the previous embodiment will be appropriately omitted.
如图 4所示, 本实施例的信道估计和均衡装置 400包括: 信道估计器 401 , 其被配置为响应于接收超声波信号, 估计超声波信道的信道响应; 线 性均衡器 402, 其被配置为基于所估计的信道响应, 对超声波信号进行均 衡; 以及调整器 403, 其被配置为根据信道响应的变化, 调整线性均衡器 402的系数。 As shown in FIG. 4, the channel estimation and equalization apparatus 400 of the present embodiment includes: a channel estimator 401 configured to estimate a channel response of an ultrasonic channel in response to receiving an ultrasonic signal; a linear equalizer 402 configured to be based on The estimated channel response, equalizing the ultrasonic signal; and an adjuster 403 configured to adjust the coefficients of the linear equalizer 402 based on changes in the channel response.
所接收的超声波信号在经过适当的处理后, 获得超声波信号的同步频 域信号, 并被提供给本实施例的装置 400。在装置 400中, 信道估计器 401 根据超声波信号的同步频域信号(以下简称为 "超声波信号" :)对超声波
信道进行信道估计, 以获得超声波信道的信道响应。 在一个例子中, 信道 估计器 401中的信道响应计算模块 4011使用超声波信号,计算超声波信道 的初始信道响应。如前所述,信道响应计算模块 4011可使用已有的信道估 计方法估计信道响应。接着, 自适应估计模块 4012对所获得的初始信道响 应进行基于最小均方的自适应估计, 以获得超声波信道的信道响应。 The received ultrasonic signal is subjected to appropriate processing to obtain a synchronized frequency domain signal of the ultrasonic signal, and is supplied to the apparatus 400 of the present embodiment. In the device 400, the channel estimator 401 pairs the ultrasonic wave according to the synchronous frequency domain signal of the ultrasonic signal (hereinafter referred to as "ultrasonic signal":) The channel performs channel estimation to obtain the channel response of the ultrasonic channel. In one example, channel response calculation module 4011 in channel estimator 401 calculates the initial channel response of the ultrasound channel using the ultrasound signal. As previously discussed, channel response calculation module 4011 can estimate the channel response using existing channel estimation methods. Next, the adaptive estimation module 4012 performs a least mean square based adaptive estimation on the obtained initial channel response to obtain a channel response of the ultrasonic channel.
接着, 信道响应被提供给线性均衡器 402, 以对超声波信号进行均衡。 线性均衡器 402的系数可由调整器 403根据信道响应的变化来调整。 在一 个例子中, 线性均衡器 402可使用已有的自适应均衡方法对超声波信号进 行均衡。 The channel response is then provided to a linear equalizer 402 to equalize the ultrasonic signals. The coefficients of linear equalizer 402 can be adjusted by regulator 403 based on changes in channel response. In one example, linear equalizer 402 can equalize the ultrasonic signals using existing adaptive equalization methods.
在调整器 403中 ,系数计算模块 4031根据通过信道估计器 401获得的 当前采样时刻的信道响应, 计算线性均衡器 402在当前采样时刻的系数。 然后,变化量计算模块 4032可计算当前采样时刻的信道响应与随后的采样 时刻的信道响应的变化量。 随后的采样时刻的信道响应通过信道估计器 401 获得。 在一个例子中, 信道响应的变化量被定义为当前采样时刻的信 道响应与随后的采样时刻的信道响应的差值的绝对值。 然后, 第一比较模 块 4033将所计算的变化量与预定的信道变化阈值进行比较。如果变化量大 于信道变化阈值,则系数计算模块 4031根据所获得的随后的采样时刻的信 道响应, 计算线性均衡器 402在 的采样时刻的系数。 另外, ^的采 样时刻的信道响应被设置为当前采样时刻的信道响应。 如果变化量小于信 道变化阈值,则系数计算模块 4031维持线性均衡器 402在当前采样时刻的 系数。 在每个采样时刻, 变化量计算模块 4032和第一比较模块 4033的操 作可被重复执行, 直到超声波信号的一帧结束。 In the adjuster 403, the coefficient calculation module 4031 calculates the coefficient of the linear equalizer 402 at the current sampling instant based on the channel response of the current sampling instant obtained by the channel estimator 401. The delta calculation module 4032 can then calculate the amount of change in the channel response at the current sampling instant and the channel response at the subsequent sampling instant. The channel response at the subsequent sampling instant is obtained by the channel estimator 401. In one example, the amount of change in the channel response is defined as the absolute value of the difference between the channel response at the current sampling instant and the channel response at the subsequent sampling instant. The first comparison module 4033 then compares the calculated amount of change to a predetermined channel change threshold. If the amount of change is greater than the channel change threshold, the coefficient calculation module 4031 calculates the coefficient of the sampling instant at which the linear equalizer 402 is based on the obtained channel response of the subsequent sampling instant. In addition, the channel response of the sampling time of ^ is set to the channel response at the current sampling time. If the amount of change is less than the channel change threshold, coefficient calculation module 4031 maintains the coefficients of linear equalizer 402 at the current sampling instant. At each sampling instant, the operations of the delta calculation module 4032 and the first comparison module 4033 can be repeatedly executed until one frame of the ultrasonic signal ends.
在另一个例子中, 调整器 403还可以包括系数更新模块 4034、 阈值确 定模块 4035、 第二比较模块 4036和置零模块 4037。 系数更新模块 4034 可以在通过变化量计算模块 4033获得的变化量小于信道变化阈值时,使用 基于最小均方的自适应估计来更新线性均衡器 402在当前采样时刻的系 数。 然后, 阈值确定模块 4035根据线性均衡器 402的更新的系数, 确定用 于对系数迫零的第一阈值。 在一个实施例中, 第一阈值可被确定为线性均
衡器 402的更新的系数中的最大值的绝对值的 0.1。 然后, 第二比较模块 4036将线性均衡器 402的更新的各个系数与第一阈值进行比较, 并由置零 模块 4037将小于第一阈值的线性均衡器 402的更新的系数设置为零。在一 个实施例中,第二比较模块 4036将线性均衡器 402的各个系数的绝对值与 第一阈值进行比较,并由置零模块 4037将绝对值小于第一阈值的线性均衡 器 402的系数设置为零。 In another example, the adjuster 403 can further include a coefficient update module 4034, a threshold determination module 4035, a second comparison module 4036, and a zeroing module 4037. The coefficient update module 4034 may update the coefficients of the linear equalizer 402 at the current sampling instant using the least mean square based adaptive estimation when the amount of change obtained by the delta calculation module 4033 is less than the channel change threshold. Threshold determination module 4035 then determines a first threshold for zeroing the coefficient based on the updated coefficients of linear equalizer 402. In one embodiment, the first threshold can be determined to be linear The absolute value of the maximum of the updated coefficients of the scale 402 is 0.1. Then, the second comparison module 4036 compares the updated respective coefficients of the linear equalizer 402 with the first threshold, and sets the updated coefficients of the linear equalizer 402 that are less than the first threshold to zero by the zeroing module 4037. In one embodiment, the second comparison module 4036 compares the absolute values of the coefficients of the linear equalizer 402 with a first threshold and sets the coefficients of the linear equalizer 402 whose absolute value is less than the first threshold by the zeroing module 4037. Zero.
应当指出, 本实施例的用于超声波通信的信道估计和均衡装置 400在 操作上能够实现图 1至图 3所示的实施例的用于超声波通信的信道估计和 均衡方法。 It should be noted that the channel estimation and equalization apparatus 400 for ultrasonic communication of the present embodiment is operationally capable of realizing the channel estimation and equalization method for ultrasonic communication of the embodiment shown in Figs.
此外, 上述实施例的用于超声波通信的信道估计和均衡装置 400可包 括在移动终端中, 以对混合在音频信号中的超声波信号进行信道估计和均 衡。 Furthermore, the channel estimation and equalization apparatus 400 for ultrasonic communication of the above embodiment may be included in the mobile terminal to perform channel estimation and equalization on the ultrasonic signals mixed in the audio signal.
以上所公开的实施例的方法可以在软件、 硬件、 或软件和硬件的结合 中实现。 硬件部分可以利用专用逻辑来实现。 例如, 上述实施例中的提供 增强音频数据流的装置及其各个组成部分可以由诸如超大规模集成电路或 门阵列、诸如逻辑芯片、 晶体管等的半导体、或者诸如现场可编程门阵列、 可编程逻辑设备等的可编程硬件设备的硬件电路实现, 也可以用由各种类 型的处理器执行的软件实现, 也可以由上述硬件电路和软件的结合实现。 软件部分可以存储在存储器中, 由适当的指令执行系统, 例如微处理器、 个人计算机 ( PC )或大型机来执行。 The methods of the above disclosed embodiments can be implemented in software, hardware, or a combination of software and hardware. The hardware part can be implemented using dedicated logic. For example, the apparatus for providing enhanced audio data streams and its various components in the above embodiments may be comprised of semiconductors such as very large scale integrated circuits or gate arrays, such as logic chips, transistors, etc., or such as field programmable gate arrays, programmable logic The hardware circuit implementation of the programmable hardware device such as a device can also be implemented by software executed by various types of processors, or by a combination of the above hardware circuits and software. The software portion can be stored in memory and executed by a suitable instruction execution system, such as a microprocessor, personal computer (PC) or mainframe.
以上虽然通过示例性的实施例详细描述了本发明的用于超声波通信的 信道估计和均衡方法及装置, 但是以上这些实施例并不是穷举的, 本领域 技术人员可以在本发明的精神和范围内实现各种变化和修改。 因此, 本发 明并不限于这些实施例, 本发明的范围仅由所附的权利要求限定。
Although the channel estimation and equalization method and apparatus for ultrasonic communication of the present invention have been described in detail above by way of exemplary embodiments, the above embodiments are not exhaustive, and those skilled in the art may have the spirit and scope of the present invention. Various changes and modifications are implemented within. Therefore, the invention is not limited to the embodiments, and the scope of the invention is limited only by the appended claims.