WO2012155382A1 - 升压变换器 - Google Patents

升压变换器 Download PDF

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Publication number
WO2012155382A1
WO2012155382A1 PCT/CN2011/076798 CN2011076798W WO2012155382A1 WO 2012155382 A1 WO2012155382 A1 WO 2012155382A1 CN 2011076798 W CN2011076798 W CN 2011076798W WO 2012155382 A1 WO2012155382 A1 WO 2012155382A1
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WIPO (PCT)
Prior art keywords
inductor
diode
boost converter
anode
capacitor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Ceased
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PCT/CN2011/076798
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English (en)
French (fr)
Inventor
高新明
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
TCL China Star Optoelectronics Technology Co Ltd
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Shenzhen China Star Optoelectronics Technology Co Ltd
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Priority to US13/318,147 priority Critical patent/US8797005B2/en
Publication of WO2012155382A1 publication Critical patent/WO2012155382A1/zh
Anticipated expiration legal-status Critical
Ceased legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/005—Conversion of DC power input into DC power output using Cuk converters

Definitions

  • the present invention relates to the field of voltage conversion technologies, and in particular, to a boost converter.
  • a lower voltage is typically boosted to provide power to a higher voltage demand circuit, where a boost converter is typically used to implement this function.
  • FIG. 1 is a prior art boost converter.
  • the boost converter includes a DC voltage input terminal Vin, a DC voltage output terminal Vout, a fuse F101, and a first inductor.
  • the second inductor L102 and the first inductor L101 are coupled inductors, and the turns ratio of the former to the latter is N.
  • the DC voltage input terminal Vin is sequentially connected to the anode of the rectifier diode D101 via the fuse F101, the first inductor L101, and the second inductor L102, and the cathode of the rectifier diode D101 is connected to the DC voltage output terminal Vout.
  • the drain of the switching power transistor Q101 is connected between the first inductor and the second inductor, the source is grounded, and the gate receives a driving signal DRV.
  • the filter capacitor C102 is connected to the ground GND, and the other end is connected to the DC voltage output terminal Vout.
  • the working principle of the boost converter is as follows:
  • the DC voltage input terminal Vin charges the first inductor L101, and the first inductor L101 and the second inductor L102 generate an induced electromotive force.
  • the voltage across the first inductor L101 is Vin, and the voltage across the second inductor L102 is N*Vin. Since the left end of the second inductor L102 is grounded, the voltage at the right end is -N* Vin, that is, the anode voltage of the rectifier diode D101 is -N*Vin.
  • the switching power transistor Q101 When the switching power transistor Q101 is turned off, the first inductor L101 releases energy, and the DC voltage output terminal Vout reaches the voltage Vo, that is, the cathode voltage of the rectifier diode D101 is Vo.
  • the boost converter has a high withstand voltage requirement for the rectifier diode D101, and when the rectifier diode D101 is selected, it faces the problem of the withstand voltage limitation of the rectifier diode D101.
  • the switching power transistor Q101 when the switching power transistor Q101 is turned on, the second inductor L102 The voltage at the left end is higher than the voltage at the right end, the rectifier diode D101 is turned off, and the second inductor L102 is not in a loop, and the storage of the electric energy cannot be performed. Therefore, the utilization of the inductor is low.
  • the technical problem mainly solved by the present invention is how to design a boost converter with high coupling inductance utilization and convenient selection.
  • one technical solution adopted by the present invention is to provide a boost converter including a switching element, a first diode, a second diode, a first inductor, a second inductor, a first capacitor, a DC voltage input terminal, and a DC voltage output terminal; the DC inductor input terminal and the DC voltage output terminal are sequentially connected to the first inductor, the second inductor, the first capacitor, and the second a cathode tube; an anode of the second diode is connected to the first capacitor, and a cathode is connected to the DC voltage output terminal; the switching element includes a first end portion, a second end portion, and a first end portion for controlling the first end a third end portion that is electrically connected to and disconnected from the second end portion, the first end portion is connected between the first inductor and the second inductor, the second end portion is grounded, and the third end portion is used Receiving a driving signal; a cathode of the first diode is
  • a boost converter including a switching element, a first diode, a second diode, and a first inductor.
  • a second inductor a DC voltage input terminal, and a DC voltage output terminal;
  • the DC inductor input terminal and the DC voltage output terminal are sequentially connected to the first inductor, the second inductor, and the second diode;
  • the anode of the diode is connected to the second inductor, and the cathode is connected to the DC voltage output terminal;
  • the switching element includes a first end portion, a second end portion, and a first end portion and a second end portion for controlling a third end portion that is connected to and off, the first end portion is connected between the first inductor and the second inductor, the second end portion is grounded, and the third end portion is configured to receive a driving signal;
  • a cathode of the first diode is coupled to an anode of the second diode, and an ano
  • the boost converter further includes a first capacitor and a second capacitor, the first capacitor being connected between the second inductor and the anode of the second diode, and one end of the second capacitor and the DC voltage output The end is connected and the other end is grounded.
  • the boost converter further includes a third capacitor connected between the DC voltage input terminal and the ground.
  • the booster further includes a current limiting resistor, one end of the current limiting resistor is connected to the anode of the first diode, and the other end is grounded.
  • the switching element is a field effect transistor, the first end of which is a drain, the second end is a source, and the third end is a gate.
  • the first inductor and the second inductor are coupled inductors, the same name end of the first inductor is connected to the DC voltage input end, the different name end is connected to the same name end of the second inductor, and the second inductor is connected with the different name end.
  • the boost converter of the present invention further includes a first diode, and the voltage of the second and second diodes is low, and the component of the boost converter of the present invention has low cost and is convenient to use.
  • the first diode further causes the second inductor to form a loop when the switching element is turned on, and the second inductor can store energy during power transmission to improve inductance utilization. Therefore, the boost converter of the present invention has the advantages of convenient selection and high inductance utilization.
  • FIG. 1 is a circuit diagram of a prior art boost converter
  • FIG. 2 is a circuit diagram of a first embodiment of a boost converter of the present invention
  • FIG. 3 is a circuit diagram of a second embodiment of the boost converter of the present invention.
  • FIG. 2 is a circuit diagram of the first embodiment of the boost converter of the present invention.
  • the boost converter includes a DC voltage input terminal Vin, a DC voltage output terminal Vout, a fuse (not labeled), a switching element Q1, a first diode D1, and a second diode D2.
  • the second inductor L2 and the first inductor L1 are coupled inductors.
  • the same-name end of the first inductor L1 is connected to the DC voltage input terminal Vin via the fuse, and the different-name end of the first inductor L1 is connected to the same-name end of the second inductor L2.
  • the different end of the second inductor L2 is connected to the anode of the second diode D2 via the first capacitor C1.
  • the cathode of the second diode D2 is connected to the DC voltage output terminal Vout.
  • the second diode D2 is a rectifier diode.
  • the first diode D1 is a clamp diode, The anode is connected to the ground GND, and the cathode is connected to the anode of the second diode D2.
  • the second capacitor C2 is a filter capacitor, one end of which is connected to the cathode of the second diode D2, and the other end of which is grounded to GND.
  • the switching element Q1 includes a first end portion, a second end portion, and a third end portion for controlling the first end portion and the second end portion to be turned on and off.
  • the first end is connected to the same end of the second inductor L2, the second end is grounded to GND, and the third end receives a drive signal DRV.
  • the third end of the switching element Q1 controls the conduction and the turning off of the first end portion and the second end portion according to the received driving signal DRV.
  • the ratio of the turns of the second inductor L2 to the first inductor L1 is N, and the working principle of the boost converter is as follows:
  • the DC voltage input terminal Vin charges and stores the first inductor L1, and the first inductor L1 and the second inductor L2 generate an induced electromotive force.
  • the voltage across the first inductor L1 is Vin
  • the voltage across the second inductor L2 is N*Vin. Since the same-name end of the second inductor L2 is grounded to GND via the switching element Q1, the voltage of the second inductor L2 is -N*Vin, and the anode voltage of the first diode D1 is higher than the cathode. The voltage, the first diode D1 is turned on.
  • the second inductor L2, the first capacitor C1 and the first rectifier diode D1 form a loop, so that the second inductor L2 can also perform charging and energy storage when the switching element Q1 is turned on, and the second inductor is improved. L2 coupling efficiency.
  • the first capacitor C1 is used to filter out the DC component in the loop to prevent overcurrent from occurring in the loop. Further, since the first diode D1 is turned on, the anode of the second diode D2 is clamped to the ground.
  • the boost converter of the present invention further includes a first diode D1 that causes the anode voltage of the second diode D2 to be turned on at the switching element Q1.
  • the first diode D1 also causes the second inductor L2 to form a loop when the switching element Q1 is turned on, and the second inductor L2 can store energy during power transmission to improve the utilization of the inductor. Therefore, the boost converter of the present invention is convenient in selection and high in inductance utilization.
  • the switching element Q1 is an N-channel field effect transistor, and the corresponding switching element
  • the first end of the device Q1 is a drain, the second end is a source, and the third end is a gate.
  • P-channel FETs or other components having equivalent functions can also be selected as needed.
  • FIG. 3 is a circuit diagram of a second embodiment of the boost converter of the present invention.
  • the boost converter of the second embodiment is substantially the same as the boost converter of the first embodiment.
  • the main difference is that the boost converter of the second embodiment further includes a third capacitor C13 and a current limiting resistor R11.
  • the third capacitor is used as a filter capacitor.
  • the third capacitor C13-terminal is connected to the DC voltage input terminal Vin via a fuse, and the other terminal is grounded to GND.
  • the current limiting resistor R11 is connected to the anode of the first diode D11, and the other end is connected to the ground GND.
  • the third capacitor C13 is used to filter out noise signals in the voltage input from the DC voltage input terminal Vin.
  • the current limiting resistor R11 is used to limit current protection when the switching element Q11 is turned on, thereby improving the safety and durability of the boost converter.
  • the boost converters of the first embodiment and the second embodiment of the present invention can be used for boosting conversion of a DC voltage of a liquid crystal display device in a circuit using a liquid crystal display device.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Description

升压变换器
【技术领域】
本发明涉及电压转换技术领域， 特别涉及一种升压变换器。
【背景技术】
在对电子器件供电时， 通常会将一较低的电压进行升压变换以实现对一较 高电压需求的电路进行供电， 在这种供电电路中通常会使用升压变换器来实现 这一功能。
如图 1所示， 图 1是一种现有技术的升压变换器， 所述升压变换器包括一 直流电压输入端 Vin、一直流电压输出端 Vout、一保险管 F101、一第一电感 L101、 一第二电感 L102、一开关功率管 Q101、一整流二极管 D101和一滤波电容 C102。 所述第二电感 L102与所述第一电感 L101为耦合电感， 前者与后者的匝数比为 N。
所述直流电压输入端 Vin依序经由所述保险管 F101、 所述第一电感 L101、 第二电感 L102连接至整流二极管 D101的阳极， 整流二极管 D101的阴极连接 到所述直流电压输出端 Vout。所述开关功率管 Q101的漏极连接在所述第一电感 与第二电感之间， 源极接地， 栅极接收一驱动信号 DRV。 滤波电容 C102—端 接地 GND, 另一端连接直流电压输出端 Vout。
所述升压变换器的工作原理如下：
当开关功率管 Q101导通时， 所述直流电压输入端 Vin为第一电感 L101充 电储能， 第一电感 L101和第二电感 L102产生感应电动势。 所述第一电感 L101 两端的电压为 Vin,所述第二电感 L102两端的电压为 N*Vin。由于第二电感 L102 的左端接地，因此右端电压为 -N* Vin,即整流二极管 D101的阳极电压为 -N*Vin。
当开关功率管 Q101关断时，第一电感 L101释放能量，直流电压输出端 Vout 的达到电压 Vo, 即整流二极管 D101的阴极电压为 Vo。
由上可知，整流二极管 D101的阴极和阳极间的电压差最大时为 Vo+N*Vin。 整流二极管 D101的耐压值需要大于 Vo+N*Vin。 因此上述升压变换器对整流二 极管 D101的耐压值要求较高， 在选用整流二极管 D101时， 会面临整流二极管 D101的耐压限制问题。
其次，这种升压变换器在所述开关功率管 Q101导通时，所述第二电感 L102 的左端电压高于右端电压， 整流二极管 D101截止， 所述第二电感 L102没有处 于一个回路中， 不能进行电能的存储， 因此， 电感利用率低。
因此， 如何设计出一种选件方便且耦合电感利用率高的升压变换器是业界 急需解决的课题。
【发明内容】
本发明主要解决的技术问题是如何设计出一种耦合电感利用率高和选件方 便的升压变换器。
为解决上述技术问题， 本发明釆用的一个技术方案是： 提供一种升压变换 器， 所述升压变换器包括开关元件、 第一二极管、 第二二极管、 第一电感、 第 二电感、 第一电容、 直流电压输入端和直流电压输出端； 所述直流电压输入端 与直流电压输出端之间依次连接所述第一电感、 第二电感、 第一电容、 第二二 极管； 所述第二二极管的阳极与第一电容连接， 阴极与直流电压输出端连接； 所述开关元件包括第一端部、 第二端部和一用于控制所述第一端部与第二端部 导通与关断的第三端部， 所述第一端部连接在第一电感与第二电感之间， 所述 第二端部接地， 所述第三端部用于接收驱动信号； 所述第一二极管的阴极与所 述第二二极管的阳极连接， 第一二极管的阳极接地。
为解决上述技术问题， 本发明釆用的另一个技术方案是： 提供一种升压变 换器， 所述升压变换器包括开关元件、 第一二极管、 第二二极管、 第一电感、 第二电感、 直流电压输入端和直流电压输出端； 所述直流电压输入端与直流电 压输出端之间依次连接所述第一电感、 第二电感、 第二二极管； 所述第二二极 管的阳极与第二电感连接， 阴极与直流电压输出端连接； 所述开关元件包括第 一端部、 第二端部和一用于控制所述第一端部与第二端部导通与关断的第三端 部， 所述第一端部连接在第一电感与第二电感之间， 所述第二端部接地， 所述 第三端部用于接收驱动信号； 所述第一二极管的阴极与所述第二二极管的阳极 连接， 第一二极管的阳极接地。
其中， 所述升压变换器进一步包括第一电容和第二电容， 所述第一电容连 接于第二电感和第二二极管的阳极之间， 所述第二电容的一端与直流电压输出 端连接， 另一端接地。
其中， 所述升压变换器进一步包括一连接于直流电压输入端和地之间的第 三电容。 其中， 所述升压器还进一步包括一限流电阻， 所述限流电阻的一端与第一 二极管的阳极连接， 另一端接地。
其中， 所述开关元件为场效应管， 其第一端部为漏极， 第二端部为源极， 第三端部为栅极。
其中， 所述第一电感与第二电感为耦合电感， 所述第一电感的同名端与直 流电压输入端连接， 异名端与第二电感的同名端连接， 第二电感的异名端连接 到上述第二二极管的阳极。
相较于现有技术， 本发明的升压变换器进一步包括一第一二极管， 所述第 低第二二极管承受的电压， 使本发明升压变换器选用元件成本低， 使用方便。 此外， 所述第一二极管还使得第二电感在开关元件导通时形成回路， 所述第二 电感能够在电能传输过程中存储能量， 提高电感利用率。 因此， 本发明的升压 变换器具有选件方便且电感利用率高的优点。
【附图说明】
图 1是现有技术升压变换器的电路示意图；
图 2是本发明的升压变换器第一实施例的电路示意图；
图 3是本发明的升压变换器第二实施例的电路示意图。
【具体实施方式】
下面结合附图对本发明进行说明。
请参阅图 2, 图 2是本发明的升压变换器第一实施例的电路示意图。 所述升 压变换器包括一直流电压输入端 Vin、 一直流电压输出端 Vout、 一保险管（未标 识）、 一开关元件 Ql、 一第一二极管 Dl、 一第二二极管 D2、 一第一电容 Cl、 一第二电容 C2、 一第一电感 L1和一第二电感 L2。
所述第二电感 L2与所述第一电感 L1为耦合电感。所述第一电感 L1的同名 端经由上述保险管与直流电压输入端 Vin连接， 第一电感 L1的异名端与第二电 感 L2的同名端连接。第二电感 L2的异名端经由第一电容 C1连接到上述第二二 极管 D2的阳极。 所述第二二极管 D2的阴极连接到所述直流电压输出端 Vout。 所述第二二极管 D2是一整流二极管。 所述第一二极管 D1是一钳位二极管， 其 阳极接地 GND, 阴极连接第二二极管 D2的阳极。 所述第二电容 C2是一滤波电 容， 其一端与第二二极管 D2的阴极连接， 另一端接地 GND。
所述开关元件 Q1包括一第一端部、一第二端部和一用于控制所述第一端部 与第二端部导通与关断的第三端部。所述第一端部与第二电感 L2的同名端连接， 第二端部接地 GND, 第三端部接收一驱动信号 DRV。 所述开关元件 Q1的第三 端部根据接收到的驱动信号 DRV对应控制第一端部与第二端部的导通与关断。
4叚设第二电感 L2与第一电感 L1的线圈匝数比为 N , 所述升压变换器的工 作原理如下：
当所述开关元件 Q 1 的第一端部与第二端部导通时， 所述直流电压输入端 Vin为第一电感 L1充电储能， 第一电感 L1和第二电感 L2产生感应电动势， 所 述第一电感 L1两端的电压为 Vin, 所述第二电感 L2两端的电压为 N*Vin。 由于 所述第二电感 L2的同名端经由开关元件 Q1接地 GND, 因此所述第二电感 L2 异名端电压为 -N*Vin, 此时所述第一二极管 D1的阳极电压高于阴极电压， 第一 二极管 D1导通。 所述第二电感 L2, 第一电容 C1和第一整流二极管 D1形成一 个回路， 使所述第二电感 L2在所述开关元件 Q1导通时也能进行充电储能， 提 高所述第二电感 L2的耦合效率。 所述第一电容 C1用于把上述回路中的直流分 量滤掉， 以防止回路中产生过电流。 此外， 由于所述第一二极管 D1导通， 因此 所述第二二极管 D2的阳极被钳位至地。
当所述开关元件 Q1的第一端部与第二端部关断时， 所述第一电感 L1和第 二电感 L2释放电量，所述第一整流二极管 D1截止，此时，直流电压输出端 Vout 的电压 Vo=Vin+VLl+VL2, VL1为所述第一电感 L1上的电压， VL2为所述第二 电感 L2上的电压。
由上可知， 第二二极管 D2的阴极和阳极间的电压差最大时为 Vo, 因此所 述第二二极管 D2的耐压只要达到 Vo的电压即可。
相较于现有技术， 本发明的升压变换器进一步包括一第一二极管 D1 , 所述 第一二极管 D1使得第二二极管 D2的阳极电压在所述开关元件 Q1导通时钳位 至地， 大大降低第二二极管 D2承受的电压， 使本发明升压变换器选用元件成本 低， 使用方便。 此外， 所述第一二极管 D1还使得第二电感 L2在开关元件 Q1 导通时形成回路， 所述第二电感 L2能够在电能传输过程中存储能量， 提高电感 利用率。 因此， 本发明的升压变换器选件方便且电感利用率高。
在本实施例中， 所述开关元件 Q1为 N沟道场效应管， 对应的所述开关元 件 Ql的第一端部为漏极， 第二端部为源极， 第三端部为栅极。 当然也可以根据 需要选用 P沟道场效应管或者其它具有等同功用的元件。
请参阅图 3 , 其是本发明的升压变换器第二实施例的电路示意图。 第二实施 例的升压变换器与第一实施例的升压变换器大致相同， 主要区别在于， 第二实 施例的升压变换器进一步包括一第三电容 C13和一限流电阻 R11 , 所述第三电 容用作滤波电容。 上述第三电容 C13—端经由一保险管连接至一直流电压输入 端 Vin, 另一端接地 GND。 上述限流电阻 R11—端连接一第一二极管 D11的阳 极， 另一端接地 GND。
所述第三电容 C13用于滤除直流电压输入端 Vin输入的电压中的杂讯信号。 所述限流电阻 R11用于在开关元件 Q11导通时， 起到限流保护的作用， 提高升 压变换器的安全性和耐用性。
本发明第一实施例和第二实施例的升压变换器均可被用液晶显示装置的电 路中， 用于对液晶显示装置的直流电压进行升压变换。
以上所述仅为本发明的实施例， 并非因此限制本发明的专利范围， 凡是利 用本发明说明书及附图内容所作的等效结构或等效流程变换， 或直接或间接运 用在其他相关的技术领域， 均同理包括在本发明的专利保护范围内。

Claims

1、 一种升压变换器， 其特征在于： 包括开关元件、 第一二极管、 第二二极 管、 第一电感、 第二电感、 第一电容、 直流电压输入端和直流电压输出端； 所 述直流电压输入端与直流电压输出端之间依次连接所述第一电感、 第二电感、 第一电容、 第二二极管； 所述第二二极管的阳极与第一电容连接， 阴极与直流 电压输出端连接； 所述开关元件包括第一端部、 第二端部和一用于控制所述第 一端部与第二端部导通与关断的第三端部， 所述第一端部连接在第一电感与第 二电感之间， 所述第二端部接地， 所述第三端部用于接收驱动信号； 所述第一 二极管的阴极与所述第二二极管的阳极连接， 第一二极管的阳极接地。
2、 一种升压变换器， 其特征在于， 包括开关元件、 第一二极管、 第二二极 管、 第一电感、 第二电感、 直流电压输入端和直流电压输出端； 所述直流电压 输入端与直流电压输出端之间依次连接所述第一电感、 第二电感、 第二二极管； 所述第二二极管的阳极与第二电感连接， 阴极与直流电压输出端连接； 所述开 关元件包括第一端部、 第二端部和一用于控制所述第一端部与第二端部导通与 关断的第三端部， 所述第一端部连接在第一电感与第二电感之间， 所述第二端 部接地， 所述第三端部用于接收驱动信号； 所述第一二极管的阴极与所述第二 二极管的阳极连接， 第一二极管的阳极接地。
3、 根据权利要求 2所述的升压变换器， 其特征在于： 所述升压变换器进一 步包括第一电容和第二电容， 所述第一电容连接于第二电感和第二二极管的阳 极之间， 所述第二电容的一端与直流电压输出端连接， 另一端接地。
4、 根据权利要求 3所述的升压变换器， 其特征在于： 所述升压变换器进一 步包括一连接于直流电压输入端和地之间的第三电容。
5、 根据权利要求 4所述的升压变换器， 其特征在于： 所述升压器还进一步 包括一限流电阻， 所述限流电阻的一端与第一二极管的阳极连接， 另一端接地。
6、 根据权利要求 2所述的升压变换器， 其特征在于： 所述开关元件为场效 应管， 其第一端部为漏极， 第二端部为源极， 第三端部为栅极。
7、 根据权利要求 2所述的升压变换器， 其特征在于： 所述第一电感与第二 电感为耦合电感， 所述第一电感的同名端与直流电压输入端连接， 异名端与第 二电感的同名端连接， 第二电感的异名端连接到上述第二二极管的阳极。
PCT/CN2011/076798 2011-05-19 2011-07-04 升压变换器 Ceased WO2012155382A1 (zh)

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WO2021035616A1 (zh) * 2019-08-29 2021-03-04 深圳市大疆创新科技有限公司 驱动电路、驱动电路板与驱动器

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5550458A (en) * 1994-05-31 1996-08-27 Lucent Technologies Inc. Low-loss snubber for a power factor corrected boost converter
CN101783588A (zh) * 2009-12-31 2010-07-21 杭州浙大太阳电气有限公司 无源无损箝位单相高增益变换器
CN201656768U (zh) * 2009-12-14 2010-11-24 浙江大学 耦合电感实现高增益倍压升压型变换器

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US5550458A (en) * 1994-05-31 1996-08-27 Lucent Technologies Inc. Low-loss snubber for a power factor corrected boost converter
CN201656768U (zh) * 2009-12-14 2010-11-24 浙江大学 耦合电感实现高增益倍压升压型变换器
CN101783588A (zh) * 2009-12-31 2010-07-21 杭州浙大太阳电气有限公司 无源无损箝位单相高增益变换器

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