WO2012061960A1 - 特定频率电流旁路的滤波器 - Google Patents

特定频率电流旁路的滤波器 Download PDF

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Publication number
WO2012061960A1
WO2012061960A1 PCT/CN2010/001945 CN2010001945W WO2012061960A1 WO 2012061960 A1 WO2012061960 A1 WO 2012061960A1 CN 2010001945 W CN2010001945 W CN 2010001945W WO 2012061960 A1 WO2012061960 A1 WO 2012061960A1
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WIPO (PCT)
Prior art keywords
filter
inductor
specific frequency
frequency current
inductance
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PCT/CN2010/001945
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English (en)
French (fr)
Inventor
吴卫民
Original Assignee
Wu Weimin
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Publication of WO2012061960A1 publication Critical patent/WO2012061960A1/zh

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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/42—Networks for transforming balanced signals into unbalanced signals and vice versa, e.g. baluns
    • H03H7/425—Balance-balance networks
    • H03H7/427—Common-mode filters
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/01—Frequency selective two-port networks
    • H03H7/17—Structural details of sub-circuits of frequency selective networks
    • H03H7/1741—Comprising typical LC combinations, irrespective of presence and location of additional resistors
    • H03H7/1758—Series LC in shunt or branch path

Definitions

  • the present invention relates to a grid-connected filter, and more particularly to a specific frequency current bypass filter for connecting a PWM converter device to a public grid (i.e., grid-connected).
  • the above low-pass filters mainly include three categories:
  • a first-order low-pass filter consisting of a single inductor.
  • the advantage of this filter is that the structure is simple, so the control of the PWM converter system is simple. However, to form sufficient attenuation of the switching subharmonics, the inductance of the inductor must be relatively large, and the volume and price are relatively high.
  • a second-order low-pass filter consisting of an inductor and a capacitor. This filter structure is relatively simple, and the corresponding converter system control is susceptible to changes in grid parameters while introducing additional reactive current. .
  • a third-order low-pass filter consisting of two inductors and one capacitor, LCL (inductor-inductor-capacitor) and improved. Because it is a third-order low-pass, it can form enough attenuation for the switching subharmonics, and the inductance of the inductor can be appropriately reduced; but the corresponding converter control is relatively complicated, and at the same time introduces additional reactive current.
  • LCL filters add inductance to the bypass
  • the purpose of adding this inductor is to reduce the power loss of the passive damping resistor connected in series with the capacitive branch of the LCL filter.
  • Other LCL filter designs In order to reduce the volume of the filter, the two inductors are simultaneously wound on the same core, so that an additional equivalent inductance is also formed on the capacitor branch.
  • the additional inductor does not take into account the resonant circuit that forms a specific frequency with the capacitor C, and is a low-impedance channel for the ripple current flowing through the main filter inductor; thus, the desired inductance is small, and additional Reactive power Small stream effect. Summary of the invention:
  • a filter for a specific frequency current bypass includes a main filter inductor and an auxiliary filter inductor, and is characterized in that it further comprises a specific frequency series resonant circuit composed of an inductor and a capacitor.
  • the series resonant frequency corresponds to the ripple current frequency flowing through the main filter inductor.
  • the series resonant frequency is the same as or similar to the ripple current flowing through the main filter inductor. Still further, the series resonant frequency is the same as or close to an integer multiple of the frequency of the ripple current flowing through the main filter inductor.
  • the main filter inductor, the auxiliary filter inductor, and the series resonant circuit may be variable inductors whose inductance can be adjusted.
  • the series resonant circuit capacitor described above is a variable capacitor whose capacitance can be adjusted.
  • the specific frequency current bypass filter provided by the present invention, because the above inductor and capacitor constitute a set series resonant circuit, and the series resonant frequency is the same as or similar to the ripple current flowing through the main filter inductor, or flows through The integer ripple of the main filter inductor's ripple current frequency is the same or similar, thus providing a low impedance path for the switching ripple current.
  • the specific frequency current bypass filter and the corresponding grid-connected PWM converter device can The following advantages are achieved:
  • the total inductance of the recommended solution is greatly reduced when the total distortion rate of the current injected into the grid is the same.
  • FIG. 1 is a circuit schematic diagram of a grid-connected filter of the present invention.
  • Figure 2 is a schematic circuit diagram of a first embodiment of the present invention.
  • Figure 3 is another schematic circuit diagram of the first embodiment of the present invention.
  • Figure 4 is a schematic circuit diagram of a second embodiment of the present invention.
  • Figure 5 is a schematic circuit diagram of a third embodiment of the present invention.
  • Figure 6 is a schematic circuit diagram of a fourth embodiment of the present invention.
  • Fig. 7 is a schematic circuit diagram of a fifth embodiment of the present invention.
  • Figure 8 is a schematic circuit diagram of a sixth embodiment of the present invention.
  • Figure 9 is a schematic circuit diagram of a seventh embodiment of the present invention.
  • Figure 10 is a schematic circuit diagram of an eighth embodiment of the present invention.
  • Figure 11 is a schematic circuit diagram of a ninth embodiment of the present invention.
  • Figure 12 is a schematic circuit diagram of a tenth embodiment of the present invention.
  • Figure 13 is a schematic circuit diagram of an eleventh embodiment of the present invention.
  • Figure 14 is a schematic circuit diagram of a twelfth embodiment of the present invention.
  • Figure 15 is a schematic circuit diagram of a thirteenth embodiment of the present invention.
  • Figure 16 is a schematic circuit diagram of a fourteenth embodiment of the present invention. The invention is further described below in conjunction with the drawings and specific embodiments.
  • FIG. 1 is a schematic diagram of the present invention.
  • the converter 1 receives power from other energy sources such as new clean energy sources (such as solar energy, fuel cells, wind energy, etc.) through the main filter inductor L1, an auxiliary filter inductor L2, and input to the public AC grid GRID;
  • the series resonant circuit composed of the inductor L3 and a capacitor C of a specific frequency has a series resonant frequency which is the same as or similar to the ripple current flowing through the main filter inductor L1, or a ripple current frequency flowing through the main filter inductor.
  • the integer multiples are the same or similar.
  • the main filter inductor L1, an auxiliary filter inductor L2, the resonant inductor L3 and the bypass capacitor C constitute a filter of the present invention having a specific frequency current bypass (series resonance circuit).
  • FIG. 2 is a schematic illustration of the filter of the first embodiment of Figure 1 of the present invention under normal use conditions.
  • the PWM converter can be regarded as a specific voltage source 1, and the main filter inductor L1, an auxiliary filter inductor L2, the inductor L3 and a capacitor C constitute the filter 2 of the present invention.
  • the present invention forms a specific current source by applying a feedback control and current adjustment to the main filter inductor current, and the voltage source 1 acts on the main filter inductor L1 to form a specific current source including a desired value and a specific frequency harmonic portion associated with the switching ripple.
  • the ripple current is bypassed by the resonant branch of the specific frequency filter 2, and only the desired value is partially
  • the flow is effectively injected into the public AC grid 3 (GRID) o
  • GRID public AC grid 3
  • Fig. 3 is a view showing another variation of the filter of the first embodiment shown in Fig. 1 of the present invention under normal use conditions.
  • the PWM converter can be regarded as a specific voltage source 1, and the main filter inductor L1, an auxiliary filter inductor L2, the inductor L3 and a capacitor C constitute the filter 2 of the present invention.
  • the present invention forms a specific current source by applying a feedback control and current adjustment to the auxiliary filter inductor current, and the voltage source 1 acts on the main filter inductor L1 to form a specific current source including a desired value and a specific frequency harmonic portion associated with the switching ripple.
  • the switching ripple current is bypassed by the resonant branch of the specific frequency filter 2, and only the desired portion of the current is effectively injected into the common AC grid 3 (GRID) o
  • Figure 4 is a schematic circuit diagram of a second embodiment of the present invention. Compared with the first embodiment, the difference is that the main filter inductor is composed of inductors L11 and L12, and the auxiliary inductor is composed of inductors L21 and L22, and inductors L11 and L12 are respectively connected in series with the series resonant circuit, inductors L21 and L22. Also in series with the series resonant circuit. The series resonant circuit is still composed of the resonant inductor L3 and the capacitor C.
  • FIG. 5 is a schematic circuit diagram of a third embodiment of the present invention. Compared with the first embodiment, the difference is that the auxiliary filter inductor L2 is connected in parallel with a resistor RP2, and the series resonance circuit is still composed of the resonant inductor L3 and the capacitor C.
  • Figure 6 is a schematic circuit diagram of a fourth embodiment of the present invention. Compared with the first embodiment, the difference is that the resonant inductor L3 employs an adjustable inductance.
  • Fig. 7 is a schematic circuit diagram of a fifth embodiment of the present invention.
  • the difference is that the resonant capacitor C employs an adjustable capacitance.
  • Figure 8 is a schematic circuit diagram of a sixth embodiment of the present invention. In contrast to the first embodiment, the difference is that the auxiliary filter inductor L2 employs an adjustable inductance.
  • Figure 9 is a schematic circuit diagram of a seventh embodiment of the present invention. Compared with the first embodiment, the difference is that the vibration inductance L3 is connected in parallel with a resistor RP3.
  • FIG. 10 is a schematic circuit diagram of an eighth embodiment of the present invention. Compared with the first embodiment, the difference is that the bypass capacitor C is connected in parallel with a resistor RPC.
  • FIG 11 is a schematic circuit diagram of a ninth embodiment of the present invention. Compared with the first embodiment, the difference is that the bypass capacitor C is connected in series with a resistor RS.
  • Figure 12 is a schematic circuit diagram of a tenth embodiment of the present invention. Compared with the first embodiment, the difference The auxiliary filter inductor L2 is replaced by the leakage inductance of the grid-connected transformer T.
  • Figure 13 is a schematic circuit diagram of an eleventh embodiment of the present invention. Compared with the first embodiment, the difference is that the auxiliary filter inductor L2 is replaced by the leakage inductance of the grid-connected transformer T, and the resonance branch is connected in series with a resistor Rs.
  • Figure 14 is a schematic circuit diagram of a twelfth embodiment of the present invention. Compared with the first embodiment, the difference is that the main filter inductor L1 is a variable inductor.
  • the above embodiments are all in the case of two-phase current. Also, it can be applied to three-phase currents.
  • a variable inductor or a variable capacitor it is easier to adjust the resonant frequency of the series resonant circuit to be the same as or close to the ripple current flowing through the main filter inductor, or the ripple flowing through the main filter inductor.
  • the integer multiples of the current frequency are the same or similar.
  • passive damping can be used to prevent system resonance.
  • FIG. 15 is a schematic circuit diagram of a thirteenth embodiment of the present invention.
  • Lai is the main filter inductor
  • La2 is the auxiliary filter inductor
  • La3 is the resonant inductor
  • Ca is the bypass capacitor, which constitutes a filter in one phase, wherein The resonant inductor La3 and the bypass capacitor Ca constitute a series resonant circuit of the filter of the present invention.
  • Lbl is the main filter inductor
  • Lb2 is the auxiliary filter inductor
  • Lb3 is the resonant inductor
  • Cb is the bypass capacitor, which constitutes the filter in the phase, where the resonant inductor Lb3 and the bypass capacitor Cb A series resonant circuit constituting the filter of the present invention.
  • Lcl is the main filter inductor
  • Lc2 is the auxiliary filter inductor
  • 1x3 is the resonant inductor
  • Cc is the bypass capacitor, which constitutes the filter in the phase, wherein the resonant inductor 1x3 and the bypass capacitor Cc constitute the present A series resonant circuit of the inventive filter.
  • FIG 16 is a schematic circuit diagram of a fourteenth embodiment of the present invention.
  • the three-phase current circuit is applied in a delta connection
  • Lai is a main filter inductor
  • La2 is an auxiliary filter inductor
  • La3 is a resonant inductor
  • Ca is a bypass capacitor, which constitutes a filter in one phase, wherein The resonant inductor La3 and the bypass capacitor Ca constitute a series resonant circuit of the filter of the present invention.
  • Lbl is the main filter inductor
  • Lb2 is the auxiliary filter inductor
  • Lb3 is the resonant inductor
  • Cb is the bypass capacitor, which constitutes the filter in the phase, where the resonant inductor Lb3 and the bypass capacitor Cb A series resonant circuit constituting the filter of the present invention.
  • Lcl is the main filter inductor
  • 1x2 is the auxiliary filter inductor
  • 1x3 is the resonant inductor
  • Cc is the bypass capacitor, which constitutes the filter in the phase, where the resonant inductor Lc3 and bypass capacitor Cc constitute a series resonant circuit of the filter of the present invention.
  • the auxiliary filter inductor may be composed of a transformer leakage inductance or a grid equivalent inductance.
  • the physical position of the inductor and capacitor on the branch of the series resonant circuit can be reversed.
  • the filter of each phase circuit can adopt the second embodiment to the twelfth embodiment of FIGS. 4 to 14. a circuit. It is not listed here.

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  • Dc-Dc Converters (AREA)
  • Supply And Distribution Of Alternating Current (AREA)

Description

特定频率电流旁路的滤波器 技术领域：
本发明涉及一种并网滤波器， 特别涉及一种连接 PWM变流器装置与公共 电网 （即并网） 的特定频率电流旁路滤波器。
背景技术：
随着社会经济的发展， 传统能源日益紧张， 新型清洁能源（如太阳能、 燃 料电池、 风能等）发电技术越来越受到人们的关注， 但是， 这些再生能源在并 网发电时就需要 DC/AC变流器进行直流 /交流电压变换。 同时考虑到 "绿色" 电网的要求， PWM (脉冲宽度调整）整流， PFC (功率因数校正） 电路， 有源 电力滤波器等装置的使用也越来越普遍。这些电力电子变换装置与公共电网之 间一般要通过一个低通滤波器相连接， 防止过量开关次电流谐波注入公共电 网。
目前， 上述低通滤波器主要包括三类：
1、 单电感组成的一阶低通滤波器。 这种滤波器优点在于结构简单， 因而 组成 PWM变流器系统控制简单。但要对开关次谐波形成足够衰减， 电感的电 感量必须比较大， 体积和价格都相对很高。
2、 一个电感与一个电容组成的二阶低通滤波器。 这种滤波器结构相对简 单， 相应的变流器系统控制容易受电网参数变化的影响， 同时引入额外的无功 电流。 .
3、 由两个电感与一个电容组成的 LCL (电感-电感-电容） 的三阶低通滤 波器以及改进型。 由于是三阶低通， 能对开关次谐波形成足够衰减， 电感的电 感量可适当减少； 但相应的变流器控制相对复杂， 同时引入额外的无功电流。
另外， 虽然也有些 LCL滤波器在旁路上增加了电感， 但是， 增加该电感 的目的是为了降低 LCL滤波器的电容支路所串接的无源阻尼电阻的功率损耗; 另有些 LCL滤波器设计者为了减少滤波器的体积， 将两个电感同时绕接在同 一磁芯上， 这样在电容支路上也会形成的附加等效电感。 以上两种情况， 附加 的电感都并没有考虑到与电容 C形成一特定频率的谐振电路，为流过主滤波电 感的纹波电流低阻抗通道； 因而不能实现期望的电感量小、 附加额外的无功电 流小的功效。 发明内容：
本发明的目的是提供一种电感量小、附加额外的无功电流小且成本低的特 定频率电流旁路滤波器， 以便克服现有技术的上述连接电网与 PWM变流器之 间的低通滤波器所存在的不足。
为了实现上述发明目的， 本发明所提供的特定频率电流旁路的滤波器， 包 括一主滤波电感、一辅助滤波电感， 其特征在于还包括一由电感和一电容组成 的特定频率串联谐振电路，其串联谐振频率与流过主滤波电感的紋波电流频率 相对应。
进一步，所述串联谐振频率与流过主滤波电感的纹波电流频率相同或相近。 再进一步， 所述串联谐振频率与流过主滤波电感的纹波电流频率的整数倍 相同或相近。
而且， 上述主滤波电感、 辅助滤波电感、 串联谐振电路可以是电感量可以 调节的可变电感。 上述串联谐振电路电容是电容量可以调节的可变电容。
本发明提供的特定频率电流旁路滤波器， 由于上述电感和电容组成了一设 定的串联谐振电路，并且串联谐振频率与流过主滤波电感的紋波电流频率相同 或相近， 或是流过主滤波电感的纹波电流频率的整数倍相同或相近， 从而为开 关纹波电流提供了低阻抗通道，根据上述技术方案得到的特定频率电流旁路滤 波器以及相应并网 PWM变流器装置能够达到下述优点：
1、 与传统 L型滤波器相比， 在注入电网的电流的总畸变率要求相同的前 提下， 推荐方案的电感总容量大为下降。
2、 与传统 LC或 LCL滤波器相比， 在注入电网的电流的总畸变率要求相 同的前提下， 推荐方案的电感总容量下降； 附加的额外无功电流大为减少。 附图说明
图 1为本发明的并网滤波器的电路原理图。
图 2是本发明的第一实施例的一个示意电路图。
图 3是本^：明的第一实施例的另一个示意电路图
图 4是本发明的第二实施例的示意电路图。 图 5是本发明的第三实施例的示意电路图。
图 6是本发明的第四实施例的示意电路图。
图 7是本发明的第五实施例的示意电路图。
图 8是本发明的第六实施例的示意电路图。
图 9是本发明的第七实施例的示意电路图。
图 10是本发明的第八实施例的示意电路图。
图 11是本发明的第九实施例的示意电路图。
图 12是本发明的第十实施例的示意电路图。
图 13是本发明的第十一实施例的示意电路图。
图 14是本发明的第十二实施例的示意电路图。
图 15是本发明的第十三实施例的示意电路图。
图 16是本发明的第十四实施例的示意电路图。 以下结合附图和具体实施例来进一步说明本发明。
具体实施方式
图 1是本发明的原理图。 在三相电流的情况， 通常有三个电路， 而在两相 电流的情况， 有一个相电路。 在每一相电流电路中， 变流器 1接收其他能源例 如新型清洁能源 （如太阳能、 燃料电池、 风能等） 的电源通过主滤波电感 Ll、 一辅助滤波电感 L2、 输入到公共交流电网 GRID; 另外， 由电感 L3和一电容 C组成一特定频率的串联谐振电路， 其串联谐振频率与流过主滤波电感 L1的 紋波电流频率相同或相近，或与流过主滤波电感的纹波电流频率的整数倍相同 或相近。上述主滤波电感 Ll、一辅助滤波电感 L2、谐振电感 L3和旁路电容 C 构成本发明的滤波器， 它具有特定频率电流旁路 （串联谐振电路）。
图 2是本发明的图 1所示的第一实施例的滤波器在正常使用条件下的一个 示意图。 PWM变流器可视为一个特定的电压源 1， 主滤波电感 L1、 一辅助滤 波电感 L2、 电感 L3和一电容 C组成本发明的滤波器 2。 本发明通过对主滤波 电感电流的反馈控制和电流调节， 电压源 1作用于主滤波电感 L1形成一个特 定的电流源， 该电流源包含期望值以及与开关纹波相关的特定频率谐波部分， 开关紋波电流通过特定频率滤波器 2的谐振支路被旁路，而只有期望值部分电 流被有效注入公共交流电网 3 (GRID)o
图 3是本发明的图 1所示的第一实施例的滤波器在正常使用条件下的另一 变化的示意图。 PWM变流器可视为一个特定的电压源 1， 主滤波电感 Ll、 一 辅助滤波电感 L2、 电感 L3和一电容 C组成本发明的滤波器 2、。 本发明通过对 辅助的滤波电感电流的反馈控制和电流调节， 电压源 1作用于主滤波电感 L1 形成一个特定的电流源，该电流源包含期望值以及与开关纹波相关的特定频率 谐波部分， 开关纹波电流通过特定频率滤波器 2的谐振支路被旁路， 而只有期 望值部分电流被有效注入公共交流电网 3 (GRID)o
图 4是本发明的第二实施例的示意电路图。 与第一实施例相比， 其区别在 于所述主滤波电感由电感 L11和 L12组成， 辅助电感由电感 L21和 L22组成 其中， 电感 L11和 L12分别与所述串联谐振电路串联， 电感 L21和 L22也分 别与所述串联谐振电路串联。 而串联谐振电路仍然由谐振电感 L3和电容 C组 成。
图 5是本发明的第三实施例的示意电路图。 与第一实施例相比， 其区别在 于所述辅助滤波电感 L2与一电阻 RP2并联， 而串联谐振电路仍然由谐振电感 L3和电容 C组成。
图 6是本发明的第四实施例的示意电路图。与第一实施例相比， 其区别在 于所述谐振电感 L3采用一可调节电感。
图 7是本发明的第五实施例的示意电路图。与第一实施例相比， 其区别在 于所述谐振电容 C采用一可调节电容。
图 8是本发明的第六实施例的示意电路图。与第一实施例相比， 其区别在 于所述辅助滤波电感 L2采用一可调节电感。
图 9是本发明的第七实施例的示意电路图。与第一实施例相比， 其区别在 于所述振电感 L3与一电阻 RP3并联。
- 图 10是本发明的第八实施例的示意电路图。 与第一实施例相比， 其区别 在于所述旁路电容 C与一电阻 RPC并联。
图 11是本发明的第九实施例的示意电路图。 与第一实施例相比， 其区别 在于所述旁路电容 C与一电阻 RS串联。
图 12是本发明的第十实施例的示意电路图。 与第一实施例相比， 其区别 在于所述辅助滤波电感 L2由并网变压器 T的漏感代替。
图 13是本发明的第十一实施例的示意电路图。 与第一实施例相比， 其区 别在于所述辅助滤波电感 L2由并网变压器 T的漏感代替， 且谐振支路串联一 电阻 Rs。
图 14是本发明的第十二实施例的示意电路图。 与第一实施例相比， 其区 别在于所述主滤波电感 L1是可变电感
上述实施例都是在两相电流的情况。 同样， 在三相电流中也可以适用。 上述通过采用可变电感或和可变电容，使得更加容易使串联谐振电路的谐 振频率调整到与流过主滤波电感的纹波电流频率相同或相近，或是流过主滤波 电感的紋波电流频率的整数倍相同或相近。
另外， 通过在电感或电容上并联或串联电阻， 可以起到无源阻尼的作用， 防止系统谐振。
图 15是本发明的第十三实施例的示意电路图。 在该实施例应用在星形接 法的三相电流电路中， Lai为主滤波电感、 La2为辅助滤波电感、 La3为谐振 电感， Ca为旁路电容， 它们构成一相中的滤波器， 其中， 谐振电感 La3和旁 路电容 Ca构成本发明的滤波器的串联谐振电路。 同样， 在另一相中， Lbl为 主滤波电感、 Lb2为辅助滤波电感、 Lb3为谐振电感， Cb为旁路电容， 它们构 成该相中的滤波器， 其中， 谐振电感 Lb3和旁路电容 Cb构成本发明的滤波器 的串联谐振电路。 在第三相中， Lcl为主滤波电感、 Lc2为辅助滤波电感、 1x3 为谐振电感， Cc为旁路电容， 它们构成该相中的滤波器， 其中， 谐振电感 1x3 和旁路电容 Cc构成本发明的滤波器的串联谐振电路。
图 16是本发明的第十四实施例的示意电路图。 在该实施例应用在三角形 接法的三相电流电路中， Lai为主滤波电感、 La2为辅助滤波电感、 La3为谐 振电感， Ca为旁路电容， 它们构成一相中的滤波器， 其中， 谐振电感 La3和 旁路电容 Ca构成本发明的滤波器的串联谐振电路。 同样， 在另一相中， Lbl 为主滤波电感、 Lb2为辅助滤波电感、 Lb3为谐振电感， Cb为旁路电容， 它们 构成该相中的滤波器， 其中， 谐振电感 Lb3和旁路电容 Cb构成本发明的滤波 器的串联谐振电路。 在第三相中， Lcl为主滤波电感、 1x2为辅助滤波电感、 1x3为谐振电感， Cc为旁路电容， 它们构成该相中的滤波器， 其中， 谐振电感 Lc3和旁路电容 Cc构成本发明的滤波器的串联谐振电路。
在本发明的特定频率电流旁路的滤波器，上述辅助滤波电感可由变压器漏 感或电网等效电感组成。 另外， 上述串联谐振电路支路上的电感和电容的物理 位置可以对调。 对本领域的技术人员来说， 在上述实施例第十三与第十四实施例中， 每一 相电路的滤波器可以采用图 4到图 14的第二实施例到第十二实施例的任一电 路。 这里就不再列举。
通过以上描述， 可以发现， 本发明的发明人由于通过研究， 发现了只有通 过在电流旁路上设置由电感和电容组成的串联谐振电路，并且使得该串联谐振 电路的谐振频率与流过主滤波电感的紋波电流频率相同或相近，或是流过主滤 波电感的紋波电流频率的整数倍相同或相近，才能为开关紋波电流提供一低阻 抗通道， 从而有效地减少电感总容量并使附加的额外无功电流大为减少， 从而 大大地减少料设备成本， 达到了很好的技术效果。
以上显示和描述了本发明的基本原理和主要特征和本发明的优点。本领域 的技术人员应该了解， 本发明不受上述具体实施例的限制， 上述实施例和说明 书中描述的只是说明本发明的原理， 在不脱离本发明精神和范围的前提下， 本 发明还会有各种变化和改进， 这些变化和改进都落入要求保护的本发明范围 内。

Claims

权利要求
1、 一特定频率电流旁路的滤波器， 包括一主滤波电感、 一辅助滤波电感， 其 特征在于还包括一由电感和一电容组成的特定频率串联谐振电路，其串联谐振 频率与流过主滤波电感的纹波电流频率相对应。
2、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振频率与流过主滤波电感的纹波电流频率相同或相近。
3、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振频率与流过主滤波电感的纹波电流频率的整数倍相同或相近。
4、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路的电感是可变电感。
5、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路的电容是可变电容。
6、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路的电容并联一电阻。
7、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路的电感并联一电阻。
8、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路支路上串联一电阻。
9、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于主滤波电感 是可变电感。
10、如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于辅助滤波电 感是可变电感。
11、如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述主滤波 电感并联一电阻。
12、如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述辅助滤 波电感并联一电阻。
13、如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述主滤波 电感由两个分别与所述串联谐振电路的两端串联的电感组成。
14、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述辅助滤 波电感由两个分别与所述串联谐振电路的两端串联的电感组成。
15、 如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述辅助滤 波电感可由变压器漏感或电网等效电感组成。
16、如权利要求 1所述的特定频率电流旁路的滤波器， 其特征在于所述串联谐 振电路支路上的电感和电容的物理位置可以对调。
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