WO2011060697A1 - 动态色散检测方法及装置 - Google Patents

动态色散检测方法及装置 Download PDF

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Publication number
WO2011060697A1
WO2011060697A1 PCT/CN2010/078608 CN2010078608W WO2011060697A1 WO 2011060697 A1 WO2011060697 A1 WO 2011060697A1 CN 2010078608 W CN2010078608 W CN 2010078608W WO 2011060697 A1 WO2011060697 A1 WO 2011060697A1
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Prior art keywords
value
electrical signal
dispersion
ratio
radio frequency
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PCT/CN2010/078608
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English (en)
French (fr)
Inventor
喻德忠
孟凡明
谢俊波
徐昱
曾嘉宏
邓彬林
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华为技术有限公司
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Publication of WO2011060697A1 publication Critical patent/WO2011060697A1/zh
Priority to US13/476,653 priority Critical patent/US9071355B2/en

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B10/00—Transmission systems employing electromagnetic waves other than radio-waves, e.g. infrared, visible or ultraviolet light, or employing corpuscular radiation, e.g. quantum communication
    • H04B10/25—Arrangements specific to fibre transmission
    • H04B10/2507—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion
    • H04B10/2513—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion due to chromatic dispersion
    • H04B10/25133—Arrangements specific to fibre transmission for the reduction or elimination of distortion or dispersion due to chromatic dispersion including a lumped electrical or optical dispersion compensator

Definitions

  • the present invention relates to the field of communications technologies, and in particular, to a dynamic dispersion detection method and apparatus. Background technique
  • the dispersion tolerance is inversely proportional to the bit rate. As the transmission rate increases, the dispersion tolerance of the system decreases rapidly. In the future intelligent global communication network, the channel of each node is switched on and off. The more complex, the receiver can not predict the specific path of the optical signal, so the link dispersion has uncertainty, the residual dispersion value easily exceeds the dispersion tolerance of the system, which has a serious impact on system performance, so how to economically and effectively dynamic the system dispersion Compensation has become a hot topic of research.
  • bit error rate performance bit error rate (BER, Bi t Error Ra io ) generated after the service is connected is used to dynamically compensate the system dispersion, and the specific contents are as follows:
  • the coarse adjustment of the dispersion compensation is performed by the TDC (Tunable Diversation Compensa tor), and the optical receiving module performs signal demodulation while performing coarse adjustment of the dispersion compensation, and the like.
  • Demodulation of the signal is completed when the system dispersion falls within the dispersion window that the light receiving module can receive;
  • the TDC coarse adjustment After the service is connected, stop the TDC coarse adjustment, collect the BER of the system, and feed back to the TDC.
  • the TDC fine-tunes the TDC according to the BER of the system until the feedback BER is minimum for a period of time.
  • the TDC value at this time can be considered as the best system.
  • the dispersion compensation value therefore, the dispersion dynamic compensation can be completed.
  • the BER needs to be adjusted under the condition that the error can be sent after the service is passed, and the adjustment time is slower and increased. Added time for system communication.
  • the technical problem to be solved by the embodiments of the present invention is to provide a dynamic dispersion detection method and device, which can detect the optimal dispersion of the system and effectively improve the system performance.
  • an embodiment of the present invention provides a dynamic dispersion detecting apparatus, including: a tunable dispersion compensation adjuster, a demodulator, a receiver, a partial band RF power detecting unit, and an electrical signal ratio calculation.
  • the received optical signal is sent to the demodulator;
  • the demodulator performs phase demodulation on the received optical signal
  • the receiver converts the optical signal output by the demodulator into an electrical signal
  • a partial band RF power detecting unit performs radio frequency power sampling on the electrical signal obtained by the receiver conversion to obtain a radio frequency signal
  • the electrical signal ratio calculating unit obtains an electrical signal ratio of the radio frequency signal, and continuously transmits the electrical signal ratio to the adjustable dispersion compensation adjuster;
  • the tonable dispersion compensation adjuster compares the value of the currently received electrical signal ratio with the value of the previously received electrical signal, and adjusts the dispersion compensation value according to the comparison result to obtain a peak value of the electrical signal ratio, according to the The peak value of the electrical signal ratio determines the residual dispersion value of the system.
  • a dynamic dispersion detection method including:
  • the optical signal is converted into an electrical signal, the electrical signal ratio peak value is sought, and the residual dispersion value of the system is obtained according to the electrical signal ratio peak value.
  • the dispersion value corresponding to the peak value of the electrical signal is the best residual of the system. The dispersion value, therefore, the optimal residual dispersion value of the system can be detected. Since the pulse width of the electrical signal ratio is narrower, it is easier to find the peak value and use the electrical signal.
  • the accuracy is higher, the accuracy of the residual dispersion of the detection system can be improved, and the detected residual residual dispersion can be further applied to the dispersion compensation, so that the problem that the signal misses the optimal window of the system dispersion can be avoided, and the problem can be improved.
  • FIG. 1 is a system block diagram of a dynamic dispersion detecting apparatus according to an embodiment of the present invention
  • FIG. 2 is a flowchart of a method for detecting dynamic dispersion according to an embodiment of the present invention
  • Figure 3 is a graph showing the relationship between signal amplitude and cumulative dispersion d
  • Figure 4 is a simulation curve of the electrical signal spectrum under different dispersion values
  • FIG. 5 is a structural diagram of a partial band RF power detecting unit according to an embodiment of the present invention
  • FIG. 6 is a structural diagram of a tonable dispersion compensation adjuster according to an embodiment of the present invention.
  • the dispersion detection technology and compensation have a core position.
  • the range and accuracy of the dispersion detection directly determine the range and accuracy of the dynamic dispersion compensation system.
  • the complexity also directly determines the total cost of the compensation system, above 40Gbp s.
  • the optical module has low dispersion tolerance, requires dispersion compensation, and how to find the best dispersion point, which becomes the key technology of dynamic dispersion compensation.
  • Embodiments of the present invention provide a dynamic dispersion detection method and apparatus, which can detect the optimal dispersion of the system and effectively improve system performance.
  • the dynamic dispersion detecting apparatus provided by the embodiment of the invention includes:
  • a tunable dispersion compensation regulator a demodulator, a receiver, a partial band RF power detecting unit, an electrical signal ratio calculating unit;
  • the received optical signal is sent to the demodulator;
  • a demodulator that performs phase demodulation on the received optical signal
  • a receiver converting the optical signal output by the demodulator into an electrical signal
  • a partial band RF power detecting unit performs RF power sampling on the electrical signal obtained by converting the receiver to obtain a radio frequency signal
  • the electrical signal ratio calculating unit obtains an electrical signal ratio of the radio frequency signal, and continuously transmits the electrical signal ratio to the tonable dispersion compensation adjuster;
  • the ratio of the electrical signal to the electrical signal obtained by the computing unit is a ratio of the radio frequency peak to the radio frequency valley of the radio frequency signal detected over a predetermined period of time.
  • the tonable dispersion compensation adjuster compares the value of the currently received electrical signal ratio with the value of the previously received electrical signal, adjusts the dispersion compensation value according to the comparison result, and finds the peak value of the electrical signal ratio, according to the electrical The peak of the signal ratio determines the residual dispersion value of the system.
  • the dynamic dispersion detecting apparatus converts an optical signal into an electrical signal, searches for an electrical signal ratio peak value, and then obtains a residual dispersion value of the system according to the electrical signal ratio peak value, and the dispersion value corresponding to the peak value of the electrical signal is the system The best residual dispersion value, so the optimal residual dispersion value of the system can be detected. Since the pulse width of the electrical signal ratio is narrower, it is easier to find the peak value, and the electrical signal ratio is used to confirm the optimum residual dispersion value, and the accuracy is high.
  • the accuracy of the residual dispersion of the detection system can be improved, and the detected residual residual dispersion can be further applied to the dispersion compensation, thereby avoiding the problem that the signal misses the optimal window of the system dispersion, improving the reliability, and not waiting for the service to pass. Adjustments are made under the condition of error code, which speeds up the time of system communication.
  • FIG. 1 is a system block diagram of a dynamic dispersion detecting apparatus according to an embodiment of the present invention, including: a TDCM (TDC Modulation) (101), a demodulator (Demona tor) 102, and a receiver 103. , a partial frequency band radio frequency (RF, Radio Frequency) power detecting unit 104, an electrical signal ratio (ESR, Elect ri ca lsi gna l Ra t io ) calculating unit 105.
  • TDCM TDC Modulation
  • RF Radio Frequency
  • ESR Electrical signal ratio
  • the tunable dispersion compensation adjuster 101 After receiving the optical signal, the tunable dispersion compensation adjuster 101 performs the received optical signal first. Dispersion compensation, and then the optical signal is sent to the demodulator 102.
  • the tunable dispersion compensation adjuster 101 has an initial dispersion compensation value, which can be preset by the user according to experience. System presets can be used.
  • phase demodulation of the optical signal is completed.
  • the receiver 103 is a photoelectric conversion portion, and mainly performs conversion of an optical signal output from the demodulator 102 into an electrical signal.
  • the partial band RF power detecting unit 104 is configured to sample a certain frequency band of the converted electrical signal, calculate the RF power in a part of the frequency band of the converted electrical signal, and mainly complete the RF power sampling of the electrical signal, and deliver the subsequent electrical signal ratio.
  • the computing unit 105; the main components constituting the partial band RF power detecting unit 104, may be a power detector and a partial filtering circuit.
  • the electrical signal ratio calculating unit 105 is mainly responsible for the logic processing portion, and is mainly used for calculating the ESR value of the RF signal detected by the partial band RF power detecting unit 104.
  • the value of the ESR is equal to the ratio of the RF peak obtained by detecting the RF signal to the RF valley value.
  • the ESR value 1 ⁇ peak/RF valley value; the process of calculating the ESR value is a continuous calculation process, and the ESR value of different time periods can be obtained with time, and then the calculated ESR value is continuously given to the adjustable
  • the dispersion compensation adjuster 101; the electrical signal ratio calculation unit 105 can be implemented using a microprogram controller (MCU) or a field programmable gate array (FPGA, Field Programmab le Ga te Array) device. .
  • MCU microprogram controller
  • FPGA Field Programmab le Ga te Array
  • the tunable dispersion compensation adjuster 101 After receiving the ESR value obtained by the calculation unit 105, the tunable dispersion compensation adjuster 101 compares the currently received ESR value with the previously received ESR value, and if the received ESR value continues to rise, continues Adjusting the dispersion compensation value, when the received ESR value begins to decrease, it can be confirmed that the ESR value of the previously received ESR value has already appeared, that is, the received ESR maximum value, and the dispersion value corresponding to the ESR maximum value is the system.
  • the optimal residual dispersion value therefore, the residual dispersion value of the system can be confirmed according to the ESR peak value. Further, the system residual dispersion compensation can be performed in time according to the residual dispersion value, and the adjustment of the dispersion compensation value is stopped.
  • the way to confirm the ESR peak value may be that when the received ESR value is smaller than the previous ESR value, the previous ESR value is considered to be the ESR peak value, or the ESR value may continue to decrease for a period of time.
  • the maximum ESR to be reached is the ESR peak to avoid errors caused by jitter in the ESR value.
  • the partial band RF power detecting unit may include:
  • a squarer that squares the electrical signal
  • a low pass filter that performs low pass filtering on the result of the squarer operation
  • the mean square value is obtained by filtering the result of the low pass filter
  • An analog to digital converter that performs analog to digital conversion on the RF signal.
  • this is an embodiment in which a radio frequency signal is obtained to implement a partial band RF power detecting unit, and other device configurations for obtaining a radio frequency signal can also be used.
  • the above is a description of the dynamic dispersion detecting apparatus provided by the embodiment of the present invention.
  • the specific principle of the dynamic dispersion detecting apparatus provided by the embodiment of the present invention is analyzed by the principle principle.
  • the description of the dynamic dispersion detecting method provided by the embodiment of the present invention can be referred to below.
  • the flow of the dynamic dispersion detection method provided by the embodiment of the present invention is as shown in FIG. 2, and includes:
  • an electrical signal ratio of the radio frequency signal the ratio of the radio frequency peak to the radio frequency valley of the radio frequency signal detected for a predetermined period of time, that is, the ESR value RF peak value / RF valley value; the process of calculating the ESR value is a continuous
  • the process of calculation, the ESR value of different time periods can be obtained as time changes.
  • the dispersion compensation value is continuously adjusted, and when the received ESR value begins to decrease, It can be confirmed that the ESR value received before has already reached the peak value of the ESR value, that is, the received ESR maximum value, and the dispersion value corresponding to the ESR maximum value is the optimal residual dispersion value of the system, so the residual of the system can be confirmed according to the ESR peak value. Dispersion value.
  • the way to confirm the ESR peak value may be that when the received ESR value is smaller than the previous ESR value, the previous ESR value is considered to be the ESR peak value, or the ESR value may continue to decrease for a period of time.
  • the maximum ESR to be reached is the ESR peak to avoid errors caused by jitter in the ESR value.
  • the residual dispersion value can be used to perform system residual dispersion compensation in time.
  • the dynamic dispersion detection method provided by the embodiment of the invention converts an optical signal into an electrical signal, searches for an electrical signal ratio peak value, and then obtains a residual dispersion value of the system according to the electrical signal ratio peak value, because the dispersion value corresponding to the electrical signal ratio peak is the system The best residual dispersion value, so the optimal residual dispersion value of the system can be detected. Since the pulse width of the electrical signal ratio is narrower, it is easier to find the peak value, and the electrical signal ratio is used to confirm the optimum residual dispersion value, and the accuracy is high.
  • the accuracy of the residual dispersion of the detection system can be improved, and the detected residual residual dispersion can be further applied to the dispersion compensation, thereby avoiding the problem that the signal misses the optimal window of the system dispersion, improving the reliability, and not waiting for the service to pass. Adjustments are made under the condition of error code, which speeds up the time of system communication.
  • the demodulator 102 receives an optical signal, and the different frequency components of the signal transmitted by the optical fiber or the group speeds of different mode components are different, and the same distance will have different delays, causing a transmission signal.
  • Distortion mainly the broadening of the pulse; the transmitted signal is regarded as a Gaussian pulse, and T is set.
  • T is the signal width in the signal time domain, and T will gradually increase as the transmission I increases.
  • Equation 1 Equation 1
  • the signal width ⁇ is broadened, which causes the amplitude of the signal power u to decrease.
  • Equation 3 The transmission distances z and 2 in the equation are represented by the cumulative dispersion d, which can be expressed as Equation 3:
  • the cumulative dispersion d broadens the signal pulse from the time domain, and its broadening depends on the cumulative dispersion d.
  • the relationship between the signal amplitude and the cumulative dispersion d is shown in Fig. 3:
  • Curve S 1 is a signal normalized amplitude curve with cumulative dispersion Ops /nm
  • curve S2 is a signal normalized amplitude curve with cumulative dispersion 68 ps /nm
  • curve S 3 is cumulative dispersion The signal normalized amplitude curve at 136 ps/nm.
  • the electric power detection is to detect the power of the optical pulse signal to output an electric signal through the photodetecting device
  • the receiver 103 is a photoelectric detecting device.
  • Chromatic dispersion causes the light pulses transmitted in the fiber to broaden in the time domain, but does not affect the spectrum of the light pulse, but only changes the phase of each spectral component.
  • the receiver 103 detects the intensity of the input optical signal, ignores the phase change of the optical signal, and changes the input optical pulse into an electrical pulse.
  • the frequency spectrum of the electrical pulse narrows as the envelope of the optical pulse broadens, resulting in electrical power at a given frequency point. The value varies with the chromaticity dispersion.
  • the receiver 103 converts the received optical signal into an electrical signal to effectively convert the incident optical power into a photocurrent.
  • the optical power to the photodetector, IP is the photocurrent generated.
  • the optical power Po is proportional to the square of the magnitude of the optical pulse envelope U(z, T). Therefore, when the input optical signal is the light given by Equation 2 Formula 4
  • Equation 5 can also obtain the spectrum of the electrical signal I ( d, T ), and the spectrum of the electrical signal I ( d, T ) can be expressed as a formula Equation 6 It can be seen from Equation 6 that although the chromatic dispersion does not affect the spectrum of the optical pulse signal, it can change the spectrum of the electrical signal. Therefore, by analyzing the relationship between the cumulative dispersion value and the spectrum of the electrical signal, the magnitude of the cumulative chromatic dispersion value in the optical fiber communication system can be obtained by detecting the spectrum of the electrical signal.
  • Figure 4 is a simulation curve of the electric signal spectrum under different dispersion values.
  • the curve HI is the simulation curve of the electric signal spectrum with cumulative dispersion Ops/nm; the curve H2 is the simulation curve of the electric signal spectrum with the cumulative dispersion 68ps/nm.
  • Curve H3 is a simulation curve of the electrical signal spectrum with cumulative dispersion of 136 ps/nm.
  • ESR is used as a feedback signal for dynamic chromatic dispersion compensation to monitor the variation of cumulative dispersion in a fiber-optic communication system and to control the compensation amount of the dynamic chromatic dispersion compensation device.
  • the structure of the partial band RF power detecting unit 104 provided by the embodiment of the present invention is as shown in FIG. 5, and includes: a squarer 501, a low-pass filter (LPF) 502, and a mean square (RMS) unit. 503, an amplifier (AMP, Amplifier) 504, an analog to digital converter (AD converter) 505.
  • the squarer 501, the low pass filter 502, the squarer 503, and the amplifier 504 constitute a power detector, and the detection of the electric power is mainly performed by the power detector.
  • the electrical signal Xi After the electrical signal Xi enters the power detector, it is first squared by the squarer 501, that is, X 2 ; the signal Xi is the square of the optical signal U(z, T);
  • the LPF filtering process is then performed by the low pass filter 502;
  • the output RF is amplified by the amplifier 504 having a gain of G.
  • Ut can use formula expression
  • Analog to digital converter 505 receives the RF. After ut , it is subjected to analog-to-digital conversion, and a digital signal is outputted to the electrical signal ratio calculation unit.
  • the power detector is a linear transfer function of the signal amplitude.
  • the larger the system residual dispersion value the lower the amplitude of the signal, and the extinction ratio of the signal.
  • the residual dispersion value of the system will be smaller, and the calculated ESR will be larger;
  • the ESR value corresponds to the minimum system residual dispersion value, which is the optimal dispersion compensation value of the system.
  • the tunable dispersion compensation adjuster adjusts according to the feedback ESR value until the ESR value of the feedback feedback is a peak.
  • the dispersion compensation is performed using the dispersion value corresponding to the ESR peak.
  • the structure of the partial band radio frequency power detecting unit 101 provided by the embodiment of the present invention is as shown in FIG. 6, and includes:
  • the comparing unit 601 is configured to compare the value of the currently received electrical signal ratio with the value of the previously received electrical signal ratio, and continue to adjust the dispersion compensation value when the received electrical signal ratio increases. When the value of the electrical signal ratio decreases, the maximum value of the received electrical signal ratio is the peak value of the electrical signal ratio;
  • the residual dispersion value determining unit 602 is configured to determine a residual dispersion value of the system based on the peak value of the electrical signal ratio.
  • a dynamic dispersion detection method includes:
  • the above-mentioned storage medium may be a read only memory, a magnetic disk or an optical disk or the like.
  • the above describes a dynamic dispersion detecting method and device provided by the present invention in detail.
  • the description of the embodiments is only for helping to understand the method of the present invention and its core ideas; at the same time, for those skilled in the art, according to the idea of the present invention, there will be changes in the specific embodiments and application scopes. The contents of this specification are not to be construed as limiting the invention.

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Description

动态色散检测方法及装置 本申请要求于 2009 年 11 月 19 日提交中国专利局、 申请号为 200910222614.3、 发明名称为 "动态色散检测方法及装置" 的中国专利申请 的优先权， 其全部内容通过引用结合在本申请中。
技术领域
本发明涉及通信技术领域， 尤其涉及一种动态色散检测方法及装置。 背景技术
在光纤通信系统中色散容限与比特速率成反比， 随着传速速率的增加， 系统的色散容限迅速下降， 在将来的智能化全球通信网络中， 各个节点信 道上下路及交换情况越来越复杂， 接收端无法预知光信号的具体通路， 因 此链路色散具有不确定性， 残余色散值容易超过系统的色散容限， 对系统 性能产生严重影响， 因此如何经济有效地对系统色散进行动态补偿成为研 究的热点。
在现有技术中，主要利用业务接通后产生的误码率性能误比特率（ BER， Bi t Error Ra t io )来对系统色散进行动态补偿， 具体内容如下：
在接通业务之前， 由可调色散补偿器 （TDC， Tunable Di spers ion Compensa tor )进行色散补偿的粗调， 在进行色散补偿粗调的同时， 光接收 模块进行信号解调， 等光纤通信系统色散落在光接收模块可以接收的色散 窗口内时完成信号的解调；
业务接通后， 停止 TDC粗调， 采集系统的 BER， 反馈给 TDC， TDC根据 系统的 BER进行 TDC细调， 直至反馈的 BER在一段时间内最小， 此时的 TDC 值可以认为是系统最佳色散补偿值， 因此可以完成色散动态补偿。
在对现有技术的研究和实践过程中， 发明人发现现有技术存在以下问 题：
由于 TDC调节和信号解调同步进行， 可能出现 TDC 已经在调节到信号 允许的色散窗口内， 而此时信号解调还没完成， 无法接通业务， 错过最佳 色散窗口而业务不通的情形， 导致出现第二次 TDC搜索， 造成接通业务时 间变长。
BER需要在业务通后能下发误码的条件下才能调节， 调节时间较慢， 增 加了系统通业务的时间。
发明内容
本发明实施例要解决的技术问题是提供一种动态色散检测方法及装 置， 可以检测到系统的最佳色散， 有效提高系统性能。
为解决上述技术问题， 本发明实施例一方面， 提供了一种动态色散检 测装置， 包括： 可调色散补偿调节器、 解调器、 接收机、 部分频带射频功 率检测单元、 电信号比计算单元；
所述可调色散补偿调节器对接收到的光信号进行色散补偿后， 将收到 的光信号发送到解调器；
所述解调器对接收到的光信号进行相位解调；
接收机将所述解调器输出的光信号转换为电信号；
部分频带射频功率检测单元， 对所述接收机转换获得的电信号进行射 频功率取样， 获取射频信号；
电信号比计算单元， 获取所述射频信号的电信号比， 持续向所述可调 色散补偿调节器发送所述电信号比；
可调色散补偿调节器， 使用当前接收到的电信号比的值与之前收到的 电信号比的值相比较， 根据比较结果调节色散补偿值， 得到所述电信号比 的峰值， 根据所述电信号比的峰值确定系统的残余色散值。
另一方面， 提供了一种动态色散检测方法， 包括：
对接收到的光信号进行相位解调；
将解调后的光信号转换为电信号；
对所述电信号进行射频功率取样， 获取射频信号；
获取所述射频信号的电信号比；
使用当前检测到的电信号比的值与之前检测到的电信号比的值相比 较， 根据比较结果调节色散补偿值， 找到所述电信号比的峰值， 根据所述 电信号比的峰值获取系统的残余色散值。
由以上技术方案可以看出， 将光信号转换为电信号， 寻找电信号比峰 值， 再根据电信号比峰值获取系统的残余色散值， 由于电信号比峰值对应 的色散值就是系统的最佳残余色散值， 因此可以检测到系统的最佳残余色 散值， 由于电信号比的脉沖展宽较窄， 因此更容易找到峰值， 使用电信号 比确认最佳残余色散值， 准确度较高， 可以提高检测系统残余色散的精度， 进一步将检测到的最佳残余色散应用于色散补偿， 就可以避免信号错过系 统色散最佳窗口的问题， 提高了可靠性， 且不需要等待业务通后能下发误 码的条件下再进行调节， 加快了系统通业务的时间。
附图说明
为了更清楚地说明本发明实施例或现有技术中的技术方案， 下面将对 实施例或现有技术描述中所需要使用的附图作简单地介绍， 显而易见地， 下面描述中的附图仅仅是本发明的一些实施例， 对于本领域普通技术人员 来讲， 在不付出创造性劳动性的前提下， 还可以根据这些附图获得其他的 附图。
图 1为本发明实施例提供的动态色散检测装置的系统框图；
图 2为本发明实施例提供的动态色散检测方法流程图；
图 3为信号幅度与累积色散 d的关系曲线图；
图 4为不同色散值情况下电信号频谱的仿真曲线；
图 5为本发明实施例提供的部分频带射频功率检测单元的结构图； 图 6为本发明实施例提供的可调色散补偿调节器的结构图。
具体实施方式
下面将结合本发明实施例中的附图， 对本发明实施例中的技术方案进 行清楚、 完整地描述， 显然， 所描述的实施例仅仅是本发明一部分实施例， 而不是全部的实施例。 基于本发明中的实施例， 本领域普通技术人员在没 有作出创造性劳动前提下所获得的所有其他实施例， 都属于本发明保护的 范围。
动态色散补偿系统中， 色散检测技术和补偿具有核心地位， 色散检测 的范围和精度直接决定了动态色散补偿系统的范围和精度， 其复杂程度也 直接决定了补偿系统的总成本， 40Gbp s速率以上的光模块色散容限低， 需 要进行色散补偿， 如何寻找最佳色散点， 成为动态色散补偿的关键技术。
本发明实施例提供了一种动态色散检测方法及装置， 可以检测到系统 的最佳色散， 有效提高系统性能。 本发明实施例提供的动态色散检测装置， 包括：
可调色散补偿调节器、 解调器、 接收机、 部分频带射频功率检测单元、 电信号比计算单元；
该可调色散补偿调节器对接收到的光信号进行色散补偿后， 将收到的 光信号发送到解调器；
解调器， 对接收到的光信号进行相位解调；
接收机， 将该解调器输出的光信号转换为电信号；
部分频带射频功率检测单元， 对该接收机转换获得的电信号进行射频 功率取样， 获取射频信号；
电信号比计算单元， 获取该射频信号的电信号比， 持续向该可调色散 补偿调节器发送该电信号比；
其中， 电信号比计算单元获取的电信号比为在一段预定时间内检测该 射频信号的射频峰值与射频谷值的比值。
可调色散补偿调节器， 使用当前接收到的电信号比的值与之前收到的 电信号比的值相比较， 根据比较结果调节色散补偿值， 找到该电信号比的 峰值， 根据该电信号比的峰值确定系统的残余色散值。
本发明实施例提供的动态色散检测装置， 将光信号转换为电信号， 寻 找电信号比峰值， 再根据电信号比峰值获取系统的残余色散值， 由于电信 号比峰值对应的色散值就是系统的最佳残余色散值， 因此可以检测到系统 的最佳残余色散值， 由于电信号比的脉沖展宽较窄， 因此更容易找到峰值， 使用电信号比确认最佳残余色散值， 准确度较高， 可以提高检测系统残余 色散的精度， 进一步将检测到的最佳残余色散应用于色散补偿， 就可以避 免信号错过系统色散最佳窗口的问题， 提高了可靠性， 且不需要等待业务 通后能下发误码的条件下再进行调节， 加快了系统通业务的时间。
图 1 为本发明实施例提供的动态色散检测装置的系统框图， 包括： 可 调色散补偿调节器（TDCM， TDC Modula t ion ) 101 ,解调器（画， Demodula tor ) 102、 接收机 103、 部分频带射频 ( RF , Radio Frequency ) 功率检测单元 104、 电信号比 （ESR， Elect r i ca l s i gna l Ra t io )计算单元 105。
可调色散补偿调节器 101接收到光信号后， 先对接收到的光信号进行 色散补偿， 然后将光信号发送到解调器 102， 在系统初始运行时， 可调色散 补偿调节器 101 会有一个初始色散补偿值， 该初始色散补偿值可以由用户 根据经验预设， 也可以使用系统预设值。
解调器 102接收到光信号时， 完成对光信号的相位解调。
接收机 1 03为光电转换部分， 主要完成将解调器 102输出的光信号转 换成电信号。
部分频带射频功率检测单元 104 用于对转换后的电信号某一段频段进 行采样， 计算转换后电信号的部分频带上的 RF功率， 主要完成电信号的 RF 功率取样， 交予后续的电信号比计算单元 105 ; 构成部分频带射频功率检测 单元 104的主要器件， 可以是功率检波器和部分滤波电路。
电信号比计算单元 105 主要负责逻辑处理部分， 主要用来计算部分频 带射频功率检测单元 104检测到的 RF信号的 ESR值， ESR的值等于检测 RF 信号得到的 RF峰值与 RF谷值的比值，即 ESR值=1^峰值 /RF谷值；计算 ESR 值的过程是一个持续计算的过程， 随着时间的变化可以得到不同时间段的 ESR值， 然后将计算出的 ESR值持续交给可调色散补偿调节器 101 ; 电信号 比计算单元 1 05可以使用微程序控制器 （MCU， Mi crocont ro l l er Uni t )或 者现场可编程门阵列 （FPGA， F i e l d Programmab l e Ga t e Array ) 器件实现。
可调色散补偿调节器 101收到电信号比计算单元 105获取的 ESR值后， 使用当前收到的 ESR值与之前收到的 ESR值进行比较， 如果收到的 ESR值 持续上升， 则继续调节色散补偿值， 在收到的 ESR值开始出现下降时， 可 以确认之前收到的 ESR值已经出现了 ESR值的峰值， 也就是收到的 ESR最 大值， ESR最大值对应的色散值就是系统的最佳残余色散值， 因此可以根据 ESR峰值确认系统的残余色散值， 进一步， 可以根据该残余色散值及时进行 系统残余色散补偿， 停止调节色散补偿值。
其中确认 ESR峰值的方式可以是， 在发现收到的 ESR值比前一个 ESR 值小的时候， 即认为前一个 ESR值为 ESR峰值，也可以是在一段时间内 ESR 值持续下降， 以之前收到的 ESR最大值为 ESR峰值， 以避免 ESR值抖动造 成的误差。
其中， 部分频带射频功率检测单元可以包括：
平方器， 对该电信号进行平方运算； 低通滤波器， 对该平方器运算的结果进行低通滤波；
均方器， 对该低通滤波器滤波的结果求均方值；
放大器， 对该均方器放大输出射频信号；
模数转换器， 对该射频信号进行模数转换。
当然这是一种获取射频信号实现部分频带射频功率检测单元的实施 例， 其他获取射频信号的装置构成也可以使用。
以上为对本发明实施例提供的动态色散检测装置的描述， 本发明实施 例提供的动态色散检测装置的具体使用方法极原理分析， 可参考下文对本 发明实施例提供的动态色散检测方法的描述。 本发明实施例提供的动态色散检测方法流程如图 2所示， 包括：
201、 对接收到的光信号进行相位解调。
202、 将解调后的光信号转换为电信号。
203、 对电信号进行射频功率取样， 获取射频信号。
204、 获取该射频信号的电信号比。
获取该射频信号的电信号比， 该电信号比为在一段预定时间内检测射 频信号的射频峰值与射频谷值的比值，即 ESR值 RF峰值 /RF谷值；计算 ESR 值的过程是一个持续计算的过程， 随着时间的变化可以得到不同时间段的 ESR值。
205、 根据该电信号比值获取系统的残余色散值。
使用当前检测到的电信号比的值与之前检测到的电信号比的值相比 较， 如果收到的 ESR值持续上升， 则继续调节色散补偿值， 在收到的 ESR 值开始出现下降时， 可以确认之前收到的 ESR值已经出现了 ESR值的峰值， 也就是收到的 ESR最大值， ESR最大值对应的色散值就是系统的最佳残余色 散值， 因此可以根据 ESR峰值确认系统的残余色散值。
其中确认 ESR峰值的方式可以是， 在发现收到的 ESR值比前一个 ESR 值小的时候， 即认为前一个 ESR值为 ESR峰值，也可以是在一段时间内 ESR 值持续下降， 以之前收到的 ESR最大值为 ESR峰值， 以避免 ESR值抖动造 成的误差。
进一步， 可以使用该残余色散值及时进行系统残余色散补偿。 本发明实施例提供的动态色散检测方法， 将光信号转换为电信号， 寻 找电信号比峰值， 再根据电信号比峰值获取系统的残余色散值， 由于电信 号比峰值对应的色散值就是系统的最佳残余色散值， 因此可以检测到系统 的最佳残余色散值， 由于电信号比的脉沖展宽较窄， 因此更容易找到峰值， 使用电信号比确认最佳残余色散值， 准确度较高， 可以提高检测系统残余 色散的精度， 进一步将检测到的最佳残余色散应用于色散补偿， 就可以避 免信号错过系统色散最佳窗口的问题， 提高了可靠性， 且不需要等待业务 通后能下发误码的条件下再进行调节， 加快了系统通业务的时间。
以下将论述电信号比和残余色散值的对应关系。
参考图 1可以看出， 解调器 1 02接收的是光信号， 光纤所传送信号的 不同频率成分或不同模式成分的群速度不同， 传过同样的距离会有不同的 时延， 引起传输信号畸变， 主要为脉沖的展宽； 将传输信号视为高斯脉沖， 设 T。为信号时域上的初始信号宽度， T为信号时域上信号宽度， T会随着传 输 I的增加而逐渐增大， T与 Z的关系参见公式①： 公式①
Figure imgf000009_0001
信号宽度 τ展宽，会导致信号功率 u的幅度下降， u与 τ的关系参见公 式②
， {τΙ- β2ζ) μ 2 TH 、) 公式②
把式中的传输距离 z和 2用累计色散 d表示， u可以表示为公式③：
从上述公式看出， 累积色散 d从时域上展宽信号脉沖， 其展宽大小取 决与累积色散 d， 其信号幅度与累积色散 d的关系曲线如图 3所示：
曲线 S 1为有累积色散 Ops /nm下的信号归一化幅度曲线； 曲线 S2为有 累积色散 68 ps /nm 下的信号归一化幅度曲线； 曲线 S 3 为有累积色散 136ps/nm下的信号归一化幅度曲线。
从图 3 可以看出， 随着累积色散值的增加其信号的幅度会随之下降， 且下降关系明显，定义光信号消光比为： Ex=信号的功率峰值与谷值的比值， 则累积色散值越大， 信号幅度越小， 光信号消光比越小。
电功率检测是检测光脉沖信号经过光电检测器件输出电信号的功率， 接收机 103就是一种光电检测器件。 色度色散使光纤中传输的光脉沖在时 域展宽， 但不影啊光脉沖的频谱， 而只改变了每个频谱分量的相位。 接收 机 103探测输入光信号的光强， 忽略光信号的相位变化， 将输入光脉沖变 为电脉沖， 电脉沖的频谱随着光脉沖包络的展宽而变窄， 导致给定频点处 电功率值随色度色散变化。
接收机 103将接收到的光信号转换成电信号， 使入射光功率有效的转 换成光电流，接收机 103的一个重要参量是响应度 R，定义为： R=Ip/P0， 其 中 Po为入射到光探测器上的光功率， IP为产生的光电流。 光功率 Po与光 脉沖包络 U ( z， T )大小的平方成正比。 因此， 当输入光信号为公式②给定 的光
Figure imgf000010_0001
公式 ④
Figure imgf000010_0002
公式 ⑤ 同时可以得到电信号 I ( d， T )频谱， 电信号 I ( d， T )频谱可表述为 公式
Figure imgf000010_0003
公式 ⑥ 从公式⑥中可以看出， 虽然色度色散不会影响光脉沖信号的频谱， 却 能改变电信号的频谱。 因此， 通过分析累积色散值和电信号频谱的关系， 就可通过检测电信号的频谱， 得到光纤通信系统中累积色度色散值的大小。 图 4为不同色散值情况下电信号频谱的仿真曲线， 曲线 HI为有累积色 散 Ops/nm下的电信号频谱的仿真曲线； 曲线 H2为有累积色散 68ps/nm下 的电信号频谱的仿真曲线； 曲线 H3为有累积色散 136ps/nm下的电信号频 谱的仿真曲线。
从图 4 中可以看出， 在整个频谱范围内， 每个频点的谱密度都随累积 色散值的大小变化， 因此可以通过检测指定频点的谱密度或检测指定频带 范围内的电功率值的 ESR作为动态色度色散补偿的反馈信号， 来监测光纤 通信系统中累积色散的变化， 并控制动态色度色散补偿器件的补偿量。
本发明实施例提供的部分频带射频功率检测单元 104的结构如图 5所 示， 包括： 平方器 501、 氏通滤波（LPF， low-pass filter ) 器 502、 均方 (RMS, mean square ) 器 503、 放大器 （AMP， Amplifier ) 504、 模数转换 器 ( AD converter ) 505。
其中， 平方器 501、 低通滤波器 502、 均方器 503、 放大器 504构成功 率检波器， 电功率的检测主要由功率检波器完成。
电信号 Xi进入功率检波器后，首先由平方器 501进行平方运算，即 X2； 信号 Xi即为光信号 U(z，T)的平方；
然后由低通滤波器 502进行 LPF滤波处理；
滤波处理后由均方器 503求 RMS值， RMS值就是一组统计数据的平方的 平均值的平方才艮，运算公式为 RMS = ( XI平方 + X2平方 + +Xn平方 )
/n 的 - 1/2次方；
获得 RMS值后通过增益为 G的放大器 504放大输出 RF。ut信号； RF。ut可 以使用公式表述
RF outf = G
Figure imgf000011_0001
模数转换器 505收到 RF。ut后， 对其进行模数转换， 输出数字信号到电 信号比计算单元。
由以上描述可知， 功率检波器是一个信号幅度的线性传递函数， 根据 上文描述， 系统残余色散值越大， 信号的幅度会降低， 信号的消光比也会 变小， 经过 RF功率检波器做 RMS求值后， 计算出来的 ESR 功率峰值 /功率 谷值就会变小， 反之， 系统的残余色散值较小， 计算出来的 ESR就会越大； 因此最大 ESR值对应的也就是最小的系统残余色散值， 也就是系统的最佳 色散补偿值， 可调色散补偿调节器会根据反馈的 ESR值进行调节， 直到确 认反馈的 ESR值是一个峰值， 则使用 ESR峰值对应的色散值进行色散补偿。 本发明实施例提供的部分频带射频功率检测单元 101的结构如图 6所 示， 包括：
比较单元 601，用于使用当前接收到的电信号比的值与之前收到的电信 号比的值相比较， 在收到的电信号比的值上升时， 继续调节色散补偿值， 在收到的电信号比的值出现下降时， 以收到的该电信号比的最大值为该电 信号比的峰值；
残余色散值确定单元 602，用于根据该电信号比的峰值确定系统的残余 色散值。 本领域普通技术人员可以理解实现上述实施例方法中的全部或部分步 骤是可以通过程序来指令相关的硬件完成， 该的程序可以存储于一种计算 机可读存储介质中， 该程序在执行时， 包括如下步骤：
一种动态色散检测方法， 包括：
对接收到的光信号进行相位解调；
将解调后的光信号转换为电信号；
对所述电信号进行射频功率取样， 获取射频信号；
获取所述射频信号的电信号比；
使用当前检测到的电信号比的值与之前检测到的电信号比的值相比 较， 根据比较结果调节色散补偿值， 找到所述电信号比的峰值， 根据所述 电信号比的峰值获取系统的残余色散值。
上述提到的存储介质可以是只读存储器， 磁盘或光盘等。 以上对本发明所提供的一种动态色散检测方法及装置进行了详细介 实施例的说明只是用于帮助理解本发明的方法及其核心思想； 同时， 对于 本领域的一般技术人员， 依据本发明的思想， 在具体实施方式及应用范围 上均会有改变之处， 综上该， 本说明书内容不应理解为对本发明的限制。

Claims

权利要求
1、 一种动态色散检测装置， 其特征在于， 包括： 可调色散补偿调节器、 解调器、 接收机、 部分频带射频功率检测单元、 电信号比计算单元；
所述可调色散补偿调节器对接收到的光信号进行色散补偿后， 将收到 的光信号发送到解调器；
所述解调器对接收到的光信号进行相位解调；
接收机将所述解调器输出的光信号转换为电信号；
部分频带射频功率检测单元， 对所述接收机转换获得的电信号进行射 频功率取样， 获取射频信号；
电信号比计算单元， 获取所述射频信号的电信号比， 持续向所述可调 色散补偿调节器发送所述电信号比；
可调色散补偿调节器， 使用当前接收到的电信号比的值与之前收到的 电信号比的值相比较， 根据比较结果调节色散补偿值， 得到所述电信号比 的峰值， 根据所述电信号比的峰值确定系统的残余色散值。
2、 如权利要求 1所述的动态色散检测装置， 其特征在于， 所述部分频 带射频功率检测单元包括：
平方器， 对所述电信号进行平方运算；
低通滤波器， 对所述平方器运算的结果进行低通滤波；
均方器， 对所述低通滤波器滤波的结果求均方值；
放大器， 对所述均方器求得的均方值放大输出射频信号；
模数转换器， 对所述射频信号进行模数转换。
3、如权利要求 1或 2所述的动态色散检测装置，其特征在于，还包括： 所述可调色散补偿调节器根据所述系统的残余色散值对系统进行色散 补偿。
4、 如权利要求 1或 2所述的动态色散检测装置， 其特征在于， 所述电 信号比计算单元获取的电信号比为在一段预定时间内检测所述射频信号的 射频峰值与射频谷值的比值。
5、 如权利要求 1或 2所述的动态色散检测装置， 其特征在于， 所述可 调色散补偿调节器包括：
比较单元， 用于使用当前接收到的电信号比的值与之前收到的电信号 比的值相比较， 在收到的电信号比的值上升时， 继续调节色散补偿值， 在 收到的电信号比的值出现下降时， 以收到的所述电信号比的最大值为所述 电信号比的峰值；
残余色散值确定单元， 用于根据所述电信号比的峰值确定系统的残余 色散值。
6、 如权利要求 1或 2所述的动态色散检测装置， 其特征在于， 所述残 余色散值确定单元具体用于： 查找所述电信号比的峰值对应的色散值， 所 述色散值为系统的残余色散值。
7、 一种动态色散检测方法， 其特征在于， 包括：
对接收到的光信号进行相位解调；
将解调后的光信号转换为电信号；
对所述电信号进行射频功率取样， 获取射频信号；
获取所述射频信号的电信号比；
使用当前检测到的电信号比的值与之前检测到的电信号比的值相比 较， 根据比较结果调节色散补偿值， 找到所述电信号比的峰值， 根据所述 电信号比的峰值获取系统的残余色散值。
8、 如权利要求 7所述的方法， 其特征在于， 所述对所述电信号进行射 频功率取样， 获取射频信号包括：
对所述电信号进行平方运算； 对所述平方运算的结果进行低通滤波； 对所述低通滤波的结果求均方值； 对所述均方值放大输出射频信号； 对所 述射频信号进行模数转换。
9、 如权利要求 7或 8所述的方法， 其特征在于， 还包括：
根据所述残余色散值， 对系统残余色散进行补偿。
1 0、 如权利要求 Ί或 8所述的方法， 其特征在于， 所述电信号比计算 单元获取的电信号比为在一段预定时间内检测所述射频信号的射频峰值与 射频谷值的比值。
1 1、 如权利要求 7或 8所述的方法， 其特征在于， 所述使用当前检测 到的电信号比的值与之前检测到的电信号比的值相比较， 根据比较结果调 节色散补偿值， 找到所述电信号比的峰值包括：
使用当前检测到的电信号比的值与之前检测到电信号比的值相比较， 在检测到电信号比的值上升时， 继续调节色散补偿值， 在检测到电信号比 的值出现下降时， 以检测到电信号比的最大值为所述电信号比的峰值。
PCT/CN2010/078608 2009-11-19 2010-11-10 动态色散检测方法及装置 WO2011060697A1 (zh)

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