Classifications

• • G—PHYSICS
  • G05—CONTROLLING; REGULATING
  • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
  • G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
  • G05F1/10—Regulating voltage or current 
  • G05F1/46—Regulating voltage or current  wherein the variable actually regulated by the final control device is DC
  • G05F1/56—Regulating voltage or current  wherein the variable actually regulated by the final control device is DC using semiconductor devices in series with the load as final control devices
• • G—PHYSICS
  • G06—COMPUTING OR CALCULATING; COUNTING
  • G06F—ELECTRIC DIGITAL DATA PROCESSING
  • G06F1/00—Details not covered by groups G06F3/00 - G06F13/00 and G06F21/00
  • G06F1/24—Resetting means
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of DC power input into DC power output
  • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
  • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
  • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
  • H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
  • H02J7/34—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering
  • H02J7/345—Parallel operation in networks using both storage and other DC sources, e.g. providing buffering using capacitors as storage or buffering devices
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0096—Means for increasing hold-up time, i.e. the duration of time that a converter's output will remain within regulated limits following a loss of input power
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/36—Means for starting or stopping converters
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M3/00—Conversion of DC power input into DC power output
  • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
  • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
  • H02M3/06—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider
  • H02M3/07—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
  • H02M3/073—Charge pumps of the Schenkel-type

Definitions

• the invention relates generally to charge controllers; and, more particularly, to charge controllers that provide an amount of energy to prolong operation for a minimum time when power is disconnected in order to enable an orderly shutdown.
• power down should be controlled enough so the system can gracefully shut down.
• An example of such an application is the digital subscriber line or xDSL modem standards compliant applications, which require manufacturers to allow for a "dying gasp" time when input power is disconnected.
• the term "dying gasp” refers to providing a final amount of energy at shutdown, such as, e.g., provided by a local energy storage capacitor, to power the device and prolong operation for a sufficient time to allow for an orderly shutdown. Typically, this "dying gasp" is on the order of about 60ms. During this "dying gasp," xDSL modems can communicate with the central computer about the shutdown and allow for better traffic handling.
• An example embodiment of the invention provides an apparatus.
• the apparatus comprising an input node; an internal capacitor that is coupled to the input node; an output node; and a dying gasp charge controller including: a dump circuit that is coupled to the input node and the output node, wherein the dump circuit provides charge to the output node from the input node on startup when the voltage on the output node is less than a precharge voltage, and wherein the dump circuit provides charge to the input node from the output node when the voltage on the input node falls below a gasp voltage; and a pump circuit that is coupled to the input node and the output node, wherein the pump circuit provides charge to the output node from the input node when the voltage on the output node is less than a charge voltage.
• the dump circuit further comprises a first transistor having a first passive electrode, a second passive electrode, and a control electrode, wherein the first passive electrode of the first transistor is coupled to the input node; a current limiter that is coupled to the input node and the control electrode of the first transistor; a second transistor having a first passive electrode, a second passive electrode, and a control electrode, wherein the first passive electrode of the first transistor is coupled to the second passive electrode of the first transistor, and wherein the second passive electrode of the second transistor is coupled to the output node; and an amplifier having a first input terminal, a second input terminal, and an output terminal, wherein the first input terminal of the amplifier is coupled to the input node, and wherein the second input terminal of the amplifier receives the gasp voltage, and wherein the output terminal of the amplifier is coupled to the control electrode of the second transistor.
• the first transistor is a PMOS transistor with the first passive electrode being the source, the second passive electrode being the drain, and the control electrode being the gate.
• the second transistor is a PMOS transistor with the first passive electrode being the drain, the second passive electrode being the source, and the control electrode being the gate.
• the pump circuit further comprises a low drop-out (LDO) regulator that is coupled to the input node; and a charge pump coupled between the LDO regulator and the output node.
• LDO low drop-out
• the pump circuit further comprises a charge pump.
• the pump circuit further comprises a boost converter.
• an apparatus comprising an input node; a first capacitor that is coupled to the input node; an output node; a dying gasp charge controller including: a first PMOS transistor that is coupled to the input node at its source; a current limiter that is coupled to the input node and the gate of the first PMOS transistor; a second PMOS transistor that is coupled to the drain of the first PMOS transistor at its drain and the output node at its source; and an amplifier having a first input terminal, a second input terminal, and an output terminal, wherein the first input terminal of the amplifier is coupled to the input node, and wherein the second input terminal of the amplifier receives the gasp voltage, and wherein the output terminal of the amplifier is coupled to the gate of the second PMOS transistor; and a pump circuit that is coupled to the input node and the output node, wherein the dump circuit provides charge to the output node from the input node when the voltage on the output node is less than a charge voltage; and
• the LDO regulator further comprises: a third PMOS transistor that is coupled to the input node at its source; and a second amplifier having a first input terminal, a second input terminal, and an output terminal, wherein the first input terminal of the second amplifier receives the charge voltage, and wherein the second input terminal of the second amplifier is coupled to the output node, and wherein the output terminal of the second amplifier is coupled to the gate of the third PMOS transistor.
• the charge pump further comprises: a first diode that is coupled to the drain of the third PMOS transistor; a second diode coupled between the first diode and the output node; and a third capacitor that is coupled to a node between the first and second diodes and that is coupled to a switching node.
• the apparatus further comprises a buck converter having the switching node which is coupled to the third capacitor.
• an apparatus comprising an input node; a first capacitor that is coupled to the input node; an output node; a buck converter having: a first NMOS transistor that coupled to the input node at its drain and a switching node at its source; a second NMOS transistor that is coupled to the switching node at its drain and ground at its source; a pulse width modulator (PWM) coupled to the gates of the first and second NMOS transistors; a dying gasp charge controller including: a first PMOS transistor that is coupled to the input node at its source; a current limiter that is coupled to the input node and the gate of the first PMOS transistor; a second PMOS transistor that is coupled to the drain of the first PMOS transistor at its drain and the output node at its source; a first amplifier having a first input terminal, a second input terminal, and an output terminal, wherein the first input terminal of the first amplifier is coupled to the input node, and wherein the second input
• PWM pulse width modulator
• FIG. 1 is a circuit diagram of a dying gasp charge controller in accordance with an example embodiment of the invention
• FIG. 2 is a more detailed example of the dying gasp charge controller of FIG. 1;
• FIG 3 is a state diagram for the dying gasp charge controller of FIG. 2.
• reference numeral 100 generally designates an example of a "dying gasp" power shutdown charge controller in accordance with an example embodiment of the invention.
• the energy stored on a capacitor is 1 ⁇ 2CV , where C is the capacitance of the capacitor and V is the voltage on the capacitor.
• C is the capacitance of the capacitor
• V is the voltage on the capacitor.
• this principle is applied to the controller 100, where an input large capacitor has been divided to an internal capacitor CIN and an external capacitor CEXT (which are coupled to the input node NIN and output node NOUT of the controller 100, respectively) so that the voltage can be varied to have the same energy as a large capacitor.
• Each of capacitors CIN and CEXT are also about ⁇ and about 1000 ⁇ , respectively.
• controller 100 employs a pump circuit 102 and a dump circuit 104.
• the pump circuit 102 provides charge to the output node NOUT (and the external capacitor CEXT) from the input node NIN (which receives an input voltage VIN) on startup.
• dump circuit 104 charges the external or storage capacitor CEXT in a precharge mode when the voltage on the output node NOUT is less than a precharge voltage (typically about the input voltage VIN minus a voltage drop across a body diode).
• the pump circuit 102 continues to charge the external capacitor CEXT by allowing charge to flow from the input node NIN to the output node NOUT until the voltage on the output node NOUT (and external capacitor CEXT) is greater than a charge voltage VMAX (which is typically about twice the input voltage VIN and which can be selectable by digital controls to generally ensure that the charge voltage VMAX does not exceed the voltage rating of the external capacitor CEXT).
• VMAX charge voltage
• Controller 100 then continues to monitor the input voltage VIN (voltage on the input node NIN), and when the input voltage VIN (which is typical between about 9V and about 12V) falls below a gasp voltage VGASP (which is typically about 90% of the input voltage VIN), the external capacitor CEXT is discharged through the dump circuit 104 to the input node NIN.
• VIN voltage on the input node NIN
• VGASP gasp voltage
• the pump circuit 102 can be implemented as a charge pump, a boost regulator, or a linear drop-out (LDO) regulator with a charge pump.
• LDO linear drop-out
• controller 100 (indicated by reference numeral 100-1) that employs an LDO regulator with a charge pump is shown along with its state diagram.
• controller 100-1 is coupled to internal capacitors CIN, CI, and C2, external capacitor CEXT, and buck converter 112.
• the dump circuit 104-1 (which has the same general operation as dump circuit 104 of FIG. 1) is generally comprised of PMOS transistors Ql and Q2, current limiter 106, and amplifier 108.
• the pump circuit 102-1 (which has the same general operation as pump circuit 102 of FIG. 1) is generally comprised of amplifier 110, PMOS (or NMOS) transistor Q3, diodes Dl and D2, and capacitor C2.
• buck converter 112 is generally comprised of a pulse width modulator 114, an error amplifier 116, voltage divider Rl and R2, inductor L, capacitor C3, and NMOS transistors Q4 and Q5.
• Buck converter 112 operates in the conventional manner by applying PWM signals (which are adjusted through the error amplifier 116 comparing the feedback voltage from voltage divider Rl and R2 to a reference voltage VREF) to the gates of transistors Q4 and Q5. This allows the switching node NSW to switch between ground and input voltage VIN to drive inductor L and capacitor C3.
• buck converter 112 can be replaced by another circuit that provides a switching node similar to that provided buck converter 112.
• controller 100-1 is able to charge and discharge the external capacitor CEXT in generally the same manner as controller 100 of FIG. 1.
• the input voltage VIN rises to a desired level (for example, about 12V and typically above about 1.5V) of state 302, and the controller 100-1 enters the precharge mode of state 304.
• amplifier 108 maintains transistor Q2 in an "off state so that it operates as a diode (using the inherent body diode of transistor Q2), and current limiter 106 measures the current from the input node NIN to the output node NOUT so as to operate transistor Ql as a current-limited switch.
• the dump circuit 104-1 then, continues to charge the external capacitor CEXT until the voltage on the output node (and capacitor CEXT) is greater than the precharge voltage (typically about the input voltage VIN minus a voltage drop across the body diode of transistor Q3). Once the voltage on capacitor CEXT is greater than the precharge voltage, the controller 100-1 enters a charge mode of state 306 where the amplifier 110 actuates transistor Q3 to allow charge to continue to flow from the input node NIN to the output node NOUT until the voltage on the output node NOUT (and capacitor CEXT) is greater than the charge voltage VMAX.
• the precharge voltage typically about the input voltage VIN minus a voltage drop across the body diode of transistor Q3
• a stepping voltage (which is lower than the input voltage VIN) is applied to capacitor C2 (which is coupled to a node between diodes Dl and D2) by a switching node (for example, from switching node NSW of buck converter 112) to provide additional charge control, operating as a charge pump.
• amplifier 108 continues to monitor the input voltage VIN to determine whether it has fallen below the gasp voltage VGASP (indicating power loss). When this power loss is detected, controller 100-1 enters a dump mode of state 308. In the dump mode of state 308, amplifier 108 actuates transistor Q2, and the current limiter 106 does not limit any current flowing from output to input node during dump mode, allowing transistor Q2 to act as a power field effect transistor (FET) of an LDO and allowing transistor Ql act as a switch. Current can then flow from the output node NOUT (and capacitor CEXT) to the input node NIN.
• FET power field effect transistor
• the system can use the energy stored on capacitors CIN and CEXT to continue to power the system during a "dying gasp" period without the use of a bulky and expensive external capacitor. Additionally, because a large voltage is applied to capacitors CIN and CEXT, the energy storage capacity meets or exceeds that of conventional circuits.

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• Engineering & Computer Science (AREA)
• Physics & Mathematics (AREA)
• General Physics & Mathematics (AREA)
• Theoretical Computer Science (AREA)
• Electromagnetism (AREA)
• Radar, Positioning & Navigation (AREA)
• Automation & Control Theory (AREA)
• Power Engineering (AREA)
• General Engineering & Computer Science (AREA)
• Dc-Dc Converters (AREA)

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Publications (2)

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• 2009
  • 2009-11-11 US US12/616,549 patent/US7940118B1/en active Active
• 2010
  • 2010-11-09 CN CN201080051053.6A patent/CN102598578B/zh active Active
  • 2010-11-09 JP JP2012538875A patent/JP5832440B2/ja active Active
  • 2010-11-09 WO PCT/US2010/055895 patent/WO2011059930A2/en not_active Ceased

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