WO2008152565A2 - Circuit d'alimentation, en particulier pour del - Google Patents

Circuit d'alimentation, en particulier pour del Download PDF

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Publication number
WO2008152565A2
WO2008152565A2 PCT/IB2008/052259 IB2008052259W WO2008152565A2 WO 2008152565 A2 WO2008152565 A2 WO 2008152565A2 IB 2008052259 W IB2008052259 W IB 2008052259W WO 2008152565 A2 WO2008152565 A2 WO 2008152565A2
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WO
WIPO (PCT)
Prior art keywords
circuit
input
signal
bridge
output
Prior art date
Application number
PCT/IB2008/052259
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English (en)
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WO2008152565A3 (fr
Inventor
Matthias Wendt
Georg Sauerlaender
Heinz W. Van Der Broeck
Martin Christoph
Joseph H. A. M. Jacobs
Dirk Hente
Original Assignee
Philips Intellectual Property & Standards Gmbh
Koninklijke Philips Electronics N.V.
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Application filed by Philips Intellectual Property & Standards Gmbh, Koninklijke Philips Electronics N.V. filed Critical Philips Intellectual Property & Standards Gmbh
Publication of WO2008152565A2 publication Critical patent/WO2008152565A2/fr
Publication of WO2008152565A3 publication Critical patent/WO2008152565A3/fr

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/10—Controlling the intensity of the light
    • H05B45/14—Controlling the intensity of the light using electrical feedback from LEDs or from LED modules
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/382—Switched mode power supply [SMPS] with galvanic isolation between input and output
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/39—Circuits containing inverter bridges
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0083—Converters characterised by their input or output configuration
    • H02M1/0085—Partially controlled bridges
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/355—Power factor correction [PFC]; Reactive power compensation
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/38—Switched mode power supply [SMPS] using boost topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/392—Switched mode power supply [SMPS] wherein the LEDs are placed as freewheeling diodes at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B20/00—Energy efficient lighting technologies, e.g. halogen lamps or gas discharge lamps
    • Y02B20/30—Semiconductor lamps, e.g. solid state lamps [SSL] light emitting diodes [LED] or organic LED [OLED]

Definitions

  • the present invention relates to a supply circuit for supplying an output signal to a load, in particular for supplying a DC output current to an electronic lamp unit. Further, the present invention relates to a corresponding method for supplying an output signal.
  • Solid state lighting is of growing interest for residential, automotive and professional applications. Since solid state lamps such as LEDs cannot be supplied from a battery or the AC mains directly, electronic power drivers are needed. For efficiency reasons LED drivers have to be operated in a switched mode. They convert the available DC or AC voltage into a DC current for LEDs. Moreover, these electronic drivers have to control the current in the LEDs, which are typically connected in series (LED string).
  • European patent application 06110730.6 describes a resonant galvanic isolating power driver, which feeds a current into a series connection of LEDs.
  • a supply circuit for supplying output current signals to loads and comprising first circuits with transistors coupled as a H-bridge for converting input voltage signals into pulse signals and comprising second circuits with inductance circuits and rectifying circuits for receiving the pulse signals and for supplying the output current signals to the loads are provided with third circuits for controlling the first circuits.
  • the third circuits comprise generators for generating control signals for controlling the transistors for reducing dependencies between the input voltage signals and the output current signals.
  • the third circuits supply the control signals in dependence on the input voltage signals and independently of the output current signals.
  • the pulse signals comprise first pulses having a first amplitude and second pulses having a second amplitude different from the first amplitude and they comprise levels having a third amplitude different from the first and second amplitudes.
  • This supply circuit uses this supply circuit to dimmed by reducing the frequency. In most applications the power of the whole LED lighting system has to be supplied from the AC mains.
  • One standard solution for the required AC to DC conversion consists of a diode bridge rectifier with a smoothing capacitor. As is well known, this rectifier circuit shows some disadvantages: a) The rectified output voltage varies with the mains voltage: b) the resulting mains current consists of small current pulses and the corresponding low frequency harmonics exceed certain standards; and c) the power factor is poor.
  • the problems can be solved by applying a preconditioner circuit, where apart from the diode bridge rectifier a boost converter is used to control the current drawn from the mains.
  • the current can be controlled by the transistor to be proportional to the mains voltage.
  • the low- frequency harmonics are substantially reduced and a one-per-unit power factor can be achieved.
  • the disadvantage of this solution is that the LED driver as a whole needs an additional active power stage, which increases size and cost.
  • PFC mains rectifier power factor correction
  • a supply circuit for supplying an output signal to a load, in particular for supplying a DC output current to an electronic lamp unit, comprising: an input circuit comprising input terminals for receiving an input supply signal, a transistor H-bridge circuit having separately controllable transistors for converting said input supply signal into a pulse signal, and an inductance circuit coupled between an input terminal and a H-bridge circuit input terminal, an output circuit comprising a resonance circuit, a transformer and an output rectifier circuit, in particular a full bridge rectifier circuit, for converting said pulse signal into said output signal and output terminals for outputting said output signal to said load, a control circuit for generating control signals for controlling the transistors of said transistor H-bridge.
  • the invention is based on the idea to achieve PFC mains input performance without the need for additional transistors and diodes.
  • the transistors of the H-bridge circuit are not only used to control the output current in the load, but they also perform the function of the active elements of a PFC rectifier.
  • the PFC performance is achieved according to the present invention without needing additional power semiconductors.
  • the supply circuit according to the present invention not only an output signal is provided to a load, but also an input signal is generated.
  • a DC output current is supplied to an electronic lamp unit and a sinusoidal current is drawn from the mains.
  • the supply circuit further comprises a supply signal conversion circuit, coupled to said input terminals of said input circuit, comprising an input rectifier circuit, in particular a full bridge rectifier circuit comprising a bridge of diodes and/or electronic switches, for rectifying a mains signal, in particular an AC mains voltage signal, to obtain said input supply signal, in particular a DC supply voltage signal.
  • a supply signal conversion circuit further comprises a low-pass filter circuit, coupled to input terminals of said input rectifier circuit, for low-pass filtering said mains signal.
  • a discontinuous signal flow in particular discontinuous current flow
  • the additional filtering are applied to achieve an optimized preconditioning or power factor correcting function and to enable an adaptation of the power drawn from the mains depending on a variation of the load, e.g. due to dimming or a change of the load elements (e.g. LEDs).
  • an electronic switch can be provided to the input path to disconnect the converter from mains in order to reduce the delivered power.
  • the inductance circuit comprises an one or more inductors having a low inductance value, in particular in the range from lO ⁇ H to ImH, which leads to a discontinuous current flow through the inductor.
  • two inductors, each being connected to a half bridge of the transistor H-bridge is provided, preferably coupled by a diode so that both inductors can be used alternately. With such an embodiment losses can be reduced and smaller input current ripples can be obtained.
  • said input supply signal is supplied to a first and a second input terminal of said input circuit, said pulse signal being outputted at a first and a second output terminal of said input circuit, and said second input terminal corresponding to to said first output terminal or being coupled via inductors to said first and second output terminals.
  • An advantageous embodiment of the input circuit comprises transistor control means, in particular gate drivers, for separately switching said transistors on and off.
  • transistor control means in particular gate drivers
  • other means can equally be applied, e.g. digital control means, by which the same switching function can be achieved.
  • said transistor control means and/or said control circuit are adapted for controlling first transistors of first half-bridges of said H- bridge circuit, such that they are switched on when the corresponding second transistor of the respective half-bridge of said transistor H-bridge circuit is switched off and vice versa. It is also possible that the dead times can be set individually.
  • gate drivers can be used which operate with an inverse output, and four gate drivers can be controlled by only two control signals.
  • either the upper or lower transistor is conducting, so that the output terminal of each half- bridge is either connected to the positive or negative rail of a DC link voltage across the H- bridge circuit.
  • said input circuit is adapted to generate a pulse signal having alternately positive and negative pulses of a pulse width, said pulse width being adapted to the resonant period of said resonance circuit.
  • said input circuit is adapted to generate a pulse signal having a freewheel path between the pulses, the freewheel time being variable to control the pulse signal, in particular to control the repetition frequency. This is particularly important in the case of a dimming operation and input voltage compensation.
  • preferred embodiments of the control circuit are defined. According to one embodiment said control circuit is adapted to generate said control signals based on a measured DC link voltage across said H-bridge circuit and on a predetermined average output current to said load. This allows a stabilisation of the DC link voltage.
  • said control circuit is adapted to generate two control signals having pulses which do not overlap in time, the first control signal being provided for control of the first two transistors of the H-bridge circuit and the second control signal being provided for control of the second two transistors of the H-bridge circuit.
  • the voltage related to the difference of these two control signals determines the output current.
  • the voltage related to the first control signal determines the input current of the H-bridge and thus the mains current. In case of a sinusoidal mains voltage, this results in an almost sinusoidal mains current.
  • said control circuit is adapted to two control signals having pulses which do partly overlap in time, the first control signal being provided for control of the first two transistors of the H-bridge circuit and the second control signal being provided for control of the second two transistors of the H-bridge circuit.
  • control circuit is adapted to generate two control signals having a constant switching frequency, rather than a changing switching frequency (changed simultaneously with the on-time of the transistors of the H-bridge). In this way flicker can be avoided or reduced. It is also advantageous that the control circuit is adapted to generate two control signals each having a fixed duty cycle, in particular a duty cycle of 25%, 50% or 75%. In this way zero voltage switching (ZVS) can be obtained.
  • ZVS zero voltage switching
  • control circuit is adapted to generate two control signals such that the product of switching frequency and DC link voltage is kept constant so that all transistors can be operated in ZVS mode.
  • Fig. 1 shows a block diagram of a known supply circuit
  • Fig. 2 shows the characteristic voltages and current waves of the supply circuit shown in Fig. 1
  • Fig. 3 shows a block diagram of a diode bridge rectifier circuit
  • Fig. 4 shows a block diagram of a preconditioner circuit
  • Fig. 5 shows a block diagram of an embodiment of a supply circuit according to the present invention
  • Fig. 6 shows control signals, converter current and output voltage of the supply circuit shown in Fig. 5 having a duty cycle of 25%
  • Fig. 7 shows the simulated averaged mains current for a sinusoidal mains voltage
  • Fig. 8 shows a further embodiment of control signals, converter current and output voltage of the supply circuit shown in Fig. 5 having a duty cycle between 25% and 40%
  • Fig. 9 shows a further embodiment of control signals, converter current and output voltage of the supply circuit shown in Fig. 5 having a duty cycle of 40%
  • Figs. 10 to 12 show a further embodiments of control signals, converter current and output voltage of the supply circuit shown in Fig. 5 having various duty cycles, but a constant switching period
  • Fig. 13 shows a further embodiment of control signals, converter current and output voltage of the supply circuit shown in Fig. 5 for achieving zero voltage switching
  • Fig. 14 shows the PFC current at different DC link voltages
  • Fig. 15 shows the switching frequency and PFC power for constant output current
  • Fig. 16 shows a block diagram of a rectifier circuit using thyristors only
  • Fig. 17 shows a block diagram of a rectifier circuit using thyristors and diodes
  • Fig. 18 shows a block diagram of a rectifier circuit using an additional switch
  • Fig. 19 shows a block diagram of another embodiment of a supply circuit according to the present invention.
  • Fig. 20 shows a block diagram of still another embodiment of a supply circuit according to the present invention.
  • Fig. 1 shows a supply circuit (also called driver) as described in European patent application 06110730.6 the description of which is herewith incorporated by reference.
  • this driver comprises a transistor H-bridge 12 having four transistors Tl, T2, T3, T4, a transformer Tr, a series capacitor Cs, a full bridge rectifier B2 and a smoothing capacitor Co connected in parallel to the load LE (here five LEDs).
  • the series capacitor Cs and the leakage inductance Ls of the transformer form a series resonant circuit, which is
  • Figs. 2 A and 2B show the characteristic voltages and current waves of this circuit.
  • the LED light can be dimmed by reducing the frequency — • fres ⁇ fs > 0 .
  • One standard solution for the required AC to DC conversion consists of a diode bridge rectifier comprising four diodes D1-D4 with a smoothing capacitor Cl as shown in Fig. 3.
  • the disadvantages of such a rectifier circuit can be solved by applying a preconditioner circuit as shown in Fig. 4, where apart from the diode bridge rectifier a boost converter (Tp, Dp, Lp) is used to control the current Im(t) drawn from the mains.
  • the current Im(t) can be controlled by the transistor Tp to be proportional to the mains voltage Um(t).
  • the low frequency harmonics are substantially reduced and a one-per-unit power factor can be achieved.
  • FIG. 5 An embodiment of the supply circuit according to the present invention is shown in Fig. 5. This embodiment is based on the H-bridge LED driver as shown in Fig. 1 extended with a mains rectifier Bl and an inductor Li and by applying an advanced control scheme to the H-bridge, as will be explained below.
  • the supply circuit comprises an input circuit 1 having input terminals 10, 11 for receiving an input supply voltage Us, the transistor H-bridge circuit 12 having separately controllable transistors Tl, T2, T3, T4 for converting said input supply voltage Us into a stabilised DC link voltage Ui and for converting the DC link voltage Ui into pulse voltage signal Ul (outputted by output terminals 122, 123), and an inductance circuit Li coupled between the first input terminal 10 and an upper H-bridge circuit input terminal 121.
  • the supply circuit further comprises an output circuit 2 comprising a resonance circuit formed by the capacitor Cs and the inductor Ls, a transformer Tr and a full bridge rectifier circuit B2 for converting said pulse voltage signal Ul into the output current Io and output terminals 20, 21 for outputting said output current Io to said load LE.
  • a control circuit is provided for generating control signals si, s2 for controlling the transistors Tl, T2, T3, T4 of said transistor H-bridge circuit 12.
  • the mains voltage Um is first rectified by a full bridge rectifier Bl (e.g. a simple diode bridge shown in Fig. 3, but without the smoothing capacitor Cl) of a supply signal conversion circuit 4. Its output terminals 10, 11 are connected in parallel to the transistor Tl of the H-bridge 12 via an inductor Li. Between the mains 5 and the rectifier bridge BI a low pass frequency filter Fl is inserted.
  • Bl full bridge rectifier
  • the inductor Li, the transistor Tl and the internal reverse diode of transistor T3 perform a boost converter function for the mains rectifier B 1. It can be used to draw an almost sinusoidal current from the mains 5 and to stabilize the DC link voltage Ui. Since the freewheel operation of the H-bridge 12 can either be realized by turning on Tl and T2 or by turning on T3 and T4 one degree of freedom is given to adapt the input mains current Im to the load LE.
  • the boost converter operates in the discontinuous mode. This results in a triangular input current whose peak value is proportional to the instantaneous mains voltage.
  • the low pass frequency filter Fl smoothes the high frequency triangular current so that the mains current is almost sinusoidal and contains no high frequency parts.
  • the power drawn from the mains 5 is set by mains voltage Um, the on-time of transistor Tl and the repetition frequency fs.
  • Input and output power should be equal, which can be set by the inductance Li of the choke (the lower the inductance Li the higher the input power).
  • a mains rectifier PFC function can be performed according to the present invention without influencing the resonant driver operation of the H-bridge to a variable LED load.
  • the H-bridge cl2 consisting of the transistors Tl, T2, T3 andT4 controls both the output current Io in the LED and the mains input current Im.
  • the DC link voltage Ui supplies the H-bridge.
  • a capacitor Ci is applied to smooth the DC link voltage Ui.
  • Each transistor Tl, T2, T3 andT4 is connected to a gate driver Gl, G2, G3, G4.
  • the two gate drivers of one half-bridge are turned-on and turned-off by a common binary control signal si, s2.
  • the lower gate drivers G3, G4 operate with an inverted output.
  • either the upper or the lower transistor is conducting, so that the output terminal of each half- bridge is either connected to the positive or the negative rail of the DC link voltage Ui.
  • the output terminals of the H-bridge are connected to the primary winding Nl of a transformer Tr via the series capacitor Cs.
  • the secondary winding N2 of the transformer Tr is connected to a full bridge rectifier B2. Its output feeds the LED load and a capacitor Co is used to smooth the current in the LEDs.
  • the full bridge rectifier Bl rectifies the mains voltage Um.
  • the positive terminal of the rectifier bridge is connected to the positive rail of the DC link voltage Ui via the inductor Li while the negative terminal of the bridge rectifier is connected to the output terminal of the first half-bridge Tl, T3.
  • a low-pass frequency filter Fl between the mains and the rectifier prevents HF currents in the mains.
  • the two control signals sl(t) and s2(t) are generated by the control unit 3.
  • This control unit measures the DC link voltage Ui and needs a set value for the desired average output current Io .
  • the operation of the whole converter will be explained by studying the signals sl(t) and s2(t) and the resulting output voltage Ul(t). This is illustrated in Fig. 6.
  • the repetition frequency fs is constant for a certain operation point but it can be varied to set another output current.
  • the rectifier part is shorted if signal sl(t) is in the on- state, and it is connected to the DC link voltage Ui if sl(t) is zero.
  • the inductor Li of the rectifier part is small. Preferred values are in the range from lO ⁇ H to ImH. This leads to a discontinuous current Ii(t). Hence, the current Ii(t) rises linearly if the signal sl(t) is HIGH. If sl(t) is LOW, transistor Tl is turned off. Since the DC link voltage Ui is larger than the rectified mains voltage
  • the characteristic current wave Ii(t) is also depicted in Fig. 6.
  • the peak value of the current Ii(t) is given by the equation: Since the on-time of transistor Tl is fixed, the peak value of current Ii(t) is proportional to the instantaneous voltage of the mains
  • the fall time tf of the current Ii(t) depends on the difference between the DC link voltage Ui and the absolute mains
  • both the inductor Li and the filter Fl are provided in the supply circuit.
  • the current Ii(t) flows discontinuously at a high frequency.
  • the filter Fl separates the high frequency part of current Ii(t). Under ideal conditions the line current Im(t) becomes sinusoidal at the mains frequency of 50Hz.
  • the filter Fl is optional.
  • the average current flowing into the capacitor Ci has to be equal to the average current drawn from the H- bridge / : ⁇ s ⁇ t)- Z 1 ( ⁇ . This condition can be fulfilled by varying the on-time of transistor
  • the inserted pulse enlargement ti can be used to stabilize the DC link voltage and thus to match input and output power
  • the time span tl of the freewheel operation of the H-bridge between the pulses s2(t) and sl(t) should be at least t ⁇ > ⁇ + ti . No extra restrictions are required for the freewheel operation between pulse sl(t) and s2(t). This time span t2 can be reduced down to t 2 ⁇ .
  • time span tl may be equal to time span t2.
  • t ⁇ max ⁇ .
  • the output current in the LEDs can still be controlled from a maximum value to zero by decreasing the switching frequency fs without influencing the power match, since the input and the output power vary proportionally to the switching frequency fs.
  • Potential applications of the invention are for example energy saving lamps with LEDs, ballasts for LED installations for general illumination. Also LCD backlight drivers could make use of the integrated preconditioner function.
  • the input voltage Ui may be directly supplied by a standard rectifier or by a PFC rectifier.
  • the PFC rectifier (as shown in Fig. 4) prevents mains interactions and draws a sinusoidal current from the mains.
  • a preconditioner instead of a simple rectifier (as shown in Fig. 3) it is also possible to stabilize the DC voltage Ui above the peak voltage of the mains.
  • the mains AC voltage is rectified by a diode bridge and connected in parallel to transistor Tl via the inductor Li.
  • the main advantage of the new concept is that PFC mains input performance can be achieved without the need for additional transistors and diodes.
  • the transistors Tl and T2 are not only used to control the output current in the load, but the transistor Tl and the inner diode of T2 also perform the function of the transistor Tp and the diode Dp in the PFC rectifier shown in Fig. 4. This means that the PFC performance is added to the circuit by only a modified control scheme, without the need for additional power semiconductors.
  • the boost converter of the PFC stage and the discontinuous series resonant converter with constant average current output are combined into a single stage as depicted in Fig. 5.
  • the big advantages of this topology are the reduced number of components and, hence a higher power density and reduced bill of materials.
  • the control algorithm described above uses a variable duty cycle for the boost operation in order to keep the DC link voltage Ui at a constant level.
  • the variation in duty cycle is achieved through alternating between the two freewheeling states. In the first freewheeling state, the upper two transistors Tl and T2 are closed and in the second freewheeling state, the lower two transistors T3 and T4 are closed. Additionally, on-time is added to the switching period of transistor Tl. Hence, the duty cycle of Tl can be varied between 25% and 40%.
  • This control technique enables the reduction of the DC link voltage. Hence, the rating of components can be reduced saving costs.
  • the resulting waveforms for this mode of operation are depicted in Fig. 8.
  • the graphs depicted in Fig. 6 show the waveforms for the case only the second freewheeling mode (T3 and T4) is used.
  • the on-time ton of Tl is enhanced by ⁇ .
  • the duty cycle has to be adjusted. This is done by varying the on-time ton of transistor Tl .
  • this control strategy might prevent that zero-voltage switching (ZVS) is obtained for all switching transitions leading to a reduction in efficiency.
  • ZVS zero-voltage switching
  • control guarantees a minimum duty cycle of 25%, so that dimming over a full range, i.e. down to zero, is not possible. Still further, there might be changes in the constant current output behavior.
  • further embodiments of the present invention are presented providing solutions for these possible problems.
  • the switching scheme presented in Figs. 6, 8 and 9 changes the on-time ton and the switching frequency fs simultaneously. This leads to a lower switching frequency fs if the on-time is enhanced. Of course, this leads to a higher input power, because it is proportional to the switching frequency and proportional to the square of the on-time.
  • the switching scheme can be set at the beginning of every mains period and kept constant during this mains period to avoid current peaks and to obtain sinusoidal mains currents (grid-cycle variation between 25% and 50% duty cycle).
  • the DC-link capacitor C 1n has to be designed bigger. This does not mean that the size of the converter also increases, because heat sinks of the switches can be made small (ZVS) and/or other passive components can be designed smaller (high switching frequency). If flicker is still a problem in some applications, only operation modes that guarantee no flicker can be allowed.
  • a solution is provided to control the PFC stage without changing the on-time of transistor Tl and to obtain ZVS.
  • the power of the converter which is delivered by the PFC stage, depends on the DC link voltage Ui (sometimes also called DC-bus voltage). At a lower DC link voltage Ui the PFC power is higher than at a high DC link voltage Ui.
  • the PFC inductor current Ii(t) is shown in Fig. 14 at high DC link voltage Ui (Fig. 14A) and at low DC link voltage Ui (Fig. 14B).
  • the reason for a difference in the power is the different time the current needs to slope down t 0 ff. At a lower DC link voltage, this time is longer. Sequentially, more energy is transferred from mains to the DC-bus.
  • This interrelation can be used to control the PFC power. If the load or the input voltage varies and the product of switching frequency and DC link voltage is kept constant, the converter will operate at stable operating points with different DC link voltages. With this control strategy, the converter only switches at its normal switching points. Consequently, all transistors can operate in ZVS mode.
  • Full range dimming can be achieved by replacing the rectifier diodes of the input rectifier bridge Bl (cf. Figs. 3 and 4) with electronic switches, e.g. thyristors.
  • Two examples for those embodiments of an input rectifier bridge are depicted in Figs. 16 and 17 using thyristors TyI- Ty4 only (Fig. 16) or using two thyristors TyI, Ty3 and two diodes D2, D4 (Fig. 17).
  • the gating of the thyristors TyI - Ty4 can be controlled by the central control unit 3 (cf. Fig. 5).
  • Another possibility is to add an electronic switch S to the input path as depicted in the example of Fig. 18.
  • the depicted transistor can be controlled by the central control unit 3.
  • the converter can be disconnected from mains in order to reduce the power delivered by the preconditioner.
  • the embodiment presented in Fig. 5 uses only one PFC inductor Li. Additionally, the PFC operates in discontinuous boost mode. This might lead to a high current ripple. Consequently, the PFC stage may cause losses and possibly requires an input filter to avoid mains current disturbance.
  • a solution to achieve lower losses and a smaller input current ripple is the use of two PFC inductors LiI, Li2 as shown in the embodiment depicted in Fig. 19. Each of the two PFC inductors LiI, Li2 is connected to a half-bridge of the full-bridge converter 12. Both PFC inductors LiI, Li2 are decoupled by diodes DiI, Di2.
  • both PFC inductors LiI, Li2 are used alternately resulting from the switching scheme of the full bridge 12.
  • the first PFC inductor LiI is used at the beginning of the switching period and the second PFC inductor Li2 is used after the half switching period.
  • the peak currents of the inductors LiI, Li2 will be lower if the same power is delivered. Consequently, losses of the inductors LiI, Li2 may become lower and the input current ripple will be lower, due to the decreased peak currents and two discontinuous boost PFC converters are used alternately.
  • the PFC current Ii is distributed more evenly on all four transistors Tl - T4. This can reduce the transistor losses of the converter.
  • FIG. 20 shows a block diagram of still another embodiment of a supply circuit according to the present invention.
  • These additional elements provide for a softer switching of the transistors T1-T4. This is achieved by zero voltage switching.

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  • Dc-Dc Converters (AREA)
  • Circuit Arrangement For Electric Light Sources In General (AREA)

Abstract

La présente invention porte sur un circuit d'alimentation pour fournir un signal de sortie à une charge, en particulier pour fournir un courant de sortie continu (Io) à une unité de lampe électronique (LE), comprenant un circuit d'entrée (1) comprenant des bornes d'entrée (10, 11) pour recevoir un signal d'alimentation d'entrée (Us), un circuit à pont en H à transistors (12) ayant des transistors (T1, T2, T3, T4) commandables séparément pour convertir ledit signal d'alimentation d'entrée (Us) en un signal d'impulsion (Ul), et un circuit d'inductance (Li) couplé entre une borne d'entrée (10, 11) et une borne d'entrée (121) de circuit à pont en H, un circuit de sortie (2) comprenant un circuit résonant (Cs, Ls), un transformateur (Tr) et un circuit redresseur de sortie (B2), en particulier un circuit à pont redresseur pleine onde, pour convertir ledit signal d'impulsion (Ul) en ledit signal de sortie (Io), et des bornes de sortie (20, 21) pour fournir ledit signal de sortie (Io) à ladite charge (LE), un circuit de commande (3) pour générer des signaux de commande (si, s2) pour commander les transistors (T1, T2, T3, T4) dudit circuit à pont en H à transistors (12).
PCT/IB2008/052259 2007-06-13 2008-06-09 Circuit d'alimentation, en particulier pour del WO2008152565A2 (fr)

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DE102010031233A1 (de) * 2010-03-19 2011-09-22 Tridonic Ag LED-Betriebsschaltung mit adaptivem isolierenden energieübertragenden DC/DC-Wandler
DE102010031239A1 (de) * 2010-03-19 2011-09-22 Tridonic Ag LED-Ansteuerung mit getakteter Konstantstromquelle
EP2464198A1 (fr) * 2010-12-13 2012-06-13 Schneider Electric Industries SAS Dispositif et procédé d'alimentation pour système d'éclairage à diodes électroluminescentes et ensemble d'éclairage comportant un tel dispositif
CN102550128A (zh) * 2009-09-30 2012-07-04 皇家飞利浦电子股份有限公司 Led驱动器的调光
DE102011000441A1 (de) * 2011-02-01 2012-08-02 Vossloh-Schwabe Deutschland Gmbh Betriebssteuergerät und Verfahren zum Dimmen eines Leuchtmittels über die Versorgungsspannung und die Spannungsfrequenz
WO2012137130A3 (fr) * 2011-04-04 2013-01-24 Sgm A/S Procédé d'attaque de diodes électroluminescentes
WO2013092662A1 (fr) * 2011-12-23 2013-06-27 Tridonic Gmbh & Co Kg Convertisseur à del à cfp adaptatif et convertisseur à résonance
US8624520B2 (en) 2010-04-30 2014-01-07 Minebea Co., Ltd. Electrical appliance having a lighting device having light emitting diodes
WO2014064578A1 (fr) * 2012-10-25 2014-05-01 Koninklijke Philips N.V. Dispositif de pilotage et procédé de pilotage pour piloter une charge, en particulier une unité de del
US9225254B2 (en) 2009-02-26 2015-12-29 Koninklijke Philips N.V. Supply circuit having at least one switching unit coupled between a bridge circuit and an associated load circuit
US9282600B2 (en) 2009-03-23 2016-03-08 Koninklijke Philips N.V. Transformerless resonant boost supply circuit
WO2018137240A1 (fr) 2017-01-26 2018-08-02 Redisem Ltd. Circuit convertisseur de puissance
US10103631B2 (en) 2014-03-24 2018-10-16 Redisem Ltd. Power converter circuit and method thereof
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US9225254B2 (en) 2009-02-26 2015-12-29 Koninklijke Philips N.V. Supply circuit having at least one switching unit coupled between a bridge circuit and an associated load circuit
US9282600B2 (en) 2009-03-23 2016-03-08 Koninklijke Philips N.V. Transformerless resonant boost supply circuit
CN102550128A (zh) * 2009-09-30 2012-07-04 皇家飞利浦电子股份有限公司 Led驱动器的调光
US8836225B2 (en) 2009-09-30 2014-09-16 Koninklijke Philips N.V. Dimming of LED driver
CN102907173A (zh) * 2010-03-19 2013-01-30 特里多尼克股份有限公司 带有以时钟信号工作的恒流源的led 操控部
DE102010031239A1 (de) * 2010-03-19 2011-09-22 Tridonic Ag LED-Ansteuerung mit getakteter Konstantstromquelle
WO2011113960A3 (fr) * 2010-03-19 2012-03-29 Tridonic Ag Circuit de commande de del comprenant un convertisseur cc/cc isolant à transfert d'énergie
DE102010031233A1 (de) * 2010-03-19 2011-09-22 Tridonic Ag LED-Betriebsschaltung mit adaptivem isolierenden energieübertragenden DC/DC-Wandler
US8624520B2 (en) 2010-04-30 2014-01-07 Minebea Co., Ltd. Electrical appliance having a lighting device having light emitting diodes
US8593081B2 (en) 2010-12-13 2013-11-26 Schneider Electric Industries Sas Power supply device and method for a lighting system with light-emitting diodes and lighting assembly comprising one such device
CN102548131A (zh) * 2010-12-13 2012-07-04 施耐德电器工业公司 具有发光二极管的照明系统的电源设备和方法及照明组件
CN102548131B (zh) * 2010-12-13 2015-05-20 施耐德电器工业公司 具有发光二极管的照明系统的电源设备和方法及照明组件
FR2968887A1 (fr) * 2010-12-13 2012-06-15 Schneider Electric Ind Sas Dispositif et procede d'alimentation pour systeme d'eclairage a diodes electroluminescentes et ensemble d'eclairage comportant un tel dispositif
EP2464198A1 (fr) * 2010-12-13 2012-06-13 Schneider Electric Industries SAS Dispositif et procédé d'alimentation pour système d'éclairage à diodes électroluminescentes et ensemble d'éclairage comportant un tel dispositif
DE102011000441A1 (de) * 2011-02-01 2012-08-02 Vossloh-Schwabe Deutschland Gmbh Betriebssteuergerät und Verfahren zum Dimmen eines Leuchtmittels über die Versorgungsspannung und die Spannungsfrequenz
DE102011000441B4 (de) * 2011-02-01 2014-12-18 Vossloh-Schwabe Deutschland Gmbh Betriebssteuergerät und Verfahren zum Dimmen eines Leuchtmittels über die Versorgungsspannung und die Spannungsfrequenz
WO2012137130A3 (fr) * 2011-04-04 2013-01-24 Sgm A/S Procédé d'attaque de diodes électroluminescentes
US9332604B2 (en) 2011-12-23 2016-05-03 Tridonic Gmbh & Co Kg LED converter with adaptive PFC and resonant converter
WO2013092662A1 (fr) * 2011-12-23 2013-06-27 Tridonic Gmbh & Co Kg Convertisseur à del à cfp adaptatif et convertisseur à résonance
US11330688B2 (en) * 2012-06-15 2022-05-10 Aleddra Inc. Solid-state lighting with reduced light flickering
WO2014064578A1 (fr) * 2012-10-25 2014-05-01 Koninklijke Philips N.V. Dispositif de pilotage et procédé de pilotage pour piloter une charge, en particulier une unité de del
US9363856B2 (en) 2012-10-25 2016-06-07 Koninklijke Philips N.V. Driver device and driving method for driving a load, in particular an LED unit
CN104380844B (zh) * 2012-10-25 2017-07-28 飞利浦灯具控股公司 用于驱动负载尤其是led单元的驱动器设备和驱动方法
CN104380844A (zh) * 2012-10-25 2015-02-25 皇家飞利浦有限公司 用于驱动负载尤其是led单元的驱动器设备和驱动方法
US10103631B2 (en) 2014-03-24 2018-10-16 Redisem Ltd. Power converter circuit and method thereof
WO2018137240A1 (fr) 2017-01-26 2018-08-02 Redisem Ltd. Circuit convertisseur de puissance
US11309790B2 (en) 2017-01-26 2022-04-19 Redisem Ltd. Power converter circuit

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