WO2006032211A1 - Multicell joint detection method in slotted code division multiple access system - Google Patents

Multicell joint detection method in slotted code division multiple access system Download PDF

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Publication number
WO2006032211A1
WO2006032211A1 PCT/CN2005/001539 CN2005001539W WO2006032211A1 WO 2006032211 A1 WO2006032211 A1 WO 2006032211A1 CN 2005001539 W CN2005001539 W CN 2005001539W WO 2006032211 A1 WO2006032211 A1 WO 2006032211A1
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Prior art keywords
code channel
code
channel
joint detection
interference
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PCT/CN2005/001539
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English (en)
French (fr)
Inventor
Yingmin Wang
Nan Zhong
Shiyan Ren
Ning Liu
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Da Tang Mobile Communications Equipment Co., Ltd.
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Priority to KR1020077008939A priority Critical patent/KR100874507B1/ko
Priority to EP05791531A priority patent/EP1793518A4/en
Priority to JP2007532750A priority patent/JP4866357B2/ja
Priority to US11/663,789 priority patent/US8023486B2/en
Publication of WO2006032211A1 publication Critical patent/WO2006032211A1/zh

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    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H04B1/7103—Interference-related aspects the interference being multiple access interference
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H04B1/7103—Interference-related aspects the interference being multiple access interference
    • H04B1/7105—Joint detection techniques, e.g. linear detectors
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04J—MULTIPLEX COMMUNICATION
    • H04J13/00—Code division multiplex systems
    • H04J13/16—Code allocation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L25/00—Baseband systems
    • H04L25/02—Details ; arrangements for supplying electrical power along data transmission lines
    • H04L25/0202—Channel estimation
    • H04L25/0204—Channel estimation of multiple channels
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/69—Spread spectrum techniques
    • H04B1/707—Spread spectrum techniques using direct sequence modulation
    • H04B1/7097—Interference-related aspects
    • H04B1/7103—Interference-related aspects the interference being multiple access interference
    • H04B1/7107—Subtractive interference cancellation
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B2201/00—Indexing scheme relating to details of transmission systems not covered by a single group of H04B3/00 - H04B13/00
    • H04B2201/69—Orthogonal indexing scheme relating to spread spectrum techniques in general
    • H04B2201/707—Orthogonal indexing scheme relating to spread spectrum techniques in general relating to direct sequence modulation
    • H04B2201/70702—Intercell-related aspects

Definitions

  • the present invention relates to a joint detection method in the field of mobile communication technologies, and more particularly to a wireless communication system suitable for a slot code division multiple access (CDMA) system or a signal structure similar to a slot code division multiple access system signal structure. Multi-cell joint detection method. Background of the invention
  • joint detection techniques can be used for the received local cell signal to eliminate multiple access interference and intersymbol interference.
  • the joint detection method is to use the transmission signal of all users in the cell and the information of the channel response thereof to complete the signal detection as a unified interrelated joint detection process. Since the joint detection technique effectively suppresses intersymbol interference and multiple access interference in the cell, the performance of the code division multiple access system is greatly improved.
  • the Time Division Duplex-Synchronous Code Division Multiple Access (TD-SCDMA) system is a time slot CDMA system that uses a joint detection scheme for multi-user signals in the cell.
  • the burst signal structure of the regular time slot is as shown in Fig. 1:
  • the midamble (middle code, also called channel estimation code) in the middle of the burst signal is used for channel estimation, and the data blocks on both sides are used. Transfer business data.
  • e is the sampled data received by the receiver
  • d is the transmitted data
  • n is the received noise
  • matrix A is the transmission matrix.
  • the transmission matrix A consists of the combined response vectors of the individual code channels
  • k is the code channel number, assuming a total of K code channels (according to the A matrix, w Is a column in each block of the matrix that is distributed on the diagonal).
  • Each vector corresponds to a combined channel response of a user code channel with a code track number k:
  • C ( « is the spreading code of the user code channel corresponding to the code track number k
  • ten is the convolution operator
  • h w is the channel response of the corresponding code channel of the code track number k
  • using the midamble is obtained by channel estimation.
  • the soft output value of the demodulated transmitted data d is estimated as:
  • R d E ⁇ d.(f T ⁇ )
  • R d I
  • I represents the identity matrix.
  • MF in (6) is the matching filter, and the corresponding is the matching filtering method
  • ZF-BLE is a Zero-Forcing Block Liner Equaliaer method, which corresponds to the maximum likelihood linear solution
  • MMSE-BLE is the Zero-Forcing Block Liner Equaliaer The method corresponds to a linear solution of the minimum mean square error.
  • the above three methods for solving T can be selected, and the second ZF-BLE or the third MMSE-BLE method is usually selected.
  • the single cell joint detection method utilizes structural information (including a spreading code and a channel response) of signals transmitted by all users of the cell, that is, only the signal structure information of the current cell is used, and at this time, the detection method treats the interference signals of other cells as The Gaussian white noise of time is processed, so the single cell joint detection algorithm has strong ability to suppress intersymbol interference and local cell multiple access interference.
  • the single cell joint detection method can greatly improve the performance of the system for a single-cell or multi-frequency network code division multiple access system.
  • the single-cell joint detection algorithm can also improve the performance of the system.
  • the same-frequency networking there is strong mutual interference between the signals of the same-frequency neighboring cells, and the interference between the adjacent-frequency neighboring cells has a very important impact on the performance of the system, especially in the same At the intersection of adjacent frequency cells, co-channel interference is often the most important interference.
  • the single-cell joint detection method will be incapable of interference to the same-frequency neighboring cell.
  • the system performance will be Significant decline.
  • the neighbor cell user signal will cause a large interference to the user signal of the cell.
  • the single cell joint detection method will seriously degrade the system performance.
  • the system performance of the single cell joint detection method will be significantly reduced, and the system performance requirements are often not met, and a better joint detection method needs to be provided.
  • the joint detection technology is extended from a single cell to an intra-frequency multi-cell, It can greatly improve the performance of the time slot CDMA system in the same frequency networking.
  • each neighboring cell gives a different intermediate code as the basic code when generating the channel estimation code
  • different users of the cell use different cyclically shifted versions of the basic code as its channel estimation code, thus, one cell
  • These different cyclically shifted versions may be referred to as a code set, and multiple cells have multiple code sets, and thus the channel estimate of the multi-code set is the channel estimate of the multi-cell.
  • slot code division multiple access system multi-code set channel estimation method a multi-slot code division multiple access system is disclosed.
  • a code set channel estimation method that is, a multi-cell channel estimation method.
  • An object of the present invention is to provide a multi-cell joint detection method for a slot code division multiple access system, which implements multi-cell joint detection by using multi-cell structure information in the case where mutual frequency multi-cell interference occurs.
  • the method provided by the present invention will greatly improve the system performance of the time slot CDMA system when operating in the same frequency neighboring cell.
  • a multi-cell joint detection method for a slot code division multiple access system which utilizes structural information of multiple intra-frequency neighboring cells for joint detection, and is characterized by the following steps: A. obtaining channel estimation results of each neighboring cell by using a multi-code set channel estimation method;
  • joint detection is performed by the joint detection method to obtain the detection data.
  • the present invention utilizes a multi-code set channel estimation method to obtain channel estimation results of respective neighboring cells; and performs code channel grouping on the code channels of each neighboring cell according to the grouping method of the present invention
  • the grouping method includes grouping based on cells to which the code channel belongs, A packet based on code channel power or amplitude strength, a packet based on code channel correlation strength, and a hybrid packet thereof, and a joint detection using channel estimation results and code channel grouping results of respective neighboring cells.
  • the joint detection process specifically includes constructing an A matrix; matching filtering; and finally completing multi-cell joint detection. When different code channel grouping methods are used, the constructed A matrix will be different, and thus some differences will be brought about by joint detection using channel estimation results and code channel grouping results.
  • the method of the present invention can fully utilize the structure information of multiple cell signals to perform multi-cell joint detection, thereby greatly suppressing multiple access interference of the same frequency neighboring cell.
  • the method provided by the invention will greatly improve the system performance of the time slot CDMA system when operating in the same frequency neighboring cell.
  • Figure 1 shows the slot burst structure of the TD-SCDMA service.
  • FIG. 2 is a schematic block diagram of a general flow of multi-cell joint detection in a time slot CDMA system.
  • 3 is a flow chart of a system for multi-cell joint detection based on cell code channel grouping.
  • FIG. 4 is a system flow diagram of a packet embodiment embodiment for multi-cell joint detection based on code channel amplitude or power packets or based on code channel correlation. Mode for carrying out the invention
  • the present invention proposes a joint detection method based on multi-cell structure information.
  • the steps of the specific implementation method are shown in Figure 2.
  • the first step is multi-cell channel estimation.
  • the channel estimation result of each neighboring cell is obtained by the channel estimation method of the multi-code set introduced in the background art. Because each neighboring cell is given a different intermediate code as the base when generating the channel estimation code, different users of the cell use different cyclically shifted versions of the basic code as its channel estimation code, one cell.
  • the different cyclically shifted versions of these basic codes are called a code set, and multiple cells have multiple code sets, so the channel estimation of the multi-code set is the channel estimation of the multi-cell.
  • the multi-cell channel estimation in the technical solution of the present invention utilizes the multi-code set channel estimation technology in the patent application No.
  • the processed multi-code set joint channel iterative estimation method obtains channel estimation results of multiple cells.
  • the multi-cell of the channel estimation is a neighboring cell, and the neighboring cell includes the local cell where the user to be detected is located and the cell that is the most adjacent to the local cell in the geographical location.
  • the second step is the code channel grouping.
  • the code channel grouping method is determined, and then the code channels of the respective neighboring cells are code-coded according to a selected grouping method.
  • the specific scheme of the present invention for determining code channel grouping is as follows:
  • the first type is a grouping method based on a cell to which a code track belongs. There are several co-frequency cells set up in several groups, then the code channel in each group is the code channel of the corresponding cell.
  • the second is a grouping method based on code channel power or amplitude.
  • the combined channel response of each code channel can be obtained, or the output result of each code channel matched filter can be used to estimate the amplitude or power of each code channel signal (the amplitude can be obtained by squaring), and then Grouping according to the strength of the amplitude or power. For example, determining a threshold value of amplitude or power, the amplitude or power of the code channel signal is greater than the threshold value, and is lower than the threshold
  • the code value is weak, the code channel with strong amplitude or power is one group, and the code channel with weak power or amplitude is another group.
  • the third is a grouping method based on code channel correlation.
  • the combined channel response of each code channel is obtained by using the multi-cell channel estimation result, and the correlation between each code channel in the multi-cell signal is estimated by using the combined channel response of each code channel, and then all the code channels are matched according to the strength of the correlation.
  • Group by For example, a threshold value of correlation is determined, a correlation between code channels is greater than the threshold value, and a value lower than the threshold value is weak, and a code channel with strong correlation is divided into a group, and a code with weak correlation is used. The road is divided into another group.
  • the correlation of multiple code channels can be average correlation, maximum correlation, or minimal correlation.
  • the joint detection uses the multi-cell channel estimation result and the result of the code channel grouping to perform joint detection, and obtains the multi-cell joint detection result.
  • the joint detection method may be an interference cancellation method, a linear block equalization method, or a mixture of the two.
  • the code channel participating in the code channel grouping may be a code channel pre-allocated by each neighboring cell (grouping without activation processing:), or All the code channels of the neighboring cells that have been retained after the activation detection process are retained (required to be activated before being grouped).
  • the code channel participating in the joint detection may be a pre-allocated code channel of each neighboring cell (joint detection by code channel group without activation processing), or may be all codes of the adjacent cell.
  • the active code channels that are retained after the activation detection process (requires activation processing and then joint detection by code channel grouping).
  • the secondary activation detection may be performed, that is, the activation code channel after the activation detection process is performed before the grouping, the matched filtering is performed after the grouping, and the secondary activation detection is performed, and the secondary activation code channel passing the detection is jointly detected.
  • the meaning of grouping the code channels in the method of the present invention is also: because when a plurality of adjacent cells are allocated a large number of code channels when working in the same frequency neighboring cell, the code channel can be activated and detected first. After activating the detection process, a large number of active code channels will still exist in the multi-cell. In order to achieve multi-cell joint detection with low cost and good performance, those active code channels that have been retained after the activation detection process are grouped. Further, the method of grouped joint detection is further adopted.
  • the multi-user signal of the same-frequency cell in the cell can be expressed as:
  • Step 31 Perform data segmentation on the multi-user signal e, that is, divide the conventional slot burst structure shown in FIG. 1, and divide the segmented intermediate code portion e m (the received signal of the intermediate code or the channel estimation code) The response signal is sent to the multi-cell channel estimation, and the segmented data symbol portion e d is sent for matching filtering.
  • Step 32 multi-cell channel estimation.
  • the channel estimation code portions of the three co-frequency cells respectively correspond to the channel estimation code signals e ml , em2 , and e m3 of the three code sets, and thus the total channel estimation code portion received is en ⁇ enn+e ⁇ +ems.
  • the channel estimation results of three co-frequency neighboring cells can be obtained (for details, see: CN03100670.1, 2003.05.09 "Slot Code Division Multiple Access System Multi-Code Set Channel" Estimate method ").
  • Step 37 the code channel grouping, grouping the code channels of the three cells.
  • the code channel can be divided into three groups according to the number of cells.
  • Step 38 using b w to construct the transfer matrix A in equations (8)-(10) (according to formula (2), obtained by h ( ").
  • the grouping method used construct equation (8)- The corresponding transmission matrix in (10).
  • the constructed transmission matrix A is the transmission matrix A Q , ⁇ > A 2 of the three cells.
  • the constructed three cells ⁇ transmission matrix A., Aj A 2
  • the joint detection of step 39 is sent separately.
  • step 39 the multi-cell joint detection is finally completed.
  • the joint detection can adopt the method of "linear block equalization + interference cancellation", that is, the joint detection method using linear block equalization in three groups, and the joint detection method using interference cancellation between the three groups. Includes:
  • the interference of the non-interfering cell 1 signal is obtained by using the single cell joint detection method (formula (3)) to obtain d l 5 to obtain d 2 .
  • the interference recovery is performed by the detected group results, and the interference of the interfering cell 1 and the interfering cell 2 to the user of the cell ⁇ , A 2 d 2 are obtained respectively .
  • Step 4) Perform joint detection of linear block equalization on the net signal of the packet to be detected by the user, and obtain a transmission signal result d Q (formula (3)) of the user to be detected.
  • Step 4) Obtained d 0 phase d obtained by the method of joint detection by single cell directly in step 1. , because the elimination of the same frequency neighbor cell interference, will be more accurate.
  • the above process is only a process of using one interference cancellation, and a process of multiple interference cancellation can also be used.
  • the specific implementation method that needs to be cancelled one or more times can be done by setting the number of iterations and looping through the "linear block equalization + interference cancellation" step.
  • the number of iterations is the number of times the interference is cancelled. Proceed as follows:
  • step 2 1) performing a single-cell joint detection on each code channel group by using a linear block equalization method, detecting a joint detection result of each group, and determining whether the number of iterations is reached, and if yes, outputting the joint detection result of the group of the user to be detected, otherwise Perform step 2);
  • the receiving signal cancels the interference component of the non-group, and obtains the net signal of each group
  • the linear block equalization method described above obtains the detected data according to the formula (3), and e in the equation (3) is the net signal after the interference cancellation.
  • the second embodiment of the present invention based on code channel amplitude or power grouping or a third type of code channel correlation based grouping will be specifically described below with reference to FIG.
  • steps 31, 32 are the same as the steps of Figure 3.
  • step 33 if the grouping method based on the code channel amplitude or power is used, the combined channel response of each code channel is obtained according to the channel estimation result, and then the amplitude or power of each code channel signal is estimated, or The power of each code channel signal is estimated by the output result of each code channel matching filter; then, all the code channels are divided into two groups according to the strength of the power, and the code channel of the user to be detected (refer to joint detection) and the power are stronger.
  • the interference code channel is divided into the code channel group participating in the joint detection, and the interference code channel that does not include the user to be detected and whose power is weak is divided into the interference code channel group.
  • the interference code channel refers to other user code channels except the user code channel to be detected, including other user code channels of the local cell and the same User code channel of the frequency neighboring cell.
  • the grouped data symbol total received signal e d can be expressed as:
  • 5 and (1 are the transmission matrix and the transmission data participating in the joint detection of the code channel group; and d, the transmission matrix and the transmission data of the interference code channel group.
  • the combined channel response of each code channel is obtained by the channel estimation result of each neighboring cell, and then all code codes of the non-to-be-detected user code and the user to be detected are estimated.
  • the mean value of the correlation of the track and then divide all the code channels into two groups according to the strength of the correlation mean, and all the code channels of the user to be detected and all the code channels with the highest correlation with the code channel are divided into the participation joints.
  • the detected code channel group the remaining code channels that do not contain the user to be detected and whose average correlation is weak are classified into the interference code channel group.
  • the grouped data symbol total received signal e d can be expressed as:
  • e d A s d s + (A 7 d 7 + n 0 ) (10) where, the sum (1 5 is the transmission matrix and the transmission data participating in the joint detection of the code channel group; and d, is the interference code channel group
  • the transmission matrix and the transmission data (the second and third grouping methods, the same expression is applied to the grouped data symbol total received signal e d ).
  • Step 34 using b w to construct the transfer matrix A in equations (8)-(10) ( obtaining b w from h (i) according to formula (2)) 0 according to the grouping method used, constructing equation (8)- The corresponding transmission matrix ⁇ in (10). , ⁇
  • the constructed transmission matrix A is A s (the transmission matrix participating in the joint detection code channel group), (the transmission matrix of the interference code channel group not participating in the joint detection).
  • Step 35 Calculate the formula according to the formula (3) of the soft output value estimated by the transmission data d.
  • the process of ⁇ TR, is the matching filtering process of this step.
  • e is the data symbol portion e d after data segmentation
  • A is the constructed matrix.
  • a in the matching filtering process is A s .
  • R n is the covariance matrix of the colored noise sequence n.
  • step 36 the multi-cell joint detection is finally completed.
  • Multi-cell joint detection is performed for different code channel grouping methods and different transmission matrices constructed, that is, T is obtained by one method in formula (4), and then the formula is completed on the basis of matching filtering to obtain ' 7 ⁇ ; ).
  • the joint detection method of linear block equalization is performed on the code channel groups participating in the joint detection.
  • a s and A obtained when the transmission matrix A is constructed wherein A s is a transmission matrix constructed by the current user code channel of the current cell plus the power or correlation of the cell or the neighboring cell, and is used for multi-user joint detection; It is a transmission matrix of the code channel structure of other users or neighboring cells of the cell with low power or correlation, and is used to calculate R n .
  • the covariance matrix R n in which the colored noise interferes can be calculated by the interference code channel grouping and the background noise, and the expression is:
  • Another method is to treat the co-channel interference in the interference code channel packet as a white noise, as shown in the following equation (14):
  • Steps 32, 33, 34, 35, 36 of Figure 3 or steps 32, 37, 38, 39 of Figure 4 are collectively referred to as the multi-cell joint detection process of the method of the present invention. That is, steps 1, 2, and 3 in Figure 2.
  • the method of the present invention can be applied to a time slot CDMA system or a wireless communication system employing a similar signal structure.

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Description

时隙码分多址系统多小区联合检测方法 技术领域
本发明涉及移动通信技术领域的联合检测方法， 更确切地说是涉及 一种适用于时隙码分多址 (CDMA)系统或采用类似于时隙码分多址系统 信号结构的无线通信系统的多小区联合检测方法。 发明背景
在 CDMA移动通信系统中， 存在着严重的多址干扰和符号间干扰。 在时隙 CDMA 系统中， 对接收的本小区信号可以采用联合检测技术来 消除多址干扰与符号间干扰。 联合检测方法是利用本小区所有用户的发 送信号及其信道响应的信息， 把信号检测当作一个统一的相互关联的联 合检测过程来完成。 由于联合检测技术有效地抑制了符号间干扰和本小 区的多址干扰， 故极大地提高了码分多址系统的性能。
时分双工-同步码分多址 ( TD-SCDMA ) 系统是一种对本小区多用 户信号采用了联合检测方案的时隙 CDMA系统。在 TD-SCDMA系统中， 常规时隙的突发信号结构如图 1所示： 突发信号中部的 midamble (中间 码， 也称为信道估计码）用来进行信道估计， 两边的数据块用来传送业 务数据。
TD-SCDMA系统的单小区联合检测的具体过程如下：
首先得到时隙 CDMA系统单小区接收机接收到的信号模型：
e = Ad + n ( \ )
其中， e为接收机收到信号的采样数据， d为发送数据， n为接收到 的噪声， 矩阵 A为传输矩阵。 传输矩阵 A由各个码道的组合响应向量 构成, k是码道编号,假设总共有 K个码道 (根据 可以计算 A矩阵， w 是矩阵中分布在对角线上的各个块中的一列）。
每个向量 对应为一个码道编号为 k的用户码道的组合信道响应：
bw=cw@hw k=l-K (2)
其中， C(«是对应的码道编号为 k的用户码道的扩频码， ㊉是卷积 运算符， hw是对应的码道编号为 k 的用户码道的信道响应， 利用 midamble (中间码）进行信道估计得到。
然后利用上述信息就可以进行联合检测。 联合检测算法有多种， 可 以是干扰抵消的方法， 可以是线性块均衡的方法， 也可以是两者方法的 混合。对线性块均衡的方法，经解调后的发送数据 d估计的软输出值为：
(3) 其中， 矩阵 T由下式给出
Figure imgf000004_0001
式中， *T是共轭转置， Rd=E{d.(fT}, 是数据序列 d的协方差矩阵， 对于相互独立的数据序列， Rd = I ; Rn =E{n-n*T}, 是噪声序列 n的协 方差矩阵。 对于相互独立且平稳的噪声序列 （如白噪声） Rn = σ2 I, I 表示单位矩阵。 在 Rd = I和 ΙΙη = σ2Ι的条件下， （3)、 （4) 式可以简化表示为：
d = (T)— 1 A*Te (
MF
T = Α*ΤΑ ZF-BLE
Α*τΑ + σ2 MMSE-BLE
(6)
(4)、 (6)式中的 MF即匹配滤波， 对应的就是匹配滤波的方法; ZF-BLE即迫零线性块均衡（ Zero-Forcing Block Liner Equaliaer )的方法， 对应的是最大似然的线性解； MMSE-BLE 即最小均方误差线性块均衡 ( Zero-Forcing Block Liner Equaliaer ) 的方法， 对应的是最小均方误差 的线性解。上述三种求解 T的方法择其一即可，通常选择第二种 ZF-BLE 或第三种 MMSE-BLE方法。
单小区联合检测方法， 利用小区所有用户发送信号的结构信息（包 括扩频码和信道响应）， 即利用的只是本小区的信号结构信息， 这时， 检测方法将其它小区的干扰信号都当成是时间的高斯白噪声来进行处 理， 所以， 单小区联合检测算法对抑制符号间干扰和本小区多址干扰有 较强的能力。 单小区联合检测方法对于单小区或异频组网的码分多址系 统， 可极大地提高系统的性能。
对于相邻小区同频组网的时隙 CDMA 系统， 采用单小区联合检测 算法也可以提高系统的性能。 但是， 在同频组网情况下， 同频相邻小区 信号之间存在着较强的相互干扰， 且同频相邻小区之间的干扰对系统的 性能有非常重要的影响， 尤其是在同频相邻小区的交界处， 同频干扰往 往是最重要的干扰， 此时， 单小区联合检测的方法对同频邻小区的干扰 将无能为力， 在同频相邻小区干扰存在时， 系统性能将明显下降。
例如， 小区交界处有同频相邻小区用户在多个码道工作时， 尤其是 扩频增益较小的系统， 相邻小区用户信号将会对本小区用户信号造成艮 大的干扰。 在这种情况下， 单小区联合检测方法将会使系统性能严重恶 化。
因此， 时隙 CDMA蜂窝移动通信系统在同频相邻小区工作的情况 下， 采用单小区联合检测方法系统性能会明显下降， 往往不能达到系统 对性能的要求， 需要提供性能更好的联合检测方法。 如果能够利用同 频相邻小区的结构信息， 将联合检测技术从单小区扩展到同频多小区， 就可极大地提高时隙 CDMA系统同频组网时的性能。
为了获得除本小区外的同频相邻小区的结构信息， 需要很多先验信 息， 其中很重要的一类先验信息就是除本小区外的同频相邻小区的信道 估计结果， 即多小区信道估计结果。 因为在生成信道估计码时， 每个相 邻小区给定一个不同的中间码作为基本码， 该小区不同的用户采用这个 基本码的不同循环移位版本作为它的信道估计码， 这样， 一个小区的这 些不同的循环移位版本可以称作一个码集， 多个小区就有多个码集， 因 而多码集的信道估计就是多小区的信道估计。
在本申奇人的中国专利申倩号为 03100670.1、 发明名称为 "时隙码 分多址系统多码集信道估计方法" 的技术方案中， 公开了一种时隙码分 多址系统中的多码集信道估计方法， 也即多小区信道估计方法。
该技术方案对单码集信道估计结果进行有限时间判决处理， 只保留 具有较强信号响应的有限个抽头， 由此恢复出其它码集干扰信号， 并抵 消该干扰信号， 得到各个码集的净信号， 再将各个码集的净信号进行单 码集信道估计， 重复上述处理直至达到迭代次数后， 输出多码集即多小 区信道估计结果。 发明内容 本发明的目的在于提供一种时隙码分多址系统多小区联合检测方 法， 针对存在同频多小区相互干扰的情况， 利用多小区结构信息实现多 小区联合检测。 本发明提供的方法将大大提高时隙 CDMA 系统在同频 相邻小区工作时的系统性能。
实现本发明目的的技术方案是这样的： 一种时隙码分多址系统多小 区联合检测方法， 利用多个同频相邻小区的结构信息进行联合检测， 其 特征在于包含如下步骤： A. 利用多码集的信道估计方法得到各个相邻小区的信道估计结果；
B. 从预定的码道分组方法中选择至少一种分组方法， 对所述各个 相邻小区的码道进行码道分组；
C. 利用所述各个相邻小区的信道估计结果和码道分组的结果， 用 联合检测方法进行联合检测，获得检测数据。
本发明利用多码集信道估计方法得到各个相邻小区的信道估计结 果； 对各个相邻小区的码道按本发明的分组方法进行码道分组， 该分组 方法包括基于码道所属小区的分组、 基于码道功率或幅度强弱的分组、 基于码道相关性强弱的分组、 及其上述分组方法的混合分组； 利用各个 相邻小区的信道估计结果及码道分组结果进行联合检测。 联合检测过程 具体包括构造 A矩阵； 匹配滤波； 和最终完成多小区联合检测。 采用不 同的码道分组方法时， 构造的 A矩阵会有所不同， 因而给利用信道估计 结果及码道分组结果进行联合检测带来一些差异。
CDMA系统。 本发明的方法与单小区联合检测方法相比 , 可以充分地利 用多个小区信号的结构信息， 进行多小区联合检测， 从而极大地抑制了 同频相邻小区的多址干扰。 本发明提供的方法将大大提高时隙 CDMA 系统在同频相邻小区工作时的系统性能。 附图简要说明
图 1为 TD-SCDMA业务时隙突发结构。
图 2为时隙 CDMA系统多小区联合检测总流程示意框图。
图 3为多小区联合检测基于小区码道分组实施例系统流程图。
图 4为多小区联合检测基于码道幅度或功率分组时或者基于码道相 关性的分组实施例系统流程图。 实施本发明的方式
考虑到时隙 CDMA 系统同频相邻小区信号之间的相互干扰， 本发 明提出了一种基于多小区结构信息的联合检测方法。 具体实现方法的步 驟如图 2中所示。
第一步， 多小区信道估计。 利用背景技术中介绍的多码集的信道估 计方法得到各个相邻小区的信道估计结果。 因为在生成信道估计码时， 每个相邻小区给定一个不同的中间码作为基^ ^马， 该小区不同的用户采 用这个基本码的不同循环移位版本作为它的信道估计码， 一个小区的这 些基本码的不同的循环移位版本被称作一个码集， 多个小区就有多个码 集， 因而多码集的信道估计就是多小区的信道估计。 本发明技术方案中 的多小区信道估计，利用专利申请 031006701中的多码集信道估计技术， 针对同频多小区工作时存在多码集信道估计码响应信号的情况， 采用基 于有限时间位置判决反馈处理的多码集联合信道迭代估计方法， 得到多 个小区的信道估计结果。 信道估计的多小区是相邻小区， 相邻小区包括 待检测用户所在的本小区及与本小区在地域位置上最相邻的小区。
第二步， 码道分组。 首先确定码道分组方法， 然后按选择的一种分 组方法对各个相邻小区的码道进行码道分组。 本发明确定码道分组的具 体方案如下：
第一种是基于码道所属小区的分组方法。 有几个同频小区就设成几 个组， 那么每组内的码道就是相应小区的码道。
第二种是基于码道功率或幅度的分组方法。 利用多小区信道估计结 果可得到各码道的组合信道响应， 或者由各个码道匹配滤波的输出结 果， 可以估算出各码道信号的幅度或功率（幅度通过求平方可以获得功 率）， 然后， 依据幅度或功率的强弱来进行分组。 例如确定一个幅度或 功率的门限值， 码道信号的幅度或功率大于该门限值为强， 低于该门限 值为弱， 幅度或功率强的码道为一组， 功率或幅度弱的码道为另一组。 第三种是基于码道相关性的分组方法。 首先利用多小区信道估计结 果得到各码道的组合信道响应， 用各码道的组合信道响应估算出多小区 信号中各个码道之间的相关性， 然后按照相关性的强弱对所有码道进行 分组。 例如确定一个相关性的门限值， 码道间相关性大于该门限值的为 强， 低于该门限值的为弱， 相关性强的码道分为一组， 相关性弱的码道 分为另一组。 多个码道的相关性可以是平均的相关性、 最大的相关性或 者是最小的相关性。
也可以采用上述方法的混合方法分组， 或基于其它原则的分组。 第三步， 联合检测， 利用多小区信道估计结果及码道分组的结果进 行联合检测， 获得多小区联合检测结果。
如背景技术中所述的， 联合检测方法可以是干扰抵消方法， 可以是 线性块均衡的方法， 也可以是两者混合的方法。 例如， 我们可以在各个 分組内采用线性块均衡的联合检测方法， 而在不同的码道分组间采用干 扰抵消的方法。
需要进一步说明的是， 在本发明的多小区联合检测方法中， 参与进 行码道分组的码道可以是各个相邻小区预先分配的码道（无需作激活处 理就进行分组：)， 也可以是对所述相邻小区的所有码道经过激活检测处 理后保留下来的那些激活码道（需要先作激活处理后再进行分组）。 同 理， 对参与进行联合检测的码道可以是各个相邻小区预先分配的.码道 (无需作激活处理就按码道分组进行联合检测）， 也可以是对所述相邻 小区的所有码道经过激活检测处理后保留下来的那些激活码道 (需要先 作激活处理后再按码道分组进行联合检测）。 实施时还可以作二次激活 检测， 即在分组前经过一次激活检测处理的激活码道， 分组后经过匹配 滤波，再进行二次激活检测，对通过检测的二次激活码道进行联合检测。 本发明方法中对码道进行分组的意义还在于： 因为在同频相邻小区 工作时， 当多个相邻小区分配了大量的码道时， 可以对这些码道先进行 激活检测处理， 而通常经过激活检测处理后， 多小区仍将存在大量的激 活码道， 为了能够以较低的代价和良好的性能实现多小区联合检测， 对 经过激活检测处理后保留下来的那些激活码道进行分组， 再进一步采用 分组联合检测的方法。
下面结合图 3并以三个同频相邻小区为例， 具体说明第一种基于小 区码道分组时本发明的实现方法。
才艮据公式 ( 1 ) 的原理， 本小区加两个同频小区的多用户信号可以 表示为：
2
ε = Α0(1。+2 Α,Α· +n。 （7 )
;=1 其中， 和^分別是本用户本小区的传输矩阵和发送数据； ,.和(1; 分别是第 i ( = 1,2 )个邻小区的传输矩阵和发送数据； n。是除去相邻 2 个小区干 4尤后的干扰和噪声功率（如白噪声）。
步驟 31 , 对该多用户信号 e进行数据分割， 即对图 1中所示的常规 时隙突发结构进行分割， 将分割出的中间码部分 em (中间码的接收信号 或称信道估计码的响应信号）送多小区信道估计， 将分割出的数据符号 部分 ed送匹配滤波。
步驟 32, 多小区信道估计。 三个同频小区的信道估计码部分分别对 应的是三个码集的信道估计码信号 eml、 em2、 em3, 因而接收到的总的信 道估计码部分为 en^enn+e^+ems, 对 em采用多码集信道估计的方法， 可 以得到三个同频相邻小区的信道估计结果 （具体方法见： CN03100670.1,2003.05.09 "时隙码分多址系统多码集信道估计方法"）。
步骤 37, 码道分组， 对三个小区的码道进行分组。 若按照本发明第一种基于码道所属小区的分组方法， 可以将码 道按小区个数分成三个组。 按公式（7 )的原理， 分組后的数据符号 总接收信号 ed可以表示为： ed = A0d。 + + A2d2 +π。 (8) 步驟 38, 利用 bw构造式 (8)-(10)中的传输矩阵 A (根据公式（2 ), 由 h( "获得 ）。根据所采用的分组方法，构造式 (8)-(10)中相应的传输矩 阵 。 采用第一种分组方法，构造的传输矩阵 A就是三个小区的传输矩 阵 AQ、 Αι> A2。 构造的三个小区妁传输矩阵 A。、 Aj A2分别送步骤 39 的联合检测。
步骤 39, 最终完成多小区联合检测。 联合检测可以采用 "线性块均 衡 +干扰抵消" 的方法， 即三个分组内采用线性块均衡的联合检测方法， 三个分组间采用干扰抵消的联合检测方法。 包括：
1 )各个分组对数据符号接收信号 ed用线性块均衡的联合检测方法 进行各自分组的检测， 即对各分组采用单小区联合检测算法进行检测 , 根据公式（ 8 ), ed=A0do+A1d1+A2d2+n0当对干扰小区 1作单小区联合检 测时， 认为： ed= Aidi + ( A0do+A2d2+n0 ) = Aidi + , 为非干扰小区 1 信号的干扰， 利用单小区联合检测方法（公式（3 ) )得到 dl 5 同理可以 得到 d2。
2 )由检测出的各组结果进行干扰恢复， 分别得到干扰小区 1、 干扰 小区 2对本小区本用户的干扰 ^、 A2d2。
3 )从总的数据符号接收信号 ed中抵消掉非本组的干扰 ^、 A2d2, 获得本组的净信号： A。d。+nQ=ed - ( Α1( "Α2(12 );
4 )对待检测用户所在分组的净信号进行线性块均衡的联合检测， 得到待检测用户的发送信号结果 dQ (公式（3 ) )。 步骤 4 )获得的 d0相 对于直接在步骤 1中用单小区联合检测的方法求得的 d。， 由于消除了同 频邻小区干扰， 将更为准确。
上述过程只是使用一次干扰抵消的过程， 还可以使用多次干扰抵消 的过程。 需要抵消一次或多次时的具体实施方法， 可通过设置迭代次数 并循环执行 "线性块均衡 +干扰抵消" 步驟来完成。 迭代次数即为干扰 抵消的次数。 步骤如下：
1 )用线性块均衡方法对各个码道分组分别进行单小区联合检测， 检测出各分组的联合检测结果， 判断是否达到迭代次数， 如杲是则输出 待检测用户所在分组的联合检测结果， 否则执行步骤 2 );
2 ) 由各分组的联合检测结果恢复各个分组信号响应引起的干扰分 量；
3 )接收信号抵消非本组的干扰分量， 获得各组的净信号；
4 )将净信号作为下一步处理的分组结果， 返回步骤 1 )。
采用上述线性块均衡方法是按照公式（3 )得到检测数据， 式（3 ) 中 e为干扰抵消后的净信号。 下面结合图 4具体说明第二种基于码道幅度或功率分组时或者第三 种基于码道相关性的分组时本发明的实现方法。
参见图 4所示， 步驟 31、 32与图 3中的步棟相同。 步錄 33中， 若 按照笫二种基于码道幅度或功率的分组方法， 如先根据信道估计结果得 到各码道的组合信道响应， 再由此估算出各码道信号的幅度或功率， 或 者由各个码道匹配滤波的输出结果， 估算各码道信号的功率； 然后， 依 据功率的强弱将所有码道分成两组， 将待检测 （指联合检测）用户的码 道以及功率较强的干扰码道分到参与联合检测的码道组中， 将不包含待 检测用户且功率较弱的干扰码道分到干扰码道组中。 所述干扰码道是指 除待检测用户码道外的其它用户码道,包括本小区的其它用户码道和同 频邻小区的用户码道。. 按公式（7 ) 的原理， 分组后的数据符号总接收 信号 ed可以表示为：
ed = Asds + (A/d/ +n0) (9)
其中， 5和(1是参与联合检测码道组的传输矩阵和发送数据； 和 d,是干扰码道组的传输矩阵和发送数据。
若按照第三种基于码道相关性的分組方法， 首先由各相邻小区的信 道估计结果得到各码道的組合信道响应， 再由此估算所有非待检测用户 码道与待检测用户所有码道的相关性的均值， 再按照相关性均值的强弱 将上述所有码道分成两组， 将待检测用户的所有码道和所有与其码道平 均的相关性较强的码道分到参与联合检测的码道组中， 将剩下的不包含 待检测用户且平均的相关性较弱的码道分到干扰码道组中。 按公式（7 ) 的原理， 分组后的数据符号总接收信号 ed可以表示为：
ed = Asds + (A7d7 +n0) ( 10) 其中，入和(15是参与联合检测码道组的传输矩阵和发送数据； 和 d,是干扰码道组的传输矩阵和发送数据（第二种与第三种分组方法， 对 分组后的数据符号总接收信号 ed采用了相同的表达式）。
步骤 34， 利用 bw构造式 (8)-(10)中的传输矩阵 A (根据公式（2 )， 由 h(i)获得 bw )0根据所采用的分组方法，构造式 (8)-(10)中相应的传输矩 阵 Α。 ， ·
釆用第二、 第三种分组方法， 构造的传输矩阵 A就是 As (参与联 合检测码道组的传输矩阵）、 （不参与联合检测的干扰码道组的传输矩 阵）。
其中， As送步驟 35的匹配滤波， As、 送步骤 36的联合检测。 步驟 35, 根据求发送数据 d估计的软输出值的公式（3 ), 求出式中 的^ TR, 的过程就是本步骤的匹配滤波过程。 其中的 e就是经数据分割 后的数据符号部分 ed, A是构造的矩阵。 匹配滤波过程中的 A就是 As。
Rn是有色噪声序列 n的协方差矩阵。
步骤 36, 最终完成多小区联合检测。 针对不同的码道分组方法、 所 构造的不同传输矩阵完成多小区联合检测， 即利用公式（4) 中的一种 方法得到 T, 再在匹配滤波获得 '7^; 的基础上完成公式（ 3)。 在采用第二种和第三种码道分组方法时，对参与联合检测的码道组 , 采用线性块均衡的联合检测方法进行检测。在构造传输矩阵 A时所获得 的 As、 A其中 As是由本小区本用户码道加上本小区或邻小区功率或相 关性大的码道构造的传输矩阵， 用于多用户联合检测； 是本小区其它 用户或邻小区功率或相关性小的码道构造的传输矩阵, 用于计算 Rn。
由此， 根据公式（3)经解调后的发送数据 ds估计的软输出值为：
as = (T - (ID 其中， 矩阵 Ts由下式给出 （选择其中一种方法）：
Figure imgf000014_0001
其中有色噪声干扰的协方差矩阵 Rn可以由干扰码道分组及背景噪 声来计算， 其表达式为：
Rn =E{n-n*T}=E{(A d/ +n0)-(A/d/ +η0)*Γ} = A7A +σ21 ( 13 )
R»的具体计算通常有两种方法：
一种方法严格按公式 (13)计算， 即首先由干扰码道分组中码道的组 合信道响应 (定义见 (2)式)， 构造干扰码道分组的传输矩阵 ， 然后计算 A,A;T和背景噪声功率 σ2, 最后求得 =^ '/+^1； 另一种方法是将干扰码道分组中的同频干扰当作白噪声的筒化处 理， 如下式 ( 14):
Rn = E{n ·η*τ}= E{(A7d7 +η0)· (A.d, + n0 f } = A, A*/ +σ21 « Ι + σ21 = (σχ 2 + σ2)Ι
( 14)
即计算干扰码道分组中各码道的功率并求和， 得到 ^ ( 21也是 Α,Α;Τ的对角阵)， 然后计算背景噪声功率 σ·2, 最后求得 =( 2 +^72)1。
图 3中步骤 32、 33、 34、 35、 36或者图 4中步骤 32、 37、 38、 39、 被总称为本发明方法的多小区联合检测过程。 即图 2中的步驟 1、 2、 3。
本发明的方法， 可以用于时隙 CDMA 系统或采用类似信号结构的 无线通信系统。

Claims

权利要求书
1. 一种时隙码分多址系统多小区联合检测方法， 其特征在于， 利- 用多个同频相邻小区的结构信息进行联合检测， 包含如下步骤：
A. 利用多码集的信道估计方法得到各个相邻小区的信道估计结果；
B. 从预定的码道分组方法中选择至少一种分组方法， 对所述各个 相邻小区的码道进行码道分组；
C. 利用所述各个相邻小区的信道估计结果和码道分组的结果， 用 联合检测方法进行联合检测，获得检测数据。
2. 根据权利要求 1所述的方法， 其特征在于：
所述步驟 B中， 选择的分组方法是基于码道所属小区的分组方法， 码道分組数与同频小区个数相同， 每个分组内的码道就是对应小区的码 道。
3. 根据权利要求 2所述的方法， 其特征在于： 所述步驟 C, 是在各 分组内采用单小区线性块均衡和在分组间采用干扰抵消的联合检测方 法。
4. 根据权利要求 3 所述的方法， 其特征在于， 所述在各分組内采 下步驟：
C11. 对各个分组分别进行单小区联合检测， 检测出各分组的联合 检测结果， 判断是否达到迭代次数， 如果是则输出待检测用户所在分组 的联合检测结果， 否则执行步骤 C12;
C12. 由检测出的各分组的联合检测结果恢复各个分组信号响应引 起的干扰分量；
C13. 接收信号抵消非本组的干扰分量， 获得各组的净信号； C14. 将净信号作为下一步处理的分组结果， 返回步驟 Cll。
5. 才艮据权利要求 4所述的方法， 其特征在于： 所述步驟 C11中， 是利用所述步骤 A获得的各个相邻小区的信道估计结果计算各个码道 的组合信道响应， 再由该組合信道响应构造出各个相邻小区的传输矩 阵， 通过传输矩阵以及从接收信号中分割出的数据部分进行匹配滤波， 和对匹配滤波的结果进行单小区线性块均衡获得各分组的联合检测结 果。
6. 根据权利要求 1所述的方法， 其特征在于：
所述步驟 B中，选择的分组方法是基于码道幅度或功率的分组方法， ■按码道幅度或功率的强弱分成参与联合检测的码道分组和干扰码道分 组》
7. 根据权利要求 6 所述的方法， 其特征在于： 所述的按码道幅度 或功率的强弱分组， 包括： 由相邻小区的信道估计结果得到各码道的组 合信道响应， 或者由各个码道匹配滤波的输出结果， 估算出各码道信号 的幅度或功率； 将待检测用户的码道， 以及幅度或功率大于门限值的干 扰码道， 分到参与联合检测的码道分组中， 将不包含待检测用户的且幅 度或功率低于门限值的干扰码道分到干扰码道分组中。
8. 根据权利要求 1所述的方法， 其特征在于：
所述步骤 B中， 选择的分组方法是基于码道相关性的分组方法， 按 码道相关性的强弱分成参与联合检测的码道分组和干扰码道分组。
9. 根据权利要求 8 所述的方法， 其特征在于， 所述的按码道相关 性的强弱分组， 包括： 由相邻小区的信道估计结果得到各码道的组合信 道响应， 估算相邻小区信号中各个码道之间的相关性； 将所有待检测用 户的码道和相关性大于门限值的干扰码道， 分到参与联合检测的码道分 码道分组中。
10. 根据权利要求 9所述的方法， 其特征在于： 所述码道之间的相 关性包括平均相关性、 最大相关性和最小相关性， 是从中选择一种相关 性并按大小进行分组。
11.根据权利要求 6或 8所述的方法，其特征在于：所述步骤 C中， 对参与联合检测的码道分组采用线性块均衡的联合检测方法进行检测。
12. 根据权利要求 11所述的方法， 其特征在于所述步骤 C中， 对 参与联合检测的码道分组采用线性块均衡的联合检测方法进行检测进 一步包括：
C21. 利用各个码道的组合信道响应构造出参与联合检测码道分组 的传输矩阵和干扰码道分组的传输矩阵；
C22. 将参与联合检测码道分组的传输矩阵、 有色噪声干扰的协方 差矩阵以及从接收信号中分割出的数据部分进行匹配滤波；
C23. 采用线性块均衡的方法对匹配滤波结果进行联合检测， 将获 得的发送数据估计的软输出值作为检测数据输出。
13. 根据权利要求 12所述的方法， 其特征在于： 所述步驟 C22中 的有色噪声干扰的协方差矩阵， 是根据干扰码道分组及背景噪声计算 的， 具体是用所述的干扰码道分组的传输矩阵与所述的背景噪声功率来 计算干扰的协方差矩阵。
14. 根据权利要求 12所述的方法， 其特征在于： 所述步骤 C22中 的有色噪声干扰的协方差矩阵， 是根据干扰码道分组及背景噪声计算 的， 具体是将干扰码道分组中的同频干扰当作白噪声的处理， 包括： 计 算干扰码道分组中各码道的功率和； 计算所述功率和与背景噪声功率之 和， 作为干扰的协方差矩阵。
15. 根据权利要求 1所述的方法， 其特征在于： 所述步骤 B中， 参 与进行码道分組的码道是各个相邻小区预先分配的码道， 或者是对各个 相邻小区的所有码道经过激活检测处理后保留下来的那些激活码道。
16. 根据权利要求 1所述的方法， 其特征在于： 所述步骤 C中， 参 与进行联合检测的码道是各个相邻小区预先分配的码道， 或者是对各个 相邻小区的所有码道经过激活检测处理后保留下来的那些激活码道。
17. 根据权利要求 1所述的方法， 其特征在于： 所述步驟 B中， 对 各个相邻小区所有码道进行激活检测处理， 用保留下来的那些激活码道 参与码道分组； 所述步戳 C中， 同时对各个相邻小区的所有激活码道再 次进行激活检测处理， 用保留下来的那些激活码道参与联合检测。
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EP2618507A1 (en) 2013-07-24
JP4866357B2 (ja) 2012-02-01
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CN1753322A (zh) 2006-03-29

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