WO2006027744A2 - Convertisseur continu-continu a pont integral triphase monte en parallele sur le cote primaire - Google Patents

Convertisseur continu-continu a pont integral triphase monte en parallele sur le cote primaire Download PDF

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Publication number
WO2006027744A2
WO2006027744A2 PCT/IB2005/052909 IB2005052909W WO2006027744A2 WO 2006027744 A2 WO2006027744 A2 WO 2006027744A2 IB 2005052909 W IB2005052909 W IB 2005052909W WO 2006027744 A2 WO2006027744 A2 WO 2006027744A2
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WO
WIPO (PCT)
Prior art keywords
transformer
voltage
bridge
output
windings
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Application number
PCT/IB2005/052909
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English (en)
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WO2006027744A3 (fr
Inventor
Ian T. Wallace
Jun Kikuchi
Madhav D. Manjrekar
Edward F. Buck
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Eaton Corporation
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Publication of WO2006027744A2 publication Critical patent/WO2006027744A2/fr
Publication of WO2006027744A3 publication Critical patent/WO2006027744A3/fr

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/493—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode the static converters being arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/285—Single converters with a plurality of output stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0043—Converters switched with a phase shift, i.e. interleaved

Definitions

  • the present invention relates generally to voltage conversion and, more par ⁇ ticularly, a primary paralleled, three-phase full-bridge DC-DC voltage converter.
  • DC-DC converters Direct-current-to-direct-current voltage converters
  • High power DC-DC converters with galvanic isolation are needed, for example, in hybrid electric trucks, such as utility trucks, to interface DC energy storage to the auxiliary AC power generation devices.
  • DC-DC converters are designed to accept a DC input voltage and produce a DC output voltage that is typically at a different voltage level than the input voltage.
  • DC-DC converters provide noise isolation, power bus regulation, and the like.
  • an input DC voltage is converted to an AC voltage using high frequency switching of the input voltage.
  • the AC voltage is then fed to a transformer that converts the input AC voltage to another AC voltage.
  • the AC output of the transformer is then fed to a rectifier circuit that converts the AC voltage to a DC voltage.
  • the DC output of the rectifier can then have a voltage level greater than, less than or equal to the original DC input. Not only does the transformer “buck” or “boost” the voltage level, but it also provides isolation between the DC input and the DC output.
  • a three-phase transformer core typically has less volume compared to three single-phase transformer cores.
  • splitting the three-phase high-frequency transformer into two pieces may lead to even more volume savings because larger total core surface area can be obtained for the same total core volume.
  • the present invention is directed to an apparatus and method of DC to DC conversion that overcomes the aforementioned drawbacks.
  • a DC-DC converter having two active, three-phase full-bridge DC-AC inverters arranged in parallel on a primary side of a pair of high-frequency transformers.
  • Modulation schemes of the three-phase full-bridges include phase-shifted operation between two six step controlled three-phase bridges.
  • a second scheme includes a pulse width modulation (PWM) operation in each three-phase active bridge.
  • PWM pulse width modulation
  • a voltage converter includes a first three-phase full-bridge inverter having an input and an output, and a second three-phase full-bridge inverter having an input and an output.
  • the input of the first three-phase full-bridge inverter is connected in parallel with the input of the second three-phase full-bridge inverter.
  • a voltage converter in accordance with another aspect of the present invention, includes a first transformer having a primary set of windings and a first voltage inverter connected to the primary set of windings of the first transformer.
  • a second transformer is included that has a primary set of windings, and a second voltage inverter is connected to the primary set of windings of the second transformer.
  • the primary set of windings of the first transformer and the first voltage inverter are in parallel with the primary set of windings of the second transformer and the second voltage inverter.
  • a method of supplying conditioned power to a load includes the step of receiving a DC input voltage.
  • the method includes the steps of converting the DC input voltage into a first three-phased AC voltage and converting the DC input voltage into a second three- phased AC voltage.
  • the first three-phased AC voltage is supplied to a first transformer and the second three-phased AC voltage is supplied to a second transformer in parallel with the first transformer.
  • FIG. 1 is a schematic diagram of a DC-DC converter in accordance with the present invention.
  • Fig. 2 is a graph illustrating v out vs. phase-shift angle, ⁇ , characteristics for the DC-
  • Fig. 3 is a graph illustrating v out vs. phase-shift angle, ⁇ , characteristics for the DC-
  • Fig. 4 is a graph illustrating v vs. phase-shift angle, ⁇ , characteristics for the DC- out
  • Fig. 5 is a graph illustrating v out vs. phase-shift angle, ⁇ , characteristics for the DC-
  • Fig. 6 is a graph illustrating v out vs. phase-shift angle, ⁇ , characteristics for the DC-
  • FIG. 7-9 are graphs showing typical transformer and rectifier output voltages of the
  • Fig. 10 is a graph illustrating the relation between output voltage, v out , and phase- shift angle, ⁇ of the DC-DC converter of Fig. 1.
  • Figs. 11-14 show representative circuit simulation results using computer software for the DC-DC converter of Fig. 1.
  • Fig. 15 is a schematic diagram of another DC-DC converter in accordance with the present invention.
  • Fig. 16 is a graph showing an exemplary pulse width modulation (PWM) switching control sequence for DC-DC converter of Figs. 1 and 15.
  • PWM pulse width modulation
  • FIG. 1 shows a schematic diagram of a DC-DC converter 10 in accordance with one exemplary embodiment of the present invention.
  • Converter 10 has a pair of active three-phase full-bridge inverters 14, 16 that receive a DC input voltage 12.
  • the inverters 14, 16 are connected to a primary winding 18, 19 of a pair of high-frequency transformers 20, 22, respectively.
  • Each three-phase full-bridge inverter 14, 16 contains a plurality of high frequency power switches 24.
  • the plurality of high frequency power switches 24 are Insulated Gate Bipolar Transistors (IGBTs); however, one skilled in the art would appreciate that other high frequency power switches may be used, such as Bipolar Junction Transistors (BJTs), Metal- Oxide-Semiconductor Field-Effect Transistors (MOSFETs), and the like.
  • IGBTs Insulated Gate Bipolar Transistors
  • BJTs Bipolar Junction Transistors
  • MOSFETs Metal- Oxide-Semiconductor Field-Effect Transistors
  • Three-phase full-bridge inverters 14, 16 convert the DC input voltage 12 into an AC voltage for input into the primary windings 18, 19 of transformers 20, 22.
  • the AC voltage (v abl ⁇ and v abl ⁇ ) at the output of each three-phase full-bridge inverter 14, 16, are at the same fundamental frequency and are phase shifted from each other by an angle ⁇ .
  • a secondary winding 26 of transformer 22 is serially connected to a secondary winding 28 of transformer 20.
  • the AC voltage at the output of the series windings 26 and 28 is preferably a multi-level waveform with a maximum of seven levels.
  • the AC voltage input into the primary windings 18, 19 of transformers 20, 22 is converted by transformers 20, 22, and the AC output is fed into a three-phase rectifier bridge 30 connected to secondary winding 28 of transformer 20.
  • three-phase rectifier bridge 30 includes a pair of diodes 32 for each phase.
  • the three-phase rectifier bridge 30 is connected to an L-C filter circuit 34, and a DC output voltage 36 is fed to a load 38.
  • Standard six-pack, three-phase full-bridge modules can be utilized for both the active bridges and the passive bridge with potential cost savings.
  • the transformers are designed to "boost" the voltage input thereto, but is contemplated that the transformers may also be designed to reduce or "buck" the input voltage.
  • the three-phase transformer core advantageously has less volume than three single-phase transformer cores designed to provide a similar voltage conversion.
  • splitting the three-phase high-frequency transformer into two sections is believed to provide additional volume savings because larger total core surface area can be obtained for the same total core volume.
  • the transformer configuration of transformers 20, 22 is ⁇ -Y, where primary winding 18 of transformer 20 is in a ⁇ configuration, the primary winding 19 of second transformer 22 is in a ⁇ configuration, and secondary windings 26, 28 of transformers 20 and 22 are connected in series to form a Y winding con ⁇ figuration.
  • transformer con ⁇ figurations such as ⁇ - ⁇ , YY- ⁇ , YY-Y, ⁇ Y-Y and ⁇ Y- ⁇ , are possible.
  • Figs. 2-6 show output voltage, v , vs. phase-shift angle, ⁇ , relations where output voltage is out normalized by nv , for the various transformer configurations. in
  • FIGs. 2 and 3 show v out vs. ⁇ characteristics for transformer configurations ⁇ -Y and YY- ⁇ , respectively, of the DC-DC converter 10 of Fig. 1.
  • the v out vs. ⁇ characteristics for transformer configurations ⁇ -Y and YY- ⁇ are similar.
  • the waveforms differ by a factor of three because of the voltage relation of delta windings and wye windings. Hence, its output voltage is also different by the factor of three at any given value of ⁇ .
  • This scaled relation suggests that ⁇ -Y is preferred for higher output voltage design and YY- ⁇ is suitable for lower output voltage design.
  • the maximum number of available voltage levels in the transformer secondary multi ⁇ level waveforms for these transformer configurations is seven.
  • the maximum number of available voltage levels in the transformer secondary multi-level waveforms, five levels is lower than for the ⁇ -Y or YY- ⁇ configurations.
  • Figs. 5 and 6 show v out vs. ⁇ characteristics of the DC-DC converter 10 of Fig. 1 for mixed primary winding configurations ⁇ Y-Y and ⁇ Y- ⁇ , respectively.
  • two voltage waveforms, which are summed at the series-connected secondary winding terminals, are different.
  • the modulation strategy of the primary paralleled, three-phase full-bridge DC-DC converter 10 is based on the combination of two schemes.
  • a first scheme is preferably a three-phase, six-step operation in each active three-phase full-bridge 14, 16.
  • a second scheme is a phase-shifted operation between the active three-phase full-bridges 14, 16.
  • Figs. 7-9 show typical transformer and rectifier input/output voltages of DC-DC converter 10 of Fig. 1.
  • One of the three output line-to-line voltages of each three-phase full-bridge 14, 16 is shown along with one of the three output line-to-line voltages of transformers 20, 22 and the output voltage of three-phase rectifier bridge 30.
  • the voltages v abl ⁇ and v abl ⁇ are normalized by in r put voltag °e v in , and the voltag °e v ab2 is normalized by nv in , where n is the transformer turns-ratio normalized by the number of primary turns.
  • a switching frequency, f of 10 kHz is used. As shown in Figs.
  • the transformer secondary line-to-line voltages (only v ab2 is shown in the figures) have multi-level waveforms.
  • the highest absolute secondary line-to-line voltage among the three secondary line-to-line voltages appears at the three-phase rectifier bridge 30 output.
  • the three-phase rectifier bridge 30 output voltage, v rect is (a) 3nv in + square wave with height nv in as shown in Fig. 7, (b) 2nv in + square wave with height nv in as shown in Fig. 8, or (c) 0 + square wave with height 2nv as shown in Fig. 9, depending on ⁇ .
  • the closed form input-output voltage relation is:
  • rectifier output voltage ripple frequency is 6f . This is three times the rectifier output voltage ripple frequency in conventional single-phase full-bridge DC-DC converters. This higher ripple frequency results in a smaller DC inductance than those in the conventional single-phase full-bridge DC-DC converter.
  • Fig. 10 shows a trace 40 that illustrates the relation between output voltage, v out , and phase-shift angle, ⁇ , of the DC-DC converter 10 of Fig. 1. At a phase-shift angle of 120°, the slope of trace 40 changes because the height of the square wave portion in rectifier output voltage, v rect , changes from nv in to 2nv in at this angle.
  • the lost volt-second during this period is (nv in )t ov for 0 ° ⁇ ⁇ ⁇ 60° and (0.5nv in )t ov for 60° ⁇ ⁇ ⁇ 180°, where t ov is the commutation overlap time.
  • Eqns. 3, 4, and 5 their first terms are the same as Eqns. 1 and 2 for each cor ⁇ responding ⁇ , and their second terms are the effects of duty cycle loss.
  • L Ltot2ph is the secondary J referred total leakag °e inductance * per r phase-cou V pling ° and i Ldc is the DC current flowing through DC inductor L dc .
  • n is the turns-ratio of single-phase high-frequency transformer single normalized by the number of primary turns and L is the secondary referred total
  • This advantage may be utilized to increase power throughput of the converter
  • FIGs. 11-14 illustrate representative circuit simulation results obtained using Matlab® Simulink® of the DC-DC converter 10 of Fig. 1 .
  • Matlab® and Simulink® are registered trademarks of The MathWorks, Inc. of Natick, Massachusetts.
  • Table 2 ' shows specification summary of the DC-DC converter simulated.
  • the assumed ap ⁇ plication is an auxiliary power conversion unit of a hybrid electric vehicle which is equipped with a high-voltage battery stack.
  • the operating voltage of the battery stack is 240V-400V (340V nominal).
  • 2.5mH of magnetizing inductance and 3 ⁇ H of secondary referred total leakage inductance are assumed for each phase of the high-frequ ency transformers.
  • Table 2 Specification summary of simulated DC-DC converter
  • Traces 46, 48, and 50 represent delta winding currents a, b, and c, re ⁇ spectively.
  • Fig. 13 shows diode rectifier voltage and current waveforms for the same operating point.
  • Traces 52, 54, and 56 are secondary side AC currents a, b, and c, respectively.
  • Trace 58 illustrates the rectified voltage, v rect .
  • the DC inductor current, i Ldc is il- lustrated in trace 60. The effect of commutation overlap can be seen, which was neglected in operating principle as described above in Figs. 7-10.
  • the repetitive square wave frequency in the rectified voltage is 6f , as expected. This high frequency and smaller voltage swing between 3nv in and (3/2)nv in results in small peak-to-peak current ripples in the DC inductor, as can be seen in trace 60.
  • Fig. 14 shows two AC side currents 62, 64 (phase a and b) of the diode rectifier and two anode-cathode voltages 66, 68 of the upper diodes for these two phases in order to show incoming/outgoing diode currents and voltages.
  • ⁇ illustrated the reverse bias voltage at diode turn-off can be low because of the multilevel voltage waveform, as expected from its operating principle. It was found that a voltage spike was induced by the parasitic inductance including the transformer leakage and di/dt of diode reverse recovery and that the voltage oscillation was due to the L-C resonance between the parasitic inductance and diode junction capacitance. Therefore, in an exemplary embodiment, a voltage clamp (not shown) or snubbing in the diode bridge may reduce voltage spikes and oscillations.
  • Fig. 15 shows another embodiment of a DC-DC converter 70 according to the present invention.
  • the DC-DC converter 70 has a pair of three-phase full-bridges 72, 74 and the primary windings 76, 78 of a pair of transformers 80, 82 connected in parallel to a DC input voltage 84.
  • the secondary windings 86, 88 are each connected to a three-phase diode rectifier and L-C filter set 90, 92, respectively.
  • the three-phase diode rectifier and L-C filter sets 90, 92 are connected in series allowing a voltage stress across each diode 94 to be one-half of the voltage stress across each diode 32 in the three-phase rectifier bridge 30 of the DC-DC converter 10 of Fig. 1. In this manner, a lossless voltage clamp scheme may be introduced.
  • a DC output voltage 96 is fed to a load 98.
  • transformer configuration of transformers 80, 82 is ⁇ -Y.
  • transformer configurations such as ⁇ - ⁇ , Y- ⁇ , Y-Y are possible.
  • Fig. 16 shows an exemplary pulse width modulation (PWM) switching sequence
  • each gate pulse 102 has the same pulse width T on , which is between T sw /6 and T sw /2 while avoiding shoot-through.
  • the phase-shifted six-step or PWM switching schemes described above, or combination of both, may be used to control the output DC voltage 36 of the three- phase full-bridge DC-DC converter 10 of Fig. 1.
  • the PWM switching schemes described above, or a combination of PWM and phase-shifted operation, may be used to control the output DC voltage 96 of the three-phase full-bridge DC-DC converter 70 of Fig. 15. Having a variety of different switching schemes allows a degree of freedom in DC-DC power conversion designs to optimize the design depending on the required specifications.
  • the DC-DC converter described herein advantageously allows for a smaller secondary side DC inductor, lower total volume of high-frequency isolation transformers, lower duty cycle loss, and utilization of standard six-pack power semi ⁇ conductor devices when compared to conventional single phase and/or single three- phase full bridge converters.
  • a voltage converter includes a first three-phase full-bridge inverter having an input and an output and a second three-phase full-bridge inverter having an input and an output.
  • the input of the first three-phase full-bridge inverter is connected in parallel with the input of the second three-phase full-bridge inverter.
  • a voltage converter in accordance with another embodiment of the present invention, includes a first transformer having a primary set of windings and a first voltage inverter connected to the primary set of windings of the first transformer.
  • a second transformer is included that has a primary set of windings, and a second voltage inverter is connected to the primary set of windings of the second transformer.
  • the primary set of windings of the first transformer and the first voltage inverter are in parallel with the primary set of windings of the second transformer and the second voltage inverter.
  • a method of supplying conditional power to a load includes the step of receiving a DC input voltage.
  • the method includes the steps of converting the DC input voltage into a first three-phased AC voltage and converting the DC input voltage into a second three- phased AC voltage.
  • the first three-phased AC voltage is supplied to a first transformer and the second three-phased AC voltage is supplied to a second transformer in parallel with the first transformer.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un procédé et un appareil de conversion continu-continu comprenant un convertisseur continu-continu équipé de deux ponts intégraux actifs triphasés montés en parallèle sur le côté primaire d'une paire de transformateurs à fréquence élevée. Le côté secondaire de chaque transformateur peut être connecté séparément à l'un des ponts d'une paire de ponts de diode triphasé monté en série ou connecté ensemble de manière sérielle à un seul pont de diode triphasé.
PCT/IB2005/052909 2004-09-08 2005-09-06 Convertisseur continu-continu a pont integral triphase monte en parallele sur le cote primaire WO2006027744A2 (fr)

Applications Claiming Priority (2)

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US60807004P 2004-09-08 2004-09-08
US60/608,070 2004-09-08

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WO2006027744A3 WO2006027744A3 (fr) 2007-06-07

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Cited By (8)

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WO2010015974A1 (fr) * 2008-08-08 2010-02-11 Philips Intellectual Property & Standards Gmbh Procédé de commande d'un convertisseur de secteur
TWI465027B (zh) * 2012-09-19 2014-12-11 Ind Tech Res Inst 全橋式準諧振直流－直流轉換器及其驅動方法
WO2016040828A1 (fr) * 2014-09-11 2016-03-17 The University Of North Carolina At Charlotte Onduleur à niveaux multiples
US9318974B2 (en) 2014-03-26 2016-04-19 Solaredge Technologies Ltd. Multi-level inverter with flying capacitor topology
DE102015215869A1 (de) 2015-08-20 2017-02-23 Robert Bosch Gmbh Dreiphasiger Gleichspannungswandler
WO2017149906A1 (fr) * 2016-03-02 2017-09-08 株式会社電菱 Circuit d'alimentation à découpage
US9941813B2 (en) 2013-03-14 2018-04-10 Solaredge Technologies Ltd. High frequency multi-level inverter
EP3425785A4 (fr) * 2016-03-02 2019-10-30 Kabushiki Kaisha Toshiba Dispositif de conversion de puissance

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US5886888A (en) * 1995-04-27 1999-03-23 Mitsubishi Denki Kabushiki Kaisha Voltage source type power converting apparatus

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Publication number Priority date Publication date Assignee Title
US5272612A (en) * 1989-06-30 1993-12-21 Kabushiki Kaisha Toshiba X-ray power supply utilizing A.C. frequency conversion to generate a high D.C. voltage
US5886888A (en) * 1995-04-27 1999-03-23 Mitsubishi Denki Kabushiki Kaisha Voltage source type power converting apparatus

Cited By (22)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2010015974A1 (fr) * 2008-08-08 2010-02-11 Philips Intellectual Property & Standards Gmbh Procédé de commande d'un convertisseur de secteur
TWI465027B (zh) * 2012-09-19 2014-12-11 Ind Tech Res Inst 全橋式準諧振直流－直流轉換器及其驅動方法
US9306463B2 (en) 2012-09-19 2016-04-05 Industrial Technology Research Institute Full-bridge quasi resonant DC-DC converter and driving method thereof
US9941813B2 (en) 2013-03-14 2018-04-10 Solaredge Technologies Ltd. High frequency multi-level inverter
US11742777B2 (en) 2013-03-14 2023-08-29 Solaredge Technologies Ltd. High frequency multi-level inverter
US11545912B2 (en) 2013-03-14 2023-01-03 Solaredge Technologies Ltd. High frequency multi-level inverter
US10886831B2 (en) 2014-03-26 2021-01-05 Solaredge Technologies Ltd. Multi-level inverter
US10680505B2 (en) 2014-03-26 2020-06-09 Solaredge Technologies Ltd. Multi-level inverter
US11855552B2 (en) 2014-03-26 2023-12-26 Solaredge Technologies Ltd. Multi-level inverter
US10153685B2 (en) 2014-03-26 2018-12-11 Solaredge Technologies Ltd. Power ripple compensation
US10404154B2 (en) 2014-03-26 2019-09-03 Solaredge Technologies Ltd Multi-level inverter with flying capacitor topology
US11632058B2 (en) 2014-03-26 2023-04-18 Solaredge Technologies Ltd. Multi-level inverter
US10680506B2 (en) 2014-03-26 2020-06-09 Solaredge Technologies Ltd. Multi-level inverter
US9318974B2 (en) 2014-03-26 2016-04-19 Solaredge Technologies Ltd. Multi-level inverter with flying capacitor topology
US10700588B2 (en) 2014-03-26 2020-06-30 Solaredge Technologies Ltd. Multi-level inverter
US11296590B2 (en) 2014-03-26 2022-04-05 Solaredge Technologies Ltd. Multi-level inverter
US10886832B2 (en) 2014-03-26 2021-01-05 Solaredge Technologies Ltd. Multi-level inverter
WO2016040828A1 (fr) * 2014-09-11 2016-03-17 The University Of North Carolina At Charlotte Onduleur à niveaux multiples
US10141866B2 (en) 2014-09-11 2018-11-27 The University Of North Carolina At Charlotte Multi-level inverter with first and second switch banks
DE102015215869A1 (de) 2015-08-20 2017-02-23 Robert Bosch Gmbh Dreiphasiger Gleichspannungswandler
WO2017149906A1 (fr) * 2016-03-02 2017-09-08 株式会社電菱 Circuit d'alimentation à découpage
EP3425785A4 (fr) * 2016-03-02 2019-10-30 Kabushiki Kaisha Toshiba Dispositif de conversion de puissance

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