WO2003102610A2 - Procede et dispositif de detection dans le domaine frequentiel en fonction d'une mesure dans le domaine temporel - Google Patents

Procede et dispositif de detection dans le domaine frequentiel en fonction d'une mesure dans le domaine temporel Download PDF

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Publication number
WO2003102610A2
WO2003102610A2 PCT/EP2003/004996 EP0304996W WO03102610A2 WO 2003102610 A2 WO2003102610 A2 WO 2003102610A2 EP 0304996 W EP0304996 W EP 0304996W WO 03102610 A2 WO03102610 A2 WO 03102610A2
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WIPO (PCT)
Prior art keywords
signal
spectral
measurement
detector model
measuring system
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PCT/EP2003/004996
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German (de)
English (en)
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WO2003102610A3 (fr
Inventor
Florian Krug
Peter Russer
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Technische Universität München
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Priority to DE10392151T priority Critical patent/DE10392151B4/de
Priority to AU2003240238A priority patent/AU2003240238A1/en
Publication of WO2003102610A2 publication Critical patent/WO2003102610A2/fr
Publication of WO2003102610A3 publication Critical patent/WO2003102610A3/fr

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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R23/00—Arrangements for measuring frequencies; Arrangements for analysing frequency spectra
    • G01R23/16—Spectrum analysis; Fourier analysis
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R29/00—Arrangements for measuring or indicating electric quantities not covered by groups G01R19/00 - G01R27/00
    • G01R29/08—Measuring electromagnetic field characteristics
    • G01R29/0864—Measuring electromagnetic field characteristics characterised by constructional or functional features
    • G01R29/0892—Details related to signal analysis or treatment; presenting results, e.g. displays; measuring specific signal features other than field strength, e.g. polarisation, field modes, phase, envelope, maximum value
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
    • G01R31/00—Arrangements for testing electric properties; Arrangements for locating electric faults; Arrangements for electrical testing characterised by what is being tested not provided for elsewhere
    • G01R31/001—Measuring interference from external sources to, or emission from, the device under test, e.g. EMC, EMI, EMP or ESD testing

Definitions

  • the present invention relates to a method and to a device for detecting a disturbance in the frequency domain, which is caused by a device to be tested, and in particular to a method and to a device, which detects the signals emitted by the test device in the time domain to capture.
  • DE 43 30 345 Cl describes a measuring system which offers the possibility of converting an electromagnetic disturbance variable into a functional error of the object under investigation.
  • the measuring system is unable to measure and evaluate the emission spectrum.
  • EP 1 111 396 A2 describes a signal detection system in the time domain, which offers the possibility of sampling, digitizing, storing and evaluating the measurement signal by means of signal processing in the frequency domain.
  • this measuring system it is possible to correctly record broadband signals, however, a signal analysis that conforms to standards (according to the standard CISPR. 16-1, CISPR. 16-2) is not possible due to the fact that data acquisition is only possible sequentially. The reason for this lies in the generation of data that can no longer be handled, which is associated with a very high-resolution signal recording that takes a long measurement time.
  • the system does not offer the possibility of evaluating the signal spectrum with a detector characteristic and. carry out a systematic correction of the frequency response of the measuring device.
  • the present invention has for its object to provide a method and an apparatus for detecting a disturbance in the frequency range, which is caused by a device to be tested, which rapid and accurate detection of a measurement signal that the disturbance characterized, enables.
  • the present invention provides a method for detecting a disturbance in the frequency domain, which is caused by a device to be tested, with the following steps:
  • the present invention also provides a device for detecting a disturbance in the frequency range, which is caused by a device to be tested, with:
  • a measuring system for receiving a signal from the device under test in the time domain; and a signal processing device configured to
  • a peak value detector model, an average value detector model and / or an RMS detector model is preferably used as the detector model.
  • the present invention provides a method for detecting a disturbance in the frequency domain, which is caused by a device to be tested, with the following steps:
  • the present invention further provides an apparatus for detecting a frequency domain disturbance caused by a device under test, comprising:
  • a measuring system for receiving a signal from the device under test in the time domain
  • a signal processing device configured to:
  • a quasi-peak detector model (quasi-peak detector model) is preferably used as the detector model.
  • the measurement is started in the frequency domain and instead the measurement signal is recorded for a very short duration (less than one second) in the time domain compared to the measurement in the frequency domain (two to four hours).
  • the time domain signal is then converted into the frequency domain and the corresponding signal processing for generating the standard-compliant signals, ie the signals corresponding to the CISPR standard.
  • this is achieved in that, on the one hand, the errors in the spectral signal introduced by the measuring system, which carries out the detection of the signal in the time domain, are corrected, and, on the other hand, one or more detector models are applied to the spectral signal in order to obtain the standard-compliant measurement results receive.
  • the advantage of the present invention is obvious, since this enables a very precise and at the same time very fast measurement, and at the same time, according to a particular advantage, the detection and evaluation of transient processes such as the starting process of an engine or without further ado Similar, can be detected - a possibility that was not at all or only to a very limited extent and with considerable effort in frequency domain measurements.
  • the present invention provides a method for measuring electronic and / or electromagnetic interference by means of a sensor for recording the interference signals to be measured, an amplifier with a frequency range filter and an analog-digital converter and a digital signal evaluation unit, with digital processing the short-term Fourier transform of the digitized measurement signal is formed, the errors caused by the transmission property of the analog part of the measurement system are corrected, and the signal is divided into a stationary and an impulsive component and by means of digital evaluation mean values and peak values of the disturbances both globally (in entire frequency range) and frequency-resolved.
  • the present invention also provides an apparatus for measuring electrical or electromagnetic interference consisting of a sensor for recording the interference signals to be measured, an amplifier with a frequency domain filter, an analog-digital converter and a digital signal evaluation unit, the short-term Fourier
  • Transformed of the digitized measurement signal is formed by the transmission properties of the analog
  • the measuring system consists of an analog-digital converter and a digital signal processor.
  • the interference signal to be examined is passed on to the analog-digital converter by means of line-based and / or radiation-based coupling. This converts the continuous value and time signal into a digital numerical value, and the digitized measurement data are then processed using the analog-to-digital converter, e.g. B. an oscilloscope, further processed.
  • the analog-to-digital converter e.g. B. an oscilloscope
  • a data reduction is preferably carried out, which is necessary when a quasi-peak detector is used, which requires a very long recording time which, according to the CISPR.16-1 standard, has a maximum discharge time of 550 ms.
  • the digital recording of the measurement data is preferably triggered on high-energy interference pulses, which ensures that a high-resolution measurement only begins when the interference signal amplitude shows a clear increase.
  • high-energy interference pulses In order to measure the stationary components of the interference signal as efficiently as possible in memory, only limited sections of the interference signal are recorded. men. This division of the interference signal into an impulsive and stationary signal component results in a reduction in measurement time, memory requirement minimization and a saving in computing time.
  • FFT Fast Fourier transform
  • STFFT Short Time FFT
  • the resulting amplitude spectrum is corrected with regard to the transfer function of the measuring system, as a result of which no time-consuming reference measurements with a conventional measuring receiver operating in the frequency range are required.
  • an evaluation is carried out according to the invention with one or more detectors, with the behavior of the detectors for this purpose is mathematically modeled and applied to the measured spectrum.
  • the method according to the invention is implemented in software, which offers the further advantage that a plurality of possible amplitude spectra, such as is produced by a plurality of detectors, can now be calculated in parallel.
  • the first and the second aspect can be easily connected, for example, by providing the spectral signal to a first signal processing branch and a second signal processing branch, for example in parallel, after the transformation, the spectral signal in the first branch being provided to a detector model, eg the RMS, Mean value and / or peak value detector model is provided and is subsequently corrected, and wherein in the second branch the spectral signal is first corrected and then extended to a detector model, for example a quasi-detector model.
  • a detector model eg the RMS, Mean value and / or peak value detector model
  • the peak value detector only ever stores an amplitude value if it is greater than a previously stored value.
  • the statistics of the pulse repetition frequency, the statistics of the pulse duration, the statistics of the pulse amplitudes, the spectrogram, the phase spectrum, etc. only one time domain measurement process is required according to the invention, since the additional signal examinations can be carried out by means of software-based signal processing.
  • the system according to the invention which includes a time-domain measuring system u, offers the possibility of carrying out an immunity test.
  • the data stored in the signal processing device are transmitted by predetermined test pulses via the converter, which then applies a corresponding interference pulse of an analog type to the device under test. Due to the preferably software-based implementation, all possible types of malfunctions can be provided in a simple manner.
  • the advantage of the present invention is that, according to the invention, a measuring system is created which offers the complete functionality of a traditional measuring receiver (working in the frequency range) for emission measurements as well as an analog pulse generator for immunity measurements.
  • a standard right frequency range display with the known setting options, such as. B. filter bandwidth, dwell time and detector characteristics can be obtained, although the system works completely in the time domain.
  • Another advantage of the present invention is that due to the possibility of differentiating different signal classes in software, the time domain measurement can be made very efficiently. Furthermore, any measurement setting can be simulated by software with the measurement system, so that, unlike traditional measurement receivers, it is not necessary to carry out separate measurements. In other words, different types of detectors can be simulated and applied to the spectral signal, whereas the traditional approach required a plurality of measurement runs, with the detector provided at the output of the measurement receiver being exchanged for each measurement run.
  • 1 is a block diagram showing the arrangement according to the invention for detecting an interference signal
  • FIG. 2 is a detailed illustration of the inventive device according to a preferred exporting ⁇ approximately example
  • FIG. 3 is a flow diagram showing the inventive method according to a preferred whichsbei ⁇ game
  • FIG. 4A shows the course of the antenna factor and the amplifier gain versus frequency for the measuring device shown in FIG. 2;
  • FIG. 4B shows the course of the filter response and the line losses versus frequency for the measuring device shown in FIG. 2;
  • FIG. 5 shows a course of the measurement results (black), as they are obtained by the approach according to the invention, with measurement results (gray), as they are obtained by a conventional EMI receiver
  • FIG. 5A the measurement results when using an FFT
  • FIG. 5B shows the measurement results using the Bartlett periodogram
  • FIG. 5C shows the measurement results using the Welch periodogram for transforming the detected signal in the spectral range.
  • the device 100 comprises an analog-digital converter 102 which receives a signal from a device to be tested (EUT) 104, as is indicated schematically by the arrow 106.
  • the analog-to-digital converter 102 samples the received signal 106 and transmits the digitized signal to a digital signal processing device (DSV) 108, as is schematically indicated by the arrow 110.
  • DSV digital signal processing device
  • the system according to the invention is set to receive interference signals from the EUT 104 in order to carry out an EMI measurement.
  • the invention System may also be configured to perform an immunity test on the EUT 104.
  • a test pulse for example stored therein, is selected by means of the digital signal processing device 108 and transmitted to the converter 102, as is indicated schematically by the arrow 112.
  • converter 102 works as a digital-to-analog converter in order to convert the digital signal provided by digital signal processing device 108, which reproduces the desired test pulse, into an analog signal, which is then applied to EUT 104, as described by the arrow 114 is shown schematically.
  • the device according to the invention is further configured to subsequently record, process and characterize the reaction of the EUT 104, that is to say a signal caused by the test pulse and which is emitted by the EUT 104, to the EUT 104 with the desired test pulse.
  • the measurement signals achieved are compared with measurement signals as obtained by a traditional measurement receiver.
  • the system according to the invention further comprises a low-pass filter 116, an amplifier 118, a broadband antenna 120 and / or a connecting line 122.
  • a low-pass filter 116 receives signals emitted by the EUT 104 via a wired connection 122. These signals are amplified in the amplifier 118, filtered by means of the low-pass filter 116 and thus fed to the converter 102, the digitized output signals of which are provided to the computer 108 for signal processing, which will be explained in more detail below.
  • the broadband antenna 120 combines the characteristics of a two-lobe antenna and a logarithmic periodic antenna to enable measurement in the frequency range from 30 to 1,000 MHz.
  • the amplifier is required due to the low sensitivity of the oscilloscope that forms converter 102.
  • the low pass filter 116 or anti-aliasing filter limits the signal bandwidth according to the requirement of the sampling theorem.
  • the oscilloscope 102 has an analog bandwidth of 1 GHz.
  • the data is transferred to computer 108 over a GPIB bus.
  • the device under test (EUT) 104 is, for example, a conventional laptop with a clock frequency of 200 MHz. The measurements on the laptop are made while it is on and powered by an internal battery. All measurements are preferably carried out in an anechoic chamber, the distance between the preferably vertically polarized antenna 120 and the EUT 104 being approximately 1 m.
  • the initial parameter M and the initial parameter N are initially provided in a first step 124, as will be explained below.
  • a first pass a first number of samples of the time signal detected by the oscilloscope 102 is read in in step 126.
  • a spectral estimate is then carried out at 128 in order to obtain a spectral sequence, which is then at 130 a detector model, through which, for example, a Peak value detector, an RMS detector, a mean value detector or a quasi-peak detector is simulated.
  • the running index m is increased by 1 to determine at 134 whether it has reached the maximum value M.
  • the method goes back to 126 in order to read in a next data sequence or a next data vector and to process them in accordance with the steps described above. If it is found that the index M has been reached, the amplitude spectrum is now in logarithmic form, as shown at 136, and at 138 the amplitude spectrum present at 136 is corrected with regard to the frequency characteristics of the measuring system which was used. to capture the signal over time.
  • the detected signal is transformed with the oscilloscope 102 from the time domain into the frequency domain, processed and errors due to the frequency characteristics of the antenna 120, the amplifier 118, a transmission line 140 arranged between the antenna 120 and the amplifier 118, and the Filters 116 are corrected by signal processing. This correction compensates for the frequency characteristics of the time domain measurement system, so that an accurate spectrum is obtained from the time domain measurement.
  • FIG. 4A shows the antenna factor H AF as a solid line and the amplifier gain H A in p (f) over frequency as a dotted line.
  • the antenna factor depends on the effective antenna length, the antenna impedance and the input impedance of the amplifier 118.
  • the measured filter frequency response H LP (f) is shown as a solid line over the frequency, and the line losses H Ca bie (f) are shown as a dashed line.
  • Oscilloscope 102 samples and quantizes the continuous input signal x (t).
  • Shannon's theorem requires that f s is twice the highest signal frequency.
  • the upper limit imposed on the signal frequency by the sampling process is the so-called Nyquist frequency.
  • the data is provided to the assessment routine in blocks of N samples to serve as an input to the method shown in FIG. 3, particularly as an input to spectral estimation 128.
  • the mathematical basis for the spectral estimation methods used in accordance with the invention is the discrete Fourier transform (DFT).
  • DFT discrete Fourier transform
  • the DFT transforms the discrete time signal sequence x [n] into a discrete frequency spectral sequence X [r], where n and r define the discrete time variable and the discrete frequency variable, respectively:
  • the value X [0] corresponds to the mean DC signal component of the signal and the absolute values
  • , 0 ⁇ r ⁇ N correspond to the amplitude of the complex pointer at the frequency index r.
  • for which r> 1 applies is divided by 2, the crest factor for sinusoidal signals.
  • the frequency index R which corresponds to the Nyquist frequency, is given as follows:
  • Equation (2) The numerical implementation of equation (2) (see above) is carried out in the form of a fast Fourier transform (FFT).
  • FFT fast Fourier transform
  • a window function has a global maximum around the point N / 2 and goes smoothly to zero at the end points 0 and N - 1, thereby avoiding edge effects when x [n] overlaps.
  • the windowed signal vector x w [n] has less energy content than the original signal after parts of the signal have been attenuated.
  • the window sequence w [n] is scaled such that its integral is 1 over the observation interval ⁇ T N.
  • the scaling factor is also called the coherent gain G c of w [n]:
  • G c is a scalar factor, it can be used together with after the spectral transformation into the frequency domain the other scaling factors due to the linearity of the DFT. This results in the following definition for the modified one-sided amplitude spectrum:
  • Different window functions offer different compromises between the suppression of the occurrence of a signal component and the spectral resolution.
  • Conventional window functions include the Hann window, the Hamming window and the flat-top window.
  • Oscilloscope 102 begins. The spectra are then digitally calculated using the fast Fourier transform in the manner described above. Then one
  • ⁇ T M is the observation time
  • ⁇ f is the frequency resolution
  • f s is the sampling frequency.
  • the process then enters the loop shown in Fig. 3 which is cycled M times. With each pass, a time domain data vector of length N is read in at 126, transformed into the frequency domain at 128 and fed to a detector model at 130. After all M iterations have been performed, the resulting amplitude spectrum of the detector modeling will become a logarithmic procedure. This is followed by the above-described correction of the errors which are caused on the basis of the frequency characteristics of the measuring system.
  • the detector model applied to the spectral data at 130 is discussed in more detail below.
  • a spectrum vector S ⁇ 'jr] is obtained at the output of block 128. If the values for a given frequency index r are concatenated for all M vectors, a discrete time representation of the amplitude envelope function at this frequency is obtained.
  • the detector models according to the invention in the system according to the invention assess this function obtained in this way.
  • the peak detector model determines the maximum value of the envelope as follows:
  • the data vectors that come from the spectral estimation block 128 are collected during the running time of the measuring loop and subsequently normalized with regard to the number of iterations.
  • the EMI spectrum is calculated from the time domain signal using the Bartlett periodogram or the Welch periodogram. Both methods are based on averaging the spectra, which are obtained by the fast Fourier transform of segments of the time signal.
  • the Bartlett method which is a special periodogram method
  • the time domain sequence x (m) is divided into P non-overlapping segments, each segment having a length D.
  • the periodogram is calculated for each segment and the Bartlett spectral power estimate is obtained by averaging the periodogram for the P segments.
  • the frequency spectrum calculated using the Bartlett periodogram is defined as follows:
  • This averaging of the spectrum reduces the variance of the spectrum estimate by the factor P, but at the cost of reducing the frequency resolution by the factor P.
  • Welch modified the Bartlett method by using windowed data segments that overlap in time.
  • the overlap is used to further reduce the peri-dogram variance, while the windowing is used to reduce spectral losses associated with the finite observation intervals.
  • the frequency spectrum which is calculated by a Welch periodogram, is as follows:
  • U is the discrete time window energy of the window function w [m] used and is defined as follows:
  • FIG. 5A-B show the results of this comparison, which is a comparison between the classic fast Fourier transform, the Bartlett periodogram and the Welch periodogram and the measured results of a conventional EMI receiver using a peak value detector. tector and an average detector. As can be seen, the mean deviation of the amplitude spectrum for a frequency range from 30 MHz to 1,000 MHz is always below 3 dB.
  • FIG. 5A shows the comparison between the FFT and the EMI receiver in the peak detector mode, black showing the results according to the invention and gray showing the results according to a conventional receiver.
  • FIG. 5B shows the comparison between the Bartlett periodogram and the EMI receiver in the mean value detector mode and
  • FIG. 50 shows the comparison between the Welch periodogram and the EMI receiver, also in the mean value detector mode.
  • the time-domain EMI measuring system makes it possible to reduce the time required for the measurement by a factor of 10 compared to a conventional superheterodyne EMI receiver.
  • different signal processing methods are used to calculate the spectra from the time-domain data, the mean measured value deviation between, as explained above the time domain measurement and the measurement by an EMI receiver is below 3 dB over the entire frequency range from 30 to 1,000 MHz.
  • the measuring device according to the invention was configured as follows.
  • Antenna 120 was an HL562 antenna from Rohde & Schwarz.
  • the amplifier was a ZFL-1000LN.
  • Filter 116 was a low pass filter SLP-1000.
  • Converter 102 was a Teletronix TDS7104 oscilloscope.
  • the signal processing device was implemented in software on a conventional personal computer.
  • An EMI receiver ESCS30 from Rohde & Schwarz was used for the comparison measurements mentioned above.
  • 100,000 samples were acquired during a measuring time of 13 ⁇ s.
  • the readout time from the oscilloscope was approximately 100 ms and the calculation time was two minutes, which resulted in a total measuring time of approximately 2.5 minutes.
  • a conventional EMI receiver captures 19,000 samples, which takes 40 minutes, which is the total measurement time.
  • the detector model is an RMS, an average value or a peak value detector model, in which case the signal was then corrected with respect to the transmission properties of the measuring system.
  • the spectral signal can also be corrected first and then fed to the detector model, which is preferably done when using a quasi-peak detector model. Since the present invention is preferably implemented in software, this opens up the possibility of parallel signal processing. After the transformation, this can be rale signal here a first signal processing branch and a second signal processing branch, for example in parallel. In the first branch, the spectral signal is made available to a detector model, for example the RMS, mean value and / or peak value detector model, and is subsequently corrected.
  • the spectral signal is first corrected and then extended to a detector model, for example a quasi-detector model.
  • a detector model for example a quasi-detector model.
  • the method according to the invention can be implemented in hardware or in software.
  • the implementation can take place on a digital storage medium, in particular a floppy disk or CD with electronically readable control signals, which can cooperate with a programmable computer system in such a way that the corresponding method is carried out.
  • the invention thus also consists in a computer program product with program code stored on a machine-readable carrier for carrying out the method according to the invention when the computer program product runs on a computer.
  • the invention can thus be implemented as a computer program with a program code for carrying out the method if the computer program runs on a computer.

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  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Mathematical Physics (AREA)
  • Measurement Of Resistance Or Impedance (AREA)
  • Monitoring And Testing Of Transmission In General (AREA)

Abstract

L'invention concerne un procédé et un dispositif permettant de détecter une perturbation dans le domaine fréquenciel, qui est provoquée par un appareil à contrôler. Selon ce procédé, un signal est tout d'abord reçu (126) par l'appareil à contrôler, dans le domaine temporel au moyen d'un système de mesure. Puis, le signal reçu est transformé (128), du domaine temporel au domaine fréquenciel, pour obtenir un signal spectral. Un signal de détection (130) prédéterminé est appliqué sur ce signal spectral pour obtenir un signal de mesure spectral caractérisant la perturbation. Ce signal de mesure spectral est corrigé (138) pour compenser un défaut causé par une fonction de transmission du système de mesure.
PCT/EP2003/004996 2002-05-31 2003-05-13 Procede et dispositif de detection dans le domaine frequentiel en fonction d'une mesure dans le domaine temporel WO2003102610A2 (fr)

Priority Applications (2)

Application Number Priority Date Filing Date Title
DE10392151T DE10392151B4 (de) 2002-05-31 2003-05-13 Verfahren und Vorrichtung zur Erfassung im Frequenzbereich basierend auf einer Zeitbereichsmessung
AU2003240238A AU2003240238A1 (en) 2002-05-31 2003-05-13 Method and device for detection in the frequency range, based on a time range measurement

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DE10224096 2002-05-31
DE10224096.5 2002-05-31

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DE102007042266A1 (de) 2007-09-06 2009-03-12 Stephan Braun Verfahren und Anordnung zur umgebungsstörkompensierten Emissionsmessung im Zeitbereich
DE102005026928B4 (de) * 2004-07-14 2013-02-21 Technische Universität München Verfahren und Vorrichtung zur Analog-Digital-Wandlung eines Eingangssignals mit hoher Dynamik
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CN107787455A (zh) * 2015-06-23 2018-03-09 西门子股份公司 用于分析信号的方法以及用于执行该方法的装置
WO2019043874A1 (fr) * 2017-08-31 2019-03-07 株式会社東陽テクニカ Procédé de mesure d'onde d'interférence de rayonnement et système de mesure d'onde d'interférence de rayonnement
CN114166253A (zh) * 2021-12-07 2022-03-11 山东大学 一种基于非线性回归数据处理的提高马赫-泽德型传感器测量范围的方法及系统
WO2023011682A1 (fr) * 2021-08-06 2023-02-09 Schaeffler Technologies AG & Co. KG Procédé et dispositif de mesure de couple
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EP3232208A1 (fr) 2016-04-13 2017-10-18 Universitat Politècnica De Catalunya Procédé de domaine de temps complet permettant de mesurer et de contrôler des signaux d'interférence électromagnétique et système
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DE102005026928B4 (de) * 2004-07-14 2013-02-21 Technische Universität München Verfahren und Vorrichtung zur Analog-Digital-Wandlung eines Eingangssignals mit hoher Dynamik
DE102005026928B8 (de) * 2004-07-14 2013-05-16 GAUSS Instruments GmbH Gesellschaft für AUtomatisierte StöremissionsmessSysteme Verfahren und Vorrichtung zur Analog-Digital-Wandlung eines Eingangssignals mit hoher Dynamik
DE102006062995B3 (de) 2006-02-06 2023-06-07 GAUSS INSTRUMENTS International GmbH Verfahren und Anordnung zur Messung von Störemissionen in Realzeit
DE102006005595B8 (de) * 2006-02-06 2015-03-12 GAUSS INSTRUMENTS Vertriebs GmbH Vorrichtung und Verfahren zur Messung von Störemissionen in Echtzeit
DE102006005595B4 (de) * 2006-02-06 2015-01-22 GAUSS INSTRUMENTS Vertriebs GmbH Vorrichtung und Verfahren zur Messung von Störemissionen in Echtzeit
US7613576B2 (en) 2007-04-12 2009-11-03 Sun Microsystems, Inc. Using EMI signals to facilitate proactive fault monitoring in computer systems
WO2008127909A2 (fr) * 2007-04-12 2008-10-23 Sun Microsystems, Inc. Utilisation des signaux emi pour faciliter le contrôle proactif des défaillances dans des systèmes informatiques
GB2460376A (en) * 2007-04-12 2009-12-02 Sun Microsystems Inc Using EMI signals to facilitate proactive fault monitoring in computer systems
GB2460376B (en) * 2007-04-12 2011-07-20 Sun Microsystems Inc Using EMI signals to facilitate proactive fault monitoring in computer systems
GB2460212B (en) * 2007-04-12 2012-02-22 Oracle America Inc Method and apparatus for generating an EMI fingerprint for a computer system
WO2008127908A1 (fr) * 2007-04-12 2008-10-23 Sun Microsystems, Inc. Procédé et appareil pour générer une empreinte emi pour un système informatique
US7613580B2 (en) 2007-04-12 2009-11-03 Sun Microsystems, Inc. Method and apparatus for generating an EMI fingerprint for a computer system
GB2460212A (en) * 2007-04-12 2009-11-25 Sun Microsystems Inc Method and apparatus for generating an emi fingerprint for a computer system
WO2008127909A3 (fr) * 2007-04-12 2009-01-22 Sun Microsystems Inc Utilisation des signaux emi pour faciliter le contrôle proactif des défaillances dans des systèmes informatiques
DE102007042266A1 (de) 2007-09-06 2009-03-12 Stephan Braun Verfahren und Anordnung zur umgebungsstörkompensierten Emissionsmessung im Zeitbereich
US10234491B2 (en) 2015-06-23 2019-03-19 Siemens Aktiengesellschaft Method for analysing a signal and apparatus for carrying out the method
CN107787455A (zh) * 2015-06-23 2018-03-09 西门子股份公司 用于分析信号的方法以及用于执行该方法的装置
WO2019043874A1 (fr) * 2017-08-31 2019-03-07 株式会社東陽テクニカ Procédé de mesure d'onde d'interférence de rayonnement et système de mesure d'onde d'interférence de rayonnement
WO2023011682A1 (fr) * 2021-08-06 2023-02-09 Schaeffler Technologies AG & Co. KG Procédé et dispositif de mesure de couple
CN114166253A (zh) * 2021-12-07 2022-03-11 山东大学 一种基于非线性回归数据处理的提高马赫-泽德型传感器测量范围的方法及系统

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