WO1995020783A1 - Integrierte schaltung - Google Patents
Integrierte schaltung Download PDFInfo
- Publication number
- WO1995020783A1 WO1995020783A1 PCT/DE1995/000039 DE9500039W WO9520783A1 WO 1995020783 A1 WO1995020783 A1 WO 1995020783A1 DE 9500039 W DE9500039 W DE 9500039W WO 9520783 A1 WO9520783 A1 WO 9520783A1
- Authority
- WO
- WIPO (PCT)
- Prior art keywords
- transistor
- current
- emitter
- integrated circuit
- resistor
- Prior art date
Links
- 230000008878 coupling Effects 0.000 claims description 4
- 238000010168 coupling process Methods 0.000 claims description 4
- 238000005859 coupling reaction Methods 0.000 claims description 4
- 238000010079 rubber tapping Methods 0.000 claims 1
- 238000009529 body temperature measurement Methods 0.000 abstract description 2
- 238000005259 measurement Methods 0.000 abstract description 2
- 230000001939 inductive effect Effects 0.000 description 4
- 238000010586 diagram Methods 0.000 description 3
- 230000009467 reduction Effects 0.000 description 3
- 230000003321 amplification Effects 0.000 description 2
- 230000008901 benefit Effects 0.000 description 2
- 230000001419 dependent effect Effects 0.000 description 2
- 238000003199 nucleic acid amplification method Methods 0.000 description 2
- 230000004044 response Effects 0.000 description 2
- 230000004913 activation Effects 0.000 description 1
- 238000011161 development Methods 0.000 description 1
- 230000018109 developmental process Effects 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000010438 heat treatment Methods 0.000 description 1
- 238000013021 overheating Methods 0.000 description 1
- 230000000717 retained effect Effects 0.000 description 1
- 230000001360 synchronised effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
- H03K17/082—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit
- H03K17/0826—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit in bipolar transistor switches
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03K—PULSE TECHNIQUE
- H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
- H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
- H03K2017/0806—Modifications for protecting switching circuit against overcurrent or overvoltage against excessive temperature
Definitions
- the invention is based on an integrated circuit according to the preamble of independent claim 1. From the book by Tietze and Schenk, 9th edition, page 523, a circuit with a power transistor is already known, in which a current control transistor and a current measuring resistor are provided. The current control transistor is driven by the voltage drop across the current measuring resistor.
- the integrated circuit according to the invention with the characterizing features of independent claim 1 has the advantage that the current flow through the power transistor is reduced depending on the component temperature. This measure protects the power transistor from overheating.
- the measures listed in the dependent claims allow advantageous developments and improvements of the integrated circuit specified in the independent claim.
- a temperature measuring transistor with a larger emitter area than the current regulation transistor, the temperature dependence of the circuit can be controlled particularly precisely.
- the current measuring transistor connected in parallel to the power transistor, the current measurement takes place with low losses, since no measuring resistor has to be arranged in the emitter circuit.
- the switching potential for the current control transistor and the temperature measuring transistor can be set to a corresponding level.
- the positive temperature coefficient of the current control can be set to the desired value.
- the size of the thermal curtailment is set by appropriately dimensioning a coupling resistance.
- the potential is particularly easily influenced by the current flow of the further transistor via a third node of the voltage divider.
- the corresponding amplifications can be increased by using Darlington transistors or other current control transistors.
- FIG. 1 shows a circuit diagram of the integrated circuit
- FIG. 2 shows the integrated circuit in connection with an inductive load
- FIG. 3 shows a diagram with the time course of the current through the integrated circuit.
- FIG. 1 A circuit diagram of the integrated circuit is shown in FIG.
- the circuit has a collector terminal C, a base terminal B, an emitter terminal E and transistors T1, T2, T3, TE, T5, T6, T9 and T10.
- the transistors T1, T2, TE, T3, T9, T5 are designed as NPN transistors.
- the transistors T10 and T6 are designed as pnp transistors. It goes without saying that by changing the applied potentials accordingly, npn- and pnp- Transistors can be interchanged.
- the transistors T1, T2, T3 operate in a Darlington circuit, but this is not a necessary prerequisite for the basic function of the circuit presented.
- the base terminal B is connected to the base terminal of the first transistor Tl via a resistor R1.
- the collector of the transistor T1 is connected to the collector terminal C.
- the emitter of transistor T1 is connected to the base of transistor T2.
- the collector of transistor T2 is connected to the collector terminal.
- the emitter of the collector T2 is connected to the base of the current measuring transistor TE and transistor T3.
- the collectors of the current measuring transistor TE and the transistor T3 are connected to the collector terminal.
- the emitter of the current measuring transistor TE is connected to the emitter terminal E via a resistor R5.
- the emitter of transistor T3 is connected to the emitter terminal.
- the emitter terminal E is connected to the anode of a diode Dl.
- the collector connection is connected to the cathode of the diode Dl.
- the emitter of transistor T6 is connected to the base of transistor Tl.
- the collector of transistor T6 is connected to the emitter terminal.
- the base of transistor T6 is connected to the base of transistor Tl via a resistor R6.
- the base of transistor T6 is connected to the collector of transistor T5.
- the emitter of the transistor T5 is connected to the emitter terminal E.
- the base of the transistor T5 is connected to the node K2 of a voltage divider (formed from R7, R8, R9A and R9B).
- the emitter of transistor T10 is connected to the base of transistor Tl.
- the collector of transistor T10 is connected to node K3 of the voltage divider mentioned above.
- the base of transistor T10 is connected to the base of transistor Tl via a resistor R2.
- a transistor T9 has its collector connected to the base of transistor T10.
- the base of transistor T9 is connected to node K2.
- the emitter of transistor T9 is via a Resistor R3 connected to the emitter terminal E.
- the voltage divider is formed by resistors R7, R8, R9A and R9B.
- the resistor R7 is arranged between the emitter of the transistor T1 and a node Kl.
- the resistor R8 is arranged between the node Kl and the node K2.
- the resistor R9A is arranged between the node K2 and the node K3.
- the resistor R9B is arranged between the node K3 and the emitter terminal E.
- the node Kl is connected to the anode of a diode D2.
- the cathode of the diode D2 is connected to the anode of a diode D3.
- the cathode of the diode D3 is connected to the emitter of the current measuring transistor TE.
- the emitter of the transistor T1 is connected to the emitter of the temperature measuring transistor T9 via a coupling resistor R4.
- the Darlington transistors T1, T2, T3 form a power transistor with which a load between the collector and emitter can be switched accordingly.
- the current measuring transistor TE is connected in parallel to the last transistor T3. A current flows through this transistor TE which is clearly dependent on the current flow through the transistor T3. This current produces a voltage drop across resistor R5. Since only a small current flows through the parallel-connected current measuring transistor TE, the power loss is kept low.
- a voltage divider is formed by the resistors R7, R8, R9A and R9B.
- the base of the current control transistor T5 and the base of the temperature measuring transistor T9 are connected to the node K2.
- the transistor T9 has a much larger emitter area than the transistor T5.
- Resistor R2 also has a larger value than R6. Due to the lower current density in T9 compared to T5, T9 has a lower one Base emitter voltage as T5. Furthermore, the negative temperature coefficient of the base emitter voltage of the temperature measuring transistor T9 is significantly larger than that of the transistor T5. Below a predetermined temperature, the voltage drop across resistor R3 has the effect that the voltage drop across resistor R5 only acts on current control transistor T5.
- the current control transistor T5 When the predetermined control current through the power transistor T1, T2, T3 is reached, the current control transistor T5 is turned on, which derives part of the base current directly to the emitter connection.
- a further current control transistor T6 is provided here for amplification, which is turned on by the current flow through transistor T5. In principle, however, the circuit also works without the transistor T6.
- the temperature measurement transistor T9 Above a predetermined temperature, the temperature measurement transistor T9 is then activated, and a further current flow between the base connection B and the emitter connection E is then made possible via the resistors R2 and R3. With this current flow, a potential arises at the base connection of T10, which turns on the transistor T10.
- thermal regulation is determined by the ratio of thermally synchronous resistances, by the areas of the transistors T5, T6, T9, T10 and by the base emitter voltage U BE (T2, T3) of the transistors T2 and T3.
- the base emitter voltage U BE (T9) of the transistor T9 depends on the temperature because of the larger emitter area of the transistor T9 than the base emitter voltage U BE (T5) of the transistor T5.
- the transistor T10 becomes conductive if:
- the base emitter voltage of the power transistor T2, T3 has the largest spread. However, since this variable only comes into play with the very small resistance ratio R3 / R4, the operating temperature of the thermal limitation is only affected by very small tolerances. The circuit can also be tested by external R3 reduction below the intended response temperature.
- FIG. 2 shows an application of the circuit according to the invention for switching an inductive load.
- the inductive load represented by the coil 1 can be, for example, an ignition coil which can be connected to a ground potential by the circuit, shown here in a simplified manner as a transistor.
- the circuit is activated, for example, by a controller 2.
- the collector current I shown as a function of time for the arrangement according to FIG.
- Curve A shows the time course of the collector current when only the current limitation by the current limiting transistor T5 and the transistor T6 is effective.
- Curve B describes the time course of the collector current when the thermal control by the temperature measuring transistor T9 also intervenes.
- the difference ⁇ I the lowering of the current level after the circuit has responded, essentially depends on the dimensioning of the resistor R4.
- the time ⁇ t can be influenced within certain limits by suitable placement of the temperature measuring transistor T9 and the current control transistor T5 relative to the output stage T3.
- the circuit shown is particularly suitable for wiring with an inductive load, such as. B. with an ignition coil; this is shown in FIG. 2.
- the transistor is opened by a corresponding signal from the controller 2, and the coil 1 is thus arranged between the collector-emitter potential of the switched transistor and a supply voltage. Due to the inductance, the current through the coil and the transistor will slowly increase when charging the coil 1. In this phase, the Darlington transistor works in saturation, with no high power loss due to the low collector-emitter voltage.
- the transistor 2 should be switched off by the controller 2 before the current flow through the coil and the transistor becomes constant over time, since otherwise the transistor has to take over the largest part of the supply voltage, with high power losses having to be dissipated.
- the thermal cut-off only starts when a large current flows through the circuit at high temperature. If the current flow is limited by the inductance of the coil, according to the above explanations, there is no high power loss in the transistor - and therefore no significant increase in temperature, so that the thermal regulation is not activated.
- the diode Dl works as an inverse diode by limiting negative collector-emitter voltages to low values in order, for. B. in ignition applications to vaporize the high-frequency vibrations transformed back from the secondary side of the ignition coil.
- the diodes D2 and D3 are switched in the direction of flow during normal operation of the circuit. A voltage that has a negative temperature coefficient therefore drops across these diodes. This negative temperature coefficient is used to set the temperature coefficient of the current control to the desired value.
- the temperature behavior of the circuit is mainly defined by the thermal properties of the temperature measuring transistor T9. The response temperature of the thermal current control can thus be set exactly.
Abstract
Description
Claims
Priority Applications (4)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US08/669,342 US5841312A (en) | 1994-01-27 | 1995-01-14 | Gating circuit having current measuring and regulating elements and a temperature measuring transistor |
EP95905052A EP0741881B1 (de) | 1994-01-27 | 1995-01-14 | Integrierte schaltung |
DE59502827T DE59502827D1 (de) | 1994-01-27 | 1995-01-14 | Integrierte schaltung |
JP7519808A JPH09508247A (ja) | 1994-01-27 | 1995-01-14 | 集積回路 |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE4402340A DE4402340C1 (de) | 1994-01-27 | 1994-01-27 | Integrierte Schaltung |
DEP4402340.5 | 1994-01-27 |
Publications (1)
Publication Number | Publication Date |
---|---|
WO1995020783A1 true WO1995020783A1 (de) | 1995-08-03 |
Family
ID=6508788
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
PCT/DE1995/000039 WO1995020783A1 (de) | 1994-01-27 | 1995-01-14 | Integrierte schaltung |
Country Status (5)
Country | Link |
---|---|
US (1) | US5841312A (de) |
EP (1) | EP0741881B1 (de) |
JP (1) | JPH09508247A (de) |
DE (2) | DE4402340C1 (de) |
WO (1) | WO1995020783A1 (de) |
Families Citing this family (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DE19519477C2 (de) * | 1995-05-27 | 1998-07-09 | Bosch Gmbh Robert | Integrierte Schaltung mit thermischem Überlastschutz, insb. geeignet für KfZ-Zündspulenansteuerung |
US7411436B2 (en) * | 2006-02-28 | 2008-08-12 | Cornell Research Foundation, Inc. | Self-timed thermally-aware circuits and methods of use thereof |
CN104053976B (zh) * | 2011-11-21 | 2016-01-27 | 穆尔芬根依必派特股份有限公司 | 包括功率晶体管的电子控制电路和监控功率晶体管的使用寿命的方法 |
JP6432201B2 (ja) * | 2014-03-17 | 2018-12-05 | 富士電機株式会社 | 半導体装置および半導体装置の製造方法 |
US10505528B1 (en) * | 2017-09-18 | 2019-12-10 | Apple Inc. | Deterministic shutdown of power module |
Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
FR2281603A1 (fr) * | 1974-08-09 | 1976-03-05 | Texas Instruments France | Source de tension regulee a coefficient de temperature defini |
EP0189885A2 (de) * | 1985-02-01 | 1986-08-06 | Hitachi, Ltd. | Spannungsregler für einen in einem Auto eingesetzten Generator |
EP0498727A1 (de) * | 1991-02-07 | 1992-08-12 | Valeo Equipements Electriques Moteur | Schaltung, die eine temperaturabhängige Referenzspannung produziert, vor allem zur Regulierung der Batterieladungsspannung von einem Wechselstromgenerator |
EP0557739A1 (de) * | 1992-02-26 | 1993-09-01 | Motorola, Inc. | Thermisch abhängige, selbständernde Spannungsquelle |
Family Cites Families (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
DD227835B3 (de) * | 1984-10-01 | 1993-03-11 | Albrecht Juergen Dipl Ing | Integrierte uebertemperatur-schutzschaltungsanordnung |
JPH07113861B2 (ja) * | 1988-01-29 | 1995-12-06 | 株式会社日立製作所 | 半導体素子の状態検出及び保護回路とそれを用いたインバータ回路 |
JPH05299431A (ja) * | 1992-04-16 | 1993-11-12 | Toyota Autom Loom Works Ltd | 電流検出機能付トランジスタ |
JP3363980B2 (ja) * | 1993-01-27 | 2003-01-08 | 三星電子株式会社 | 出力トランジスタのベース電流制御回路および電子装置の出力駆動段回路 |
US5406130A (en) * | 1993-08-09 | 1995-04-11 | Micrel, Inc. | Current driver with shutdown circuit |
-
1994
- 1994-01-27 DE DE4402340A patent/DE4402340C1/de not_active Expired - Fee Related
-
1995
- 1995-01-14 US US08/669,342 patent/US5841312A/en not_active Expired - Fee Related
- 1995-01-14 JP JP7519808A patent/JPH09508247A/ja active Pending
- 1995-01-14 EP EP95905052A patent/EP0741881B1/de not_active Expired - Lifetime
- 1995-01-14 DE DE59502827T patent/DE59502827D1/de not_active Expired - Fee Related
- 1995-01-14 WO PCT/DE1995/000039 patent/WO1995020783A1/de active IP Right Grant
Patent Citations (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
FR2281603A1 (fr) * | 1974-08-09 | 1976-03-05 | Texas Instruments France | Source de tension regulee a coefficient de temperature defini |
EP0189885A2 (de) * | 1985-02-01 | 1986-08-06 | Hitachi, Ltd. | Spannungsregler für einen in einem Auto eingesetzten Generator |
EP0498727A1 (de) * | 1991-02-07 | 1992-08-12 | Valeo Equipements Electriques Moteur | Schaltung, die eine temperaturabhängige Referenzspannung produziert, vor allem zur Regulierung der Batterieladungsspannung von einem Wechselstromgenerator |
EP0557739A1 (de) * | 1992-02-26 | 1993-09-01 | Motorola, Inc. | Thermisch abhängige, selbständernde Spannungsquelle |
Also Published As
Publication number | Publication date |
---|---|
JPH09508247A (ja) | 1997-08-19 |
US5841312A (en) | 1998-11-24 |
EP0741881B1 (de) | 1998-07-15 |
DE59502827D1 (de) | 1998-08-20 |
EP0741881A1 (de) | 1996-11-13 |
DE4402340C1 (de) | 1995-05-24 |
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