USRE41518E1 - Bandpass sigma-delta modulator - Google Patents
Bandpass sigma-delta modulator Download PDFInfo
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- USRE41518E1 USRE41518E1 US11/496,085 US49608506A USRE41518E US RE41518 E1 USRE41518 E1 US RE41518E1 US 49608506 A US49608506 A US 49608506A US RE41518 E USRE41518 E US RE41518E
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M3/00—Conversion of analogue values to or from differential modulation
- H03M3/02—Delta modulation, i.e. one-bit differential modulation
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M3/00—Conversion of analogue values to or from differential modulation
- H03M3/30—Delta-sigma modulation
- H03M3/39—Structural details of delta-sigma modulators, e.g. incremental delta-sigma modulators
- H03M3/402—Arrangements specific to bandpass modulators
- H03M3/404—Arrangements specific to bandpass modulators characterised by the type of bandpass filters used
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
- H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
- H03H7/01—Frequency selective two-port networks
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M7/00—Conversion of a code where information is represented by a given sequence or number of digits to a code where the same, similar or subset of information is represented by a different sequence or number of digits
- H03M7/30—Compression; Expansion; Suppression of unnecessary data, e.g. redundancy reduction
- H03M7/3002—Conversion to or from differential modulation
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M3/00—Conversion of analogue values to or from differential modulation
- H03M3/30—Delta-sigma modulation
- H03M3/322—Continuously compensating for, or preventing, undesired influence of physical parameters
- H03M3/324—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by means or methods for compensating or preventing more than one type of error at a time, e.g. by synchronisation or using a ratiometric arrangement
- H03M3/344—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by means or methods for compensating or preventing more than one type of error at a time, e.g. by synchronisation or using a ratiometric arrangement by filtering other than the noise-shaping inherent to delta-sigma modulators, e.g. anti-aliasing
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03M—CODING; DECODING; CODE CONVERSION IN GENERAL
- H03M3/00—Conversion of analogue values to or from differential modulation
- H03M3/30—Delta-sigma modulation
- H03M3/322—Continuously compensating for, or preventing, undesired influence of physical parameters
- H03M3/324—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by means or methods for compensating or preventing more than one type of error at a time, e.g. by synchronisation or using a ratiometric arrangement
- H03M3/346—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by means or methods for compensating or preventing more than one type of error at a time, e.g. by synchronisation or using a ratiometric arrangement by suppressing active signals at predetermined times, e.g. muting, using non-overlapping clock phases
- H03M3/348—Continuously compensating for, or preventing, undesired influence of physical parameters characterised by means or methods for compensating or preventing more than one type of error at a time, e.g. by synchronisation or using a ratiometric arrangement by suppressing active signals at predetermined times, e.g. muting, using non-overlapping clock phases using return-to-zero signals
Definitions
- a sigma-delta A/D converter consists of a sigma-delta modulator and a digital filter.
- FIG. 1 shows a typical arrangement of a bandpass sigma-delta modulator.
- the key element in the modulator is the resonator 2 which provides the quantization noise shaping. That is, the resonator acts as a bandpass filter in a band around its resonance frequency. The resonator needs to operate at a high frequency and have a high Q (quality factor) value.
- the output of the resonator is passed to a quantizer 3 which produces a digital “1” signal if its input exceeds a threshold and a digital “0” signal if the input is less than the threshold.
- the bandpass modulator shown in FIG. 3 is of the second order, and provides second order noise-shaping as shown in FIG. 4 .
- This modulator based on the micro-mechanical resonator is capable of digitizing the analog input signal, but with a limited resolution. Better resolution can be obtained using a fourth order modulator as will be described below.
- the Q values of the micro-mechanical resonator can easily be greater than 1000 and even as high as 10,000, it is possible to have a high resonance frequency, up to a gigahertz using this type of resonator. Accordingly, the use of this different resonator allows the modulator to operate at the gigahertz sampling frequency range with good resolution.
- FIG. 5 illustrates a corresponding fourth order bandpass sigma-delta modulator using a micro-mechanical resonator.
- Input summing circuit 1 adds the input to the modulator and the feedback from 2 gain stages in a similar fashion to FIG. 3 .
- the output of the summing circuit is fed to micro-mechanical resonator 2 which produces an output to gain stage G 1 , 6 .
- This output is then applied to the second summing circuit 9 along with two additional feedback signals.
- the sum of these signals is used as the input to the second micro-mechanical resonator 10 which also selectively passes the signal at the resonance frequency and attenuates the signal at other frequencies. This output is adjusted by gain stage G 4 , 11 and its output is applied to quantizer 3 .
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- Engineering & Computer Science (AREA)
- Theoretical Computer Science (AREA)
- Compression, Expansion, Code Conversion, And Decoders (AREA)
- Piezo-Electric Or Mechanical Vibrators, Or Delay Or Filter Circuits (AREA)
- Surface Acoustic Wave Elements And Circuit Networks Thereof (AREA)
- Magnetic Resonance Imaging Apparatus (AREA)
- Measuring Pulse, Heart Rate, Blood Pressure Or Blood Flow (AREA)
- Control Of Gas Discharge Display Tubes (AREA)
- Measurement And Recording Of Electrical Phenomena And Electrical Characteristics Of The Living Body (AREA)
- Oscillators With Electromechanical Resonators (AREA)
- Table Devices Or Equipment (AREA)
Abstract
A bandpass sigma-delta modulator using acoustic resonators or micro-mechanical resonators. In order to improve resolution at high frequencies, acoustic resonators or micro-mechanical resonators are utilized in a sigma-delta modulator instead of electronic resonators. The quantized output is fed back using a pair of D/A converters to an input summation device. In fourth order devices, the feed back is to two summation devices in series. Such a sigma-delta modulator is usable in a software defined radio cellular telephone system and in other applications where high-frequency and high-resolution A/D conversion is required.
Description
This application claims priority on provisional Application No. 60/331,256 filed Nov. 13, 2001, the entire contents of which are hereby incorporated by reference.
The present invention relates generally to a bandpass sigma-delta modulator, and more particularly to a bandpass sigma-delta modulator using an acoustic resonator or micro-mechanical resonator.
Cellular telephone systems have become very popular in many countries throughout the world. Unfortunately, the specific standards adopted by different countries are often different and cellular devices from one country will not be operable within another system. Accordingly, completely different handsets are necessary if a person is operating in two different countries having different standards.
As a result of this difficulty, there have been some efforts to provide a single device that is operable in different countries having different standards. A technology known as software-defined radio (SDR) provides one solution to this problem. In the SDR system, the entire band of RF or IF signal is digitized and the channel is selected using a programmable digital filter. Thus, the SDR can be reconfigured through the software to suit different standards. However, this effort has not been completely successful because it requires a high-speed A/D converter that must have not only high-speed, but also provide adequate resolution. In the ideal SDR arrangement, the RF is directly digitized in the receiver. It requires that the A/D converter have a speed in the gigahertz range, and also have a dynamic range over a 100 dB, which is equivalent to a 16-bit resolution. Among the various A/D converters, the sigma-delta A/D converter has promise in achieving the desired dynamic range. However, it is only achievable at a much lower frequency band. As the frequency increases, circuit imperfections become dominant and degrade the dynamic range of the A/D converter. At the gigahertz sampling frequency range, the highest dynamic range for the reported bandpass sigma-delta modulator is 75 dB, which only corresponds to a 12.5 bit resolution.
A sigma-delta A/D converter consists of a sigma-delta modulator and a digital filter. FIG. 1 shows a typical arrangement of a bandpass sigma-delta modulator. The key element in the modulator is the resonator 2 which provides the quantization noise shaping. That is, the resonator acts as a bandpass filter in a band around its resonance frequency. The resonator needs to operate at a high frequency and have a high Q (quality factor) value. The output of the resonator is passed to a quantizer 3 which produces a digital “1” signal if its input exceeds a threshold and a digital “0” signal if the input is less than the threshold. This digital signal of a series of 0's and 1's becomes the output of the sigma-delta modulator. These signals are also fed back to a D/A converter 4, and the resultant analog signal is applied as a second input to summation device 1 which also receives the input to the modulator. The difference between the input and the feedback of the summation device produces an input to the resonator.
Typically, the resonator is made of one of three different electronic circuits, namely, a passive L-C tank, a transconductor-capacitor or a switch-capacitor. However, none of these circuits have been successful in the situation described. The first two circuits cannot achieve a high Q value due to parasitic losses and non-linearity. Typical Q values are around 10 and 40 for the integrated L-C tank with and without Q enhancement, respectively. The enhanced Q value for the transconductor-capacitor resonator can be up to 300 at a frequency of several hundred MHz. The switch-capacitor resonator is restricted by its low resonant frequency (<100 MHz) due to the slow settling behavior of the circuit. The use of these types of resonators prevents the sigma-delta modulator from achieving a high speed and high dynamic range at the same time as is required in an SDR situation. In order to achieve a workable SDR system, it is necessary to find a resonator which is usable in a sigma-delta modulator to achieve high speed and high dynamic range.
Accordingly, one object of this invention is to provide a bandpass sigma-delta modulator having high-speed and high-dynamic range.
Another object of the invention is to provide a bandpass sigma-delta modulator using a micro-mechanical resonator.
Another object of the invention is to provide a bandpass sigma-delta modulator utilizing an acoustic resonator.
A further object of this invention is to provide a second order bandpass sigma-delta modulator having two D/A converters.
A still further object of this invention is to provide a fourth order sigma-delta modulator having two D/A converters and two summation devices.
A still further object of this invention is to provide a sigma-delta A/D converter including a sigma-delta modulator having a resonator of the micro-mechanical or acoustical type.
Briefly, these and other objects of the invention are achieved by using either a micro-mechanical resonator or an acoustical resonator as a bandpass filter which provides an output to a quantizer. The output of the quantizer acts as the output of the modulator and is also fed back to two different D/A converters. The output of the two converters is adjusted by a gain and applied to a summation device, along with the input. The output of the summation device is applied as an input to the resonator. In the fourth order device, two resonators are used along with a second summation device.
A more complete appreciation of the invention and many of the attendant advantages thereof will be readily obtained as the same becomes better understood by reference to the following detailed description when considered in connection with the accompanying drawings, wherein:
Referring now to the drawings, wherein like reference numerals designate identical corresponding parts throughout the several views, and more particularly to FIG. 3 which shows a second order sigma-delta modulator using a micro-mechanical resonator. The summing circuit 1 adds the analog input to two outputs from two gain stages. The sum forming the output of the summing circuit becomes the input to the micro-mechanical resonator 2. The resonator selectively passes the signal at its resonance frequency and attenuates signals at other frequencies. The output from the resonator is adjusted by gain stage G1, 6 and fed to quantizer 3. The signal is quantized to form a series of binary bits as in FIG. 1 which form the output of the modulator. The output is also fed back as an input to a pair of D/A converters, DAC1, 4, and DAC2, 5. The converters are both one bit converters but have different output pulses. One is a return to zero converter, whereas the other is a half return to zero converter. As a result, they have different transfer functions in the frequency domain. The output of the converters are analog signals which are fed back to the summing circuit through gain stages G2, 7 and G3, 8. The value of the gains in G1-G3 may be either positive or negative and often the gains in the feedback path are negative so that the feedback is subtracted from the input signal in a similar fashion to FIG. 1.
Since the micro-mechanical resonator 2 is a second order system, the bandpass modulator shown in FIG. 3 is of the second order, and provides second order noise-shaping as shown in FIG. 4. This modulator based on the micro-mechanical resonator is capable of digitizing the analog input signal, but with a limited resolution. Better resolution can be obtained using a fourth order modulator as will be described below. However, since the Q values of the micro-mechanical resonator can easily be greater than 1000 and even as high as 10,000, it is possible to have a high resonance frequency, up to a gigahertz using this type of resonator. Accordingly, the use of this different resonator allows the modulator to operate at the gigahertz sampling frequency range with good resolution.
The output is the output of a fourth order bandpass sigma-delta modulator having a digitized form of the input analog signal. By having two micro-mechanical resonators in the loop, this device provides fourth order noise-shaping as shown in FIG. 6. This fourth order modulator using two micro-mechanical resonators is able to provide digitization of the analog signal with high resolution.
As in the embodiment of FIG. 3 , the gain stages can be either positive or negative, and either gain or attenuation, as necessary.
Another type of resonator which has superior performance to electronic resonators are acoustic resonators. A surface acoustic wave (SAW) resonator has a resonance frequency of 50-2,000 MHz. It also has a Q factor of 4,000-15,000. A film bulk acoustic resonator (FBAR) has a resonance frequency of 300-10,000 MHz and a Q factor of 100 to 1000. The use of these types of resonators in the bandpass sigma-delta modulator also produces a digital output with high resolution at high frequencies.
Numerous additional modifications and variations of the present invention are possible in light of the above teachings. It is therefore to be understood that within the scope of the appended claims, the invention may be practiced otherwise than as specifically described herein.
Claims (12)
1. A bandpass sigma-delta modulator comprising:
a summing device for receiving an input and first and second feedback signals and producing an output;
a micro-mechanical resonator receiving the output of said summing circuit as an input and producing an output;
a quantizer receiving the output of said micro-mechanical resonator and producing a digital output which is the output of said modulator and;
first and second D/A converters receiving said output of said quantizer as an input and producing said first and second feedback signals.
2. The bandpass sigma-delta modulator according to claim 1 , wherein gain stages are provided between said first D/A converter and said summing device, between said second D/A converter and said summing device, and between said micro-mechanical resonator and said quantizer.
3. A bandpass sigma-delta modulator comprising:
a first summing device receiving an input, a first feedback signal and a second feedback signal and producing an output;
a first micro-mechanical resonator receiving said output from said first summing device and producing an output;
a second summing device receiving said output from said first micro-mechanical resonator and receiving third and fourth feedback signals and producing an output;
a second micro-mechanical resonator receiving said output from said second summing circuit and producing an output;
a quantizer receiving said output from said second micro-mechanical resonator and producing an output which is the output of said modulator; and
first and second D/A converters, each receiving the output of said quantizer as an input, said first D/A converter producing said first and third feedback signals, and said second D/A converter producing said second and fourth feedback signals.
4. The bandpass sigma-delta modulator according to claim 3 , further comprising gain stages between said first micro-mechanical resonator and said second summing device, between said second micro-mechanical resonator and said quantizer, between said first D/A converter and said first summing device, between said first D/A converter and said second summing device, between said second D/A converter and said first summing device and between said second D/A converter and said second summing device.
5. A bandpass sigma-delta modulator, comprising:
a summing device configured to receive an input signal, and produce a first output signal;
a micro-mechanical resonator coupled to the summing device and configured to provide a second output signal based, at least in part, on the first output signal;
a quantizer coupled to the micro-mechanical resonator and configured to provide a digital output signal based, at least in part, on the second output signal; and
first and second D/A converters coupled to the quantizer and configured to produce the first and second feedback signals based, at least in part, on the digital output, wherein the first and second feedback signals affect a gain applied to the input signal.
6. The bandpass sigma-delta modulator of claim 5 , further comprising one or more gain stages coupled to the first and second D/A converters and configured to apply the gain to the input signal based, at least in part, on the first and second feedback signals.
7. The bandpass sigma-delta modulator of claim 5 , further comprising:
a first gain stage coupled between the summing device and the first D/A converter;
a second gain stage coupled between the summing device and the second D/A converter; and
a third gain stage coupled between the micro-mechanical resonator and the quantizer.
8. A method, comprising:
combining an input signal with a first analog feedback signal and a second analog feedback signal to apply a gain to the input signal and to provide a first output signal;
receiving a second output signal from a micro-mechanical resonator, wherein the second output signal is generated based, at least in part, on the first output signal;
quantizing the second output signal to provide a digital output signal based, at least in part, on the second output signal; and
generating the first analog feedback signal and the second analog feedback signal based, at least in part, on the digital output signal.
9. The method of claim 8 , further comprising employing one or more gain stages to apply the gain to the input signal based, at least in part, on the first analog feedback signal and the second analog feedback signal.
10. A cellular telephone, comprising:
a software-defined radio configured to receive a digital signal; and
a bandpass sigma-delta modulator including:
a summing device configured to receive an input signal and produce a first output signal;
a micro-mechanical resonator coupled to the summing device and configured to provide a second output signal based, at least in part, on the first output signal;
a quantizer coupled to the micro-mechanical resonator and configured to provide the digital signal based, at least in part, on the second output signal; and
first and second D/A converters coupled to the quantizer and configured to produce first and second feedback signals based, at least in part, on the digital signal, wherein the first and second feedback signals affect a gain applied to the input signal.
11. The cellular telephone of claim 10 , wherein the bandpass sigma-delta modulator further comprises one or more gain stages coupled to the first and second D/A converters and configured to apply the gain to the input signal based, at least in part, on the first and second feedback signals.
12. The cellular telephone of claim 10 , wherein the bandpass sigma-delta modulator further comprises:
a first gain stage coupled between the summing device and the first D/A converter;
a second gain stage coupled between the summing device and the second D/A converter; and
a third gain stage coupled between the micro-mechanical resonator and the quantizer.
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US11/496,085 USRE41518E1 (en) | 2001-11-13 | 2006-07-27 | Bandpass sigma-delta modulator |
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US33125601P | 2001-11-13 | 2001-11-13 | |
US10/188,071 US6768435B2 (en) | 2001-11-13 | 2002-07-03 | Bandpass sigma-delta modulator |
US11/496,085 USRE41518E1 (en) | 2001-11-13 | 2006-07-27 | Bandpass sigma-delta modulator |
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US10/188,071 Reissue US6768435B2 (en) | 2001-11-13 | 2002-07-03 | Bandpass sigma-delta modulator |
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US10/188,071 Ceased US6768435B2 (en) | 2001-11-13 | 2002-07-03 | Bandpass sigma-delta modulator |
US10/867,688 Expired - Lifetime US7034727B2 (en) | 2001-11-13 | 2004-06-16 | Bandpass sigma-delta modulator |
US11/496,085 Expired - Lifetime USRE41518E1 (en) | 2001-11-13 | 2006-07-27 | Bandpass sigma-delta modulator |
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US10/188,071 Ceased US6768435B2 (en) | 2001-11-13 | 2002-07-03 | Bandpass sigma-delta modulator |
US10/867,688 Expired - Lifetime US7034727B2 (en) | 2001-11-13 | 2004-06-16 | Bandpass sigma-delta modulator |
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US (3) | US6768435B2 (en) |
EP (2) | EP1684421B1 (en) |
JP (2) | JP4355841B2 (en) |
KR (1) | KR100896570B1 (en) |
AT (2) | ATE330368T1 (en) |
AU (1) | AU2002349865A1 (en) |
DE (2) | DE60212440T2 (en) |
SG (1) | SG146443A1 (en) |
WO (1) | WO2003043198A2 (en) |
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20140285368A1 (en) * | 2011-11-14 | 2014-09-25 | Telefonaiktiebolaget L M Ericsson (publ) | Analog-to-Digital Converter |
US9225349B2 (en) | 2013-08-20 | 2015-12-29 | Skyworks Solutions, Inc. | Dither-less multi-stage noise shaping fractional-N frequency synthesizer systems and methods |
US9407282B2 (en) | 2011-11-14 | 2016-08-02 | Telefonaktiebolaget Lm Ericsson (Publ) | Analog-to-digital converter |
Families Citing this family (23)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6768435B2 (en) * | 2001-11-13 | 2004-07-27 | National University Of Singapore | Bandpass sigma-delta modulator |
US7885409B2 (en) | 2002-08-28 | 2011-02-08 | Rockwell Collins, Inc. | Software radio system and method |
DE10320674B4 (en) * | 2003-05-08 | 2009-01-15 | Litef Gmbh | Pulse modulator and method for pulse modulation |
DE10320675B4 (en) * | 2003-05-08 | 2006-03-16 | Litef Gmbh | Operating method for a Coriolis gyro and appropriate evaluation / control electronics |
DE10331572B4 (en) * | 2003-07-11 | 2005-06-09 | Infineon Technologies Ag | Sigma-delta converter arrangement |
US7034728B2 (en) * | 2004-08-11 | 2006-04-25 | Raytheon Company | Bandpass delta-sigma modulator with distributed feedforward paths |
US7307564B1 (en) | 2004-10-25 | 2007-12-11 | Hrl Laboratories, Llc | Continuous-time delta-sigma modulators using distributed resonators |
CN101248580B (en) * | 2005-07-20 | 2012-05-02 | 新加坡国立大学 | Anti-resonance counteraction in resonator |
US20070223599A1 (en) * | 2005-07-25 | 2007-09-27 | Sysair, Inc., A Delaware Corporation | Cellular PC modem architecture and method of operation |
US7262726B2 (en) * | 2005-08-09 | 2007-08-28 | Analog Devices, Inc. | Quadrature bandpass ΔΣ converter |
DE102005057768B4 (en) * | 2005-12-02 | 2012-01-12 | Xignal Technologies Ag | Time-continuous delta-sigma analog-to-digital converter |
US7720506B1 (en) | 2006-07-28 | 2010-05-18 | Rockwell Collins, Inc. | System and method of providing antenna specific front ends for aviation software defined radios |
US7831255B1 (en) | 2006-07-31 | 2010-11-09 | Rockwell Collins, Inc. | System and method of providing automated availability and integrity verification for aviation software defined radios |
US7352311B2 (en) * | 2006-08-22 | 2008-04-01 | Freescale Semiconductor, Inc. | Continuous time noise shaping analog-to-digital converter |
US7852247B2 (en) * | 2006-12-05 | 2010-12-14 | Texas Instruments Incorporated | Mixed-signal filter |
JP4789211B2 (en) * | 2007-01-16 | 2011-10-12 | ルネサスエレクトロニクス株式会社 | Semiconductor integrated circuit including an A / D converter composed of a bandpass ΔΣ modulator |
US20090312196A1 (en) * | 2008-06-13 | 2009-12-17 | Codexis, Inc. | Method of synthesizing polynucleotide variants |
GB2463879A (en) * | 2008-09-25 | 2010-03-31 | Ubidyne Inc | Apparatus and method for the calibration of delta-sigma modulators of the continuous time, band pass, type. |
WO2010046859A1 (en) | 2008-10-23 | 2010-04-29 | Nxp B.V. | Sigma-delta modulator |
JP5198427B2 (en) * | 2009-12-29 | 2013-05-15 | ザインエレクトロニクス株式会社 | Sigma delta modulator |
US8576024B2 (en) * | 2010-02-11 | 2013-11-05 | Hollinworth Fund, L.L.C. | Electro-acoustic filter |
KR101136969B1 (en) * | 2010-12-30 | 2012-04-19 | 전자부품연구원 | Bandpass modulator |
JP4906146B2 (en) * | 2011-06-24 | 2012-03-28 | ルネサスエレクトロニクス株式会社 | Semiconductor integrated circuit including an A / D converter composed of a bandpass ΔΣ modulator |
Citations (15)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US3731230A (en) | 1971-12-17 | 1973-05-01 | Motorola Inc | Broadband circuit for minimizing the effects of crystal shunt capacitance |
US4577168A (en) | 1984-12-03 | 1986-03-18 | R. F. Monolithics, Inc. | Notch filter |
US4754242A (en) | 1986-03-04 | 1988-06-28 | Murata Manufacturing Co., Ltd. | Resonator |
US5392039A (en) * | 1991-06-01 | 1995-02-21 | Gec-Marconi Lmited | Sigma-delta analog to digital converter |
US5499003A (en) | 1994-10-03 | 1996-03-12 | Motorola, Inc. | Differential saw filter including series coupled resonant/antiresonant tracks |
EP0740411A1 (en) | 1994-11-10 | 1996-10-30 | Fujitsu Limited | Acoustic wave filter |
US5675296A (en) | 1995-01-11 | 1997-10-07 | Tomikawa; Yoshiro | Capacitive-component reducing circuit in electrostatic-type transducer means |
JP2001044790A (en) | 1999-07-30 | 2001-02-16 | Kyocera Corp | Surface acoustic wave device |
JP2001217649A (en) | 2000-02-04 | 2001-08-10 | Nippon Dempa Kogyo Co Ltd | Piezoelectric oscillation circuit |
US6281652B1 (en) * | 2000-03-24 | 2001-08-28 | Western Digital Corporation | Method of using two low-resolution DACS for converting high-resolution digital demands into analog output signals that monotonically drive an actuator motor in a disk drive |
US6346898B1 (en) * | 2000-08-07 | 2002-02-12 | Audio Logic, Inc. | Multilevel analog to digital data converter having dynamic element matching in a reference data path |
US6362764B1 (en) * | 1999-08-05 | 2002-03-26 | Yamaha Corporation | Digital to analog conversion apparatus and method with cross-fading between new and old data |
US6414615B1 (en) * | 2000-03-22 | 2002-07-02 | Raytheon Company | Excess delay compensation in a delta sigma modulator analog-to-digital converter |
US6462687B1 (en) * | 2001-04-03 | 2002-10-08 | International Business Machines Corporatiom | High performance delta sigma ADC using a feedback NRZ sin DAC |
US6473011B1 (en) * | 1999-08-19 | 2002-10-29 | Jesper Steensgaard-Madsen | Serial D/A converter compensating for capacitor mismatch errors |
Family Cites Families (21)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
JPS61157112A (en) * | 1984-12-28 | 1986-07-16 | Toshiba Corp | Surface acoustic wave resonator |
JP2545757B2 (en) * | 1987-03-26 | 1996-10-23 | 大日本インキ化学工業株式会社 | Novel pyridine-based optically active compound |
JPH04134913A (en) * | 1990-09-26 | 1992-05-08 | Nippon Dempa Kogyo Co Ltd | Crystal oscillator |
US5283578A (en) * | 1992-11-16 | 1994-02-01 | General Electric Company | Multistage bandpass Δ Σ modulators and analog-to-digital converters |
JPH08210856A (en) * | 1994-11-18 | 1996-08-20 | Yoshiro Tomikawa | Detector using piezoelectric vibrator |
US5729230A (en) * | 1996-01-17 | 1998-03-17 | Hughes Aircraft Company | Delta-Sigma Δ-Σ modulator having a dynamically tunable continuous time Gm-C architecture |
US5983719A (en) * | 1997-07-31 | 1999-11-16 | Litton Systems, Inc. | Low quantization method and apparatus for vibratory rotation sensors |
US5982315A (en) * | 1997-09-12 | 1999-11-09 | Qualcomm Incorporated | Multi-loop Σ Δ analog to digital converter |
US6292121B1 (en) * | 1998-01-09 | 2001-09-18 | Lecroy Corporation | Delta sigma-analog-to-digital converter |
US6271781B1 (en) * | 1998-06-10 | 2001-08-07 | Lockheed Martin Corporation | Nonlinear filter correction of multibit ΣΔ modulators |
US6225928B1 (en) * | 1999-03-10 | 2001-05-01 | Cirrus Logic Inc. | Complex bandpass modulator and method for analog-to-digital converters |
JP2001298365A (en) * | 2000-04-11 | 2001-10-26 | Nippon Telegr & Teleph Corp <Ntt> | Noise shaping a/d conversion circuit and noise shaping circuit |
US6868288B2 (en) * | 2000-08-26 | 2005-03-15 | Medtronic, Inc. | Implanted medical device telemetry using integrated thin film bulk acoustic resonator filtering |
FR2823619B1 (en) * | 2001-04-11 | 2003-06-27 | Commissariat Energie Atomique | SIGMA-DELTA BANDWAY MODULATOR AND USES OF THE SIGMA DELTA MOLOR FOR CONVERSION, DETECTION AND PRODUCTION OF SIGNALS |
FR2826207B1 (en) * | 2001-06-13 | 2004-12-10 | Eads Defence & Security Ntwk | SIGMA-DELTA BANDPASS ANALOG-TO-DIGITAL CONVERTER AND SIGMA-DELTA MASH CONVERTER INCORPORATING |
US6768435B2 (en) * | 2001-11-13 | 2004-07-27 | National University Of Singapore | Bandpass sigma-delta modulator |
EP1324497B1 (en) * | 2001-12-27 | 2004-09-29 | STMicroelectronics S.r.l. | Method for self-calibrating a frequency of a modulator circuit, and circuit using said method |
TW543304B (en) * | 2002-02-19 | 2003-07-21 | Ind Tech Res Inst | Four order sigma-delta modulator |
JP2004158970A (en) * | 2002-11-05 | 2004-06-03 | Ube Ind Ltd | Band filter employing thin film piezoelectric resonator |
US6954159B1 (en) * | 2003-07-01 | 2005-10-11 | Impinj, Inc. | Low distortion band-pass analog to digital converter with feed forward |
DE10331572B4 (en) * | 2003-07-11 | 2005-06-09 | Infineon Technologies Ag | Sigma-delta converter arrangement |
-
2002
- 2002-07-03 US US10/188,071 patent/US6768435B2/en not_active Ceased
- 2002-11-13 DE DE60212440T patent/DE60212440T2/en not_active Expired - Lifetime
- 2002-11-13 DE DE60224461T patent/DE60224461T2/en not_active Expired - Lifetime
- 2002-11-13 AT AT02786344T patent/ATE330368T1/en not_active IP Right Cessation
- 2002-11-13 AU AU2002349865A patent/AU2002349865A1/en not_active Abandoned
- 2002-11-13 WO PCT/SG2002/000266 patent/WO2003043198A2/en active IP Right Grant
- 2002-11-13 AT AT06002858T patent/ATE382983T1/en not_active IP Right Cessation
- 2002-11-13 KR KR1020047007308A patent/KR100896570B1/en active IP Right Grant
- 2002-11-13 EP EP06002858A patent/EP1684421B1/en not_active Expired - Lifetime
- 2002-11-13 EP EP02786344A patent/EP1454416B1/en not_active Expired - Lifetime
- 2002-11-13 SG SG200602780-9A patent/SG146443A1/en unknown
- 2002-11-13 JP JP2003544913A patent/JP4355841B2/en not_active Expired - Fee Related
-
2004
- 2004-06-16 US US10/867,688 patent/US7034727B2/en not_active Expired - Lifetime
-
2006
- 2006-07-27 US US11/496,085 patent/USRE41518E1/en not_active Expired - Lifetime
-
2008
- 2008-12-26 JP JP2008331872A patent/JP4776681B2/en not_active Expired - Fee Related
Patent Citations (15)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US3731230A (en) | 1971-12-17 | 1973-05-01 | Motorola Inc | Broadband circuit for minimizing the effects of crystal shunt capacitance |
US4577168A (en) | 1984-12-03 | 1986-03-18 | R. F. Monolithics, Inc. | Notch filter |
US4754242A (en) | 1986-03-04 | 1988-06-28 | Murata Manufacturing Co., Ltd. | Resonator |
US5392039A (en) * | 1991-06-01 | 1995-02-21 | Gec-Marconi Lmited | Sigma-delta analog to digital converter |
US5499003A (en) | 1994-10-03 | 1996-03-12 | Motorola, Inc. | Differential saw filter including series coupled resonant/antiresonant tracks |
EP0740411A1 (en) | 1994-11-10 | 1996-10-30 | Fujitsu Limited | Acoustic wave filter |
US5675296A (en) | 1995-01-11 | 1997-10-07 | Tomikawa; Yoshiro | Capacitive-component reducing circuit in electrostatic-type transducer means |
JP2001044790A (en) | 1999-07-30 | 2001-02-16 | Kyocera Corp | Surface acoustic wave device |
US6362764B1 (en) * | 1999-08-05 | 2002-03-26 | Yamaha Corporation | Digital to analog conversion apparatus and method with cross-fading between new and old data |
US6473011B1 (en) * | 1999-08-19 | 2002-10-29 | Jesper Steensgaard-Madsen | Serial D/A converter compensating for capacitor mismatch errors |
JP2001217649A (en) | 2000-02-04 | 2001-08-10 | Nippon Dempa Kogyo Co Ltd | Piezoelectric oscillation circuit |
US6414615B1 (en) * | 2000-03-22 | 2002-07-02 | Raytheon Company | Excess delay compensation in a delta sigma modulator analog-to-digital converter |
US6281652B1 (en) * | 2000-03-24 | 2001-08-28 | Western Digital Corporation | Method of using two low-resolution DACS for converting high-resolution digital demands into analog output signals that monotonically drive an actuator motor in a disk drive |
US6346898B1 (en) * | 2000-08-07 | 2002-02-12 | Audio Logic, Inc. | Multilevel analog to digital data converter having dynamic element matching in a reference data path |
US6462687B1 (en) * | 2001-04-03 | 2002-10-08 | International Business Machines Corporatiom | High performance delta sigma ADC using a feedback NRZ sin DAC |
Non-Patent Citations (1)
Title |
---|
Chen, Wai-Kai: "Two-Port Synthesis by Ladder Development," 1995, The Circuits and Filters Handbook 72, CRC Press, Inc., Chicago XP002254884, ISBN-0-8493-8341-2. |
Cited By (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20140285368A1 (en) * | 2011-11-14 | 2014-09-25 | Telefonaiktiebolaget L M Ericsson (publ) | Analog-to-Digital Converter |
US9118344B2 (en) * | 2011-11-14 | 2015-08-25 | Telefonaktiebolaget L M Ericsson (Publ) | Analog-to-digital converter |
US9407282B2 (en) | 2011-11-14 | 2016-08-02 | Telefonaktiebolaget Lm Ericsson (Publ) | Analog-to-digital converter |
US9225349B2 (en) | 2013-08-20 | 2015-12-29 | Skyworks Solutions, Inc. | Dither-less multi-stage noise shaping fractional-N frequency synthesizer systems and methods |
US9231606B2 (en) * | 2013-08-20 | 2016-01-05 | Skyworks Solutions, Inc. | Dither-less error feedback fractional-N frequency synthesizer systems and methods |
US9450593B2 (en) | 2013-08-20 | 2016-09-20 | Skyworks Solutions, Inc. | Dither-less error feedback fractional-n frequency synthesizer systems and methods |
US9654122B2 (en) | 2013-08-20 | 2017-05-16 | Skyworks Solutions, Inc. | Dither-less multi-stage noise shaping fractional-N frequency synthesizer systems and methods |
Also Published As
Publication number | Publication date |
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KR20040066119A (en) | 2004-07-23 |
US6768435B2 (en) | 2004-07-27 |
EP1684421A1 (en) | 2006-07-26 |
JP4355841B2 (en) | 2009-11-04 |
US20030090399A1 (en) | 2003-05-15 |
KR100896570B1 (en) | 2009-05-07 |
ATE382983T1 (en) | 2008-01-15 |
AU2002349865A1 (en) | 2003-05-26 |
US20040239541A1 (en) | 2004-12-02 |
JP4776681B2 (en) | 2011-09-21 |
JP2009112043A (en) | 2009-05-21 |
EP1454416B1 (en) | 2006-06-14 |
DE60224461D1 (en) | 2008-02-14 |
WO2003043198A3 (en) | 2004-02-26 |
ATE330368T1 (en) | 2006-07-15 |
US7034727B2 (en) | 2006-04-25 |
JP2005510111A (en) | 2005-04-14 |
EP1684421B1 (en) | 2008-01-02 |
EP1454416A2 (en) | 2004-09-08 |
SG146443A1 (en) | 2008-10-30 |
DE60212440T2 (en) | 2007-02-08 |
WO2003043198A2 (en) | 2003-05-22 |
DE60212440D1 (en) | 2006-07-27 |
DE60224461T2 (en) | 2008-12-24 |
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