US6169683B1 - Resonant gate drive for synchronous rectifiers - Google Patents

Resonant gate drive for synchronous rectifiers Download PDF

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Publication number
US6169683B1
US6169683B1 US09/414,247 US41424799A US6169683B1 US 6169683 B1 US6169683 B1 US 6169683B1 US 41424799 A US41424799 A US 41424799A US 6169683 B1 US6169683 B1 US 6169683B1
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Prior art keywords
circuit
energy
coupled
synchronous rectifier
terminal
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Expired - Lifetime
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US09/414,247
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English (en)
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Richard Farrington
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Ericsson Inc
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Ericsson Inc
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Assigned to ERICSSON INC. reassignment ERICSSON INC. ASSIGNMENT OF ASSIGNORS INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: FARRINGTON, RICHARD
Priority to US09/414,247 priority Critical patent/US6169683B1/en
Priority to AU77486/00A priority patent/AU7748600A/en
Priority to PCT/US2000/027204 priority patent/WO2001026209A1/en
Priority to DE60007558T priority patent/DE60007558T2/de
Priority to EP00967262A priority patent/EP1243065B1/en
Priority to JP2001529063A priority patent/JP4574930B2/ja
Priority to CNB008167397A priority patent/CN100492848C/zh
Priority to AT00967262T priority patent/ATE257290T1/de
Priority to TW089120998A priority patent/TW561678B/zh
Publication of US6169683B1 publication Critical patent/US6169683B1/en
Application granted granted Critical
Priority to HK03106736.3A priority patent/HK1054470B/zh
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This invention relates generally to DC-to-DC converters, and to a resonant gate drive for synchronous rectifiers using an external driving circuit. More particularly, the invention relates to an externally driven synchronous rectifier circuit for a DC-to-DC power converter having an energy recovery circuit configured for storing energy associated with charging and discharging the input capacitance of MOSFET type synchronous rectifier devices.
  • the energy dissipated by charging and discharging the input capacitance of the rectifiers can be significant.
  • components with low drain to source resistance have to be selected.
  • low drain to source resistance usually results in devices with a relatively large die and a large input capacitance.
  • the input capacitance needs to be charged and discharged in nano-seconds. This means that as the frequency of operation increases the losses associated with the gate-drive circuitry become significant.
  • ZVS zero-voltage-switched
  • QRC quasi-resonant converter
  • the first two (2) prior art solutions do not embrace a level of efficiency where most of the charging and discharging energy is recovered.
  • the third solution is better suited for switching frequencies in the megahertz range because of its basic operation thus limiting its use in synchronous rectifier circuits. What is needed is a resonant gate drive for an externally-driven synchronous rectification circuit which does not lose large amounts of circulating energy and which can be efficiently used with switching frequencies outside the megahertz range.
  • This present invention is a new gate drive configuration that can be used in applications where an external driving circuit is needed to drive the synchronous rectifiers in non self-driven applications.
  • an energy recovery mechanism for an externally driven synchronous rectifier circuit having a primary transformer, first and second synchronous rectifiers, an output terminal, and an external driving circuit configured to provide the timing signals for driving said first and second synchronous rectifiers.
  • the energy recovery mechanism comprises first and second resonant inductors each having first and second terminals.
  • Corresponding first and second recovery switches are coupled to the first terminals of the first and second resonant inductors.
  • a first set of diodes is arranged to direct current into the second terminal of the first resonant inductor and a second set of diodes arranged to direct current into the second terminal of the second resonant inductor.
  • the first and second recovery switches are further coupled to the external driving circuit for causing current to enter the first and second resonant inductors for recovering energy used in charging and discharging the input capacitance associated with the first and second synchronous rectifiers.
  • the synchronous rectifier circuit comprises a primary transformer having a primary and secondary winding with the secondary winding having a first terminal and a second terminal.
  • a first synchronous rectifier is operably coupled to the first terminal of the secondary winding and a second synchronous rectifier is operably coupled to the second terminal of the secondary winding.
  • An external drive circuit is used and operably coupled to the first and second synchronous rectifiers to provide the drive timing for the first and second synchronous rectifiers.
  • An energy recovery circuit is coupled to the first and second synchronous rectifiers and configured for storing energy associated with charging and discharging their input capacitance.
  • An output voltage terminal is coupled to said energy recovery circuit for receiving rectified voltage waveforms.
  • the energy recovery circuit for each rectifier includes an additional resistor coupled to the first synchronous rectifier diode of the recovery circuit.
  • the resistor ensures that the energy recovery circuit will operate correctly in situations where current flows back through the first synchronous diode thus re-charging the input capacitance of the synchronous rectifiers which will turn back on at an incorrect time.
  • the voltage across the gate of the synchronous rectifiers is allowed to swing below zero to account for the back current.
  • the circuit for energy recovery will utilize N-type MOSFETS to limit the voltage across the synchronous rectifiers to a different value than that of the input voltage of the synchronous rectifiers.
  • the circuit for energy recovery will utilize an auxiliary winding to charge the gate capacitance of the synchronous rectifiers in a manner where the energy to charge the gate capacitance is recovered.
  • the auxiliary winding will facilitate the correct charging pulse for the synchronous rectifiers.
  • the method includes the steps of capturing energy from the input capacitance of the synchronous rectifiers in at least one inductor and transferring the energy from the storage inductors to the output when the recovery switches turn off.
  • the method also includes the step of recovering the energy needed for charging and discharging the synchronous rectifiers.
  • a technical advantage of the invention is the use of a resonant gate drive utilizing an externally driven synchronous rectification scheme.
  • Still another advantage is the achievement of a loss-less drive that can be used with both full-wave and half-wave rectifier configurations.
  • FIG. 1 illustrates a prior art hard-switched full-bridge converter with externally driven synchronous rectification
  • FIG. 2A illustrates a full wave rectifier with externally driven synchronous rectification utilizing an embodiment of the present invention
  • FIG. 2B shows voltage waveforms of the externally driven synchronous rectifier for a push-pull topology
  • FIG. 3 shows an embodiment of the present externally-driven synchronous rectifier having diode reverse recovery limiting resistors
  • FIG. 4 shows an embodiment of the present externally-driven synchronous rectifier when the two resonant networks are merged
  • FIG. 5 is another embodiment of the present invention with voltage limiting MOSFETs
  • FIG. 6A is yet another embodiment of the present invention with an auxiliary output inductor winding
  • FIG. 6B shows typical waveforms representing the operation of the resonant gate drive shown in FIG. 6A;
  • FIG. 7A illustrates an alternative embodiment of the present invention having an auxiliary output inductor winding
  • FIG. 7B illustrates another alternative embodiment of the present invention having an auxiliary output inductor winding
  • FIG. 8 is an implementation for a typical half-wave rectifier utilizing the present invention.
  • FIG. 9A is an implementation for a buck type converter utilizing the present invention.
  • FIG. 9B is another implementation for a buck type converter utilizing the present invention.
  • FIG. 1 shows a prior art externally-driven synchronous rectifier circuit for a hard-switched full-bridge converter, generally labeled 10 .
  • the synchronous rectifier circuit 10 includes a set of synchronous rectifiers SQ 1 and SQ 2 , primary transformer Tx having a primary winding 11 and secondary winding 12 , respectively, output inductor Lo, and output capacitor Co, and an external drive circuit 16 .
  • SQ 1 and SQ 2 are coupled to the secondary winding 12 of the transformer Tx.
  • Synchronous rectifiers SQ 1 and SQ 2 are also coupled to transformer Tsx of external drive circuit to derive the necessary timing signals that provide the turn-on and turn-off signals for the synchronous rectifiers SQ 1 and SQ 2 .
  • the power loss associated with charging and discharging the input capacitance of each of the synchronous rectifiers SQ 1 and SQ 2 is greater than or equal to fs•C iss — eq •Vgs 2 where fs is the frequency of operation, C iss — eq is the equivalent input capacitance of the synchronous rectifiers SQ 1 and SQ 2 , and Vgs is the voltage to which the input capacitance is charged.
  • the energy loss associated with the charging and discharging C iss — eq is not recovered, meaning the rectification circuit 10 , as a whole, is inefficient.
  • a means for recovering the energy associated with charging and discharging the input capacitance C iss — eq of the first and second synchronous rectifiers SQ 1 and SQ 2 .
  • FIG. 2A shows a synchronous rectifier circuit 18 with an energy recovery circuit 20 , according to the present invention.
  • the energy recovery circuit 20 can be used to recover the energy stored in the equivalent capacitance C iss — eq of the synchronous rectifiers SQ 1 and SQ 2 upon discharging.
  • the energy recovery circuit 20 comprises two resonant inductors LR 1 and LR 2 and four diodes D 1 , D 2 , D 3 , and D 4 .
  • Resonant inductors LR 1 and LR 2 and diodes D 1 , D 2 , D 3 , and D 4 are used to store the energy resulting from discharging the first and second synchronous rectifiers SQ 1 and SQ 2 .
  • the resonant inductors LR 1 ad LR 2 are coupled to the recovery switches SQ 3 and SQ 5 .
  • the recovery switches SQ 3 and SQ 5 are, in turn, coupled to the output terminal Vout. Any drive cross conduction energy and all of the energy stored in the resonant inductors LR 1 and LR 2 are transferred to the recovery switches SQ 3 and SQ 4 and then to the output terminal Vout, thus providing a more energy efficient circuit 18 .
  • the energy required to charge the input capacitance C iss — eq of the synchronous rectifiers SQ 1 and SQ 2 is recovered.
  • FIG. 2B shows the basic waveforms representing the operation of the synchronous rectifier circuit 18 for recovering the energy from discharging first synchronous rectifier SQ 1 .
  • both synchronous rectifiers are on and the load current freewheels through the shorted secondary winding 12 and the synchronous rectifiers SQ 1 and SQ 2 .
  • the signal coming from the primary winding 11 turns on recovery switch SQ 3 . Since switch SQ 4 is still on, current builds through resonant inductor LR 1 .
  • switch SQ 4 turns off and the current through LR 1 starts discharging the input capacitance of synchronous rectifier SQ 1 .
  • inductor LR 1 discharges the input capacitance C iss — eq of the synchronous rectifier SQ 1 in a resonant manner.
  • Switch SQ 3 transfers this energy to the output terminal Vout. This resonance drives the voltage across the gate of first synchronous rectifier SQ 1 below ground as the resonant inductor LR 1 resets. Diode D 1 is provided to prevent this voltage from swinging negative.
  • the resonant inductor LR 1 has been reset and diode D 2 disconnects the resonant inductor LR 1 from the first synchronous rectifier SQ 1 . Since both recovery switch SQ 3 and switch SQ 4 are driven from the same signal, the delay between the turn-on of recovery switch SQ 3 and the turn-off of switch SQ 4 is controlled by the value of resistor R 1 and the input capacitance of switch SQ 4 .
  • the operation of recovery switch SQ 5 and resonant inductor LR 2 operate in the same manner, as described above, to recover the energy from discharging second synchronous rectifier SQ 2 .
  • a saturable inductor can be used in place of resonant inductors LR 1 and LR 2 , or resistors R 3 and R 4 can be placed in series with diodes D 1 and D 3 , respectively, within the energy recovery circuit 20 as shown in FIG. 3 .
  • resistors R 3 and R 4 allows the voltage across the synchronous rectifiers SQ 1 and SQ 2 to swing below ground. Therefore, the input capacitance C iss — eq of synchronous rectifiers SQ 1 and SQ 2 is recharged. Due to the effects of reverse recovery on diodes D 2 and D 3 , the voltage across the synchronous rectifiers SQ 1 and SQ 2 will remain below ground. This will guarantee the correct operation of the energy recovery circuit 20 for synchronous rectifier circuit 30 of FIG. 30 .
  • Vccs 2 has a lower value than Vccs to limit the charging voltage across the synchronous rectifiers SQ 1 and SQ 2 .
  • the totem-pole drivers SQ 4 and SQ 6 are now driven from a pulsating source provided by the auxiliary winding 50 in the output inductor Lo. It is this pulsating source that allows the gate capacitance of the synchronous rectifiers SQ 1 and SQ 2 to be charged in a loss-less manner.
  • the auxiliary winding 50 in the output inductor Lo has a high number of turns making it impractical.
  • the embodiments of the present invention shown in FIGS. 7A and 7B can be used. Specifically, in the synchronous rectifier circuit 70 , the auxiliary winding 50 is coupled to the positive side of the voltage terminal Vout as opposed to coupling of the auxiliary winding 50 to the return end of the voltage terminal Vout as shown in FIG. 6 A. This will allow a reduced number of turns for the auxiliary winding 50 .
  • the pulsating source voltage does not necessarily swing negative.
  • the auxiliary winding turns ratios are less than 1/(1-Vo*N/Vin), where N is the primary transformer turns ratio, the pulsating source voltage is always positive.
  • true loss-less charging of the input capacitance C iss — eq of the synchronous rectifiers SQ 1 and SQ 2 is not attained.
  • the losses associated with charging the input capacitance C iss — eq of synchronous rectifiers SQ 1 and SQ 2 are substantially reduced.
  • driving capability will be not lost during short circuit conditions.
  • FIG. 8 shows an embodiment for the resonant gate drive synchronous rectifier 85 for the half-wave rectifier.
  • a second auxiliary winding 52 has been added to facilitate the use of the present invention for a half-wave rectifier.
  • Both resonant networks can be combined and the auxiliary windings 50 and 52 can be referenced from different places in the synchronous rectifier circuit 85 as explained above.
  • the recovery of the discharged energy stored in the input capacitance C iss — eq of the main switch and synchronous rectifiers SQ 1 and SQ 2 for a buck type converter 90 (step down converter) not having an isolation stage can also be achieved as shown in FIG. 9 A.
  • the input capacitance C iss — eq of the synchronous rectifiers SQ 1 and SQ 2 can also be charged in a loss-less manner as shown by the synchronous rectifier circuit 100 of FIG. 9 B.
  • the novel method and system of the present resonant gate drive provides the advantage of efficiently recovering the energy from charging and discharging the synchronous rectifiers SQ 1 and SQ 2 .
  • Another advantage of the present invention is the ability recover large amounts of the circulating energy of the circuit.
  • Yet another advantage of the present invention is the adaptability of the present invention to be efficiently used with a broad range of switching frequencies.
  • a further advantage of the present invention is the ability to adapt the present invention to various types of converter topologies.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Rectifiers (AREA)
  • Power Conversion In General (AREA)
  • Centrifugal Separators (AREA)
  • Vehicle Body Suspensions (AREA)
  • Electrical Discharge Machining, Electrochemical Machining, And Combined Machining (AREA)
US09/414,247 1999-10-07 1999-10-07 Resonant gate drive for synchronous rectifiers Expired - Lifetime US6169683B1 (en)

Priority Applications (10)

Application Number Priority Date Filing Date Title
US09/414,247 US6169683B1 (en) 1999-10-07 1999-10-07 Resonant gate drive for synchronous rectifiers
CNB008167397A CN100492848C (zh) 1999-10-07 2000-10-02 能量回收电路和能量回收方法
PCT/US2000/027204 WO2001026209A1 (en) 1999-10-07 2000-10-02 Resonant gate drive for synchronous rectifiers
DE60007558T DE60007558T2 (de) 1999-10-07 2000-10-02 Resonante gatteransteuerung für sychrongleichrichter
EP00967262A EP1243065B1 (en) 1999-10-07 2000-10-02 Resonant gate drive for synchronous rectifiers
JP2001529063A JP4574930B2 (ja) 1999-10-07 2000-10-02 同期整流器のための共振ゲート駆動装置
AU77486/00A AU7748600A (en) 1999-10-07 2000-10-02 Resonant gate drive for synchronous rectifiers
AT00967262T ATE257290T1 (de) 1999-10-07 2000-10-02 Resonante gatteransteuerung für sychrongleichrichter
TW089120998A TW561678B (en) 1999-10-07 2000-10-07 Resonant gate drive for synchronous rectifiers
HK03106736.3A HK1054470B (zh) 1999-10-07 2003-09-19 能量回收電路和能量回收方法

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US09/414,247 US6169683B1 (en) 1999-10-07 1999-10-07 Resonant gate drive for synchronous rectifiers

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EP (1) EP1243065B1 (zh)
JP (1) JP4574930B2 (zh)
CN (1) CN100492848C (zh)
AT (1) ATE257290T1 (zh)
AU (1) AU7748600A (zh)
DE (1) DE60007558T2 (zh)
HK (1) HK1054470B (zh)
TW (1) TW561678B (zh)
WO (1) WO2001026209A1 (zh)

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US20020097588A1 (en) * 2001-01-25 2002-07-25 Texas Instruments Incorporated Active gate clamp circuit for self driven synchronous rectifiers
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US20030090918A1 (en) * 2001-11-05 2003-05-15 Krishna Shenai DC-DC converter with resonant gate drive
US20030090237A1 (en) * 2001-11-05 2003-05-15 Krishna Shenai Monolithic battery charging device
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US20060034108A1 (en) * 2004-08-11 2006-02-16 Smk Corporation Synchronous rectifying switching power source circuit
US20060170042A1 (en) * 2005-01-31 2006-08-03 Zhihua Yang Resonant gate drive circuits
US20060170043A1 (en) * 2005-01-31 2006-08-03 Yan-Fei Liu Resonant gate drive circuits
US7102898B2 (en) 2001-02-01 2006-09-05 Di/Dt, Inc. Isolated drive circuitry used in switch-mode power converters
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US20070085133A1 (en) * 2001-12-15 2007-04-19 Huettinger Elektronik Gmbh + Co. Kg High frequency excitation system
US20070109025A1 (en) * 2005-11-04 2007-05-17 Yan-Fei Liu Resonant gate drive circuit with centre-tapped transformer
US20070298731A1 (en) * 2006-06-23 2007-12-27 Alireza Zolfaghari Multi-band transformer for wireless transmitter
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US20090161390A1 (en) * 2007-11-15 2009-06-25 Ming-Ho Huang Synchronous Rectification Control Circuit Assembly
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CN100521492C (zh) * 2007-06-13 2009-07-29 艾默生网络能源有限公司 一种谐振变换器
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US8693214B2 (en) 2010-06-29 2014-04-08 Brusa Elektronik Ag Voltage converter
US8866332B2 (en) 2009-06-24 2014-10-21 Brusa Elektronik Ag Circuit arrangement for power distribution in a motor vehicle
US20170040903A1 (en) * 2013-11-12 2017-02-09 Futurewei Technologies, Inc. Gate Drive Apparatus for Resonant Converters
US10116224B1 (en) * 2017-06-14 2018-10-30 Northrop Grumman Systems Corporation Switching power converter circuit
CN111565498A (zh) * 2019-02-13 2020-08-21 益力半导体股份有限公司 线性驱动能量回收系统
US10754366B2 (en) 2018-06-06 2020-08-25 L3 Cincinnati Electronics Corporation Power switching circuits having a saturable inductor
US10777967B2 (en) * 2017-05-03 2020-09-15 Analog Modules, Inc. Pulsed laser diode drivers and methods

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HK1054470A1 (en) 2003-11-28
DE60007558T2 (de) 2004-11-25
AU7748600A (en) 2001-05-10
WO2001026209A1 (en) 2001-04-12
HK1054470B (zh) 2009-12-11
TW561678B (en) 2003-11-11
JP2003512000A (ja) 2003-03-25
EP1243065A1 (en) 2002-09-25
JP4574930B2 (ja) 2010-11-04
EP1243065B1 (en) 2004-01-02
CN1408140A (zh) 2003-04-02
CN100492848C (zh) 2009-05-27

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