US4626766A - Circuit arrangement for feeding electrical users - Google Patents

Circuit arrangement for feeding electrical users Download PDF

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Publication number
US4626766A
US4626766A US06/753,108 US75310885A US4626766A US 4626766 A US4626766 A US 4626766A US 75310885 A US75310885 A US 75310885A US 4626766 A US4626766 A US 4626766A
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Prior art keywords
switch
voltage
switch controller
circuit arrangement
input
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Expired - Fee Related
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US06/753,108
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English (en)
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Gerhard Musil
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Siemens AG
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Siemens AG
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/36—Means for starting or stopping converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S323/00—Electricity: power supply or regulation systems
    • Y10S323/901—Starting circuits

Definitions

  • the invention relates to a circuit arrangement for feeding electrical users from a remote feed apparatus by means of a DC series feed from at least one current source. At least one user is connectable to the remote feed circuit via a DC-DC converter at various locations of the remote feed circuit.
  • the DC-DC converter contains a switch controller for generating a DC voltage from constant current.
  • a switch element is positioned parallel to an input of the first switch controller.
  • a control circuit controls the DC-DC converter dependent on a DC voltage to be held at least approximately constant.
  • a diode is provided between the switch element and a capacitor connected parallel to an output of the switch controller. The diode is poled such that the diode is inhibited given a conductive switch element.
  • German No. OS 32 42 023 discloses a constant-current-fed converter which generates a constant, potential-separated voltage for a variable load in such fashion that a correspondingly controlled inductor converter converts a variably accepted voltage into a stabilized voltage.
  • the stabilized voltage is somewhat higher than the input voltage allocated to the maximum power.
  • the output voltage is generated in potential-separated manner from the stabilized voltage by an uncontrolled flow converter.
  • the known circuit arrangement When starting up, the known circuit arrangement first accepts a voltage which is roughly equal to the voltage the current-voltage converter outputs to the voltage converter. For covering overload cases, however, this could have been selected relatively high.
  • the control circuit controlling the DC-DC converter emits a pulse sequence during start-up operation.
  • the pulse sequence has a pulse-duty factor set such that a voltage at the input of the first switch controller is lower than a maximum possible value of the input voltage at a conclusion of the start-up operation.
  • the switch controller thus runs up with a duty factor cycle matched to the remote feed device and does not switch to its normal control mode until the voltage output from the switch controller to the DC voltage converter has built up.
  • the connection of the load circuit or of the load circuits can be delayed until after the run-up.
  • the advantage arises that the input voltage which results during the run-up operation can be selected in consideration of the requirements of the remote feed device. If required, the input voltage can even be significantly lower than the maximum input voltage appearing during normal operation when this is necessary on the basis of specific prescriptions for the remote feed system.
  • FIG. 1 is a diagram of an apparatus for the remote feed of electrical users by means of DC series feed
  • FIG. 2 is a diagram of a switch controller which converts an impressed DC into a constant voltage, and a device for generating auxiliary voltage;
  • FIG. 3 is a diagram of a switch controller according to FIG. 1 with further details of the device for generating auxiliary voltage;
  • FIG. 4 is a diagram of a detail from the circuit arrangement of FIG. 3 showing further details
  • FIG. 5 is a diagram of a switch controller comprising a relay contact at the input which also serves for the elimination of overcurrents;
  • FIG. 6 is a diagram of a further embodiment of the arrangement of FIG. 5.
  • FIG. 7 is a diagram of a switch controller whose switch element is additionally exploited for the elimination of overcurrents.
  • FIG. 1 shows a remotely fed system as a block circuit diagram.
  • the remote feeding device F emits a constant direct current i o .
  • the users V1, V2, . . . Vn to be remotely fed are best operated with constant voltage at their feed input.
  • the preceding switch controllers W1, W2, . . . , Wn convert the current i o impressed at their input into a constant voltage U V1 , U V2 , . . . U Vn for the user.
  • the circuit arrangement shown in FIG. 2 contains the switch controller SR, the voltage converter 8, and the device H for generating auxiliary voltage.
  • the switch controller is designed in known fashion as an inductive converter and can, however, also be executed in some other fashion. What is essential is that it is equipped with a switch in its shunt arm and this switch is opened and closed by a control circuit which can in turn be influenced from the outside. When the circuit arrangement has a tendency to initially accept a high input voltage, the described start-up behavior with a limited duty cycle is particularly advantageous.
  • the switch controller SR the capacitor 1 is parallel to the input and the capacitor 5 is parallel to the output.
  • the capacitors 1 and 5 and the switch element 3 are connected in unipolar fashion to one another.
  • the capacitors 1 and 5 are connected at the side facing away from this junction via a series connection of the inductor 2 and the diode 4, whereby the inductor 2 is at the input and the diode 4 is poled such that it is transmissive for currents from the input to the output.
  • the switch element 3 is in a shunt arm of the switch controller between the junction of the inductor 2 and diode 4 on the one hand and the junction of the capacitors 1 and 5 on the other hand.
  • the switch controller SR forms the actual current-voltage converter. This is composed of the inductor 2 and the semiconductor switch 3 which lie in series with one another directly in the remotely fed line train; the capacitor 1 which is small in comparison to the capacitor 5 at the output of the switch controller, is parallel thereto.
  • the semiconductor switch 3 is opened and closed by a pulse-width-modulated signal so that exactly as much energy from the remote feed circuit and from the energy stored in the inductor 2 and the input capacitor 1 is conducted via the diode 4 to the output capacitor 5, and so that the voltage remains constant at the output capacitor 5 as long as a specific, maximum load current which can at most be equal to the remote feed current I o at this location is not exceeded.
  • the control of the pulse-width-modulated signal occurs in the same manner as in known inductor converters.
  • the DC converter 8 following the switch controller can be designed in a simple fashion according to one of the known principles. It is preferably an unregulated flow converter with an isolation transformer. Its clock frequency is advantageously taken from the same oscillator 6 which also controls the switch controller.
  • the device can also follow rapid load fluctuations since the input capacitor 1 is relatively small and is therefore quickly re-charged to the new input voltage corresponding to the modified load case.
  • the voltage converter which is sluggish in comparison thereto based on its principle of operation, is not affected by the change in its operating mode.
  • This is generated in the further switch controller H.
  • it has the same function as the switch controller SR.
  • Switch means corresponding to one another are 9 and 1, 10 and 2, 11 and 3, 12 and 4, 13 and 5, 14 and 6 as well as 15 and 7.
  • the switch means of the switch controller H are dimensioned for the demands prevailing there, and are dimensioned according to the same principles as the switch controller SR.
  • the clock generator 6 is also employed for the switch controller H so that the clock generator 14 can be omitted.
  • the switch controller H generates a positive and a negative auxiliary voltage related to the potential of the terminals B1 and B2 directly connected to one another. Since the voltage U5 is greater than the voltage U4 and both voltages relate to the potential of the terminal connection B4, B5, the positive auxiliary voltage available is the voltage U5 - U4. The voltage U4 serves as a negative auxiliary voltage. Given standard dimensioning, U5 is thus greater than U4 by roughly the factor 5 to 10, this also meeting the demands which are usually raised. Given, for example, a remote feed current of 0.4 A, standard auxiliary voltages of about 10 . . . 20 V thus derive and the comparatively low output power of the auxiliary voltage source produces a voltage U4 of about 2V.
  • the voltage U5 first reaches the value at which the clock generator 14 and the control device 15 begin to operate.
  • the regulator 15 begins to operate and correspondingly drives the switch 11 with pulses such that it is periodically closed.
  • the voltage U4 which is initially about as great as the voltage U5, is reduced within a few milliseconds to its later value.
  • the positive auxiliary voltage U5 - U4 is then available for the switch controller SR and for the converter 8.
  • the reduced voltage U4 remains as a negative auxiliary voltage.
  • the auxiliary voltage begins very quickly in an advantageous way. This results since, after the turn-on, the capacitors 9 and 13 first charge and, following thereupon when the control of the switch controller H begins, the voltage at the capacitor 9, which has a relatively small capacitance, collapses. No transition states, which could damage sensitive power components, thus occur for the circuit arrangement.
  • a switch 16 is inserted at the input of the switch controller SR in the arrangement shown in FIG. 2.
  • the switch 3 can be wired such that it remains closed as long as the auxiliary voltage has not yet begun.
  • the switch 16 can be omitted.
  • the switch 16 which lies at the input of the switch controller SR is initially closed and is only opened when the auxiliary voltage is present. Given a slow run-up of the voltage lying between the points A1 and B4 as occurs under certain conditions due to poor dynamic properties of the remote feeding device F, or due to cable capacitances, it thus can be avoided that the switch controller SR picks up too much voltage in an uncontrolled fashion.
  • the switch 16 is preferably a normally closed contact of a relay whose winding is driven by the auxiliary voltage (U5 - U4).
  • the auxiliary voltage can also be generated in some fashion other than that described above. It can, for example, be derived from the input voltage U1 or from the output voltage U2 of the switch controller SR. In both instances, a resistor or Zener diode then preferably lies in series with the switch 16 in order to guarantee a certain minimum voltage for generating the auxiliary voltage. However, the module H generating the auxiliary voltage must then be fed with a voltage which fluctuates greatly when it runs-up itself, and when there are load fluctuations, this makes the realization of a stable auxiliary voltage source more difficult.
  • the integrated circuit SG 3524 J referenced 7b serves as clock generator 6 and regulator 7. It generates the clock and controls the switch controller SR with width-modulated control pulses.
  • the saw-tooth voltage output by this circuit is conducted to the comparator 19 which compares it to the voltage U5 reduced by the voltage drop at a Zener diode 20.
  • the pulses at the output of the comparator 19 control switching transistor 11 via the driver 17.
  • the stabilization acquired with this simple arrangement is adequate.
  • the additional components 3f . . . 3l around the control component 3b of the switch in the switch controller SR prevent the voltages in the auxiliary converter H which are initially negative in comparison to the potential of terminal B1, from establishing a negative voltage at the gate of the field effect transistor 3m and thus prevent the closing of this switch.
  • the resistor 3f between the gate and drain of the field effect transistor 3m of such high resistance that it only causes very low losses in the operating condition.
  • This type of generated auxiliary voltage can also be combined in an advantageous way with current-fed converters provided in some other fashion.
  • it is likewise applicable to power supply circuits for the auxiliary voltage required at the input side wherein a switch element is inserted into the feed circuit in combination with differently constituted switch means.
  • the switch 16 is open and/or the switch 3 is driven with pulses by the drive device. Since the voltage U2 is still too low at first, the regulation in and of itself would be the maximum possible input voltage U1.
  • the switch controller SR is preferably dimensioned such that an overload produced, for example, due to a malfunctioning user V can still be governed at least over a short duration. One need only count on one or a few such overload cases in a remote feed device having many users.
  • the switch controllers SR during a turn-on, occurring simultaneously for all circuit arrangements according to FIG. 1 in such a remote feed device, behave as they behave when handling overload situations, then the constant current source of the remote feed device must be correspondingly dimensioned. It is then over-dimensioned for practical operation or can perhaps not even be realized at all.
  • the regulated control module 7 is operated such that a pulse sequence having a fixed or at least limited pulse-duty factor is first output, and thus a voltage V 1on which is lower than the maximum possible input voltage U 1max after the conclusion of the start-up operation is established at the terminal pair A1, B1 during the overall start-up operation.
  • the switch controller SR and, under given conditions, the converter 8 are then initially operated with the power consumption allocated to the voltage V 1on and their capacitors charged.
  • a voltage discriminator informs the regulator 7 of this, the regulator 7 then being switched into its normal operating mode.
  • the regulation then initially reacts with a reduction of the input voltage U1, whereby the voltage U2 also drops.
  • the voltage U1 allocated to the output power is established. Instead of the voltage U2, the voltage U3 can be evaluated under given conditions.
  • the acquisition of the voltage U2 can occur in known fashion.
  • the same voltage divider 23, 24, 25 as serves for regulation in the operating situation, and the same reference voltage which is available at the terminal 16a of the drive device 7b, are preferably employed.
  • the drive of the switch 16 can also be provided with a time delay, or with a device which only responds when the auxiliary voltage has reached a certain minimum value required for the faultless operation of the modules to be driven.
  • a means can, in particular, be a Zener diode in series with resistor 16h in the FIG. 6 to be described below whose value approximately corresponds to the minimum required value of the auxiliary voltage.
  • a further advantageous development is that users are first entirely or partially disconnected, and the possible power consumption for the start-up of the switch controller is dimensioned according to the operating situation in which the lowest remote feed voltage is available per device. The user or users are then connected after the start-up operation. The initiation of this operation preferably occurs by means of the same apparatus which also recognizes the end of the start-up operation and switches to the normal operating mode.
  • FIG. 4 shows a detail from a circuit arrangement of FIG. 2.
  • the regulator 7b is an integrated drive circuit SG 3524 J, and contains an operational amplifier which has its negative input at the terminal 1a, has its positive input at the terminal 2a, and has its output at the terminal 9a.
  • the regulator 7b also contains a reference voltage source whose output is at the terminal 16a.
  • the voltage divider 36, 37 at 16a divides the reference voltage 5V to 2.5V, which in turn forms the rated value of the regulator in 7b and, on the other hand, is adjacent to the negative input of the comparator or discriminator 26 which has an open collector output.
  • the voltage divider 23+24 to 25 defines the actual value of A2, B4 which governs the control circuit in the module 7b.
  • the open collector of discriminator 26 is connected to B4.
  • the regulating amplifier in the circuit 7b encounters a stop which is formed by the voltage divider 33, 34, and 35 in cooperation with the base-emitter diode of 32 and with the diode 38.
  • the voltage divider 23 and 24 is effective in the start-up mode since the output of discriminator 26 shorts the resistor 25.
  • the value at this voltage divider is compared to a voltage of 2.5V.
  • the voltage A2, B4 has exceeded the rated value by a small prescribed amount, the 2.5 V is exceeded and the output of discriminator 26 becomes a high resistance.
  • the start-up is thus concluded.
  • the regulator in module 7b can now function freely, and via the voltage divider resistors 33, 34, and 35, the transistor 29 has been simultaneously switched in conjunction with a time constant formed by resistor 27 and capacitor 28.
  • the resistor chain 33, 34, and 35 simultaneously controls the transistor 32 and biases it into its conductive condition so that it then addresses the LED 30a in the opto-coupler 30 via the resistor 31.
  • this opto-coupler 30 disconnects the user V since its transistor 30b then shorts the base-emitter diode of the transistor 22.
  • the transistor 32 is inhibited by the transistor 29, which is now conductive, and the light-emitting diode 30a in the opto-coupler is no longer driven.
  • the transistor 30b thus becomes high in resistance, the transistor 22 becomes conductive via the current through the resistor 21, and the user V is supplied with current.
  • the connection of the user or of the users can also be indirectly or directly effected in some other fashion.
  • the disconnection of the user is started according to FIG. 4 by the arrangement which serves for switching from a limited pulse-duty factor for start-up to a freely regulated pulse-duty factor in the operating case.
  • This is particularly advantageous when the circuit arrangement is to operate in a plurality of different remote feed devices, or is to be operated with different users.
  • the start-up behavior can then be adapted to the operating case or turn-on case for which there are the most restrictions, i.e. for the remote feed system, the lowest voltage per circuit arrangement is made available to the circuit arrangement in the operating case, or during the start-up of the remote feed system.
  • the remote feed current is acquired with a sensor element.
  • the converter can be bridged during the time of the impermissible overcurrent by an additional current path which is driven from the sensor element, and which eliminates the overcurrent.
  • This current path is formed in a particularly simple way by the same devices which also short-circuit the switch controller SR functioning as a main converter during the start-up of the auxiliary voltage.
  • the switch 16 of FIG. 2 insures that the input of the switch controller SR is bridged during the time of an impermissibly high input current i o .
  • the switch 3 of the switch controller SR can also be advantageously employed for this purpose. Although it must be designed for overcurrent in this case, it need not switch this current with the clock frequency. This represents a considerable alleviation.
  • the switch 16 comprises a relay which has a normally closed contact 16k in order to guarantee the start-up behavior of the circuit arrangement.
  • the switch is opened by this voltage via the winding 16b.
  • a second winding in the line sequence of the terminals B1-A4, preceding the terminal A1 or following B4, is preferably provided for the relay 16. This closes the normally closed contact in the sense of a make contact.
  • This winding is shown in FIG. 5 between the terminal B1 and A4 and is referenced 16c.
  • the second winding is dimensioned such that the auxiliary voltage can hold the contact of the relay open given normal remote feed current.
  • a further advantageous possibility is to close the switch 3 given overcurrent.
  • the auxiliary converter H must continue to operate at least adequately in order to guarantee an active drive of the switch 3. That is usually possible given the usually comparatively low power output of the auxiliary converter H.
  • FIG. 7 shows a detail of a circuit arrangement wherein the switch 3 is used for eliminating the overcurrent.
  • the current is acquired here as a voltage drop at a 1 ohm resistor 38 in series with the power MOS field effect transistor forming the switch 3 and is conducted via a RC element 39, 40 to a transistor 41.
  • the transistor 41 is operated on the line sequence of the drive in such a fashion that the switching transistor 3m remains constantly conductive. Since only high overcurrents are to be acquired, it is of little significance whether the sensor element lies directly in the path of the remote feed current or in series with the switch 3 where the current flowing in the output circuit of the switch controller SR is not acquired.
  • the described techniques for bridging the switch controller SR during run-up of the auxiliary voltage and given overcurrent can also be combined, for example a relay 16 having a normally closed contact which is closed by the auxiliary voltage, and a second relay which has a make contact parallel to this normally closed contact and which is closed by a winding in the remote feed circuit given overcurrent.
  • the relay with its normally closed contact and its winding 16b and 16c from FIG. 5 can, under given conditions, be designed as an electronic relay or electronic circuit with or without a relay, and thereby also employ the switch 3.
  • the circuit arrangement can be fed in a remote feed system according to FIG. 1 in common with identical or different, further circuit arrangements.
  • the circuit arrangements W1 . . . Wn can be identically or differently designed and/or dimensioned.
  • the value of the resistor 3j is 1 M ohm.
  • a diode having a low leakage current is selected as diode 3i.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)
  • Direct Current Feeding And Distribution (AREA)
  • Details Of Television Systems (AREA)
  • Details Of Connecting Devices For Male And Female Coupling (AREA)
  • Selective Calling Equipment (AREA)
US06/753,108 1984-07-13 1985-07-09 Circuit arrangement for feeding electrical users Expired - Fee Related US4626766A (en)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3425905 1984-07-13
DE3425905 1984-07-13

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US4626766A true US4626766A (en) 1986-12-02

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US06/753,108 Expired - Fee Related US4626766A (en) 1984-07-13 1985-07-09 Circuit arrangement for feeding electrical users

Country Status (5)

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US (1) US4626766A (enrdf_load_stackoverflow)
EP (1) EP0169462B1 (enrdf_load_stackoverflow)
JP (1) JPS6154874A (enrdf_load_stackoverflow)
AT (1) ATE41569T1 (enrdf_load_stackoverflow)
DE (1) DE3568921D1 (enrdf_load_stackoverflow)

Cited By (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4962349A (en) * 1988-01-29 1990-10-09 U.S. Philips Corporation Battery operated power supply with low voltage start circuit
US5103147A (en) * 1988-07-14 1992-04-07 Bsg-Schalttechnik Gmbh & Co. Kg Operating device for consumers connected to the electric system of mobile units
US5375028A (en) * 1992-01-23 1994-12-20 Mitsubishi Denki Kabushiki Kaisha Overcurrent protective device and device for detecting overcurrent
US5394076A (en) * 1993-08-25 1995-02-28 Alliedsignal Inc. Pulse width modulated power supply operative over an extended input power range without output power dropout
US5847549A (en) * 1996-11-19 1998-12-08 Pairgain Technologies, Inc. Power converter stabilization loop
EP0837548A3 (en) * 1996-10-17 1999-12-29 Matsushita Electric Industrial Co., Ltd. Interleaved switching converter circuit and switching converter controlling method
US6060869A (en) * 1998-03-03 2000-05-09 Seiko Instruments Inc. Power supply circuit
US6329800B1 (en) * 2000-10-17 2001-12-11 Sigmatel Method and apparatus for reducing power consumption in driver circuits
US20020054764A1 (en) * 2000-11-06 2002-05-09 Asahi Seimitsu Kabushiki Kaisha Automatic aperture control circuit for automatic diaphragm lens of CCTV camera
US20030125844A1 (en) * 2000-03-20 2003-07-03 Christiane Foertsch Computer-assisted configuring tool
US6798177B1 (en) * 2002-10-15 2004-09-28 Arques Technology, Inc. Boost-buck cascade converter for pulsating loads
US20120194156A1 (en) * 2009-10-12 2012-08-02 Junhyeong Myoung Load driving signal-linked high voltage driving method and driving circuit thereof

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3865479D1 (de) * 1987-03-31 1991-11-21 Siemens Ag Schaltungsanordnung zur speisung mittels gleichstrom-reihenspeisung.
JP6635526B1 (ja) * 2018-11-08 2020-01-29 Ｎｅｃプラットフォームズ株式会社 給電システム、給電方法及びプログラム

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3160829A (en) * 1961-03-16 1964-12-08 Rca Corp Starting circuit for transistor converter
US4245285A (en) * 1979-08-31 1981-01-13 Burroughs Corporation Booster-inverter power supply circuit
DE3221404A1 (de) * 1982-06-05 1983-12-08 Philips Kommunikations Industrie AG, 8500 Nürnberg Stromversorgungsschaltung

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE3242023A1 (de) * 1982-11-12 1984-05-17 Siemens AG, 1000 Berlin und 8000 München Schaltungsanordnung zur speisung von elektrischen verbrauchern mit einer gleichspannung

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3160829A (en) * 1961-03-16 1964-12-08 Rca Corp Starting circuit for transistor converter
US4245285A (en) * 1979-08-31 1981-01-13 Burroughs Corporation Booster-inverter power supply circuit
DE3221404A1 (de) * 1982-06-05 1983-12-08 Philips Kommunikations Industrie AG, 8500 Nürnberg Stromversorgungsschaltung

Cited By (13)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4962349A (en) * 1988-01-29 1990-10-09 U.S. Philips Corporation Battery operated power supply with low voltage start circuit
US5103147A (en) * 1988-07-14 1992-04-07 Bsg-Schalttechnik Gmbh & Co. Kg Operating device for consumers connected to the electric system of mobile units
US5375028A (en) * 1992-01-23 1994-12-20 Mitsubishi Denki Kabushiki Kaisha Overcurrent protective device and device for detecting overcurrent
US5394076A (en) * 1993-08-25 1995-02-28 Alliedsignal Inc. Pulse width modulated power supply operative over an extended input power range without output power dropout
EP0837548A3 (en) * 1996-10-17 1999-12-29 Matsushita Electric Industrial Co., Ltd. Interleaved switching converter circuit and switching converter controlling method
US5847549A (en) * 1996-11-19 1998-12-08 Pairgain Technologies, Inc. Power converter stabilization loop
US6060869A (en) * 1998-03-03 2000-05-09 Seiko Instruments Inc. Power supply circuit
US20030125844A1 (en) * 2000-03-20 2003-07-03 Christiane Foertsch Computer-assisted configuring tool
US6845299B2 (en) * 2000-03-20 2005-01-18 Siemens Aktiengesellschaft Computer-assisted configuring tool
US6329800B1 (en) * 2000-10-17 2001-12-11 Sigmatel Method and apparatus for reducing power consumption in driver circuits
US20020054764A1 (en) * 2000-11-06 2002-05-09 Asahi Seimitsu Kabushiki Kaisha Automatic aperture control circuit for automatic diaphragm lens of CCTV camera
US6798177B1 (en) * 2002-10-15 2004-09-28 Arques Technology, Inc. Boost-buck cascade converter for pulsating loads
US20120194156A1 (en) * 2009-10-12 2012-08-02 Junhyeong Myoung Load driving signal-linked high voltage driving method and driving circuit thereof

Also Published As

Publication number Publication date
EP0169462A1 (de) 1986-01-29
JPH0250708B2 (enrdf_load_stackoverflow) 1990-11-05
JPS6154874A (ja) 1986-03-19
EP0169462B1 (de) 1989-03-15
ATE41569T1 (de) 1989-04-15
DE3568921D1 (en) 1989-04-20

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