US4464721A - Digitized pickoff system - Google Patents

Digitized pickoff system Download PDF

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Publication number
US4464721A
US4464721A US06/346,690 US34669082A US4464721A US 4464721 A US4464721 A US 4464721A US 34669082 A US34669082 A US 34669082A US 4464721 A US4464721 A US 4464721A
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Prior art keywords
pickoff
output
input
counter
data
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Joseph V. McKenna
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Kearfott Guidance and Navigation Corp
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Singer Co
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Assigned to SINGER COMPANY THE, A CORP. OF NJ. reassignment SINGER COMPANY THE, A CORP. OF NJ. ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: MC KENNA, JOSEPH V.
Priority to US06/346,690 priority Critical patent/US4464721A/en
Priority to IL67287A priority patent/IL67287A/xx
Priority to AU90662/82A priority patent/AU550181B2/en
Priority to CA000415737A priority patent/CA1189931A/en
Priority to FR8220316A priority patent/FR2521317B1/fr
Priority to NO824146A priority patent/NO155864C/no
Priority to JP58001816A priority patent/JPS58139009A/ja
Priority to GB08302685A priority patent/GB2114836B/en
Priority to IT8319435A priority patent/IT1207452B/it
Priority to SE8300618A priority patent/SE452205B/sv
Priority to DE19833304205 priority patent/DE3304205A1/de
Publication of US4464721A publication Critical patent/US4464721A/en
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Assigned to KEARFOTT GUIDANCE AND NAVIGATION CORPORATION reassignment KEARFOTT GUIDANCE AND NAVIGATION CORPORATION ASSIGNMENT OF ASSIGNORS INTEREST. Assignors: SINGER COMPANY, THE
Assigned to CONTINENTEL ILLINOIS NATIONAL BANK AND TRUST COMPANY OF CHICAGO, 231 SOUTH LASALLE STREET, CHICAGO, IL 60697 reassignment CONTINENTEL ILLINOIS NATIONAL BANK AND TRUST COMPANY OF CHICAGO, 231 SOUTH LASALLE STREET, CHICAGO, IL 60697 SECURITY INTEREST (SEE DOCUMENT FOR DETAILS). Assignors: KEARFOTT GUIDANCE & NAVIGATION CORPORATION
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    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01C—MEASURING DISTANCES, LEVELS OR BEARINGS; SURVEYING; NAVIGATION; GYROSCOPIC INSTRUMENTS; PHOTOGRAMMETRY OR VIDEOGRAMMETRY
    • G01C19/00—Gyroscopes; Turn-sensitive devices using vibrating masses; Turn-sensitive devices without moving masses; Measuring angular rate using gyroscopic effects
    • G01C19/02—Rotary gyroscopes
    • G01C19/04—Details
    • G01C19/28—Pick-offs, i.e. devices for taking-off an indication of the displacement of the rotor axis
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10T—TECHNICAL SUBJECTS COVERED BY FORMER US CLASSIFICATION
    • Y10T74/00—Machine element or mechanism
    • Y10T74/12—Gyroscopes
    • Y10T74/1261—Gyroscopes with pick off
    • Y10T74/1275—Electrical

Definitions

  • the present invention relates to a pickoff system for use with an inertial navigation assembly and particularly to a digitized pickoff system having a relaxation oscillator for use with an inertial sensor of an inertial navigation assembly.
  • the digitized pickoff system is intended to generate a digitized error signal from the pickoff elements of conventional inertial sensors, i.e., gyroscopes and accelerometers.
  • the digital error may then be introduced to microcomputer circuitry wherein capture loop stabilization is effected.
  • the conventional inertial sensors are equipped with either variable inductance or variable capacitance error pickoffs, composed of two diametrically opposed elements. Displacement error of the sensor causes air gap variations which increase the reactance of one element and reduce that of its companion element.
  • the prior art pickoff system by which pickoff error signal is generated, relies on connections of pickoff elements in series and exciting each end of the combination with a different polarity of balanced carrier signals referred to ground. An error signal, relative to ground, then appears at the junction of the pickoff elements. This signal is normally introduced to a carrier amplifier, then to a demodulator, excited by a carrier reference, whose output is the analog of displacement error in the sensor.
  • the prior art pickoff system includes capture loops for these sensors, which require the inclusion of the above circuitry and the use of an analog to digital converter between the analog error and the digital processor input.
  • the primary disadvantage of the prior art pickoff system is the extent of circuitry required, i.e., a reference excitation source, an excitation transformer, a preamplifier, a demodulator and a standard analog to digital converter.
  • a second disadvantage of the prior art pickoff system is the sensitivity of digital output to offset of the demodulator and the analog to digital converter, compared to virtual insensitivity to amplifier offset voltage in the circuit in the invention.
  • the aforementioned extent of circuitry is minimized by using a relaxation oscillator connected to the pickoff elements, a data converter connected to the relaxation oscillator, and logic means connected to the data converter and having an output providing a digital representation of the pickoff displacement.
  • a digitized pickoff system for sensing relative displacement of two spaced pickoff elements comprising, a relaxation oscillator adapted to sequentially select a pickoff element and adapted to determine the oscillating frequency of the selected pickoff element, a data converter adapted to measure the period of the oscillating frequency of the selected pickoff element, and logic means for measuring the difference in periods and having a digital output for providing a digital representation of the period difference as the measure of the relative displacement of the two pickoff elements.
  • FIG. 1 is a block diagram of a digitized pickoff system according to the invention
  • FIG. 2 is a schematic drawing of a sensor circuit portion of the system of FIG. 1;
  • FIG. 3 is a block diagram of a control circuit portion of the system of FIG. 1;
  • FIG. 4A and FIG. 4B are schematic drawings of two parts of the control circuit portion of FIG. 3.
  • Digitized pickoff system 10 includes an inertial measurement unit 12, and a pickoff digitizing circuitry 14.
  • inertial measurement unit 12 includes a first gyro, or inertial sensor 16, and a second gyro, or inertial sensor 18.
  • First gyro 16 has a first pickoff assembly 20 and a second pickoff assembly 22.
  • Pickoff 20 has a first pickoff element 24 and a second pickoff element 26.
  • Pickoff 22 has a first element 28 and a second element 30.
  • Second gyro 18 has a first pickoff assembly 32 and a second pickoff assembly 34.
  • Pickoff 32 has a first element 36 and a second element 38.
  • Pickoff 34 has a first element 40 and a second element 42.
  • a prior art gyro, such as gyro 16 and gyro 18, is shown and described in U.S. Pat. No. 3,354,726 of inventors W. J. Krupick and R. Cimera, which is assigned to the same assignee as this invention.
  • pickoff digitizing circuitry 14 includes a sensor circuit 44, a control circuit 46, and a data link 48.
  • Sensor circuit 44 includes a high speed differential amplifier 50, a multiplexer 52, and a dual counter 54, which has a sensor channel counter section 56 and a sensor index counter section 58.
  • Sensor circuit 44 also includes an inverter assembly 60, a comparator 62, and a dual multivibrator unit 64, which has a first one-shot multivibrator 66 and a second one-shot multivibrator 68.
  • Sensor circuit 44 also includes a control flip-flop 70, an amplifier network 72, a multivibrator and comparator input network 74, a reference resistor network 76, and a trim resistor network 78.
  • a relaxation oscillator is formed by the assembly of the aforementioned amplifier 50, multiplexer 52, comparator 62, amplifier network 72, input network 74, and reference resistance network 76.
  • Logic means includes the assembly of the aforementioned sensor channel counter 56, index counter 58, inverter assembly 60, multivibrator 64 and control flip-flop 70.
  • Control circuit 46 includes a control period counter 80, a control channel counter 81, a gate generator 82, and a gated counter 83.
  • Circuit 46 also includes a clock oscillator 84, which is preferably a crystal controlled, temperature compensated oscillator, a transfer and reset control circuit 85, and a data processor 87.
  • a data converter is formed by the assembly of the aforementioned gate generator 82, gated counter 83 and clock oscillator 84.
  • An additional part of the logic means includes the assembly of the control period counter 80, control channel counter 81, transfer and reset control circuit 85 and data processor 87.
  • control period counter 80 includes shift register A4, gate A15B and ripple counter A9A.
  • Control channel counter 81 includes the flip-flops of A1, gate A8B and ripple counter A9B.
  • Gate generator 82 includes the flip-flops of A10.
  • Gated counter 83 includes gate A15D, and ripple counters A14, A13A, A13B and A12A.
  • High frequency clock oscillator includes A20.
  • Transfer and reset control circuit 85 includes flip-flops of A2, gate A8D and shift register A7.
  • Data processor includes ripple counter A19, output data shift registers A17 and A18, timing and control flip-flops of A16, A22, A24, A25, the 64 bit shift registers of A29, A30, the quad 1 of 2 selector A28, and adder/subtractor A27.
  • Each of the above A-number parts has respective pins, marked 1, 2, 3, etc., as shown in FIG. 4A and FIG. 4B. It is noted that a cut line at the bottom edge of FIG. 4A corresponds to a cut line at the top edge of FIG. 4B; so that five leads only are cut along such common cut line.
  • the pickoff circuit 14, which is constructed to supply N channels of data comprises sensor circuit 44 and control circuit 46, as shown in FIG. 1.
  • Sensor circuit 44 comprises:
  • Index counter 58 which is advanced by a pulse from the control circuit 46 on the data link 48 and delivers an advance pulse to the channel counter 56.
  • channel counter 56 which advances one count after each output pulse from the index counter 58, and which has 2N binary stages and the output of which supplies the selector code to the multiplexer 52.
  • Control circuit 46 comprises (a) a period counter 80, which is indexed by each pulse on the data link and arranged to select a predetermined number of oscillator periods for measurement; (b) a channel counter 81, indexed by an output of the period counter, and used to generate a pulse on the data link following each channel measurement, and a double pulse following each complete sequence of channel measurements; (c) a gate generator 82, which accepts data link pulses and an output from the period counter, and generates a timing gate at its output; (d) a gated counter 83, which counts pulses during the timing gate, said pulses derived from (e) a high frequency clock oscillator 84; (f) a transfer and reset control circuit 85, which, at the end of each timing gate, first provides a transfer pulse to effect a transfer of data from the gated counter and then a reset pulse to reset the gated counter; (g) a data processor 87, which accepts digital data from the gated counter upon reception of the
  • amplifier 50 of sensor circuit 44 includes an inverting input lead 86, a non-inverting input lead 88, and an output lead 90.
  • Multiplexer 52 includes a positive supply lead 92, a negative supply lead 94, first ground lead 96, a second ground lead 98, a first selector code lead 100, a second selector code lead 102, a third selector code lead 104, a plurality of signal input leads 106, 108, 110, 112, 114, 116, 118, 120, and an output lead 121.
  • Channel counter 56 includes an input clock lead 122, output pins 124, 126, 128, which connect respectively to leads 100, 102, 104, and includes a reset lead 130.
  • Index counter 58 includes an input lead 132, output leads 134, 136, and a reset lead 138.
  • Inverter assembly 60 includes a first inverter 140, a second inverter 142, and a third inverter 144.
  • First inverter 140 has an input lead 146, and an output lead 148.
  • Second inverter 142 has an input lead 150, and an output lead 152.
  • the inputs 146 and 150 are connected in parallel.
  • the outputs 148 and 152 are also connected in parallel, to supply sufficient drive to the data link network (A8) 72.
  • Third inverter 144 has an input lead 154, and an output lead 156.
  • Input lead 154 receives the least significant bit (LSB) of period counter 58 on line 136.
  • the output on lead 156 which connects to clock lead 122, is pulled up to +5 V when in the logic one state.
  • the outputs 148 and 152 are pulled up to +5 V by resistor 158, and the output 156 is pulled up to +5 V by resistor 160.
  • Comparator 62 includes an inverting input lead 162, a non-inverting input lead 164, a true output lead 166, and a complementary output lead 168.
  • First multivibrator 66 includes, a clock input lead 170, a positive output Q lead 172, a negative output Q lead 174, and a timing control input lead 176.
  • Second multivibrator 68 includes, a clock input lead 178, a negative output Q lead 180, and a timing control input lead 182.
  • Control flip-flop 70 which is a J-K type of flip-flop includes a J input lead 184, which is connected to ground, a K input lead 186, which is connected to +5 V, a clock input lead 188, a Q output lead 190, and a preset input lead 192.
  • Amplifier network 72 includes a first pullup resistor 194 and a second pullup resistor 196, which effect the pullup to +5 V of output leads 166 and 168 of the comparator 62.
  • Network 72 also includes a third resistor 198, a fourth resistor 200, a fifth resistor 202, and a sixth resistor 204. Resistors 198, 200, 202, and 204 are arranged so that amplifier 50 supplies an inverted amplification of the true output of comparator 62.
  • input network 74 includes a resistor 206 and a capacitor 208, which control the width of the output pulse of multivibrator 66.
  • Network 74 also includes a resistor 210 and a capacitor 212, which control the width of the output pulse of multivibrator 68.
  • Network 74 also includes a first resistor 214 and a second resistor 216, which form a divider of the output signal of amplifier 50, for introduction to the non-inverting input lead 164 of the comparator 62.
  • Network 74 also includes a capacitor 218, which is disposed in parallel with second resistor 216, in order to provide high frequency filtering.
  • Network 74 also has a capacitor 220, which is employed as a high frequency filter for the multiplexer output 121, which is also connected as the non-inverting input lead 164 of comparator 62.
  • Reference resistor network 76 includes eight high stability resistors 222, 224, 226, 228, 230, 232, 234, 236.
  • Trim resistor network 78 includes eight selected resistors 238, 240, 242, 246, 248, 250, 252 which are selected during a trimming operation, and includes eight shunt trim resistors 254, 256, 258, 260, 262, 264, 266, 268, which are also selected during the trimming operation.
  • the trim network 78 is arranged so that each pickoff element, for example element 24, is supplied current from the amplifier 50 output through the high stability resistor 222, the series trim resistor 238, and shunt trim resistor 254, across the combination of the previous two resistors 222 and 238.
  • the approach to pickoff digitizing of pickoff system 10 consists of independent sequential measurements of the inductances exhibited of the two diametrically opposed cores, for example 24, 26 of the standard pickoff, of gyro 20, and determination of gyro displacement error as proportional to the difference of these measurements.
  • Inductance measurement is accomplished by introduction of core impedance (primarily L) to an astable multivibrator 64, whose oscillating frequency is a direct function of R/L, where R is a highly stable resistor, for example 222, placed in series with the pickoff core 24.
  • the period of multivibrator oscillation (directly proportional to L) is measured by gating a high frequency clock into a counter (64 MegaHertz used in present circuitry).
  • a pickoff element with inductance L 1 is selected by the multiplexer and a digital measurement of the resultant oscillating period made. Then that pickoff's companion element with inductance L 2 is selected and a similar measurement made. The difference of these two digital measurements is then computed and becomes a measure of pickoff displacement.
  • the error sensed by the pickoff circuitry 14 is proportional to (L 1 -L 2 ) where L 1 and L 2 are the respective inductances of the opposing cores of a pickoff assembly.
  • the error sensed by the standard prior art, analog system is directly proportional to (L 1 -L 2 )/(L 1 +L 2 ). Since (L 1 +L 2 ) is virtually constant for small error angles, the present invention and analog systems produce essentially the same error response.
  • the pickoff circuitry 14, as shown in FIG. 1, is presently partitioned with sensor circuit 44 assumed to be on the platform connected by a data link 48 to the control circuit 46, which is remote from the platform on which gyros 16 and 18 are mounted.
  • the DC supply voltages ( ⁇ 10 to ⁇ 15 VDC) required by the sensor circuit 44 are presumed to be available on the platform. +5 VDC is also required.
  • the sensor circuit 44 schematic is presented in FIG. 2. It consists essentially of a free running multivibrator with multiplexed feedback paths from the 8 cores 24, 26, 28, 30, 36, 38, 40, 42, of a 4-axis system, a channel counter 56 which receives pulses from the control circuit 46 and controls multiplexer indexing, and the components of a data link 48 which carries the above pulses from the control circuit and also sends pulses to the control circuit 46 on the negative-going excursions of the multivibrator 64. Series and shunt trim capability of the resistances in series with the cores is provided for frequency adjustment and pickoff nulling. Very high speed components are used in the multivibrator 64 and data link 48 to minimize jitter and present sharp leading edges for high resolution period measurement in the control circuit 46.
  • the control circuit 46 schematic is presented in FIG. 3. It consists of:
  • a channel counter 81 which tracks the channel counter 56 of the sensor circuit 44 and originates a channel counter reset pulse sent to the sensor circuit 44 over the data link 48 to properly synchronize both counters.
  • a period counter 80 which determines the number of periods of the multivibrator oscillation which are to be counted for each core selection.
  • a gated counter 83 which counts the total time required for the number of periods of oscillation selected.
  • the gated counter includes a 16 bit output shift register A17, A18, to which gated counter output is parallel transferred and from which this data is serially shifted to memory shift registers in a data processor 87, as described hereinafter.
  • a 64 MegaHertz crystal oscillator 84 which serves as a clock for the gate counter and a reference from which various shift pulse trains are generated.
  • a data processor 87 which contains four 64 bit memory shift registers A29, A30, which serially store the gate counter outputs as they are generated and output this data in 64 bit strings following each interrogation pulse.
  • the data processor 87 includes a serial substractor A27 which accepts the 64 bit strings and effects subtraction of the most recent B core measurements from the most recent A core measurements and outputs a 64 bit error data word following each interrogation. (A pickoff consists of two diametrically opposed cores, A and B).
  • the data processor also includes a countdown chain providing frequencies from 64 MegaHertz to 250 KiloHertz and various sequencing control and shift pulse generating circuits.
  • control circuit 46 The essential purpose of the control circuit 46 is the measurement of the period of oscillation of the multivibrator as it "samples" each pickoff core.
  • the oscillation frequency is constrained at the high end by parasitic effects in the cores and at the low end by power considerations.
  • a reasonable middle ground, with gyroscopes used in prototype circuitry, is obtained with frequencies between 50 and 75 KiloHertz.
  • a pulse is generated in the control circuit 46 and transmitted via the data link 48 to the sensor circuit 44, which then advances its channel counter 56 and directs the multiplexer 52 to switch to the next core to be sampled.
  • the new core's oscillating period measurement cannot begin until the next crossover of the multivibrator output, and some time is also required to dump the gated counter data into its output shift register and reset the counter. Therefore, a "housekeeping" interval is employed and the next period measurement commences on the next negative-going excursion of the DAD multivibrator. This allows relatively slow transitions of the multiplexer and sufficient time for effects of "initial conditions" of the multivibrator to be cleared away.
  • Control circuit 46 has been designed to make measurements of one core of each pickoff per interrogation pulse. Measurements of the opposing cores of these pickoffs are made on alternate interrogation pulses.
  • a jumpering scheme permits selection of the number of multivibrator periods to be measured in each core sampling, i.e., 4, 8, 16 or 32. By adjustment of nominal multivibrator frequency, selection of clock reference frequency and this period selection a very wide range of error resolution is available.
  • sensor circuit 44 A detailed explanation of the operation of sensor circuit 44 is presented hereafter in paragraphs a through e.
  • FIG. 2 The schematic of the sensor circuit 44 is presented in FIG. 2.
  • the multivibrator's comparator is buffered by a wide band inverting amplifier 50. This buffering is needed to center output levels at zero volts and to supply enough current to drive all eight cores.
  • the data link connection is shown to the right of the schematic. Output pulses are applied to the link from the top two inverters of inverter assembly 60.
  • the data link receiver is a one-shot multivibrator 66 which generates positive and negative one microsecond pulses (positive on line 172, negative on line 174), for each negative-going excursion on the data link. It thus reacts to both "sent" and “received” pulses.
  • 68 a retriggerable six microsecond one shot is triggered on the falling edges of the positive pulses of 66. Whenever 68 is inactive, i.e., in its non-triggered state, it holds the index counter 58 in its reset state.
  • the multiplexer 52 has line 121 for its output.
  • Channel selection is determined by the input code on lines 100, 102, 104, supplied from the channel counter 56. This counter is incremented each time the first bit of the index counter 58 goes to the "1" state. This, it may be seen, requires a pulse from 66 while 68 is active, i.e., when two data link pulses occur within less than 7 microseconds of one another. A 1 microsecond negative pulse is "sent” over the data link 48 on each negative going swing of the multiplexer output (which normally will occur every 12 to 18 microseconds) via 62, 70, 60. Thus multiplexer indexing can only result when a "received" pulse from the control circuit 46 is interleaved with the "sent” pulses.
  • channel counter 56 will be reset whenever the second bit of the index counter 58 goes to the "1" state. This requires that a succession of 3 pulses appear on the data link 48 with a maximum pulse-to-pulse spacing of 7 microseconds.
  • the control circuit 46 is designed to send one 1 microsecond pulse up the data link 48 with 3.5 to 4.5 microseconds following that multiplexer transition which completes one core measurement interval, thus advancing the multiplexer 52 to the next core and setting up for the next core measurement interval. After 8 successive advancements of the multiplexer 52 (2 interrogation pulses) an additional one microsecond pulse, following the indexing pulse by 4 microseconds, is sent up to the sensor circuit 44 to reset its channel counter 56, thus guaranteeing a channel sequence lock.
  • control circuit 46 A detailed explanation of the operation of control circuit 46 is explained hereafter in paragraphs a through f.
  • control circuit 46 (a) The primary functions of the control circuit 46 are:
  • the control circuit 46 includes the circuitry necessary for the computation of displacement errors and generation of a serial 64 bit error "word" (16 bits per axis) for utilization by a digital processor (not shown) which, in reaction to displacement data, might generate digital commands to torquer amplifiers (not shown) involved in loop closure.
  • FIG. 4A and 4B The schematic of the control circuit 46 is presented in FIG. 4A and 4B.
  • a summary of the control sequence follows:
  • A25B is set for 1 microsecond, then reset.
  • This "START" pulse (appearing at A25B pin 2) commences sequences in the parts of the circuit shown in FIG. 4A, which performs the "data gathering” function, and sequences in the parts of the circuit shown in FIG. 4B, which perform the "data outputting" function. We will treat the data gathering section first.
  • the START pulse resets flip-flop A1A and A1B.
  • the A1A-Q output which becomes a logical "1" removes the direct set of flip-flops A10A and A10B.
  • the A1A-Q output via NAND gate A8A, removes the reset on null period counter A11A and applies direct reset to A10A, thus preparing A10B for resetting on the next negative pulse from the data link network (upper left corner of FIG. 4A).
  • Reset of A10B occurs as the DAD multivibrator output swings negative, thereby generating a negative pulse on the data link.
  • This pulse exhibits very rapid fall time and A10B is a fast acting flip-flop so that the timing gate at its Q output (pin 7) exhibits minimum jitter relative to the multivibrator's change of state.
  • This output enables NAND gate A15D, which gates the 64 MegaHertz clock into the 16 bit gate counter A14, A13 and A12A.
  • Each data link pulse resets delay timer A4, which is an 8 bit shift register clocked at 1 MegaHertz.
  • delay timer A4 is an 8 bit shift register clocked at 1 MegaHertz.
  • outputs at pins 11 and 13 immediately go to "0" but return to the "1" state nominally 6 and 8 microseconds, respectively, following the data link pulse.
  • counter A9A is indexed via A15B.
  • the number of multivibrator periods to be measured is selected by the jumper arrangement at the top of the page. For example, if 8 periods are desired, pin (14) is jumpered to pin (9), the former coming from the period counter A9A and the latter being the clock input to A10A.
  • A10A is set, preparing A10B to be set, and end that channel's measurement period, by the next data link pulse.
  • gate A15D is inhibited and gate counting stops.
  • the period counter A9A is reset and, via gate A8A, A10A is reset.
  • the channel counter A9B is incremented and flip-flop A2A is set.
  • Flip-flop A2B is set on the next negative excursion of the 1 MegaHertz clock and reset 1 microsecond later. While it is set information from the gate counter is loaded into the 16 bit shift register A18 and A17 via the connection to pins 1 of these devices ("load") from A2B-Q.
  • the A2B-Q signal is shifted into an 8 bit sequence control shift register A7 which is clocked at a 1 MegaHertz rate.
  • the outputs of this register are 1 microsecond positive pulses appearing at pins 6, 10 and 13 starting nominally 4, 5 and 8 microseconds, respectively, following the transfer of gate counter data to the 16 bit register.
  • the output pulse at pin 6 of A7 causes reset of the gate counter (positive pulse to A13A, A13B and A12A, negative pulse to A14 via gate A15C). This pulse is also directed to power NOR gates A3C and A3D to generate a data link pulse for the incrementing of the channel counter in the DAD sensor circuit and stepping of its multiplexer.
  • the NOR gate arrangement used is to provide the high current drive required on the 75 ohm data link line.
  • the pulse at pin 13 is applied to the data link via NOR gates A3A and A3D and serves to reset the channel counter 56 in the sensor circuit, thus providing a lock of the channel counters in both the sensor and control circuits and ensuring the sequence of data output following an interrogation pulse.
  • the START pulse at A25B-Q (pin 2) also resets flip-flop A24B which, in turn, removes the direct resetting of 8 bit counter A23, thereby enabling its indexing by the applied one MegaHertz clock.
  • flip-flop A24B is clocked to a set condition again, thereby reapplying direct reset to the counter. This process causes a train of 64 positive pulses at a 500 KiloHertz rate to be generated at the output (pin 3) of the first bit of the 8 bit counter.
  • the 5th bit of this counter goes to a "0" at the end of each 16th positive pulse of the 64 pulse train, and is utilized to set flip-flop A21A, which in turn applies a direct reset to flip-flop A22B.
  • the A22B-Q output (pin 8) is the "carry” input (pin 3) of adder A27.
  • the START pulse at A25B-Q also applies a direct reset to flip-flop A22A.
  • the output A22A-Q (pin 5) follows the form of the 64 pulse train generated at A23A pin 6 but lags by 1/2 microsecond, since it changes state on positive-going excursions of the one MegaHertz clock, whereas the pulse train changes state on the negative going excursions of the same clock.
  • This delayed clock is applied the carry flip-flop A22B, 64 bit shift registers A29A and A29B, and to either 64 bit shift register A30A or A30B, depending upon the state of selector A28.
  • the adder A27 is arranged to perform the subtraction process necessary for pickoff displacement measurement, wherein the differences of the counts accumulated in the gate counter for opposing core samples is representative of this displacement. If we denote one core of each pickoff as core A and the other as core B and let the numbers X and Y represent the gate counter outputs for these core samplings, the digitized displacement error is (X-Y).
  • selector A28 is placed in state 0 where the lower inputs to its 4 selectors appear on the selector outputs. This causes data generated while sampling pickoff elements 1A, 2A, 3A and 4A to shift (LSB first) into A30A, a 64 bit shift register, as it is outputted in 16 bit trains from the 16 bit shift register A17/A18.
  • selector A28 is placed in state 1 where the upper inputs to the selector appear as outputs, and the data in A30A is shifted into A29A, another 64 bit shift register, and into the "X" input (pin 8) of adder A27 in one continuous 64 bit train.
  • selector A28 returns to state 0 and the data in A29A is shifted into the "X" input of adder A27, also in a 64 bit train.
  • the "X" input of the adder receives "new” and “old” data from the A cores of the gyro pickoffs.
  • the "Y" input (pin 2) of the adder receives "old” and “new” data from the B cores of the gyro pickoffs. Since the carry input is set at the start of each 16 bits of data, i.e., at the start of each channel's data output, the adder performs the function (X+Y+1) or (X-Y).
  • the net sequence of output data for successive interrogation pulses is therefore (A NEW -B OLD ), (A OLD -B NEW ), (A NEW -B OLD ), etc.
  • data is shifted in 64 bit shift registers A29A, A29B, and A30A or A30b, as selected, entering the next data bit into adder A27.
  • the data shift and subsequent subtraction procedure may require up to 0.6 microseconds for stabilization, which still allows a minimum of 0.9 microseconds for data rise time in the serial data line and receiver set-up before the next "SP" pulse clocks this data into the receiver.
  • flip-flops A21B and A25A employed here were designed to permit self-interrogation at the end of each measurement sequence, as well as to permit external interrogation.
  • the output of A15-6 is connected to the "INT" input which is connected to A22B-12. This supplies an interrogation pulse 6 to 7 microseconds after the leading edge each data link pulse. If data shift from the 16 bit register A17/A18 is not taking place at this time, flip-flop A22B is reset and a clocking pulse is applied to flip-flop A25A. If, at this time flip-flop A1A is in the set condition, a "START" pulse will be generated and a measurement cycle will result.
  • a "START" is normally generated 6 to 7 microseconds after the first negative-going excursion of the DAD multivibrator output following completion of a four channel measurement cycle.
  • Data shift from the 16 bit shift register A17/A18 is complete 18.5 to 19.5 microseconds following the last negative going multivibrator excursion in a measurement cycle. During this interval the multivibrator will normally have gone through a subsequent negative-going excursion).
  • a new measurement cycle takes place every (4N+5) periods of the oscillating multivibrator, where N is the number of oscillation periods selected for measurement of a core's inductance.
  • the nominal interrogation interval would be (4.8+5) or 37 periods, i.e., 555 microseconds, generating an effective interrogation rate of 1802 Hertz.
  • pulses are applied to the "INT" terminal from an external source. Should the external source frequency exceed the nominal 1802 Hertz noted above, a "count down” will occur wherein conversion takes place only for each 2nd, 3rd, etc. pulse of the pulse source.
  • An alternate embodiment of the present invention for inertial devices with capacitive pickoffs can be provided by modifying the multivibrator parts as shown in FIG. 2, from a resistance-inductance (RL) type oscillator to a resistance-capacitance (RC) type oscillator.
  • RL resistance-inductance
  • RC resistance-capacitance

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  • Engineering & Computer Science (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Physics & Mathematics (AREA)
  • Arrangements For Transmission Of Measured Signals (AREA)
  • Navigation (AREA)
  • Measurement Of Length, Angles, Or The Like Using Electric Or Magnetic Means (AREA)
  • Optical Record Carriers And Manufacture Thereof (AREA)
  • Gyroscopes (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
  • Transmission And Conversion Of Sensor Element Output (AREA)
  • Cereal-Derived Products (AREA)
US06/346,690 1982-02-08 1982-02-08 Digitized pickoff system Expired - Lifetime US4464721A (en)

Priority Applications (11)

Application Number Priority Date Filing Date Title
US06/346,690 US4464721A (en) 1982-02-08 1982-02-08 Digitized pickoff system
IL67287A IL67287A (en) 1982-02-08 1982-11-17 Digitized pickoff system
AU90662/82A AU550181B2 (en) 1982-02-08 1982-11-17 Digitized pickoff system
CA000415737A CA1189931A (en) 1982-02-08 1982-11-17 Digitized pickoff system
FR8220316A FR2521317B1 (fr) 1982-02-08 1982-12-03 Systeme de capteurs d'informations mises sous forme numerique
NO824146A NO155864C (no) 1982-02-08 1982-12-09 Digitalisert giversystem.
JP58001816A JPS58139009A (ja) 1982-02-08 1983-01-11 デジタルピツクオフ装置
GB08302685A GB2114836B (en) 1982-02-08 1983-02-01 Digitised pickoff system
IT8319435A IT1207452B (it) 1982-02-08 1983-02-04 Sistema a rilevatori digitalizzato.
SE8300618A SE452205B (sv) 1982-02-08 1983-02-07 Digitaliserad avkennaranordning
DE19833304205 DE3304205A1 (de) 1982-02-08 1983-02-08 Digitalisiertes abgriffsystem

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
US06/346,690 US4464721A (en) 1982-02-08 1982-02-08 Digitized pickoff system

Publications (1)

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US4464721A true US4464721A (en) 1984-08-07

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US06/346,690 Expired - Lifetime US4464721A (en) 1982-02-08 1982-02-08 Digitized pickoff system

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US (1) US4464721A (it)
JP (1) JPS58139009A (it)
AU (1) AU550181B2 (it)
CA (1) CA1189931A (it)
DE (1) DE3304205A1 (it)
FR (1) FR2521317B1 (it)
GB (1) GB2114836B (it)
IL (1) IL67287A (it)
IT (1) IT1207452B (it)
NO (1) NO155864C (it)
SE (1) SE452205B (it)

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4634965A (en) * 1984-12-31 1987-01-06 Sundstrand Data Control, Inc. Charge balancing detection circuit
US5535142A (en) * 1992-07-22 1996-07-09 Mehnert; Walter Circuit arrangement for an inductive position indicator
US6275951B1 (en) * 1997-11-22 2001-08-14 Hyundai Electronics Industries Co., Ltd. Reset signal control circuit of a one-chip microcomputer
US6278914B1 (en) * 1999-08-26 2001-08-21 Bombardier Inc. Adaptive signal conditioning device for train tilting control systems

Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3707091A (en) * 1970-06-18 1972-12-26 Systron Donner Corp Dual pick-off electronic circuitry for linear servo accelerometer
US3782205A (en) * 1972-11-09 1974-01-01 Nasa Temperature compensated digital inertial sensor
US3797321A (en) * 1972-05-08 1974-03-19 Systron Donner Corp Pivot mechanism with electronic dither circuit
US3797320A (en) * 1972-11-29 1974-03-19 Systron Donner Corp Electronic dither circuit for a mechanical bearing assembly and method and accelerometer using the same
US3913406A (en) * 1973-08-02 1975-10-21 Us Army Digital pulse rebalance accelerometer
US4329884A (en) * 1980-10-14 1982-05-18 The Singer Company Signal processor for a resonator restrained gyro
US4386535A (en) * 1980-09-12 1983-06-07 The Singer Company Resonator restrained gyro
US4417234A (en) * 1981-12-03 1983-11-22 The Singer Company Multiplexed analog to digital converter having a feedback stabilized ramp

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3670585A (en) * 1970-04-17 1972-06-20 Northrop Corp Attitude readout for floated inertial platform

Patent Citations (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3707091A (en) * 1970-06-18 1972-12-26 Systron Donner Corp Dual pick-off electronic circuitry for linear servo accelerometer
US3797321A (en) * 1972-05-08 1974-03-19 Systron Donner Corp Pivot mechanism with electronic dither circuit
US3782205A (en) * 1972-11-09 1974-01-01 Nasa Temperature compensated digital inertial sensor
US3797320A (en) * 1972-11-29 1974-03-19 Systron Donner Corp Electronic dither circuit for a mechanical bearing assembly and method and accelerometer using the same
US3913406A (en) * 1973-08-02 1975-10-21 Us Army Digital pulse rebalance accelerometer
US4386535A (en) * 1980-09-12 1983-06-07 The Singer Company Resonator restrained gyro
US4329884A (en) * 1980-10-14 1982-05-18 The Singer Company Signal processor for a resonator restrained gyro
US4417234A (en) * 1981-12-03 1983-11-22 The Singer Company Multiplexed analog to digital converter having a feedback stabilized ramp

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4634965A (en) * 1984-12-31 1987-01-06 Sundstrand Data Control, Inc. Charge balancing detection circuit
US5535142A (en) * 1992-07-22 1996-07-09 Mehnert; Walter Circuit arrangement for an inductive position indicator
US6275951B1 (en) * 1997-11-22 2001-08-14 Hyundai Electronics Industries Co., Ltd. Reset signal control circuit of a one-chip microcomputer
US6278914B1 (en) * 1999-08-26 2001-08-21 Bombardier Inc. Adaptive signal conditioning device for train tilting control systems

Also Published As

Publication number Publication date
SE452205B (sv) 1987-11-16
NO155864B (no) 1987-03-02
IT1207452B (it) 1989-05-25
AU550181B2 (en) 1986-03-06
FR2521317A1 (fr) 1983-08-12
DE3304205A1 (de) 1983-08-18
IT8319435A0 (it) 1983-02-04
AU9066282A (en) 1983-08-18
GB2114836B (en) 1985-07-24
FR2521317B1 (fr) 1987-02-13
NO155864C (no) 1987-06-10
IL67287A (en) 1988-09-30
NO824146L (no) 1983-08-09
GB8302685D0 (en) 1983-03-02
CA1189931A (en) 1985-07-02
SE8300618L (sv) 1983-08-09
GB2114836A (en) 1983-08-24
SE8300618D0 (sv) 1983-02-07
JPS58139009A (ja) 1983-08-18

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